CS5253B-1 3.0 A LDO 5-Pin Adjustable Linear Regulator with Remote Sense Applications This new very low dropout linear regulator reduces total power dissipation in the application. To achieve very low dropout, the internal pass transistor is powered separately from the control circuitry. Furthermore, with the control and power inputs tied together, this device can be used in single supply configuration and still offer a better dropout voltage than conventional PNP–NPN based LDO regulators. In this mode the dropout is determined by the minimum control voltage. The CS5253B–1 is offered in a five–terminal D2PAK package, which allows for the implementation of a remote–sense pin permitting very accurate regulation of output voltage directly at the load, where it counts, rather than at the regulator. This remote sensing feature virtually eliminates output voltage variations due to load changes and resistive voltage drops. Typical load regulation measured at the sense pin is less than 1.0 mV for an output voltage of 2.5 V with a load step of 10 mA to 3.0 A. The CS5253B–1 has a very fast transient loop response which can be adjusted using a small capacitor on the Adjust pin. Internal protection circuitry provides for “bust–proof” operation, similar to three–terminal regulators. This circuitry, which includes overcurrent, short circuit, and overtemperature protection will self protect the regulator under all fault conditions. The CS5253B–1 is ideal for generating a 2.5 V supply to power graphics controllers used on VGA cards. Its remote sense and low value capacitance requirements make this a low cost, high performance solution. The CS5253B–1 is optimized from the CS5253–1 to allow a lower value of output capacitor to be used at the expense of a slower transient response. Features VOUT Range is 1.25 V to 5.0 V @ 3.0 A VPOWER Dropout < 0.40 V @ 3.0 A VCONTROL Dropout < 1.05 V @ 3.0 A 1.0% Trimmed Reference Fast Transient Response Remote Voltage Sensing Thermal Shutdown Current Limit Short Circuit Protection Drop–In Replacement for EZ1582 Backwards Compatible with 3–Pin Regulators Very Low Dropout Reduces Total Power Consumption • • • • • • • • • • • • Semiconductor Components Industries, LLC, 2001 April, 2001 – Rev. 2 http://onsemi.com Tab = VOUT Pin 1. VSENSE 2. Adjust 3. VOUT 4. VCONTROL 5. VPOWER 1 5 D2PAK 5–PIN DP SUFFIX CASE 936F MARKING DIAGRAM CS 5253B–1 AWLYWW 1 A WL, L YY, Y WW, W = Assembly Location = Wafer Lot = Year = Work Week ORDERING INFORMATION Device Package Shipping CS5253B–1GDP5 D2PAK* 50 Units/Rail CS5253B–1GDPR5 D2PAK* 750 Tape & Reel *5–Pin. 1 Publication Order Number: CS5253B–1/D CS5253B–1 5.0 V RDIS VOUT VCONTROL 2.5 V @ 3.0 A CS5253B–1 VPOWER VSENSE 3.3 V 124 Adjust 10 µF 10 V 100 µF 5.0 V 33 µF 5.0 V CLOAD (Optional) 124 GND GND RDIS Figure 1. Application Diagram MAXIMUM RATINGS* Rating Value Unit VPOWER Input Voltage 6.0 V VCONTROL Input Voltage 13 V 0 to 150 °C –65 to +150 °C 2.0 kV 230 peak °C Operating Junction Temperature Range, TJ Storage Temperature Range ESD Damage Threshold Lead Temperature Soldering: Reflow: (SMD styles only) (Note 1) 1. 60 second maximum above 183°C. *The maximum package power dissipation must be observed. ELECTRICAL CHARACTERISTICS (0°C ≤ TA ≤ 70°C; 0°C ≤ TJ ≤ 150°C; VSENSE = VOUT and VADJ = 0 V; unless otherwise specified.) Characteristic Test Conditions Min Typ Max Unit Reference Voltage VCONTROL = 2.75 V to 12 V, VPOWER = 2.05 V to 5.5 V, IOUT = 10 mA to 3.0 A 1.237 (–1.0%) 1.250 1.263 (+1.0%) V Line Regulation VCONTROL = 2.5 V to 12 V, VPOWER = 1.75 V to 5.5 V, IOUT = 10 mA – 0.02 0.2 % Load Regulation VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 10 mA to 3.0 A, with Remote Sense – 0.04 0.3 % Minimum Load Current (Note 2) VCONTROL = 5.0 V, VPOWER = 3.3 V, ∆VOUT = +1.0% – 5.0 10 mA Control Pin Current (Note 3) VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 100 mA VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 3.0 A – – 6.0 35 10 120 mA mA Adjust Pin Current VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 10 mA – 60 120 µA Current Limit VCONTROL = 2.75 V, VPOWER = 2.05 V, ∆VOUT = –4.0% 3.1 4.0 – A Short Circuit Current VCONTROL = 2.75 V, VPOWER = 2.05 V, VOUT = 0 V 2.0 3.5 – A Ripple Rejection (Note 4) VCONTROL = VPOWER = 3.25 V, VRIPPLE = 1.0 VP–P @ 120 Hz, IOUT = 3.0 A, CADJ = 0.1 µF 60 80 – dB CS5253B–1 2. The minimum load current is the minimum current required to maintain regulation. Normally the current in the resistor divider used to set the output voltage is selected to meet the minimum load current requirement. 3. The VCONTROL pin current is the drive current required for the output transistor. This current will track output current with roughly a 1:100 ratio. The minimum value is equal to the quiescent current of the device. 4. This parameter is guaranteed by design and is not 100% production tested. http://onsemi.com 2 CS5253B–1 ELECTRICAL CHARACTERISTICS (continued) (0°C ≤ TA ≤ 70°C; 0°C ≤ TJ ≤ 150°C; VSENSE = VOUT and VADJ = 0 V; unless otherwise specified.) Characteristic Test Conditions Min Typ Max Unit CS5253B–1 (continued) Thermal Regulation 30 ms Pulse, TA = 25°C – 0.002 – %/W VCONTROL Dropout Voltage (Minimum VCONTROL – VOUT) (Note 5) VPOWER = 2.05 V, IOUT = 100 mA VPOWER = 2.05 V, IOUT = 1.0 A VPOWER = 2.05 V, IOUT = 3.0 A – – – 0.90 1.00 1.05 1.15 1.15 1.30 V V V VPOWER Dropout Voltage (Minimum VPOWER – VOUT) (Note 5) VCONTROL = 2.75 V, IOUT = 100 mA VCONTROL = 2.75 V, IOUT = 1.0 A VCONTROL = 2.75 V, IOUT = 3.0 A – – – 0.05 0.15 0.40 0.15 0.25 0.60 V V V RMS Output Noise Freq = 10 Hz to 10 kHz, TA = 25°C – 0.003 – %VOUT Temperature Stability – 0.5 – – % Thermal Shutdown (Note 6) – 150 180 210 °C Thermal Shutdown Hysteresis – – 25 – °C VCONTROL Supply Only Output Current VCONTROL = 13 V, VPOWER Not Connected, VADJ = VOUT = VSENSE = 0 V – – 50 mA VPOWER Supply Only Output Current VPOWER = 6.0 V, VCONTROL Not Connected, VADJ = VOUT = VSENSE = 0 V – 0.1 1.0 mA 5. Dropout is defined as either the minimum control voltage (VCONTROL) or minimum power voltage (VPOWER) to output voltage differential required to maintain 1.0% regulation at a particular load current. 6. This parameter is guaranteed by design, but not parametrically tested in production. However, a 100% thermal shutdown functional test is performed on each part. PACKAGE PIN DESCRIPTION PACKAGE PIN # D2PAK PIN SYMBOL 1 VSENSE This Kelvin sense pin allows for remote sensing of the output voltage at the load for improved regulation. It is internally connected to the positive input of the voltage sensing error amplifier. 2 Adjust This pin is connected to the low side of the internally trimmed 1.0% bandgap reference voltage and carries a bias current of about 50 µA. A resistor divider from Adjust to VOUT and from Adjust to ground sets the output voltage. Also, transient response can be improved by adding a small bypass capacitor from this pin to ground. 3 VOUT This pin is connected to the emitter of the power pass transistor and provides a regulated voltage capable of sourcing 3.0 A of current. 4 VCONTROL 5 VPOWER FUNCTION This is the supply voltage for the regulator control circuitry. For the device to regulate, this voltage should be between 0.9 V and 1.3 V (depending on the output current) greater than the output voltage. The control pin current will be about 1.0% of the output current. This is the power input voltage. This pin is physically connected to the collector of the power pass transistor. For the device to regulate, this voltage should be between 0.1 V and 0.6 V greater than the output voltage depending on the output current. The output load current of 3.0 A is supplied through this pin. http://onsemi.com 3 CS5253B–1 VPOWER VCONTROL BIAS and TSD EA – + VREF IA + – VOUT VSENSE Adjust Figure 2. Block Diagram 0.12 1.252 0.10 Load Regulation (%) 1.253 1.251 1.250 1.249 1.248 1.247 TJ = 120°C 0.08 0.06 TJ = 20°C 0.04 TJ = 0°C 0.02 0 20 40 60 80 100 0 120 0 0.5 Junction Temperature (°C) 15 A/µs 1.5 2.0 2.5 3.0 Figure 4. Load Regulation vs Output Current 5.0 VCONTROL = 5.0 V VPOWER = 3.3 V VOUT = 2.5 V CCONTROL = 10 µF CADJ = 0.1 µF 1.0 Output Current (A) Figure 3. Reference Voltage vs Junction Temperature VOUT CS5253–1 COUT = 330 µF VOUT CS5253B–1 COUT = 33 µF Measured at ∆VOUT = –1.0% 4.5 4.0 Output Current (A) Reference Voltage (V) TYPICAL PERFORMANCE CHARACTERISTICS 3.5 3.0 2.5 2.0 1.5 1.0 80 A/µs ILOAD 10 mA to 3.0 A 0.5 0 0 1 2 3 4 5 VPOWER – VOUT (V) Figure 6. Output Current vs VPOWER – VOUT Figure 5. Transient Response Comparison between CS5253–1 and CS5253B–1 http://onsemi.com 4 6 CS5253B–1 85 Minimum Load Current (µA) 1200 IADJ (µA) 80 75 70 65 VPOWER = 3.3 V ∆VOUT = +1.0% 1150 1100 1050 1000 950 900 850 60 0 20 40 60 80 100 120 800 1.0 140 2.0 3.0 Junction Temperature (°C) VCONTROL = 5.0 V VPOWER = 3.3 V 8.0 9.0 10 11 Ripple Rejection (dB) 80 3.7 3.6 3.5 3.4 70 60 50 VIN – VOUT = 2.0 V IOUT = 3.0 A VRIPPLE = 1.0 VP–P COUT = 22 µF CADJ = 0.1 µF 40 30 20 0 20 40 60 80 100 120 10 101 140 102 103 104 105 106 Frequency (Hz) Junction Temperature (°C) Figure 9. Short Circuit Output Current vs Junction Temperature Figure 10. Ripple Rejection vs Frequency 1100 12 VCONTROL Dropout Voltage (mV) VCONTROL = 13 V VOUT = 0 V VPOWER Not Connected 10 8 IOUT (mA) 7.0 90 3.8 6 4 2 0 6.0 Figure 8. Minimum Load Current vs VCONTROL – VOUT 3.9 Short Circuit Output Current Limit (A) 5.0 VCONTROL – VOUT (V) Figure 7. Adjust Pin Current vs Junction Temperature 3.3 4.0 0 20 40 60 80 100 120 140 VPOWER = 2.05 V TJ = 0°C 1000 TJ = 20°C 900 TJ = 120°C 800 0 0.5 1.0 1.5 2.0 2.5 Output Current (A) Junction Temperature (°C) Figure 11. VCONTROL Only Output Current vs Junction Temperature Figure 12. VCONTROL Dropout Voltage vs Output Current http://onsemi.com 5 3.0 CS5253B–1 916.4 400 TJ = 120°C 350 300 TJ = 0°C 250 TJ = 20°C 200 150 50 0 VCONTROL = 5.0 V ∆VOUT = +1.0% 916.3 450 Minimum Load Current (µA) VPOWER Dropout Voltage (V) 500 916.2 916.1 916.0 915.9 915.8 915.7 915.6 915.5 0 0.5 1.0 1.5 2.0 2.5 3.0 915.4 0.5 1.5 2.5 VPOWER – VOUT (V) Output Current (A) Figure 13. VPOWER Dropout Voltage vs Output Current 4.5 Figure 14. Minimum Load Current vs VPOWER – VOUT 30 40 VPOWER = 6.0 V VOUT = 0 V VCONTROL Not Connected ICONTROL (mA) 25 20 IOUT (µA) 3.5 15 10 35 VCONTROL = 2.75 V VPOWER = 2.05 V 30 IOUT = 3.0 A 25 20 15 IOUT = 1.0 A 10 5 0 IOUT = 100 mA 5 0 20 40 80 60 100 120 0 140 0 20 Junction Temperature (°C) 60 80 100 120 140 Junction Temperature (°C) Figure 15. VPOWER Only Output Current vs Junction Temperature Figure 16. VCONTROL Supply Current vs Junction Temperature 5.0 6 VPOWER = 3.3 V VCONTROL = 5.0 V VOUT set for 2.5 V TA = 25°C VPOWER = 3.3 V VCONTROL = 5.0 V ILOAD = 0 to 3.0 A 5 VOUT = 2.5 V VOUT Shorted to VSENSE TJ = 0°C to 150°C 4 4.5 ESR (Ω) Current Limit (A) 40 Unstable 3 2 4.0 Stable Region 1 3.5 0 0.5 1.0 1.5 2.0 2.5 3.0 0 0 10 20 30 40 50 60 70 Capacitance (µF) VOUT (V) Figure 18. Stability vs ESR Figure 17. Current Limit vs VOUT http://onsemi.com 6 80 90 100 CS5253B–1 APPLICATIONS NOTES THEORY OF OPERATION Output Voltage Sensing The CS5253B–1 linear regulator provides adjustable voltages from 1.25 V to 5.0 V at currents up to 3.0 A. The regulator is protected against short circuits, and includes a thermal shutdown circuit with hysteresis. The output, which is current limited, consists of a PNP–NPN transistor pair and requires an output capacitor for stability. A detailed procedure for selecting this capacitor is included in the Stability Considerations section. The CS5253B–1 five terminal linear regulator includes a dedicated VSENSE function. This allows for true Kelvin sensing of the output voltage. This feature can virtually eliminate errors in the output voltage due to load regulation. Regulation will be optimized at the point where the sense pin is tied to the output. VPOWER Function Remote Sense DESIGN GUIDELINES Remote sense operation can be easily obtained with the CS5253B–1 but some care must be paid to the layout and positioning of the filter capacitors around the part. The ground side of the input capacitors on the +5.0 V and +3.3 V lines and the local VOUT–to–ground local output capacitor on the IC output must be tied close to the ground connected resistor voltage divider feedback network. The top resistor of the divider must be connected directly to the VSENSE pin of the regulator. This will establish the stability of the part. This capacitor–divider resistor connection may then be connected to ground remotely at the load, giving the ground portion remote sense operation. The VSENSE line can then be tied remotely at the load connection, giving the feedback remote sense operation. The remote sense lines should be Kelvin connected so as to eliminate the effect of load current voltage drop. An optional bypass capacitor may be used at the load to reduce the effect of load variations and spikes. The CS5253B–1 utilizes a two supply approach to maximize efficiency. The collector of the power device is brought out to the VPOWER pin to minimize internal power dissipation under high current loads. VCONTROL provides for the control circuitry and the drive for the output NPN transistor. VCONTROL should be at least 1.0 V greater than the output voltage. Special care has been taken to ensure that there are no supply sequencing problems. The output voltage will not turn on until both supplies are operating. If the control voltage comes up first, the output current will be limited to about three milliamperes until the power input voltage comes up. If the power input voltage comes up first, the output will not turn on at all until the control voltage comes up. The output can never come up unregulated. The CS5253B–1 can also be used as a single supply device with the control and power inputs tied together. In this mode, the dropout will be determined by the minimum control voltage. RDIS +5.0 V VCONTROL +3.3 V VPOWER VSENSE CS5253B–1 + 10 µF + +Load VOUT 124 + ADJ 100 µF 33 µF Remote Connections + Optional 124 Local Connections –Load GND RDIS Figure 19. Remote Sense http://onsemi.com 7 CS5253B–1 Adjustable Operation remain in dropout, and current is passed to the load until VOUT is in regulation. Further increase in the supply voltage brings the pass transistor out of dropout. In this manner, any output voltage less than 13 V may be regulated, provided the VPOWER to VOUT differential is less than 6.0 V. In the case where VCONTROL and VPOWER are shorted, there is no theoretical limit to the regulated voltage as long as the VPOWER to VOUT differential of 6.0 V is not exceeded. There is a possibility of damaging the IC when VPOWER – VOUT is greater than 6.0 V if a short circuit occurs. Short circuit conditions will result in the immediate operation of the pass transistor outside of its safe operating area. Overvoltage stresses will then cause destruction of the pass transistor before overcurrent or thermal shutdown circuitry can become active. Additional circuitry may be required to clamp the VPOWER to VOUT differential to less than 6.0 V if fail safe operation is required. One possible clamp circuit is illustrated in Figure 21; however, the design of clamp circuitry must be done on an application by application basis. Care must be taken to ensure the clamp actually protects the design. Components used in the clamp design must be able to withstand the short circuit condition indefinitely while protecting the IC. This LDO adjustable regulator has an output voltage range of 1.25 V to 5.0 V. An external resistor divider sets the output voltage as shown in Figure 20. The regulator’s voltage sensing error amplifier maintains a fixed 1.25 V reference between the output pin and the adjust pin. 5.0 V VCONTROL VOUT 2.5 V @ 3.0 A CS5253B–1 3.3 V VPOWER VSENSE Adjust R1 R2 Figure 20. Typical Application Schematic. The Resistor Divider Sets VOUT, With the Internal 1.260 V Reference Dropped Across R1. A resistor divider network R1 and R2 causes a fixed current to flow to ground. This current creates a voltage across R2 that adds to the 1.25 V across R1 and sets the overall output voltage. The adjust pin current (typically 50 µA) also flows through R2 and adds a small error that should be taken into account if precise adjustment of VOUT is necessary. The output voltage is set according to the formula: VOUT 1.25 V External Supply External Supply VCONTROL VSENSE CS5253B–1 VPOWER VOUT R1 R2 R2 IADJ R1 VADJ The term IADJ × R2 represents the error added by the adjust pin current. R1 is chosen so that the minimum load current is at least 10 mA. R1 and R2 should be of the same composition for best tracking over temperature. While not required, a bypass capacitor connected between the adjust pin and ground will improve transient response and ripple rejection. A 0.1 µF tantalum capacitor is recommended for “first cut” design. Value and type may be varied to optimize performance vs. price. Figure 21. This Circuit Is an Example of How the CS5253B–1 Can Be Short–Circuit Protected When Operating With VOUT > 6.0 V Stability Considerations Other Adjustable Operation Considerations The output compensation capacitor helps determine three main characteristics of a linear regulator: loop stability, start–up delay, and load transient response. Different capacitor types vary widely in tolerance, ESR (equivalent series resistance), ESL (equivalent series inductance), and variation over temperature. Tantalum and aluminum electrolytic capacitors work best, with electrolytic capacitors being less expensive in general, but varying more in capacitor value and ESR over temperature. The CS5253B–1 requires an output capacitor to guarantee loop stability. The Stability vs ESR graph in the typical performance section shows the minimum ESR needed to The CS5253B–1 linear regulator has an absolute maximum specification of 6.0 V for the voltage difference between VPOWER and VOUT. However, the IC may be used to regulate voltages in excess of 6.0 V. The two main considerations in such a design are the sequencing of power supplies and short circuit capability. Power supply sequencing should be such that the VCONTROL supply is brought up coincidentally with or before the VPOWER supply. This allows the IC to begin charging the output capacitor as soon as the VPOWER to VOUT differential is large enough that the pass transistor conducts. As VPOWER increases, the pass transistor will http://onsemi.com 8 CS5253B–1 guarantee stability, but under ideal conditions. These include: having VOUT connected to VSENSE directly at the IC pins; the compensation capacitor located right at the pins with a minimum lead length; the adjust feedback resistor divider ground, (bottom of R2 in Figure 20), connected right at the capacitor ground; and with power supply decoupling capacitors located close to the IC pins. The actual performance will vary greatly with board layout for each application. In particular, the use of the remote sensing feature will require a larger capacitor with less ESR. For most applications, a minimum of 33 µF tantalum or 150 µF aluminum electrolytic, with an ESR less than 1.0 Ω over temperature, is recommended. Larger capacitors and lower ESR will improve stability. The load transient response, during the time it takes the regulator to respond, is also determined by the output capacitor. For large changes in load current, the ESR of the output capacitor causes an immediate drop in output voltage given by: VCONTROL VOUT CS5253B–1 VPOWER VSENSE Adjust Figure 22. Diode Protection Circuit A rule of thumb useful in determining if a protection diode is required is to solve for current: ICV T V I ESR where: I is the current flow out of the load capacitance when VCONTROL is shorted, C is the value of load capacitance V is the output voltage, and T is the time duration required for VCONTROL to transition from high to being shorted. If the calculated current is greater than or equal to the typical short circuit current value provided in the specifications, serious thought should be given to the use of a protection diode. There is then an additional drop in output voltage given by: V I TC where T is the time for the regulation loop to begin to respond. The very fast transient response time of the CS5253B–1 allows the ESR effect to dominate. For microprocessor applications, it is customary to use an output capacitor network consisting of several tantalum and ceramic capacitors in parallel. This reduces the overall ESR and reduces the instantaneous output voltage drop under transient load conditions. The output capacitor network should be as close to the load as possible for the best transient response. Current Limit The internal current limit circuit limits the output current under excessive load conditions. Protection Diodes Short Circuit Protection When large external capacitors are used with a linear regulator, it is sometimes necessary to add protection diodes. If the input voltage of the regulator gets shorted, the output capacitor will discharge into the output of the regulator. The discharge current depends on the value of the capacitor, the output voltage, and the rate at which VCONTROL drops. In the CS5253B–1 regulator, the discharge path is through a large junction and protection diodes are not usually needed. If the regulator is used with large values of output capacitance and the input voltage is instantaneously shorted to ground, damage can occur. In this case, a diode connected as shown in Figure 22 is recommended. The device includes short circuit protection circuitry that clamps the output current at approximately 500 mA less than its current limit value. This provides for a current foldback function, which reduces power dissipation under a direct shorted load. Thermal Shutdown The thermal shutdown circuitry is guaranteed by design to activate above a die junction temperature of approximately 150°C and to shut down the regulator output. This circuitry has 25°C of typical hysteresis, thereby allowing the regulator to recover from a thermal fault automatically. http://onsemi.com 9 CS5253B–1 Calculating Power Dissipation and Heat Sink Requirements A heat sink effectively increases the surface area of the package to improve the flow of heat away from the IC and into the surrounding air. Each material in the heat flow path between the IC and the outside environment has a thermal resistance which is measured in degrees per watt. Like series electrical resistances, these thermal resistances are summed to determine the total thermal resistance between the die junction and the surrounding air, RΘJA. This total thermal resistance is comprised of three components. These resistive terms are measured from junction to case (RΘJC), case to heat sink (RΘCS), and heat sink to ambient air (RΘSA). The equation is: High power regulators such as the CS5253B–1 usually operate at high junction temperatures. Therefore, it is important to calculate the power dissipation and junction temperatures accurately to ensure that an adequate heat sink is used. Since the package tab is connected to VOUT on the CS5253B–1, electrical isolation may be required for some applications. Also, as with all high power packages, thermal compound in necessary to ensure proper heat flow. For added safety, this high current LDO includes an internal thermal shutdown circuit The thermal characteristics of an IC depend on the following four factors: junction temperature, ambient temperature, die power dissipation, and the thermal resistance from the die junction to ambient air. The maximum junction temperature can be determined by: RJA RJC RCS RSA The value for RQJC is 2.5°C/watt for the CS5253B–1 in the D2PAK package. For a high current regulator such as the CS5253B–1 the majority of heat is generated in the power transistor section. The value for RΘSA depends on the heat sink type, while the RΘCS depends on factors such as package type, heat sink interface (is an insulator and thermal grease used?), and the contact area between the heat sink and the package. Once these calculations are complete, the maximum permissible value of RΘJA can be calculated and the proper heat sink selected. For further discussion on heat sink selection, see our application note “Thermal Management for Linear Regulators,” document number SR006AN/D, available through the Literature Distribution Center or via our website at http://www.onsemi.com. TJ(max) TA(max) PD(max) RJA The maximum ambient temperature and the power dissipation are determined by the design while the maximum junction temperature and the thermal resistance depend on the manufacturer and the package type. The maximum power dissipation for a regulator is: PD(max) (VIN(max) VOUT(min))IOUT(max) VIN(max) IIN(max) http://onsemi.com 10 CS5253B–1 PACKAGE DIMENSIONS D2PAK 5–PIN DP SUFFIX CASE 936F–01 ISSUE O –T– SEATING PLANE B M NOTES: 1. DIMENSIONS AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: INCH. 3. TAB CONTOUR OPTIONAL WITHIN DIMENSIONS B AND M. 4. DIMENSIONS A AND B DO NOT INCLUDE MOLD FLASH OR GATE PROTRUSIONS. MOLD FLASH AND GATE PROTRUSIONS NOT TO EXCEED 0.025 (0.635) MAX. C E DIM A B C D E F G H J K M N A 1 2 3 4 5 K F G D H 5 PL 0.13 (0.005) M T B J M INCHES MIN MAX 0.326 0.336 0.396 0.406 0.170 0.180 0.026 0.035 0.045 0.055 0.090 0.110 0.067 BSC 0.098 0.108 0.018 0.025 0.204 0.214 0.055 0.066 0.000 0.004 N PACKAGE THERMAL DATA Parameter D2PAK, 5–Pin Unit RΘJC Typical 2.5 °C/W RΘJA Typical 10–50* °C/W *Depending on thermal properties of substrate. RΘJA = RΘJC + RΘCA. http://onsemi.com 11 MILLIMETERS MIN MAX 8.28 8.53 10.05 10.31 4.31 4.57 0.66 0.91 1.14 1.40 2.29 2.79 1.70 BSC 2.49 2.74 0.46 0.64 5.18 5.44 1.40 1.68 0.00 0.10 CS5253B–1 ON Semiconductor and are trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. 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PUBLICATION ORDERING INFORMATION Literature Fulfillment: Literature Distribution Center for ON Semiconductor P.O. Box 5163, Denver, Colorado 80217 USA Phone: 303–675–2175 or 800–344–3860 Toll Free USA/Canada Fax: 303–675–2176 or 800–344–3867 Toll Free USA/Canada Email: [email protected] JAPAN: ON Semiconductor, Japan Customer Focus Center 4–32–1 Nishi–Gotanda, Shinagawa–ku, Tokyo, Japan 141–0031 Phone: 81–3–5740–2700 Email: [email protected] ON Semiconductor Website: http://onsemi.com For additional information, please contact your local Sales Representative. N. American Technical Support: 800–282–9855 Toll Free USA/Canada http://onsemi.com 12 CS5253B–1/D