a FEATURES Pin-Programmable 2.5 V or 3.0 V Output Ultralow Drift: 3 ppm/C max High Accuracy: 2.5 V or 3.0 V 1 mV max Low Noise: 100 nV/√Hz Noise Reduction Capability Low Quiescent Current: 1 mA max Output Trim Capability Plug-In Upgrade for Present References Temperature Output Pin Series or Shunt Mode Operation (2.5 V, 3.0 V) 2.5 V/3.0 V High Precision Reference AD780 FUNCTIONAL BLOCK DIAGRAM +VIN NC 2 7 AD780 R10 R11 NC 1 The AD780 can be used to source or sink up to 10 mA and can be used in series or shunt mode, thus allowing positive or negative output voltages without external components. This makes it suitable for virtually any high performance reference application. Unlike some competing references, the AD780 has no “region of possible instability.” The part is stable under all load conditions when a 1 µF bypass capacitor is used on the supply. 5 TRIM Q7 R5 The AD780 is an ultrahigh precision bandgap reference voltage which provides a 2.5 V or 3.0 V output from inputs between 4.0 V and 36 V. Low initial error and temperature drift combined with low output noise and the ability to drive any value of capacitance make the AD780 the ideal choice for enhancing the performance of high resolution ADCs and DACs and for any general purpose precision reference application. A unique low headroom design facilitates a 3.0 V output from a 5.0 V ± 10% input, providing a 20% boost to the dynamic range of an ADC, over performance with existing 2.5 V references. VOUT R13 Q6 PRODUCT DESCRIPTION 6 TEMP R16 R14 3 R15 R4 4 GND NC = NO CONNECT 8 O/P SELECT 2.5V - NC 3.0V - GND PRODUCT HIGHLIGHTS 1. The AD780 provides a pin-programmable 2.5 V or 3.0 V output from a 4 V to 36 V input. 2. Laser trimming of both initial accuracy and temperature coefficients results in low errors over temperature without the use of external components. The AD780BN has a maximum variation of 0.9 mV from –40°C to +85°C. 3. For applications requiring even higher accuracy, an optional fine-trim connection is provided. A temperature output pin is provided on the AD780. This provides an output voltage that varies linearly with temperature, allowing the AD780 to be configured as a temperature transducer while providing a stable 2.5 V or 3.0 V output. 4. The AD780 noise is extremely low, typically 4 µV p-p from 0.1 Hz to 10 Hz and a wideband spectral noise density of typically 100 nV/√Hz. This can be further reduced if desired, by simply using two external capacitors. The AD780 is a pin-compatible performance upgrade for the LT1019(A)–2.5 and the AD680. The latter is targeted toward low power applications. 5. The temperature output pin enables the AD780 to be configured as a temperature transducer while providing a stable output reference voltage. The AD780 is available in three grades in plastic DIP, SOIC, and cerdip packages. The AD780AN, AD780AR, AD780BN, AD780BR, and AD780CR are specified for operation from –40°C to +85°C. REV. B Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781/329-4700 World Wide Web Site: http://www.analog.com Fax: 781/326-8703 © Analog Devices, Inc., 2000 AD780–SPECIFICATIONS (T = +25C, V A IN = +5 V unless otherwise noted) AD780AN/AR Parameter Min OUTPUT VOLTAGE 2.5 V Out 3.0 V Out 2.495 2.995 Typ OUTPUT VOLTAGE DRIFT1 –40°C to +85°C –55°C to +125°C LINE REGULATION 2.5 V Output, 4 V ≤ +VIN ≤ 36 V TMIN to TMAX 3.0 V Output, 4.5 V ≤ +VIN ≤ 36 V TMIN to TMAX LOAD REGULATION, SERIES MODE Sourcing 0 < IOUT < 10 mA TMIN to TMAX Sinking –10 < IOUT < 0 mA –40°C to +85°C –55°C to +125°C LOAD REGULATION, SHUNT MODE I < ISHUNT < 10 mA QUIESCENT CURRENT, 2.5 V SERIES MODE –40°C to +85°C –55°C to +125°C AD780CR Max Min 2.505 3.005 2.4985 2.9950 Typ AD780BN/BR Max Min 2.5015 3.0050 2.499 2.999 Typ Max Unit 2.501 3.001 Volts Volts 7 20 7 20 3 ppm/°C ppm/°C 10 * * µV/V 10 * * µV/V 50 75 75 75 150 * * * * * * * * * * µV/mA µV/mA µV/mA µV/mA µV/mA 75 * * µV/mA 2 0.75 0.8 1.0 1.3 * * * * * * * * mA mA MINIMUM SHUNT CURRENT 0.7 1.0 * * * * mA OUTPUT NOISE 0.1 Hz to 10 Hz Spectral Density, 100 Hz 4 100 * * * * * * * * µV p-p nV/√Hz LONG TERM STABILITY3 20 * TRIM RANGE TEMPERATURE PIN Voltage Output @ 25°C Temperature Sensitivity Output Resistance 4.0 500 SHORT CIRCUIT CURRENT TO GROUND TEMPERATURE RANGE Specified Performance (A, B, C) Operating Performance (A, B, C)4 Specified Performance (S) Operating Performance (S) * 560 1.9 3 620 * 30 –40 –55 –55 –55 * * * * ±% * * * * * * * +85 +125 +125 +125 ± ppm/ 1000 Hr * * * * * * * * * * * * * * mV mV/°C kΩ mA * * * * °C °C °C °C NOTES 1 Maximum output voltage drift is guaranteed for all packages. 2 3.0 V mode typically adds 100 µA to the quiescent current. Also, Iq increases by 2 µA/V above an input voltage of 5 V. 3 The long term stability specification is noncumulative. The drift in subsequent 1000 hr. periods is significantly lower than in the first 1000 hr. period. 4 The operating temperature range is defined as the temperature extremes at which the device will still function. Parts may deviate from their specified performance outside their specified temperature range. *Same as AD780AN/AR specification. Specifications subject to change without notice. –2– REV. B AD780 ABSOLUTE MAXIMUM RATINGS* DIE LAYOUT VIN to Ground . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 36 V Trim Pin to Ground . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 36 V Temp Pin to Ground . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 36 V Power Dissipation (25°C) . . . . . . . . . . . . . . . . . . . . . . 500 mW Storage Temperature . . . . . . . . . . . . . . . . . . . –65°C to +150°C Lead Temperature (Soldering, 10 sec) . . . . . . . . . . . . . 300°C Output Protection: Output safe for indefinite short to ground and momentary short to VIN. ESD Classification . . . . . . . . . . . . . . . . . . . . . Class 1 (1000 V) *Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any conditions above those indicated in the operational specification is not implied. Exposure to absolute maximum specifications for extended periods may affect device reliability. PIN CONFIGURATION 8-Lead Plastic DIP, SOIC and Cerdip Packages NC 1 +V IN 2 TEMP 3 GND 4 8 2.5/3.0V SELECT (NC OR GND) AD780 7 NC TOP VIEW (Not to Scale) 6 VOUT 5 TRIM NOTES Both VOUT pads should be connected to the output Die Thickness: The standard thickness of Analog Devices Bipolar dice is 24 mils ± 2 mils. Die Dimensions: The dimensions given have a tolerance of ± 2 mils. Backing: The standard backside surface is silicon (not plated). Analog Devices does not recommend gold-backed dice for most applications. Edges: A diamond saw is used to separate wafers into dice thus providing perpendicular edges half-way through the die. NC = NO CONNECT In contrast to scribed dice, this technique provides a more uniform die shape and size. The perpendicular edges facilitate handling (such as tweezer pick-up) while the uniform shape and size simplifies substrate design and die attach. Top Surface: The standard top surface of the die is covered by a layer of glassivation. All areas are covered except bonding pads and scribe lines. Surface Metalization: The metalization to Analog Devices bipolar dice is aluminum. Minimum thickness is 10,000Å. Bonding Pads: All bonding pads have a minimum size of 4.0 mils by 6.0 mils. The passivation windows have a 3.6 mils by 5.6 mils minimum size. ORDERING GUIDE Model Initial Error Temperature Range Temperature Coefficient Package Options AD780AN AD780AR AD780AR-REEL7 AD780BN AD780BR AD780BR-REEL AD780BR-REEL7 AD780CR AD780CR-REEL7 ⫾5.0 mV ⫾5.0 mV ⫾5.0 mV ⫾1.0 mV ⫾1.0 mV ⫾1.0 mV ⫾1.0 mV ⫾1.5 mV ⫾1.5 mV –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C 7 ppm/°C 7 ppm/°C 7 ppm/°C 3 ppm/°C 3 ppm/°C 3 ppm/°C 3 ppm/°C 7 ppm/°C 7 ppm/°C Plastic Dip SOIC SOIC Plastic Dip SOIC SOIC SOIC SOIC SOIC CAUTION ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection. Although the AD780 features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high-energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality. REV. B –3– WARNING! ESD SENSITIVE DEVICE AD780 THEORY OF OPERATION APPLYING THE AD780 Bandgap references are the high performance solution for low supply voltage and low power voltage reference applications. In this technique a voltage with a positive temperature coefficient is combined with the negative coefficient of a transistor’s Vbe to produce a constant bandgap voltage. The AD780 can be used without any external components to achieve specified performance. If power is supplied to Pin 2 and Pin 4 is grounded, Pin 6 provides a 2.5 V or 3.0 V output depending on whether Pin 8 is left unconnected or grounded. In the AD780, the bandgap cell contains two npn transistors (Q6 and Q7) which differ in emitter area by 12⫻. The difference in their Vbe’s produces a PTAT current in R5. This in turn produces a PTAT voltage across R4, which when combined with the Vbe of Q7, produces a voltage Vbg that does not vary with temperature. Precision laser trimming of the resistors and other patented circuit techniques are used to further enhance the drift performance. +VIN A bypass capacitor of 1 µF (VIN to GND) should be used if the load capacitance in the application is expected to be greater than 1 nF. The AD780 in 2.5 V mode typically draws 700 µA of Iq at 5 V. This increases by ~2 µA/V up to 36 V. NC +VIN VOUT NC 1F NC AD780 RNULL TRIM R POT. TEMP AD780 GND R11 R10 NC VOUT NC = NO CONNECT Figure 2. Optional Fine Trim Circuit R13 Q6 Q7 R16 R5 R14 TEMP TRIM R15 R4 GND NC = NO CONNECT O/P SELECT 2.5V – NC 3.0V – GND O/P SELECT 2.5V - NC 3.0V - GND Figure 1. Schematic Diagram The output voltage of the AD780 is determined by the configuration of resistors R13, R14 and R15 in the amplifier’s feedback loop. This sets the output to either 2.5 V or 3.0 V depending on whether R15 (Pin 8) is grounded or not connected. Initial error can be nulled using a single 25 kΩ potentiometer connected between VOUT, Trim and GND. This is a coarse trim with an adjustment range of ± 4% and is only included here for compatibility purposes with other references. A fine trim can be implemented by inserting a large value resistor (e.g. 1–5 MΩ) in series with the wiper of the potentiometer. See Figure 2 above. The trim range, expressed as a fraction of the output, is simply greater than or equal to 2.1 kΩ/RNULL for either the 2.5 V or 3.0 V mode. The external null resistor affects the overall temperature coefficient by a factor equal to the percentage of VOUT nulled. For example a 1 mV (.03%) shift in the output caused by the trim circuit, with a 100 ppm/°C null resistor will add less than 0.06 ppm/°C to the output drift (0.03% ⫻ 200 ppm/°C, since the resistors internal to the AD780 also have temperature coefficients of less than 100 ppm/°C). A unique feature of the AD780 is the low headroom design of the high gain amplifier which produces a precision 3 V output from an input voltage as low as 4.5 V (or 2.5 V from a 4.0 V input). The amplifier design also allows the part to work with VIN = VOUT when current is forced into the output terminal. This allows the AD780 to work as a two terminal shunt regulator providing a –2.5 V or –3.0 V reference voltage output without external components. The PTAT voltage is also used to provide the user with a thermometer output voltage (at Pin 3) which increases at a rate of approximately 2 mV/°C. The AD780’s NC Pin 7 is a 20 kΩ resistor to V+ which is used solely for production test purposes. Users who are currently using the LT1019 self-heater pin (Pin 7) must take into account the different load on the heater supply. –4– REV. B AD780 NOISE PERFORMANCE NOISE COMPARISON The impressive noise performance of the AD780 can be further improved if desired by the addition of two capacitors: a load capacitor C1 between the output and ground, and a compensation capacitor C2 between the TEMP pin and ground. Suitable values are shown in Figure 3. The wideband noise performance of the AD780 can also be expressed in ppm. The typical performance with C1, C2 is 0.6 ppm and without external capacitors is 1.2 ppm. This performance is respectively 7⫻ and 3⫻ lower than the specified performance of the LT1019. 100 NO AMPLIFIER COMPENSATION CAP, C2 – nF 20V 10ms 100 90 10 10 1 0% 10Hz TO 10kHz Figure 6. Reduced Noise Performance with C1 = 100 µ F, C2 = 100 nF 0.1 0.1 1 10 100 LOAD CAPACITOR, C1 – F TEMPERATURE PERFORMANCE Figure 3. Compensation and Load Capacitor Combinations The AD780 provides superior performance over temperature by means of a combination of patented circuit design techniques, precision thin film resistors and drift trimming. Temperature performance is specified in terms of ppm/°C, but because of nonlinearity in the temperature characteristic, the Box-Test method is used to test and specify the part. The nonlinearity takes the form of the characteristic S-shaped curve shown in Figure 7. The Box-Test method forms a rectangular box around this curve, enclosing the maximum and minimum output voltages over the specified temperature range. The specified drift is equal to the slope of the diagonal of this box. C1 and C2 also improve the settling performance of the AD780 when subjected to load transients. The improvement in noise performance is shown in Figures 4, 5 and 6 following. AMPLIFIER GAIN = 100 NO AMPLIFIER 100V 20V 1s 100 100 90 90 10 10 0% 0% 10ms 2.0 0.1 TO 10Hz 1.6 10Hz TO 10kHz Figure 4. Stand-Alone Noise Performance ERROR – mV 1.2 NC +VIN VOUT NC 0.8 0.4 0 AD780 1F –0.4 TRIM C1 TEMP C2 GND O/P SELECT 2.5V – NC 3.0V – GND –0.8 –60 –40 –20 0 20 40 60 80 100 120 140 TEMPERATURE – C Figure 7. Typical AD780BN Temperature Drift NC = NO CONNECT Figure 5. Noise Reduction Circuit REV. B –5– AD780 TEMPERATURE OUTPUT PIN TEMPERATURE TRANSDUCER CIRCUIT The AD780 provides a “TEMP” output (Pin 3) that varies linearly with temperature. This output can be used to monitor changes in system ambient temperature and to initiate calibration of the system if desired. The voltage VTEMP is 560 mV at 25°C, and the temperature coefficient is approximately 2 mV/°C. Figure 8 shows the typical VTEMP characteristic curve over temperature taken at the output of the op amp with a noninverting gain of five. The circuit shown in Figure 9 is a temperature transducer which a amplifies the TEMP output voltage by a gain of a little over 5 to provide a wider full scale output range. The trimpot can be used to adjust the output so it varies exactly by 10 mV/°C. To minimize resistance changes with temperature, resistors with low temperature coefficients, such as metal film resistors should be used. +5V 4.25 CIRCUIT CALIBRATED AT 25C REFER TO FIGURE 9 4.00 VOLTAGE – VOUT 3.75 VIN 3.50 1F 3.25 TEMP 10mV PER C 10mV/C AD820 AD780 3.00 2.75 RF 2.50 6.04k (1%) GND RB 2.25 2.00 –75 –50 –25 0 25 50 75 100 125 150 RBP TEMPERATURE – C 1.27k (1%) 200 Figure 8. Temperature Pin Transfer Characteristic Since the TEMP voltage is acquired from the bandgap core circuit, current pulled from this pin will have a significant effect on VOUT. Care must be taken to buffer the TEMP output with a suitable op amp, e.g., an OP07, AD820 or AD711 (all of which would result in less than a 100 µV change in VOUT). The relationship between ITEMP and VOUT is as follows: ∆VOUT = 5.8 mV/µA × ITEMP (2.5 V range) or ∆VOUT = 6.9 mV/µA × ITEMP (3.0 V range) Figure 9. Differential Temperature Transducer SUPPLY CURRENT OVER TEMPERATURE The AD780’s quiescent current will vary slightly over temperature and input supply range. The test limit is 1 mA over the industrial and 1.3 mA over the military temperature range. Typical performance with input voltage and temperature variation is shown in Figure 10 following. 0.85 Notice how sensitive the current dependent factor on VOUT is. A large amount of current, even in tens of microamp, drawn from TEMP pin can cause VOUT and TEMP Output to fail. QUIESCENT CURRENT – mA –55C The choice of C1 and C2 was dictated primarily by the need for a relatively flat response that rolled off early in the high frequency noise at the output. But there is considerable margin in the choice of these capacitors. For example, the user can actually put a huge C2 on the TEMP pin with none on the output pin. However, one must either put very little or a lot of capacitance at the TEMP pin. Intermediate values of capacitance can sometimes cause oscillation. In any case, the user should follow the recommendation in Figure 3. 0.80 25C 0.75 125C 0.70 0.65 0.60 4 36 INPUT VOLTAGE – Volts Figure 10. Typical Supply Current over Temperature –6– REV. B AD780 TURN-ON TIME The time required for the output voltage to reach its final value within a specified error band is defined as the turn-on settling time. The two major factors that affect this are the active circuit settling time and the time for the thermal gradients on the chip to stabilize. Typical settling performance is shown in Figure 11 following. The AD780 settles to within 0.1% of its final value within 10 µs. 0mA ILOAD OUTPUT CHANGE – 50mV/DIV 10mA VIN 5V VOUT (CL = 0pF) 10s/DIV 0V Figure 12b. Settling Under Transient Resistive Load VOUT The dynamic load may be resistive and capacitive. For example the load may be connected via a long capacitive cable. Figure 13 following shows the performance of the AD780 driving a 1000 pF, 0 mA to 10 mA load. 2.500V 2.499V 2.498V +VIN 10s/DIV Figure 11. Turn-On Settling Time Performance DYNAMIC PERFORMANCE The output stage of the AD780 has been designed to provide superior static and dynamic load regulation. AD780 1F VOUT CL 1000pF Figure 12 shows the performance of the AD780 while driving a 0 mA to 10 mA load. 249 +VIN VL 1F VOUT 0V Figure 13a. Capacitive Load Transient Response Test Circuit AD780 VOUT 0mA 249 ILOAD VL OUTPUT CHANGE – 50mV/DIV 10mA VOUT 0V Figure 12a. Transient Resistive Load Test Circuit VOUT (CL = 1000pF) 10s/DIV Figure 13b. Settling Under Dynamic Capacitive Load REV. B –7– AD780 LINE REGULATION Line regulation is a measure of the change in output voltage due to a specified change in input voltage. It is intended to simulate worst case unregulated supply conditions and is measured in µV/V. Figure 14 shows typical performance with 4.0 V < VIN < 15.0 V. The AD780 is also ideal for use with higher resolution converters such as the AD7710/AD7711/AD7712. (See Figure 16.) While these parts are specified with a 2.5 V internal reference, the AD780 in 3 V mode can be used to improve the absolute accuracy, temperature stability and dynamic range. It is shown following with the two optional noise reduction capacitors. +5V 200 OUTPUT CHANGE – V T = 25C 100 VIN VOUT 1F 0 REFIN+ AD780 AD7710 100F –100 100nF GND 2.5/3.0V SELECT –200 4 10 REFIN– 15 INPUT VOLTAGE – Volts Figure 14. Output Voltage Change vs. Input Voltage Figure 16. Precision 2.5 V or 3.0 V Reference for the AD7710 High Resolution, Sigma-Delta ADC PRECISION REFERENCE FOR HIGH RESOLUTION +5 V DATA CONVERTERS The AD780 is ideally suited to be the reference for most +5 V high resolution ADCs. The AD780 is stable under any capacitive load, it has superior dynamic load performance, and the 3.0 V output provides the converter with maximum dynamic range without requiring an additional and expensive buffer amplifier. One of the many ADCs that the AD780 is suited for is the AD7884, a 16-bit, high speed sampling ADC. (See Figure 15.) This part previously needed a precision 5.0 V reference, resistor divider and buffer amplifier to do this function. +4.5 V REFERENCE FROM +5 V SUPPLY Some +5 V high resolution ADCs can accommodate reference voltages up to +4.5 V. The AD780 can be used to provide a precision +4.5 V reference voltage from a +5 V supply using the circuit shown following in Figure 17. This circuit will provide a regulated +4.5 V output from a supply voltage as low as +4.7 V. The high quality tantalum 10 µF capacitor in parallel with the ceramic 0.1 µF capacitor and the 3.9 Ω resistor ensure a low output impedance up to around 50 MHz. +5V VSUPPLY 0.1F 1k VIN 1F 2N2907 VOUT VREF +F OP90 AD780 VOUT 2.5k AD780 10F VREF +S GND 0.1F 2.5/3.0V SELECT AD7884 5k 0.01% 0.1F 3.9 4k 0.01% Figure 17. +4.5 V Reference from a Single +5 V Supply Figure 15. Precision 3.0 V Reference for the AD7884 16-Bit, High Speed ADC –8– REV. B AD780 A precise –2.5 V (or –3.0 V) reference capable of supplying up to 100 mA to a load can be implemented with the AD780 in series mode using the bootstrap circuit following. NEGATIVE (–2.5 V OR –3.0 V) REFERENCE The AD780 can produce a negative output voltage in shunt mode, simply by connecting the input and output to ground connecting the AD780’s GND pin to a negative supply via a bias resistor as shown in Figure 18. +5V VIN +VIN 1k NC VOUT NC OUT AD780 +5V CONNECT IF –3V OUTPUT DESIRED AD780 TEMP 1F GND TRIM –2.5V (IL ⱕ 100mA) O/P SELECT 2.5V – NC 3.0V – GND OP07 –5V –2.5 VOUT R= VOUT – (V–) IL + IS MIN V– –5V NOTE: IL = LOAD CURRENT IS MIN = MINIMUM SHUNT CURRENT NC = NO CONNECT 1000pF Figure 19. –2.5 V High Load Current Reference Figure 18. Negative (–2.5 V) Shunt Mode Reference REV. B 2N3906 –9– AD780 OUTLINE DIMENSIONS Dimensions shown in inches and (mm). C1758–0–6/00 (rev. B) 00841 SOIC (R) Package 0.198 (5.00) 0.188 (4.75) 5 8 0.158 (4.00) 0.150 (3.80) 1 0.244 (6.200) 0.228 (5.80) 4 0.050 (1.27) TYP 0.018 (0.46) 0.014 (0.36) 0.069 (1.75) 0.053 (1.35) 0.010 (0.25) 0.004 (0.10) 0.205 (5.20) 0.181 (4.60) 0.015 (0.38) 0.045 (1.15) 0.007 (0.18) 0.020 (0.50) Plastic Mini-DIP (N) Package 8 5 0.280 (7.11) 0.240 (6.10) PIN 1 1 4 0.325 (8.25) 0.300 (7.62) 0.430 (10.92) 0.348 (8.84) 0.060 (1.52) 0.015 (0.38) 0.210 (5.33) MAX 0.130 (3.30) MIN 0.160 (4.06) 0.115 (2.93) 0.022 (0.558) 0.014 (0.356) 0.100 (2.54) BSC 0.070 (1.77) 0.045 (1.15) 0.195 (4.95) 0.115 (2.93) 0.015 (0.381) 0.008 (0.204) SEATING PLANE Cerdip (Q) Package 0.005 (0.13) MIN 0.055 (1.4) MAX 8 5 0.310 (7.87) 0.220 (5.59) 0.070 (1.78) 0.030 (0.76) 0.405 (10.29) MAX 0.200 (5.08) MAX PRINTED IN U.S.A. 4 1 0.320 (8.13) 0.290 (7.37) 0.060 (1.52) 0.015 (0.38) 0.150 (3.81) MIN 0.200 (5.08) 0.125 (3.18) 0.023 (0.58) 0.014 (0.36) 0.015 (0.38) 0.008 (0.20) 0°-15° 0.100 (2.54) BSC SEATING PLANE –10– REV. B