800 MHz, Linear-in-dB VGA with AGC Detector AD8368 FEATURES FUNCTIONAL BLOCK DIAGRAM Analog variable gain range: −12 db to +22 dB Linear-in-dB scaling: 37.5 dB/V 3 dB bandwidth: 800 MHz @ VGAIN = 0.5 V Integrated rms detector P1 dB: 16 dBm @ 140 MHz Output IP3: 33 dBm @ 140 MHz Noise figure at maximum gain: 9.5 dB @ 140 MHz Input and output impedances: 50 Ω Single-supply voltages from 4.5 V to 5.5 V RoHS-compliant, 24-lead LFCSP VPSO MODE 10 21 VPSO VPSI VPSI VPSI VPSI VPSI 9 11 12 22 ICOM 16 GAIN INTERPOLATOR FIXED-GAIN AMPLIFIER OCOM 7 OUTPUT BUFFER gm STAGES –4dB –36dB REF INPT 19 ICOM 18 50Ω DECL ATTENUATOR LADDER – X2 ENBL 8 OUTP 3 HPFL 4 DECL 14 DECL 15 DECL + ICOM 20 APPLICATIONS Complete IF AGC amplifiers Gain trimming and leveling Cellular base station Point-to-point radio links RF instrumentation 24 2 5 DETO DETI 05907-001 0dB –2dB ICOM 17 13 AD8368 OCOM 6 GAIN 1 23 Figure 1. GENERAL DESCRIPTION The AD8368 is a variable gain amplifier with analog linearin-dB gain control that can be used from low frequencies to 800 MHz. Its excellent gain range, conformance, and flatness are attributed to Analog Devices’ X-AMP® architecture, an innovative technique for implementing high performance variable gain control. The gain range of −12 dB to +22 dB is scaled accurately to 37.5 dB/V with excellent conformance error. The AD8368 has a 3 dB bandwidth of 800 MHz that is nominally independent of gain setting. At 140 MHz, the OIP3 is 33 dBm at maximum gain. The output noise floor is –143 dBm/Hz, which corresponds to a 9.5 dB noise figure at maximum gain. The single-ended input and output impedances are nominally 50 Ω. The gain of the AD8368 can be configured to be an increasing or decreasing function of the gain control voltage depending on whether the MODE pin is pulled to the positive supply or to ground, respectively. When MODE is pulled high, the AD8368 operates as a typical VGA with increasing gain. By connecting MODE to ground and using the on-board rms detector, the AD8368 can be configured as a complete AGC system with RSSI. The output power is accurately leveled to the internal default setpoint of 63 mV rms (−11 dBm referenced to 50 Ω), independent of the waveform crest factor. Because the uncommitted detector input is available at DETI, the AGC loop can level the signal at the AD8368 output or at any other point in the signal chain over a maximum input power range of 34 dB. Furthermore, the setpoint level can be raised by dividing down the output signal before applying it to the detector. The AD8368 operates from a supply voltage of 4.5 V to 5.5 V and consumes 60 mA of current. It can be fully powered down to <3 mA by grounding the ENBL pin. The AD8368 is fabricated using Analog Devices’ proprietary SiGe SOI complementary bipolar IC process. It is available in a 24-lead CSP and operates over the industrial temperature range of −40°C to +85°C. Application boards are available upon request. Rev. 0 Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©2006 Analog Devices, Inc. All rights reserved. AD8368 TABLE OF CONTENTS Features .............................................................................................. 1 Fixed-Gain Stage and Output Buffer ....................................... 12 Applications....................................................................................... 1 Output Offset Correction.......................................................... 12 Functional Block Diagram .............................................................. 1 Input and Output Impedances ................................................. 12 General Description ......................................................................... 1 Gain Control Interface............................................................... 13 Revision History ............................................................................... 2 Applications..................................................................................... 14 Specifications..................................................................................... 3 VGA Operation .......................................................................... 14 Absolute Maximum Ratings............................................................ 5 AGC Operation .......................................................................... 14 ESD Caution.................................................................................. 5 Evaluation Board ............................................................................ 17 Pin Configuration and Function Descriptions............................. 6 Outline Dimensions ....................................................................... 18 Typical Performance Characteristics ............................................. 7 Ordering Guide .......................................................................... 18 Circuit Description......................................................................... 12 Input Attenuator and Interpolator ........................................... 12 REVISION HISTORY 4/06—Revision 0: Initial Version Rev. 0 | Page 2 of 20 AD8368 SPECIFICATIONS VS = 5 V, T = 25°C, system impedance Z0 = 50 Ω, VMODE = 5 V, RF input = 140 MHz, unless otherwise noted. Table 1. Parameter OVERALL FUNCTION Frequency Range Maximum Input Maximum Output 1 AC Input Impedance AC Output Impedance GAIN CONTROL INTERFACE (GAIN) Gain Span Gain Scaling Gain Accuracy Maximum Gain Minimum Gain VGAIN Range Gain Step Response GAIN Input Impedance GAIN Input Bias Current f = 70 MHz Noise Figure Output IP3 Output P1dB1 f = 140 MHz Noise Figure Output IP3 Output P1dB1 f = 240 MHz Noise Figure Output IP3 Output P1dB1 f = 380 MHz Noise Figure Output IP3 Output P1dB1 Min Typ LF Max Unit Conditions 800 MHz Vp Vp Ω Ω 3 dB bandwidth To avoid input overload To avoid clipping From INPT to ICOM From OUTP to OCOM 3 2 50 50 34 37.5 −38 ±0.4 22 −12 0 1 100 10 −2 dB dB/V dB/V dB dB dB V ns kΩ μA VMODE = 5 V, 50 mV ≤ VGAIN ≤ 950 mV VMODE = 0 V, 50 mV ≤ VGAIN ≤ 950 mV 100 mV ≤ VGAIN ≤ 900 mV VGAIN = 1 V VGAIN = 0 V For 6 dB gain step From GAIN to ICOM 9.5 34 16 dB dBm dBm Maximum gain f1 = 70 MHz, f2 = 71 MHz, VGAIN = 1 V, 0 dBm per output tone VGAIN = 0 V, VMODE = 0 V 9.5 33 16 dB dBm dBm Maximum gain f1 = 140 MHz, f2 = 141 MHz, VGAIN = 1 V, 0 dBm per output tone VGAIN = 0 V, VMODE = 0 V 9.7 33 15 dB dBm dBm Maximum gain f1 = 240 MHz, f2 = 241 MHz, VGAIN = 1 V, 0 dBm per output tone VGAIN = 0 V, VMODE = 0 V 10 29 13 dB dBm dBm Maximum gain f1 = 380 MHz, f2 = 381 MHz, VGAIN = 1 V, 0 dBm per output tone VGAIN = 0 V, VMODE = 0 V 1 Operation at compression is not recommended due to adverse distortion components. Rev. 0 | Page 3 of 20 AD8368 VS = 5 V, T = 25°C, system impedance Z0 = 50 Ω, VMODE = 5 V, RF input = 140 MHz, unless otherwise noted. Table 2. Parameter SQUARE LAW DETECTOR (DETI, DETO) Output Setpoint DETI DC Bias Level to ICOM DETI Impedance Min DETO Output Range 1 AGC Step Response MODE CONTROL INTERFACE (MODE) Mode Threshold MODE Input Bias Current POWER INTERFACE (VPSI, VPSO) Supply Voltage Total Supply Current Disable Current ENABLE INTERFACE (ENBL) Enable Threshold Enable Response Time 0.1 Max −11 VS/2 710 0.6 VS/2 30 3.5 50 4.5 ENBL Input Bias Current 1 Typ 5 60 2 5.5 Unit Conditions dBm V Ω pF V μs OUTP connected to DETI V μA V mA mA 2.5 1.5 V μs 3 μs 150 For −6 dB input power step (CDETO = 1 nF) μA Refer to AGC operation in the Applications section. Rev. 0 | Page 4 of 20 ENBL HIGH ENBL LOW Time delay following off to on transition until output reaches 90% of final value. Time delay following on to off transition until supply current is less than 5 mA. VENBL = 5 V AD8368 ABSOLUTE MAXIMUM RATINGS Table 3. Parameter Supply Voltage, VPSO, VPSI ENBL and MODE Select Voltage RF Input Level Internal Power Dissipation θJA Maximum Junction Temperature Operating Temperature Range Storage Temperature Range Lead Temperature (Soldering 60 sec) Rating 5.5 V 5.5 V 20 dBm 440 mW 52°C/W 125°C −40°C to +85°C −65°C to +150°C 300°C Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. ESD CAUTION ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection. Although this product features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality. Rev. 0 | Page 5 of 20 AD8368 ENBL VPSI VPSI MODE ICOM INPT PIN CONFIGURATION AND FUNCTION DESCRIPTIONS 24 23 22 21 20 19 GAIN 1 18 ICOM DETO 2 17 ICOM HPFL 3 AD8368 16 ICOM DECL 4 TOP VIEW (Not to Scale) 15 DECL DETI 5 14 DECL 8 9 10 11 12 VPSO VPSO VPSI VPSI 05907-002 7 OUTP 13 VPSI OCOM OCOM 6 Figure 2. AD8368 24-Lead LFCSP Pin Out Table 4. Pin Function Descriptions Pin No. 1 2 3 Name GAIN DETO HPFL 4, 14, 15 DECL 5 6, 7 16, 17, 18, 20 8 9, 10 DETI OCOM ICOM OUTP VPSO 11, 12, 13, 22, 23 19 21 24 VPSI INPT MODE ENBL Function Gain Control. Detector Output. Provides an output error current for the AGC function. High-Pass Filter Connection. A capacitor to ground sets the corner frequency of the internal output offset control loop which controls the minimum usable input frequency. Decoupling Pin. Nominally ~VS/2. Decoupling capacitance may need to be adjusted for AGC operation (see the Applications section). Detector Input. DC level referenced to DECL pin. Connect OCOM to low impedance ground. Connect ICOM to low impedance ground. Signal Output. Must be ac-coupled. Positive Supply Voltage, 4.5 V to 5.5 V. VPSO and VPSI must be connected together externally and properly bypassed. Positive Supply Voltage, 4.5 V to 5.5 V. VPSO and VPSI must be connected together externally and properly bypassed. Signal Input. Must be ac-coupled. Gain Direction Control. HIGH for positive slope. LOW for negative slope. Apply a positive voltage (2.5V ≤ VENBL ≤ VPSI ) to activate device. Rev. 0 | Page 6 of 20 AD8368 TYPICAL PERFORMANCE CHARACTERISTICS VS = 5 V, T = 25°C, system impedance Z0 = 50 Ω, MODE = 5 V, unless otherwise noted. 25 4 25 240MHz +85°C 10 1 5 0 –1 0 +25°C 0.25V –40°C –5 –10 100 –15 1000 0 0.2 0.4 FREQUENCY (MHz) 0.6 VGAIN (V) Figure 3. Frequency Response vs. VGAIN Figure 6. Gain and Conformance Error vs. VGAIN (f = 240 MHz) 4 25 25 4 70MHz 380MHz 3 10 1 5 0 –1 +25°C –40°C –5 –2 –10 –3 –15 0 0.2 0.4 0.6 –4 1.0 0.8 3 15 GAIN (dB) GAIN (dB) +85°C CONFORMANCE ERROR (dB) 2 15 20 2 +85°C 10 1 5 0 0 –1 +25°C –40°C –5 –2 –10 05907-004 20 0 –4 1.0 0.8 –15 CONFORMANCE ERROR (dB) –20 10 –3 –10 05907-003 0V –15 –2 05907-006 GAIN (dB) S21 (dB) 0.5V 0 –5 2 15 0.75V 10 5 3 20 CONFORMANCE ERROR (dB) 1V 15 –3 0 0.2 0.4 VGAIN (V) 0.6 05907-007 20 –4 1.0 0.8 VGAIN (V) Figure 4. Gain and Conformance Error vs. VGAIN (f = 70 MHz) Figure 7. Gain and Conformance Error vs. VGAIN (f = 380 MHz) 4 25 0.7 140MHz 20 3 15 2 0.6 5 0 –1 0 +25°C –40°C –5 –2 –10 –3 –15 –4 1.0 0 0.2 0.4 0.6 0.8 VGAIN (V) 0.3 0.2 VOUTP 0.1 0 –0.1 –0.2 05907-008 1 VGAIN 0.4 AMPLITUDE (V) 10 05907-005 GAIN (dB) +85°C CONFORMANCE ERROR (dB) 0.5 –0.3 –0.4 –0.5 –0.4 –0.3 –0.2 –0.1 0 0.1 0.2 0.3 0.4 TIME (µs) Figure 8. Gain Step Time Domain Response (6 dB Gain Step) Figure 5. Gain and Conformance Error vs. VGAIN (f = 140 MHz) Rev. 0 | Page 7 of 20 0.5 AD8368 20 +85°C +25°C –40°C 20 15 10 5 0 70 110 150 190 230 270 310 350 +25°C 16 14 12 10 –40°C 8 6 4 05907-012 OUTPUT 1dB COMPRESSION (dBm) 30 25 +85°C 18 35 05907-009 OUTPUT THIRD-ORDER INTERCEPT (dBm) 40 2 0 70 380 110 150 RF INPUT (MHz) 70MHz 140MHz 350 380 240MHz 380MHz 20 15 10 5 0 0.2 0.4 0.6 0.8 16 14 380MHz 12 240MHz 10 8 6 4 05907-013 OUTPUT 1dB COMPRESSION (dBm) 30 25 140MHz 18 35 05907-010 OUTPUT THIRD-ORDER INTERCEPT (dBm) 310 20 70MHz 2 0 1.0 0 0.2 0.4 VGAIN (V) 0.6 0.8 1.0 VGAIN (V) Figure 13. Output Compression Point vs. VGAIN (VMODE = 0 V) Figure 10. OIP3 vs. VGAIN (VMODE = 0 V) 20 0 5.5V 18 –20 –30 –40 380MHz 240MHz –50 –70 140MHz 0 0.2 0.4 0.6 70MHz 0.8 05907-011 –60 14 5.0V 12 4.5V 10 8 6 4 2 0 70 1.0 110 150 190 230 270 310 350 380 RF INPUT (MHz) VGAIN (V) Figure 11. Third-Order IMD vs. VGAIN (Output Power Is 0 dBm per Tone, VMODE = 0 V) 16 05907-014 OUTPUT 1dB COMPRESSION (dBm) –10 THIRD-ORDER IMD (dBc) 270 Figure 12. Output Compression Point vs. Frequency at Maximum Gain (VMODE = 0 V) 40 –80 230 RF INPUT (MHz) Figure 9. OIP3 vs. Frequency at Maximum Gain (VMODE = 0 V) 0 190 Figure 14. Output Compression Point vs. Supply Voltage at Maximum Gain (VMODE = 0 V) Rev. 0 | Page 8 of 20 AD8368 50 45 35 VGAIN = 0.75V 30 25 VGAIN = 0V 20 VGAIN = 1V 15 VGAIN = 0.25V 10 0 10 100 05907-018 05907-015 VGAIN = 0.5V 5 1000 FREQUENCY (MHz) Figure 18. Input Reflection Coefficient vs. Frequency Figure 15. Noise Figure vs. Frequency at Maximum Gain (VMODE = 0 V) 50 0 45 –5 OUTPUT RETURN LOSS (dB) 34 30 25 20 15 70MHz 140MHz 240MHz 380MHz 10 5 0 0 0.2 0.4 0.6 0.8 –10 –15 –20 –25 –30 –35 05907-016 NOISE FIGURE (dB) 40 VGAIN = 1V VGAIN = 0V –40 10 1.0 100 VGAIN (V) 1000 FREQUENCY (MHz) Figure 16. Noise Figure vs. VGAIN (VMODE = 0 V) Figure 19. Output Reflection Coefficient vs. Frequency 0 –5 VGAIN = 0.75V –15 VGAIN = 1V VGAIN = 1V –25 –30 VGAIN = 0V VGAIN = 0.25V –40 10 100 VGAIN = 0V 05907-020 –35 05907-017 INPUT RETURN LOSS (dB) VGAIN = 0.5V –10 –20 1000 FREQUENCY (MHz) Figure 17. Input Return Loss vs. Frequency Figure 20. Output Reflection Coefficient vs. Frequency Rev. 0 | Page 9 of 20 05907-019 NOISE FIGURE (dB) 40 1.0 0.9 0.8 0.9 0.8 0.8 0.6 0.8 0.4 0.6 0.2 0.5 0 –0.2 +25°C –0.4 +25°C 0.2 –0.6 0.1 –0.8 –40°C –35 +85°C –30 –25 –20 –15 –10 –5 0 5 –1.0 0.6 0.2 0.5 0 –40°C 0.4 0.2 –0.6 0.1 –0.8 0 –40 +25°C +85°C –35 –30 –25 0.6 0.7 0.4 0.6 0.2 0.5 0 +25°C +85°C –0.2 –40°C –0.4 –40°C 0.2 –0.6 0.1 –0.8 +85°C –25 –20 –15 –10 –5 0 5 –1.0 0.8 0.8 0.6 0.7 0.4 0.6 0.2 0.5 0 +25°C +85°C –0.2 –40°C –0.4 –40°C 0.2 –0.6 0.1 0 –40 –0.8 –35 +85°C –30 –25 –20 –15 –10 –5 0 5 –1.0 SUPPLY CURRENT (mA) 1.0 0.9 CONFORMANCE ERROR (dB) 1.0 +25°C –1.0 410mV Figure 25. AGC Time Domain Response (3 dB Power Step, CDETO =1 nF) 05907-023 RSSI (V) Figure 22. RSSI (VDETO) and Conformance Error vs. Input Power (f = 140 MHz) 0.3 5 VOUTP CH2 50mV Ω CH3 100mV Ω M20µs 500MS/s A CH1 2.0ns/PT RF INPUT (dBm) 0.4 0 05907-025 0.8 –30 –5 VRSSI AMPLITUDE (V) 0.8 –35 –10 Figure 24. RSSI (VDETO) and Conformance Error vs. Input Power (f = 380 MHz) CONFORMANCE ERROR (dB) 1.0 0.9 0 –40 –15 05907-022 RSSI (V) 1.0 +25°C –20 RF INPUT (dBm) Figure 21. RSSI (VDETO) and Conformance Error vs. Input Power (f = 70 MHz) 0.3 –0.4 –40°C RF INPUT (dBm) 0.4 –0.2 +25°C 0.3 RF INPUT (dBm) 80 8 70 7 60 4.5V 6 50 40 5 5.0V 5.5V 5.5V 4 30 3 5.0V 20 2 10 1 4.5V 0 –40 –20 0 20 40 60 80 0 TEMPERATURE (°C) Figure 23. RSSI (VDETO) and Conformance Error vs. Input Power (f = 240 MHz) Rev. 0 | Page 10 of 20 Figure 26. Supply Current and Disable Current vs. Supply Voltage DISABLE CURRENT (mA) 0 –40 0.4 05907-026 0.4 0.3 –40°C +85°C 0.7 RSSI (V) 0.7 0.6 +85°C CONFORMANCE ERROR (dB) 1.0 05907-024 1.0 CONFORMANCE ERROR (dB) 1.0 05907-021 RSSI (V) AD8368 AD8368 50 VENBL PERCENTAGE (%) AMPLITUDE (V) 40 VOUTP 30 20 CH2 500mV Ω CH3 5V Ω M2.0µs 250MS/s 4.0ns/PT A CH3 0 0.0V 30 20 10 05907-028 PERCENTAGE (%) 40 37.2 37.4 37.6 –14.7 –14.4 –14.1 –13.8 –13.5 Figure 29. Gain Intercept Distribution (140 MHz) 50 37.0 –15.0 INTERCEPT (dB) Figure 27. ENBL Response Time 0 36.8 05907-029 05907-027 10 37.8 38.0 38.2 SLOPE (dB/V) Figure 28. Gain Scaling Distribution (140 MHz) Rev. 0 | Page 11 of 20 AD8368 CIRCUIT DESCRIPTION The main signal path, shown in Figure 30, consists of a variable input attenuator followed by a fixed-gain amplifier and output stage. This architecture allows for a constant OIP3 and output noise floor as a function of gain setting. As a result, NF and IIP3 increase 1 dB for every 1 dB decrease in gain, resulting in a part with constant dynamic range over gain setting. OUTPUT OFFSET CORRECTION The dc level at the input, INPT, is driven by an internal reference to VS/2. The reference is made available at the DECL pin for external decoupling with CDECL. The dc level at the output, OUTP, is regulated to the same midsupply reference by an offset correction loop independent of gain setting, temperature, and process. The low-pass response of this loop creates a high-pass corner frequency in the signal path transfer function, which can be set by choosing CDECL and CHPFL. FIXED-GAIN OUTPUT AMPLIFIER BUFFER FROM INTERPOLATOR gm STAGES gm ×1 MODE GAIN GAIN INTERPOLATOR –4dB HPFL DECL CHP CDECL VMID FIXED-GAIN OUTPUT AMPLIFIER BUFFER gm STAGES 0dB –2dB VOUT VOUT –36dB 50Ω DECL ATTENUATOR LADDER 05907-033 INPT Figure 30. Simplified Block Diagram INPUT ATTENUATOR AND INTERPOLATOR The input attenuator is built from an 18-section resistor ladder providing 2 dB of attenuation at each successive tap point. The resistor ladder acts as a linear input attenuator, in addition to providing an accurate 50 Ω input impedance. The variable transconductance (gm) stages are used to select the attenuated signal from the appropriate tap point along the ladder and feed this signal to the fixed-gain amplifier. To realize a continuous gain control function from discrete tap points, the gain interpolator creates a weighted sum of signals appearing on adjacent tap points by carefully controlling the variable gm stages. FIXED-GAIN STAGE AND OUTPUT BUFFER The weighted sum of the different tap points is fed into the fixed-gain stage which drives the output buffer. Because the resistive input attenuator is linear and contributes minimal noise as a passive termination, the dynamic range as a function of gain is determined primarily by the noise and distortion of the fixed-gain amplifier. This explains the constant OIP3 and constant output noise floor with gain setting and the corresponding dB-for-dB increase in IIP3 and NF with decreasing gain. The output buffer has 6 dB of gain and provides a broadband 50 Ω single-ended output impedance. 05907-034 The AD8368 is a single-ended VGA with a bandwidth of 800 MHz and a gain control span of 34 dB ranging from −12 dB to +22 dB. It incorporates an uncommitted square law detector that can be used to form a tight AGC loop around the VGA. Using Analog Devices’ patented X-AMP architecture, the AD8368 achieves accurate linear-in-dB gain control with excellent linearity (OIP3) and noise figure (NF). The part also features 50 Ω input and output impedances for ease of use. Figure 31. Output Centering Control Loop The input and output coupling capacitors should be selected to provide low impedances at the frequencies of interest relative to 50 Ω so as not to affect the high-pass corner. In this case, the high-pass corner frequency can be set by either CHPFL or CDECL which form independent poles in the feedback path of the offset correction loop. The high-pass corner is determined by the highest of these poles, which are given by: fHP , HPFL(kHz) = 0.8 (0.005 + CHPFL) fHP , DECL(kHz) = 5700 (0.005 + CDECL) where CHPFL and CDECL are in nF. When using this method to set the high-pass frequency, the other capacitor should be sized such that its pole is at least 30× lower in frequency. Also note that CDECL represents the total decoupling capacitance at the DECL pins. INPUT AND OUTPUT IMPEDANCES The AD8368 offers single-ended broadband 50 Ω input and output impedances. The excellent match to 50 Ω is maintained from part to part, over frequency, and over gain setting. Both the input and output pins must be externally ac coupled to prevent disruption of the internal dc levels. Sufficiently large coupling capacitors should be used so that their impedance is negligible relative to the 50 Ω presented by the ladder at the input and by the output buffer at the output. Rev. 0 | Page 12 of 20 AD8368 GAIN CONTROL INTERFACE 4 25 3 15 2 10 ERROR_L 1 0 5 0 ERROR_H –1 –2 –5 –3 –10 GAIN_L The gain functions for MODE pulled high and low are given respectively by: –15 where VGAIN is expressed in volts. 0.2 0.4 0.6 0.8 –4 1.0 VGAIN (V) GainHIGH (dB) = 37.5 × VGAIN − 14 GainLOW (dB) = −38 × VGAIN + 24.8 0 Figure 32. Gain and Conformance Error vs. VGAIN As shown in Figure 32, the gain function can be either an increasing or decreasing function of VGAIN, depending on the MODE pin. Rev. 0 | Page 13 of 20 05907-035 20 CONFORMANCE ERROR (dB) GAIN_H GAIN (dB) The AD8368 has a linear-in-dB gain control interface that can be operated in either a gain-up mode or gain-down mode. In the gain-up mode with the MODE pin pulled high, the gain increases with increasing gain voltages. In the gain-down mode, with the MODE pin pulled low, the gain decreases with increasing gain voltages. In both modes of operation, the gain control slope is maintained at +37.5 dB/V or −38 dB/V (depending on mode selection) over temperature, supply, and process as VGAIN varies from 100 mV to 900 mV. Note that MODE LOW is required to form an AGC loop with the onboard detector around the VGA. AD8368 APPLICATIONS VGA OPERATION The AD8368 is a general-purpose VGA suitable for use in a wide variety of applications where accurate, continuous, linear-in-dB gain control over a broad range of frequencies is important. Its stability over temperature and supply in comparison to other variable-gain techniques can be traced back to the X-AMP architecture. While having an 800 MHz bandwidth, its low frequency operation can be extended by properly selecting CHPFL and CDECL. The typical connections for using the AD8368 in VGA mode are illustrated in Figure 33. The input (INPT) and output (OUTP) of the AD8368 should be externally ac coupled to prevent disrupting the dc levels on the chip. Thus, a sufficiently large coupling capacitor should be used such that the series impedance of the capacitor is negligible at the frequencies of interest. VIN INPT VPSI CDETO R2 ICOM X2 DECL ICOM REF – DECL + DECL OCOM VPSI VPSI AD8368 VPSI R1 Figure 33. Typical Connections for VGA Mode for Increasing Gain with Increasing VGAIN (MODE HIGH) The gain control voltage ranging from 0 V to 1 V is applied to the GAIN pin. The MODE pin controls whether the gain of the part is an increasing or decreasing function of the gain voltage. When the MODE pin is pulled high, the gain increases with increasing gain voltages. When the MODE pin is pulled low, the gain decreases with increasing gain voltages. The ENBL pin is used to enable or disable the part. ENBL is active high; when ENBL is pulled low, the part is disabled and draws a fraction of the normal supply current. INPT ICOM DETO DETI 05907-036 VPOS VOUT GAIN HPFL VPSI VPSI VPSO OUTP OCOM VPSO AD8368 OCOM VPOS VOUT 05907-037 RSSI DECL VPSO + DETI ICOM DECL MODE ENBL ICOM REF – OCOM X2 VPOS VPSI ICOM VPSI DETO VIN VPSO ICOM DECL The AD8368 can be configured as a standalone AGC amplifier by using the on-board rms detector, as shown in Figure 34. The detector output, DETO, is an error current representing the difference of squares between the root-mean-square (rms) of the sensed signal and an internal reference of 63 mV rms. This error current is integrated on CDETO and connected to the GAIN pin to form the AGC loop. OUTP ICOM MODE VPSI VPSI ENBL GAIN HPFL AGC OPERATION The 63 mV rms reference corresponds to 178 mV p-p for a sine wave but the detector accuracy is maintained for more complex signals such as Gaussian noise, complex envelopes, and multicarrier signals with high peak-to-average ratios. VPOS VGAIN 0V TO 1V The DECL pin provides the internal midsupply dc reference for the AD8368. It should be well decoupled to ground using a large capacitor with low ESR. The capacitors connected to the HPFL pin and DECL pin are used to control the low-pass corner frequency of the output offset correction loop. The resulting high-pass corner frequency is inversely proportional to their values. Figure 34. AGC Mode of Operation The AGC mode of operation requires a specific gain direction. The gain must fall as VDETO increases to restore the needed balance against the setpoint. Therefore, the MODE pin must be pulled low. By connecting the signal at OUTP directly to the detector input (DETI), the output level is driven to the 63 mV rms reference setpoint. Rev. 0 | Page 14 of 20 AD8368 Figure 36 shows a plot of the RSSI voltage at DETO as input power is swept. 3.0 2.5 2.0 RSSI (V) The output setpoint may be increased using an external resistive divider network between OUTP and DETI, referenced to DECL as depicted in Figure 34. In this configuration, the rms output voltage is forced to (1 + R1/R2)63 mV rms by the AGC loop. For a 0 dBm (224 mV rms referenced to 50 Ω) output setpoint, this ratio is 3.5. After correcting for the input impedance of DETI, the choice of R1 = 226 Ω and R2 = 100 Ω yields a setpoint of roughly 0 dBm. This very accurate leveling function is shown in Figure 35, where the rms output is held to within 0.2 dB of the 0 dBm setpoint for >30 dB range of input levels. 1.5 1.0 10 5 05907-039 0.5 POWER OUT (dBm) 0 0 –40 –5 –30 –20 –10 0 10 20 POWER IN (dBm) –10 Figure 36. Monitoring the GAIN/DETO RSSI Voltage vs. Input Power –15 In some cases, it may be found that, if driven into AGC overload, the AD8368 requires unusually long times to recover; that is, the voltage at DETO remains at an abnormally high value, and the gain is at its lowest value. To avoid this situation, it is recommended that a clamp be placed on the DETO pin as shown in Figure 37. –20 –30 –40 05907-038 –25 –30 –20 –10 0 10 20 POWER IN (dBm) VPSI DECL DECL VPSI ICOM VPSI VPSO AD8368 VPSI +VS VPSO OCOM OCOM DETI ENBL DECL OUTP HPFL VPSI DETO CAGC 0.1µF C20 (pF) 2200 560 150 68 39 GAIN VAGC RB 0.5V A valuable feature of using a square law detector in AGC mode is that the RSSI voltage is a true reflection of signal power and may be converted to an absolute power measurement for any given source impedance. The RSSI in units of dBm referenced to 50 Ω and based on the voltage available on the DETO pin is given by Q1 2N2907 RA 05907-042 C4 (pF) 1000 270 68 33 15 INPT MODE Table 5. IF Frequency (MHz) 70 140 240 380 480 ICOM Note that to achieve the accurate level of AGC output power, the DECL capacitor must be adjusted for the corresponding RF frequency. The DECL capacitor value varies depending on board parasitics. Table 5 shows the DECL capacitor value based on the evaluation board parasitics. ICOM ICOM Figure 35. Output Power vs. Input Power in AGC Mode at 140 MHz Figure 37. External Clamp to Prevent AGC Overload The resistive divider network, RA and RB, should be designed such that the base of Q1 is driven to 0.5 V. RSSI = −11 + 20 log10(1 + R1/R2) + 38 × VDETO − 24.8 Rev. 0 | Page 15 of 20 AD8368 REF –4.9dBm SR 10kHz CF 100MHz 16 QAM MEAS SIGNAL CONST DIAG Figure 39 illustrates the measured EVM performance for a 16 QAM modulation at 10 Msymbols/s using CDETO = 1 nF. 10 9 8 7 EVM (%) The choice of CDETO is a compromise of averaging time constant, response time, and carrier leakage. If CDETO is selected to be too small to speed up the response time, the AGC loop could start tracking and leveling any amplitude envelope and corrupt the constellation. Figure 38 illustrates a 16 QAM, 100 ksymbols/s constellation with a degraded error vector magnitude (EVM) of 5%. By increasing CDETO to 0.01 μF, the EVM is improved to 1.1%. 1U 6 5 4 3 05907-041 2 1 0 –40 –30 –20 –10 0 10 POWER IN (dBm) 05907-040 Figure 39. Error Vector Magnitude Performance for 16 QAM 10 Msymbols/s –1U –1.31289U 262.578mU/ 1.31289U Figure 38. Degraded Error Vector Magnitude Performance for 16 QAM at 100 ksymbols/s(CDETO Too Small) Rev. 0 | Page 16 of 20 20 AD8368 EVALUATION BOARD VPOS C20 1nF VPSI VPSI DECL DECL VPSI OUTP ENBL OCOM R2 10kΩ GAIN GAIN JP4 DET_OUT_TP R35 OPEN OUTPUT C12 1nF VPOS3 C15 0.1µF R31 OPEN C23 10nF R32 OPEN C6 1nF C14 0.1µF R12 0Ω COUT 10nF VPOS2 OCOM C10 1nF C11 1nF VPSO DETI OFF AD8368 DECL ENABLE SW2 R11 0Ω VPSO MODE R10 0Ω ON VPSI HPFL C13 0.1µF ICOM DETO HI VPOS1 SW1 VPSI GAIN LOW INPT C1 OPEN C4 1nF R30 OPEN DET_IN 05907-043 R1 10kΩ ICOM CIN 10nF INPUT ICOM ICOM VPOS1 VPOS2 VPOS3 Figure 40. Table 6. Evaluation Board Configuration Options Component R1, R2 R10, R11, R12, C10, C11, C12, C13, C14, C15 CIN COUT R31, R32 R35 C23 C1, R30 C6 C20, C4 JP4 SW1 SW2 Function Pull-Down Resistors for Mode and Enable. Supply Decoupling. Jumpers, power supply decoupling resistors, and filter capacitors. RF Input. CIN provides dc block for RF input. RF Output. CIN provides dc block for RF output. Feedback Path for AGC Operation. For a default setpoint of 63 mV rms, set R31 = 0 Ω and remove R32. For other AGC setpoints, the rms voltage is determined from (1 + n) × 63 mV rms, where n = R31/R32. Populate with 0 Ω to feed detector output RSSI voltage to DET_OUT_TP. Sets the corner frequency of output offset control loop high-pass filter. Used for driving detector externally. Set R30 to 50 Ω for matching. Set C1 to be a large ac coupling cap. DETO Capacitor. Needs to be made larger for lower data rates (see the AGC Operation section). DECL Capacitor. Needs to be adjusted based on RF frequency in AGC operation (see the AGC Operation section). Jumper for AGC Mode of Operation. Provides feedback from the detector output to the gain pin. Mode Switch. LOW mode puts the part in gain down mode. HIGH puts the part in gain up mode. AGC operation requires gain down mode. Power-Down. The part is disabled when the enable pin is tied to ground. Rev. 0 | Page 17 of 20 Default Conditions R1 = R2 = 10 kΩ R10 = R11 = R12 = 0 Ω C10 = C11 = C12 = 1 nF C13 = C14 = C15 = 0.1 μF CIN = 10 nF COUT = 10 nF R31 = R32 = open (VGA mode) R35 = open C23 = 10 nF C1 = not populated R30 = not populated C6 = 1 nF C20 = C4 = 1 nF JP4 = not populated (VGA mode) SW1 = JP2 SW2 = JP3 AD8368 OUTLINE DIMENSIONS 0.60 MAX 4.00 BSC SQ PIN 1 INDICATOR 0.60 MAX TOP VIEW 0.50 BSC 3.75 BSC SQ 0.50 0.40 0.30 1.00 0.85 0.80 12° MAX SEATING PLANE 0.80 MAX 0.65 TYP 0.30 0.23 0.18 PIN 1 INDICATOR 19 18 24 1 2.65 2.50 SQ 2.35 EXPOSED PAD (BOTTOMVIEW) 13 12 7 6 0.23 MIN 2.50 REF 0.05 MAX 0.02 NOM 0.20 REF COPLANARITY 0.08 COMPLIANT TO JEDEC STANDARDS MO-220-VGGD-8 Figure 41. 24-Lead Lead Frame Chip Scale Package [LFCSP_VQ] 4 mm × 4 mm Body, Very Thin Quad (CP-24-4) Dimensions shown in millimeters ORDERING GUIDE Model AD8368ACPZ-REEL71 AD8368ACPZ-WP1, 2 AD8368-EVALZ1 1 2 Temperature Range −40°C to +85°C −40°C to +85°C Package Description 24-Lead Lead Frame Chip Scale Package (LFCSP_VQ) 24-Lead Lead Frame Chip Scale Package (LFCSP_VQ) Evaluation Board Z = Pb-free part. WP = Waffle pack. Rev. 0 | Page 18 of 20 Package Option CP-24-4 CP-24-4 Ordering Quantity 1500 64 AD8368 NOTES Rev. 0 | Page 19 of 20 AD8368 NOTES ©2006 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D05907-0-4/06(0) Rev. 0 | Page 20 of 20