5 –OUT 6 NC 7 –VS 8 INP 10kΩ 10kΩ AD8476 10195-001 +OUT 4 VOCM 3 +VS 2 10kΩ NOTES 1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN. 13 –VS 14 –VS 15 –VS Figure 1. 8-Lead MSOP INP 1 INP 2 INN 3 12 NC 10kΩ 10kΩ 11 –OUT AD8476 10kΩ 10 +OUT 10kΩ VOCM +VS 8 9 NOTES 1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN. 10195-002 INN 4 +VS 7 ADC driver Differential instrumentation amplifier building block Single-ended-to-differential converter Battery-powered instruments 10kΩ +VS 6 APPLICATIONS FUNCTIONAL BLOCK DIAGRAM INN 1 Very low power 330 μA supply current Extremely low harmonic distortion −126 HD2 at 10 kHz −128 HD3 at 10 kHz Fully differential or single-ended inputs/outputs Differential output designed to drive precision ADCs Drives switched capacitor and Σ-Δ ADCs Rail-to-rail outputs VOCM pin adjusts output common mode Robust overvoltage up to 18 V beyond supplies High performance Suitable for driving 16-bit converter up to 250 kSPS 39 nV/√Hz output noise 1 ppm/°C gain drift maximum 200 μV maximum output offset 10 V/μs slew rate 6 MHz bandwidth Single supply: 3 V to 18 V Dual supplies: ±1.5 V to ±9 V 16 –VS FEATURES +VS 5 Data Sheet Low Power, Unity Gain, Fully Differential Amplifier and ADC Driver AD8476 Figure 2. 16-Lead LFCSP GENERAL DESCRIPTION The AD8476 is a very low power, fully differential precision amplifier with integrated gain resistors for unity gain. It is an ideal choice for driving low power, high performance ADCs as a single-ended-to-differential or differential-to-differential amplifier. It provides a precision gain of 1, common-mode level shifting, low temperature drift, and rail-to-rail outputs for maximum dynamic range. The AD8476 also provides overvoltage protection from large industrial input voltages up to ±23 V while operating on a dual 5 V supply. Power dissipation on a single 5 V supply is only 1.5 mW. The AD8476 works well with SAR, Σ-Δ, and pipeline converters. The high current output stage of the part allows it to drive the switched capacitor front-end circuits of many ADCs with minimal error. Unlike many differential drivers on the market, the AD8476 is a high precision amplifier. With 200 µV maximum output offset, 39 nV/√Hz noise, and −102 dB THD + N at 10 kHz, the AD8476 pairs well with low power, high accuracy converters. Considering its low power consumption and high precision, the slew-enhanced AD8476 has excellent speed, settling to 16-bit precision for 250 kSPS acquisition times. The AD8476 is available in space-saving 16-lead, 3 mm × 3 mm LFCSP and 8-lead MSOP packages. It is fully specified over the −40°C to +125°C temperature range. Rev. B Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©2011–2012 Analog Devices, Inc. All rights reserved. AD8476 Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 Overview ..................................................................................... 17 Applications ....................................................................................... 1 Circuit Information .................................................................... 17 Functional Block Diagram .............................................................. 1 DC Precision ............................................................................... 17 General Description ........................................................................... 1 Input Voltage Range ................................................................... 18 Revision History ............................................................................... 2 Driving the AD8476................................................................... 18 Specifications..................................................................................... 3 Power Supplies ............................................................................ 18 Absolute Maximum Ratings ............................................................ 5 Applications Information .............................................................. 19 Thermal Resistance ...................................................................... 5 Typical Configuration ................................................................ 19 Maximum Power Dissipation ..................................................... 5 Single-Ended-to-Differential Conversion............................... 19 ESD Caution .................................................................................. 5 Setting the Output Common-Mode Voltage .......................... 19 Pin Configuration and Function Descriptions ............................. 6 Low Power ADC Driving .......................................................... 20 Typical Performance Characteristics ............................................. 8 Outline Dimensions ....................................................................... 21 Terminology .................................................................................... 16 Ordering Guide .......................................................................... 22 Theory of Operation ...................................................................... 17 REVISION HISTORY 5/12—Rev. A to Rev. B Added LFCSP Throughout.............................................................. 1 Added Harmonic Distortion Values to Features Section and Changed Bandwidth from 5 MHz to 6 MHz ................................ 1 Changed −3 dB Small Signal Bandwidth from 5 MHz to 6 MHz, Changed HD2 from −120 dB to −126 dB, and Changed HD3 from −122 dB to −128 dB, Table 1.................................................. 3 Changes to Figure 17 and Figure 19............................................. 10 Changes to Figure 25 ...................................................................... 11 Changes to Figure 30 ...................................................................... 12 Added Low Power ADC Driving Section ................................... 20 Updated Outline Dimensions ....................................................... 21 Changes to Ordering Guide .......................................................... 22 11/11—Rev. 0 to Rev. A Changes to Table 1 ............................................................................ 3 Changes to Typical Performance Characteristics ......................... 7 Added Figure 39; Renumbered Sequentially .............................. 13 Added Table 5.................................................................................. 18 Removed Low Power ADC Driving Section ............................... 19 Removed Figure 52 ......................................................................... 19 10/11—Revision 0: Initial Version Rev. B | Page 2 of 24 Data Sheet AD8476 SPECIFICATIONS VS = +5 to ±5 V, VOCM = midsupply, VOUT = V+OUT − V−OUT, RL = 2 kΩ differential, referred to output (RTO), TA = 25°C, unless otherwise noted. Table 1. Parameter DYNAMIC PERFORMANCE −3 dB Small Signal Bandwidth −3 dB Large Signal Bandwidth Slew Rate Settling Time to 0.01% Settling Time to 0.001% NOISE/DISTORTION 1 THD + N HD2 HD3 IMD3 Output Voltage Noise Spectral Noise Density GAIN Gain Error Gain Drift Gain Nonlinearity OFFSET AND CMRR Differential Offset 2 vs. Temperature Average TC vs. Power Supply (PSRR) Common-Mode Offset2 Common-Mode Rejection Ratio INPUT CHARACTERISTICS Input Voltage Range 3 Impedance 4 Single-Ended Input Differential Input Common-Mode Input OUTPUT CHARACTERISTICS Output Swing Output Balance Error Output Impedance Capacitive Load Short-Circuit Current Limit VOCM CHARACTERISTICS VOCM Input Voltage Range VOCM Input Impedance VOCM Gain Error Test Conditions/Comments Min B Grade Typ Max Min A Grade Typ Max Unit VOUT = 200 mV p-p VOUT = 2 V p-p VOUT = 2 V step VOUT = 2 V step VOUT = 2 V step 6 1 10 1.0 1.6 6 1 10 1.0 1.6 MHz MHz V/µs µs µs f = 10 kHz, VOUT = 2 V p-p, 22 kHz filter f = 10 kHz, VOUT = 2 V p-p f = 10 kHz, VOUT = 2 V p-p f1 = 95 kHz, f2 = 105 kHz, VOUT = 2 V p-p f = 0.1 Hz to 10 Hz f = 10 kHz −102 −102 dB −126 −128 −82 −126 −128 −82 dB dB dBc 6 39 1 6 39 1 µV p-p nV/√Hz V/V % ppm/°C ppm RL = ∞ −40°C ≤ TA ≤ +125°C VOUT = 4 V p-p 0.02 1 0.04 1 5 50 −40°C ≤ TA ≤ +125°C −40°C ≤ TA ≤ +125°C VS = ±2.5 V to ±9 V 90 VIN,cm = ±5 V 90 Differential input Single-ended input Vcm = VS/2 −VS + 0.05 2(−VS + 0.05) 1 5 200 900 4 50 1 90 50 50 80 +VS − 0.05 −VS + 0.05 2(+V − 0.05) 2(−VS + 0.05) 13.3 20 10 VS = +5 V VS = ±5 V ∆VOUT,cm/∆VOUT,dm −VS + 0.125 −VS + 0.155 90 +VS − 0.14 +VS − 0.18 −VS + 1 −VS + 0.125 −VS + 0.155 80 +VS − 1 V V +VS − 0.14 +VS − 0.18 dB Ω pF mA −VS + 1 +VS − 1 500 0.05 µV µV µV/°C dB µV dB kΩ kΩ kΩ 0.1 20 35 500 Rev. B | Page 3 of 24 +VS − 0.05 2(+VS − 0.05) 13.3 20 10 0.1 20 35 Per output 500 900 4 0.05 V kΩ % AD8476 Parameter POWER SUPPLY Specified Supply Voltage Operating Supply Voltage Range Supply Current Over Temperature TEMPERATURE RANGE Specified Performance Range Data Sheet Test Conditions/Comments Min B Grade Typ Max Min ±5 3 VS = +5 V, TA = 25°C VS = ±5 V, TA = 25°C −40°C ≤ TA ≤ +125°C −40 1 Includes amplifier voltage and current noise, as well as noise of internal resistors. Includes input bias and offset current errors. The input voltage range is a function of the voltage supplies and ESD diodes. 4 Internal resistors are trimmed to be ratio matched but have ±20% absolute accuracy. 2 3 Rev. B | Page 4 of 24 ±5 18 300 330 400 A Grade Typ Max 3 330 380 500 +125 300 330 400 −40 Unit 18 V V 330 380 500 μA μA μA +125 °C Data Sheet AD8476 ABSOLUTE MAXIMUM RATINGS THERMAL RESISTANCE Table 2. Parameter Supply Voltage Maximum Voltage at Any Input Pin Minimum Voltage at Any Input Pin Storage Temperature Range Specified Temperature Range Package Glass Transition Temperature (TG) ESD (Human Body Model) Rating ±10 V +VS + 18 V −VS – 18 V −65°C to +150°C −40°C to +125°C 150°C 2500 V Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. The θJA values in Table 3 assume a 4-layer JEDEC standard board with zero airflow. Table 3. Thermal Resistance Package Type 8-Lead MSOP 16-Lead LFCSP, 3 mm × 3 mm θJA 209.0 78.5 Unit °C/W °C/W MAXIMUM POWER DISSIPATION The maximum safe power dissipation for the AD8476 is limited by the associated rise in junction temperature (TJ) on the die. At approximately 150°C, which is the glass transition temperature, the properties of the plastic change. Even temporarily exceeding this temperature limit may change the stresses that the package exerts on the die, permanently shifting the parametric performance of the amplifiers. Exceeding a temperature of 150°C for an extended period may result in a loss of functionality. ESD CAUTION Rev. B | Page 5 of 24 AD8476 Data Sheet INN 1 +VS 2 VOCM 3 +OUT 4 8 INP 7 –VS 6 NC 5 –OUT AD8476 TOP VIEW (Not to Scale) NOTES 1. PINS LABELED NC CAN BE ALLOWED TO FLOAT, BUT IT IS BETTER TO CONNECT THESE PINS TO GROUND. AVOID ROUTING HIGH SPEED SIGNALS THROUGH THESE PINS BECAUSE NOISE COUPLING MAY RESULT. Figure 3. 8-Lead MSOP Pin Configuration Table 4. 8-Lead MSOP Pin Function Descriptions Pin No. 1 2 3 4 5 6 7 8 Mnemonic INN +VS VOCM +OUT −OUT NC −VS INP Description Negative Input . Positive Supply. Output Common-Mode Adjust. Noninverting Output. Inverting Output. This pin is not connected internally (see Figure 3). Negative Supply. Positive Input. Rev. B | Page 6 of 24 10195-004 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS 13 –VS 14 –VS 15 –VS AD8476 16 –VS Data Sheet INP 1 12 NC INP 2 AD8476 INN 3 TOP VIEW (Not to Scale) 11 –OUT INN 4 10 +OUT NOTES 1. PINS LABELED NC CAN BE ALLOWED TO FLOAT, BUT IT IS BETTER TO CONNECT THESE PINS TO GROUND. AVOID ROUTING HIGH SPEED SIGNALS THROUGH THESE PINS BECAUSE NOISE COUPLING MAY RESULT. 2. SOLDER THE EXPOSED PADDLE ON THE BACK OF THE PACKAGE TO A GROUND PLANE. 10195-003 +VS 8 +VS 7 +VS 6 +VS 5 9 VOCM Figure 4. 16-Lead LFCSP Pin Configuration Table 5. 16-Lead LFCSP Pin Function Descriptions Pin No. 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 Mnemonic INP INP INN INN +VS +VS +VS +VS VOCM +OUT −OUT NC −VS −VS −VS −VS EPAD Description Positive Input. Positive Input. Negative Input. Negative Input . Positive Supply. Positive Supply. Positive Supply. Positive Supply. Output Common-Mode Adjust. Noninverting Output. Inverting Output. This pin is not connected internally (see Figure 4). Negative Supply. Negative Supply. Negative Supply. Negative Supply. Solder the exposed paddle on the back of the package to a ground plane. Rev. B | Page 7 of 24 AD8476 Data Sheet TYPICAL PERFORMANCE CHARACTERISTICS VS = +5 V, G = 1, VOCM connected to 2.5 V, RL = 2 kΩ differentially, TA = 25°C, referred to output (RTO), unless otherwise noted. 50 15 NORMALIZED TO 25°C 40 VS = ±5V 10 COMMON-MODE VOLTAGE (V) 30 CMRR (µV/V) 20 10 0 –10 –20 –30 VS = ±2.5V 5 0 –5 –10 –25 –10 5 20 35 50 65 80 95 110 125 TEMPERATURE (°C) –15 –15 10195-005 –50 –40 0 5 10 15 Figure 8. Input Common-Mode Voltage vs. Output Voltage, VS = ±5 V and ±2.5 V 1500 115 VS = ±5V VS = +5V NORMALIZED TO 25°C 110 1100 900 105 700 100 500 300 CMRR (dB) 100 –100 –300 –500 95 90 85 80 –700 –900 75 –1100 70 –1300 –25 –10 5 20 35 50 65 80 95 110 125 TEMPERATURE (°C) 65 10 10195-006 –1500 –40 100 1k 10k 100k 1M FREQUENCY (Hz) 10195-010 OFFSET VOLTAGE (µV) –5 OUTPUT VOLTAGE (V) Figure 5. CMRR vs. Temperature 1300 –10 10195-008 –40 Figure 9. Common-Mode Rejection vs. Frequency Figure 6. System Offset Temperature Drift –20 150 VS = ±5V NORMALIZED TO 25°C VS = +5V –30 100 PSRR (dB) 0 –50 –60 –70 –50 –80 –100 –150 –40 –25 –10 5 20 35 50 65 80 TEMPERATURE (°C) 95 110 125 Figure 7. Gain Error vs. Temperature –100 100 1k 10k 100k 1M FREQUENCY (Hz) Figure 10. Power Supply Rejection vs. Frequency Rev. B | Page 8 of 24 10M 10195-011 –90 10195-007 GAIN ERROR (µV/V) –40 50 Data Sheet AD8476 50 2kΩ LOAD NO LOAD 18 45 16 40 VS = ±5V 14 35 CURRENT (mA) 12 10 8 30 25 20 6 VS = ±2.5V 15 4 1k 10k 100k 1M 10M FREQUENCY (Hz) 5 –40 10195-012 0 100 OUTPUT VOLTAGE SWING (V) REFERRED TO SUPPLY VOLTAGES 10195-013 OUTPUT VOLTAGE SWING (V) REFERRED TO SUPPLY VOLTAGES –55°C –40°C +25°C +85°C +125°C 100k 5 20 35 50 65 80 95 110 125 Figure 14. Short-Circuit Current vs. Temperature +VS 0.025 0.050 0.075 0.100 0.125 0.150 0.175 10k –10 TEMPERATURE (°C) Figure 11. Maximum Output Voltage vs. Frequency 0.175 0.150 0.125 0.100 0.075 0.050 0.025 –VS 1k –25 1M RLOAD (Ω) +VS 0.025 0.050 0.075 0.100 0.125 0.150 0.175 –55°C –40°C +25°C +85°C +125°C 0.175 0.150 0.125 0.100 0.075 0.050 0.025 –VS 10µA 100µA 1mA 10mA CURRENT (A) Figure 15. Output Voltage Swing vs. Load Current vs. Temperature, VS = ±5 V Figure 12. Output Voltage Swing vs. RLOAD vs. Temperature, VS = ±5 V 15 VIN 14 VOUT 12 2V/DIV 11 RISE 9 8 FALL 7 5 –40 –25 –10 5 20 35 50 65 80 TEMPERATURE (°C) 95 110 125 2µs/DIV Figure 16. Overdrive Recovery, VS = +5 V Figure 13. Slew Rate vs. Temperature Rev. B | Page 9 of 24 10195-051 6 10195-015 SLEW RATE (V/µS) 13 10 10195-016 10 2 10195-014 MAXIMUM OUTPUT VOLTAGE (V p-p) 20 Data Sheet 10 10 5 5 0 0 –5 –5 –10 –10 –15 –15 GAIN (dB) –20 –25 –25 –30 –30 –35 –35 –40 –50 100 VS = ±5V VS = +5V 1k –45 10k 100k 1M 10M FREQUENCY (Hz) –50 100 10195-017 –45 10 5 5 0 100k 1M 10M 0 OUTPUT MAGNITUDE (dB) –5 –10 –15 –20 –25 –30 –35 1k –5 –10 –15 –20 –25 –30 RL = 10kΩ RL = 2kΩ RL = 200Ω –35 10k 100k 1M 10M FREQUENCY (Hz) –40 100 10195-018 –50 100 10k Figure 20. Large Signal Frequency Response for Various Supplies 10 –45 1k FREQUENCY (Hz) Figure 17. Small Signal Frequency Response for Various Supplies –40 VS = ±5V VS = +5V 10195-020 –40 GAIN (dB) –20 RL = 10kΩ RL = 2kΩ RL = 200Ω 1k 10k 100k 1M 10M FREQUENCY (Hz) Figure 18. Small Signal Frequency Response for Various Loads 10195-021 GAIN (dB) AD8476 Figure 21. Large Signal Frequency Response for Various Loads 10 10 5 5 0 OUTPUT MAGNITUDE (dB) –10 –15 –20 –25 –30 –35 –45 –50 100 –5 –10 –15 –20 –25 –30 CL = 5pF CL = 10pF CL = 15pF 1k –35 10k 100k FREQUENCY (Hz) 1M 10M –40 100 Figure 19. Small Signal Frequency Response for Various Capacitive Loads CL = 5pF CL = 10pF CL = 15pF 1k 10k 100k FREQUENCY (Hz) 1M 10M 10195-101 –40 10195-019 OUTPUT MAGNITUDE (dB) 0 –5 Figure 22. Large Signal Frequency Response for Various Capacitive Loads Rev. B | Page 10 of 24 Data Sheet AD8476 5 5 0 –10 –15 –20 –25 1k VOCM = 1.0V VOCM = 2.5V VOCM = 4.0V 10k –10 –15 –20 –25 –30 100k 1M 10M FREQUENCY (Hz) Figure 23. Small Signal Frequency Response for Various VOCM Levels –35 1k 100k 1M 10M Figure 26. Large Signal Frequency Response for Various VOCM Level 5 POSITIVE OUTPUT (2kΩ LOAD) NEGATIVE OUTPUT (2kΩ LOAD) VS = 5V POSITIVE OUTPUT NEGATIVE OUTPUT OUTPUT MAGNITUDE (dB) 0 –5 –10 –15 –20 –25 –5 –10 –15 –20 10k 100k 1M 10195-056 –25 10M VOCM INPUT FREQUENCY (Hz) –30 1k 10k 100k 1M VOCM INPUT FREQUENCY (Hz) Figure 24. VOCM Small Signal Frequency Response Figure 27. VOCM Large Signal Frequency Response VS = ±5V VS = +5V VS = +3V 10195-029 500ns/DIV 500ns/DIV Figure 28. Large Signal Pulse Response for Various Supplies Figure 25. Small Signal Pulse Response for Various Supplies Rev. B | Page 11 of 24 10195-032 500mV/DIV VS = ±5V VS = +5V VS = +3V 50mV/DIV OUTPUT MAGNITUDE (dB) 10k FREQUENCY (Hz) 0 –30 1k CL = 5pF CL = 10pF CL = 15pF 10195-055 5 –5 10195-027 OUTPUT MAGNITUDE (dB) –5 10195-024 OUTPUT MAGNITUDE (dB) 0 AD8476 Data Sheet RL = 10kΩ RL = 2kΩ RL = 200Ω 500ns/DIV 10195-033 10195-031 50mV/DIV 500mV/DIV RL = 10kΩ RL = 2kΩ RL = 200Ω 500ns/DIV Figure 29. Small Signal Step Response for Various Resistive Loads, VS = ±5 V Figure 32. Large Signal Step Response for Various Resistive Loads, VS = ±5 V CL = 0pF CL = 5pF CL = 10pF 500ns/DIV Figure 33. Large Signal Step Response for Various Capacitive Loads, VS = ±5 V 10µs/DIV Figure 34. VOCM Large Signal Step Response Figure 31. VOCM Small Signal Step Response Rev. B | Page 12 of 24 10195-038 500ns/DIV 10195-035 20mV/DIV 500mV/DIV Figure 30. Small Signal Step Response for Various Capacitive Loads, VS = ±5 V 10195-034 500ns/DIV 10195-030 50mV/DIV 500mV/DIV CL = 0pF CL = 5pF CL = 10pF Data Sheet AD8476 140 2.5 130 SPECTRAL NOISE DENSITY (nV/ Hz) 3.0 1.5 1.0 0.5 0 –0.5 –1.0 –1.5 –2.0 120 110 100 90 80 70 60 50 40 10 20 30 40 50 60 70 80 90 100 TIME (Seconds) 20 1 –20 RL = NO LOAD RL = NO LOAD RL = 2kΩ LOAD RL = 2kΩ LOAD HARMONIC DISTORTION (dBc) –40 –50 –60 –70 –80 –90 –100 –110 –70 –80 –90 –100 –110 –120 –130 10k 100k 1M FREQUENCY (Hz) –140 100 –40 –50 –20 HD2 (VS = ±5V, RL = 2kΩ) HD3 (VS = ±5V, RL = 2kΩ) HD2 (VS = +5V, RL = 2kΩ) HD3 (VS = +5V, RL = 2kΩ) –30 100k 1M HD2, HD3, VS = 5V VS = 5V 1 2 –40 –60 –70 –80 –90 –100 –110 –120 –50 –60 –70 –80 –90 –100 –110 –120 –130 –130 1k 10k 100k 1M FREQUENCY (Hz) 10195-042 –140 100 10k Figure 39. Harmonic Distortion vs. Frequency at Various VOUT,dm HARMONIC DISTORTION (dBc) –30 1k FREQUENCY (Hz) Figure 36. Harmonic Distortion vs. Frequency at Various Loads HARMONIC DISTORTION (dBc) –60 –130 1k 100k –50 –120 –140 100 10k HD2 (VOUT = 4V p-p) HD3 (VOUT = 4V p-p) HD2 (VOUT = 2V p-p) HD3 (VOUT = 2V p-p) –30 10195-040 HARMONIC DISTORTION (dBc) –40 1k Figure 38. Voltage Noise Density vs. Frequency –20 –30 100 FREQUENCY (Hz) Figure 35. 0.1 Hz to 10 Hz Voltage Noise HD2, HD3, HD2, HD3, 10 10195-046 0 10195-039 –3.0 10195-036 30 –2.5 Figure 37. Harmonic Distortion vs. Frequency at Various Supplies –140 0 3 4 5 6 7 8 9 VOUT (V p-p) Figure 40. Harmonic Distortion vs. VOUT,dm, f = 10 kHz Rev. B | Page 13 of 24 10 10195-047 OUTPUT VOLTAGE (µV) 2.0 Data Sheet 0 –40 ERROR (ppm) –50 –60 –70 –80 –90 –100 –110 –120 –140 100 1k 10k 100k 1M FREQUENCY (Hz) 10195-139 –130 –20 SPURIOUS-FREE DYNAMCIC RANGE (dBc) VOUT = 2V p-p VOUT = 4V p-p VOUT = 8V p-p –95 –100 –105 –110 1k 10k 100k FREQUENCY (Hz) 10195-053 –115 –30 0.2 0.4 0.6 0.8 1.0 VS = 5V, RL = 2kΩ VS = 5V, RL = NO LOAD –40 –50 –60 –70 –80 –90 –100 –110 –120 –130 –140 100 1k 10k 100k 1M FREQUENCY (Hz) Figure 45. Spurious-Free Dynamic Range vs. Frequency at Various Loads Figure 42. Total Harmonic Distortion + Noise vs. Frequency 1V/DIV 1V/DIV 20µV/DIV 0.001%/DIV 200µV/DIV 0.01%/DIV 1µs/DIV 10195-037 THD + N (dB) –90 100 0 Figure 44. Gain Nonlinearity –80 –120 10 –0.2 OUTPUT VOLTAGE (V) Figure 41. Harmonic Distortion vs. Input Drive –85 –0.4 10195-049 –30 2µs/DIV Figure 46. Settling Time to 0.001% of 2 V Step Figure 43. Settling Time to 0.01% of 2 V Step Rev. B | Page 14 of 24 10195-100 –20 HARMONIC DISTORTION (dBc) 40 VS = ±5V 35 30 25 20 15 10 5 0 –5 –10 –15 –20 –25 –30 –35 –40 –1.0 –0.8 –0.6 HD2 (SINGLE-ENDED INPUT) HD3 (SINGLE-ENDED INPUT) HD2 (DIFFERENTIAL INPUT) HD3 (DIFFERENTIAL INPUT) –10 10195-200 AD8476 Data Sheet AD8476 –30 1k POSITIVE OUTPUT NEGATIVE OUTPUT 100 –50 IMPEDANCE (Ω) OUTPUT BALANCE ERROR (dB) –40 –60 –70 –80 10 1 1k 10k 100k 1M 10M FREQUENCY (Hz) Figure 47. Output Balance Error vs. Frequency –10 –20 –30 –40 –50 –60 –70 –80 –90 90 95 100 105 110 FREQUENCY (Hz) 115 120 10195-054 NORMALIZED SPECTRUM (dBc) 0 85 100k 1M FREQUENCY (Hz) Figure 49. Output Impedance vs. Frequency 10 –100 80 0.1 10k Figure 48. 100 kHz Intermodulation Distortion Rev. B | Page 15 of 24 10M 10195-052 –100 100 10195-050 –90 AD8476 Data Sheet TERMINOLOGY Common-Mode Voltage Common-mode voltage refers to the average of two node voltages with respect to the local ground reference. The output commonmode voltage is defined as 10kΩ 10kΩ VOCM –IN –OUT RL, dm VOUT, dm AD8476 10kΩ VOUT, cm = (V+OUT + V−OUT)/2 +OUT 10kΩ 10195-057 +IN Figure 50. Signal and Circuit Definitions Differential Voltage Differential voltage refers to the difference between two node voltages. For example, the output differential voltage (or equivalently, output differential mode voltage) is defined as VOUT, dm = (V+OUT − V−OUT) where V+OUT and V−OUT refer to the voltages at the +OUT and −OUT terminals with respect to a common ground reference. Similarly, the differential input voltage is defined as Balance Output balance is a measure of how close the output differential signals are to being equal in amplitude and opposite in phase. Output balance is most easily determined by placing a wellmatched resistor divider between the differential voltage nodes and comparing the magnitude of the signal at the divider midpoint with the magnitude of the differential signal. By this definition, output balance is the magnitude of the output common-mode voltage divided by the magnitude of the output differential mode voltage. VIN, dm = (V+IN − V−IN) Rev. B | Page 16 of 24 Output Balance Error = ∆VOUT , cm ∆VOUT , dm Data Sheet AD8476 THEORY OF OPERATION OVERVIEW The AD8476 is a fully differential amplifier, with integrated lasertrimmed resistors, that provides a precision gain of 1. The internal differential amplifier of the AD8476 differs from conventional operational amplifiers in that it has two outputs whose voltages are equal in magnitude, but move in opposite directions (180° out of phase). 5 –OUT DC PRECISION The dc precision of the AD8476 is highly dependent on the accuracy of its integrated gain resistors. Using superposition to analyze the circuit shown in Figure 52, the following equation shows the relationship between the input and output voltages of the amplifier: 1 (2RP RN + RP + RN ) 2 1 = VOUT ,cm (RP − RN ) + VOUT ,dm (2 + RP + RN ) 2 VIN ,cm (RP − RN ) + VIN ,dm where: RP = 10kΩ 10kΩ 10kΩ VIN ,dm = VP − VN AD8476 1 VIN ,cm = (VP + VN ) 2 The differential closed-loop gain of the amplifier is +OUT 4 NOTES 1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN. VOUT ,dm 10195-058 VOCM 3 +VS 2 10kΩ INN 1 RFN RFP , RN = RGN RGP VIN ,dm = 2RP RN + RP + RN 2 + RP + RN and the common rejection of the amplifier is Figure 51. Block Diagram VOUT ,dm CIRCUIT INFORMATION VIN ,cm The AD8476 amplifier uses a voltage feedback topology; therefore, the amplifier exhibits a nominally constant gain bandwidth product. Like a voltage feedback operational amplifier, the AD8476 also has high input impedance at its internal input terminals (the summing nodes of the internal amplifier) and low output impedance. = 2(RP − RN ) 2 + RP + RN VP RGP RFP VON VOCM VOP The AD8476 employs two feedback loops, one each to control the differential and common-mode output voltages. The differential feedback loop, which is fixed with precision laser-trimmed on-chip resistors, controls the differential output voltage. Output Common-Mode Voltage (VOCM) The internal common-mode feedback controls the commonmode output voltage. This architecture makes it easy for the user to set the output common-mode level to any arbitrary value independent of the input voltage. The output commonmode voltage is forced by the internal common-mode feedback loop to be equal to the voltage applied to the VOCM input. The VOCM pin can be left unconnected, and the output commonmode voltage self-biases to midsupply by the internal feedback control. VN RGN RFN 10195-059 6 NC 8 INP 7 –VS The AD8476 is designed to greatly simplify single-ended-todifferential conversion, common-mode level shifting and precision driving of differential signals into low power, differential input ADCs. The VOCM input allows the user to set the output common-mode voltage to match with the input range of the ADC. Like an operational amplifier, the VOCM function relies on high open-loop gain and negative feedback to force the output nodes to the desired voltages. Due to the internal common-mode feedback loop and the fully differential topology of the amplifier, the AD8476 outputs are precisely balanced over a wide frequency range. This means that the amplifier’s differential outputs are very close to the ideal of being identical in amplitude and exactly 180° out of phase. Figure 52. Functional Circuit Diagram of the AD8476 at a Given Gain The preceding equations show that the gain accuracy and the common-mode rejection (CMRR) of the AD8476 are determined primarily by the matching of the feedback networks (resistor ratios). If the two networks are perfectly matched, that is, if RP and RN equal RF/RG, then the resistor network does not generate any CMRR errors and the differential closed loop gain of the amplifier reduces to Rev. B | Page 17 of 24 v OUT ,dm v IN ,dm = RF RG AD8476 Data Sheet DRIVING THE AD8476 The AD8476 integrated resistors are precision wafer-lasertrimmed to guarantee a minimum CMRR of 90 dB (32 μV/V), and gain error of less that 0.02%. To achieve equivalent precision and performance using a discrete solution, resistors must be matched to 0.01% or better. Care should be taken to drive the AD8476 with a low impedance source: for example, another amplifier. Source resistance can unbalance the resistor ratios and, therefore, significantly degrade the gain accuracy and common-mode rejection of the AD8476. For the best performance, source impedance to the AD8476 input terminals should be kept below 0.1 Ω. Refer to the DC Precision section for details on the critical role of resistor ratios in the precision of the AD8476. INPUT VOLTAGE RANGE The AD8476 can measure input voltages as large as the supply rails. The internal gain and feedback resistors form a divider, which reduces the input voltage seen by the internal input nodes of the amplifier. The largest voltage that can be measured properly is constrained by the output range of the amplifier and the capability of the amplifier’s internal summing nodes. This voltage is defined by the input voltage, and the ratio between the feedback and the gain resistors. POWER SUPPLIES The AD8476 operates over a wide range of supply voltages. It can be powered on a single supply as low as 3 V and as high as 18 V. The AD8476 can also operate on dual supplies from ±1.5 V to ±9 V Figure 53 shows the voltage at the internal summing nodes of the amplifier, defined by the input voltage and internal resistor network. If VN is grounded, the expression shown reduces to VPLUS = V MINUS = A stable dc voltage should be used to power the AD8476. Note that noise on the supply pins can adversely affect performance. For more information, see the PSRR performance curve in Figure 10. RG 1 RF VP VOCM + RF + RG 2 RG Place a bypass capacitor of 0.1 μF between each supply pin and ground, as close as possible to each supply pin. Use a tantalum capacitor of 10 μF between each supply and ground. It can be farther away from the supply pins and, typically, it can be shared by other precision integrated circuits. The internal amplifier of the AD8476 has rail-to-rail inputs. To obtain accurate measurements with minimal distortion, the voltage at the internal inputs of the amplifier must stay below +VS − 1 V and above −VS. The AD8476 provides overvoltage protection for excessive input voltages beyond the supply rails. Integrated ESD protection diodes at the inputs prevent damage to the AD8476 up to +VS + 18 V and −VS − 18 V. VP RF + RG VOCM + 1 RF 2 RG VP − VN + RF RF + RG RF VON VN VOCM VOP VN RG RF Figure 53. Voltages at the Internal Op Amp Inputs of the AD8476 Rev. B | Page 18 of 24 10195-060 RG RG Data Sheet AD8476 APPLICATIONS INFORMATION TYPICAL CONFIGURATION The AD8476 is designed to facilitate single-ended-to-differential conversion, common-mode level shifting, and precision processing of signals so that they are compatible with low voltage ADCs. Figure 54 shows a typical connection diagram of the AD8476. SINGLE-ENDED-TO-DIFFERENTIAL CONVERSION Many industrial systems have single-ended inputs from input sensors; however, the signals are frequently processed by high performance differential input ADCs for higher precision. The AD8476 performs the critical function of precisely converting single-ended signals to the differential inputs of precision ADCs, and it does so with no need for external components. To convert a single-ended signal to a differential signal, connect one input to the signal source and the other input to ground (see Figure 54). Note that either input can be driven by the source with the only effect being that the outputs have reversed polarity. The AD8476 also accepts truly differential input signals in precision systems with differential signal paths. SETTING THE OUTPUT COMMON-MODE VOLTAGE The VOCM pin of the AD8476 is internally biased by a precision voltage divider comprising of two 1 MΩ resistors between the supplies. This divider level shifts the output to midsupply. Relying on the internal bias results in an output common-mode voltage that is within 0.05% of the expected value. Table 6. Differential Input ADCs1 –OUT 5 7 6 NC –VS 10µF 10kΩ –VOUT AD8476 LOAD +VOUT 0.1µF 10µF 4 +OUT VOCM 3 +VS INN 1 2 10kΩ + +5V 10195-102 10kΩ 10kΩ Resolution Throughput Rate Power Dissipation 16 Bits 100 kSPS 25 mW 16 Bits 100 kSPS 6 mW 16 Bits 250 kSPS 12.5 mW 16 Bits 500 kSPS* 21.5 mW Depending on measurement/application type, check that the AD8476 meets settling time requirements. + INP It is also possible to connect the VOCM input to the commonmode level output of an ADC; however, care must be taken to ensure that the output has sufficient drive capability. The input impedance of the VOCM pin is 500 kΩ. If multiple AD8476 devices share one ADC reference output, a buffer may be necessary to drive the parallel inputs. 1 0.1µF 8 Because of the internal divider, the VOCM pin sources and sinks current, depending on the externally applied voltage and its associated source resistance. ADC AD7674 AD7684 AD7687 AD7688 –5V INPUT SIGNAL SOURCE In cases where control of the output common-mode level is desired, an external source or resistor divider can be used to drive the VOCM pin. If driven directly from a source, or with a resistor divider of unequal resistor values, the resistance seen by the VOCM pin should be less than 1 kΩ. If an external voltage divider consisting of equal resistor values is used to set VOCM to midsupply, higher values can be used because the external resistors are placed in parallel with the internal resistors. The output common-mode offset listed in the Specifications section assumes that the VOCM input is driven by a low impedance voltage source. Figure 54. Typical Configuration—8-Lead MSOP Rev. B | Page 19 of 24 AD8476 Data Sheet frequency (see Figure 49). This higher output impedance yields slower settling, thus be certain to choose your capacitance so that the filter still meets the settling requirement at the maximum frequency of interest. LOW POWER ADC DRIVING The AD8476 is designed to be a low power driver for ADCs with up to 16-bit precision and sampling rates of up to 250 kSPS. The circuit in Figure 56 shows the AD8476 driving the AD7687, a 16-bit, 250 kSPS fully differential SAR ADC. The filter between the AD8476 and the ADC reduces high frequency noise and reduces switching transients from the sampling of the ADC. In the application shown, a 100 Ω resistors and 2.2 nF capacitors at each output were chosen. For driving the AD7687, this combination yields an SNR loss of 2.5 dB and good THD performance for a 20 kHz fundamental frequency, with an ADC throughput rate of 250kSPS. The filter bandwidth can be determined by the following equation: ADC FULL SCALE (dB) Filter Frequency Additional considerations help determine the values of the individual components. THD of the ADC is likely to increase with source resistance. This is stated in the ADC data sheet. To reduce this effect, try to use smaller resistance and larger capacitance. Large capacitance values much greater than 2 nF are hard for the amplifier to drive. Higher capacitance also increases the effect of changes in output impedance. 0 –10 –20 –30 –40 –50 –60 –70 –80 –90 –100 –110 –120 –130 –140 –150 –160 –170 –180 1 2RC VIN = 8V p-p THD = –112dB SNR = 93dB 0 20 40 60 80 100 Figure 55. FFT of AD8476 Driving the AD7687 +4.5V 4V +2.5V +5V +0.5V +VS 4V –OUT 4V –IN –VS +OUT VOCM VIO IN– SDI 2.2nF AD8476 +4V +1.8V TO +5V VDD 100Ω +IN 0V +2V +2.5V AD7687 2.2nF REF +4.5V 0V 4V SDO CNV IN+ 100Ω SCK GND +5V +2.5V +0.5V Figure 56. AD8476 Conditioning and Level Shifting a Differential Voltage to Drive Single-Supply ADC Rev. B | Page 20 of 24 10195-063 +4V +2V 120 FREQUENCY (kHz) It is also important to consider the signal frequency range of interest. The AD8476 THD decreases with higher frequency (see Figure 42) and output impedance increases with higher 140 10195-064 Choose the values of this filter with care. Optimal values for the filter may need to be determined empirically, but the guidelines discussed herein are provided to help the user. For optimum performance, this filter should be fast enough to settle full-scale to 0.5 LSB of the ADC within the acquisition time specified in the ADC data sheet, in this case, the AD7687. If the filter is slower than the acquisition time, distortion can result that looks like harmonics. If the filter is too fast, the noise bandwidth of the amplifier increases, thereby reducing the SNR of your system. Data Sheet AD8476 OUTLINE DIMENSIONS 3.20 3.00 2.80 8 3.20 3.00 2.80 1 5.15 4.90 4.65 5 4 PIN 1 IDENTIFIER 0.65 BSC 0.95 0.85 0.75 15° MAX 1.10 MAX 0.80 0.55 0.40 0.23 0.09 6° 0° 0.40 0.25 10-07-2009-B 0.15 0.05 COPLANARITY 0.10 COMPLIANT TO JEDEC STANDARDS MO-187-AA Figure 57. 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters 0.27 0.20 0.15 0.50 BSC 13 PIN 1 INDICATOR 16 1 12 EXPOSED PAD 1.75 1.60 SQ 1.45 9 TOP VIEW 0.80 0.75 0.70 SEATING PLANE 0.50 0.40 0.30 4 8 5 0.20 MIN BOTTOM VIEW 0.05 MAX 0.02 NOM COPLANARITY 0.08 0.20 REF FOR PROPER CONNECTION OF THE EXPOSED PAD, REFER TO THE PIN CONFIGURATION AND FUNCTION DESCRIPTIONS SECTION OF THIS DATA SHEET. COMPLIANT TO JEDEC STANDARDS MO-229-WEEE. Figure 58. 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ] 3 mm × 3 mm Body, Very Very Thin Quad (CP-16-25) Dimensions shown in millimeters Rev. B | Page 21 of 24 01-28-2010-B PIN 1 INDICATOR 3.10 3.00 SQ 2.90 AD8476 Data Sheet ORDERING GUIDE Model 1 AD8476BCPZ-R7 AD8476BCPZ-RL AD8476BCPZ-WP AD8476ACPZ-R7 AD8476ACPZ-RL AD8476ACPZ-WP AD8476BRMZ AD8476BRMZ-R7 AD8476BRMZ-RL AD8476ARMZ AD8476ARMZ-R7 AD8476ARMZ-RL AD8476-EVALZ 1 Temperature Range −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C Package Description 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ] 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ] 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ] 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ] 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ] 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ] 8-Lead Mini Small Outline Package [MSOP] 8-Lead Mini Small Outline Package [MSOP] 8-Lead Mini Small Outline Package [MSOP] 8-Lead Mini Small Outline Package [MSOP] 8-Lead Mini Small Outline Package [MSOP] 8-Lead Mini Small Outline Package [MSOP] Evaluation Board Z = RoHS Compliant Part. Rev. B | Page 22 of 24 Package Option CP-16-25 CP-16-25 CP-16-25 CP-16-25 CP-16-25 CP-16-25 RM-8 RM-8 RM-8 RM-8 RM-8 RM-8 Branding Y45 Y45 Y45 Y44 Y44 Y44 Y47 Y47 Y47 Y46 Y46 Y46 Data Sheet AD8476 NOTES Rev. B | Page 23 of 24 AD8476 Data Sheet NOTES ©2011–2012 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D10195-0-5/12(B) Rev. B | Page 24 of 24