Cirrus CS5501-BP Non-aliasing, 16- & 20-bit a/d converter Datasheet

CS5501
CS5501
CS5503
CS5503
16 & 20-Bit
Converter
Non-aliasing,
16- & A/D
20-bit
A/D Converters
Features
I
Description
Monolithic CMOS ADC with Filtering
The CS5501 and CS5503 are CMOS A/D converters
ideal for measuring low-frequency signals representing
physical, chemical, and biological processes. They utilize charge-balance techniques to achieve 16-bit
(CS5501) and 20-bit (CS5503) performance with up to 4
kSps word rates.
- 6-pole, Low-pass Gaussian Filter
Up to 4 kHz Output Word Rates
- On Chip Self-calibration Circuitry
- Linearity Error: ±0.0003%
- Differential Nonlinearity:
CS5501: 16-bit, No Missing Codes
(DNL ±1/8 LSB)
CS5503: 20-bit, No Missing Codes
The converters continuously sample at a rate set by the
user in the form of either a CMOS clock or a crystal. Onchip digital filtering processes the data and updates the
output register at up to a 4 kSps rate. The converters' lowpass, 6-pole Gaussian response filter is designed to allow corner frequency settings from 0.1 Hz to 10 Hz in the
CS5501 and 0.5 Hz to 10 Hz in the CS5503. Thus, each
converter rejects 50 Hz and 60 Hz line frequencies as
well as any noise at spurious frequencies.
System Calibration Capability
Flexible Serial Communications Port
- Microcontroller-compatible Formats
- 3-state Data and Clock Outputs
- UART Format (CS5501 only)
Pin-selectable Unipolar/Bipolar Ranges
Low Power Consumption: 25 mW
- 10 µW Sleep Mode for Portable Applications
The CS5501 and CS5503 include on-chip self-calibration circuitry which can be initiated at any time or
temperature to insure offset and full-scale errors of typically less than 1/2 LSB for the CS5501 and less than
4 LSB for the CS5503. The devices can also be applied
in system calibration schemes to null offset and gain errors in the input channel.
Each device's serial port offers two general purpose
modes of operation for direct interface to shift registers
or synchronous serial ports of industry-standard microcontrollers. In addition, the CS5501's serial port offers a
third, UART-compatible mode of asynchronous
communication.
ORDERING INFORMATION
See page 33.
I
BP/UP SLEEP
BP/UPSLEEP
12
CS550112
11
SC1
SC2
SC1 4 SC2 17
4
13
CS5503
Calibration
Calibration
CAL
Calibration
Calibration
SRAM
Microcontroller13 CAL
Microcontroller
SRAM
14 14
10
VA+ VA+
Charge-balanced A/D Converter
VREF
10
Charge-Balanced A/D Converter
7
7
VREF
VAAnalog
6-pole Gaussian
VA9
Digital Filter 15
Analog Modulator 6-PoleLow-pass
Gaussian
VD+
9
AIN
15
AIN
Modulator
Low-Pass Digital Filter
6 VD- VD+
6
8
VDAGND
AGND 8
20
20
Clock Generator
Serial
Interface
Logic
SDATA
Clock Generator Serial Interface Logic
SDATA
DGND5 5
DGND
2 18 18
1
19
23
3
16 116
19
CLKIN
CLKOUT
CS MODE SCLK
CLKOUTCLKIN
DRDYDRDY
CS MODESCLK
Cirrus Logic, Inc.
www.cirrus.com
http://www.cirrus.com
11
Copyright
 Cirrus
Logic,
2003
Copyright
© Cirrus
Logic,
Inc.Inc.
2005
Rights
Reserved)
(All(All
Rights
Reserved)
SEP ‘04
AUG
‘05
DS31F4
DS31F5
1
CS5501 CS5503
CS5501/CS5503
CS5501 ANALOG CHARACTERISTICS (TA = TMIN to TMAX; VA+, VD+ = 5V;
VA-, VD- = -5V; VREF = 2.5V; CLKIN = 4.096MHz; Bipolar Mode; MODE = +5V; Rsource = 750Ω with a 1nF
to AGND at AIN (see Note 1); Digital Inputs: Logic 0 = GND; Logic 1 = VD+; unless otherwise specified.)
CS5501-A, B, C
Parameter*
Min
Specified Temperature Range
Typ
CS5501-S, T
Max
Min
-40 to +85
Typ
Max
Units
°C
-55 to +125
Accuracy
-A, S
-B, T
-C
-
0.0015
0.0007
0.0003
0.003
0.0015
0.0012
-
0.0007
0.003
0.0015
±%FS
±%FS
±%FS
TMIN to TMAX
-
±1/8
±1/2
-
±1/8
±1/2
LSB16
Full Scale Error
(Note 2)
-
±0.13
±0.5
-
±0.13
±0.5
LSB16
Full Scale Drift
(Note 3)
-
±1.2
-
-
±2.3
-
LSB16
Unipolar Offset
(Note 2)
-
±0.25
±1
-
±0.25
±1
LSB16
Unipolar Offset Drift
(Note 3)
-
±4.2
-
-
+3.0
-25.0
-
LSB16
Bipolar Offset
(Note 2)
-
±0.25
±1
-
±0.25
±1
LSB16
Bipolar Offset Drift
(Note 3)
-
±2.1
-
-
+1.5
-12.5
-
LSB16
Bipolar Negative Full Scale Error
(Note 2)
-
±0.5
±2
-
±0.5
±2
LSB16
Bipolar Negative Full Scale Drift
(Note 3)
-
±0.6
-
-
±1.2
-
LSB16
-
1/10
-
-
1/10
-
LSBrms
Linearity Error
Differential Nonlinearity
Noise (Referred to Output)
Notes: 1. The AIN pin presents a very high input resistance at dc and a minor dynamic load which scales to the
master clock frequency. Both source resistance and shunt capacitance are therefore critical in
determining the CS5501’s source impedance requirements. For more information refer the text section
Analog Input Impedance Considerations.
2. Applies after calibration at the temperature of interest.
3. Total drift over the specified temperature range since calibration at power-up at 25°C (see Figure 11).
This is guaranteed by design and /or characterization. Recalibration at any temperature will remove
these errors.
µV
Unipolar Mode
Bipolar Mode
LSB’s
%FS ppm FS LSB’s
%FS ppm FS
10
0.26
0.0004
4
0.13
0.0002
2
19
0.50
0.0008
8
0.26
0.0004
4
38
1.00
0.0015
15
0.50
0.0008
8
76
2.00
0.0030
30
1.00
0.0015
15
152
4.00
0.0061
61
2.00
0.0030
30
CS5501 Unit Conversion Factors, VREF = 2.5V
* Refer to the Specification Definitions immediately following the Pin Description Section.
22
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
CS5503 ANALOG CHARACTERISTICS (TA = TMIN to TMAX;
VA+, VD+ = 5V;
VA-, VD- = -5V; VREF = 2.5V; CLKIN = 4.096MHz; Bipolar Mode; MODE = +5V; Rsource = 750. with a 1nF
to AGND at AIN (see Note 1): unless otherwise specified.)
CS5503-A, B, C
Parameter*
Min
Specified Temperature Range
Typ
CS5503-S, T
Max
Min
-40 to +85
Accuracy
Linearity Error
Typ
Max
Units
°C
-55 to +125
-A, S
-B, T
-C
-
0.0015
0.0007
0.0003
0.003
0.0015
0.0012
-
0.0007
0.003
TBD
±%FS
±%FS
±%FS
TMIN to TMAX
-
20
-
-
20
-
Bits
Full Scale Error
(Note 2)
-
±4
±16
-
±4
±16
LSB20
Full Scale Error Drift
(Note 3)
-
±19
-
-
±37
-
LSB20
±16
-
±4
±16
LSB20
+48
-400
±4
-
LSB20
±16
LSB20
Differential Nonlinearity
(Not Missing Codes)
Unipolar Offset
(Note 2)
-
±4
Unipolar Offset Drift
(Note 3)
-
±67
-
-
Bipolar Offset
(Note 2)
-
±4
±16
-
Bipolar Offset Drift
(Note 3)
-
±34
-
-
Bipolar Negative Full Scale Error
(Note 2)
-
±8
±32
Bipolar Negative Full Scale Drift
(Note 3)
-
±10
-
1.6
Noise (Referred to Output)
. V
-
LSB20
-
+24
-200
±8
±32
LSB20
-
-
±20
-
LSB20
-
-
1.6
-
LSBrms
(20)
Unipolar Mode
Bipolar Mode
%FS ppm Fs LSB’s
%FS ppm FS
LSB’s
0.596 0.25 0.0000238 0.24
0.13
0.0000119 0.12
1.192 0.50 0.0000477 0.47
0.26
0.0000238 0.24
2.384 1.00 0.0000954 0.95
0.50
0.0000477 0.47
4.768 2.00 0.0001907 1.91
1.00
0.0000954 0.95
9.537 4.000 0.0003814 3.81
2.00
0.0001907 1.91
CS5503 Unit Conversion Factors, VREF = 2.5V
* Refer to the Specification Definitions immediately following the Pin Description Section.
DS31F5
DS31F4
3
3
CS5501 CS5503
CS5501/CS5503
ANALOG CHARACTERISTICS (Continued)
CS5501/3-A, B, C
Parameter*
CS5501/3-S, T
Min
Typ
Max
Min
Typ
Max
Units
(Note 4)
-
2
2
1
0.03
3.2
3.2
1.5
0.1
-
2
2
1
0.03
3.2
3.2
1.5
0.1
mA
mA
mA
mA
(Note 4)
-
25
10
40
20
-
25
10
40
40
mW
µW
(Note 5)
-
70
75
-
-
70
75
-
dB
dB
Power Supplies
DC Power Supply Currents
IA+
IAID+
IDPower Dissipation
SLEEP High
SLEEP Low
Power Supply Rejection
Positive Supplies
Negative Supplies
Analog Input
Analog Input Range
Unipolar
0 to +2.5
0 to +2.5
Bipolar
Input Capacitance
DC Bias Current
(Note 1)
V
-
±2.5
-
-
±2.5
-
V
-
20
-
-
20
-
pF
-
1
-
-
1
-
nA
System Calibration Specifications
Positive Full Scale Calibration Range
VREF+0.1
VREF+0.1
V
Positive Full Scale Input Overrange
VREF+0.1
VREF+0.1
V
Negative Full Scale Input Overrange
-(VREF+0.1)
-(VREF+0.1)
V
-(VREF +0.1)
-40%VREF to +40%VREF
-(VREF +0.1)
-40%VREF to +40%VREF
V
V
80%
VREF
80%
VREF
V
Maximum Offset
Calibration Range
Unipolar Mode
Bipolar Mode
Input Span
(Notes 6, 7)
(Note 8)
2VREF
+0.2
2VREF
+0.2
Notes: 4. All outputs unloaded.
5. 0.1Hz to 10Hz. PSRR at 60 Hz will exceed 120 dB due to the benefit of the digital filter.
6. In unipolar mode the offset can have a negative value (-VREF) such that the unipolar mode can mimic
bipolar mode operation.
7. The specifications for Input Overrange and for Input Span apply additional constraints on the offset
calibration range.
8. For Unipolar mode, Input Span is the difference between full scale and zero scale. For Bipolar mode,
Input Span is the difference between positive and negative full scale points. When using less than
the maximum input span, the span range may be placed anywhere within the range of ±(VREF + 0.1).
Specifications are subject to change without notice.
44
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
DYNAMIC CHARACTERISTICS
Symbol
Ratio
Units
Sampling Frequency
fs
CLKIN/ 256
Hz
Output Update Rate
f out
CLKIN /1024
Sps
CLKIN /409,600
Hz
506,880/CLKIN
s
Parameter
f -3dB
Filter Corner Frequency
Settling Time to
ts
+0.0007%
_
FS (FS Step)
20
0
Output Amplitude in dB
-20
CLKIN = 4 MHz
-40
-60
CLKIN = 2 MHz
-80
-100
CLKIN = 1 MHz
-120
-140
1
10
100
1000
Frequency in Hz
Frequency Response
j2
j1
-σ
-2
jω
S1,2 = -1.4667 ± j1.8199
S3,4 = -1.7559 ± j1.0008
-1
-j1
S5,6 = -1.8746 ± j0.32276
-j2
S-Domain Pole/Zero Plot (Continuous-Time Representation)
H(x) = [1 + 0.694x2 + 0.241x4 + 0.0557x6 + 0.009664x8 + 0.00134x10 + 0.000155x12]-1/2
where x = f/f-3dB, f-3dB = CLKIN/409,600, and f is the frequency of interest.
Continuous-Time Representation of 6-Pole Gaussian Filter
DS31F5
DS31F4
55
CS5501 CS5503
CS5501/CS5503
DIGITAL CHARACTERISTICS (TA = Tmin to Tmax; VA+, VD+ = 5V ± 10%; VA-, VD- = -5V ± 10%)
Parameter
Symbol
Min
Typ
Max
Units
Calibration Memory Retention
Power Supply Voltage (VD+ and VA+)
VMR
2.0
-
-
V
High-Level Input Voltage All Except CLKIN
VIH
2.0
-
-
V
High-Level Input Voltage CLKIN
VIH
3.5
-
-
V
Low-Level Input Voltage All Except CLKIN
VIL
-
-
0.8
V
Low-Level Input Voltage CLKIN
VIL
-
-
1.5
V
VOH
(VD+)-1.0V
-
-
V
VOL
-
-
0.4
V
Input Leakage Current
Iin
-
-
10
µA
3-State Leakage Current
IOZ
-
-
±10
µA
Digital Output Pin Capacitance
Cout
-
9
-
pF
High-Level Output Voltage
Low-Level Output Voltage
(Note 9)
Iout=1.6mA
Notes: 9. Iout = -100 µA. This guarantees the ability to drive one TTL load. (VOH = 2.4V @ Iout = -40 µA).
ABSOLUTE MAXIMUM RATINGS
Parameter
Symbol
Min
Max
Units
VD+
VDVA+
VA-
-0.3
0.3
-0.3
0.3
(VA+)+0.3
-6.0
6.0
-6.0
V
V
V
V
Iin
-
±10
mA
Analog Input Voltage (AIN and VREF pins)
VINA
(VA-)-0.3
(VA+)+0.3
V
Digital Input Voltage
VIND
-0.3
(VA+)+0.3
V
TA
-55
125
C°
Tstg
-65
150
C°
DC Power Supplies:
Positive Digital
Negative Digital
Positive Analog
Negative Analog
Input Current, Any Pin Except Supplies (Notes 10, 11)
Ambient Operating Temperature
Storage Temperature
Notes: 10. Applies to all pins including continuous overvoltage conditions at the analog input (AIN) pin.
11. Transient currents of up to 100mA will not cause SCR latch-up. Maximum input current for a power
supply pin is ± 50 mA.
66
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
RECOMMENDED OPERATING CONDITIONS (AGND, DGND = 0V) (Note 12)
Parameter
DC Power Supplies:
Positive Digital
Negative Digital
Positive Analog
Negative Analog
Analog Reference Voltage
Analog Input Voltage:
Symbol
Min
Typ
Max
Units
VD+
VDVA+
VA-
4.5
-4.5
4.5
-4.5
5.0
-5.0
5.0
-5.0
VA+
-5.5
5.5
-5.5
V
V
V
V
VREF
1.0
2.5
3.0
V
VAIN
VAIN
AGND
-VREF
-
VREF
VREF
V
V
(Note 13)
Unipolar
Bipolar
Notes: 12. All voltages with respect to ground.
13. The CS5501 and CS5503 can accept input voltages up to the analog supplies (VA+ and VA-). They
will accurately convert and filter signals with noise excursions up to 100mV beyond |VREF|.
After filtering, the devices will output all 1’s for any input above VREF and all 0’s for any input below
AGND in unipolar mode and -VREF in bipolar mode.
SWITCHING CHARACTERISTICS (TA = Tmin to Tmax; CLKIN=4.096 MHz; VA+, VD+ = 5V±10%;
VA-, VD- = -5V ± 10%; Input Levels: Logic 0 = 0V, Logic 1 = VD+; CL = 50 pF; unless otherwise specified.)
Parameter
Master Clock Frequency:
Symbol
Internal Gate Oscillator
CLKIN
(See Table 1)
Externally Supplied:
(Note 14)
CLKIN
Maximum
Minimum
(Note 15) CLKIN
CLKIN Duty Cycle
Rise Times:
Fall Times:
Set Up Times:
Hold Time:
Min
Typ
Max
Units
200
4096
5000
kHz
200
40
5000
-
kHz
kHz
20
-
80
%
Any Digital Input
Any Digital Output
(Note 16)
trise
trise
-
20
1.0
-
µs
ns
Any Digital Input
Any Digital Output
(Note 16)
tfall
tfall
-
20
1.0
-
µs
ns
SC1, SC2 to CAL Low
SLEEP High to CLKIN High (Note 17)
tscs
tsls
100
1
-
-
ns
µs
SC1, SC2 hold after CAL falls
tsch
100
-
-
ns
Notes: 14. CLKIN must be supplied whenever the CS5501 or CS5503 is not in SLEEP mode. If no clock is
present when not in SLEEP mode, the device can draw higher current than specified
and possibly become uncalibrated.
15. The CS5501/CS5503 is production tested at 4.096 MHz. It is guaranteed by characterization
to operate at 200 kHz.
16. Specified using 10% and 90% points on waveform of interest.
17. In order to synchronize several CS5501’s or CS5503’s together using the SLEEP pin,
this specification must be met.
DS31F5
DS31F4
7
7
CS5501 CS5503
CS5501/CS5503
SWITCHING CHARACTERISTICS (continued) (TA = Tmin to Tmax; VA+, VD+ = 5V ± 10%;
VA-, VD- = -5V ± 10%; Input Levels: Logic 0 = 0V, Logic 1 = VD+; CL = 50 pF)
Parameter
Symbol
Min
Typ
Max
Units
SSC Mode (Mode = VD+)
Access Time
CS Low to SDATA Out
tcsd1
3/CLKIN
-
-
ns
SDATA Delay Time
SCLK Falling to New SDATA bit
tdd1
-
25
100
ns
SCLK Delay Time
(at 4.096 MHz)
SDATA MSB bit to SCLK Rising
tcd1
250
380
-
ns
Serial Clock
(Out)
Pulse Width High (at 4.096 MHz)
Pulse Width Low
tph1
tpl1
-
240
730
300
790
ns
Output Float Delay
SCLK Rising to Hi-Z
tfd2
-
1/CLKIN
+ 100
1/CLKIN
+ 200
ns
Output Float Delay
CS High to Output Hi-Z (Note 18)
tfd1
-
-
4/CLKIN
+200
ns
fsclk
dc
-
4.2
MHz
tph2
tpl2
50
180
-
-
ns
SEC Mode (Mode = DGND)
Serial Clock (In)
Serial Clock (In)
Pulse Width High
Pulse Width Low
Access Time
CS Low to Data Valid
(Note 19)
tcsd2
-
80
160
ns
Maximum Data Delay Time
(Note 20)
SCLK Falling to New SDATA bit
tdd2
-
75
150
ns
CS High to Output Hi-Z
tfd3
-
-
250
ns
Output Float Delay
100
200
ns
Output Float Delay
SCLK Falling to Output Hi-Z
tfd4
Notes: 18. If CS is returned high before all data bits are output, the SDATA and SCLK outputs will complete
the current data bit and then go to high impedance.
19. If CS is activated asynchronously to DRDY, CS will not be recognized if it occurs when DRDY is high
for 4 clock cycles. The propagation delay time may be as great as 4 CLKIN cycles plus 160 ns.
To guarantee proper clocking of SDATA when using asychronous CS, SCLK(i) should not be taken
high sooner than 4 CLKIN cycles plus 160ns after CS goes low.
20. SDATA transitions on the falling edge of SCLK(i).
CLKIN
CAL
t scs
SC1, SC2
VALID
Calibration Control Timing
88
CS
t sls
t sch
SLEEP
Sleep Mode Timing for
Synchronization
tfd1
SDATA
Output Float Delay
SSC Mode (Note 19)
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
CLKIN
CS
t csd1
SDATA
Hi-Z
MSB
MSB-1
MSB-2
t dd1
Hi-Z
t fd2
t cd1
SCLK (o)
LSB
Hi-Z
Hi-Z
t ph1
t pl1
SSC MODE Timing Relationships
DRDY
CS
t csd2
SDATA
t fd3
Hi-Z
MSB
MSB-1
Hi-Z
t dd2
SCLK (i)
t pl2
t ph2
CS
t csd2
SDATA
Hi-Z
MSB
MSB-1
t dd2
SCLK (i)
LSB
Hi-Z
t fd4
t ph2
SEC MODE Timing Relationships
DS31F5
DS31F4
9
9
CS5501 CS5503
CS5501/CS5503
SWITCHING CHARACTERISTICS (continued) (TA = Tmin to Tmax;
VA+, VD+ = 5V ± 10%; VA-, VD- = -5V ± 10%; Input Levels: Logic 0 = 0V, Logic 1 = VD+; C L = 50 pF)
Parameter
Symbol
Min
Typ
Max
Units
fsclk
dc
-
4.2
MHz
AC Mode (Mode = VD-) CS5501 only
Serial Clock (In)
Serial Clock (In)
Pulse Width High
Pulse Width Low
tph3
tpl3
50
180
-
-
ns
ns
Set-up Time
CS Low to SCLK Falling
tcss
-
20
40
ns
Maximum Data Delay Time SCLK Fall to New SDATA bit
tdd3
-
90
180
ns
Output Float Delay
tfd5
-
100
200
ns
CS High to Output Hi-Z (Note 21)
Notes: 21. If CS is returned high after an 11-bit data packet is started, the SDATA output will continue to output
data until the end of the second stop bit. At that time the SDATA output will go to high impedance.
DRDY
CS
t css
t ph3
SCLK(i)
t pl3
t dd3
SDATA
Hi-Z
START BIT8
High Byte
BIT9
BIT6
t fd5
BIT7 STOP1 STOP2
Hi-Z
Low Byte
AC MODE Timing Relationships (CS5501 only)
10
10
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
GENERAL DESCRIPTION
The CS5501/CS5503 are monolithic CMOS A/D
converters designed specifically for high resolution measurement of low-frequency signals. Each
device consists of a charge-balance converter (16Bit for the CS5501, 20-Bit for the CS5503),
calibration microcontroller with on-chip SRAM,
and serial communications port.
mation in the form of frequency (or duty cycle),
which is then filtered (averaged) by the counter
for higher resolution.
LP Filter
S/H Amp
1-bit
Digital Filter
Comparator
DAC
16-bits
The CS5501/CS5503 A/D converters perform
conversions continuously and update their output
ports after every conversion (unless the serial port
is active). Conversions are performed and the serial port is updated independent of external
control. Both devices are capable of measuring
either unipolar or bipolar input signals, and calibration cycles may be initiated at any time to
ensure measurement accuracy.
The CS5501/CS5503 perform conversions at a
rate determined by the master clock signal. The
master clock can be set by an external clock or
with a crystal connected to the pins of the on-chip
gate oscillator. The master clock frequency determines:
1. The sample rate of the analog input signal.
2. The corner frequency of the on-chip digital
filter.
3. The output update rate of the serial output port.
The CS5501/CS5503 design includes several selfcalibration modes and several serial port interface
modes to offer users maximum system design
flexiblity.
The Delta-Sigma Conversion Method
The CS5501/CS5503 A/D converters use chargebalance techniques to achieve low cost, high
resolution measurements. A charge-balance A/D
converter consists of two basic blocks: an analog
modulator and a digital filter. An elementary example of a charge-balance A/D converter is a
conventional voltage-to-frequency converter and
counter. The VFC’s 1-bit output conveys inforDS31F5
DS31F4
Figure 1. Charge Balance (Delta-Sigma) A/D Converter
The analog modulator of the CS5501/CS5503 is a
multi-order delta-sigma modulator. The modulator
consists of a 1-bit A/D converter (that is, a comparator) embedded in an analog feedback loop
with high open loop gain (see Figure 1). The
modulator samples and converts the input at a rate
well above the bandwidth of interest. The 1-bit
output of the comparator is sampled at intervals
based on the clock rate of the part and this information (either a 1 or 0) is conveyed to the digital
filter. The digital filter is much more sophisticated
than a simple counter. The filter on the chip has a
6-pole low pass Gaussian response which rolls off
at 120 dB/decade (36 dB/octave). The corner frequency of the digital filter scales with the master
clock frequency. In comparison, VFC’s and dual
slope converters offer (sin x)/x filtering for high
frequency rejection (see Figure 2 for a comparison of the characteristics of these two filter types).
When operating from a 1 MHz master clock the
digital filter in the CS5501/CS5503 offers better
than 120 dB rejection of 50 and 60 Hz line frequencies and does not require any type of line
synchronization to achieve this rejection. It should
be noted that the CS5501/CS5503 will update its
output port almost at 1000 times per second when
operating from the 1 MHz clock. This is a much
higher update rate (typically by a factor of at least
50 times) than either VFCs or dual-slope converters can offer.
For a more detailed discussion on the delta-sigma
modulator see the Application note "Delta-Sigma
11
11
CS5501 CS5503
0
0
-20
-20
Magnitude (dB)
Magnitude (dB)
CS5501/CS5503
-40
-60
-40
CLKIN = 4 MHz
-60
CLKIN = 2 MHz
-80
-80
-100
-100
CLKIN=1 MHz
0
20
40
60
Frequency (Hz)
80
100
0
20
a. Averaging (Integrating) Filter Response (tavg = 100 ms)
40
60
Frequency (Hz)
80
100
b. 6-Pole Gaussian Filter Response
Figure 2. Filter Responses
A/D Conversion Technique Overview" in the application note section of the data book. The
application note discusses the delta-sigma modulator and some aspects of digital filtering.
OVERVIEW
As shown in the block diagram on the front page
of the data sheet, the CS5501/CS5503 can be segmented into five circuit functions. The heart of the
chip is the charge balance A/D converter (16-bit
for the CS5501, 20-bit for the CS5503). The converter and all of the other circuit functions on the
chip must be driven by a clock signal from the
clock generator. The serial interface logic outputs
the converted data. The calibration microcontroller along with the calibration SRAM (static
RAM), supervises the device calibration. Each
segment of the chip has control lines associated
with it. The function of each of the pins is described in the pin description section of the data
sheet.
Clock Generator
The CS5501/CS5503 both include gates which
can be connected as a crystal oscillator to provide
the master clock signal for the chip. Alternatively,
an external (CMOS compatible) clock can be input to the CLKIN pin as the master clock for the
device. Figure 3 illustrates a simple model of the
on-chip gate oscillator. The gate has a typical
transconductance of 1500 µmho. The gate model
includes 10 pf capacitors at the input and output
pins. These capacitances include the typical stray
capacitance of the pins of the device. The on-chip
R1
500 k Ω
CLKIN
3
CLKOUT
2
10pF
10pF
g
m
C1 *
1500 umho
Y1
C2 *
* See Table 1
Figure 3. On-chip Gate Oscillator Model
12
12
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
gate oscillator is designed to properly operate
without additional loading capacitors when using
a 4.096 MHz (or 4 MHz) crystal. If other crystal
frequencies or if ceramic resonators are used,
loading capacitors may be necessary for reliable
operation of the oscillator. Table 1 illustrates some
typical capacitor values to be used with selected
resonating elements.
Resonators
C1
C2
200 kHz
330pF
470pF
455 kHz
100pF
100pF
1.0 MHz
50pF
50pF
2.0 MHz
20pF
20pF
2.000 MHz
30pF
30pF
3.579 MHz
20pF
20pF
4.096 MHz
None
None
Ceramic
Crystals
Table 1. Resonator Loading Capacitors
CLKOUT (pin 2) can be used to drive one external CMOS gate for system clock requirements. In
this case, the external gate capacitance must be
taken into account when choosing the value of
C2.
Caution: A clock signal should always be present
whenever the SLEEP is inactive (SLEEP = VD+).
If no clock is provided to the part when not in
SLEEP, the part may draw excess current and
possibly even lose its calibration data. This is because the device is built using dynamic logic.
Serial Interface Logic
The CS5501 serial data output can operate in any
one of the following three different serial interface
modes depending upon the MODE pin selection:
SSC (Synchronous Self-Clocking) mode;
MODE pin tied to VD+ (+5V).
SEC (Synchronous External Clocking) mode;
MODE pin tied to DGND.
DS31F5
DS31F4
and AC (Asynchronous Communication) mode;
CS5501 only
MODE pin tied to VD- (-5V)
The CS5503 can only operate in the first two
modes, SEC and SSC.
Synchronous Self-Clocking Mode
When operated in the SSC mode (MODE pin tied
to VD+), the CS5501/CS5503 furnish both serial
output data (SDATA) and an internally-generated
serial clock (SCLK). Internal timing for the SSC
mode is illustrated in Figure 4. Figure 5 shows
detailed SSC mode timing for both the
CS5501/CS5503. A filter cycle occurs every 1024
cycles of CLKIN. During each filter cycle, the
status of CS is polled at eight specific times during the cycle. If CS is low when it is polled, the
CS5501/CS5503 begin clocking the data bits out,
MSB first, at a SCLK output rate of CLKIN/4.
Once transmission is complete, DRDY rises and
both SDATA and SCLK outputs go into a high
impedance state. A filter cycle begins each time
DRDY falls. If the CS line is not active, DRDY
will return high 1020 clock cycles after it falls.
Four clock cycles later DRDY will fall to signal
that the serial port has been updated with new
data and that a new filter cycle has begun. The
first CS polling during a filter cycle occurs 76
clock cycles after DRDY falls (the rising edge of
CLKIN on which DRDY falls is considered clock
cycle number one). Subsequent pollings of CS occur at intervals of 128 clock cycles thereafter (76,
204, 332, etc.). The CS signal is polled at the beginning of each of eight data output windows
which occur in a filter cycle. To transmit data during any one of the eight output windows, CS must
be low at least three CLKIN cycles before it is
polled. If CS does not meet this set-up time, data
will not be transmitted during the window time.
Furthermore, CS is not latched internally and
therefore must be held low during the entire data
transmission to obtain all of the data bits.
13
13
CS5501 CS5503
CS5501/CS5503
64/CLKIN
Internal
Status
Note 1
Analog Time 0
fout =1024/CLKIN
64/CLKIN
Digital Time 0
76/CLKIN
Analog Time 1
Digital Time1
CS Polled
DRDY (o)
CS (i)
CS5501
SCLK (o)
Hi-Z
CS5501
SDATA (o)
Hi-Z
CS5503
SCLK (o)
Hi-Z
CS5503
SDATA (o)
Hi-Z
Hi-Z
(MSB)
(LSB)
Hi-Z
Hi-Z
(MSB)
(LSB)
Hi-Z
Note: 1. There are 16 analog and digital settling periods per filter cycle (4 are shown). Data can be output in the
SSC mode in only 1 of the 8 digital time periods in each filter cycle.
Figure 4. Internal Timing
CLKIN (i)
76 CLKIN cycles
DRDY (o)
CS (i)
SDATA (o)
Hi-Z
(MSB)
B15*
B19**
B14*
B18**
B1
Hi-Z
SCLK (o)
(LSB)
B0
Hi-Z
Hi-Z
* CS5501
** CS5503
Figure 5. Synchronous Self-Clocking (SSC) Mode Timing
The eighth output window time overlaps the time
in which the serial output port is to be updated. If
the CS is recognized as being low when it is
polled for the eighth window time, data will be
output as normal, but the serial port will not be
updated with new data until the next serial port
update time. Under these conditions, the serial
port will experience an update rate of only 2 kSps
14
14
(CLKIN = 4.096 MHz) instead of the normal
4 kSps serial port update rate.
Upon completion of transmission of all the data
bits, the SCLK and SDATA outputs will go to a
high impedance state even with CS held low. In
the event that CS is taken high before all data bits
are output, the SDATA and SCLK outputs will
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
complete the current data bit output and go to a
high impedance state when SCLK goes low.
This insures that CS will be recognized and the
MSB bit will become stable before the SCLK
transitions positive to latch the MSB data bit.
Synchronous External Clocking Mode
When operated in the SEC mode (MODE pin tied
to DGND), the CS5501/CS5503 outputs the data
in its serial port at a rate determined by an external clock which is input into the SCLK pin. In
this mode the output port will be updated every
1024 CLKIN cycles. DRDY will go low when
new data is loaded into the output port. If CS is
not active, DRDY will return positive 1020
CLKIN cycles later and remain so for four
CLKIN cycles. If CS is taken low it will be recognized immediately unless it occurs while
DRDY is high for the four clock cycles. As soon
as CS is recognized, the SDATA output will come
out of its high-impedance state and present the
MSB data bit. The MSB data bit will remain present until a falling edge of SCLK occurs to
advance the output to the MSB-1 bit. If the CS
and external SCLK are operated asynchronously
to CLKIN, errors can result in the output data unless certain precautions are taken. If CS is
activated asynchronously, it may occur during the
four clock cycles when DRDY is high and therefore not be recognized immediately. To be certain
that data misread errors will not result if CS occurs at this time, the SCLK input should not
transition high to latch the MSB until four
CLKIN cycles plus 160 ns after CS is taken low.
When SCLK returns low the serial port will present the MSB-1 data bit on its output.
Subsequent cycles of SCLK will advance the data
output. When all data bits are clocked out, DRDY
will then go high and the SDATA output will go
into a high impedance state. If the CS input goes
low and all of the data bits are not clocked out of
the port, filter cycles will continue to occur but
the output serial port will not be updated with
new data (DRDY will remain low). If CS is taken
high at any time, the SDATA output pin will go to
a high impedance state. If any of the data bits in
the serial port have not been clocked out, they
will remain available until DRDY returns high for
four clock cycles. After this DRDY will fall and
the port will be updated with a new 16-bit word
in the CS5501 or 20-bit word in the CS5503. It
is acceptable to clock out less than all possible
data bits if CS is returned high to allow the port
to be updated. Figure 6 illustrates the serial port
timing in the SEC mode.
Asynchronous Communication Mode (CS5501
Only)
In the CS5501, the AC mode is activated when
the MODE pin is tied to VD- (-5 V). When operating in the AC mode the CS5501 is designed to
DRDY (o)
CS (i)
SCLK (i)
SDATA (o)
Hi-Z
(MSB)
B15*
B19**
(LSB)
B14*
B18**
B1
B0
Hi-Z
* CS5501
** CS5503
Figure 6. Synchronous External-Clocking (SEC) Mode Timing
DS31F5
DS31F4
15
15
CS5501 CS5503
CS5501/CS5503
provide data output in UART compatible format.
The baud rate of the SDATA output will be determined by the rate of the SCLK input. The data
which is output of the SDATA pin will be formatted such that it will contain two 11 bit data
packets. Each packet includes one start bit, eight
data bits, and two stop bits. The packet which carries the most-significant-byte data will be output
first, with its lsb being the first data bit output
after the start bit.
In this mode, DRDY will occur every 1024 clock
cycles. If the serial port is not outputting a data
byte, DRDY will return high after 1020 clock cycles and remain high for 4 clock cycles. DRDY
will then go low to indicate that an update to the
serial output port with a new 16 bit word has occurred. To initiate a transmission from the port the
CS line must be taken low. Then SCLK, which is
an input in this mode, must transition from a high
to a low to latch the state of CS internal to the
CS5501. Once CS is recognized and latched as a
low, the port will begin to output data. Figure 7
details the timing for this output. CS can be returned high before the end of the 11-bit
transmission and the transmission will continue
until the second stop bit of the first 11-bit packet
is output. The SDATA output will go into a high
impedance state after the second stop bit is output.
To obtain the second 11-bit packet CS must again
be brought low before DRDY goes high or the
second 11-bit data packet will be overwritten with
a serial port update. For the second 11-bit packet,
CS need only to go low for 50 ns; it need not be
latched by a falling edge of SCLK. Alternately,
the CS line can be taken low and held low until
both 11-bit data packets are output. This is the
preferred method of control as it will prevent losing the second 11-bit data packet if the port is
updated. Some serial data rates can be quite slow
compared to the rate at which the CS5501 can update its output port. A slow data rate will leave
only a short period of time to start the second 11bit packet if CS is returned high momentarily. If
CS is held low continuously (CS hard-wired to
DGND), the serial port will be updated only after
all 22 bits have been clocked out of the port.
Upon the completion of a transmission of the two
11-bit data packets the SDATA output will go into
a high impedance state. If at any time during
transmission the CS is taken back high, the current 11-bit data packet will continue to be output.
At the end of the second stop bit of the data
packet, the SDATA output will go into a high impedance state.
Linearity Performance
The CS5501/CS5503 delta-sigma converters are
like conventional charge-balance converters in
that they have no source of nonmonotonicity. The
devices therefore have no missing codes in their
transfer functions. See Figure 8 for a plot of the
SCLK (i)
DRDY (o)
CS (i)
SDATA (o)
Hi-Z
Start B8
B9
B14 B15
Stop Stop
Start B0
1
2
B1
B6
B7
Stop Stop
1
2
Figure 7. CS5501 Asynchronous (UART) Mode Timing
16
16
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
+1
DNL (LSB)
+1/2
0
-1/2
-1
0
32,768
65,535
Codes
Figure 8. CS5501 Differential Nonlinearity Plot
excellent differential linearity achieved by the
CS5501. The CS5501/CS5503 also have excellent
integral linearity, which is accomplished with a
well-designed charge-balance architecture. Each
device also achieves low input drift through the
use of chopper-stabilized techniques in its input
stage. To assure that the CS5501/CS5503 achieves
excellent performance over time and temperature,
it uses digital calibration techniques to minimize
offset and gain errors to typically within ±1/2
LSB at 16 bits in the CS5501 and ±4 LSB at 20
bits in the CS5503.
Calibration
The CS5501/CS5503 offer both self-calibration
and system level calibration capability. To understand the calibration features, a basic
comprehension of the internal workings of the
converter are helpful. As mentioned previously in
this data sheet, the converter consists of two sections. First is the analog modulator which is a
delta-sigma type charge-balance converter. This
is followed by a digital filter. The filter circuitry
is actually an arithmetic logic unit (ALU) whose
architecture and instructions execute the filter
function. The modulator (explained in more detail in the applications note "Delta-Sigma
Conversion Technique Overview") uses the VREF
voltage connected to pin 10 to determine the magnitude of the voltages used in its feedback DAC.
The modulator accepts an analog signal at its input and produces a data stream of 1’s and 0’s as
its output. This data stream value can change
DS31F5
DS31F4
(from 1 to 0 or vice versa) every 256 CLKIN cycles. As the input voltage increases the ratio of
1’s to 0’s out of the modulator increases proportionally. The 1’s density of the data stream out of
the modulator therefore provides a digital representation of the analog input signal where the 1’s
density is defined as the ratio of the number of 1’s
to the number of 0’s out of the modulator for a
given period of time. The 1’s density output of the
modulator is also a function of the voltage on the
VREF pin. If the voltage on the VREF pin increases in value (say, due to temperature drift), and
the analog input voltage into the modulator remains
constant, the 1’s density output of the modulator will
decrease (less 1’s will occur). The analog input into
the modulator which is necessary to produce a given
binary output code from the converter is ratiometric
to the voltage on the VREF pin. This means that if
VREF increases by one per cent, the analog signal
on AIN must also increase by one per cent to maintain the same binary output code from the converter.
For a complete calibration to occur, the calibration
microcontroller inside the device needs to record
the data stream 1’s density out of the modulator
for two different input conditions. First, a "zero
scale" point must be presented to the modulator.
Then a "full scale" point must be presented to the
modulator. In unipolar self-cal mode the zero
scale point is AGND and the full scale point is the
voltage on the VREF pin. The calibration microcontroller then remembers the 1’s density out of
the modulator for each of these points and calculates a slope factor (LSB/µV). This slope factor
17
17
CS5501 CS5503
CS5501/CS5503
represents the gain slope for the input to output
transfer function of the converter. In unipolar
mode the calibration microcontroller determines
the slope factor by dividing the span between the
zero point and the full scale point by the total
resolution of the converter (216 for the CS5501,
resulting in 65,536 segments or 220 for the
CS5503, resulting in 1,048,578 segments). In bipolar mode the calibration microcontroller divides
the span between the zero point and the full scale
point into 524,288 segments for the CS5503 and
32,768 segments for the CS5501. It then extends
the measurement range 524,288 segments for the
CS5503, 32,768 segments for the CS5501, below
the zero scale point to achieve bipolar measurement capability. In either unipolar or bipolar
modes the calculated slope factor is saved and
later used to calculate the binary output code
when an analog signal is present at the AIN pin
during measurement conversions.
Figure 9). System calibration performs the same
slope factor calculations as self cal but uses voltage values presented by the system to the AIN pin
for the zero scale point and for the full scale
point. Table 2 depicts the calibration modes
available. Two system calibration modes are
listed. The first mode offers system level calibration for system offset and for system gain. This is
a two step calibration. The zero scale point (system offset) must be presented to the converter
first. The voltage that represents zero scale point
must be input to the converter before the calibration step is initiated and must remain stable until
the step is complete. The DRDY output from the
converter will signal when the step is complete by
going low. After the zero scale point is calibrated,
the voltage representing the full scale point is input to the converter and the second calibration
step is initiated. Again the voltage must remain
stable throughout the calibration step.
System calibration allows the A/D converter to
compensate for system gain and offset errors (see
This two step calibration mode offers another calibration feature. After a two step calibration
VREF sys
Signal
Conditioning
Circuitry
Analog
MUX
Transducer
SCLK
CS5501
CS5503
SDATA
CAL SC1 SC2
A0 A1
CLK
DATA
µC
I/O 1
I/O 2
I/O 3
I/O 4
I/O 5
Figure 9. System Calibration
CAL
SC1
SC2
Cal Type
ZS Cal
FS Cal
Sequence
Calibration Time
0
0
Self-Cal
AGND
VREF
One Step
3,145,655/fclk
1
1
AIN
-
1st Step
1,052,599/fclk
0
1
System Offset
& System Gain
-
AIN
2nd Step
1,068,813/fclk
1
0
System Offset
AIN
VREF
One Step
2,117,389/fclk
* DRDY remains high throughout the calibration sequence. In Self-Cal mode (SC1 and SC2 low) DRDY
falls once the CS5501 or CS5503 has settled to the analog input. In all other modes DRDY falls
immediately after the calibration term has been determined.
Table 2. Calibration Control
18
18
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
sequence (system offset and system gain) has
been properly performed, additional offset calibrations can be performed by themselves to
reposition the gain slope (the slope factor is not
changed) to adjust its zero reference point to the
new system zero reference value.
A second system calibration mode is available
which uses an input voltage for the zero scale
calibration point, but uses the VREF voltage as
the full scale calibration point.
Whenever a system calibration mode is used,
there are limits to the amount of offset and to the
amount of span which can be accommodated.
The range of input span which can be accommodated in either unipolar or bipolar mode is
restricted to not less than 80% of the voltage on
VREF and not more than 200% of (VREF +
0.1) V. The amount of offset which can be calibrated depends upon whether unipolar or bipolar
mode is being used. In unipolar mode the system
calibration modes can handle offsets as positive as
20% of VREF (this is restricted by the minimum
span requirement of 80% VREF) or as negative as
-(VREF + 0.1) V. This capability enables the
unipolar mode of the CS5501/CS5503 to be calibrated to mimic bipolar mode operation.
In the bipolar mode the system offset calibration
range is restricted to a maximum of ±40% of
VREF. It should be noted that the span restrictions
limit the amount of offset which can be calibrated.
The span range of the converter in bipolar mode
extends an equidistance (+ and -) from the voltage
used for the zero scale point. When the zero scale
point is calibrated it must not cause either of the
two endpoints of the bipolar transfer function to
exceed the positive or the negative input overrange points (+(VREF + 0.1) V or - (VREF +
0.1) V). If the span range is set to a minimum
(80% VREF) the offset voltage can move ±40%
VREF without causing the end points of the transfer function to exceed the overrange points.
Alternatively, if the span range is set to 200% of
DS31F5
DS31F4
VREF, the input offset cannot move more than
+0.1 or 0.1 V before an endpoint of the transfer
function exceeds the input overrange limit.
Initiating Calibration
Table 2 illustrates the calibration modes available
in the CS5501/CS5503. Not shown in the table is
the function of the BP/UP pin which determines
whether the converter is calibrated to measure bipolar or unipolar signals. A calibration step is
initiated by bringing the CAL pin (13) high for at
least 4 CLKIN cycles to reset the part and then
bringing CAL low. The states of SC1 (pin 4) and
SC2 (pin 17) along with the BP/UP (pin 12) will
determine the type of calibration to be performed.
The SC1 and SC2 inputs are latched when CAL
goes low. The BP/UP input is not latched and
therefore must remain in a fixed state throughout
the calibration and measurement cycles. Any time
the state of the BP/UP pin is changed, a new calibration cycle must be performed to enable the
CS5501/CS5503 to properly function in the new
mode.
When a calibration step is initiated, the DRDY
signal will go high and remain high until the step
is finished. Table 2 illustrates the number of
clock cycles each calibration requires. Once a
calibration step is initiated it must finish before a
new calibration step can be executed. In the two
step system calibration mode, the offset calibration step must be initiated before initiating the
gain calibration step.
When a self-cal is completed DRDY falls and the
output port is updated with a data word that represents the analog input signal at the AIN pin.
When a system calibration step is completed,
DRDY will fall and the output port will be updated with the appropriate data value (zero scale
point, or full scale point). In the system calibration mode, the digital filter must settle before the
output code will represent the value of the analog
input signal.
19
19
CS5501 CS5503
CS5501/CS5503
Cal Mode
Zero Scale
1LSB
Gain Factor
Unipolar
Bipolar
CS5501
CS5503
CS5501
CS5503
Self-Cal
AGND
VREF
VREF
65,536
VREF
1,048,526
2VREF
65,536
2VREF
1,048,526
System Cal
SOFF
SGAIN
SGAIN−SOFF
65,536
SGAIN−SOFF
1,048,526
2(SGAIN−SOFF)
65,536
2(SGAIN−SOFF)
1,048,526
Table 3. Output Code Size After Calibration
Input Voltage, Unipolar Mode
System-Cal
Self-Cal
>(SGAIN - 1.5 LSB)
SGAIN - 1.5 LSB
Input Voltage, Bipolar Mode
Output Codes (Hex)
CS5501
CS5503
Self-Cal
System Cal
>(VREF - 1.5 LSB)
FFFF
FFFFF
>(VREF - 1.5 LSB)
>(SGAIN - 1.5 LSB)
FFFF
FFFFF
VREF - 1.5 LSB
FFFE
FFFFE
VREF - 1.5 LSB
SGAIN - 1.5 LSB
AGND - 0.5 LSB
SOFF -0.5 LSB
(SGAIN - SOFF)/2 - 0.5 LSB VREF/2 - 0.5 LSB
8000
80000
7FFF
7FFFF
0001
00001
SOFF + 0.5 LSB
AGND + 0.5 LSB
0000
00000
-VREF+ 0.5 LSB
-SGAIN + 2SOFF + 0.5 LSB
<(SOFF + 0.5 LSB)
<(AGND+0.5 LSB)
0000
00000
<(-VREF+0.5 LSB)
<(-SGAIN+2SOFF+0.5 LSB)
Table 4. Output Coding
Tables 3 and 4 indicate the output code size and
output coding of the CS5501/CS5503 in its various modes. The calibration equations which
represent the CS5501/CS5503 transfer function
are shown in Figure 10.
DOUT = Slope (AIN - Unipolar Offset) + 0.5 LSB
a. Unipolar Calibration
CS5501
15
DOUT = Slope (AIN - Bipolar Offset) + 2 + 0.5 LSB16
CS5503
19
DOUT = Slope(AIN - Bipolar Offset) + 2 + 0.5 LSB20
b. Bipolar Calibration
Figure 10. Calibration Equations
20
20
Underrange And Overrange Considerations
The input signal range of the CS5501/CS5503
will be determined by the mode in which the part
is calibrated. Table 4 indicates the input signal
range in the various modes of operation. If the
input signal exceeds the full scale point the converter will output all ones. If the signal is less
than the zero scale point (in unipolar) or more
negative in magnitude than minus the full scale
point (in bipolar) it will output all zeroes.
Note that the modulator-filter combination in the
chip CS5501/CS5503 is designed to accurately
convert and filter input signals with noise excursions which extend up to 100 mV below the
analog value which produces all zeros out or
above the analog value which produces all ones
out. Overrange noise excursions greater than
100 mV may increase output noise.
All pins of the CS5501/CS5503 include diodes
which clamp the input signals to within the positive and negative supplies. If a signal on any pin
(including AIN) exceeds the supply voltage (either
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
+ or -) a clamp diode will be forward-biased. Under these fault conditions the CS5501/CS5503
might be damaged. Under normal operating conditions (with the power supplies established), the
device will survive transient currents through the
clamp diodes up to 100 mA and continuous currents up to 10 mA. The drive current into the AIN
pin should be limited to a safe value if an overvoltage condition is likely to occur. See the
application note "Buffer Amplifiers for the
CS501X Series of A/D Converters" for further
discussion on the clamp diode input structure and
on current limiting circuits.
System Synchronization
If more than one CS5501/CS5503 is included in a
system which is operating from a common clock,
all of the devices can be synchronized to sample
and output at exactly the same time. This can be
accomplished in either of two ways. First, a single
CAL signal can be issued to all the
CS5501/CS5503’s in the system. To insure synchronization on the same clock signal the CAL
signal should go low on the falling edge of
CLKIN. Or second, a common SLEEP control
signal can be issued. If the SLEEP signal goes
positive with the appropriate set up time to
CLKIN, all parts will be synchronized on the
same clock cycle.
Analog Input Impedance Considerations
The analog input of the CS5501/CS5503 can be
modeled as illustrated in Figure 11. A 20 pF capacitor is used to dynamically sample the input
signal. Every 64 CLKIN cycles the switch alternately connects the capacitor to the output of the
buffer and then directly to the AIN pin. Whenever the sample capacitor is switched from the
output of the buffer to the AIN pin, a small packet
of charge (a dynamic demand of current) will be
required from the input source to settle the voltage on the sample capacitor to its final value.
The voltage at the output of the buffer may differ
up to 100 mV from the actual input voltage due to
DS31F5
DS31F4
CS5501
CS5503
AIN
+
-
20 pF
Vos ≤ 100 mv
AGND
Figure 11. Analog Input Model
the offset voltage of the buffer. Timing allows 64
cycles of master clock (CLKIN) for the voltage
on the sample capacitor to settle to its final value.
The equation which defines settling time is:
−t
Ve = Vmax e ⁄RC
Where Ve is the final settled value, Vmax is the
maximum error voltage value of the input signal,
R is the value of the input source resistance, C is
the 20 pF sample capacitor plus the value of any
stray or additional capacitance at the input pin.
The value of t is equal to 64/CLKIN.
Vmax occurs the instance when the sample capacitor is switched from the buffer output to the AIN
pin. Prior to the switch, AIN has an error estimated as being less than or equal to Ve. Vmax is
equal to the prior error (Ve) plus the additional
error from the buffer offset. The estimate for
Vmax is:
Vmax = Ve+100mV
20pF
(20pF+CEXT)
Where CEXT is the combination of any external
or stray capacitance.
From the equation which defines settling time, an
equation for the maximum acceptable source resistance is derived
21
21
CS5501 CS5503
CS5501/CS5503
equation which defines settling time, an equation
for the maximum acceptable source resistance is
derived
Rsmax =
−64
Ve


CLKIN(20pF+CEXT ) ln 

20pF(100mv)

 Ve +

( 20pF+CEXT ) 


This equation assumes that the offset voltage of
the buffer is 100 mV, which is the worst case.
The value of Ve is the maximum error voltage
which is acceptable.
10
160
5
80
0
0
-5
-80
-10
-160
-15
-240
-20
-55
-35
-15
5
25
45
65
85
Temperature in Deg. C.
105
CS5503 Bipolar Offset in LSB
CS5501 Bipolar Offset in LSB
For a maximum error voltage (Ve) of 10 µV in
the CS5501 (1/4LSB at 16-bits) and 600 nV in
the CS5503 (1/4LSB at 20-bits), the above equation indicates that when operating from a
4.096 MHz CLKIN, source resistances up to
84 kΩ in the CS5501 or 64 kΩ in the CS5503 are
acceptable in the absence of external capacitance
(CEXT = 0). If higher input source resistances
are desired the master clock rate can be reduced
to yield a longer settling time for the 64 cycle period.
-320
125
Figure 12. Typical Self-Cal Bipolar Offset vs. Temperature After Calibration at 25 °C
Analog Input Drift Considerations
The CS5501/CS5503 analog input uses chopperstabilization techniques to minimize input offset
22
22
drift. Charge injection in the analog switches and
leakage currents at the sampling node are the primary sources of offset voltage drift in the
converter. Figure 12 indicates the typical offset
drift due to temperature changes experienced after
calibration at 25 °C. Drift is relatively flat up to
about 75 °C. Above 75 °C leakage current becomes the dominant source of offset drift.
Leakage currents approximately double with each
10 °C of temperature increase. Therefore the offset drift due to leakage current increases as the
temperature increases. The value of the voltage on
the sample capacitor is updated at a rate determined by the master clock, therefore the amount
of offset drift which occurs will be proportional to
the elapsed time between samples. In conclusion,
the offset drift increases with temperature and is
inversely proportional to the CLKIN rate. To
minimize offset drift with increased temperature,
higher CLKIN rates are desirable. At temperatures
above 100 °C, a CLKIN rate above 1 MHz is recommended. The effects of offset drift due to
temperature changes can be eliminated by recalibrating the CS5501/CS5503 whenever the
temperature has changed.
Gain drift within the converter depends predominately upon the temperature tracking of internal
capacitors. Gain drift is not affected by leakage
currents, therefore gain drift is significantly less
than comparable offset errors due to temperature
increases. The typical gain drift over the specified
temperature range is less than 2.5 LSBs for the
CS5501 and less than 40 LSBs for the CS5503 .
Measurement errors due to offset drift or gain
drift can be eliminated at any time by recalibrating the converter. Using the system calibration
mode can also minimize offset and gain errors in
the signal conditioning circuitry. The
CS5501/CS5503 can be recalibrated at any temperature to remove the effects of these errors.
Linearity and differential non linearity are not significantly affected by temperature changes.
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
Filtering
At the system level, the digital filter in the
CS5501/CS5503 can be modeled exactly like
an analog filter with a few minor differences.
Digital filtering resides behind the A/D conversion and can thus reject noise injected during
the conversion process (i.e. power supply ripple, voltage reference noise, or noise in the
ADC itself). Analog filtering cannot.
Also, since digital filtering resides behind the
A/D converter, noise riding unfiltered on a
near-full-scale input could potentially overrange the ADC. In contrast, analog filtering
removes the noise before it ever reaches the
c o n v e rt e r. To a dd re s s t hi s i s s ue, the
CS5501/CS5503 each contain an analog modulator and digital filter which reserve headroom
such that the device can process signals with
100mV "excursions" above full-scale and still
output accurately converted and filtered data.
Filtered input signals above full-scale still result
in an output of all ones.
The digital filter’s corner frequency occurs at
CLKIN/409,600, where CLKIN is the master
clock frequency. With a 4.096MHz clock, the
filter corner is at 10Hz and the output register is
updated at a 4kHz rate. CLKIN frequency can be
reduced with a proportional reduction in the filter
corner frequency and in the update rate to the output register. A plot of the filter response is shown
in the specification tables section of this data
sheet.
Both the CS5501/CS5503 employ internal digital filtering which creates a 6-pole Gaussian
relationship. With the corner frequency set at
1 0H z for m ini mi zed s ett li ng t im e, the
CS5501/CS5503 offer approximately 55dB rejection at 60Hz to signals coming into either
the AIN or VREF pins. With a 5Hz cut-off,
60Hz rejection increases to more than 90dB.
The digital filter (rather than the analog modulator) dominates the converters’ settling for
step-function inputs. Figure 13 illustrates the settling characteristics of the filter. The vertical axis
is normalized to the input step size. The horizontal axis is in filter cycles. With a full scale input
step (2.5 V in unipolar mode) the output will exhibit an overshoot of about 0.25 LSB16 in the
CS5501 and 4 LSB20 in the CS5503.
1.1
1.0000125
Vertical scale normalized
to input step size
1.0
0.9
1.0000100
0.7
Settling Accuracy
Settling Accuracy
1.0000075
See (b) for
expanded view
0.8
0.6
0.5
0.4
1.0000000
0.9999975
0.9999950
0.2
0.9999925
0.1
0.9999900
0
50
100
150
200
250
300
350
400
450
Filter Cycles (1024 CLKIN cycles)
(a) Settling Time Due to Input Step Change
DS31F5
DS31F4
500
Vertical scale normalized
to input step size
1.0000025
0.3
0.0
1.00000381
1.0000050
0.99999850
Settling response is monotonically
increasing from zero to here, and
then exhibits one overshoot and
one undershoot as shown.
0.9999875
500
530
560
590
620
650
680
710
740
Filter Cycles (1024 CLKIN cycles)
(b) Expanded Version of (a)
23
23
CS5501 CS5503
CS5501/CS5503
Anti-Alias Considerations
Post Filtering
The digital filter in the CS5501/CS5503 does not
provide rejection around integer multiples of the
oversampling rate [(N*CLKIN)/256, where
N = 1,2,3,...]. That is, with a 4.096 MHz master
clock the noise on the analog input signal within
the narrow ±10 Hz bands around the 16 kHz,
32 kHz, 48 kHz, etc., passes unfiltered to the digital output. Most broadband noise will be very
well filtered because the CS5501/CS5503 use a
very high oversampling ratio of 800 (16 kHz:
2x10 Hz). Broadband noise is reduced by:
Post filtering is useful to enhance the noise performance of the CS5503. With a constant input
voltage the output codes from the CS5503 will
exhibit some variation due to noise. The CS5503
has typically 1.6 LSB20 rms noise in its output
codes. Additional variation in the output codes
can arise due to noise from the input signal source
and from the voltage reference. Post filtering
(digital averaging) will be necessary to achieve
less than 1 LSB p-p noise at the 20-bit level. The
CS5503 has peak noise less than the 18-bit level
without additional filtering if care is exercised in
the design of the voltage reference and the input
signal condition circuitry. Noise in the bandwidth
from dc to 10 Hz on both the AIN and VREF
inputs should be minimized to ensure maximum
performance. As the amount of noise will be
highly system dependent, a specific recommendation for post filtering for all applications cannot be
stated. The following guidelines are helpful. Realize that the digital filter in the CS5503, like any
other low pass filter, acts as an information storage unit. The filter retains past information for a
period of time even after the input signal has
changed. The implication of this is that immediately sequential 20-bit updates to the serial port
contain highly correlated information. To most efficiently post filter the CS5503 output data,
uncorrelated samples should be used. Samples
which have sufficiently reduced correlation can be
obtained if the CS5503 is allowed to execute 200
filter cycles between each subsequent data word
collected for post filtering.
eout = ein √

2f−3dB ⁄ fs
eout = 0.035 ein
where ein and eout are rms noise terms referred to
the input. Since f-3dB equals CLKIN/409,600 and
fs equals CLKIN/256, the digital filter reduces
white, broadband noise by 96.5% independent of
the CLKIN frequency. For example, a typical operational amplifier’s 50µV rms noise would be
reduced to 1.75µV rms (0.035 LSB’s rms at the
16-bit level in the CS5501 and 0.4 LSB’s rms at
the 20-bit level in the CS5503).
Simple high frequency analog filtering in the signal conditioning circuitry can aid in removing
energy at multiples of the sampling rate.
Bits of
Output
Accuracy
Filter
Cycles
CLKIN
Cycles
9
10
11
12
13
14
15
16
17
18
19
20
340
356
389
435
459
475
486
495
500
504
506
507
348,160
364,544
398,336
445,440
470,016
486,400
497,664
506,880
512,000
516,096
518,144
519,168
Table 5. Settling Time of the 6 Pole Low Pass Filter in
the CS5501 to 1/2 LSB Accuracy with a Full Scale
Step Input
24
24
The character of the noise in the data will influence the post filtering requirements. As a general
rule, averaging N uncorrelated data samples will
reduce noise by 1/√N. While this rule assumes
that the noise is white (which is true for the
CS5503 but not true for all real system signals
between dc and 10Hz), it does offer a starting
point for developing a post filtering algorithm for
removing the noise from the data. The algorithm
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
will have to be empirically tested to see if it meets
the system requirements. It is recommended that
any testing include input signals across the entire
input span of the converter as the signal level will
affect the amount of noise from the reference input which is transferred to the output data.
band-gap references are available which can supply 2.5 V for use with the CS5501/CS5503.
Many of these devices are not specified for noise,
especially in the 0.1 to 10 Hz bandwidth. Some
of these devices may exhibit noise characteristics
which degrade the performance of the
CS5501/CS5503.
Voltage Reference
Power Supplies And Grounding
The voltage reference applied to the VREF input
pin defines the analog input range of the
CS5501/CS5503. The preferred reference is 2.5V,
but the device can typically accept references
from 1V to 3V. Input signals which exceed 2.6V
(+ or -) can cause some linearity degradation. Figure 14 illustrates the voltage reference
connections to the CS5501/CS5503.
CS5501
CS5503
VA+
+5V
For Example
LT1019 -2.5
2.5 V
VREF
AGND
Figure 14. Voltage Reference Connections
The CS5501/CS5503 use the analog ground connection, AGND, as a measurement reference
node. It carries no power supply current. The
AGND pin should be used as the reference node
for both the analog input signal and for the reference voltage which is input into the VREF pin.
The analog and digital supply inputs are pinned
out separately to minimize coupling between the
analog and digital sections of the chip. To
achieve maximum performance, all four supplies
for the CS5501/CS5503 should be decoupled to
their respective grounds using 0.1 µF capacitors.
This is illustrated in the System Connection Diagram, Figure 15, at the beginning of this data
sheet.
The circuitry inside the VREF pin is identical to
that as seen at the AIN pin. The sample capacitor
(see Figure 12) requires packets of charge from
the external reference just as the AIN pin does.
Therefore the same settling time requirements apply. Most reference IC’s can handle this dynamic
load requirement without inducing errors. They
exhibit sufficiently low output impedance and
wide enough bandwidth to settle to within the
necessary accuracy in the requisite 64 CLKIN cycles.
As CMOS devices, the CS5501/CS5503 require
that the positive analog supply voltage always be
greater than or equal to the positive digital supply
voltage. If the voltage on the positive digital supply should ever become greater than the voltage
on the positive analog supply, diode junctions in
the CMOS structure which are normally reversebiased will become forward-biased. This may
cause the part to draw high currents and experience permanent damage. The connections shown
in Figure 15 eliminate this possibility.
Noise from the reference is filtered by the digital
filter, but the reference should be chosen to minimize noise below 10 Hz. The CS5501/CS5503
typically exhibit 0.1 LSB rms and 1.6 LSB rms
noise respectively. This specification assumes a
clean reference voltage. Many monolithic
To ensure reliable operation, be certain that power
is applied to the part before signals at AIN, VREF,
or the logic input pins are present. If current is
supplied into any pin before the chip is poweredup, latch up may result. As a system, it is
desirable to power the CS5501/CS5503, the volt-
DS31F5
DS31F4
25
25
CS5501 CS5503
CS5501/CS5503
10 Ω
+5V
Analog
Supply
0.1 µF
0.1 µF
14
VA+
13
4
Calibration
Control
0
-5V
Analog
Supply
12
200 Ω∗
VREF
or
±VREF
+5V
Analog
Supply
17
Bipolar/
Unipolar
Input Select
Analog
Signal
Source
15
9
VD+
CAL
CLKIN
SC1
CLKOUT
SC2
SLEEP
CS5501
CS5503
BP/UP
MODE
SCLK
AIN
0.0047 µF NPO
Voltage
Reference
+2.5V
0.1 µF
SDATA
10
8
DRDY
VREF
CS
AGND
DGND
VD6
VA7
3
2
Optional
Clock
Source
11
Sleep Mode
Control
1
Output
Mode Select
19
20
Serial
Data
Interface
18
16
Control
Logic
5
0.1 µF
Unused Logic Inputs
must be connected
to DGND or VD+
10 Ω
* Recommended to
reduce high
frequency noise
Figure 15. Typical Connection Diagram
age reference, and the analog signal conditioning
circuitry from the same primary source. If separate supplies are used, it is recommended that the
CS5501/CS5503 be powered up first. If a common power source is used for the analog signal
conditioning circuitry as well as the A/D converter, this power source should be applied
before application of power to the digital logic
supply.
The CS5501/CS5503 exhibit good power supply
rejection for frequencies within the passband (dc
to 10 Hz). Any small offset or gain error caused
by long term drift of the power supplies can be
26
26
removed by recalibration. Above 10 Hz the digital filter will provide additional rejection. When
the benefits of the digital filter are added to the
regular power supply rejection the effects of line
frequency variations (60 Hz) on the power supplies will be reduced greater than 120 dB. If the
supply voltages for the CS5501/CS5503 are generated with a dc-dc converter the operating
frequency of the dc-dc converter should not operate at the sampling frequency of the
CS5501/CS5503 or at integer multiples thereof.
At these frequencies the digital filter will not aid
in power supply rejection. See Anti-Alias Considerations section of this data sheet.
DS31F5
DS31F4
CS5501 CS5503
CS5501/CS5503
The recommended system connection diagram for
the CS5501/CS5503 is illustrated in Figure 15.
Note that any digital logic inputs which are to be
unused should be tied to either DGND or the
VD+ as appropriate. They should not be left floating; nor should they be tied to some other logic
supply voltage in the system.
Power-up and Initialization
Upon power-up, a calibration cycle must be initiated at the CAL pin to insure a consistent starting
condition and to initially calibrate the device. The
CAL pin must be strobed high for a minimum of
4 clock cycles. The falling edge will initiate a
calibration cycle. A simple power-on reset circuit
can be built using a resistor and capacitor (see
Figure 16). The resistor and capacitor values
should allow for clock or oscillator startup time,
and the voltage reference stabilization time.
reading will occur after a rising edge on SLEEP
occurs.
Battery Backed-up Calibrations
The CS5501/CS5503 use SRAM to store calibration information. The contents of the SRAM will
be lost whenever power is removed from the chip.
Figure 17 shows a battery back-up scheme that
can be used to retain the calibration memory during system down time and/or protect it against
intermittent power loss. Note that upon loss of
power, the SLEEP input goes low, reducing
power consumption to just 10 µW. Lithium cells
of 3.6 V are available which average 1750 mAhours before they drop below the typical 2 V
memory-retention specification of the
CS5501/CS5503.
10 Ω
1N4148
+5V
Vd
0.1 µF
1N4148
+5V
Vb
CS5501
C
CAL
R
SC2
SC1
8
5
11
1N4148
47kΩ
(2V+Vd) < Vb < 4.5V
15
14
VA+
VD+
CS5501
CS5503
AGND
DGND
SLEEP
VA7
-5V
Figure 16. Power-On Reset Circuitry
(Self-Calibration Only)
Due to the devices’ low power dissipation and
low temperature drift, no warm-up time is required to accommodate any self-heating effects.
Sleep Mode
The CS5501/CS5503 include a sleep mode
(SLEEP = DGND) which shuts down the internal
analog and digital circuitry reducing power consumption to less than 10 µW. All calibration
coefficients are retained in memory such that no
time is required after "awakening" for recalibration. Still, the CS5501/CS5503 will require time
for the digital filter to settle before an accurate
DS31F5
DS31F4
0.1 µF
0.1 µF
VD6
10 Ω
0.1 µF
Figure 17. Example Calibration Memory Battery
Back-Up Circuit
When SLEEP is active (SLEEP = DGND), both
VD+ and VA+ must remain powered to no less
than 2 V to retain calibration memory. The VDand VA- voltages can be reduced to 0 V but must
not be allowed to go above ground potential. The
negative supply must exhibit low source impedance in the powered-down state as the current into
the VA+ pin flows out the VA- pin. (AGND is
only a reference node. No power supply current
flows in or out of AGND.) Care should be taken
27
27
CS5501 CS5503
CS5503
CS5501
to ensure that logic inputs are maintained at either
VD+ ar DGND potential when SLEEP is low.
Note that battery life could be shortened if the +5 V
supply drops slowly during power-down. As the
supply drops below the battery voltage but not yet
below the logic threshold of the SLEEP pin, the
battery will be supplying the CS5501/CS5503 at
full power (typically 3 mA). Faster transitions at
SLEEP can be triggered using a resistive divider or
a simple resistor network to generate the SLEEP input from the +5 V supply.
28
28
Output Loading Considerations
To maximize performance of the CS5501/ CS5503,
the output drive currents from the digital output
lines should be minimized.
Schematic & Layout
Review Service
DS31F4
DS31F5
CS5501 CS5503
CS5501/CS5503
PIN DESCRIPTIONS
SERIAL INTERFACE MODE SELECT
CLOCK OUT
CLOCK IN
SYSTEM CALIBRATION 1
DIGITAL GROUND
NEGATIVE DIGITAL POWER
NEGATIVE ANALOG POWER
ANALOG GROUND
ANALOG IN
VOLTAGE REFERENCE
MODE
CLKOUT
CLKIN
SC1
DGND
VDVAAGND
AIN
VREF
1
20
2
19
3
18
4
17
5
16
6
15
7
14
8
13
9
12
10
11
SDATA
SCLK
DRDY
SC2
CS
VD+
VA+
CAL
BP/UP
SLEEP
SERIAL DATA OUTPUT
SERIAL CLOCK INPUT/OUTPUT
DATA READY
SYSTEM CALIBRATION 2
CHIP SELECT
POSITIVE DIGITAL POWER
POSITIVE ANALOG POWER
CALIBRATE
BIPOLAR/UNIPOLAR SELECT
SLEEP
* Pinout applies to both DIP and SOIC packages
Clock Generator
CLKIN; CLKOUT -Clock In; Clock Out, Pins 3 and 2.
A gate inside the CS5501/CS5503 is connected to these pins and can be used with a crystal or
ceramic resonator to provide the master clock for the device. Alternatively, an external (CMOS
compatible) clock can be input to the CLKIN pin as the master clock for the device. When not
in SLEEP mode, a master clock (CLKIN) should be present at all times.
Serial Output I/O
MODE -Serial Interface Mode Select, Pin 1.
Selects the operating mode of the serial port. If tied to VD- (-5V), the CS5501 will operate in
the UART-compatible AC mode for Asynchronous Communication. The SCLK pin will
operate as an input to set the data rate, and data will transmit formatted with one start and two
stop bits. If MODE is tied to DGND, the CS5501/CS5503 will operate in the SEC
(Synchronous External-Clocking) mode, with the SCLK pin operating as an input and the
output appearing MSB-first. If MODE is tied to VD+ (+5V), the CS5501/CS5503 will operate
in its SSC (Synchronous Self-Clocking) mode, with SCLK providing a serial clock output of
CLKIN/4 (25% duty-cycle).
DRDY -Data Ready, Pin 18.
DRDY goes low every 1024 cycles of CLKIN to indicate that new data has been placed in the
output port. DRDY goes high when all the serial port data is clocked out, when the serial port
is being updated with new data, when a calibration is in progress, or when SLEEP is low.
CS -Chip Select, Pin 16.
An input which can be enabled by an external device to gain control over the serial port of the
CS5501/CS5503.
DS31F4
DS31F5
29
29
CS5501 CS5503
CS5501/CS5503
SDATA -Serial Data Output, Pin 20.
Data from the serial port will be output from this pin at a rate determined by SCLK and in a
format determined by the MODE pin. It furnishes a high impedance output state when not
transmitting data.
SCLK -Serial Clock Input/Output, Pin 19.
A clock signal at this pin determines the output rate of the data from the SDATA pin. The
MODE pin determines whether the SCLK signal is an input or output. SCLK may provide a
high impedance output when data is not being output from the SDATA pin.
Calibration Control Inputs
SC1; SC2 -System Calibration 1 and 2, Pins 4 and 17.
Control inputs to the CS5501/CS5503’s calibration microcontroller for calibration. The state of
SC1 and SC2 determine which of the calibration modes is selected for operation (see Table 2).
BP/UP -Bipolar/Unipolar Select, Pin 12.
Determines whether the CS5501/CS5503 will be calibrated to measure bipolar (BP/UP = VD+)
or unipolar (BP/UP = DGND) input signals. Recalibration is necessary whenever the state of
BP/UP is changed.
CAL -Calibrate, Pin 13.
If brought high for 4 clock cycles or more, the CS5501/CS5503 will reset and upon returning
low a full calibration cycle will begin. The state of SC1, SC2, and BP/UP when CAL is
brought low determines the type and length of calibration cycle initiated (see Table 2). Also, a
single CAL signal can be used to strobe the CAL pins high on several CS5501/CS5503’s to
synchronize their operation. Any spurious glitch on this pin may inadvertently place the chip in
Calibration mode.
Other Control Input
SLEEP -Sleep, Pin 11.
When brought low, the CS5501/CS5503 will enter a low-power state. When brought high
again, the CS5501/CS5503 will resume operation without the need to recalibrate. After SLEEP
goes high again, the device’s output will settle to within +0.0007% of the analog input value
within 1.3/f-3dB, where f-3dB is the passband frequency. The SLEEP input can also be used to
synchronize sampling and the output updates of several CS5501/CS5503’s.
Analog Inputs
VREF -Voltage Reference, Pin 10.
Analog reference voltage input.
AIN -Analog Input, Pin 9.
30
30
DS31F4
DS31F5
CS5501 CS5503
CS5501/CS5503
Power Supply Connections
VD+ -Positive Digital Power, Pin 15.
Positive digital supply voltage. Nominally +5 volts.
VD- -Negative Digital Power, Pin 6.
Negative digital supply voltage. Nominally -5 volts.
DGND -Digital Ground, Pin 5.
Digital ground.
VA+ -Positive Analog Power, Pin 14.
Positive analog supply voltage. Nominally +5 volts.
VA- -Negative Analog Power, Pin 7.
Negative analog supply voltage. Nominally -5 volts.
AGND -Analog Ground, Pin 8.
Analog ground.
DS31F4
DS31F5
31
31
CS5501 CS5503
CS5501/CS5503
SPECIFICATION DEFINITIONS
Linearity Error
The deviation of a code from a straight line which connects the two endpoints of the A/D
Converter transfer function. One endpoint is located 1/2 LSB below the first code transition
and the other endpoint is located 1/2 LSB beyond the code transition to all ones. Units in
percent of full-scale.
Differential Linearity
The deviation of a code’s width from the ideal width. Units in LSB’s.
Full-Scale Error
The deviation of the last code transition from the ideal (VREF-3/2 LSB’s). Units in LSBs.
Unipolar Offset
The deviation of the first code transition from the ideal (1/2 LSB above AGND) when in
unipolar mode (BP/UP low). Units in LSBs.
Bipolar Offset
The deviation of the mid-scale transition (011...111 to 100...000) from the ideal (1/2 LSB
below AGND) when in bipolar mode (BP/UP high). Units in LSBs.
Bipolar Negative Full-Scale Error
The deviation of the first code transition from the ideal when in bipolar mode (BP/UP high).
The Ideal is defined as lying on a straight line which passes through the final and mid-scale
code transitions. Units in LSBs.
Positive Full-Scale Input Overrange
The absolute maximum positive voltage allowed for either accurate system calibration or
accurate conversions. Units in volts.
Negative Full-Scale Input Overrange
The absolute maximum negative voltage allowed for either accurate system calibration or
accurate conversions. Units in volts.
Offset Calibration Range
The CS5501/CS5503 calibrate their offset to the voltage applied to the AIN pin when in system
calibration mode. The first code transition defines Unipolar Offset when BP/UP is low and the
mid-scale transition defines Bipolar Offset when BP/UP is high. The Offset Calibration Range
specification indicates the range of voltages applied to AIN that the CS5501 or CS5503 can
accept and still calibrate offset accurately. Units in volts.
Input Span
The voltages applied to the AIN pin in system-calibration schemes define the CS5501/CS5503
analog input range. The Input Span specification indicates the minimum and maximum input
spans from zero-scale to full-scale in unipolar, or from positive full scale to negative full scale
in bipolar, that the CS5501/CS5503 can accept and still calibrate gain accurately. Units in
volts.
32
32
DS31F4
DS31F5
CS5501 CS5503
ORDERING INFORMATION
Model
Package
CS5501-BP
Resolution
Throughput
Linearity
Temperature
4 kSps
0.0015
-40 to +85 °C
20-pin Plastic DIP
CS5501-BS
CS5501-BSZ (lead free)
CS5503-BP
20-pin SOIC
16 Bits
20-pin Plastic DIP
CS5503-BS
CS5503-BSZ (lead free)
20-pin SOIC
20 Bits
ENVIRONMENTAL, MANUFACTURING, & HANDLING INFORMATION
Model
Peak Relfow Temp
MSL Rating*
Maximum Floor Life
CS5501-BP
260 °C
1
No Limit
CS5501-BS
240 °C
2
365 Days
CS5501-BSZ (lead free)
260 °C
3
7 Days
CS5503-BP
260 °C
1
No Limit
CS5503-BS
240 °C
2
365 Days
CS5503-BSZ (lead free)
260 °C
3
7 Days
* MSL (Moisture Sensitivity Level) as specified by IPC/JEDEC J-STD-020.
DS31F5
33
CS5501 CS5503
CS5501/CS5503
and returns high as the last bit shifts out. Therefore, the DRDY pin can be polled for a rising
transition directly, or it can be latched as a levelsensitive interrupt.
APPENDIX A: APPLICATIONS
Parallel Interface
Figures A1 and A2 show two serial-to-parallel
conversion circuits for interfacing the CS5501 in
its SSC mode to 16- and 8-bit systems respectively. Each circuit includes an optional
74HCT74 flip-flop to latch DRDY and generate
a level-sensitive interrupt.
With the CS input tied low the CS5501 will shift
out every available sample (4kHz word rate with
a 4MHz master clock). Lower output rates (and
interrupt rates) can be generated by dividing
down the DRDY output and applying it to CS.
Both circuits require that the parallel read process
be synchronized to the CS5501’s operation. That
is, the system must not try to enable the registers’ parallel output while they are accepting
serial data from the CS5501. The CS5501’s
DRDY falls just prior to serial data transmission
Totally asynchronous interfaces can be created
using a Shift Data control signal from the system
which enables the CS5501’s CS input and/or the
shift registers’ S1 inputs. The DRDY output can
then be used to disable serial data transmission
once an output word has been fully registered.
+5V
+5V
CS5501
CS5503
SDATA
MODE
A
PA
D0
PB
D1
PC
D2
PD
D3
PE
D4
PF
D5
PG
D6
PH
OE2 OE1
D7
SCLK
74HCT299
+5V
CS
DRDY
S1
S2
QH
S1
S2
OE1
74HCT299
A
OE2
PA
D8
PB
D9
PC
D10
PD
D11
PE
D12
PF
D13
74HCT74
CS
PG
D14
RESET
PH
D15
D
SET
Q
INT
Q
Only needed for
interrupt driven systems
DRDY
(For polling)
Figure A1. 16-bit Parallel Interface
34
34
DS31F4
DS31F5
CS5501 CS5503
CS5501/CS5503
In such asynchronous configurations the CS5501
is operated much like a successive-approximation
converter with a Convert signal and a subsequent
read cycle.
If it is required to latch the 16-bit data, then 2
74HC595 8-bit "shift register with latch" parts
may be used instead of 74HC299’s.
own serial clock. The routine also sets the
CS5501 into a known state.
For each interface, a second subroutine is also
provided which will collect one complete 16-bit
output word from the CS5501. Figure A5 illustrates the detailed timing throughout the
subroutine for one particular interface - the
COPS family interface of Figure A4.
Serial Interfaces
Figures A3 to A8 offer both the hardware and
software interfaces to several industry-standard
microcontrollers using the CS5501’s SEC and
AC output modes. In each instance a system initialization routine is provided which configures
the controller’s I/O ports to accept the CS5501’s
serial data and clock outputs and/or generate its
+5V
+5V
+5V
CS5501
CS5503
MODE
PB
SCLK
CS
DRDY
PA
A
S1
S2
74HCT299
SDATA
PC
PD
PE
PF
PG
QH
PH
OE2 OE1
D0
D1
D2
D3
D4
D5
D6
D7
CS
A0
S1
S2
74HCT299
B
PC D10
P D11
D
PE D12
P D13
F
PG D14
P D15
H
DB0
DB1
D
SET
DB4
74HCT74
OE2 OE1
PA D8
P D9
A
DB5
RESET
DB2
DB3
DB6
DB7
Q
INT
Q
Only needed for
interrupt driven systems
DRDY
(For polling)
Figure A2. 8-Bit Parallel Interface
DS31F4
DS31F5
35
35
CS5501 CS5503
CS5501/CS5503
CS5501
CS
CS5503
SCLK
MODE
SDATA
Initial Code:
68HC11
PA6
SCK
+5V
SS
MISO
SPINIT: PSHA
LDAA
STAA
LDAA
STAA
LDAA
(68HC05)
STAA
LDAA
STAA
LDAA
LDAA
PULA
RTS
Figure A3. 68HC11/CS5501 Serial Interface
Notes:
1. CS5501 in Synchronous External Clocking mode.
2. Using 68HC11’s SPI port. (Can use SCI and
CS5501’s Asynchronous mode.)
3. Maximum bit rate is 1.05 Mbps.
Assumptions:
1.
2.
3.
4.
5.
PA6 used as CS.
68HC11 in single-chip mode.
Receive data via polling.
Normal equates for peripheral registers.
Data returned in register D.
CS5501
CS5503 CS
MODE
SCLK
SDATA
COPS 444
G0
SK
DI
(All COPS)
Figure A4. COPS/CS5501 Interface
Notes:
1. CS5501 in Synchronous External Clocking mode.
2. COPS 444 max baud = 62.5 kbps. (Others = 500 kbps)
3. See timing diagram for detailed timing.
Assumptions:
1. G0 used as CS.
2. Register 0 (upper four nibbles) used to store 16-bit word.
36
36
#%x1xxxxxx
PORTA
#$10
SPCR
#%xx0110xx
DDRD
#$50
SPCR
SPSR
SPDR
;
;
;
;
;
;
;
;
;
;
;
;
;
;
Store temporary copy of A
Bit 6 = 1, all others are don’t cares
CS = 1, inactive; deselect CS5501
Disable serial port
SS-input, SCK-output,
MOSI-output, MISO-input
Data direction register for port D
Enable serial port, CMOS outputs,
master, highest clock rate (int. clk/2)
Bogus read to clr port and SPIF flag
Restore A
Code to get word of data:
SP_IN:
LDAA
STAA
STAA
WAIT1: LDAA
BPL
LDAA
STAA
WAIT2: LDAB
BPL
LDAB
STAB
LDAB
RTS
#%x0xxxxxx
PORTA
SPDR
SPSR
WAIT1
SPDR
SPDR
SPSR
WAIT2
#%x1xxxxxx
PORTA
SPDR
;
; CS = 0, active; select CS5501
; Put data in serial port to start clk
; Get port status
; If SPIF (MSB) 0, no data yet, wait
; Put most significant byte in A
; Start serial port for second byte
; Get port status
; If SPIF (MSB) 0, no data yet, wait
;
; CS = 1, inactive; deselect CS5501
; Put least significant byte in B
;
Initial Code:
SPINIT: OGI
RC
XAS
15
; CS = 1, inactive; deselect CS5501
; Reset carry, used in next
; instruction to turn SK off
Code to get word of data:
SP_IN:
LBI
0,12
SC
OGI
LEI
XAS
NOP
NOP
GETNIB: NOP
XAS
XIS
JP
RC
XAS
OGI
RET
14
0
GETNIB
15
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
Point to start of data
storage location
Set carry - enables SK in
XAS instruction
CS = 0, active; select CS5501
Shift register mode, S0 = 0
Start clocking serial port
Wait for (first) M.S. nibble
Get nibble of data from SIO
Put nibble in memory, inc. pointer,
if overflow, jump around this inst.
Reset carry - disables SK in XAS
instruction
Bogus read - stops SK
CS = 1, inactive; deselect CS5501
DS31F4
DS31F5
CS5501 CS5503
CS5501/CS5503
Instruction
GDAT:
LBI
SC
OGI
LEI
XAS
NOP
NOP
GETLP:
XAS
NOP
XIS
SYNC
(COPS internal)
CS (G0)
A
Shift in
SIO
SCLK (SK)
HI-Z
DATA (SI)
Instruction
B15 (MSB)
JP GETLP:
GETLP NOP
XAS
XIS
B14
B13
JP GETLP:
GETLP NOP XAS
B12
XIS
B11
B10
JP GETLP:
GETLP NOP
SYNC
(COPS internal)
CS (G0)
A
SIO
A
SIO
SCLK (SK)
DATA (SI)
B10
B9
B8
B7
B6
B5
B4
B3
B2
B1
B0
skip
Instruction
XAS
JP
XIS GETLP
RC
XAS
OGI
RET
SYNC
(COPS internal)
CS (G0)
A
SIO
SCLK (SK)
DATA (SI)
B0
HI-Z
Figure A5. Serial Timing Example - COPS
DS31F4
DS31F5
37
37
CS5501 CS5503
CS5501/CS5503
CS5501
MODE
8051
DRDY
INT1
CS
P1.1
SCLK
P1.2
SDATA
P1.3
Figure A6. MCS51 (8051) /CS5501 Serial Interface
Notes:
1. CS5501 in Synchronous External Clocking mode.
2. Interrupt driven I/O on 8051 (For polling, connect
DRDY to another port pin).
Assumptions:
1. INT1 external interrupt used.
2. Register bank 1, R6, R7 used to store data word,
R7 MSbyte.
3. EA enabled elsewhere.
CS
SCLK
DATA
SPINIT:
EQU
EQU
EQU
CLR
SETB
SETB
SETB
CLR
SETB
P1.1
P1.2
P1.3
EX1
IT1
DATA
CS
SCLK
EX1
;
;
;
;
;
;
Disable INT1
Set INT1 for falling edge triggered
Set DATA to be input pin
CS = 1; deselect CS5501
SCLK low
Enable INT1 interrupt
Code to get word of data:
ORG 0003H
LJMP GETWD
GETWD: PUSH PSW
PUSH A
MOV PSW,#08
MOV R6,#8
CLR
CS
MSBYTE:SETB SCLK
MOV C,DATA
CLR
SCLK
RLC
A
DJNZ R6,MSBYTE
MOV R7,A
MOV R6,#8
LSBYTE: SETB SCLK
MOV C,DATA
CLR
SCLK
RLC
A
DJNZ R6,LSBYTE
MOV R6,A
SETB CS
POP A
POP PSW
RETI
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
;
Interrupt vector
Save temp. copy
Save temp. copy
Set register bank 1 active
number of bits in a byte
CS = 0; select CS5501
Toggle SCLK high
Put bit of data into carry bit
Toggle SCLK low; next data bit
Shift DATA bit into A register
Dec. R6, if not 0, get another bit
Put MSbyte into R7
Reset R6 to number of bits in byte
Toggle SCLK high
Put bit of data into carry bit
Toggle SCLK low; next data bit
Shift DATA bit into A register
Dec. R6, if not 0, get another bit
Put LSbyte into R6
CS = 1; deselect CS5501
Restore original value
Restore original value
CS
P1.2
(Assumptions cont.)
3. Word received put in A (ACC) and B registers,
A = MSbyte.
4. No error checking done.
5. Equates used for peripheral names.
SDATA
RXD
Initial Code:
CS5501
8051
SCLK
MODE
32
OSC
-5V
Figure A7. MCS51 (8051) /CS5501 UART Interface
Notes:
1. CS5501 in Asynchronous (UART-like) mode.
2. 8051 in mode 2, with OSC = 12 MHz,
max baud = 375 kbps.
Assumptions:
1. P1.2 (port 1, bit 2) used as CS.
2. Using serial port mode 2, Baud rate = OSC/32.
38
38
Initial Code:
SPINIT: SETB SMOD
; Set SMOD = 1, baud = OSC/32
SETB P1.2
; CS = 1, inactive
MOV SCON,#1001000B
; Enable serial port mode 2,
; receiver enabled, transmitter disabled
CLR
ES
; Disable serial port interrupts (polling)
RET
;
Code to get word of data:
SP_IN:
CLR
JNB
CLR
MOV
JNB
CLR
MOV
SETB
RET
P1.2
RI,$
RI
A,SBUF
RI,$
RI
B,SBUF
P1.2
;
;
;
;
;
;
;
;
;
CS = 0, active; select CS5501
Wait for first byte
Put most significant byte in A
wait for second byte
Put least significant byte in B
CS = 1, inactive; deselect CS5501
DS31F4
DS31F5
CS5501 CS5503
CS5501/CS5503
CS5501
TMS70X2
CS
MODE
SCLK
SDATA
-5V
A0
SCLK
RXD
(TMS70CX2)
Figure A8. TMS70X2/CS5501 Serial Interface
Initial Code:
SPINIT: DINT
MOVP
MOVP
MOVP
MOVP
MOVP
MOVP
MOVP
MOVP
;
%1,ADDR
; A port is output
%1,APORT ; A0 = 1, (CS is inactive)
%0,P17
;
%>10,SCTLO ; Resets port errors
%?x1x01101,SMODE ; Set port for Isosync,
%?00x1110x,SCTLO ;
8 bits, no parity
%07,T3DATA ; Max baud rate
%?01000000,SCTL1 ; No multiprocessor;
;
prescale = 4
MOVP %0,IOCNT1 ; Disable INT4 - will poll port
PUSH A
; Store original
MOVP RXBUF,A
; Bogus read to clr receiver port flag
POP A
; Restore original
EINT
;
RET
;
Notes:
1. CS5501 in Asynchronous (UART-like) mode.
2. TMS70X2 in Isosynchronous mode.
3. TMS70X2 with 8 MHz master clock has max
baud =1.0 Mbps.
Assumptions:
1.
2.
3.
4.
5.
Code to get word of data:
SP_IN:
WAIT1
WAIT2
A0 used as CS.
Receive data via polling.
Word received put in A and B upon return, A = MS byte.
No error checking done.
Normal equates for peripheral registers.
DS31F4
DS31F5
MOVP
BTJZP
MOVP
BTJZP
MOVP
MOVP
RET
%0,APORT ; CS active, select CS5501
%2,SSTAT,WAIT1
; Wait to receive first byte
RXBUF,A
; Put most significant byte in reg. A
%2,SSTAT,WAIT2
; Wait to receive second byte
RXBUF,B
; Put least significant byte in reg. B
%1,APORT ; CS inactive, deselect CS5501
;
39
39
CS5501 CS5503
Contacting Cirrus Logic Support
For all product questions and inquiries contact a Cirrus Logic Sales Representative.
To find the one nearest to you go to www.cirrus.com
IMPORTANT NOTICE
Cirrus Logic, Inc. and its subsidiaries (“Cirrus”) believe that the information contained in this document is accurate and reliable. However, the information is subject to
change without notice and is provided “AS IS” without warranty of any kind (express or implied). Customers are advised to obtain the latest version of relevant infor
mation to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied
at the time of order acknowledgment, including those pertaining to warranty, indemnification, and limitation of liability. No responsibility is assumed by Cirrus for the
use of this information, including use of this information as the basis for manufacture or sale of any items, or for infringement of patents or other rights of third parties
This document is the property of Cirrus and by furnishing this information, Cirrus grants no license, express or implied under any patents, mask work rights, copyrights
trademarks, trade secrets or other intellectual property rights. Cirrus owns the copyrights associated with the information contained herein and gives consent for copies
to be made of the information only for use within your organization with respect to Cirrus integrated circuits or other products of Cirrus. This consent does not extend
to other copying such as copying for general distribution, advertising or promotional purposes, or for creating any work for resale.
CERTAIN APPLICATIONS USING SEMICONDUCTOR PRODUCTS MAY INVOLVE POTENTIAL RISKS OF DEATH, PERSONAL INJURY, OR SEVERE PROPER
TY OR ENVIRONMENTAL DAMAGE (“CRITICAL APPLICATIONS”). CIRRUS PRODUCTS ARE NOT DESIGNED, AUTHORIZED OR WARRANTED FOR USE IN
AIRCRAFT SYSTEMS, MILITARY APPLICATIONS, PRODUCTS SURGICALLY IMPLANTED INTO THE BODY, AUTOMOTIVE SAFETY OR SECURITY DEVICES
LIFE SUPPORT PRODUCTS OR OTHER CRITICAL APPLICATIONS. INCLUSION OF CIRRUS PRODUCTS IN SUCH APPLICATIONS IS UNDERSTOOD TO BE
FULLY AT THE CUSTOMER'S RISK AND CIRRUS DISCLAIMS AND MAKES NO WARRANTY, EXPRESS, STATUTORY OR IMPLIED, INCLUDING THE IMPLIED
WARRANTIES OF MERCHANTABILITY AND FITNESS FOR PARTICULAR PURPOSE, WITH REGARD TO ANY CIRRUS PRODUCT THAT IS USED IN SUCH A
MANNER. IF THE CUSTOMER OR CUSTOMER'S CUSTOMER USES OR PERMITS THE USE OF CIRRUS PRODUCTS IN CRITICAL APPLICATIONS, CUSTOM
ER AGREES, BY SUCH USE, TO FULLY INDEMNIFY CIRRUS, ITS OFFICERS, DIRECTORS, EMPLOYEES, DISTRIBUTORS AND OTHER AGENTS FROM ANY
AND ALL LIABILITY, INCLUDING ATTORNEYS' FEES AND COSTS, THAT MAY RESULT FROM OR ARISE IN CONNECTION WITH THESE USES.
Cirrus Logic, Cirrus, and the Cirrus Logic logo designs are trademarks of Cirrus Logic, Inc. All other brand and product names in this document may be trademarks o
service marks of their respective owners.
40
DS31F5
CDB5501
CDB5501
CDB5503
CDB5503
CS5501
& CS5503 Evaluation
Evaluation Board
Boards
CS5501/CS5503
I
Features
Description
l Operation with on-board clock generator, on-
The CDB5501/CDB5503 is an evaluation board designed for maximum flexibility when evaluating the
CS5501/CS5503 A/D converters. The board can easily
be configured to evaluate all the features of the
CS5501/CS5503, including changes in master clock
rate, calibration modes, output decimation rates, and interface modes.
board crystal, or an off-board clock source.
l DIP switch selectable or micro port
controllable:
- Unipolar/Bipolar input range
- Sleep Mode-All Cal Modes
l On-board Decimation Counter
l Multiple Data Output Interface Options:
The evaluation board interfaces with most microcontrollers and allows full control of the features of the CS5501
or CS5503. DIP switch selectable control is also available in the event a microcontroller is not used. The
evaluation board also offers computer data interfaces including RS-232 and parallel port outputs for evaluating
the CS5501.
- RS-232 (CS5501)
- Parallel Port (CS5501)
- Micro Port (CS5501 & CS5503)
All calibration modes are selectable including Self-Cal,
System Offset Cal, and System Offset and System Gain
Cal. A calibration can be initiated at any time by pressing
the CAL pushbutton switch.
ORDERING INFORMATION
CDB5501
CDB5503
Evaluation Board
Evaluation Board
I
CS5501/
CS5503
Micro
Port
Divider
AIN
Parallel
Port
Header
CLKIN
Header
Decimation
Counter
OSC
+5
Cirrus Logic, Inc.
Crystal
Semiconductor Products Division
http://www.cirrus.com
P.O. Box 17847, Austin, Texas 78760
(512) 445 7222 FAX: (512) 445 7581
http://www.crystal.com
-5
GND
Copyright
 Cirrus
Copyright © Cirrus
Logic, Inc.
2005Logic, Inc. 1998
(All Rights Reserved)
(All Rights Reserved)
RS-232
Port
Sub D
VREF
AUG ‘95
‘05
MAR
DS31DB4
DS31DB3
41
CDB5501 CDB5503
CDB5501/CDB5503
INTRODUCTION
The CDB5501/CDB5503 evaluation board provides maximum flexibility for controlling and
interfacing to the CS5501/CS5503 A/D converters. The CS5501 or the CS5503 require a minimal
amount of external circuitry. The devices can operate with a crystal (or ceramic resonator) and a
voltage reference.
The evaluation board includes several clock
source options, a 2.5 volt trimmable reference,
and circuitry to support several data interface
schemes. The board operates from +5 and -5 volt
power supplies.
Evaluation Board Overview
The CDB5501/CDB5503 evaluation board includes extensive support circuitry to aid
evaluation of the CS5501/CS5503. The support
circuitry includes the following sections:
1) A clock generator which has an on-board
oscillator and counter divider IC.
2) A 2.5 volt trimmable voltage reference.
3) A Decimation Counter.
4) A parallel output port (for CS5501 only).
5) An RS-232 interface (for CS5501 only).
6) A micro port (for CS5501 or CS5503).
7) DIP switch and CAL pushbutton.
Clock Generator
The CS5501/CS5503 can operate off its on-chip
oscillator or an off-chip clock source. The evaluation board includes a 4.9152 MHz gate oscillator
and counter-divider chain as the primary clock
source for the CS5501/CS5503. The counter-divider outputs offer several jumper-selectable
frequencies as clock inputs to the
CS5501/CS5503. The 4.9152 MHz crystal frequency was chosen to allow the counter-divider
chain to also provide the common serial data rates
42
42
(1200, 2400, 4800, etc.) when the CDB5501
evaluation board is configured to provide RS-232
data output. If a different operating frequency for
the CS5501/CS5503 is desired, three options exist. First, a BNC input is provided to allow an
external CMOS (+5V) compatible clock to be
used. Second, the crystal (Y1) in the on-board
gate oscillator can be changed. Or, third, the onchip oscillator of the CS5501/CS5503 can be
used with a crystal connected in the Y2 position.
2. 5 Volt Reference
A 2.5 volt (LT1019CN8-2.5) reference is provided on the board. Potentiometer R9 allows the
initial value of the reference to be accurately
trimmed.
Decimation Counter
The CS5501/CS5503 updates its internal output
register with a 16-bit word every 1024 clock cycles of the master clock. Each time the output
register is updated the DRDY line goes low. Although output data is updated at a high rate it
may be desirable in certain applications to activate the CS to read the data at a much lower rate.
A decimation counter is provided on the board for
this purpose. The counter reduces the rate at
which the CS line of the CS5501 is activated by
only allowing CS to occur at a sub-multiple of the
DRDY rate.
Parallel Output Port (for CS5501 only)
The output data from the CS5501/CS5503 is in
serial form. Some applications may require the
data to be read in parallel format. Therefore the
evaluation board includes two 8-bit shift registers
with three-state outputs. Data from the CS5501 is
shifted into the registers and then read out in
16 bit parallel fashion. The parallel port comes set
up for 16-bit parallel output but can be reconfigured to provide two 8-bit reads. The parallel port
supports the CS5501 only, since the CS5503 outputs 20-bit words.
DS31DB3
DS31DB4
CDB5501 CDB5503
CDB5501/CDB5503
RS-232 Port (for CS5501 only)
Jumper Selections
The CS5501 has a data output mode in which it
formats the data to be UART compatible; each
serial output byte is preceded by a start bit and
terminated with two stop bits. Serial data in this
format is commonly transferred using the RS-232
data interface. Therefore the evaluation board includes an RS-232 driver and output connector.
The CS5503 does not provide this output mode.
The evaluation board has many jumper selectable
options. This table describes the jumper selections
available.
P1 Selects between the on-board 4.9152 MHz
oscillator (INT) or an external (EXT) clock
source as the input to the clock generator/
divider chain.
P2 Allows any of the counter/divider output
clock rates to be selected as the input clock
to the CS5501/CS5503.
Micro Port
The CS5501/CS5503 was designed to be compatible with many micro-controllers. Therefore the
evaluation board provides access to all of the data
output pins and the control pins of the
CS5501/CS5503 on header connectors.
P3 Allows selection of baud rate clocks when
the CS5501 is in the UART compatible mode.
When using the on-board 4.9152 MHz standard baud rates between 1200 and 19,200 are
available.
DIP Switch and CAL Pushbutton
P4 Selects the divide ratio of the Decimation
Counter.
1
U1A
3
2
4.9152 MHz
C1
30 pF
Y1
P1
74HC00 TP1
INTCLK
5
6
4 U1B
R2
5.1 k
EXTCLK
P5 Selects one of the three available output data
modes of the CS5501 or one of two available
output data modes of the CS5503.
P9 Enables the output of the Decimation
Counter to control the CS line of the
CS5501/CS5503.
P11 Connects the baud clock from the on-board
clock divider as the input to the SCLK pin
of the CS5501/CS5503.
V+
47 k
RN 1.3
R1
10 M
RN 1.2
47 k
Although all of the control lines to the
CS5501/CS5503 are available on header connectors at the edge of the board, it is preferable to not
require software control of all of these pins.
Therefore DIP switch control is provided on some
of these control lines. The CAL input to the
CS5501/CS5503 is made available at a header pin
for remote control, but pushbutton control of CAL
is also provided.
C3
0.1 µF
12
13
14
U1C
TP3
11
7
C2
30 pF
10
CL
11
R
P2
16
U2
74HC4040
1
9
8
2 3 4 5 6 7 8 9 10 11 12
7 6 5 3 2 4 13 12 14 15 1
V+
C5
0.1 µF
P3
TP2
CLKIN
R3
200
9
8
10 U1D
N= 0
1
2 3 4 5
Master Clock
TP4
6
7
TP5
8
9 10 11 12
Baud Clock
BRCLK (fig. 2)
CLKIN (fig. 2)
Figure 1. Clock Generator
DS31DB3
DS31DB4
43
43
CDB5501 CDB5503
CDB5501/CDB5503
Connector P1 allows jumper selection of either an
external clock or the on-board 4.9152 MHz crystal oscillator (See Figure 1 for schematic) as the
clock source for the CLKIN signal on pin 3 of the
CS5501/CS5503 (shown in Figure 2).
Clock Options
Several clock source options are available. These
include:
1) an external clock (+5 V CMOS-Compatible);
2) an on-board 4.9152 MHz crystal oscillator
with a 2n divider (n = 1, 2, …7);
If the EXT position is selected, a CMOS-compatible clock signal (5 volt supply) should be input
to the BNC connector labeled CLKIN. If the INT
position is selected the 4.9152 MHz oscillator
output is input to counter/divider IC U2. In either
3) a 4.096 MHz crystal.
V+10
S
12
9
D
Q
U8B
74HC74
11
8
Q
CL
R
U6 2 V+13
1
V+
TP6
10
11
CL
R
16 0.1 µF
C5
U3
74HC4040
1 2 3 4 5 6 7 8 9 10 11 12 8
9 7 6 5 3 2 4 13 12 14 15 1
P4
N= 0 1 2 3 4
Decimation Counter
5
6
7
8
9 10 11
NC
TP7
2
1
16
CS
Y2
CLKIN
(fig. 1)
3
CLKOUT
DRDY
(fig. 4)
TP8
DRDY 18
V+
CLKIN
SDATA
SDATA
(fig. 3, 4)
TP10
20
U4
CS5501/
CS5503
DC
P9
3
U7
74HC126
C15
0.1 µF
P10
R17
100 k
14
5
6
U7
4 7
SCLK
(fig. 3)
9
R 13
100 k
V+
14
R 11
100 k
1
3
5
2
4
6
P5
V+
U7
9
R 12
100 k
V-
MODE: SSC SEC AC*
1 CS
3 DR
C23
0.1 µF
RN 3.5
47 k
4 5
6
6
U6 U6 7
74HCT04
TP9
2
4
3
SCLK 19
MODE 1
47 k
V+
RN 3.8
2
DCS
(fig. 3)
R 14
100 k
8
10
8
5 SD
7 SCO
V+
U6
8
13 12
11U7
P11
RN 3.5
47 k
10
9 SCI
BC NC
BRCLK
(fig. 1)
*AC Mode available only in CS5501
Figure 2. Decimation Counter / Microport
44
44
DS31DB3
DS31DB4
CDB5501 CDB5503
CDB5501/CDB5503
Data Output from the CS5501/CS5503
P-1
INT CLK
EXT CLK
CLKIN Source to CS5501/CS5503
On-Board 4.9152 MHz OSC
+5 CMOS CLKIN BNC
CLKIN Rate Selection (CLK/2n) with INT CLK on P1 selected.
CLK = 4.9152 MHz
P-2
0
1
2
3
4
5
6
7
CLKIN Rate
4.9152 MHz
2.4576 MHz
1.2288 MHz
614.4 kHz
307.2 kHz
153.6 kHz+
76.8 kHz+
38.4 kHz* +
* Exceeds CLKIN Specifications of CS5501.
+ Exceeds CLKIN specifications of CS5503.
Table 1. Clock Generator
case, the counter divides the input clock by 2n
where n = 0, 1, …7. Any of the binary sub-multiples of the counter input clock can be input to the
CS5501/CS5503 by jumper selection on connector P2.
The CS5501/CS5503 contains its own on-chip oscillator which needs only an external crystal to
function. Ceramic resonators can be used as well
although ceramic resonators and low frequency
crystals will require loading capacitors for proper
operation.
To test the oscillator of the CS5501/CS5503 with
a crystal (Y2) a jumper wire near crystal Y2 must
be opened and another jumper wire soldered into
the appropriate holes provided to connect the
crystal to the chip. Additional holes are provided
on the board for loading capacitors.
The CS5501 has three available data output
modes (The CS5503 has two available data output modes). The operating mode of the part is
determined by the input voltage level to the
MODE (pin 1) pin of the device. Once a mode is
selected, four other pins on the device are involved in data output. The first of these is the
DRDY pin (pin 18). It is an output from the chip
which signals whenever a new data word is available in the internal output register of the
CS5501/CS5503. Data can then be read from the
register, but only when the CS pin (pin 16) is
low.
When CS is low, data bits are output in serial
form on the SDATA pin (pin 20). In the Synchronous Self-Clocking mode of the
CS5501/CS5503, the chip provides an output data
clock from the SCLK pin (pin 19). This output
clock is synchronous with the output data and can
be used to clock the data into an external register.
In Synchronous External-Clocking and Asynchronous Communications modes of the CS5501, the
SCLK pin is an input for an external clock which
determines the rate at which data bits appear at
the SDATA output pin. In the CS5503, only synchronous external-clocking mode is available.
The signals necessary for reading data from the
CS5501/CS5503 are all available on connector
P10 as shown in Figure 2.
P-5
SSC
SEC
AC*
Data Output Mode
Synchronous Self-Clocking
Synchronous External-Clocking
Asynchronous Communications
* Available in CS5501 only.
Table 2. Data Output Mode
DS31DB3
DS31DB4
45
45
CDB5501 CDB5503
CDB5501/CDB5503
CS5501/CS5503 Data Output Mode Selection
Connector P5 (see Figure 2) allows jumper selection of any one of the three data output modes.
These modes are:
1) SSC (Synchronous Self-Clocking);
2) SEC (Synchronous External Clocking);
3) AC (Asynchronous Communication).
(AC mode is available only in the CS5501)
SSC (Synchronous Self-Clocking) Mode
The SSC mode is designed for interface to those
microcontrollers which allow external clocking of
their serial inputs. The SSC mode also allows
easy connection to serial-to-parallel conversion
circuitry.
In the SSC mode serial data and serial clock are
output from the CS5501/CS5503 whenever the
CS line is activated. As illustrated in Figure 2, all
of the signals are available at connector P10. If
the CS signal is to be controlled remotely the
jumper on P9 should be placed in the NC (No
Connection) position. This removes the Decimation Counter output from controlling the CS line.
Data Output Interface: Parallel Port (for
CS5501 evaluation only).
Whenever the CS5501 is operated in the SSC
mode the 16-bit output data is clocked into two
8-bit shift registers. The registers have three-state
parallel outputs which are available at P7 (see
Figure 3). A flip-flop (U8A) is used to signal the
remote reading device whenever the registers are
updated. The PDR (Parallel Data Ready) signal
from the flip-flop is available on P7. The Q-bar
output from the flip-flop locks out any further updates to the registers until their data is read and a
DACK (Data ACKnowledge) signal is received
from the remote device.
Activation of the CS line determines the rate at
which the CS5501 will attempt to update the output shift registers. Data will be shifted into the
46
46
registers only if a DACK signal has occurred
since the last update.
The CS line can be controlled remotely at P10 or
by the output of the Decimation Counter. If CS is
controlled remotely, the Decimation divide
jumper on P4 should be placed in the "0" position. This insures that the DCS signal will occur
at the same rate CS is activated. The positive going edge of DCS toggles the U8A flip-flop which
signals an update to the parallel port.
The parallel registers are set up to be read in 16bit parallel fashion but can be configured to be
read separately as two 8-bit bytes on an 8-bit bus.
To configure the board for byte-wide reads, the
byte-wide jumpers must be soldered in place. In
addition, for proper "one byte at a time" address
selection, a connection on the circuit board needs
to be opened and a jumper wire soldered in the
proper place to determine which register is to be
read when A0 is a "1" and vice versa. See Figure
3 for schematic details. The evaluation board
component layout diagram, Figure 7, indicates the
location of the byte-wide jumpers and A0 address
selection jumpers.
After data is read from the registers a DACK
(Data Acknowledge) signal is required from the
off-board controller to reset flip-flop U8A. This
enables the registers to accept data input once
again.
The DRB and CSB signals on connector P10
should be used to monitor and control the
CS5501 output to the serial to parallel conversion
registers. Be aware that an arbitrarily timed
DACK signal may cause the output data registers to be enabled in the middle of an output
word if the CS signal to the CS5501 is not
properly sequenced. This will result in incorrect
data in the output registers.
If the Decimation Counter is used to control the
output of the CS5501 (Jumper on P9 in the DC
position), the CSB signal on P10 can be moniDS31DB3
DS31DB4
CDB5501 CDB5503
CDB5501/CDB5503
V+
RN 3.4
47 k
TP18
Vcc
C14
0.1 µF
4
5
2 10
6
3
1
11
Header
TP17
PCS
R 18
100 k
20
Vcc
16
U10
PH
74HCT299
4
1
S1
PG
9
15
RST
PF
5
8
QA
PE
14
17
QH
PD
6
12
PC
CLK
18
13
A
PB
11
7
H
PA
OE1 OE2 S2 GND
2 3 19 10
SCLK
(fig. 2)
U6
D15
D14
D13
D12
D11
D10
D9
D8
Vcc
Byte Wide
Jumpers
C13
0.1 µF
20
Vcc
U9
PH
74HCT299
1
S1
PG
9
PF
RST
8 QA
PE
17 QH
12
CLK
18 A
11
SDATA
(fig. 2)
V+
DCS
(fig. 2)
4
14
2
S
D
U8A
74HC74
3
CL
R
7
Q
Q
1
5
PD
PC
PB
H
PA
OE1 OE2 S2 GND
2
47 k
C22
0.1 µF
V+
RN1.4
3
A0
P7
16
D7
4
D6
15
D5
5
D4
14
D3
6
D2
13
D1
7
D0
DACK
PDR
19 10
TP19
6
74HCT04
12
13
U6
V+
RN 3.2
47 k
Figure 3. 16-Bit Parallel Port
DS31DB3
DS31DB4
47
47
CDB5501 CDB5503
CDB5501/CDB5503
tored to signal when data into the output registers
is complete (DCS returns high). The DACK signal is not needed in this mode and the lockout
signal to the the S1 inputs of registers U9 and
U10 may be disabled by removing the connection
on the circuit board. A place is provided on the
board for this purpose. A pull-up resistor is provided on the S1 inputs of the registers if the
connection is opened.
ready bar) signal on P10 indicates to the microcontroller when data from the CS5501/CS5503 is
available. Clock from the microcontroller is input
into SCI (serial clock input) and data output from
the CS5501/CS5503 is presented to the SD (serial
data) pin of the P10 connector. Note that the
jumpers on connectors P9 and P11 must be in the
NC (no connection) position to allow the microcontroller full control over the signals on P10.
SEC (Synchronous External Clocking) Mode
AC (Asynchronous Communication) Mode
(for CS5501 evaluation only)
The SEC mode enables the CS5501/CS5503 to be
directly interfaced to microcontrollers which output a clock signal to synchronously input serial
data to an input port. The CS5501/CS5503 will
output its serial data at the rate determined by the
clock from the microcontroller.
Connector P10 allows a microcontroller access to
the CS5501/CS5503 signal lines which are necessary to operate in the SEC mode.
The CSB (chip select bar CS) signal allows the
microcontroller to control when the
CS5501/CS5503 is to output data. The DRB (data
Baud Rate Clock Divider (CLK/2n) with INT CLK on P1 selected.
CLK = 4.9152 MHz
P-3
8
9
10
11
12
Baud Rate CLK Divider
19.2 kHz
9.6 kHz
4.8 kHz
2.4 kHz
1.2 kHz
The AC mode enables the CS5501 to output data
in a UART-compatible format. Data is output as
two characters consisting of one start bit, eight
data bits, and two stop bits each.
The output data rate can be set by a clock input to
the SCI input at connector P10 (see Figure 2).
The jumper on P11 must be in the NC position.
Alternatively an output data bit rate can be selected as a sub-multiple of the external CLKIN
signal to the board or as a sub-multiple of the onboard 4.9152 MHz oscillator. Counter IC U2
divides its input by 2n where n = 8, 9, ...12. One
of these outputs can be jumper selected at connector P3 (see Figure 1). For example, if the
4.9152 MHz oscillator is selected as the input to
IC U2 then a 1200 baud rate clock can be selected with the jumper at n = 12. Table 3
indicates the baud rates available at connector P3
when the 4.9152 MHz oscillator is used. If the
on-board baud clock is to be used, the jumper on
connector P11 should be in the BC (Baud Clock)
position.
Data Output Interface: RS-232 (for CS5501
evaluation only).
On-Board Baud Rate Clock Input to CS5501/CS5503 SCLK Input.
P-11
NC
BC
SCLK Input to CS5501/CS5503
No Connection
Baud Clock
Table 3. On-Board Baud Rate Generator
48
48
The RS232 port is depicted in Figure 4. Sub-D
connector P6 along with interface IC U11 provides the necessary circuitry to connect the
CS5501 to an RS-232 input of a computer. For
proper operation the AC (Asynchronous Communication) data output mode must be selected. In
DS31DB3
DS31DB4
CDB5501 CDB5503
CDB5501/CDB5503
MC145406
14
SDATA (fig. 2)
V+
RN 1.5
DRDY (fig. 2)
47 k 12
10
3
U11A
5
U11B
7
U11C
DATA
CTS
DSR
DCD
13
11
V+
0.1 µF
15 16
9
V-
U11D 4
U11E 6
RTS
DTR
DECIMATION COUNTER
3
Each time a data word is available for output
from the CS5501/CS5503, the DRDY line goes
low, provided the output port was previously
emptied. If the DRDY line is directly tied to the
CS input of the CS5501/CS5503, the converter
will output data every time a data word is presented to the output pin. In some applications it is
desirable to reduce the output word rate. The rate
5
6
8
4
20
7
1
U11F
P6
2
8
0.1 µF
NC
1
Sub-D
25 pin
Figure 4. RS-232 Port
addition, an appropriate baud clock needs to be
input to the CS5501. See AC (Asynchronous
Communication) mode mentioned earlier for an
explanation of the baud rate clock generator and
the data format of the output data in the AC
mode.
The DRDY output from the CS5501 signals the
CTS (Clear To Send) line of the RS-232 interface
when data is available. The Decimation Counter
can be used to determine how frequently output
data is to be transmitted.
The RS-232 interface on the evaluation card is
functionally adequate but it is not compliant with
the EIA RS-232 standard. When the MC145406
RS-232 receiver/driver chip is operated off of ± 5
volt supplies rather than ± 6 volts (see the
MC145406 data sheet for details) its driver output
swing is reduced below the EIA specified limits.
In practical applications this signal swing limitation only reduces the length of cable the circuit is
capable of driving.
DS31DB3
DS31DB4
Decimation Counter Accumulates 2n+1 DRDY Pulses Before CS is
Enabled.
P-4
0
1
2
3
4
5
6
7
8
9
10
11
P-9
NC
DC
2n+1
2
4
8
16
32
64
128
256
512
1024
2048
4096
DC Output to CS
No Connection
Decimation Counter
Table 4. Decimation Counter Control
can be reduced by lowering the rate at which the
CS line to the chip is enabled. The
CDB5501/CDB5503 evaluation board uses a
counter, IC U3 for this purpose. It is known as a
decimation counter (see Figure 2). The outputs of
the counter are available at connector P4. The
counter accumulates 2n+1 counts (n = 0, 2, …11)
at which time the selected output enables the CS
input to the CS5501/CS5503 (if the jumper in P9
is in the DC, Decimation Counter, position). The
49
49
CDB5501 CDB5503
CDB5501/CDB5503
Switch
SW1-1
SW1-2
SW1-3
ON
SC2 = 0
OFF
SC2 = 1
SC1 = 0
SC1 = 1
CAL
SC1 SC2
UNIPOLAR BIPOLAR
SLEEP
SW1-4
AWAKE
Table 5. DIP Switch Selections
0
0
1
0
1
1
1
0
Cal Type
ZS Cal FS Cal
Sequence
Self-Cal
AGND
VREF
One Step
System Offset AIN
& System Gain -
AIN
1st Step
2nd Step
System Offset AIN
VREF
One Step
Table 6. Calibration Mode Table
"D" input to flip-flop U8B is enabled to a "1" at
the same time CS goes low. When DRDY returns
high flip-flop U8B is toggled and resets the
counter back to zero which terminates the CS enable. The counter then accumulates counts until
the selected output activates CS low once again.
DIP Switch Selections/Calibration Initiation
Several control pins of the CS5501/CS5503 can
be level activated by DIP switch selection, or by
microcontroller at P8, as shown in Figure 5. DIP
switch SW1 selections are depicted in Tables 5
and 6. The CAL pushbutton is used to initiate a
calibration cycle in accordance with DIP switch
positions 1 and 2. The CAL pushbutton should be
activated any time power is first applied to the
board or any time the conversion mode (BP/UP)
is changed on the DIP switch. Remote control of
the CAL signal is available on connector P8.
Connector P8 also allows access to the DIP
switch functions by a microcomputer/microcontroller. The DIP switches should be placed in the
off position if off-board control of the signals on
connector P8 is implemented.
Voltage Reference
The evaluation board includes a 2.5 volt reference. Potentiometer R9 can be used to trim the
reference output to a precise value.
Analog Input Range: Unipolar Mode
U4
CS5501/
CS5503
CAL
10 k
SW2
R 15
47 k
47 k
RN 2.4
47 k
13
SLEEP
11
RN 2.3
BP/UP
12
SC1
4
RN 2.5
47 k
V+
RN 2.6
SC2
17
CAL
The value of the reference voltage sets the analog
input signal range. In unipolar mode the analog
input range extends from AGND to VREF. If the
analog input goes above VREF the converter will
output all "1’s". If the input goes below AGND,
the CS5501/CS5503 will output all "0’s".
Analog Input Range: Bipolar Mode
V+
SW1
1
2
3
4
P8
SC2
SC1
B/U
SLP
CAL
WARNING: Some evaluation boards were produced with the
SC1 and SC2 labels reversed on the silkscreen
The analog signal input range in the bipolar mode
is set by the reference to be from +VREF to VREF. If the input signal goes above +VREF, the
CS5501/CS5503 will output all "1’s". Input signals below -VREF cause the output data to be all
"0’s".
Figure 5. DIP Switch / Header Control Pin Selection
50
50
DS31DB3
DS31DB4
CDB5501 CDB5503
CDB5501/CDB5503
limited to ± 10 mA as the analog input of the chip
is internally diode clamped to both supplies. Excess current into the pin can damage the device.
On the evaluation board, resistor R16 (see Figure
6) does provide some current limiting in the event
of an overrange signal which exceeds the supply
voltage.
Analog Input: Overrange Precautions
In normal operation the value of the reference
voltage determines the range of the analog input
signal. Under abnormal conditions the analog signal can extend to be equal to the VA+ and VAsupply voltages. In the event the signal exceeds
these supply voltages the input current should be
R4
10
V+
14
C20
10 µF
R6
10
TP11
+5V
C7
0.1 µF
C6
0.1 µF
C18
C10
10 µF
0.1 µF
D1
6.8
2
VIN
GND
5
VD+
CS5501/
CS5503
U4
DGND
TP14
VOUT
10
6
U5
R8
LT1019-2.5
1M
R9
TRIM
5
50 k
GND
CW
4
TP13
15
VA+
C16
C19
0.1 µF
10 µF
VREF
R10
2.4
8
AGND
TP15
9
D2
6.8
TP12
7
R7
10
-5V
R5
10
V-
C21
0.0047 µF
X7R
C17
10 µF
R16
200
6
C8
C9
0.1 µF
0.1 µF
AIN
VAVD-
TP16
AIN
Figure 6. Voltage Reference / Analog Input
DS31DB3
DS31DB4
51
51
CDB5501 CDB5503
CDB5501/CDB5503
Oscilloscope Monitoring of SDATA
The output data from either the CS5501 or the
CS5503 can be observed on a dual trace oscilloscope with the following hook-up. Set the
evaluation board to operate in the SSC mode.
Connect scope probes to TP9 (SCLK) and TP10
(SDATA). Use a third probe connected to TP8
(DRDY) to provide the external trigger input to
the scope (use falling edge of DRDY to trigger).
With proper horizontal sweep, the SDATA output
bits from the A/D converter can be observed.
Note that if the input voltage to the CS5501 is
adjusted to a mid-code value, the converter will
remain stable on the same output code. This illustrates the low noise level of the CS5501. The
CS5503 will exhibit a few LSB’s of noise in its
observed output in agreement with its noise specifications.
52
52
Evaluation Board Component Layout and
Design Considerations
Figure 7 is a reproduction of the silkscreen component placement of the PC board.
The evaluation board includes design features to
insure proper performance from the A/D converter chip. Separate analog and digital ground
planes have been used on the board to insure
good noise immunity to digital system noise.
Decoupling networks (R6, C7, and R7, C9 in Figure 6) have been used to eliminate the possibility
of noise on the power supplies on the digital section from affecting the analog part of the A/D
converter chip.
The RC network (R10, C16 and C19) on the
output of the LT1019-2.5 reference may not be
needed in all applications. It has been included to
insure the best noise performance from the reference .
DS31DB3
DS31DB4
CDB5501 CDB5503
CDB5501/CDB5503
Figure 7. CDB5501/CDB5503 Component Layout
DS31DB3
DS31DB4
53
53
CDB5501 CDB5503
Contacting Cirrus Logic Support
For all product questions and inquiries contact a Cirrus Logic Sales Representative.
To find the one nearest to you go to www.cirrus.com
IMPORTANT NOTICE
Cirrus Logic, Inc. and its subsidiaries (“Cirrus”) believe that the information contained in this document is accurate and reliable. However, the information is subject to
change without notice and is provided “AS IS” without warranty of any kind (express or implied). Customers are advised to obtain the latest version of relevant infor
mation to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied
at the time of order acknowledgment, including those pertaining to warranty, indemnification, and limitation of liability. No responsibility is assumed by Cirrus for the
use of this information, including use of this information as the basis for manufacture or sale of any items, or for infringement of patents or other rights of third parties
This document is the property of Cirrus and by furnishing this information, Cirrus grants no license, express or implied under any patents, mask work rights, copyrights
trademarks, trade secrets or other intellectual property rights. Cirrus owns the copyrights associated with the information contained herein and gives consent for copies
to be made of the information only for use within your organization with respect to Cirrus integrated circuits or other products of Cirrus. This consent does not extend
to other copying such as copying for general distribution, advertising or promotional purposes, or for creating any work for resale.
CERTAIN APPLICATIONS USING SEMICONDUCTOR PRODUCTS MAY INVOLVE POTENTIAL RISKS OF DEATH, PERSONAL INJURY, OR SEVERE PROPER
TY OR ENVIRONMENTAL DAMAGE (“CRITICAL APPLICATIONS”). CIRRUS PRODUCTS ARE NOT DESIGNED, AUTHORIZED OR WARRANTED FOR USE IN
AIRCRAFT SYSTEMS, MILITARY APPLICATIONS, PRODUCTS SURGICALLY IMPLANTED INTO THE BODY, AUTOMOTIVE SAFETY OR SECURITY DEVICES
LIFE SUPPORT PRODUCTS OR OTHER CRITICAL APPLICATIONS. INCLUSION OF CIRRUS PRODUCTS IN SUCH APPLICATIONS IS UNDERSTOOD TO BE
FULLY AT THE CUSTOMER'S RISK AND CIRRUS DISCLAIMS AND MAKES NO WARRANTY, EXPRESS, STATUTORY OR IMPLIED, INCLUDING THE IMPLIED
WARRANTIES OF MERCHANTABILITY AND FITNESS FOR PARTICULAR PURPOSE, WITH REGARD TO ANY CIRRUS PRODUCT THAT IS USED IN SUCH A
MANNER. IF THE CUSTOMER OR CUSTOMER'S CUSTOMER USES OR PERMITS THE USE OF CIRRUS PRODUCTS IN CRITICAL APPLICATIONS, CUSTOM
ER AGREES, BY SUCH USE, TO FULLY INDEMNIFY CIRRUS, ITS OFFICERS, DIRECTORS, EMPLOYEES, DISTRIBUTORS AND OTHER AGENTS FROM ANY
AND ALL LIABILITY, INCLUDING ATTORNEYS' FEES AND COSTS, THAT MAY RESULT FROM OR ARISE IN CONNECTION WITH THESE USES.
Cirrus Logic, Cirrus, and the Cirrus Logic logo designs are trademarks of Cirrus Logic, Inc. All other brand and product names in this document may be trademarks o
service marks of their respective owners.
54
DS31DB4
Similar pages