19-2930; Rev 0; 8/03 500MHz to 1100MHz Adjustable RF Predistorter The MAX2010 comes in a 28-pin thin QFN exposed pad (EP) package (5mm x 5mm) and is specified for the extended (-40°C to +85°C) temperature range. Features ♦ ♦ ♦ ♦ ♦ ♦ ♦ ♦ ♦ ♦ ♦ ♦ ♦ Up to 12dB ACPR Improvement* Independent Gain and Phase Expansion Controls Gain Expansion Up to 6dB Phase Expansion Up to 21° 500MHz to 1100MHz Frequency Range Exceptional Gain and Phase Flatness Group Delay <2.4ns (Gain and Phase Sections Combined) ±0.03ns Group Delay Ripple Over a 100MHz Band Capable of Handling Input Drives Up to +23dBm On-Chip Temperature Variation Compensation Single +5V Supply Low Power Consumption: 75mW (typ) Fully Integrated into Small 28-Pin Thin QFN Package *Performance dependent on amplifier, bias, and modulation. Ordering Information PART MAX2010ETI-T -40°C to +85°C 28 Thin QFN-EP* Functional Diagram/ Pin Configuration GCS GFS GBP GND* 28 27 26 25 24 23 22 1 GND* 5 OUTP 6 GND* 7 18 PBEXP MAX2010 17 PBIN PHASE CONTROL 16 GND* 15 VCCP 8 9 10 11 12 13 14 PDCS2 4 PDCS1 GND* 19 PBRAW PFS2 3 PFS1 ING 20 GND* GND* 2 INP GND* 21 VCCG GAIN CONTROL GND* GND* GND* Digital Baseband Predistortion Architectures OUTG Feed-Forward PA Architectures GND* cdma2000™, GSM/EDGE, and iDEN Base Stations cdma2000 is a trademark of Telecommunications Industry Assoc. PIN-PACKAGE *EP = Exposed paddle. Applications Military Applications TEMP RANGE *INTERNALLY CONNECTED TO EXPOSED GROUND PADDLE. ________________________________________________________________ Maxim Integrated Products For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at 1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com. 1 MAX2010 General Description The MAX2010 adjustable RF predistorter is designed to improve power amplifier (PA) adjacent-channel power rejection (ACPR) by introducing gain and phase expansion in a PA chain to compensate for the PA’s gain and phase compression. With its +23dBm maximum input power level and wide adjustable range, the MAX2010 can provide up to 12dB of ACPR improvement for power amplifiers operating in the 500MHz to 1100MHz frequency band. Higher frequencies of operation can be achieved with this IC’s counterpart, the MAX2009. The MAX2010 is unique in that it provides up to 6dB of gain expansion and 21° of phase expansion as the input power is increased. The amount of expansion is configurable through two independent sets of control: one set adjusts the gain expansion breakpoint and slope, while the second set controls the same parameters for phase. With these settings in place, the linearization circuit can be run in either a static set-and-forget mode, or a more sophisticated closed-loop implementation can be employed with real-time software-controlled distortion correction. Hybrid correction modes are also possible using simple lookup tables to compensate for factors such as PA temperature drift or PA loading. MAX2010 500MHz to 1100MHz Adjustable RF Predistorter ABSOLUTE MAXIMUM RATINGS VCCG, VCCP to GND ..............................................-0.3V to +5.5V ING, OUTG, GCS, GFS, GBP to GND......-0.3V to (VCCG + 0.3V) INP, OUTP, PFS_, PDCS_, PBRAW, PBEXP, PBIN to GND ............................-0.3V to (VCCP + 0.3V) Input (ING, INP, OUTP, OUTG) Level ............................+23dBm PBEXP Output Current ........................................................±1mA Continuous Power Dissipation (TA = +70°C) 28-Pin Thin QFN-EP (derate 21mW/°C above +70°C) ...............................1667mW Operating Temperature Range ...........................-40°C to +85°C Junction Temperature ......................................................+150°C Storage Temperature Range .............................-65°C to +150°C Lead Temperature (soldering 10s) ..................................+300°C Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. DC ELECTRICAL CHARACTERISTICS (MAX2010 EV kit; VCCG = VCCP = +4.75V to +5.25V; no RF signal applied; INP, ING, OUTP, OUTG are AC-coupled and terminated to 50Ω. VPF_S1 = open; PBEXP shorted to PBRAW; VPDCS1 = VPDCS2 = 0.8V; VPBIN = VGBP = VGCS = GND; VGFS = VCCG; TA = -40°C to +85°C. Typical values are at VCCG = VCCP = +5.0V, TA = +25°C, unless otherwise noted.) PARAMETER Supply Voltage Supply Current Analog Input Voltage Range CONDITIONS VCCG, VCCP UNITS 5.25 V 5.8 7 10 12.1 PBIN, PBRAW 0 VCCP GBP, GFS, GCS 0 VCCG -2 +2 VGBP = 0 to +5V -100 +170 VPBIN = 0 to +5V -100 +220 PDCS1, PDCS2 (Note 1) Logic-Input Low Voltage PDCS1, PDCS2 (Note 1) 2 MAX VCCG Logic-Input High Voltage Logic Input Current TYP VCCP VGFS = VGCS = VPBRAW = 0V Analog Input Current MIN 4.75 2.0 -2 _______________________________________________________________________________________ mA V µA V 0.8 V +2 µA 500MHz to 1100MHz Adjustable RF Predistorter (MAX2010 EV kit, VCCG = VCCP = +4.75V to +5.25V, 50Ω environment, PIN = -20dBm, fIN = 500MHz to 1100MHz, VGCS = +1.0V, VGFS = +5.0V, VGBP = +1.2V, VPBIN = VPDCS1 = VPDCS2 = 0V, VPF_S1 = +5V, VPBRAW = VPBEXP, TA = -40°C to +85°C. Typical values are at fIN = 880MHz, VCCG = VCCP = +5V, TA = +25°C, unless otherwise noted.) (Notes 1, 2) PARAMETER CONDITIONS Operating Frequency Range VSWR MIN TYP 500 ING, INP, OUTG, OUTP MAX UNITS 1100 MHz 1.3:1 PHASE CONTROL SECTION Nominal Gain -5.5 dB Gain Variation Over Temperature TA = -40°C to +85°C -1.7 dB Gain Flatness Over a 100MHz band ±0.1 dB Phase-Expansion Breakpoint Maximum VPBIN = +5V 23 dBm Phase-Expansion Breakpoint Minimum VPBIN = 0V 0.7 dBm Phase-Expansion Breakpoint Variation Over Temperature TA = -40°C to +85°C ±1.5 dB VPF_S1 = +5V, VPDCS1 = VPDCS2 = 0V, PIN = -20 dBm to +23 dBm 21 VPDCS1 = 5V, VPDCS2 = 0V, VPF_S1 = +1.5V 16 Degrees Phase Expansion VPDCS1 = 0V, VPDCS2 = 5V, VPF_S1 = +1.5V 14 VPF_S1 = 0V, VPDCS1 = VPDCS2 = +5V, PIN = -20dBm to +23dBm 6 Phase-Expansion Slope Maximum PIN = +9dBm 1.4 Degrees /dB Phase-Expansion Slope Minimum VPF_S1 = 0V, VPDCS1 = VPDCS2 = +5V, PIN = +9dBm 0.6 Degrees /dB Phase-Slope Variation Over Temperature PIN = +9dBm, TA = -40°C to +85°C 0.05 Degrees /dB Phase Ripple Over a 100MHz band, deviation from linear phase ±0.02 Degrees 5.5 dB 1.3 ns Noise Figure Absolute Group Delay Interconnects de-embedded Group Delay Ripple Over a 100MHz band ±0.01 ns Parasitic Gain Expansion PIN = -20dBm to +23dBm +0.4 dB _______________________________________________________________________________________ 3 MAX2010 AC ELECTRICAL CHARACTERISTICS MAX2010 500MHz to 1100MHz Adjustable RF Predistorter AC ELECTRICAL CHARACTERISTICS (continued) (MAX2010 EV kit, VCCG = VCCP = +4.75V to +5.25V, 50Ω environment, PIN = -20dBm, fIN = 500MHz to 1100MHz, VGCS = +1.0V, VGFS = +5.0V, VGBP = +1.2V, VPBIN = VPDCS1 = VPDCS2 = 0V, VPF_S1 = +5V, VPBRAW = VPBEXP, TA = -40°C to +85°C. Typical values are at fIN = 880MHz, VCCG = VCCP = +5V, TA = +25°C, unless otherwise noted.) (Notes 1, 2) PARAMETER CONDITIONS MIN TYP MAX UNITS GAIN CONTROL SECTION -14.9 Nominal Gain dB VGCS = 0V, VGFS = +5V -24.3 VGCS = +5V, VGFS = 0V -7.6 Gain Variation Over Temperature TA = -40°C to +85°C -1.4 dB Gain Flatness Over a 100MHz band ±0.2 dB Gain-Expansion Breakpoint Maximum VGBP = +5V 23 dBm Gain-Expansion Breakpoint Minimum VGBP = +0.5V -2.5 dBm Gain-Expansion Breakpoint Variation Over Temperature TA = -40°C to +85°C -0.5 dB VGFS = +5V, PIN = -20dBm to +23dBm 5.3 VGFS = 0V, PIN = -20dBm to +23dBm 3.1 VGFS = +5V, PIN = +15dBm 0.43 VGFS = +0V, PIN = +15dBm 0.23 PIN = +15dBm, TA = -40°C to +85°C -0.01 dB/dB Gain-Expansion Gain-Expansion Slope Gain-Slope Variation Over Temperature Noise Figure dB dB/dB 14.9 dB Absolute Group Delay Interconnects de-embedded 1.12 ns Group Delay Ripple Over a 100MHz band ±0.02 ns Phase Ripple Over a 100MHz band, deviation from linear phase ±0.09 Degrees Parasitic Phase Expansion PIN = -20dBm to +23dBm +3 Degrees Note 1: Guaranteed by design and characterization. Note 2: All limits reflect losses and characteristics of external components shown in the Typical Application Circuit, unless otherwise noted. 4 _______________________________________________________________________________________ 500MHz to 1100MHz Adjustable RF Predistorter Phase Control Section (MAX2010 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 880MHz, TA = +25°C unless otherwise noted.) SMALL-SIGNAL INPUT RETURN LOSS vs. FREQUENCY TA = +25°C 6.1 6.0 5.9 TA = -40°C 5.8 20 C 30 D 40 5.7 4.95 5.05 5.15 5.25 0.9 1.0 0.8 FREQUENCY (GHz) A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V SUPPLY VOLTAGE (V) 0.6 0.7 MAX2010 toc04 0 OUTPUT RETURN LOSS (dB) INPUT RETURN LOSS (dB) 10 A D B A 20 30 D 40 C 40 1.1 0.5 0.6 0.9 1.0 0.8 FREQUENCY (GHz) A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V 10 B D 1.1 -4.0 -4.5 A 20 30 0.7 SMALL-SIGNAL GAIN vs. FREQUENCY LARGE-SIGNAL OUTPUT RETURN LOSS vs. FREQUENCY LARGE-SIGNAL INPUT RETURN LOSS vs. FREQUENCY 0 30 50 0.5 GAIN (dB) 4.85 MAX2010 toc05 4.75 B 20 A B 50 5.6 10 MAX2010 toc06 TA = +85°C OUTPUT RETURN LOSS (dB) 6.3 6.2 10 INPUT RETURN LOSS (dB) 6.4 0 MAX2010 toc02 6.5 SUPPLY CURRENT (mA) 0 MAX2010 toc01 6.6 SMALL-SIGNAL OUTPUT RETURN LOSS vs. FREQUENCY MAX2010 toc03 SUPPLY CURRENT vs. SUPPLY VOLTAGE C 40 -5.0 TA = -40°C -5.5 TA = +25°C -6.0 TA = +85°C -6.5 C -7.0 50 50 0.5 0.6 0.7 0.9 0.8 FREQUENCY (GHz) PIN = +15dBm A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V 1.0 1.1 0.5 0.6 0.7 0.9 0.8 FREQUENCY (GHz) 1.0 1.1 0.5 0.6 0.7 0.8 0.9 FREQUENCY (GHz) 1.0 1.1 PIN = +15dBm A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V _______________________________________________________________________________________ 5 MAX2010 Typical Operating Characteristics Typical Operating Characteristics (continued) Phase Control Section (continued) (MAX2010 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 880MHz, TA = +25°C unless otherwise noted.) SMALL-SIGNAL GAIN vs. COARSE SLOPE VPF_S1 = 1.5V -5.0 GAIN (dB) VCCP = 4.75V, 5.0V, 5.25V -5.5 -5.5 VPF_S1 = 5V -6.0 -6.5 -6.5 -6.5 1.0 -7.0 PDCS1 = 0 PDCS2 = 0 1.1 GROUP DELAY vs. FREQUENCY 1.40 1.35 A 1.30 C 6.4 6.2 D 5.8 B 5.6 0.5 0.6 0.7 0.8 B 0.9 FREQUENCY (GHz) A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V INTERCONNECTS DE-EMBEDDED 1.0 B 5.90 C 5.85 D A 5.80 E A C 5.0 1.1 5.95 5.75 5.2 D 1.20 6.00 MAX2010 toc11 6.6 5.4 1.25 6 6.8 6.0 PDCS1 = 5 PDCS2 = 5 PDCS1 = 5 PDCS1 = 0 PDCS2 = 0 PDCS2 = 5 COARSE SLOPE (V) SUPPLY CURRENT vs. INPUT POWER NOISE FIGURE vs. FREQUENCY NOISE FIGURE (dB) 1.45 -7.0 PDCS1 = 0 PDCS2 = 0 PDCS1 = 5 PDCS2 = 5 7.0 MAX2010 toc10 1.50 PDCS1 = 5 PDCS1 = 0 PDCS2 = 0 PDCS2 = 5 COARSE SLOPE (V) MAX2010 toc12 0.7 0.8 0.9 FREQUENCY (GHz) SUPPLY CURRENT (mA) 0.6 TA = +85°C -5.5 -6.0 0.5 TA = +25°C -5.0 -6.0 -7.0 TA = -40°C -4.5 GAIN (dB) -5.0 VPF_S1 = 0V -4.5 -4.0 MAX2010 toc08 -4.5 GAIN (dB) -4.0 MAX2010 toc07 -4.0 SMALL-SIGNAL GAIN vs. COARSE SLOPE MAX2010 toc09 SMALL-SIGNAL GAIN vs. FREQUENCY DELAY (ns) MAX2010 500MHz to 1100MHz Adjustable RF Predistorter 0.5 1.0 0.7 0.8 0.9 FREQUENCY (GHz) A = VPDCS1 = VPDCS2 = VPF_S1 = 0V B = VPDCS1 = VPDCS2 = 0V, VPF_S1 = 5V C = VPDCS1 = VPDCS2 = 5V, VPF_S1 = 0V D = VPDCS1 = VPDCS2 = VPF_S1 = 5V 0.6 1.1 5.70 0 4 8 12 16 INPUT POWER (dBm) D = VPBIN = 1.5V A = VPBIN = 0V E = VPBIN = 3.0V B = VPBIN = 0.5V C = VPBIN = 1.0V _______________________________________________________________________________________ 20 24 500MHz to 1100MHz Adjustable RF Predistorter Phase Control Section (continued) (MAX2010 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 880MHz, TA = +25°C unless otherwise noted.) PHASE EXPANSION vs. INPUT POWER C -5.1 B -5.3 C -4.9 B 0 A -5 3 8 13 18 -7 INPUT POWER (dBm) D = VPBIN = 1.5V A = VPBIN = 0V E = VPBIN = 2.0V B = VPBIN = 0.5V C = VPBIN = 1.0V F = VPBIN = 2.5V MAX2010 toc16 13 18 10 B E 0 D -5 -10 8 13 INPUT POWER (dBm) E = VPF_S1 = 2.0V A = VPF_S1 = 0V B = VPF_S1 = 0.5V F = VPF_S1 = 5.0V C = VPF_S1 = 1.0V VPDCS1 = 5.0V D = VPF_S1 = 1.5V 18 23 13 18 23 15 10 5 B 0 A -5 D C -15 -20 3 8 A B C A -2 3 INPUT POWER (dBm) C = VPDCS1 = 0V, VPDCS2 = 5V A = VPDCS1 = VPDCS2 = 0V B = VPDCS1 = 5V, VPDCS2 = 0V D = VPDCS1 = VPDCS2 = 5V -10 -15 -5.7 -2 PHASE EXPANSION vs. INPUT POWER 5 F -7 -7 23 F PHASE (DEGREES) -5.1 E 8 15 -4.8 -5.4 3 PHASE EXPANSION vs. INPUT POWER GAIN EXPANSION vs. INPUT POWER D -2 INPUT POWER (dBm) D = VPBIN = 1.5V A = VPBIN = 0V E = VPBIN = 2.0V B = VPBIN = 0.5V C = VPBIN = 1.0V F = VPBIN = 2.5V -4.5 C -5.7 -20 23 PHASE (DEGREES) -2 MAX2010 toc17 -7 C -5.5 F -5.7 -5.1 D E -15 B A -5.3 D -5.5 GAIN (dB) -4.7 5 -10 A MAX2010 toc15 MAX2010 toc14 10 PHASE (DEGREES) GAIN (dB) -4.9 GAIN EXPANSION vs. INPUT POWER -4.5 GAIN (dB) F E MAX2010 toc13 D -4.7 15 MAX2010 toc18 GAIN EXPANSION vs. INPUT POWER -4.5 -20 -7 -2 3 8 13 INPUT POWER (dBm) D = VPF_S1 = 1.5V A = VPF_S1 = 0V B = VPF_S1 = 0.5V E = VPF_S1 = 2.0V C = VPF_S1 = 1.0V F = VPF_S1 = 5.0V VPDCS1 = 5.0V 18 23 -7 -2 3 8 13 18 23 INPUT POWER (dBm) A = VPDCS1 = VPDCS2 = 0V B = VPDCS1 = 5V, VPDCS2 = 0V C = VPDCS1 = 0V, VPDCS2 = 5V D = VPDCS1 = VPDCS2 = 5V _______________________________________________________________________________________ 7 MAX2010 Typical Operating Characteristics (continued) Typical Operating Characteristics (continued) Phase Control Section (continued) (MAX2010 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 880MHz, TA = +25°C unless otherwise noted.) GAIN EXPANSION vs. INPUT POWER GAIN (dB) -4.6 TA = -40°C -4.8 -5.0 VPDCS1 = 5.0, VPF_S1 = 1.5V -5 PHASE (DEGREES) -4.4 MAX2010 toc20 VPDCS1 = 5.0, VPF_S1 = 1.5V -4.2 PHASE EXPANSION vs. INPUT POWER 0 MAX2010 toc19 -4.0 TA = +25°C -5.2 -10 TA = +25°C -15 TA = +85°C -5.4 TA = -40°C -20 TA = +85°C -5.6 -5.8 -25 -7 -2 3 8 13 18 23 -7 -2 INPUT POWER (dBm) 3 8 13 18 23 INPUT POWER (dBm) Typical Operating Characteristics Gain Control Section (MAX2010 EV kit, VCCG = +5.0V, PIN = -20dBm, VGBP = +1.2V, VGFS = +5.0V, VGCS = +1.0V, fIN = 880MHz, TA = +25°C, unless otherwise noted.) SMALL-SIGNAL INPUT RETURN LOSS vs. FREQUENCY 6.3 TA = +85°C 6.2 6.1 TA = +25°C 6.0 TA = -40°C 5.9 5.8 0 10 OUTPUT RETURN LOSS (dB) 6.4 INPUT RETURN LOSS (dB) 6.5 MAX2010 toc22 0 MAX2010 toc21 6.6 SMALL-SIGNAL OUTPUT RETURN LOSS vs. FREQUENCY C, D 20 A, B 30 40 MAX2010 toc23 SUPPLY CURRENT vs. SUPPLY VOLTAGE SUPPLY CURRENT (mA) MAX2010 500MHz to 1100MHz Adjustable RF Predistorter 10 C, D 20 30 A, B 40 5.7 5.6 50 4.75 4.85 4.95 5.05 SUPPLY VOLTAGE (V) 8 5.15 5.25 50 0.5 0.6 0.7 0.8 0.9 1.0 1.1 FREQUENCY (GHz) A = VGCS = 0V, VGFS = 0V C = VGCS = 5V, VGFS = 0V B = VGCS = 0V, VGFS = 5V D = VGCS = 5V, VGFS = 5V 0.5 0.6 0.7 0.8 0.9 1.0 1.1 FREQUENCY (GHz) A = VGCS = 0V, VGFS = 0V C = VGCS = 5V, VGFS = 0V B = VGCS = 0V, VGFS = 5V D = VGCS = 5V, VGFS = 5V _______________________________________________________________________________________ 500MHz to 1100MHz Adjustable RF Predistorter Gain Control Section (continued) (MAX2010 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 880MHz, TA = +25°C unless otherwise noted.) LARGE-SIGNAL OUTPUT RETURN LOSS vs. FREQUENCY D 20 C A 30 PIN = +15dBm 10 D TA = -40°C -13 C -14 20 A 30 TA = +25°C -15 TA = +85°C -16 -17 B -18 40 B 40 MAX2010 toc25 10 SMALL-SIGNAL GAIN vs. FREQUENCY -12 GAIN (dB) INPUT RETURN LOSS (dB) PIN = +15dBm 0 OUTPUT RETURN LOSS (dB) MAX2010 toc24 0 MAX2010 toc26 LARGE-SIGNAL INPUT RETURN LOSS vs. FREQUENCY -19 50 0.6 0.7 0.8 0.9 1.0 -20 0.5 1.1 0.9 1.0 1.1 0.5 0.6 0.7 0.8 0.9 1.0 1.1 FREQUENCY (GHz) SMALL-SIGNAL GAIN vs. VGCS 0 MAX2010 toc27 VCCG = 4.75V, 5.0V, 5.25V 0.8 SMALL-SIGNAL GAIN vs. VGCS SMALL-SIGNAL GAIN vs. FREQUENCY -13 0.7 FREQUENCY (GHz) A = VGCS = 0V, VGFS = 0V C = VGCS = 5V, VGFS = 0V B = VGCS = 0V, VGFS = 5V D = VGCS = 5V, VGFS = 5V FREQUENCY (GHz) A = VGCS = 0V, VGFS = 0V C = VGCS = 5V, VGFS = 0V B = VGCS = 0V, VGFS = 5V D = VGCS = 5V, VGFS = 5V -12 0.6 0 MAX2010 toc28 0.5 VGFS = 0V, 1.5V, 5.0V -5 MAX2010 toc29 50 TA = -40°C -5 -14 -10 -16 -17 GAIN (dB) GAIN (dB) GAIN (dB) -10 -15 -15 -15 -20 -20 -25 -25 -30 -30 TA = +25°C TA = +85°C -18 -19 VGFS = +1.5V -20 0.5 0.6 0.7 0.8 0.9 FREQUENCY (GHz) 1.0 1.1 0 1 2 3 VGCS (V) 4 5 0 1 2 3 4 5 VGCS (V) _______________________________________________________________________________________ 9 MAX2010 Typical Operating Characteristics (continued) Typical Operating Characteristics (continued) Gain Control Section (continued) (MAX2010 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 880MHz, TA = +25°C unless otherwise noted.) NOISE FIGURE vs. FREQUENCY 1.1 A 25 SUPPLY CURRENT (mA) C, D 1.2 A 25 NOISE FIGURE (dB) 1.3 30 MAX2010 toc31 MAX2010 toc30 1.4 SUPPLY CURRENT vs. INPUT POWER 30 B 20 C 15 1.0 10 B 0.6 0.7 0.8 0.9 1.0 0.5 C -14 -17 F G H 12 16 20 24 8 INPUT POWER (dBm) A = VGBP = 0V D = VGBP = 1.5V B = VGBP = 0.5V E = VGBP = 3.0V C = VGBP = 1.0V B -9 C -11 D F -13 H G E -15 -20 -7 10 -7 A E PHASE (DEGREES) GAIN (dB) D 4 -5 MAX2010 toc33 B -8 0 PHASE EXPANSION vs. INPUT POWER GAIN EXPANSION vs. INPUT POWER A 5 0.6 -5 -11 E 1.1 0.7 0.8 0.9 1.0 FREQUENCY (GHz) D = VGCS = 5V, VGFS = 0V A = VGCS = 0V, VGFS = 0V E = VGCS = 5V, VGFS = 5V B = VGCS = 0V, VGFS = 5V C = VGCS = 1.5V, VGFS = 5V 1.1 FREQUENCY (GHz) A = VGCS = 0V, VGFS = 0V C = VGCS = 5V, VGFS = 0V B = VGCS = 0V, VGFS = 5V D = VGCS = 5V, VGFS = 5V INTERCONNECTS DE-EMBEDDED C 15 MAX2010 toc34 0.5 A 20 D D 5 0.8 B 10 E 0.9 MAX2010 toc32 GROUP DELAY vs. FREQUENCY 1.5 DELAY (ns) MAX2010 500MHz to 1100MHz Adjustable RF Predistorter -2 8 13 18 23 3 INPUT POWER (dBm) A = VGBP = 0V E = VGBP = 2.0V B = VGBP = 0.5V F = VGBP = 2.5V C = VGBP = 1.0V G = VGBP = 3.5V D = VGBP = 1.5V H = VGBP = 5.0V -7 -2 8 13 18 23 3 INPUT POWER (dBm) A = VGBP = 0V E = VGBP = 2.0V B = VGBP = 0.5V F = VGBP = 2.5V C = VGBP = 1.0V G = VGBP = 3.5V D = VGBP = 1.5V H = VGBP = 5.0V ______________________________________________________________________________________ 500MHz to 1100MHz Adjustable RF Predistorter Gain Control Section (continued) (MAX2010 EV kit, VCCP = +5.0V, PIN = -20dBm, VPBIN = 0V, VPF_S1 = +5.0V, VPDCS1 = VPDCS2 = 0V, fIN = 880MHz, TA = +25°C unless otherwise noted.) GAIN EXPANSION vs. INPUT POWER E -9 F -11 -14 C D A, B -13 D -15 -17 C -19 A, B 10 E 0 C D A, B -21 -17 20 PHASE (DEGREES) -11 GAIN (dB) GAIN (dB) F -7 PHASE EXPANSION vs. INPUT POWER 30 MAX2010 toc37 -8 MAX2010 toc35 E -5 MAX2010 toc36 GAIN EXPANSION vs. INPUT POWER -5 -10 -23 -25 8 13 18 23 3 INPUT POWER (dBm) A = VGFS = 0V D = VGFS = 1.5V B = VGFS = 0.5V E = VGFS = 2.0V C = VGFS = 1.0V F = VGFS = 5.0V -10 -8 -10 D -12 C A, B -13 -12 -13 TA = -40°C -14 TA = +25°C -15 -14 -16 -15 -17 -7 -2 8 13 18 23 3 INPUT POWER (dBm) A = VGFS = 0V D = VGFS = 1.5V B = VGFS = 0.5V E = VGFS = 2.0V C = VGFS = 1.0V F = VGFS = 5.0V -2 8 13 18 23 3 INPUT POWER (dBm) A = VGCS = 0V D = VGCS = 1.5V B = VGCS = 0.5V E = VGCS = 2.0V C = VGCS = 1.0V F = VGCS = 5.0V PHASE EXPANSION vs. INPUT POWER -11 -9 GAIN (dB) PHASE (DEGREES) -9 E -11 -7 -5 MAX2010 toc39 F 8 13 18 23 3 INPUT POWER (dBm) A = VGCS = 0V D = VGCS = 1.5V B = VGCS = 0.5V E = VGCS = 2.0V C = VGCS = 1.0V F = VGCS = 2.5V -8 MAX2010 toc38 -6 -7 -2 GAIN EXPANSION vs. INPUT POWER PHASE EXPANSION vs. INPUT POWER -5 F -20 -7 -2 -6 -7 PHASE (DEGREES) -7 MAX2010 toc40 -20 -8 -9 TA = -40°C -10 TA = +25°C -11 -12 TA = +85°C -13 TA = +85°C -14 -15 -7 -2 8 13 3 INPUT POWER (dBm) 18 23 -7 -2 8 13 3 INPUT POWER (dBm) 18 ______________________________________________________________________________________ 23 11 MAX2010 Typical Operating Characteristics (continued) MAX2010 500MHz to 1100MHz Adjustable RF Predistorter Pin Description PIN NAME FUNCTION 1, 2, 4, 5, 7, 8, 10, 16, 20, 22, 26, 28 GND Ground. Internally connected to the exposed paddle. 3 ING RF Gain Input. Connect ING to a coupling capacitor if it is not connected to OUTP. ING is interchangeable with OUTG. 6 OUTP RF Phase Output. Connect OUTP to a coupling capacitor if it is not connected to INP. OUTP is interchangeable with INP. 9 INP RF Phase Input. Connect INP to a coupling capacitor. This pin is interchangeable with OUTP. 11 PFS1 Fine Phase-Slope Control Input 1. See the Typical Application Circuit. 12 PFS2 Fine Phase-Slope Control Input 2. See the Typical Application Circuit. 13 PDCS1 Digital Coarse Phase-Slope Control Range Input 1. Set to logical zero for the steepest slope. 14 PDCS2 Digital Coarse Phase-Slope Control Range Input 2. Set to logical zero for the steepest slope. 15 VCCP Phase-Control Supply Voltage. Bypass with a 0.01µF capacitor to ground as close to the device as possible. Phase section can operate without VCCG. 17 PBIN Phase Breakpoint Control Input 18 PBEXP Phase Expansion Output. Connect PBEXP to PBRAW to use PBIN as the breakpoint control voltage. 19 PBRAW Uncompensated Phase Breakpoint Input 21 VCCG Gain-Control Supply Voltage. Bypass with a 0.01µF capacitor to ground as close to the device as possible. Gain section can operate without VCCP. 23 GBP Gain Breakpoint Control Input 24 GFS Fine Gain-Slope Control Input 25 GCS Coarse Gain-Slope Control Input 27 OUTG EP GND RF Gain Output. Connect OUTG to a coupling capacitor. OUTG is interchangeable with ING. Exposed Ground Paddle. Solder EP to the ground plane. Detailed Description The MAX2010 adjustable predistorter can provide up to 12dB of ACPR improvement for high-power amplifiers by introducing gain and phase expansion to compensate for the PA’s gain and phase compression. The MAX2010 enables real-time software-controlled distortion correction, as well as set-and-forget tuning through the adjustment of the expansion starting point (breakpoint) and the rate of expansion (slope). The gain and 12 phase breakpoints can be set over a 20dB input power range. The phase expansion slope is variable from 0.3°/dB to 2.0°/dB and can be adjusted for a maximum of 21° of phase expansion. The gain expansion slope is variable from 0.1dB/dB to 0.53dB/dB and can be adjusted for a maximum of 6dB gain expansion. The following sections describe the tuning methodology best implemented with a class A amplifier. Other classes of operation may require significantly different settings. ______________________________________________________________________________________ 500MHz to 1100MHz Adjustable RF Predistorter Phase Expansion Breakpoint The phase expansion breakpoint is typically controlled by a digital-to-analog converter (DAC) connected through the PBIN pin. The PBIN input voltage range of 0V to VCC corresponds to a breakpoint input power range of 0.7dBm to 23dBm. To achieve optimal performance, the phase expansion breakpoint of the MAX2010 must be set to equal the phase compression breakpoint of the PA. Phase Expansion Slope The phase expansion slope of the MAX2010 must also be adjusted to equal the opposite slope of the PA’s phase compression curve. The phase expansion slope of the MAX2010 is controlled by the PFS1, PFS2, PDCS1, and PDCS2 pins. With pins PFS1 and PFS2 AC-coupled and connected to a variable capacitor or varactor diode, PA PHASE COMPRESSION IMPROVED PHASE DISTORTION COMBINED PHASE (DEGREES) SLOPE MAX2010 PHASE (DEGREES) PA PHASE (DEGREES) Gain Expansion Circuitry In addition to phase compression, the PA also suffers from gain compression (AM-AM) distortion, as shown in Figure 3. The PA gain curve remains flat for input powers below the breakpoint level, and begins to compress at a given rate (slope) for input powers greater than the breakpoint level. To compensate for such gain compression, the MAX2010 generates a gain expansion, which occurs at the same breakpoint level with the opposite slope. The overall result is a flat gain response at the PA output. MAX2010 PHASE EXPANSION BREAKPOINT PIN (dBm) the PFS1 and PFS2 pins perform the task of fine tuning the phase expansion slope. Since off-chip varactor diodes are recommended for this function, they must be closely matched and identically biased. A minimum effective capacitance of 2pF to 6pF is required to achieve the full phase slope range as specified in the Electrical Characteristics tables. As shown in Figure 2, the varactors connected to PFS1 and PFS2 are in series with three internal capacitors on each pin. By connecting and disconnecting these internal capacitors, a larger change in phase expansion slope can be achieved through the logic levels presented at the PDCS1 and PDCS2 pins. The phase expansion slope is at its maximum when both VPDCS1 and V PDCS2 equal 0V. The phase tuning has a minimal effect on the small-signal gain. PIN (dBm) PIN (dBm) Figure 1. PA Phase Compression Canceled by MAX2010 Phase Expansion ______________________________________________________________________________________ 13 MAX2010 Phase Expansion Circuitry Figure 1 shows a typical PA’s phase behavior with respect to input power. For input powers less than the breakpoint level, the phase remains relatively constant. As the input power becomes greater than the breakpoint level, the phase begins to compress and deteriorate the power amplifier’s linearity. To compensate for this AM-PM distortion, the MAX2010 provides phase expansion, which occurs at the same breakpoint level but with the opposite slope. The overall result is a flat phase response. MAX2010 500MHz to 1100MHz Adjustable RF Predistorter PFS1 PF_S1 PHASE-CONTROL CIRCUITRY PFS2 2 PDCS1 PDCS2 SWITCH CONTROL MAX2010 Figure 2. Simplified Phase Slope Internal Circuitry PA GAIN COMPRESSION MAX2010 GAIN EXPANSION IMPROVED GAIN DISTORTION PIN (dBm) COMBINED GAIN (dB) SLOPE MAX2010 GAIN (dB) PA GAIN (dB) BREAKPOINT PIN (dBm) PIN (dBm) Figure 3. PA Gain Compression Canceled by MAX2010 Gain Expansion 14 ______________________________________________________________________________________ 500MHz to 1100MHz Adjustable RF Predistorter Gain Expansion Slope In addition to properly setting the breakpoint, the gain expansion slope of the MAX2010 must also be adjusted to compensate for the PA’s gain compression. The slope should be set using the following equation: MAX2010 _ SLOPE = −PA _ SLOPE 1 + PA _ SLOPE where: MAX2010_SLOPE = MAX2010 gain section’s slope in dB/dB. PA_SLOPE = PA’s gain slope in dB/dB, a negative number for compressive behavior. To modify the gain expansion slope, two adjustments must be made to the biases applied on pins GCS and GFS. Both GCS and GFS have an input voltage range of 0V to VCC, corresponding to a slope of approximately 0.1dB/dB to 0.53dB/dB. The slope is set to maximum when VGCS = 0V and VGFS = +5V, and the slope is at its minimum when VGCS = +5V and VGFS = 0V. Unlike the GBP pin, modifying the gain expansion slope bias on the GCS pin causes a change in the part’s insertion loss and noise figure. For example, a smaller slope caused by GCS results in a better insertion loss and lower noise figure. The GFS does not affect the insertion loss. It can provide up to -30% or +30% total slope variation around the nominal slope set by GCS. Large amounts of GCS bias adjustment can also lead to an undesired (or residual) phase expansion/compression behavior. There exists an optimal bias voltage that minimizes this parasitic behavior (typically GCS = 1.0V). Control voltages higher than the optimal result in parasitic phase expansion, lower control voltages result in phase compression. GFS does not contribute to the phase behavior and is preferred for slope control. Applications Information The following section describes the tuning methodology best implemented with a class A amplifier. Other classes of operation may require significantly different settings. Gain and Phase Expansion Optimization The best approach to improve the ACPR of a PA is to first optimize the AM-PM response of the phase section. For most high-frequency LDMOS amplifiers, improving the AM-PM response provides the bulk of the ACPR improvement. Figure 4 shows a typical configuration of the phase tuning circuit. A power sweep on a network analyzer allows quick real-time tuning of the AM-PM response. First, tune PBIN to achieve the phase expansion starting point (breakpoint) at the same point where the PA’s phase compression begins. Next, use control pins PF_S1, PDCS1, and PDCS2 to obtain the optimal AM-PM response. The typical values for these pins are shown in Figure 4. To further improve the ACPR, connect the phase output to the gain input through a preamplifier. The preamplifier is used to compensate for the high insertion loss of the gain section. Figure 5 shows a typical application circuit of the MAX2010 with the phase section cascaded to the gain section for further ACPR optimization. Similar to tuning the phase section, first tune the gain expansion breakpoint through the GBP pin and adjust for the desired gain expansion with pins GCS and GFS. To minimize the effect of GCS on the parasitic phase response, minimize the control voltage to around 1V. Some retuning of the AM-PM response may be necessary. Layout Considerations A properly designed PC board is an essential part of any high-frequency circuit. In order to minimize external components, the PC board can be designed to incorporate small values of inductance and capacitance to optimize the input and output VSWR (refer to the MAX2009/ MAX2010 EV Kit). The phase section’s PFS1 and PFS2 pins are sensitive to external parasitics. Minimize trace lengths and keep varactor diodes close to the pins. Remove the ground plane underneath the traces can further help reduce the parasitic capacitance. For best performance, route the ground pin traces directly to the grounded EP underneath the package. Solder the EP on the bottom of the device package evenly to the board ground plane to provide a heat transfer path along with signal grounding. ______________________________________________________________________________________ 15 MAX2010 Gain Expansion Breakpoint The gain expansion breakpoint is usually controlled by a DAC connected through the GBP pin. The GBP input voltage range of 0.5V to 5V corresponds to a breakpoint input power range of -2.5dBm to 23dBm. To achieve the optimal performance, the gain expansion breakpoint of the MAX2010 must be set to equal the gain compression point of the PA. The GBP control has a minimal effect on the small-signal gain when operated from 0.5V to 5V. MAX2010 500MHz to 1100MHz Adjustable RF Predistorter POWER AMPLIFIER POUT = 7dBm 6 OUTP 3 ING MAX2010 PREAMPLIFIER 9 INP OUTG 27 PIN = 14dBm 11 PFS1 GBP 23 VPF_S1 = 1.5V 12 PFS2 PHASE CONTROL 19 PBRAW 18 PBEXP VPBIN = 0.8V GAIN CONTROL PBIN PDCS1 PDCS2 GCS 17 25 13 14 GFS 24 VPDCS1 = 0V VPDCS2 = 5V Figure 4. AM-PM Response Tuning Circuit Power-Supply Bypassing Bypass each VCC pin with a 0.01µF capacitor. Table 1. Suggested Components of Typical Application Circuit Exposed Pad RF The exposed paddle (EP) of the MAX2010’s 28-pin thin QFN-EP package provides a low inductance path to ground. It is important that the EP be soldered to the ground plane on the PC board, either directly or through an array of plated via holes. 16 DESIGNATION VALUE TYPE C1, C2, C3, C10 100pF ±5% C4, C5 0.01µF ±10% 0603 ceramic capacitors C6, C8 15pF ±5% 0402 ceramic capacitors C11, C12 2.2pF ±0.1pF 0402 ceramic capacitors L1, L2 5.6nH ±0.3nH R1, R2 1kΩ ±5% VR1, VR2 Skyworks SMV1232-079 0402 ceramic capacitors 0402 ceramic inductors 0402 resistors Hyperabrupt varactor diodes ______________________________________________________________________________________ 500MHz to 1100MHz Adjustable RF Predistorter MAX2010 PREAMPLIFIER GAIN = 7dB 6 3 OUTP ING MAX2010 POWER AMPLIFIER PREAMPLIFIER 9 INP OUTG 27 PIN = 14dBm 11 PFS1 GBP 23 VPF_S1 = 1.5V 12 PFS2 PHASE CONTROL 19 PBRAW 18 PBEXP VPBIN = 0.8V GAIN CONTROL PBIN PDCS1 PDCS2 GCS 17 25 13 14 GFS 24 VGBP = 1V VPDCS1 = 0V VGFS = 1.5V VPDCS2 = 5V VGCS = 1V Figure 5. MAX2010 Phase and Gain Optimization Circuit ______________________________________________________________________________________ 17 500MHz to 1100MHz Adjustable RF Predistorter MAX2010 Typical Application Circuit 28 GND* GND* L2 C10 PREAMPLIFER OUTP GND* C12 GND* GBP GFS GCS 21 GAIN CONTROL 2 20 3 19 4 18 MAX2010 5 17 PHASE CONTROL 6 16 7 15 9 INP GND* PREAMPLIFER 22 1 8 10 L1 C1 23 11 C2 12 13 14 VCCG GND* C5 PBRAW PBEXP PBIN CONTROL UNIT GND* VCCP C4 PDCS2 ING 24 PDCS1 C8 25 PFS2 GND* 26 PFS1 OPTIONAL MATCH COMPENSATION 27 GND* GND* GND* GND* POWER AMPLIFER OUTG C6 C3 R2 C11 R1 *INTERNALLY CONNECTED TO EXPOSED GROUND PADDLE. VR1 VR2 Chip Information TRANSISTOR COUNT: Bipolar: 160 CMOS: 240 PROCESS: BiCMOS 18 ______________________________________________________________________________________ 500MHz to 1100MHz Adjustable RF Predistorter b CL 0.10 M C A B D2/2 D/2 PIN # 1 I.D. QFN THIN.EPS D2 0.15 C A D k 0.15 C B PIN # 1 I.D. 0.35x45 E/2 E2/2 CL (NE-1) X e E E2 k L DETAIL A e (ND-1) X e CL CL L L e e 0.10 C A C 0.08 C A1 A3 PROPRIETARY INFORMATION TITLE: PACKAGE OUTLINE 16, 20, 28, 32L, QFN THIN, 5x5x0.8 mm APPROVAL COMMON DIMENSIONS DOCUMENT CONTROL NO. REV. 21-0140 C 1 2 EXPOSED PAD VARIATIONS NOTES: 1. DIMENSIONING & TOLERANCING CONFORM TO ASME Y14.5M-1994. 2. ALL DIMENSIONS ARE IN MILLIMETERS. ANGLES ARE IN DEGREES. 3. N IS THE TOTAL NUMBER OF TERMINALS. 4. THE TERMINAL #1 IDENTIFIER AND TERMINAL NUMBERING CONVENTION SHALL CONFORM TO JESD 95-1 SPP-012. DETAILS OF TERMINAL #1 IDENTIFIER ARE OPTIONAL, BUT MUST BE LOCATED WITHIN THE ZONE INDICATED. THE TERMINAL #1 IDENTIFIER MAY BE EITHER A MOLD OR MARKED FEATURE. 5. DIMENSION b APPLIES TO METALLIZED TERMINAL AND IS MEASURED BETWEEN 0.25 mm AND 0.30 mm FROM TERMINAL TIP. 6. ND AND NE REFER TO THE NUMBER OF TERMINALS ON EACH D AND E SIDE RESPECTIVELY. 7. DEPOPULATION IS POSSIBLE IN A SYMMETRICAL FASHION. 8. COPLANARITY APPLIES TO THE EXPOSED HEAT SINK SLUG AS WELL AS THE TERMINALS. 9. DRAWING CONFORMS TO JEDEC MO220. 10. WARPAGE SHALL NOT EXCEED 0.10 mm. PROPRIETARY INFORMATION TITLE: PACKAGE OUTLINE 16, 20, 28, 32L, QFN THIN, 5x5x0.8 mm APPROVAL DOCUMENT CONTROL NO. REV. 21-0140 C 2 2 Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are implied. Maxim reserves the right to change the circuitry and specifications without notice at any time. Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600 ____________________ 19 © 2003 Maxim Integrated Products Printed USA is a registered trademark of Maxim Integrated Products. MAX2010 Package Information (The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information go to www.maxim-ic.com/packages.)