Low Distortion, 1.5 W Audio Power Amplifier SSM2211 FEATURES FUNCTIONAL BLOCK DIAGRAM 1.5 W output1 Differential (BTL2) output Single-supply operation: 2.7 V to 5.5 V Functions down to 1.75 V Wide bandwidth: 4 MHz Highly stable phase margin: >80 degrees Low distortion: 0.2% THD + N @ 1 W output Excellent power supply rejection IN– VOUTA IN+ VOUTB BYPASS APPLICATIONS BIAS SSM2211 V– (GND) 00358-001 SHUTDOWN Portable computers Personal wireless communicators Hands-free telephones Speaker phones Intercoms Musical toys and talking games Figure 1. GENERAL DESCRIPTION The SSM22113 is a high performance audio amplifier that delivers 1 W rms of low distortion audio power into a bridgeconnected 8 Ω speaker load (or 1.5 W rms into a 4 Ω load). It operates over a wide temperature range and is specified for single-supply voltages between 2.7 V and 5.5 V. When operating from batteries, it continues to operate down to 1.75 V. This makes the SSM2211 the best choice for unregulated applications, such as toys and games. Featuring a 4 MHz bandwidth and distortion below 0.2% THD + N @ 1 W, superior performance is delivered at higher power or lower speaker load impedance than competitive units. The low differential dc output voltage results in negligible losses in the speaker winding and makes high value dc blocking capacitors unnecessary. Battery life is extended by using shutdown mode, which typically reduces quiescent current drain to 100 nA. The SSM2211 is designed to operate over the –40°C to +85°C temperature range. The SSM2211 is available in 8-lead SOIC (narrow body) and LFCSP (lead frame chip scale) surfacemount packages. The advanced mechanical packaging of the LFCSP models ensures lower chip temperature and enhanced performance relative to standard packaging options. Applications include personal portable computers, hands-free telephones and transceivers, talking toys, intercom systems, and other low voltage audio systems requiring 1 W output power. 1 2 3 At RL = 4 Ω, TA = 25°C, THD + N < 1%, VS = 5 V, 4-layer PCB. Bridge-tied load. Protected by U.S. Patent No. 5,519,576. Rev. D Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©2006 Analog Devices, Inc. All rights reserved. SSM2211 TABLE OF CONTENTS Features .............................................................................................. 1 Power Dissipation....................................................................... 16 Applications....................................................................................... 1 Output Voltage Headroom........................................................ 17 Functional Block Diagram .............................................................. 1 Automatic Shutdown-Sensing Circuit..................................... 17 General Description ......................................................................... 1 Shutdown-Circuit Design Example ......................................... 18 Revision History ............................................................................... 2 Start-Up Popping Noise............................................................. 18 Electrical Characteristics ................................................................. 3 SSM2211 Amplifier Design Example .................................. 18 Absolute Maximum Ratings............................................................ 5 Single-Ended Applications........................................................ 19 Thermal Resistance ...................................................................... 5 Driving Two Speakers Single Endedly..................................... 19 ESD Caution.................................................................................. 5 Evaluation Board ........................................................................ 20 Pin Configurations and Function Descriptions ........................... 6 LFCSP Printed Circuit Board Layout Considerations .......... 20 Typical Performance Characteristics ............................................. 7 Outline Dimensions ....................................................................... 21 Product Overview........................................................................... 14 Ordering Guide .......................................................................... 21 Thermal Performance—LFCSP................................................ 14 Typical Applications ....................................................................... 15 Bridged Output vs. Single-Ended Output Configurations ... 15 Speaker Efficiency and Loudness............................................. 15 REVISION HISTORY 11/06—Rev. C to Rev. D 10/02—Data Sheet Changed from Rev. A to Rev. B Updated Format..................................................................Universal Changes to General Description .................................................... 1 Changes to Electrical Characteristics ............................................ 3 Changes to Absolute Maximum Ratings ....................................... 5 Added Table 6.................................................................................... 6 Changes to Figure 32...................................................................... 11 Changes to the Product Overview Section ................................. 14 Changes to the Output Voltage Headroom Section................... 17 Changes to the Start-Up Popping Noise Section........................ 18 Changes to the Evaluation Board Section ................................... 20 Updated Outline Dimensions ....................................................... 21 Changes to Ordering Guide .......................................................... 21 Deleted 8-Lead PDIP .........................................................Universal Updated Outline Dimensions....................................................... 15 5/02—Data Sheet Changed from Rev. 0 to Rev. A Edits to General Description ...........................................................1 Edits to Package Type .......................................................................3 Edits to Ordering Guide ...................................................................3 Edits to Product Overview ...............................................................8 Edits to Printed Circuit Board Layout Considerations ............. 13 Added section Printed Circuit Board Layout Considerations—LFCSP................................................................ 14 10/04—Data Sheet Changed from Rev. B to Rev. C Updated Format..................................................................Universal Changes to General Description .................................................... 1 Changes to Table 5............................................................................ 4 Deleted Thermal Performance—SOIC Section ........................... 8 Changes to Figure 31...................................................................... 10 Changes to Figure 40...................................................................... 12 Changes to Thermal Performance—LFCSP Section ................. 13 Deleted Figure 52, Renumbered Successive Figures .................. 14 Deleted Printed Circuit Board Layout—SOIC Section ............. 14 Changes to Output Voltage Headroom Section ......................... 16 Changes to Start-Up Popping Noise Section .............................. 17 Changes to Ordering Guide .......................................................... 20 Rev. D | Page 2 of 24 SSM2211 ELECTRICAL CHARACTERISTICS VS = 5.0 V, TA = 25°C, RL = 8 Ω, CB = 0.1 μF, VCM = VD/2, unless otherwise noted. Table 1. Parameter GENERAL CHARACTERISTICS Differential Output Offset Voltage Output Impedance SHUTDOWN CONTROL Input Voltage High Input Voltage Low POWER SUPPLY Power Supply Rejection Ratio Supply Current Supply Current, Shutdown Mode DYNAMIC PERFORMANCE Gain Bandwidth Phase Margin AUDIO PERFORMANCE Total Harmonic Distortion Total Harmonic Distortion Voltage Noise Density Symbol Conditions VOOS ZOUT AVD = 2, –40°C ≤ TA ≤ +85°C VIH VIL ISY = < 100 mA ISY = normal PSRR ISY ISD VS = 4.75 V to 5.25 V VO1 = VO2 = 2.5 V, –40°C ≤ TA ≤ +85°C Pin 1 = VDD (see Figure 32), –40°C < TA < +85°C Min Max Unit 4 0.1 50 mV Ω 3.0 66 9.5 0.1 GBP ΦM THD + N THD + N en Typ P = 0.5 W into 8 Ω, f = 1 kHz P = 1.0 W into 8 Ω, f = 1 kHz f = 1 kHz 1.3 V V 20 1 dB mA μA 4 86 MHz Degrees 0.15 0.2 85 % % nV√Hz VS = 3.3 V, TA = 25°C, RL = 8 Ω, CB = 0.1 μF, VCM = VD/2, unless otherwise noted. Table 2. Parameter GENERAL CHARACTERISTICS Differential Output Offset Voltage Output Impedance SHUTDOWN CONTROL Input Voltage High Input Voltage Low POWER SUPPLY Supply Current Supply Current, Shutdown Mode AUDIO PERFORMANCE Total Harmonic Distortion Symbol Conditions VOOS ZOUT AVD = 2, –40°C ≤ TA ≤ +85°C VIH VIL ISY = < 100 μA ISY = normal ISY ISD VO1 = VO2 = 1.65 V, –40°C ≤ TA ≤ +85°C Pin 1 = VDD (see Figure 32), –40°C ≤ TA ≤ +85°C 5.2 0.1 THD + N P = 0.35 W into 8 Ω, f = 1 kHz 0.1 Rev. D | Page 3 of 24 Min Typ Max Unit 5 0.1 50 mV Ω 1.7 1 V V 20 1 mA μA % SSM2211 VS = 2.7 V, TA = 25°C, RL = 8 Ω, CB = 0.1 μF, VCM = VS/2, unless otherwise noted. Table 3. Parameter GENERAL CHARACTERISTICS Differential Output Offset Voltage Output Impedance SHUTDOWN CONTROL Input Voltage High Input Voltage Low POWER SUPPLY Supply Current Supply Current, Shutdown Mode AUDIO PERFORMANCE Total Harmonic Distortion Symbol Conditions VOOS ZOUT AVD = 2 VIH VIL ISY = < 100 mA ISY = normal ISY ISD VO1 = VO2 = 1.35 V, –40°C ≤ TA ≤ +85°C Pin 1 = VDD (see Figure 32), –40°C ≤ TA ≤ +85°C 4.2 0.1 THD + N P = 0.25 W into 8 Ω, f = 1 kHz 0.1 Rev. D | Page 4 of 24 Min Typ Max Unit 5 0.1 50 mV Ω 1.5 0.8 V V 20 1 mA μA % SSM2211 ABSOLUTE MAXIMUM RATINGS Absolute maximum ratings apply at 25°C, unless otherwise noted. THERMAL RESISTANCE Table 4. θJA is specified for the worst-case conditions, that is, a device soldered in a circuit board for surface-mount packages. Parameter Supply Voltage Input Voltage Common-Mode Input Voltage ESD Susceptibility Storage Temperature Range Operating Temperature Range Junction Temperature Range Lead Temperature Range, Soldering (60 sec) Rating 6V VDD VDD 2000 V −65°C to +150°C −40°C to +85°C −65°C to +165°C 300°C Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Table 5. Thermal Resistance Package Type 8-Lead LFCSP_VD (CP-Suffix)1 8-Lead SOIC_N (S-Suffix)2 1 θJA 50 121 Unit °C/W °C/W For the LFCSP_VD, θJA is measured with exposed lead frame soldered to the printed circuit board. 2 For the SOIC_N, θJA is measured with the device soldered to a 4-layer printed circuit board. ESD CAUTION Rev. D | Page 5 of 24 SSM2211 PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS SSM2211 VOUTB 7 V– IN+ 3 6 V+ TOP VIEW (Not to Scale) IN– 4 5 VOUTA SHUTDOWN 1 BYPASS 2 IN+ 3 IN– 4 Figure 2. 8-Lead SOIC_N Pin Configuration (R-8) Mnemonic SHUTDOWN BYPASS IN+ IN– VOUTA V+ V– VOUTB SSM2211 TOP VIEW (Not to Scale) 8 VOUTB 7 V– 6 V+ 5 VOUTA Figure 3. 8-Lead LFCSP_VD Pin Configuration (CP-8-2) Table 6. Pin Function Descriptions Pin No. 1 2 3 4 5 6 7 8 PIN 1 INDICATOR 00358-003 BYPASS 2 8 00358-002 SHUTDOWN 1 Description Shutdown Enable. Bypass Capacitor. Noninverting Input. Inverting Input. Output A. Positive Supply. Negative Supply. Output B. Rev. D | Page 6 of 24 SSM2211 TYPICAL PERFORMANCE CHARACTERISTICS 10 TA = 25°C VDD = 5V AVD = 2 (BTL) RL = 8Ω PL = 500mW CB = 0 CB = 0.1μF CB = 1μF 20 1k 100 10k 0.01 20k CB = 1μF 20 FREQUENCY (Hz) Figure 4. THD + N vs. Frequency Figure 7. THD + N vs. Frequency 10k 20k 10 10 CB = 0 CB = 0 THD + N (%) THD + N (%) CB = 1μF 0.1 CB = 1μF 0.1 00358-005 TA = 25°C VDD = 5V AVD = 10 (BTL) RL = 8Ω PL = 500mW 20 CB = 0.1μF 1 100 1k 10k 0.01 20k TA = 25°C VDD = 5V AVD = 10 (BTL) RL = 8Ω PL = 1W 20 FREQUENCY (Hz) Figure 5. THD + N vs. Frequency Figure 8. THD + N vs. Frequency 20k 10k 20k CB = 0.1μF 1 THD + N (%) 1 THD + N (%) 10k 10 CB = 0.1μF CB = 1μF 100 CB = 1μF 0.1 TA = 25°C VDD = 5V AVD = 20 (BTL) RL = 8Ω PL = 500mW 00358-006 0.01 20 1k 100 FREQUENCY (Hz) 10 0.1 00358-008 CB = 0.1μF 1 0.01 1k 100 FREQUENCY (Hz) 1k 10k 20k 0.01 TA = 25°C VDD = 5V AVD = 20 (BTL) RL = 8Ω PL = 1W 20 100 00358-009 0.01 CB = 0.1μF 0.1 00358-004 0.1 CB = 0 1 THD + N (%) THD + N (%) 1 TA = 25°C VDD = 5V AVD = 2 (BTL) RL = 8Ω PL = 1W 00358-007 10 1k FREQUENCY (Hz) FREQUENCY (Hz) Figure 6. THD + N vs. Frequency Figure 9. THD + N vs. Frequency Rev. D | Page 7 of 24 SSM2211 10 10 TA = 25°C VDD = 5V AVD = 2 (BTL) RL = 8Ω FREQUENCY = 20Hz CB = 0.1μF 1 TA = 25°C VDD = 3.3V AVD = 2 (BTL) RL = 8Ω PL = 350mW CB = 0 THD + N (%) THD + N (%) 1 0.1 CB = 0.1μF 0.1 1 0.01 2 POUTPUT (W) 00358-013 0.1 20 20k 10k 20k CB = 0 CB = 0.1μF 1 THD + N (%) 00358-011 0.1 1 0.01 2 TA = 25°C VDD = 3.3V AVD = 10 (BTL) RL = 8Ω PL = 350mW 20 100 1k POUTPUT (W) FREQUENCY (Hz) Figure 11. THD + N vs. POUTPUT Figure 14. THD + N vs. Frequency 00358-014 THD + N (%) CB = 1μF 0.1 0.1 10 TA = 25°C VDD = 5V AVD = 2 (BTL) RL = 8Ω FREQUENCY = 20kHz CB = 0.1μF CB = 0.1μF 1 THD + N (%) THD + N (%) 1 0.1 CB = 1μF 0.1 00358-012 0.01 20n 10k 10 1 10 20k Figure 13. THD + N vs. Frequency TA = 25°C VDD = 5V AVD = 2 (BTL) RL = 8Ω FREQUENCY = 1kHz CB = 0.1μF 0.01 20n 10k FREQUENCY (Hz) Figure 10. THD + N vs. POUTPUT 10 1k 100 0.1 1 2 0.01 TA = 25°C VDD = 3.3V AVD = 20 (BTL) RL = 8Ω PL = 350mW 20 100 00358-015 0.01 20n 00358-010 CB = 1μF 1k POUTPUT (W) FREQUENCY (Hz) Figure 12. THD + N vs. POUTPUT Figure 15. THD + N vs. Frequency Rev. D | Page 8 of 24 SSM2211 10 10 TA = 25°C VDD = 3.3V AVD = 2 (BTL) RL = 8Ω FREQUENCY = 20Hz CB = 0.1μF 1 TA = 25°C VDD = 2.7V AVD = 2 (BTL) RL = 8Ω PL = 250mW CB = 0 THD + N (%) THD + N (%) 1 0.1 CB = 0.1μF 0.1 0.1 1 0.01 2 POUTPUT (W) 00358-019 0.01 20n 00358-016 CB = 1μF 20 10k 20k Figure 19. THD + N vs. Frequency 10 TA = 25°C VDD = 3.3V AVD = 2 (BTL) RL = 8Ω FREQUENCY = 1kHz CB = 0.1μF CB = 0 CB = 0.1μF 1 0.1 CB = 1μF 0.1 1 0.01 2 TA = 25°C VDD = 2.7V AVD = 10 (BTL) RL = 8Ω PL = 250mW 20 1k FREQUENCY (Hz) Figure 17. THD + N vs. POUTPUT Figure 20. THD + N vs. Frequency 10k 20k 10k 20k 10 TA = 25°C VDD = 3.3V AVD = 2 (BTL) RL = 8Ω FREQUENCY = 20kHz CB = 0.1μF CB = 0.1μF 1 THD + N (%) THD + N (%) 1 0.1 CB = 1μF 0.1 00358-018 0.01 20n 100 POUTPUT (W) 0.1 1 2 0.01 TA = 25°C VDD = 2.7V AVD = 20 (BTL) RL = 8Ω PL = 250mW 20 100 00358-021 0.01 20n 00358-017 0.1 00358-020 THD + N (%) THD + N (%) 1 10 1k FREQUENCY (Hz) Figure 16. THD + N vs. POUTPUT 10 100 1k POUTPUT (W) FREQUENCY (Hz) Figure 18. THD + N vs. POUTPUT Figure 21. THD + N vs. Frequency Rev. D | Page 9 of 24 SSM2211 10 10 TA = 25°C VDD = 2.7V AVD = 2 (BTL) RL = 8Ω FREQUENCY = 20Hz 1 TA = 25°C VDD = 5V AVD = 10 SINGLE ENDED CB = 0.1μF CC = 1000μF THD + N (%) THD + N (%) 1 0.1 RL = 8Ω PO = 250mW 0.1 10 0.1 1 0.01 2 20 100 1k POUTPUT (W) FREQUENCY (Hz) Figure 22. THD + N vs. POUTPUT Figure 25. THD + N vs. Frequency 10 TA = 25°C VDD = 2.7V AVD = 2 (BTL) RL = 8Ω FREQUENCY = 1kHz 1 10k 20k 10k 20k 10k 20k TA = 25°C VDD = 3.3V AVD = 10 SINGLE ENDED CB = 0.1μF CC = 1000μF THD + N (%) THD + N (%) 1 0.1 RL = 8Ω PO = 85mW 0.1 0.1 1 0.01 2 POUTPUT (W) 20 100 1k FREQUENCY (Hz) Figure 23. THD + N vs. POUTPUT Figure 26. THD + N vs. Frequency 10 TA = 25°C VDD = 2.7V AVD = 2 (BTL) RL = 8Ω FREQUENCY = 20kHz TA = 25°C VDD = 2.7V AVD = 10 SINGLE ENDED CB = 0.1μF CC = 1000μF 1 THD + N (%) THD + N (%) 1 RL = 8Ω PO = 65mW 0.1 0.1 1 2 RL = 32Ω PO = 15mW 0.01 20 100 00358-027 00358-024 0.1 0.01 20n 00358-026 RL = 32Ω PO = 20mW 00358-023 0.01 20n 10 00358-025 00358-022 0.01 20n RL = 32Ω PO = 60mW 1k POUTPUT (W) FREQUENCY (Hz) Figure 24. THD + N vs. POUTPUT Figure 27. THD + N vs. Frequency Rev. D | Page 10 of 24 SSM2211 4.0 VDD = 2.7V THD + N (%) 1 VDD = 3.3V VDD = 5V 0.1 1 3.0 2.0 1.5 1.0 0 2 –40 –30 –20 –10 SUPPLY CURRENT (µA) THD + N (%) VDD = 3.3V 40 50 60 70 80 90 100 110 120 TA = 25°C VDD = 5V 4k 2k 00358-029 0.1 6k 1 0 2 POUTPUT (W) 1 0 2 3 4 5 SHUTDOWN VOLTAGE AT PIN 1 (V) Figure 32. Supply Current vs. Shutdown Voltage at Pin 1 Figure 29. THD + N vs. POUTPUT 14 TA = 25°C AVD = 2 (BTL) RL = 8Ω FREQUENCY = 20kHz CB = 0.1μF VDD = 3.3V TA = 25°C RL = OPEN VDD = 2.7V 00358-030 0.1 VDD = 5V 0.1 1 2 10 8 6 4 2 0 00358-033 SUPPLY CURRENT (mA) 12 1 THD + N (%) 30 8k VDD = 5V 0.01 20n 20 10k VDD = 2.7V 0.1 10 10 Figure 31. Maximum Power Dissipation vs. Ambient Temperature 1 0.01 20n 0 AMBIENT TEMPERATURE (°C) Figure 28. THD + N vs. POUTPUT TA = 25°C AVD = 2 (BTL) RL = 8Ω FREQUENCY = 1kHz CB = 0.1μF 8-LEAD SOIC 0.5 POUTPUT (W) 10 8-LEAD LFCSP 2.5 00358-032 0.01 20n 00358-028 0.1 TJ,MAX = 150°C FREE AIR, NO HEAT SINK SOIC θJA = 121°C/W LFCSP θJA = 50°C/W 3.5 00358-031 TA = 25°C AVD = 2 (BTL) RL = 8Ω FREQUENCY = 20Hz CB = 0.1μF MAXIMUM POWER DISSIPATION (W) 10 0 1 2 3 4 5 POUTPUT (W) SUPPLY VOLTAGE (V) Figure 30. THD + N vs. POUTPUT Figure 33. Supply Current vs. Supply Voltage Rev. D | Page 11 of 24 6 SSM2211 25 1.6 VDD = 2.7V SAMPLE SIZE = 300 1.4 20 FREQUENCY 1.0 0.8 0.6 5V 00358-034 2.7V 8 12 16 20 24 28 32 36 40 44 0 –20 48 –15 –10 –5 0 5 10 15 20 LOAD RESISTANCE (Ω) OUTPUT OFFSET VOLTAGE (mV) Figure 34. POUTPUT vs. Load Resistance Figure 36. Output Offset Voltage Distribution 80 180 60 135 40 90 20 45 0 0 25 20 VDD = 3.3V SAMPLE SIZE = 300 16 –20 –45 –40 –90 –60 –135 FREQUENCY 4 PHASE SHIFT (Degrees) 12 8 4 –80 100 1k 10k 100k 1M 10M –180 100M FREQUENCY (Hz) 0 –30 00358-037 GAIN (dB) 0 10 5 3.3V 0.2 15 00358-036 0.4 00358-035 OUTPUT POWER (W) 1.2 –20 –10 0 10 20 OUTPUT OFFSET VOLTAGE (mV) Figure 35. Gain and Phase Shift vs. Frequency (Single Amplifier) Figure 37. Output Offset Voltage Distribution Rev. D | Page 12 of 24 30 SSM2211 20 –50 VDD 5V3.3V DD= = SAMPLE SIZE SIZE = = 300 300 SAMPLE TA = 25°C VDD = 5V ± 100mV CB = 15μF AVD = 2 16 12 PSRR (dB) 8 –65 0 –30 00358-038 4 –10 –20 0 10 20 –70 30 OUTPUT OFFSET VOLTAGE (mV) VDD = 5V SAMPLE SIZE = 1,700 500 300 200 100 00358-039 FREQUENCY 400 7 8 9 10 11 12 13 100 1k Figure 40. PSRR vs. Frequency 600 6 20 FREQUENCY (Hz) Figure 38. Output Offset Voltage Distribution 0 –60 00358-040 FREQUENCY –55 14 15 SUPPLY CURRENT (mA) Figure 39. Supply Current Distribution Rev. D | Page 13 of 24 10k 30k SSM2211 PRODUCT OVERVIEW The SSM2211 is a low distortion speaker amplifier that can run from a 2.7 V to 5.5 V supply. It consists of a rail-to-rail input and a differential output that can be driven within 400 mV of either supply rail while supplying a sustained output current of 350 mA. The SSM2211 is unity-gain stable, requiring no external compensation capacitors, and can be configured for gains of up to 40 dB. Figure 41 shows the simplified schematic. 20kΩ VDD 6 20kΩ SSM2211 4 3 5 A1 VO1 50kΩ 50kΩ 50kΩ 0.1μF 8 A2 2 VO2 BIAS CONTROL 50kΩ 7 1 SHUTDOWN THERMAL PERFORMANCE—LFCSP The addition of the LFCSP to the Analog Devices, Inc., package portfolio offers the SSM2211 user even greater choice when considering thermal performance criteria. For the 8-lead, 3 mm × 3 mm LFCSP, the θJA is 50°C/W. This is a significant performance improvement over most other packaging options. 00358-041 VIN Pin 4 and Pin 3 are the inverting and noninverting terminals to A1. An offset voltage is provided at Pin 2, which should be connected to Pin 3 for use in single-supply applications. The output of A1 appears at Pin 5. A second operational amplifier, A2, is configured with a fixed gain of AV = −1 and produces an inverted replica of Pin 5 at Pin 8. The SSM2211 outputs at Pin 5 and Pin 8 produce a bridged configuration output to which a speaker can be connected. This bridge configuration offers the advantage of a more efficient power transfer from the input to the speaker. Because both outputs are symmetric, the dc bias at Pin 5 and Pin 8 are exactly equal, resulting in zero dc differential voltage across the outputs. This eliminates the need for a coupling capacitor at the output. Figure 41. Simplified Schematic Rev. D | Page 14 of 24 SSM2211 TYPICAL APPLICATIONS RF the power delivered to the load. In a typical application operating from a 5 V supply, the maximum power that can be delivered by the SSM2211 to an 8 Ω speaker in a single-ended configuration is 250 mW. By driving this speaker with a bridged output, 1 W of power can be delivered. This translates to a 12 dB increase in sound pressure level from the speaker. 5V CC AUDIO INPUT RI CS 6 4 – 5 SSM2211 3 + 1 8 – SPEAKER 8V + 7 00358-042 2 CB Figure 42. Typical Configuration Figure 42 shows how the SSM2211 is connected in a typical application. The SSM2211 can be configured for gain much like a standard operational amplifier. The gain from the audio input to the speaker is R AV = 2 × F RI 1 2πR I × C C (2) Because the SSM2211 has an excellent phase margin, a feedback capacitor in parallel with RF to band limit the amplifier is not required, as it is in some competitor products. BRIDGED OUTPUT VS. SINGLE-ENDED OUTPUT CONFIGURATIONS The power delivered to a load with a sinusoidal signal can be expressed in terms of the peak voltage of the signal and the resistance of the load as V PK 2 2 × RL 1 2πR L × C C (4) where RL is the speaker resistance and CC is the coupling capacitance. CS is a supply bypass capacitor used to provide power supply filtering. Pin 2 is connected to Pin 3 to provide an offset voltage for single-supply use, with CB providing a low ac impedance to ground to help power supply rejection. Because Pin 4 is a virtual ac ground, the input impedance is equal to RI. CC is the input coupling capacitor, which also creates a high-pass filter with a corner frequency of PL = f −3dB = (1) The 2× factor comes from the fact that Pin 8 has the opposite polarity of Pin 5, providing twice the voltage swing to the speaker from the bridged-output configuration. f HP = Driving a speaker differentially from a bridged output offers another advantage in that it eliminates the need for an output coupling capacitor to the load. In a single-supply application, the quiescent voltage at the output is half of the supply voltage. If a speaker is connected in a single-ended configuration, a coupling capacitor is needed to prevent dc current from flowing through the speaker. This capacitor also needs to be large enough to prevent low frequency roll-off. The corner frequency is given by (3) By driving a load from a bridged-output configuration, the voltage swing across the load doubles. Therefore, an advantage in using a bridged-output configuration becomes apparent from Equation 3, as doubling the peak voltage results in four times For an 8 Ω speaker and a corner frequency of 20 Hz, a 1000 μF capacitor would be needed, which is physically large and costly. By connecting a speaker in a bridged-output configuration, the quiescent differential voltage across the speaker becomes nearly zero, eliminating the need for the coupling capacitor. SPEAKER EFFICIENCY AND LOUDNESS The effective loudness of 1 W of power delivered into an 8 Ω speaker is a function of speaker efficiency. The efficiency is typically rated as the sound pressure level (SPL) at 1 meter in front of the speaker with 1 W of power applied to the speaker. Most speakers are between 85 dB and 95 dB SPL at 1 meter at 1 W. Table 7 shows a comparison of the relative loudness of different sounds. Table 7. Typical Sound Pressure Levels Source of Sound Threshold of Pain Heavy Street Traffic Cabin of Jet Aircraft Average Conversation Average Home at Night Quiet Recording Studio Threshold of Hearing dB SPL 120 95 80 65 50 30 0 It can easily be seen that 1 W of power into a speaker can produce quite a bit of acoustic energy. Rev. D | Page 15 of 24 SSM2211 POWER DISSIPATION Another important advantage in using a bridged-output configuration is the fact that bridged-output amplifiers are more efficient than single-ended amplifiers in delivering power to a load. Efficiency is defined as the ratio of power from the power supply to power delivered to the load PL PSY PDISS = (7) πRL 1.5 An amplifier with a higher efficiency has less internal power dissipation, which results in a lower die-to-case junction temperature as compared to an amplifier that is less efficient. This is important when considering the amplifier maximum power dissipation rating vs. ambient temperature. An internal power dissipation vs. output power equation can be derived to fully understand this. The internal power dissipation of the amplifier is the internal voltage drop multiplied by the average value of the supply current. An easier way to find internal power dissipation is to measure the difference between the power delivered by the supply voltage source and the power delivered into the load. The waveform of the supply current for a bridged-output amplifier is shown in Figure 43. VDD = 5V 1.0 RL = 8Ω 0.5 0 Because the efficiency of a bridged-output amplifier (Equation 3 divided by Equation 6) increases with the square root of PL, the power dissipated internally by the device stays relatively flat and actually decreases with higher output power. The maximum power dissipation of the device can be found by differentiating Equation 7 with respect to load power and setting the derivative equal to zero. This yields ISY ∂PDISS IDD, PEAK ∂PL IDD, AVG 00358-043 By integrating the supply current over a period, T, then dividing the result by T, IDD,AVG can be found. Expressed in terms of peak output voltage and load resistance 2VPEAK (5) πR L Therefore, power delivered by the supply, neglecting the bias current for the device, is πRL 2 × V DD = πR L × PL −1 2 −1 = 0 (8) and occurs when PDISS, MAX = Figure 43. Bridged Amplifier Output Voltage and Supply Current vs. Time 2 VDD × VPEAK 1.5 Figure 44. Power Dissipation vs. Output Power with VDD = 5 V T TIME 1.0 OUTPUT POWER (W) TIME T 0.5 00358-044 0 VOUT I DD , AVG = RL = 4Ω RL = 16Ω VPEAK PSY = 2 2VDD × VPEAK The graph of this equation is shown in Figure 44. POWER DISSIPATION (W) η= The power dissipated by the amplifier internally is simply the difference between Equation 6 and Equation 3. The equation for internal power dissipated, PDISS, expressed in terms of power delivered to the load and load resistance, is 2 V DD 2 (9) π 2 RL Using Equation 9 and the power derating curve in Figure 31, the maximum ambient temperature can be found easily. This ensures that the SSM2211 does not exceed its maximum junction temperature of 150°C. The power dissipation for a single-ended output application where the load is capacitively coupled is given by ∂PDISS = (6) 2 2 × V DD π RL × P L − PL The graph of Equation 10 is shown in Figure 45. Rev. D | Page 16 of 24 (10) SSM2211 1.6 0.35 RL = 4Ω 1.4 MAX POUT @ 1% THD (W) 0.25 0.20 0.15 RL = 8Ω 0.10 RL = 16Ω 0 0 0.1 0.2 0.3 RL = 4Ω 1.0 RL = 8Ω 0.8 0.6 RL = 16Ω 0.4 0.2 00358-045 0.05 1.2 0 0.4 00358-046 POWER DISSIPATION (W) 0.30 1.5 2.0 2.5 Figure 45. Power Dissipation vs. Single-Ended Output Power with VDD = 5 V 2 VDD 2 π 2 RL 3.5 4.0 4.5 5.0 Figure 46. Maximum Output Power vs. VSY Shutdown Feature The maximum power dissipation for a single-ended output is PDISS , MAX = 3.0 SUPPLY VOLTAGE (V) OUTPUT POWER (W) (11) OUTPUT VOLTAGE HEADROOM The outputs of both amplifiers in the SSM2211 can come to within 400 mV of either supply rail while driving an 8 Ω load. As compared to equivalent competitor products, the SSM2211 has a higher output voltage headroom. This means that the SSM2211 can deliver an equivalent maximum output power while running from a lower supply voltage. By running at a lower supply voltage, the internal power dissipation of the device is reduced, as can be seen in Equation 9. This extended output headroom, along with the LFCSP package, allows the SSM2211 to operate in higher ambient temperatures than competitor devices. The SSM2211 is also capable of providing amplification even at supply voltages as low as 2.7 V. The maximum power available at the output is a function of the supply voltage. Therefore, as the supply voltage decreases, so does the maximum power output from the device. The maximum output power vs. supply voltage at various bridge-tied load resistances is shown in Figure 46. The maximum output power is defined as the point at which the output has 1% total harmonic distortion (THD + N). The SSM2211 can be put into a low power consumption shutdown mode by connecting Pin 1 to 5 V. In shutdown mode, the SSM2211 has an extremely low supply current of less than 10 nA. This makes the SSM2211 ideal for battery-powered applications. Connect Pin 1 to ground for normal operation. Connecting Pin 1 to VDD mutes the outputs and puts the device into shutdown mode. A pull-up or pull-down resistor is not required. Pin 1 should always be connected to a fixed potential, either VDD or ground, and never be left floating. Leaving Pin 1 unconnected can produce unpredictable results. AUTOMATIC SHUTDOWN-SENSING CIRCUIT Figure 47 shows a circuit that can be used to take the SSM2211 in and out of shutdown mode automatically. This circuit can be set to turn the SSM2211 on when an input signal of a certain amplitude is detected. The circuit also puts the device into low power shutdown mode if an input signal is not sensed within a certain amount of time. This can be useful in a variety of portable radio applications, where power conservation is critical. R8 VDD R7 R5 C2 VDD VIN To find the minimum supply voltage needed to achieve a specified maximum undistorted output power use Figure 46. For example, an application requires only 500 mW to be output for an 8 Ω speaker. With the speaker connected in a bridged-output configuration, the minimum supply voltage required is 3.3 V. R6 R4 4 1 OP181 + R1 A2 D1 C1 R3 R2 NOTE ADDITIONAL PINS OMITTED FOR CLARITY Figure 47. Automatic Shutdown Circuit Rev. D | Page 17 of 24 8 A1 – VDD 5 SSM2211 00358-047 VDD = 5V SSM2211 The input signal to the SSM2211 is also connected to the noninverting terminal of A2. R1, R2, and R3 set the threshold voltage at which the SSM2211 is to be taken out of shutdown mode. D1 half-wave rectifies the output of A2, discharging C1 to ground when an input signal greater than the set threshold voltage is detected. R4 controls the charge time of C1, which sets the time until the SSM2211 is put back into shutdown mode after the input signal is no longer detected. R5 and R6 are used to establish a voltage reference point equal to half of the supply voltage. R7 and R8 set the gain of the SSM2211. A 1N914 or equivalent diode is required for D1, and A2 must be a rail-to-rail output amplifier, such as OP181 or equivalent. This ensures that C1 discharges sufficiently to bring the SSM2211 out of shutdown mode. To find the appropriate component values, first, the gain of A2 must be determined by AV,MIN = VSY (12) VTHS where: VSY is the single supply voltage. VTHS is the threshold voltage. AV must be set to a minimum of 2 for the circuit to work properly. SHUTDOWN-CIRCUIT DESIGN EXAMPLE In this example, a portable radio application requires the SSM2211 to be turned on when an input signal greater than 50 mV is detected. The device needs to return to shutdown mode within 500 ms after the input signal is no longer detected. The lowest frequency of interest is 200 Hz, and a 5 V supply is used. The minimum gain of the shutdown circuit, from Equation 12, is AV = 100. R1 is set to 100 kΩ. Using Equation 13 and Equation 14, R2 = 98 kΩ and R3 = 4.9 MΩ. C1 is set to 0.01 μF, and based on Equation 15, R4 is set to 10 MΩ . To minimize power supply current, R5 and R6 are set to 10 MΩ. The previous procedure provides an adequate starting point for the shutdown circuit. Some component values may need to be adjusted empirically to optimize performance. START-UP POPPING NOISE During power-up or release from shutdown mode, the midrail bypass capacitor, CB, determines the rate at which the SSM2211 starts up. By adjusting the charging time constant of CB, the start-up pop noise can be pushed into the subaudible range, greatly reducing start-up popping noise. On power-up, the midrail bypass capacitor is charged through an effective resistance of 25 kΩ. To minimize start-up popping, the charging time constant for CB needs to be greater than the charging time constant for the input coupling capacitor, CC. Next, choose R1 and set R2 to ⎛ 2 ⎞ ⎟ R2 = R1 ⎜⎜ 1 − ⎟ ⎝ AV ⎠ CB × 25 kΩ > CC × R1 (13) For an application where R1 = 10 kΩ and CC = 0.22 μF, CB must be at least 0.1 μF to minimize start-up popping noise. SSM2211 Amplifier Design Example Find R3 as R3 = (16) R1× R2 R2 + R2 (A V − 1) (14) C1 can be arbitrarily set but should be small enough to prevent A2 from becoming capacitively overloaded. R4 and C1 control the shutdown rate. To prevent intermittent shutdown with low frequency input signals, the minimum time constant must be R4 × C1 ≥ 10 f LOW where fLOW is the lowest input frequency expected. (15) Maximum Output Power Input Impedance Load Impedance Input Level Bandwidth 1W 20 kΩ 8Ω 1 V rms 20 Hz − 20 kHz ± 0.25 dB The configuration shown in Figure 42 is used. The first thing to determine is the minimum supply rail necessary to obtain the specified maximum output power. From Figure 46, for 1 W of output power into an 8 Ω load, the supply voltage must be at least 4.6 V. A supply rail of 5 V can be easily obtained from a Rev. D | Page 18 of 24 SSM2211 voltage reference. The extra supply voltage also allows the SSM2211 to reproduce peaks in excess of 1 W without clipping the signal. With VDD = 5 V and RL = 8 Ω, Equation 9 shows that the maximum power dissipation for the SSM2211 is 633 mW. From the power derating curve in Figure 31, the ambient temperature must be less than 73°C for the SOIC and 118°C for the LFCSP. SINGLE-ENDED APPLICATIONS There are applications in which driving a speaker differentially is not practical, for example, a pair of stereo speakers where the minus terminal of both speakers is connected to ground. Figure 48 shows how this can be accomplished. 10kΩ 5V The required gain of the amplifier can be determined from Equation 17 as = 2 .8 (17) 10kΩ 6 4 0.47μF – 5 SSM2211 3 1 + From Equation 1 0.1μF or RF = 1.4 × RI. Because the desired input impedance is 20 kΩ, RI = 20 kΩ and R2 = 28 kΩ. The final design step is to select the input capacitor. When adding an input capacitor, CC, to create a high-pass filter, the corner frequency needs to be far enough away for the design to meet the bandwidth criteria. For a first-order filter to achieve a pass-band response within 0.25 dB, the corner frequency must be at least 4.14× away from the pass-band frequency. So, (4.14 × fHP) < 20 Hz. Using Equation 2, the minimum size of input capacitor can be found. 1 ⎛ 20 Hz ⎞ 2π × 20 kΩ ⎜⎜ ⎟⎟ ⎝ 4.14 ⎠ (2.2 μF)(20 kΩ) 25 kΩ It is not necessary to connect a dummy load to the unused output to help stabilize the output. The 470 μF coupling capacitor creates a high-pass frequency cutoff of 42 Hz, as given in Equation 4, which is acceptable for most computer speaker applications. The overall gain for a single-ended output configuration is AV = RF/R1, which for this example is equal to 1. DRIVING TWO SPEAKERS SINGLE ENDEDLY It is possible to drive two speakers single endedly with both outputs of the SSM2211. 20kΩ 5V 470μF To summarize the final design: 5V 20 kΩ 28 kΩ 2.2 μF 2.2 μF 85°C AUDIO INPUT 20kΩ 6 4 1μF – + – LEFT SPEAKER (8Ω) 5 SSM2211 3 1 + 7 2 0.1μF 8 470μF + RIGHT SPEAKER (8Ω) – Figure 49. SSM2211 Used as a Dual-Speaker Amplifier = 1.76 μF Selecting CB to be 2.2 μF for a practical value of capacitor minimizes start-up popping noise. VDD R1 RF CC CB TA, MAX 250mW SPEAKER (8Ω) Figure 48. Single-Ended Output Application (18) The gain bandwidth product for each internal amplifier in the SSM2211 is 4 MHz. Because 4 MHz is much greater than 4.14 × 20 kHz, the design meets the upper frequency bandwidth criteria. The SSM2211 can also be configured for higher differential gains without running into bandwidth limitations. Equation 16 shows an appropriate value for CB to reduce startup popping noise. + – Therefore, CC > 1.65 μF. Using a 2.2 μF is a practical choice for CC. CB > 470μF 2 RF AV = RI 2 CC > 8 7 00358-048 VIN,rms AUDIO INPUT 00358-049 AV = PL × RL (19) Each speaker is driven by a single-ended output. The trade-off is that only 250 mW of sustained power can be put into each speaker. Also, a coupling capacitor must be connected in series with each of the speakers to prevent large dc currents from flowing through the 8 Ω speakers. These coupling capacitors produce a high-pass filter with a corner frequency given by Equation 4. For a speaker load of 8 Ω and a coupling capacitor of 470 μF, this results in a −3 dB frequency of 42 Hz. Because the power of a single-ended output is one-quarter that of a bridged output, both speakers together are still half as loud (−6 dB SPL) as a single speaker driven with a bridged output. Rev. D | Page 19 of 24 SSM2211 The polarity of the speakers is important, as each output is 180 degrees out of phase with the other. By connecting the minus terminal of Speaker 1 to Pin 5, and the plus terminal of Speaker 2 to Pin 8, proper speaker phase can be established. Therefore, for PO = 1 W and RL = 8 Ω, V = 2.8 V rms, or 8 V pp. If the available input signal is 1.4 V rms or more, use the board as is, with RF = RI = 20 kΩ. If more gain is needed, increase the value of RF. The maximum power dissipation of the device, assuming both loads are equal, can be found by doubling Equation 11. If the loads are different, use Equation 11 to find the power dissipation caused by each load, then take the sum to find the total power dissipated by the SSM2211. When you have determined the closed-loop gain required by your source level, and can develop 1 W across the 8 Ω load resistor with the normal input signal level, replace the resistor with your speaker. Your speaker can be connected across the VO1 and VO2 posts for bridged-mode operation only after the 8 Ω load resistor is removed. For no phase inversion, VO2 must be connected to the (+) terminal of the speaker. EVALUATION BOARD An evaluation board for the SSM2211 is available. For more information, call 1-800-ANALOGD. VO2 C2 10µF SSM2211 C1 0.1µF SHUTDOWN AUDIO INPUT 2 CIN 1µF RL 1W 8Ω RI 20kΩ 4 7 5 J2 VO1 00358-050 C1 0.1µF Figure 50. Evaluation Board Schematic The voltage gain of the SSM2211 is given by Equation 20. (20) If desired, the input signal may be attenuated by turning the 10 kΩ potentiometer in the CW (clockwise) direction. CIN isolates the input common-mode voltage (VD/2) present at Pin 2 and Pin 3. With V+ = 5 V, there is 2.5 V common-mode voltage present at both output terminals, VO1 and VO2, as well. CAUTION: The ground lead of the oscilloscope probe, or any other instrument used to measure the output signal, must not be connected to either output, as this shorts out one of the amplifier outputs and can possibly damage the device. A safe method of displaying the differential output signal using a grounded scope is shown in Figure 51. Connect Channel A probe to the VO2 terminal post. Connect Channel B probe to the VO1 post. Invert Channel B, and add the two channels together. Most multichannel oscilloscopes have this feature built in. If you must connect the ground lead of the test instrument to either output signal pins, a power-line isolation transformer must be used to isolate the instrument ground from the power supply ground. Recall that V = PROBES CH B VO1 CH B DISPLAY INV. ON A+B Figure 51. Using an Oscilloscope to Display the Bridged-Output Voltage RF 20kΩ RF RI GND OSCILLOSCOPE SSM2211 3 + VO2 J1 8 1 AV = 2 × 8Ω 1W 8 6 ON CW 2.5V COMMON MODE 00358-051 + VOLUME 20kΩ POT. CH A 5 V+ R1 51kΩ To use the SSM2211 in a single-ended-output configuration, replace J1 and J2 jumpers with electrolytic capacitors of a suitable value, with the negative terminals to the output terminals VO1 and VO2. The single-ended loads can then be returned to ground. Note that the maximum output power is reduced to 250 mW (one-quarter of the rated maximum), due to the maximum swing in the nonbridged mode being one-half and power being proportional to the square of the voltage. For frequency response down 3 dB at 100 Hz, a 200 μF capacitor is required with 8 Ω speakers. The SSM2211 evaluation board also comes with a shutdown switch, which allows the user to switch between on (normal operation) and the power-conserving shutdown mode. LFCSP PRINTED CIRCUIT BOARD LAYOUT CONSIDERATIONS The LFCSP is a plastic encapsulated package with a copper lead frame substrate. This is a leadless package with solder lands on the bottom surface of the package, instead of conventional formed perimeter leads. A key feature that allows the user to reach the quoted θJA performance is the exposed die attach paddle (DAP) on the bottom surface of the package. When soldered to the PCB, the DAP can provide efficient conduction of heat from the die to the PCB. In order to achieve optimum package performance, consideration should be given to the PCB pad design for both the solder lands and the DAP. For further information the user is directed to the Amkor Technology document, “Application Notes for Surface Mount Assembly of Amkor’s MicroLead Frame (MLF) Packages.” This can be downloaded from the Amkor Technology website, www.amkor.com, as a product application note. P×R Rev. D | Page 20 of 24 SSM2211 OUTLINE DIMENSIONS 5.00 (0.1968) 4.80 (0.1890) 1 5 6.20 (0.2440) 5.80 (0.2284) 4 1.27 (0.0500) BSC 0.25 (0.0098) 0.10 (0.0040) COPLANARITY 0.10 SEATING PLANE 1.75 (0.0688) 1.35 (0.0532) 0.51 (0.0201) 0.31 (0.0122) 0.50 (0.0196) 0.25 (0.0099) 45° 8° 0° 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157) COMPLIANT TO JEDEC STANDARDS MS-012-A A CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. 060506-A 8 4.00 (0.1574) 3.80 (0.1497) Figure 52. 8-Lead Standard Small Outline Package [SOIC_N] Narrow Body, S-Suffix (R-8) Dimensions shown in millimeters and (inches) 3.00 BSC SQ 0.60 MAX 0.50 0.40 0.30 1 8 PIN 1 INDICATOR 0.90 MAX 0.85 NOM SEATING PLANE TOP VIEW 2.75 BSC SQ 0.50 BSC 1.50 REF 5 1.89 1.74 1.59 4 1.60 1.45 1.30 0.70 MAX 0.65 TYP 12° MAX PIN 1 INDICATOR 0.05 MAX 0.01 NOM 0.30 0.23 0.18 0.20 REF Figure 53. 8-Lead Lead Frame Chip Scale Package [LFCSP_VD] 3 mm × 3 mm Body, Very Thin, Dual Lead (CP-8-2) Dimensions shown in millimeters ORDERING GUIDE Model SSM2211CP-R2 SSM2211CP-REEL SSM2211CP-REEL7 SSM2211CPZ-R21 SSM2211CPZ-REEL 1 SSM2211CPZ-REEL71 SSM2211S SSM2211S-REEL SSM2211S-REEL7 SSM2211SZ1 SSM2211SZ-REEL1 SSM2211SZ-REEL71 SSM2211-EVAL 1 Temperature Range –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C Package Description 8-Lead LFCSP_VD 8-Lead LFCSP_VD 8-Lead LFCSP_VD 8-Lead LFCSP_VD 8-Lead LFCSP_VD 8-Lead LFCSP_VD 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead SOIC_N Evaluation Board Z = Pb-free part; # denotes lead-free product may be top or bottom marked. Rev. D | Page 21 of 24 Package Option CP-8-2 CP-8-2 CP-8-2 CP-8-2 CP-8-2 CP-8-2 R-8 (S-Suffix) R-8 (S-Suffix) R-8 (S-Suffix) R-8 (S-Suffix) R-8 (S-Suffix) R-8 (S-Suffix) Branding B5A B5A B5A B5A# B5A# B5A# SSM2211 NOTES Rev. D | Page 22 of 24 SSM2211 NOTES Rev. D | Page 23 of 24 SSM2211 NOTES ©2006 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. C00358-0-11/06(D) Rev. D | Page 24 of 24