AL6562 NEW PRODUCT Transition Mode PFC LED Controller Description Features The AL6562 is a current mode Power Factor Correction Controller and is designed for operating in Transition Mode. With a superior linear performance multiplier, it ensures the device operates over a wide input voltage range with superior THD (Total Harmonics Distortion). The output voltage is controlled by means of an error amplifier and a precise (1% @ TJ = +25°C) internal voltage reference. The AL6562 is designed to meet stringent energy-saving standards with low start-up current, and can operate with low current consumption when entering stand-by mode. Single Stage Fly-Back PFC Controller Transition Mode Operation Low Start-Up, Operating and Quiescent Currents Internal Start-Up Timer Enable/Disable Function on INV Input Totem Pole, Push-Pull Output Drive Adjustable Output Overvoltage Protection SO-8 : Available in “Green” Molding Compound (No Br, Sb) Totally Lead-Free & Fully RoHS Compliant (Notes 1 & 2) Halogen and Antimony Free. “Green” Device (Note 3) OVP circuitry increases system robustness, allowing the device to withstand transient caused at start-up and during load-disconnects. Pin Assignments Applications (Top View) INV 1 8 Vcc COMP MULT 2 7 3 6 GD GND CS 4 5 ZCD AL656 2 Electronic Single-Stage LED Driver PFC Pre-Regulators to meet IEC61000-3-2 High-End AC-DC Adaptor / Charger SO-8 (SO-8/ M Package) Notes: 1. No purposely added lead. Fully EU Directive 2002/95/EC (RoHS) & 2011/65/EU (RoHS 2) compliant. 2. See http://www.diodes.com/quality/lead_free.html for more information about Diodes Incorporated’s definitions of Halogen- and Antimony-free, "Green" and Lead-free. 3. Halogen- and Antimony-free "Green” products are defined as those which contain <900ppm bromine, <900ppm chlorine (<1500ppm total Br + Cl) and <1000ppm antimony compounds. Typical Applications Circuit Figure 1 High Power Factor Non-Isolated Constant-Current LED Driver AL6562 Document Number: DS37542 Rev. 2 - 2 1 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 Pin Descriptions NEW PRODUCT Pin Number Pin Name 1 INV 2 COMP 3 MULT 4 CS 5 ZCD 6 GND 7 GD 8 VCC Brief Description Inverting Input Pin of the Internal Error Amplifier This pin is connected externally via a resistor divider from the regulated output voltage. It can provide input to inverting input of internal error amplifier. This pin can also be used as ENABLE/DISABLE control input. Output from Error Amplifier A feedback compensation network consisting of resistor and capacitor connects between INV (Pin1) and this pin to reduce the bandwidth and achieve stability of the voltage control loop and ensure high power factor and low THD. Input to the Internal Multiplier This pin connects to the rectified mains voltage through external resistor divider to provide a sinusoidal voltage reference for the control current loop. Current Sense Connecting to External Resistor for Current Feedback The current flowing in the MOSFET is sensed through a resistor, the resulting voltage is applied to this pin and compared with an internal sinusoidal-shaped reference generated by the multiplier to determine MOSFET’s turn-off. This pin has an internal Leading-Edge-Blanking of about 200 nanoseconds to improve noise immunity. Zero Current Detection This pin takes input from inductor’s demagnetization sensing to achieve zero current detection, required for Transition Mode (TM) operation. A negative-going edge triggers turn-on of MOSFET. System Ground Ground for circuit. Current return for both the signal circuitry and the gate drive stage. Gate Driver Output This pin is able to drive external MOSFET. The totem-pole output stage is able to drive MOSFET with a peak current of 600mA/800mA for source and sink capability respectively. The high level voltage of this pin is internally clamped at about 12V to avoid excessive gate voltage in case V CC pin is supplied by a higher voltage. System Power Input Pin This pin is for supply voltage of both the signal part and gate driver of the IC. Upper limit is extended to a maximum of 22V to provide more headroom for supply voltage changes. This pin has an internal 25V Zener to protect the IC itself from overvoltage transients. Functional Block Diagram COMP INV MULT 2 1 CS 3 4 40K Multiplier INV_Disable 0.47 V/0.3V VCC Voltage Regulation Overvoltage Detection 10 pF 1.7V VCC 8 R1 24V R2 R S Internal Supply 7.5V UVLO INV_Disable Q 7 Driver GD Vref Zero Current Detector 2.1V 1.6V Starter Upper & Lower Clamp ZCD_Disable 5 ZCD AL6562 Document Number: DS37542 Rev. 2 - 2 2 of 16 www.diodes.com 6 GND February 2015 © Diodes Incorporated AL6562 Absolute Maximum Ratings (Note 4) Symbol IC Supply Voltage Icc Operating Supply Current Unit V 30 mA ESD (Human Body Model) ESD (Machine Model) V mA mA V V TJ Junction Temperature Range -40 to +150 °C TSTG Storage Temperature Range -65 to +150 °C PTOT Power Dissipation 0.65 W RθJA Thermal Resistance (Junction – Ambient) 150 °C/W TLEAD Lead Temperature (Soldering, 10 sec) +260 °C IZCD (Note 5) NEW PRODUCT Value Self Limited -0.3 to 7 Source: -50 Sink: 10 3000 200 VINV,VCOMP,VMULT ESD(HBM) ESD(MM) Notes: Description VCC Input/Output of Error Amplifier, Input of Multiplier Zero Current Detector Max. Current 4. Stresses greater than the 'Absolute Maximum Ratings' specified above, may cause permanent damage to the device. These are stress ratings only; functional operation of the device at these or any other conditions exceeding those indicated in this specification is not implied. Device reliability may be affected by exposure to absolute maximum rating conditions for extended periods of time. 5. Currents flowing into device pins are considered as positive and out of device pins are considered as negative. AL6562 Document Number: DS37542 Rev. 2 - 2 3 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 Electrical Characteristics NEW PRODUCT (Over recommended operating conditions unless otherwise specified VCC = 12.0V, TJ = -25°C to +125°C, CO = 1nF) Symbol Parameter Conditions Min Typ. SUPPLY VOLTAGE VCC IC Supply Voltage VCC ON Turn-On Threshold VCC OFF Turn-Off Threshold VCC-HYS Hysteresis VZ Zener Voltage SUPPLY CURRENT Istart-up Start-Up Current IQ Quiescent Current ICC Max Units 10.3 11.0 8.7 2.2 22 12.0 9.5 2.5 24 22 13.0 10.3 2.8 V V V V V Before turn-on, VCC=11V After turn-on @ 70kHz 40 2.5 3.5 70 3.75 5 µA mA mA In OVP condition, VINV = 2.7V 1.4 2.2 2.2 After turn-on ICC = 20 mA Operating Supply Current VZCD≤150mV, VCC>VCC-OFF IQ mA mA Quiescent Current VZCD≤150mV, VCC<VCC-OFF 20 50 90 mA 2.465 2.44 2.5 2.535 2.56 V ERROR AMPLIFIER VINV Voltage Feedback Input Threshold Line Regulation IINV GV GB Input Bias Current Voltage Gain Gain-Bandwidth Source Current ICOMP Sink Current Upper Clamp Voltage VCOMP Lower Clamp Voltage VINVdis Disable Threshold VINVen Restart Threshold MULTIPLIER INPUT VMULT Linear Operation Range VCS VMULT Output Maximum Slope K Gain (Note 7) ZERO CURRENT DETECTOR VZCDH Upper Clamp Voltage VZCDL Lower Clamp Voltage VZCDA Arming Voltage VZCDT Triggering Voltage IZCDb Input Bias Current IZCDsrc Source Current Capability IZCDsnk Sink Current Capability VZCDdis Disable Threshold VZCDen Restart Threshold IZCDres Restart Current after Disable STARTER tSTART Start Timer Period Notes: 6. 7. TJ = +25°C 10.3V < VCC < 22V VCC = 10.3V to 22V (Note 6) VINV = 0 to 3V 2 5 mV 60 -2 2.5 2.1 250 400 -0.1 80 1 -4.0 4.5 5.8 2.25 300 470 -1 -8 2.4 350 540 µA dB MHz mA mA V V mV mV 0-3 0 – 3.5 V VMULT = 0 to 0.5V, VCOMP = upper clamp 1.65 1.9 V/V VMULT = 1V,VCOMP = 4V 0.6 0.75 0.9 1/V IZCD = 3mA IZCD = -3mA Positive-going edge Negative-going edge VZCD =1 to 4.5V VZCD<VDIS, VCC>VCC-OFF 4.7 0.3 -2.5 3.0 150 330 -80 5.2 0.65 2.1 1.6 2 200 400 -120 6.1 1.0 -10 250 470 V V V V µA mA mA mV mV µA 75 130 300 µs OPEN LOOP VCOMP = 4V, VINV = 2.4V VCOMP = 4V, VINV = 2.6V ISOURCE = 0.5 mA ISINK = 0.5 mA (Note 6) All parameters are in tracking. The multiplier output is given by: current sense comparator O/P, AL6562 Document Number: DS37542 Rev. 2 - 2 4 of 16 www.diodes.com . February 2015 © Diodes Incorporated AL6562 Electrical Characteristics Symbol Parameter OUTPUT OVER-VOLTAGE IOVP VOVP_TH Conditions Min Typ Max Units 35 2.1 40 2.25 45 2.4 µA V VCS = 0 VCOMP = upper clamp VMULT = 0 VMULT = 2.5V 1.6 200 1.7 30 5 -1 350 1.8 µA ns V mV 0.9 2.5 2.0 1.9 3.0 2.8 V V V 9 30 60 11 70 110 13 ns ns V 1.1 V Dynamic OVP Triggering Current Static OVP Threshold CURRENT SENSE COMPARATOR VCS-clamp Input Bias Current Delay to Output Current Sense Clamp VCS-offset Current Sense Offset NEW PRODUCT ICS td(H-L) GATE DRIVER VOL Output Low Dropout Voltage VOH Output High Dropout Voltage tf tr VOclamp Vos Voltage Fall Time Voltage Rise Time Output Clamp Voltage UVLO Saturation IGDsink = 200 mA IGDsource = 200 mA IGDsource = 20 mA ISOURCE = 5 mA, VCC =20 V VCC =0 V to VCCon, ISINK = 10 mA . AL6562 Document Number: DS37542 Rev. 2 - 2 5 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 Performance Characteristics Supply Current vs. Supply Voltage Start-up & UVLO Vs. TJ 3.0 12.0 2.0 11.5 Voltage (V) Supply Current (mA) 2.5 1.5 CO=1nF f=70kHz o TJ=25 C 1.0 VCC-ON 11.0 10.5 10.0 0.5 9.5 VCC-OFF 0.0 0 5 10 15 20 25 Supply Voltage (V) 9.0 -50 0 50 100 150 o Junction Temperature ( C) Icc Consumption vs.TJ Vcc Zener Voltage Vs. TJ 28 8 4 27 Quiescent 2 1 0.5 0.25 VCC-CLAMP (V) ICC (mA) 26 Disabled or during OVP VCC=12V CO=1nF f=70kHz 25 24 0.125 Before start-up 0.0625 23 0.03125 -50 0 50 100 22 -50 150 0 50 100 150 o Junction Temperature ( C) o Junction Temperature ( C) Feedback Reference Voltage vs. TJ OVP Current vs. TJ 2.60 43.0 42.5 VCC=12V VCC=12V 2.55 42.0 IOVP (A) 41.5 VREF (V) NEW PRODUCT 12.5 2.50 2.45 41.0 40.5 40.0 39.5 2.40 -50 0 50 100 150 39.0 -50 O Junction Temperature ( C) AL6562 Document Number: DS37542 Rev. 2 - 2 0 50 100 150 o Junction Temperature ( C) 6 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 Performance Characteristics (cont.) Delay-to-output vs.TJ E/A Output Clamp Levels Vs. TJ 6.0 500 5.5 VCC=12V 400 Upper Clamp VCOMP (V) td(H-L) (ns) VCC=12V 4.5 300 200 4.0 3.5 3.0 100 Lower Clamp 2.5 0 -50 0 50 100 2.0 -50 150 0 o 1.0 1.8 0.8 1.6 Multiplier Gain VCS-CLAMP (V) 150 Multiplied Gain Vs. TJ 2.0 1.4 VCC=12V VCOMP=Upper Clamp 1.2 0 100 Junction Temperature ( C) VCS-CLAMP vs.TJ 1.0 -50 50 o Junction Temperature ( C) 50 100 VCC=12V VCOMP=4V VMULT=1V 0.6 0.4 0.2 150 0.0 -50 o 0 50 100 150 o Junction Temperature ( C) Junction Temperature ( C) ZCD Source Capability vs.TJ ZCD Clamp Levels Vs. TJ 0 7 VCC=12V 6 Upper Clamp VZCD=Lower Clamp -2 VZCD (V) 5 IZCD (mA) NEW PRODUCT 5.0 -4 VCC=12V IZCD= + 2.5mA 4 3 2 -6 Lower Clamp 1 -8 -50 0 50 100 150 0 -50 o Junction Temperature ( C) AL6562 Document Number: DS37542 Rev. 2 - 2 0 50 100 150 o Junction Temperature ( C) 7 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 Performance Characteristics (cont.) Start-up Timer vs.TJ Multiplier Characteristics 200 1.8 1.6 VCOMP=3.5 VCOMP=4.0 180 1.4 170 1.2 VCS (V) tSTART (S) VCC=12V VCOMP=MAX VCOMP=5.0 VCOMP=4.5 160 VCOMP=3.2 1.0 0.8 VCOMP=3.0 150 0.6 140 0.4 130 VCOMP=2.8 0.2 120 -50 0 50 100 0.0 0.0 150 VCOMP=2.6 0.5 1.0 1.5 o 2.0 2.5 3.0 3.5 4.0 4.5 VMULT (V) Junction Temperature ( C) Gate-driver Output Low Saturation Gate-driver Output High Saturation VGD (V) VCC-2.0 6 5 TJ=25 C VCC=11V SINK VGD (V) 4 o TJ=25 C VCC=11V SOURCE VCC-2.5 o VCC-3.0 3 VCC-3.5 2 VCC-4.0 1 0 0 200 400 600 800 0 1000 100 200 IGD (mA) 300 400 500 600 700 IGD (mA) Gate-driver Clamp vs. TJ UVLO Saturation vs. TJ 15 1.1 VCC=0V 1.0 14 VCC=20V 0.9 13 VGD_OFF (V) VGD_CLAMP (V) NEW PRODUCT 190 12 0.8 0.7 11 0.6 10 -50 0 50 100 150 0.5 -50 Document Number: DS37542 Rev. 2 - 2 50 100 150 o Junction Temperature ( C) AL6562 0 Junction Temperature ( C) o 8 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 NEW PRODUCT Application Information Figure 2 Boost Pre-Regulator PFC POWER FACTOR CORRECTION AL6562 functions as a transition mode PFC IC, meaning the MOSFET turns on when inductor current reaches zero, and turns off when the current meets desired input current reference voltage, as shown in Figure 3. A typical current waveform is depicted with envelope as shown, with the input current following that of the input voltage, achieving good power factor. Figure 3 Typical Waveform of Inductor Current with Fixed ON Time From a mathematical point of view, a PF value can be defined by: θ θ ∞ Where θ represents displacement factor with as the displacement angle between voltage and current fundamentals, and distortion respectively. AL6562 Document Number: DS37542 Rev. 2 - 2 9 of 16 www.diodes.com represents February 2015 © Diodes Incorporated AL6562 Application Information (cont.) NEW PRODUCT , the distortion can further be defined by: Where and are the RMS (Root Mean Square) value n-th fundamental component of the current respectively. If the current and voltage are in phase, then θ= 0, which will lead to θ and the PF will be simplified as: ZCD (Zero Current Detection) The ZCD feature detects when the transformer primary current falls to zero, as the voltage across the inductor reverses, to initiate a new cycle that switches on the power MOSFET. The signal for ZCD is obtained by an auxiliary winding on the boost inductor, as shown in Figure 2. Multiplier The internal multiplier takes two inputs, one from a portion of the instantaneous rectified line voltage (via pin 3, MULT) and the other from the output of the E/A (via pin 2, COMP), to feed the PWM comparator to determine the exact instant when the MOSFET is to be switched off. The output of multiplier is a rectified sinusoid, similar to the instantaneous rectified line voltage, multiplied by the scaling factor determined by output of the Error Amplifier. The MULT output is then fed into the PWM comparator and is compared to the current sense voltage VCS, to switch the Power MOSFET off. The formula governing all parameters is given by: Multiplier Output: Where: k is the multiplier gain. VMULT is set by external resistors R1 and R2. OVP (Output Overvoltage Protection) The output voltage can be kept constant by the operation of the PFC circuit close to its nominal value, as shown by Figure 2, which is set by the ratio of the two external resistors R3 and R4. Neglecting ripple current, current flowing through R3, I R3, will equal the current through R4, IR4. As the non-inverting input of the error amplifier is biased inside the AL6562 at 2.5V, the current through R4 is: (1) If any abrupt change of output voltage, ΔVO > 0 occurs due to a load drop, the voltage at pin INV will be kept at 2.5V by the local feedback of the EA. The network connected between INV and COMP introduces a time constant to achieve high PF. The current through R4 will remain equal to 2.5/R4, but IR3 will become: (2) The difference current will flow through the compensation network and enter the error amplifier output via pin COMP. The AL6562 monitors the current flowing into the error amplifier output pin. When the detected current is higher than 40µA, the dynamic OVP is triggered. The IC will be disabled and the driver signal will be stopped. The output ΔVo that is able to trigger the Dynamic OVP function is then: (3) AL6562 Document Number: DS37542 Rev. 2 - 2 10 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 Application Information (cont.) NEW PRODUCT On the other hand, when the loading of PFC pre-regulator becomes low, the output voltage tends to stay steadily above the nominal value, which is not the case when OVP is triggered by abrupt voltage increase. If this occurs, the E/A will saturate low, the external power transistor is switched OFF, and the IC is put in idle state (static OVP). Normal operation is resumed as the error amplifier goes back into its linear region. As a result, the device will work in burst-mode, with a repetition rate that can be very low. When either OVP is activated, the quiescent consumption of the IC is reduced to minimum by the discharge of the capacitor and increases the hold-up capability of the IC supply. THD (Total Harmonics Distortion) The AL6562 reduces the THD by reducing conduction dead-angle occurring to the AC input current near the zero-crossings of the line voltage. The important reason for this distortion to take place is the inability of the system to transfer energy effectively when the instantaneous line voltage is very low, which is the case near line-voltage zero-crossing. This effect is magnified by the high-frequency filter capacitor placed after the bridge rectifier, which retains some residual voltage that causes the diodes of the bridge rectifier to be reverse-biased and the input current flow to temporarily stop. To overcome this issue, the circuit section designed in the AL6562 forces the PFC regulator to process more energy near the line voltage zero-crossings, as compared to that commanded by the control loop. This results in both minimizing the time interval when energy transfer is lacking, and fully discharging the high-frequency filter capacitor after the bridge. In essence, the circuit artificially increases the ON-Time of the Power Switch with a positive offset added to the output of the multiplier in the proximity of the line voltage zero-crossings. This offset is reduced as the instantaneous line voltage increases, so that it becomes negligible as the line voltage moves towards the peak of the sinusoidal waveform. Therefore, to maximize the benefit from the THD improvement circuit, the high-frequency filter capacitor after the bridge rectifier should be minimized and kept to satisfy the EMI filtering requirements. Non-Latched IC Disable (Enable) Pin 1, INV, inverting input to the error amplifier, can be adapted to disable the system when the voltage on this pin is below 0.2V. In order to restart the system, a voltage exceeding 0.45V must be applied. The ON/OFF control signal can be driven by a PWM controller and using an NPN transistor to pin 1 to shut it down. AL6562 Document Number: DS37542 Rev. 2 - 2 11 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 Application Information (Cont.) Single Stage LED Driver with PFC One of the major applications of AL6562 is to provide a single stage power module with high PF for LED lighting. The following circuit, Figure 4, shows a simplified fly-back AC-DC converter with both CC and CV feedback from output side, to prevent overload and also provide an overvoltage protection facility. NEW PRODUCT CY1 Snuber Vo C6 R3 AC input R1 D1 R7 C4 R8 Z1 C5 R4 C1 (5) ZCD OptoCoupler (2) COMP (8) Vcc R6 R11 (1) R9 INV AL6562 (3) MULT C3 R2 C2 GND (6) CS (4) M1 GD (7) Secondary side loop control R12 R5 CY2 ILED R10 Figure 4 Single Stage PFC Isolated LED lighting With its high performance, the AL6562 offers the following advantages that make this solution an appropriate method against the traditional PWM controller, where a good PF value is required: The input capacitance can be reduced to replace a bulky and expensive high-voltage electrolytic capacitor (as required by regular offline SMPS) by a small-size, cheaper film capacitor. Transition mode ensures low turn-on losses in MOSFET and higher efficiency can be achieved. Lower parts count means lower material cost, as well as lower assembly cost for limited space. AL6562 Document Number: DS37542 Rev. 2 - 2 12 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 Application Information (Cont.) PFC Pre-Regulator Another major application of AL6562 is to implement a wide-range mains input PFC pre-regulator, which acts as the input stage for the cascaded DC-DC converter and can deliver above 350W in general. There are two methods, in general, to design a pre-regulator stage: NEW PRODUCT 1. 2. With fixed frequency or With fixed ON time The AL6562 can easily be implemented with fixed ON time due to its simplicity, while the fixed frequency technique is more complicated. In fixed ON time mode, AL6562 is also working in transition mode where the inductor current will be turned on when zero crossing is detected. By using boost-switching technique, the AL6562 shapes the input current by drawing a quasi-sinusoidal current in-phase with the line voltage. A simplified circuit, shown in Figure 5, explains the operation as follows: Figure 5 ZCD Pin Synchronization without Auxiliary Winding The AC mains voltage is rectified by a diode bridge and delivered to the boost converter which boosts the rectified input voltage to a higher regulated DC bus VO. The error amplifier compares a portion of the output voltage with an internal reference and generates a signal error proportional to the difference between them. The bandwidth of the internal error amplifier is set to be narrow within 20Hz; the output would be a DC value over a given half-cycle. Output of E/A fed into multiplier, multiplied by a portion of the rectified mains voltage, will generate a scaled rectified sinusoid whose peak amplitude depends on the rectified mains peak voltage as well as the value of error signal. The output of the multiplier is fed into the non-inverting pin of the internal PWM comparator. As the output from the multiplier, a sinusoidal reference for PWM, equals the voltage on the current sense pin CS(4), the MOSFET will be turned off. As a consequence, the peak inductor current will follow the envelope of a rectified sinusoid. After the MOSFET is turned off, the boost inductor discharges its stored energy to the load until zero current is detected and then the MOSFET will be turned on again. In the case where there is no auxiliary winding on the boost inductor, a solution can be implemented by sconnecting the ZCD pin to the drain of the power MOSFET through an R-C network: in this way the high-frequency edges experienced by the drain will be transferred to the ZCD pin, hence arming and triggering the ZCD comparator. The resistance value must be properly chosen to limit the current sourced/sunk by the ZCD pin. In typical applications with output voltages around 400V, recommended values for these components are 22pF (or 33pF) for CZCD and 330K for RZCD. With these values proper operation is ensured even with a few volts difference between the regulated output voltage and the peak input voltage. AL6562 Document Number: DS37542 Rev. 2 - 2 13 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 Ordering Information NEW PRODUCT AL6562 XX–13 Packing Package S : SO8 13 :13" Tape & Reel Part Number Package Package code AL6562S-13 SO-8 S 13” Tape and Reel Quantity Part Number Suffix 2,500/Tape & Reel -13 Marking Information (1) SO-8 AL6562 Document Number: DS37542 Rev. 2 - 2 14 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 Package Outline Dimensions (All Dimensions in mm.) 0.254 NEW PRODUCT Please see AP02002 at http://www.diodes.com/datasheets/ap02002.pdf for the latest version. E1 E A1 L SO-8 Dim Min Max A 1.75 A1 0.10 0.20 A2 1.30 1.50 A3 0.15 0.25 b 0.3 0.5 D 4.85 4.95 E 5.90 6.10 E1 3.85 3.95 e 1.27 Typ h 0.35 L 0.62 0.82 0 8 All Dimensions in mm Gauge Plane Seating Plane Detail ‘A’ 7°~9° h 45° Detail ‘A’ A2 A A3 b e D Suggested Pad Layout Please see AP02001 at http://www.diodes.com/datasheets/ap02001.pdf for the latest version. X C1 Dimensions X Y C1 C2 Value (in mm) 0.60 1.55 5.4 1.27 C2 Y AL6562 Document Number: DS37542 Rev. 2 - 2 15 of 16 www.diodes.com February 2015 © Diodes Incorporated AL6562 IMPORTANT NOTICE NEW PRODUCT DIODES INCORPORATED MAKES NO WARRANTY OF ANY KIND, EXPRESS OR IMPLIED, WITH REGARDS TO THIS DOCUMENT, INCLUDING, BUT NOT LIMITED TO, THE IMPLIED WARRANTIES OF MERCHANTABILITY AND FITNESS FOR A PARTICULAR PURPOSE (AND THEIR EQUIVALENTS UNDER THE LAWS OF ANY JURISDICTION). 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LIFE SUPPORT Diodes Incorporated products are specifically not authorized for use as critical components in life support devices or systems without the express written approval of the Chief Executive Officer of Diodes Incorporated. As used herein: A. Life support devices or systems are devices or systems which: 1. are intended to implant into the body, or 2. support or sustain life and whose failure to perform when properly used in accordance with instructions for use provided in the labeling can be reasonably expected to result in significant injury to the user. B. A critical component is any component in a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or to affect its safety or effectiveness. Customers represent that they have all necessary expertise in the safety and regulatory ramifications of their life support devices or systems, and acknowledge and agree that they are solely responsible for all legal, regulatory and safety-related requirements concerning their products and any use of Diodes Incorporated products in such safety-critical, life support devices or systems, notwithstanding any devices- or systemsrelated information or support that may be provided by Diodes Incorporated. Further, Customers must fully indemnify Diodes Incorporated and its representatives against any damages arising out of the use of Diodes Incorporated products in such safety-critical, life support devices or systems. Copyright © 2015, Diodes Incorporated www.diodes.com AL6562 Document Number: DS37542 Rev. 2 - 2 16 of 16 www.diodes.com February 2015 © Diodes Incorporated