MIL-PRF-38534 AND 38535 CERTIFIED FACILITY RAD HARD HIGH VOLTAGE SYNCHRONOUS SWITCHING REGULATOR 5063RH SERIES FEATURES: • • • • • • • • • Manufactured using Space Qualified RH3845 Dice Radiation Hardened to 300 Krad(Si) (Method 1019.7 Condition A) High Voltage Operation: Up to 60V Input, and 36V Output Programmable Frequency 100-500KHz, or Synchronizable to 600KHz 65µA Shutdown Supply Current Antislope Compensation – Current Limit Unaffected by Duty Cycle Reverse Inductor Current Inhibit – Improves Efficiency with Light Loads External Compensation Contact MSK for MIL-PRF-38534 Qualification Status DESCRIPTION: The MSK5063RH is a radiation hardened wide input voltage range step-down synchronous switching regulator. The wide input range, programmable output voltage and switching frequency, make these regulators suitable for a wide variety of medium to high power applications. The adjustable operating frequency provides the flexibility to keep the switching noise out of sensitive frequency bands, and when synchronized, can be ganged out of phase with other regulators for reduced noise and component size. The MSK5063RH is hermetically sealed in a 46 pin flatpack, and is available with straight or gull wing leads. EQUIVALENT SCHEMATIC TYPICAL APPLICATIONS • • • • • PIN-OUT INFORMATION POL Applications Intermediate Bus Converter Satellite System Power Supply Step Down Synchronous Regulator High Efficiency Subsystem Supply 1, 2 3, 4 5 6 7 8 VIN SGND SYNC FSET COMP VFB 9 10 11 12, 13 14 - 23 24 - 33 MODE SS SHDN BIAS PVIN PGND 34 - 43 44 45 46 SWOUT SENSE+ SENSECASE CASE = ISOLATED 1 8548-115 Rev. G 3/18 ABSOLUTE MAXIMUM RATINGS VIN PVIN BIAS SWOUT IOUT VSENSE 8 Input Voltage ..................................................... 65V Power Input Voltage .......................................... 60V Bias Supply Voltage .......................................... 14V SWOUT Voltage ........7........................... 60V to -2V Output Current .................................................. 10A SENSE+ and SENSE- Voltages ....................... 40V Differential Sense Voltage ................................ ±1V SYNC, COMP, VFB, SS and SHDN ................... 5V MODE .............................................................. 24V SHDN Pin Currents .......................................... 1mA TLD Lead Temperature Range (10 Seconds) ................................................. 300°C TST Storage Temperature ....................... -65°C to 150°C TJ Junction Temperature .................................... 150°C TC Operating Case Temperature ........ -55°C to +125°C ESD Rating ......................................................... 1C ELECTRICAL SPECIFICATIONS MSK5055K/H RH Group A Subgroup Min. Typ. Max. BIAS OPEN 1, 2, 3 7.5 1, 2, 3 3.6 3.8 4 Post 100 Krad(Si) 1 3.55 3.6 4 Post 300 Krad(Si) 1 3.45 3.5 4 BIAS ≥ 9V 1 130 - Parameter Test Conditions VIN Min Start Voltage VIN UVLO Threshold (Falling) VIN Supply Current 2 VIN Shutdown Current BIAS Supply Current 2 BIAS Current Limit Static Drain-to-Source on Resistance ID = 1.0A COMP = VFB Post 100 Krad(Si) Post 300 Krad(Si) VFB = VREF Error Amp Reference Voltage 2 SHDN Enable Threshold (Rising) SHDN Threshold Hysteresis 9 VSHDN = 0V FSYNC = 100KHz FSYNC = 600KHz 2 VFB Pin Input Current 1 Post 300 Krad(Si) 2 (VSENSE+) - (VSENSE-), VFB = 0V Post 100 Krad(Si) Post 300 Krad(Si) VSENSE (CM) = 0V Current Limit Sense Voltage Input Current (ISENSE+) + (ISENSE-) 2 RSET = 49.9KΩ Operating Frequency Post 300 Krad(Si) FSW ≤ 100kHz at RSET = 232KΩ FSW ≥ 500kHz at RSET = 20KΩ 100kHz ≤ FSYNC ≤ 600kHz Programmable Frequency Range External Sync Frequency Range Sync Voltage Threshold Soft-Start Capacitor Control Current 2 1, 2, 3 1 1 1, 2, 3 1, 2, 3 1, 2, 3 1 1 1 1, 2, 3 1 1 1, 2, 3 1 1 1 4 5, 6 4 MSK5055RH Min. Typ. Max. 7.5 3.6 3.8 4 3.55 3.6 4 3.45 3.5 4 130 - 65 65 16 16 63 63 40 40 0.06 0.1 0.06 0.1 1.214 1.231 1.250 1.214 1.231 1.250 1.200 1.222 1.250 1.200 1.222 1.250 1.173 1.197 1.250 1.173 1.197 1.250 35 35 1.3 1.37 1.5 1.3 1.37 1.5 1.25 1.3 1.5 1.25 1.3 1.5 125 125 85 100 125 85 100 125 80 103 125 80 103 125 70 92 125 70 92 125 705 705 270 320 370 270 320 370 240 390 260 320 370 260 320 370 Units V V V V uA uA mA mA mA Ohm V V V nA V V mA mV mV mV uA KHz KHz KHz 7, 8a, 8b Pass - - Pass - - Pass/Fail 7, 8a, 8b 1, 2, 3 1 Pass - 1.4 11 2 - Pass - 1.4 11 2 - Pass/Fail V uA Error Amp Transconductance 2 1, 2, 3 - 450 - - 450 - uS Error Amp DC Voltage Gain 2 1 - 62 - - 62 - dB 1 - ±30 - - ±30 - uA EACH MOSFET - - 2.2 3.8 - 2.2 3.8 °C/W CONTROLLER - - 2.3 4.2 - 2.3 4.2 °C/W Error Amp Sink/Source Current Thermal Resistance 2 2 Junction to Case @ 125°C 2 8548-115 Rev. G 3/18 NOTES: 1 Unless otherwise specified VIN = 20V, BIAS = 10V, SHDN ≥ 2V, RSET = 49.9KΩ, SENSE- = SENSE+ = 10V, SGND = PGND = SYNC = 0V. 2 Guaranteed by design but not tested. Typical parameters are representative of device performance but are for reference only. 3 Industrial grade devices shall be tested to subgroup 1 unless otherwise specified. 4 Military grade devices (“H” and “K” suffix) shall be 100% tested to subgroups 1,2,3,4 and 7. 5 Subgroup 3,6 and 8 available upon request. 6 Subgroup 1,4,7 Subgroup 2,5,8a Subgroup 3,6,8b 7 The -2V absolute maximum on the SWOUT pin is a transient condition. It is guaranteed by design, but not tested. Negative transients of up to -2V occur at SWOUT as part of normal operation. Direct application of power to the SWOUT pin may damage the device. 8 Continuous operation at or above absolute maximum ratings may adversely affect the device performance and/or life cycle. 9 Pre and post irradiation limits at 25°C, up to 300 Krad(Si) TID, are identical unless otherwise specified. TC = +25°C TC = +125°C TC = -55°C 3 8548-115 Rev. G 3/18 APPLICATION NOTES PIN FUNCTIONS COMP – The COMP pin provides a means to externally compensate the loop response of the controller. COMP is the output of the transconductance error amplifier. A capacitor to ground creates a pole in the control loop. A series RC creates a pole zero combination in the control loop. If the COMP pin is externally manipulated, use a series impedance of 1KΩ. VIN – The VIN pins are the input supply pins for the control circuitry inside the device. Decouple to SGND with a low ESR capacitor located close to the pin. BIAS – The BIAS pins provide access to the internal 8V bias supply for decoupling and optional external sourcing. It is the power supply for most of the internal functions and the MOSFET gate drive. BIAS can only source current and may be tied to an external source to improve efficiency and allow for lower voltage operation. If BIAS is tied to an external source greater than 6.5V the device will operate with Vin as low as 4V. This configuration reduces power dissipation in the device by bypassing the internal regulator. The BIAS pin charges the bootstrapped capacitor through a diode connected to the BOOST pin. In shutdown mode the BIAS pin sinks 20µA until the pin voltage is discharged to zero volts. MODE – The MODE pin is used to inhibit or enable reverse current in the synchronous rectifier. Connect to VFB to inhibit reverse current. This allows discontinous current (DCM) at light loads. The PWM will skip pulses to maintain regulation. This improves efficiency at very light load. Connect MODE to VCC to enable reverse current. This allows for continuous current (CCM) at light loads. This configuration is less efficient at light loads but operates at a constant switching frequency. SENSE-- The SENSE- pin is the negative input to the current sense amplifier. The sensed inductor current limit is set to 100mV across the SENSE inputs. NOTE: When driving VBIAS from an external source, the source must be greater than or equal to 9V and connect through a series diode. RSENSE = 70mV/IOUT(MAX) PVIN – The PVIN pins are the power input supply for the regulator. High frequency current switching is present at this node. Decouple to PGND with a low ESR tantalum capacitors in parallel with ceramic capacitors located close to the pins. Given: IP-P < 0.30 x IOUT(MAX) SENSE+ - The SENSE+ pin is the positive input to the current sense amplifier. The sensed inductor current limit is set to 100mV across the SENSE inputs. PGND – The PGND pins are the high-current ground reference. Connect them directly to the negative side of the PVIN decoupling capacitors. Care should be taken to make sure that these currents are not referenced by the SGND pin to avoid injecting noise into the ground reference. RSENSE = 70mV/IOUT(MAX) Given: IP-P < 0.30 x IOUT(MAX) SGND – the SGND pins should be connected to the negative side of the VIN capacitor. Use a common ground plane to minimize impedance, but locate the high current fast switching devices together so their returns remain local and do not corrupt the SGND reference. VFB – The VFB (Feedback) pin is used to set the output voltage. Use a resistive divider to set the voltage at the VFB pin to 1.231V when the output is at the desired level. SHDN – The SHDN pin provides a method to disable the device. This pin has 125mV of hysterisis. Pull below 1.23V (nominal) to disable switching, pull above 1.35V to enable switching. Pull below one VBE (0.7V nominal) to enter low power shutdown. A resistor divider to VIN can be used to set UVLO using the 1.35V threshold. When not in use, pull the pin up to VIN with a large value resistor. When exceeding the absolute maximum rating of 5V the pin voltage will be clamped at 6V nominal. Limit the current into the pin to less than 1mA to prevent overstress. VO = VFB 1+ R1 R2 FSET – The FSET pin programs the oscillator frequency via a single resistor to ground. The RSET resistor must be present even when synchronization mode is used—Use the formula or the table below to select the resistance value for a desired frequency. SS – The SS pin is used for soft start. It allows the user to program the rate of change of the output at start-up. The capacitance required for a given output slew rate can be calculated using the SS = 11µA(TSS/1.231V) The pin should be left open if not in use. SWOUT– The SWOUT pins are the switched output of the regulator. Connect these pins directly to the inductor of the output filter and optionally to the cathode of the schottky catch diode. The external schottky catch diode is optional. 4 8548-115 Rev. G 3/18 APPLICATION NOTES CONT'D The RMS current capability is related to power dissipation capability of the capacitor. Replace the capacitor with one that has a higher rating, or place more capacitors in parallel if more capability is needed. Sharing of ripple current between capacitors will be approximately equal if all of the capacitors are the same type, and preferably from the same lot. The RMS current seen by the input capacitors can be approximated by the following equation: RSET(KΩ) ≈ 9.55 x 104 x fSW(KHZ) (-1.31) RSET (KΩ) FSW (KHz) 229 100 135 150 92.0 200 67.3 250 IRMS ≅ IOUT x SQRT (3D^2 - 3D +1) 54.2 300 44.2 350 Given: D ≅ VOUT/VIN 37.4 400 32.0 450 27.7 500 Parallel ceramic capacitors are required to filter the high frequency components of the switching waveform. Locate the bias supply capacitors close to the VIN and SGND pins on the MSK5063RH. Locate the power input capacitors close to the drain of the forward switch (PVIN) and the source of the synchronous rectifier (Power Ground). Use short, wide PCB lands to minimize parasitic impedances. SYNC – The SYNC pin is the input for synchronization of the internal oscillator to an external clock. Program the internal oscillator to be between 10% and 25% below the external clock. The recommended signal is a square wave of at least 2V in amplitude, a pulse width greater than 1µS, and a rise time of less than 500nS. If the SYNC pin is not used in the application, tie it to SGND. SELECTING THE SWITCHING FREQUENCY The MSK5063RH can be set to operate over a frequency range of 100KHz to 500KHz, and is synchronizeable up to 600KHz. There are several factors to consider when selecting the operating frequency including: efficiency, component size, output ripple, application sensitive frequency bands, and the minimum on time of the controller. The output ripple voltage and efficiency will vary with frequency and input voltage. Higher frequencies increase switching losses, but use smaller inductors and/or bulk capacitors saving board space. Lower frequencies reduce switching losses, but increase ripple current and require larger inductors and/or bulk capacitance to achieve the same output ripple voltage. TYPICAL APPLICATION CIRCUIT SELECTING THE OUTPUT CAPACITOR The output capacitor filters the ripple current from the inductor to an acceptable ripple voltage seen by the load. The primary factor in determining voltage ripple is the ESR of the output capacitor. The voltage ripple can be approximated as follows: SELECTING THE INPUT CAPACITOR VP-P = IP-P x ESR The input capacitance provides a low impedance source to the input of the regulator. A low impedance is necessary for high speed, high efficiency switching and tight regulation. The input bus sources an average DC current while the input capacitance sources the AC component of the input current. Select the input capacitor based on voltage ripple requirements, RMS current rating and bulk capacitance. Assuming the capacitor ESR is lower than the bus impedance at the switching frequency and above, the ESR will dominate the voltage ripple. The capacitive term of the output voltage ripple lags the ESR term by 90° and can be calculated as follows: VP-P(CAP) = IP-P/ (8 x f x c) Where: C = output capacitance in Farads Select a capacitor or combination of capacitors that can tolerate the worst-case ripple current with sufficient de-rating. When using multiple capacitors in parallel to achieve lower ESR or more bulk capacitance, sharing of ripple current between capacitors will be approximately equal if all of the capacitors are the same type, and preferably from the same lot. Low ESR tantalum capacitors are recommended over aluminum electrolytic capacitors. Use ceramic decoupling capacitors to minimize high frequency noise. VP-P ≅ IP-P x ESR Given: IP-P = IOUT 5 8548-115 Rev. G 3/18 APPLICATION NOTES CONT'D COMPENSATING THE LOOP ADDITIONAL APPLICATION INFORMATION The feedback loop response can be optimized for the application by adjusting the values of the RC network from the COMP pin to ground. Analysis is recommended to determine the phase margin and gain margin at the specific input voltage and load conditions of the application. Typically, a single RC network from COMP to ground works well. An additional ceramic capacitor from COMP to ground may be needed to cancel the zero and prevent high frequency ringing or instability. For additional applications information, please reference Linear Technology’s® LT3845 data sheet. SELECTING THE INDUCTOR The important parameters for inductor selection are: its value, volt-second product, saturation and RMS current. To determine the peak current in the inductor add ½ of the p-p ripple current to the desired IOUT(MAX). A typical starting point for peak to peak current ripple is 20% of IOUT(MAX). Use the following equation to determine the RMS current: IRMS = IDC * SQRT ( 1+ (1/3) * (∆I/IDC)2 ) Given: IDC = The DC output current ∆I = ½ of the peak to peak ripple current The minimum inductance value can be calculated as follows: LMIN > VOUT x 2DCMAX-1 DCMAX x RSENSE x 8.33 fSW Given: DC = Duty Cycle = VOUT/VIN fSW = Switching Frequency This calculation also accommodates the max ripple/DC requirements for the slope compensation circuit. The volt-seconds product can be calculated as follows: V*S = VI x dt Given: VI = the inductor voltage (VIN – VO) dt = VO/(VIN x fSW) Allow sufficient derating to prevent saturation and/or overstress when selecting the inductor. TOTAL DOSE RADIATION TEST PERFORMANCE Radiation performance curves for TID testing have been generated for all testing performed by MSK. These curves show performance trends throughout the TID process, and will be located in the MSK5063RH radiation test report. The complete test report will be available in the RAD HARD PRODUCTS section of the MSK website. 6 8548-115 Rev. G 3/18 TYPICAL PERFORMANCE CURVES 7 8548-115 Rev. G 3/18 TYPICAL PERFORMANCE CURVES CONT'D 8 8548-115 Rev. G 3/18 TYPICAL PERFORMANCE CURVES CONT'D NORMALIZED POWER SWITCH STATIC RDSON BIAS CURRENT vs BIAS VOLTAGE 1.8 70 60 1.4 BIAS CURRENT (mA) NORMALIZED RDSON (Ω/Ω) 1.6 1.2 1 0.8 0.6 50 40 30 20 0.4 10 0.2 VBIAS = 10V 0 -55 -35 SYNCHRONOUS SWITCHING FREQUENCY = 300KHz 0 -15 5 25 45 65 CASE TEMPERATURE (°C) 85 105 125 8 BIAS CURRENT vs SYNCHRONOUS SWITCHING FREQUENCY 9 90 11 BIAS VOLTAGE (V) 12 13 14 EFFICIENCY vs LOAD CURRENT 90 100 10 85 70 EFFICIENCY (%) BIAS CURRENT (mA) 80 60 50 40 30 20 80 75 70 VOUT = 1.5V fSW= 500KHz MODE = BIAS = VIN = 7V 65 10 0 VBIAS = 10V 100 60 200 300 400 500 SYNCHRONOUS SWITCHING FREQUENCY (KHz) 0 600 1 2 95 95 90 90 85 85 EFFICIENCY (%) EFFICIENCY (%) 100 80 75 6 7 8 9 7 8 9 80 75 VOUT = 15V fSW= 430KHz VIN = PVIN MODE = BIAS = VOUT - 5Vz 70 VOUT = 5V fSW= 500KHz MODE = BIAS = VIN = 7V 65 4 5 LOAD CURRENT (A) EFFICIENCY vs LOAD CURRENT EFFICIENCY vs LOAD CURRENT 100 70 3 65 60 60 0 1 2 3 4 5 LOAD CURRENT (A) 6 7 8 0 9 9 1 2 3 4 5 LOAD CURRENT (A) 6 8548-115 Rev. G 3/18 MECHANICAL SPECIFICATIONS ESD TRIANGLE INDICATES PIN 1 WEIGHT=9.4 GRAMS TYPICAL DIMENSIONS ARE SPECIFIED IN INCHES ORDERING INFORMATION MSK5063 K RH LEAD CONFIGURATIONS BLANK= STRAIGHT RADIATION HARDENED SCREENING BLANK= INDUSTRIAL; H=MIL-PRF-38534 CLASS H; K=MIL-PRF-38534 CLASS K GENERAL PART NUMBER 10 8548-115 Rev. G 3/18 MECHANICAL SPECIFICATIONS ESD TRIANGLE INDICATES PIN 1 WEIGHT=9.3 GRAMS TYPICAL DIMENSIONS ARE SPECIFIED IN INCHES ORDERING INFORMATION MSK5063 K RH G LEAD CONFIGURATIONS G=GULL WING RADIATION HARDENED SCREENING BLANK= INDUSTRIAL; H=MIL-PRF-38534 CLASS H; K=MIL-PRF-38534 CLASS K GENERAL PART NUMBER 11 8548-115 Rev. G 3/18 REVISION HISTORY REV B C D E F G STATUS Released Released Released Released Released Released DATE 02/14 08/14 07/15 09/15 04/16 03/18 DESCRIPTION Release data sheet, add form #, update bias supply current, add performance curves Update post rad specifications, add efficiency curves. Revise switching frequency limits update format. Add ESD rating, correct VFB application note. Update specifications, clarification of application notes. Update to match manufacturer's specs. ANAREN, MSK Products www.anaren.com/msk The information contained herein is believed to be accurate at the time of printing. Anaren, MSK products reserves the right to make changes to its products or specifications without notice, however and assumes no liability for the use of its products. Please visit our website for the most recent revision of this datasheet. Contact Anaren, MSK Products for MIL-PRF-38534 qualification status. 12 8548-115 Rev. G 3/18