STMicroelectronics AN1842 60w wide-range power supply Datasheet

AN1842
APPLICATION NOTE
60W WIDE-RANGE POWER SUPPLY
FOR LCD MONITOR OR TV, USING THE L5991
by Claudio Spini
This document describes a reference design for a 60W Switch Mode Power Supply dedicated to LCD
TV sets or monitors. The board accepts full range input voltage (90 to 265Vrms) and delivers 5V and
12V. It has good efficiency and very good standby performance, able to meet the most stringent
standby rules.
Introduction
The LCD monitors and TVs are growing very fast, so to support this kind of applications, a dedicated reference design has been developed, taking into account all the requirements that are needed.
The proposed reference design can supply an LCD monitor or an LCD-TV as well, up to 22" panels, together with multimedia functions like audio. The SMPS accepts a full range input voltage and delivers 2
output voltages, a 5V dedicated to the scaler and µP, and a 12V dedicated to the backlight and audio. The
required standby power consumption is 0.8W at 230Vac, in order to satisfy the worldwide power saving
rules. The circuit is also fully protected against faults like output short circuit or over voltage. The market
cost pressure has requested a design approach with particular attention to the solution cost. The board
technology used is the standard thru-hole, but it can be changed very easily in SMT because most of components are available also in this technology. The circuit has been tested deeply in all the most salient
aspects with positive results and it has been integrated with a 22" LCD-TV application without showing
any problem.
Main characteristics
INPUT VOLTAGE:
90 ÷ 265 Vrms - 45-66 Hz
OUTPUT VOLTAGES:
5.1V±2% - @2A Dedicated to panel and digital circuitry for scaling
12V±10% - @4A Dedicated to backlight lamp inverters, audio and SCART
STANDBY
Input power less than 0.8W @230Vac, delivering 30mA on 5.1V
FAULT PROTECTIONS:
Short circuit on each output with auto-restart at short removal, Open loop
Safety&EMC:
Safety: Acc. to EN60950, creepage and clearance minimum distance 6.4mm
EMC: According to EN50022 Class-B
PCB TYPE & SIZE:
Cu Single Side 70 µm, CEM-1, 180 x 89 mm
January 2004
1/17
AN1842 APPLICATION NOTE
Figure 1. Electrical Diagram
2/17
AN1842 APPLICATION NOTE
The converter topology of this SMPS is the standard fly back, working in discontinuous and continuous
current mode. The operating frequency of the circuit (~50 kHz) has been chosen in order to obtain a compromise between the transformer size and the input filter complexity. Hence, the input EMI filter is a simple
Pi-filter, 1-cell only, for differential and common mode noise, using a 4-sectors coil filter. A NTC limits the
inrush current at plug-in. The transformer is a slot type, manufactured by PULSE-ELDOR designed according to the EN60950. Ferrite size is ETD34, the reflected voltage is ~95V providing enough room for
the leakage inductance voltage spike with still margin for reliability.
The reflected voltage, the switching frequency and the primary inductance have been chosen to allow the
continuous current operation of the transformer at full load, all over the input voltage range. This helps to
decrease the output capacitor size thanks to the better ratio between the rms and peak current. The network D10, C14, R5 clamps the peak of the leakage inductance voltage spike ensuring reliable operation
of the PowerMOS, while C21, D11 and R19 limit the dv/dt of the drain voltage.
The PowerMOS is a low cost STP5NK80ZFP, offering a good trade-off between the V(BR)DSS, the RDS(on)
and the equivalent COSS, housed in standard TO-220 or TO-220FP packages. In this design, the TO220FP (TO-220 insulated) has been used, mounted on a heat sink and fixed by a spring. Core of this design is the current mode primary controller, the L5991 integrating all the required blocks to manage the
control and protection of an SMPS. It is available in either DIP-16 (L5991) or in SO-16 (L5991D) packages.
The switching frequency is programmable by means of a an RC network (R11, R12, C15): during normal
operation R11 and R12 are connected in parallel by an internal switch (pin 16); when a light load is detected by the controller this internal switch is opened and the resulting frequency becomes lower, programmed only from C15 and R11.
If the load is further decreased the network D4, D5, R23 provides an additional frequency reduction, proportional to the load, allowing very low power consumption from the mains. Pins 15 and 3 are set in order
to allow the full duty-cycle operation and so the use of most of the energy stored in the bulk capacitor during hold-up operations. Because of the current mode control and the possibility for the duty cycle to exceed
50%, a slope compensation circuitry has been added.
A latched, over voltage protection has been implemented by using the pin 14 and a simple resistor network: in case of loop failure the circuit senses the Vcc and, when the voltage at that pin exceeds the internal threshold, the controller stops the operation until its Vcc drops below the UVLO voltage. The startup is done using a non-dissipative charge pump circuit to save power during standby.
The output rectifiers have been chosen in accordance with the maximum reverse voltage and their power
dissipation. The 5V rectifier is Schottky barrier type STPS5L40, a 5A-40V axial rectifier that thanks to the
low-forward voltage drop is housed in a DO-201 package.
The 12V rectifier is an STPS8H100, an high voltage Schottky rectifier offering a good trade-off between
the forward voltage drop and the maximum operating junction temperature. It is available from STM in 5
different package versions. For this design, the ISOWATT220AC (similar to a standard insulated TO-220)
has been used, mounted on a heat sink and fixed by a spring.
On both outputs, an LC filter has been added in order to filter out the high frequency ripple without increasing the output capacitors size or quality. The output voltage regulation is performed by the secondary feedback monitoring the 5.1V output. The feedback network is the typical one that uses a TL431 driving an
optocoupler, in this case an SFH617A-2, to ensure the required insulation between primary and secondary. The opto-transistor drives directly the COMP pin of the L5991. Here following some waveforms during
the normal operation at full load:
3/17
AN1842 APPLICATION NOTE
Figure 2. Drain voltage & current @115 VAC 60Hz - full load
ing the worst operating condition and they are indicated on the right of figure 5. The margin, with
respect to the maximum voltage withstood by each
diode, ensures safe operating conditions for these
devices.
Figure 4. Drain voltage & current @265 VAC 50Hz - full load
CH1:
CH2:
CH4:
VQ4 - Drain
VPIN8 (Vcc)
VR16 (Drain Current)
Figure 3. Drain voltage & current @230 VAC 50Hz - full load
CH1:
CH2:
CH4:
VQ4 - Drain
VPIN8 (Vcc)
VR16 (Drain Current)
Figure 5. Maximum rectifiers PIV @Vin = 265
VAC - 50 Hz and full load
CH1:
CH2:
CH4:
VQ4 - Drain
VPIN8 (Vcc)
VR16 (Drain Current)
The pictures here above show the drain voltage
and current at the nominal input mains voltage
during normal operation at full load. As visible, the
circuit works in CCM both at nominal high and low
mains.
The figure 4 shows the measurement of the drain
peak voltage at full load and maximum input mains
voltage. The measured voltage of 672V, ensures
a reliable operation of the MOSFET with a good
margin against the maximum BVDSS. Even the
maximum rectifiers PIV have been measured dur-
4/17
CH3:
CH4:
+5V RECTIFIER: Anode voltage
+12V RECTIFIER: Anode voltage
Here following the most salient controller IC signals are shown. In both pictures it is possible to
distinguish clean waveforms free of hard spikes or
noise that could affect the controller correct operation.
AN1842 APPLICATION NOTE
Figure 6. Drain voltage & current @115 VAC 60Hz - full load
CH2:
CH3:
CH4:
VPIN10 (Out)
VPIN6 (Comp)
VPIN2 (RCT)
Figure 7. Drain voltage & current @230 VAC 50Hz - full load
CH2:
CH3:
CH4:
VPIN10 (Out)
VPIN6 (Comp)
VPIN2 (RCT)
Cross regulation
In the following tables it has been reported the output voltage cross regulation measurements with static
loads. The overall efficiency of the converter is also calculated at the nominal input voltages.
To check the application circuit it has been tested keeping constant the current on the 5V and varying the
12V load. As visible in both tables, the voltages are within their tolerance at any load condition and the
circuit efficiency is good
.
5V ± 2%
12V ± 10%
115 Vac
TOLERANCE
PoutTOT
[W]
Pin
[W]
Efficiency
Vaux
[V]
fs
[KHz]
OK
58.65
71.7
81.8%
18.3
51
3
OK
46.90
56.6
82.9%
17.4
51
12.40
2
OK
35.02
42.1
83.2%
16.7
51
2
12.72
1
OK
22.94
27.7
82.8%
16.5
51
5.110
2
13.11
0.5
OK
16.78
20.7
81.0%
16.6
51
5.108
1
11.85
4
OK
52.51
63.9
82.2%
17.5
51
5.108
1
12.00
3
OK
41.11
49.4
83.2%
16.7
51
5.110
1
12.15
2
OK
29.41
35.0
84.0%
16.2
51
5.112
1
12.39
1
OK
17.50
21.0
83.3%
15.9
51
5.112
1
12.66
0.5
OK
11.44
14.0
81.7%
15.9
51
Vout
[V]
@Iout
[A]
Vout
[V]
@Iout
[A]
5.106
2
12.11
4
5.107
2
12.23
5.108
2
5.110
5/17
AN1842 APPLICATION NOTE
5V ± 2%
12V ± 10%
230 Vac
Vout
[V]
@Iout
[A]
Vout
[V]
@Iout
[A]
TOLERANCE
5.106
2
12.09
4
5.107
2
12.23
5.109
2
5.110
PoutTOT
[W]
Pin
[W]
Efficiency
Vaux
[V]
fs
[KHz]
OK
58.57
69.3
84.5%
17.7
51
3
OK
46.90
55.3
84.8%
17.3
51
12.40
2
OK
35.02
41.2
85.0%
16.9
51
2
12.74
1
OK
22.96
27.6
83.2%
16.6
51
5.110
2
13.12
0.5
OK
16.78
20.8
80.7%
16.6
51
5.108
1
11.85
4
OK
52.51
63.9
82.2%
17.5
51
5.108
1
12.00
3
OK
41.11
49.4
83.2%
16.7
51
5.110
1
12.15
2
OK
29.41
35.0
84.0%
16.2
51
5.112
1
12.39
1
OK
17.50
21.0
83.3%
15.9
51
5.112
1
12.66
0.5
OK
11.44
14.0
81.7%
15.9
51
Standby operation
Like in the previous section, the output voltages and the efficiency have been checked, and the input power has been measured. It is clearly visible that with the required standby load (5V@30mA, 12V@0mA)
the input power consumption is well below 800mW at both the input voltage ranges. Besides, the circuit has been characterised at both the nominal input voltage values for different output load and the efficiency is high in all conditions. In the fig. 8, it is shown the output voltage variation as a function of the 5V
current.
During the standby operation the circuit works at reduced frequency, according to load and input voltage
therefore, thanks to this function, the switching losses are minimized. This allows reaching very low standby consumption because in a power switch the switching and the capacitive losses are directly proportional to the working frequency.
5V
115 Vac
Vout [V]
@Iout [mA]
PoutTOT [W]
Pin [W]
Efficiency
5.11
20
0.102
0.433
23.6%
5.11
30
0.153
0.515
29.8%
5.11
40
0.204
0.593
34.5%
5.11
50
0.256
0.667
38.3%
5.11
60
0.307
0.745
41.1%
5.11
80
0.409
0.881
46.4%
100
0.511
1.021
5.11
5V
6/17
50.1%
230Vac
5.11
20
0.102
0.493
20.7%
5.11
30
0.153
0.582
26.3%
5.11
40
0.204
0.672
30.4%
5.11
50
0.256
0.755
33.8%
5.11
60
0.307
0.842
36.4%
5.11
80
0.409
1.008
40.6%
5.11
100
0.511
1.168
43.8%
AN1842 APPLICATION NOTE
Figure 8. INPUT POWER @LOW LOAD
Output voltage ripple @full load
1.200
Figure 11. Output voltage ripple @Vin = 115
Vac - 60 Hz and full load
1.000
Pin @Stand-by
0.800
0.600
Pin @115Vac
0.400
Pin@220Vac
0.200
0.000
20
30
40
50
60
80
100
Iout +5V [mA]
Here following, in figures 9 ad 10 some waveforms
during standby are shown:
Figure 9. Standby @115 VAC - 60Hz 5V @50mA
load
CH3:
CH4:
+5V Output voltage
+12V Output voltage
In figure 11 the output voltage ripples at switching
frequency are measured. As shown, the ripple
and the spikes are very low thanks to the additional LC filters added on both output and avoiding the
use of bigger or expensive output capacitors.
The residual line frequency modulation is very low
at any input voltage.
CH1:
CH2:
CH4:
VQ4 - Drain
VPIN8 (Vcc)
VPIN6 (Comp)
Figure 10. Standby @230 VAC - 50Hz 5V @
50mA load
CH1:
CH2:
CH4:
Dynamic Load Tests
Figure 12 shows the output voltage regulation for
a dynamic load variation of the 5V output. As
shown in the picture the voltage variation and the
response time are very good showing a good loop
behaviour. In fact, the 5V voltage variation is less
than 20mV (0,4%), and the spikes during the load
transition, due to the filter inductor on the output,
are only 75mV beyond the steady state (1,5%).
The measured recovery time is few tens of microseconds. The variations induced on the 12V output have been also checked without showing any
abnormal variation. Besides, the circuit response
has been verified at minimum, nominal and maximum input voltage, showing no significant change.
VQ4 - Drain
VPIN8 (Vcc)
VPIN6 (Comp)
7/17
AN1842 APPLICATION NOTE
Figure 12. +5V Dynamic load 1.5 ÷ 2A, 70Hz
+12V: FULL LOAD - @115 VAC - 60Hz
starts to operate and the output voltages begin to
rise up to the nominal value, where the control
loop provides for the regulation. The wake-up time
at 115Vac is 1.2 s, which is a quite typical time for
this kind of Power Supplies. Besides, on the picture it is clearly visible that no any overshoot, undershoot, dip or lost of control happens during the
power supply start-up phase.
Figure 14. Wake-up time @115 VAC - 60Hz
CH3:
CH4:
+5 Vout
+12 Vout
In Figure 13 it is reported the response of the output voltages for a load variation of the 12V output
as detailed on top of the picture. The measurement has been done varying the 12V load from
50% to 100% load: the voltage variation is around
340mV and the 5V output is almost unaffected.
Therefore, the conclusion is that there is no abnormal behaviour of the SMPS generated by a load
change, allowing a good confidence for the integration of the SMPS in the equipment.
Figure 13. +12V Dynamic load 2 ÷ 4A, 70Hz
+5V: FULL LOAD - @115 VAC - 60Hz
CH3:
CH4:
+5 Vout
+12 Vout
Start-Up Behaviour @full load and Wake-up time
In figure14 the wake-up time is measured at the
lower nominal input mains and the controller startup sequence is shown. The Vcc capacitor is
charged by the charge pump circuit and when its
voltage reaches the start-up threshold the device
8/17
CH1:
CH2:
CH3:
CH4:
VQ4 - Drain
VPIN8 (VCC)
+5 Vout
+12 Vout
Figure 15. Start-Up Behaviours @full load @90 VAC - 60Hz
CH3:
CH4:
+5 Vout
+12 Vout
In the above picture the rising slopes at full load of
the output voltages at minimum input mains voltage are captured and the rise time is measured.
As shown in the pictures, the rising time is monotonic and it is almost constant overall the input
mains range. No any overshoot or abnormal behaviour is present overall the input main range.
AN1842 APPLICATION NOTE
Turn-Off and Hold-up time
In figure 16 the most salient waveforms at turn-off
are shown. Even at turn off the transition is clean,
without abnormal behaviour like restarting attempts or loss of control by the loop. The Hold-up
time, in evidence between the vertical lines, is 13.6
ms at 115Vac-50Hz, full load and becomes around
67ms at 230Vac.
Figure 17. Short circuit on 5V @90 VAC - 60Hz full load
Figure 16. Hold-up @115 VAC -50Hz - full load
CH1:
CH2:
CH4:
VQ4 - Drain
VPIN8 (Vcc)
+5V short circuit current
Figure 18. Short circuit on 5V @265 VAC - 50Hz
- full load
CH1:
CH3:
CH4:
VC13
+12V Vout
+5V Vout
Short-Circuit Tests at Full Load
The short circuit tests have been done under several conditions, all over the input mains range. To
avoid any catastrophic failure of the circuit due to
overstress, a deep check of component stress has
been done. The main circuit parameters that have
been checked are the Mosfet drain voltage and the
mean value of the output current. The drain voltage is an important parameter to be monitored
during short circuits because an excessive increase due to the transformer leakage inductance
and the overcurrent flowing in the primary can
cause the MOSFET BVDSS to be exceeded. In the
proposed circuit, thanks to the low leakage inductance of the transformer and to the start-up component correct dimensioning, in case any output is
shorted, the MOSFET drain voltage is below its
BVDSS and the mean value of the output current is
low too, thus preventing component overheating
because of the excessive power dissipation. In this
case the reliability against long term-shorts is not
affected even at 264Vrms. The auto-restart at
short removal has been also checked and it is correct in all conditions.
CH1:
CH2:
CH4:
VQ4 - Drain
VPIN8 (Vcc)
+5V short circuit current
As clearly indicated by the waveforms in figure 17
and 18, the circuit works in hiccup mode, keeping
the mean value of the current at levels compatible
with the component rating. As visible the circuit
working time is constant because it depends only
on the auxiliary capacitor value, while the dead
time is inversely proportional to the input mains
voltage. In the following figures 19 and 20 the
waveforms relevant to the 12V output in short circuit at both the nominal input mains voltage are reported: as visible, the circuit protects itself and the
load.
9/17
AN1842 APPLICATION NOTE
Figure 19. Short circuit on 12V @90 VAC - 60Hz
- full load
tions of the equipment, with a consumption halved
with respect to the maximum output power levels
(I+12V = 2A, I+5V = 1A).
– At Vin = 90Vac: shorting each output the over
current protection works correctly, providing for
the hiccup mode.
– At Vin = 265Vac: the circuit behaves correctly.
Figure 21. Short circuit on 5V @265 VAC - 50Hz
- half load
CH1:
CH2:
CH4:
VQ4 - Drain
VPIN8 (Vcc)
+12V short circuit current
Figure 20. Short circuit on 12V @265 VAC - 50Hz
- full load
CH1:
CH2:
CH4:
CH1:
CH2:
CH4:
VQ4 - Drain
VPIN8 (Vcc)
+12V short circuit current
VQ4 - Drain
VPIN8 (Vcc)
+5V short circuit current
@Reduced Load
This condition simulates a fault during an operating transition of the equipment, with the backlight
off and a reduced consumption of the other output
(I+12V = 0A, I+5V = 0.5A).
– At Vin = 90Vac: shorting each output the over
current protection works correctly, providing for
the hiccup working mode.
– At Vin = 265Vac: the behaviour of the circuit is
correct like at 90Vac.
–
Short Circuit Protection @ Low Load
After the full load tests, some checks on the short
circuit protection with reduced loads have been
done, as reported here following. The tests have
been done even at minimum and maximum input
voltage with the same results, as the previous
tests.
@Half Load
The waveforms of figure 21 are relevant to a short
circuit test simulating a fault during normal opera-
10/17
@Standby
This condition simulates a fault during the standby
operation of the equipment, with the backlight and
the scaler off, and the µP working with a reduced
consumption (I+12V = 0A, I+5V = 33mA).
– At Vin = 90Vac: shorting each output the overcurrent protection works correctly, providing for
the hiccup working mode.
– At Vin = 265Vac: the behaviour of the circuit is
correct like at 115Vac.
AN1842 APPLICATION NOTE
Figure 22. Short circuit on 5V @265 VAC - 50Hz
- standby load
CH1:
CH2:
CH4:
VQ4 - Drain
VPIN8 (Vcc)
+5V current in short circuit
Figure 23. Short circuit on 12V @265 VAC 50Hz - standby load
turn-off, preventing the hiccup mode. To avoid
this, the circuit around Q2 and Q3 has been added, providing the hiccup mode anyway. As visible
in the pictures, the SMPS is always protected even
in this very critical load condition.
Over Voltage Protection
The open-loop operation is a very dangerous
event that could happen in case of a feedback circuitry failure. In this case, the SMPS output voltages can increase up to dangerous
values,
depending on the load by each output and the
transformer coupling between the windings. Thus,
if the circuit is not properly protected, the rectifiers
and the output capacitors can be overstressed and
be destroyed or even worse, to catch light. To
avoid this, the safety rules ask that the SMPS have
a protection against the mentioned safety risks. In
the proposed circuit, in case of a control loop failure, a L5991 internal comparator stops the controller operation when the voltage at pin 14 (DIS)
reaches 2.5V and remains latched until the Vcc
voltage decreases below the UVLO threshold. So,
a very safe protection with the L5991 is realized
just by means of few passive components.
The circuit has been tested opening the loop, the
output voltages have been measured giving the
following results overall the mains input voltage
range:
230Vac – 50Hz
@FULL LOAD
230Vac – 50Hz
@STANDBY
5V @ 2A
12V @ 4A
5V @ 0.03A
12V @0A
V5V: 5.7V
V12V: 13.5V
V5V: 6.24V
V12V: 15.8V
As shown in the table, in both conditions the measured voltages are not critical for the circuitry.
CH1:
CH2:
CH4:
VQ4 - Drain
VPIN8 (Vcc)
+5V current in short circuit
The main circuit parameter measurements have
been done also during the test at reduced load or
standby. In detail, during standby short it is possible to check the perfect functionality of the protection. This load condition in fact, is critical because
all the power available from the converter can be
delivered to one output only, because the others
are lightly loaded or unloaded, and this can bring
to the destruction of the rectifier of the shorted output. Besides, during standby operation, the transformer coupling and the leakage inductance may
be capable of supplying the controller charging the
VDD capacitor by the spikes generated at Mosfet
Conducted Noise Measurements (Pre-Compliance Test)
The following pictures are the peak conducted
noise measurements at full load and nominal
mains voltages. The limits shown on the diagrams
are those specified by the EN55022 CLASS-B,
which is the most widely used for Information
Technology Equipment intended for domestic use,
in the bandwidth 150KHz 30MHz. The filter configuration used is the 2-wires one, without the ground
connection at mains plug, suitable for domestic
equipment like LCD-TVs. As visible on the diagrams, there is a good margin between the peak
measures with respect to the AVG limits (lower
ones), and this assures that the QP and Average
measures will be within their respective limits.
11/17
AN1842 APPLICATION NOTE
Figure 24. EN55022 Class-B Peak Measure
@115 VAC - 60Hz - FULL LOAD
Figure 25. EN55022 Class-B Peak Measure 230
VAC - 50Hz - FULL LOAD
Thermal measures
In order to check the reliability of the design a thermal mapping by means of an IR camera has been done.
In the table here below the temperature of some salient components is reported at 115Vac and 230Vac
input voltage, at ambient temperature (24°C).
@115Vac
@230Vac
Point
Reference
Description
Temperature
Temperature
A
D9
BRIDGE RECTIFIER
74°C
54°C
B
L2
FILTER COIL
56°C
40°C
C
Q4
POWERMOS
70°C
58°C
D
T1
POWER TRANSF.
53°C
56°C
E
D16
+5V RECTIFIER
61°C
60°C
F
D13
+12V RECTIFIER
64°C
64°C
As visible in the above table there are not component working at a temperature level that can be considered critical for their reliability.
12/17
AN1842 APPLICATION NOTE
Board lay-out
Figure 26. Board silk-screen and bottom plane (not in scale)
■
Original size: 89x180mm
■
Copper thickness: 70µm
■
Material: CEM-1
Conclusions
An SMPS for LCD monitors or LCD-TV sets has been completely designed, assembled and tested using
the L5991. All the different aspects (Component Electrical Stress, Functions, Protections, Conducted
EMI, Thermal Stress) have been checked, giving positive results. The design meets also low-cost and lowcomplexity requirements, key factors in the Consumer Electronic market.
13/17
AN1842 APPLICATION NOTE
References
[1] "L5991 Data Sheet"
[2] "AN1537: A simple trick enhances L5991's standby function"
ANNEX1: Transformer spec
Transformer General Description
APPLICATION TYPE:
TRANSFORMER TYPE:
WINDING TYPE
COIL FORMER:
Consumer, Home Appliance
Open, Varnished only
Slot
Vertical type, 7+7 pins
MAX. TEMP. RISE:
45°C
MAX. OPERATING AMB. TEMP. : 60°C
MAINS INSULATION:
ACC. WITH EN60065 - EN60950
Electrical Characteristics
CORE TYPE/GRADE:
ETD34 - 3C90 or equivalent
PRIMARY INDUCTANCE:
825 µH ±10% @1KHz - 0.25V
LEAKAGE INDUCTANCE:
15 µH MAX @ 10KHz - 0.25V
PEAK PRIMARY CURRENT:
2 Apk
[1]: Measured between pins 3-7 with all secondary shorted
PROVIDED BY PULSE-ELDOR
[1]
P/N: 2074.5056C
Figure 27. Electrical Diagram
3
12
PRIM.
7
11
AUX
13
PRIMARY
14/17
PINS:
DC OUTPUT
VOLTAGE:
RMS
CURRENT:
NUMBER OF
TURNS:
7-3
PRIMARY
0.84 ARMS
53
2/4-6/8
5V
2.6 ARMS
3
12-10
12V
5.3 ARMS
7
11-13
15V (AUX)
0.05 ARMS
9
10
2+5V
6-
SECONDARY
AN1842 APPLICATION NOTE
ANNEX2:
Part List
Designator
C1
Part Type/
Part Value
Description
Supplier
RES
NOT MOUNTED
C10
220N - 50V
CERCAP
AVX
C101 (D17)
47N-400V
POLIESTER FILM CAP MKT
R66 - ARCOTRONICS
C102
220P - 50V
CERCAP
AVX
C11
100N - 50V
CERCAP
AVX
C12
220N - 50V
CERCAP
AVX
C13
100uF-400V
ALUMINIUM ELCAP
LP4 SERIES - ELNA
C14
2N2-1KV HR
HV CERCAP
DEHR33A222K - MURATA
C15
4N7 - 50V
CERCAP
AVX
C16
4N7 - 50V
CERCAP
AVX
C17
4N7 - 50V
CERCAP
AVX
C18
330P - 50V
CERCAP
AVX
C19
22uF-25V
ALUMINIUM ELCAP
RUBYCON
C2
RES
NOT MOUNTED
C20
22uF-25V
ALUMINIUM ELCAP
RUBYCON
C21
220PF-2KV HR
HV CERCAP
DEHR33A221K - MURATA
C22
1N0 - Y1
Y1 SAFETY CAP.
DE1E3KX102M - MURATA
C23
1N0 - Y1
Y1 SAFETY CAP.
DE1E3KX102M - MURATA
C24
2200uF-16V YXF
ALUMINIUM ELCAP
RUBYCON
C25
1000uF-35V YXF
ALUMINIUM ELCAP
RUBYCON
C26
1000uF-35V YXF
ALUMINIUM ELCAP
RUBYCON
C27
470uF-10V YXF
ALUMINIUM ELCAP
RUBYCON
C28
100uF-50V YXF
ALUMINIUM ELCAP
RUBYCON
C29
22N - 50V
CERCAP
AVX
C3
RES
NOT MOUNTED
C30
N68 - 50V
CERCAP
AVX
C31
3N3 - 50V
CERCAP
AVX
C32
47uF-25V YXF
ALUMINIUM ELCAP
RUBYCON
C33
10N - 50V
CERCAP
AVX
C4
RES
NOT MOUNTED
C5
RES
NOT MOUNTED
C6
RES
NOT MOUNTED
C7
470PF - 50V
CERCAP
AVX
C8
220N-X2
X2 FILM CAPACITOR
R46-KI 3220 00 L2M - ARCOTRONICS
C9
220N-X2
X2 FILM CAPACITOR
R46-KI 3220 00 L2M - ARCOTRONICS
D10
STTH1L06
FAST REC. RECTIFIER
STMicroelectronics
D101
1N4148
GEN. PURPOSE DIODE
WISHAY
D102 (R13)
1N4148
GEN. PURPOSE DIODE
WISHAY
D11
STTH1L06
FAST REC. RECTIFIER
STMicroelectronics
D12
RES
NOT MOUNTED
D13
STPS8H100CF
POWER SCHOTTKY RECT.
STMicroelectronics
D14
1N4007
RECTIFIER DIODE
WISHAY
15/17
AN1842 APPLICATION NOTE
Part List (continued)
Designator
Part Type/
Part Value
Description
D15
1N4007
RECTIFIER DIODE
Supplier
WISHAY
D16
STPS5L40
POWER SCHOTTKY RECT.
STMicroelectronics
D2
1N4148
GEN. PURPOSE DIODE
WISHAY
D3
BAV21
GEN. PURPOSE DIODE
WISHAY
D4
1N4148
GEN. PURPOSE DIODE
WISHAY
D5
1N4148
GEN. PURPOSE DIODE
WISHAY
D6
BAV21
GEN. PURPOSE DIODE
WISHAY
D7
1N4148
GEN. PURPOSE DIODE
WISHAY
D8
1N4148
GEN. PURPOSE DIODE
WISHAY
D9
2KBP06M
BRIDGE RECTIFIER
WISHAY
F1
FUSE T2A
FUSE 2 AMP. TIME DELAY
WICKMANN
J1
INPUT CONNECTOR, 2/3 POLES, 7.5MM
MOLEX
J2
OUTPUT CONNECTOR, 9 POLES, 2.54MM
MOLEX
JP1
JUMPER
WIRE JUMPER
JP2
RES
NOT MOUNTED
L1
RES
NOT MOUNTED
L2
253Y1R2
25mH-1.2A - CM FILTER INDUCTOR
L3
2uH-4A
2uH-4A AXIAL FILTER INDUCTOR
B82111 SERIES - EPCOS
L4
10uH
RF AXIAL CHOKE
B78108-S1103-K - EPCOS
L5
2.7uH
DRUM COIL 2.7uH-4A
ELC08D SERIES - PANASONIC
Q1
BC547A
SMALL SIGNAL NPN BJT
STMicroelectronics
Q2
BC547A
SMALL SIGNAL NPN BJT
STMicroelectronics
Q3
BC547A
SMALL SIGNAL NPN BJT
STMicroelectronics
Q4
STP5NK80ZFP
POWER MOSFET
STMicroelectronics
R1
RES
NOT MOUNTED
R10
4K7 - 1/4W - 5%
STANDARD FILM RESISTOR
TDK
BEYSCHLAG
R101 (D1)
100R - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R11
10K - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R12
12K - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R14
1K0 - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R15
47R - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R16
1R2 - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R17
1R2 - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R18
1R2 - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R19
4K7 - 2W - 5%
POWER RESISTOR 2W
BEYSCHLAG
R2
NTC_10R S236
NTC THERMISTOR
EPCOS
R20
RES
NOT MOUNTED
R21
8K2 - 1/4W - 5%
STANDARD FILM RESISTOR
R22
3K9 - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R23
6K2 - 1/4W - 1%
METAL FILM RESISTOR
BEYSCHLAG
BEYSCHLAG
R24
2K0 - 1/4W - 1%
METAL FILM RESISTOR
BEYSCHLAG
R25
12K - 1/4W - 1%
METAL FILM RESISTOR
BEYSCHLAG
R26
1K5 - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
16/17
AN1842 APPLICATION NOTE
Part List (continued)
Designator
Part Type/
Part Value
Description
Supplier
R27
10R - 1/4W - 5%
STANDARD FILM RESISTOR
R28
82K - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R29
2K43 - 1/4W - 1%
METAL FILM RESISTOR
BEYSCHLAG
R3
470K - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R30
2K43 - 1/4W - 1%
METAL FILM RESISTOR
BEYSCHLAG
R31
1K0 - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R32
47K - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R33
12K - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R34
3K3 - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R35
10K - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R4
470K - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R5
150K - 2W - 5%
POWER RESISTOR 2W
BEYSCHLAG
R6
33R - 1/4W - 5%
STANDARD FILM RESISTOR
BEYSCHLAG
R7
RES
NOT MOUNTED
R8
RES
NOT MOUNTED
R9
RES
NOT MOUNTED
T1
2074.5056C
POWER TRANSFORMER
U1
L5991
PRIMARY CONTROLLER WITH STANDBY STMicroelectronics
U2
SFH617A-2
OPTOCOUPLER
INFINEON
TL431ACZ
SHUNT REGULATOR
STMicroelectronics
U3
BEYSCHLAG
PULSE-ELDOR
HEAT SINK FOR Q4 Rth HS-AMB = 15°C/W
P/N 6098B THERMALLOY WITH
CLAMP
HEAT SINK FOR D13 Rth HS-AMB = 10°C/W
P/N 6099B THERMALLOY WITH
CLAMP
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences
of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted
by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are subject
to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products are not
authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics.
The ST logo is a registered trademark of STMicroelectronics.
All other names are the property of their respective owners
© 2004 STMicroelectronics - All rights reserved
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