TI OPA4354-Q1 Opax354-q1 250-mhz, rail-to-rail i/o, cmos operational amplifier Datasheet

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OPA354-Q1, OPA2354-Q1, OPA4354-Q1
SBOS492B – JUNE 2009 – REVISED DECEMBER 2014
OPAx354-Q1 250-MHz, Rail-to-Rail I/O, CMOS Operational Amplifiers
1 Features
3 Description
•
•
The design of the OPAx354-Q1 family of high-speed,
voltage-feedback CMOS operational amplifiers is for
video and other applications requiring wide
bandwidth. These devices are unity-gain stable and
can drive large output currents. Differential gain is
0.02% and differential phase is 0.09°. Quiescent
current is only 4.9 mA per channel.
1
•
•
•
•
•
•
•
•
•
•
•
Qualified for Automotive Applications
AEC-Q100 Qualified With the Following Results:
– Device Temperature Grade : –40°C to 125°C
Ambient Operating Temperature Range
– Device HBM ESD Classification Level 2
– Device CDM ESD Classification Level C3
Unity-Gain Bandwidth: 250 MHz
Wide Bandwidth: 100-MHz GBW
High Slew Rate: 150 V/μs
Low Noise: 6.5 nV/√Hz
Rail-to-Rail I/O
High Output Current: >100 mA
Excellent Video Performance
– Differential Gain Error: 0.02%
– Differential Phase Error: 0.09°
– 0.1-dB Gain Flatness: 40 MHz
Low Input Bias Current: 3 pA
Quiescent Current: 4.9 mA
Thermal Shutdown
Supply Range: 2.5 V to 5.5 V
2 Applications
•
•
•
•
•
•
•
•
•
•
Video Processing
Ultrasound
Optical Networking, Tunable Lasers
Photodiode Transimpedance Amplifiers
Active Filters
High-Speed Integrators
Analog-to-Digital Converter (ADC) Input Buffers
Digital-to-Analog Converter (DAC) Output
Amplifiers
Barcode Scanners
Communications
The OPAx354-Q1 family of operational amplifiers (opamps) are optimized for operation on single or dual
supplies as low as 2.5 V (±1.25 V) and up to 5.5 V
(±2.75 V). Common-mode input range extends
beyond the supplies. The output swing is within 100
mV of the rails, supporting wide dynamic range.
The single-supply version (OPA354-Q1) is available
in the tiny SOT23-5 (DBV) package. The dual-supply
version (OPA2354-Q1) is available in the miniature
VSSOP-8 (DGK) package and features completely
independent circuitry for lowest crosstalk and
freedom from interaction. The quad-supply version
(OPA4354-Q1) is available in the SOP-14 (PW)
package. The device specifications are for operation
over the automotive temperature range of –40°C to
125°C.
Device Information(1)
PART NUMBER
PACKAGE (PIN)
BODY SIZE (NOM)
OPA354-Q1
SOT-23 (5)
2.90 mm × 1.60 mm
OPA2354-Q1
VSSOP (8)
3.00 mm × 3.00 mm
OPA4354-Q1
TSSOP (14)
5.00 mm × 4.40 mm
(1) For all available packages, see the orderable addendum at
the end of the datasheet.
V+
-In
OPA354-Q1
VOUT
+In
V-
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
OPA354-Q1, OPA2354-Q1, OPA4354-Q1
SBOS492B – JUNE 2009 – REVISED DECEMBER 2014
www.ti.com
Table of Contents
1
2
3
4
5
6
7
Features ..................................................................
Applications ...........................................................
Description .............................................................
Revision History.....................................................
Pin Configuration and Functions .........................
Specifications.........................................................
1
1
1
2
3
4
6.1
6.2
6.3
6.4
6.5
6.6
4
4
4
4
5
6
Absolute Maximum Ratings ......................................
ESD Ratings..............................................................
Recommended Operating Conditions.......................
Thermal Information .................................................
Electrical Characteristics...........................................
Typical Characteristics ..............................................
Detailed Description ............................................ 12
7.1 Overview ................................................................. 12
7.2 Functional Block Diagram ....................................... 12
7.3 Feature Description................................................. 12
7.4 Device Functional Modes........................................ 17
8
Application and Implementation ........................ 18
8.1 Application Information............................................ 18
8.2 Typical Applications ................................................ 18
9
Power Supply Recommendations...................... 22
9.1 Power Dissipation ................................................... 23
10 Layout................................................................... 23
10.1 Layout Guidelines ................................................. 23
10.2 Layout Example .................................................... 24
11 Device and Documentation Support ................. 25
11.1
11.2
11.3
11.4
11.5
Documentation Support .......................................
Related Links ........................................................
Trademarks ...........................................................
Electrostatic Discharge Caution ............................
Glossary ................................................................
25
25
25
25
25
12 Mechanical, Packaging, and Orderable
Information ........................................................... 25
4 Revision History
Changes from Revision A (August 2009) to Revision B
Page
•
Added Handling Rating table, Feature Description section, Device Functional Modes, Application and
Implementation section, Power Supply Recommendations section, Layout section, Device and Documentation
Support section, and Mechanical, Packaging, and Orderable Information section................................................................ 1
•
Added the OPA4354-Q1 device to the data sheet ................................................................................................................ 1
2
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SBOS492B – JUNE 2009 – REVISED DECEMBER 2014
5 Pin Configuration and Functions
DBV Package
5-Pin SOT-23
OPA354-Q1 Top View
Out 1
DGK Package
8-Pin VSSOP
OPA2354-Q1 Top View
5 V+
Out A 1
V± 2
±In A 2
+
+In 3
8 V+
7 Out B
A
4 ±In
+In A 3
+
6 ±In B
B
+
V± 4
5 +In B
PW Package
14-Pin TSSOP
Top View
Out A 1
14 Out D
±In A 2
±
+In A 3
+
A
D
±
13 ±In D
+
12 +In D
V+ 4
11 V±
+In B 5
10 +In C
B
±In B 6
C
±
±
Out B 7
9 ±In C
8 Out C
Pin Functions
PIN
NO.
NAME
OPA354Q1
SOT-23
I/O
DESCRIPTION
OPA2354-Q1 OPA4354-Q1
VSSOP
TSSOP
+In
3
—
—
I
Noninverting input
–In
4
—
—
I
Inverting input
+In A
—
3
3
I
Noninverting input, Channel A
–In A
—
2
2
I
Inverting input, Channel A
+In B
—
5
5
I
Noninverting input, Channel B
–In B
—
6
6
I
Inverting input, Channel B
+In C
—
—
10
I
Noninverting input, Channel C
–In C
—
—
9
I
Inverting input, Channel C
+In D
—
—
12
I
Noninverting input, Channel D
–In D
—
—
13
I
Inverting input, Channel D
Out
1
—
—
O
Output
Out A
—
1
1
O
Output, Channel A
Out B
—
7
7
O
Output, Channel B
Out C
—
—
8
O
Output, Channel C
Out D
—
—
14
O
Output, Channel D
V+
5
8
4
—
Positive (highest) supply
V–
2
4
11
—
Negative (lowest) supply
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SBOS492B – JUNE 2009 – REVISED DECEMBER 2014
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6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)
(1)
MIN
MAX
UNIT
7.5
V
(V+) + 0.5
V
Supply voltage, V+ to V–, VS
Signal input terminals voltage
(2)
, VIN
(V–) – 0.5
Output short-circuit duration (3)
Continuous
Operating temperature, TA
–55
Junction temperature, TJ
Storage temperature, Tstg
(1)
(2)
(3)
–65
150
°C
150
°C
150
°C
Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
Input terminals are diode-clamped to the power-supply rails. Input signals that can swing more than 0.5 V beyond the supply rails should
be current limited to 10 mA or less.
Short circuit to ground, one amplifier per package
6.2 ESD Ratings
VALUE
V(ESD)
(1)
Human body model (HBM), per AEC Q100-002
Electrostatic discharge
(1)
±2000
Charged device model (CDM), per AEC Q100-011
UNIT
V
±250
AEC Q100-002 indicates HBM stressing is done in accordance with the ANSI/ESDA/JEDEC JS-001 specification.
6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted)
MIN
MAX
VS
Supply voltage, V– to V+
2.5
5.5
UNIT
V
TA
Operating free-air temperature
–40
125
°C
6.4 Thermal Information
THERMAL METRIC (1)
OPA354-Q1
OPA2354-Q1
OPA4354-Q1
DBV (5 Pins)
DGK (8 Pins)
PW (14 Pins)
RθJA
Junction-to-ambient thermal resistance
216.3
175.9
92.6
RθJC(top)
Junction-to-case (top) thermal resistance
84.3
67.8
27.5
RθJB
Junction-to-board thermal resistance
43.1
97.1
33.6
ψJT
Junction-to-top characterization parameter
3.8
9.3
1.9
ψJB
Junction-to-board characterization parameter
42.3
95.5
33.1
RθJC(bot)
Junction-to-case (bottom) thermal resistance
N/A
N/A
N/A
(1)
4
UNIT
°C/W
For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.
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SBOS492B – JUNE 2009 – REVISED DECEMBER 2014
6.5 Electrical Characteristics
VS = 2.5 V to 5.5 V, RF (feedback resistor) = 0 Ω, RL (load resistor) = 1 kΩ connected to VS / 2 (unless otherwise noted)
PARAMETER
TEST CONDITIONS
VS = 5 V, VCM = (V–) + 0.8 V
TA (1)
MIN
25°C
TYP
MAX
±2
±8
UNIT
VOS
Input offset voltage
ΔVOS / ΔT
Offset voltage drift over
temperature
PSRR
Offset voltage drift vs power
supply
IB
Input bias current
25°C
3
±50
IOS
Input offset current
25°C
±1
±50
Vn
Input voltage noise density
f = 1 MHz
25°C
6.5
nV/√Hz
In
Input current noise density
f = 1 MHz
25°C
50
fA/√Hz
VCM
Input common-mode voltage
range
CMRR
Input common-mode rejection
ratio
Full range
Full range
VS = 2.7 V to 5.5 V,
VCM = VS / 2 – 0.15 V
VS = 5.5 V, –0.1 V < VCM < 3.5 V
VS = 5.5 V, –0.1 V < VCM < 5.6 V
mV
±10
μV/°C
±4
25°C
±200
Full range
±800
±900
25°C
(V–) – 0.1
25°C
66
Full range
64
25°C
56
Full range
55
μV/V
pA
pA
(V+) + 0.1
V
80
dB
68
ZID
Differential input impedance
25°C
1013 || 2
Ω || pF
ZICM
Common-mode input impedance
25°C
1013 || 2
Ω || pF
VS = 5 V, 0.3 V < VO < 4.7 V
25°C
94
VS = 5 V, 0.4 V < VO < 4.6 V
Full range
90
110
AOL
Open-loop gain
f–3dB
Small-signal bandwidth
GBW
Gain-bandwidth product
G = 10
25°C
100
MHz
f0.1dB
Bandwidth for 0.1-dB gain
flatness
G = 2, VO = 100 mVp-p
25°C
40
MHz
VS = 5 V, G = 1, 4-V step
25°C
150
SR
Slew rate
trf
Rise-and-fall time
tsettle
Settling time
(1)
G = 1, VO = 100 mVp-p, RF = 25 Ω
G = 2, VO = 100 mVp-p
90
VS = 5 V, G = 1, 2-V step
130
VS = 3 V, G = 1, 2-V step
110
G = 1, VO = 200 mVp-p, 10% to 90%
G = 1, VO = 2 Vp-p, 10% to 90%
0.1%
250
25°C
2
25°C
11
30
dB
MHz
V/μs
ns
VS = 5 V, G = +1, 2-V output step
25°C
Overload recovery time
VIN × Gain = VS
25°C
5
Second-order harmonic
distortion
G = 1, f = 1 MHz, VO = 2 Vp-p,
RL = 200 Ω, VCM = 1.5 V
25°C
–75
dBc
Third-order harmonic distortion
G = 1, f = 1 MHz, VO = 2 Vp-p,
RL = 200 Ω, VCM = 1.5 V
25°C
–83
dBc
Differential gain error
NTSC, RL = 150 Ω
25°C
0.02%
Differential phase error
NTSC, RL = 150 Ω
25°C
0.09
0.01%
60
ns
ns
°
Full range TA = –40°C to 125°C
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Electrical Characteristics (continued)
VS = 2.5 V to 5.5 V, RF (feedback resistor) = 0 Ω, RL (load resistor) = 1 kΩ connected to VS / 2 (unless otherwise noted)
PARAMETER
Channel-to-channel crosstalk
(OPA2354-Q1) (OPA4354-Q1)
Voltage output swing from rail
VS = 5 V, RL = 1 kΩ, AOL > 94 dB
25°C
0.1
VS = 5 V, RL = 1 kΩ, AOL > 90 dB
Full range
MAX
0.3
100
Ω
0.05
Ω
35
Quiescent current
(per amplifier)
VS = 5 V, IO = 0, enabled
4.9
6
Full range
7.5
Shutdown
160
Reset from shutdown
140
V
mA
50
25°C
UNIT
dB
0.4
f < 100 kHz
Thermal shutdown junction
temperature
(2)
(3)
–100
Open-loop output resistance
IQ
TYP
25°C
VS = 3 V
Closed-loop output impedance
RO
f = 5 MHz
MIN
VS = 5 V
Output current (2) (3)
IO
TA (1)
TEST CONDITIONS
mA
°C
See typical characteristic graph Output Voltage Swing vs Output Current.
Not production tested
6.6 Typical Characteristics
TA = 25°C, VS = 5 V, RF = 0 Ω, RL = 1 kΩ connected to VS / 2 (unless otherwise noted)
3
3
G = 1,
RF = 25W
VO = 0.1VPP
-3
G = +2, RF = 604W
G = +5, RF = 604W
-6
G = +10, RF = 604W
-9
-12
-15
100k
VO = 0.1VPP, RF = 604W
0
Normalized Gain (dB)
Normalized Gain (dB)
0
-3
G = -1
-6
G = -5
G = -10
-12
1M
10M
Frequency (Hz)
100M
1G
-15
100k
1M
10M
Frequency (Hz)
100M
1G
Figure 2. Inverting Small-Signal Frequency Response
Output Voltage (40mV/div)
Output Voltage (500mV/div)
Figure 1. Noninverting Small-Signal Frequency Response
Time (20ns/div)
Figure 3. Noninverting Small-Signal Step Response
6
G = -2
-9
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Time (20ns/div)
Figure 4. Noninverting Large-Signal Step Response
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SBOS492B – JUNE 2009 – REVISED DECEMBER 2014
Typical Characteristics (continued)
TA = 25°C, VS = 5 V, RF = 0 Ω, RL = 1 kΩ connected to VS / 2 (unless otherwise noted)
0.5
Harmonic Distortion (dBc)
Normalized Gain (dB)
-50
VO = 0.1VPP
0.4
0.3
G = +1
RF = 25W
0.2
0.1
0
-0.1
-0.2
G = +2
RF = 604W
-0.3
G = -1
f = 1MHz
RL = 200W
-60
-70
2nd−Harmonic
-80
-90
-0.4
3rd−Harmonic
-100
-0.5
100k
1M
10M
Frequency (Hz)
100M
0
1G
Figure 5. 0.1-dB Gain Flatness
2
Output Voltage (VPP)
3
4
Figure 6. Harmonic Distortion vs Output Voltage
-50
-50
VO = 2VPP
f = 1MHz
RL = 200W
-60
Harmonic Distortion (dBc)
Harmonic Distortion (dBc)
1
-70
2nd−Harmonic
-80
-90
VO = 2VPP
f = 1MHz
RL = 200W
-60
-70
2nd−Harmonic
-80
3rd−Harmonic
-90
3rd−Harmonic
-100
-100
1
10
1
10
Gain (V/V)
Gain (V/V)
Figure 7. Harmonic Distortion vs Noninverting Gain
Figure 8. Harmonic Distortion vs Inverting Gain
-50
-60
G = +1
VO = 2VPP
RL = 200W
VCM = 1.5V
Harmonic Distortion (dBc)
Harmonic Distortion (dBc)
-50
-70
2nd−Harmonic
-80
3rd−Harmonic
-90
-100
100k
G = +1
VO = 2VPP
f = 1MHz
VCM = 1.5V
-60
-70
2nd−Harmonic
-80
3rd−Harmonic
-90
-100
1M
Frequency (Hz)
Figure 9. Harmonic Distortion vs Frequency
Copyright © 2009–2014, Texas Instruments Incorporated
10M
100
1k
RL (W)
Figure 10. Harmonic Distortion vs Load Resistance
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Typical Characteristics (continued)
TA = 25°C, VS = 5 V, RF = 0 Ω, RL = 1 kΩ connected to VS / 2 (unless otherwise noted)
3
10k
RL = 10kW
Normalized Gain (dB)
Voltage Noise (nV/√Hz),
Current Noise (fA/√Hz)
0
1k
Current Noise
Voltage Noise
100
10
G = +1
R F = 0W
VO = 0.1VPP
C L = 0pF
-3
-6
RL = 1kW
RL = 100W
-9
RL = 50W
-12
1
10
100
1k
10k
100k
1M
10M
-15
100k
100M
1M
10M
Frequency (Hz)
Frequency (Hz)
Figure 11. Input Voltage and Current Noise
Spectral Density vs Frequency
9
Normalized Gain (dB)
6
3
Figure 12. Frequency Response for Various RL
G = +1
VO = 0.1VPP
R S = 0W
120
100
RS (W)
-3
CL = 47pF
80
-6
60
-9
40
VIN
RS
VO
OPA354-Q1
CL = 5.6pF
CL
1kW
20
0
-15
100k
1M
10M
Frequency (Hz)
100M
1
1G
Figure 13. Frequency Response for Various CL
3
1k
10
100
Capacitive Load (pF)
Figure 14. Recommended RS vs Capacitive Load
100
G = +1
VO = 0.1VPP
CL = 5.6pF, RS = 0W
CMRR
80
CL = 47pF, RS = 140W
-3
CL = 100pF, RS = 120W
-6
-9
VIN
RS
VO
OPA354-Q1
CL
-12
-15
100k
CMRR, PSRR (dB)
Normalized Gain (dB)
For 0.1dB
Flatness
140
CL = 100pF
-12
PSRR+
60
PSRR40
20
1kW
0
1M
10M
Frequency (Hz)
100M
1G
Figure 15. Frequency Response vs Capacitive Load
8
1G
160
0
0
100M
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10k
100k
1M
10M
Frequency (Hz)
100M
1G
Figure 16. Common-Mode Rejection Ratio and PowerSupply Rejection Ratio vs Frequency
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SBOS492B – JUNE 2009 – REVISED DECEMBER 2014
Typical Characteristics (continued)
TA = 25°C, VS = 5 V, RF = 0 Ω, RL = 1 kΩ connected to VS / 2 (unless otherwise noted)
0.8
180
0.7
140
0.6
120
dG/dP (%/degree)
Open−Loop Phase (degrees)
Open−Loop Gain (dB)
160
Phase
100
80
60
40
Gain
20
0.5
dP
0.4
0.3
0.2
0
0.1
dG
-20
0
-40
10
100
1k
10k 100k
1M
Frequency (Hz)
10M
100M
1
1G
3
4
Figure 18. Composite Video Differential Gain and Phase
Figure 17. Open-Loop Gain and Phase
3
10k
1k
Output Voltage (V)
Input Bias Current (pA)
2
Number of 150W Loads
100
2
125°C
25°C
–55°C
1
10
0
1
-55
-35
-15
5
25
45
65
Temperature (°C)
85
0
105 125 135
20
40
60
80
100
120
Output Current (mA)
VS = 3 V
Figure 20. Output Voltage Swing vs Output Current
Figure 19. Input Bias Current vs Temperature
5
7
4
VS = 5V
Output Voltage (V)
Supply Current (mA)
6
5
4
VS = 2.5V
3
2
3
25°C
125°C
-55°C
2
1
1
0
0
-55
-35
-15
5
25
45
65
Temperature (°C)
85
105 125 135
Figure 21. Supply Current vs Temperature
Copyright © 2009–2014, Texas Instruments Incorporated
0
25
50
75
100
125
150
175
200
Output Current (mA)
Figure 22. Output Voltage Swing vs
Output Current for VS = 5 V
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Typical Characteristics (continued)
TA = 25°C, VS = 5 V, RF = 0 Ω, RL = 1 kΩ connected to VS / 2 (unless otherwise noted)
6
100
VS = 5.5V
10
Output Voltage (VPP)
Output Impedance (W)
5
1
0.1
OPA354-Q1
3
VS = 2.7V
2
1
ZO
0
0.01
100k
1M
10M
Frequency (Hz)
100M
1
1G
10
100
Frequency (MHz)
Figure 23. Closed-Loop Output Impedance vs Frequency
Figure 24. Maximum Output Voltage vs Frequency
0.5
120
0.4
RL = 1kW
VO = 2VPP
Open−Loop Gain (dB)
0.3
Output Error (%)
Maximum Output
Voltage Without
Slew−Rate
Induced Distortion
4
0.2
0.1
0
-0.1
-0.2
110
100
90
80
-0.3
-0.4
70
-0.5
0
10
20
30
40
50
60
70
80
90
100
-55
-35
-15
5
Time (ns)
Figure 25. Output Settling Time to 0.1%
25
45
65
Temperature (°C)
85
105 125 135
Figure 26. Open-Loop Gain vs Temperature
100
Population
CMRR, PSRR (dB)
90
Common−Mode Rejection Ratio
80
Power−Supply Rejection Ratio
70
60
50
-8 -7 -6 -5 -4 -3 -2 -1 0 1 2 3
Offset Voltage (mV)
4 5 6
7 8
Figure 27. Offset Voltage Production Distribution
10
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-55
-35
-15
5
25
45
65
85
105 125 135
Temperature (°C)
Figure 28. Common-Mode Rejection Ratio and
Power-Supply Rejection Ratio vs Temperature
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Typical Characteristics (continued)
TA = 25°C, VS = 5 V, RF = 0 Ω, RL = 1 kΩ connected to VS / 2 (unless otherwise noted)
Crosstalk, Input−Referred (dB)
0
-20
-40
-60
OPA2354-Q1
-80
-100
-120
100k
1M
10M
100M
1G
Frequency (Hz)
Figure 29. Channel-to-Channel Crosstalk OPAx354-Q1
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7 Detailed Description
7.1 Overview
The OPAx354-Q1 operational amplifiers are high-speed,150-V/μs, amplifiers making them excellent choices for
transimpedance applications. The devices are unity-gain stable and can operate on a single-supply voltage (2.5
V to 5.5 V), or a split-supply voltage (±1.25 V to ±2.75 V), making them highly versatile and easy to use. The
OPAx354-Q1 amplifiers are specified from 2.5 V to 5.5 V and over the automotive temperature range of –40°C to
125°C.
Table 1. OPAx354-Q1 Related Products
FEATURES
PRODUCT
Shutdown Version of OPA354 Family
OPAx357
200-MHz GBW, Rail-to-Rail Output, CMOS, Shutdown
OPAx355
200-MHz GBW, Rail-to-Rail Output, CMOS
OPAx356
38-MHz GBW, Rail-to-Rail Input/Output, CMOS
OPAx350/3
75-MHz BW, G = 2, Rail-to-Rail Output
OPAx631
150-MHz BW, G = 2, Rail-to-Rail Output
OPAx634
100-MHz BW, Differential Input/Output, 3.3-V Supply
THS412x
7.2 Functional Block Diagram
V+
Reference
Current
VIN−
VIN+
VBIAS1
Class AB
Control
Circuitry
VO
VBIAS2
V−
(Ground)
7.3 Feature Description
7.3.1 Operating Voltage
The specifications of the OPAx354-Q1 family of devices apply over a power-supply range of 2.5 V to 5.5 V
(±1.25 V to ±2.75 V). Supply voltages higher than 7.5 V (absolute maximum) can permanently damage the
amplifier.
The Typical Characteristics section of this data sheet show the parameters that vary over supply voltage or
temperature.
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Feature Description (continued)
7.3.2 Rail-to-Rail Input
The specified input common-mode voltage range of the OPAx354-Q1 family of devices extends 100 mV beyond
the supply rails. A complementary input stage—an N-channel input differential pair in parallel with a P-channel
differential pair—achieves this extension. The N-channel pair is active for input voltages close to the positive rail,
typically (V+) – 1.2 V to 100 mV above the positive supply, while the P-channel pair is on for inputs from 100 mV
below the negative supply to approximately (V+) – 1.2 V. A small transition region exists, typically (V+) – 1.5 V to
(V+) – 0.9 V, in which both pairs are on. This 600-mV transition region can vary ±500 mV with process variation.
Thus, the transition region (both input stages on) can range from (V+) – 2 V to (V+) – 1.5 V on the low end, up to
(V+) – 0.9 V to (V+) – 0.4 V on the high end.
A double-folded cascode adds the signal from the two input pairs and presents a differential signal to the class
AB output stage.
7.3.3 Rail-to-Rail Output
The device uses a class-AB output stage with common-source transistors to achieve rail-to-rail output. For highimpedance loads (> 200 Ω), the output voltage swing is typically 100 mV from the supply rails. With 10-Ω loads,
one can achieve a useful output swing while maintaining high open-loop gain. See Figure 20, Output Voltage
Swing vs Output Current.
7.3.4 Output Drive
The OPAx354-Q1 output stage can supply a continuous output current of ±100 mA and still provide
approximately 2.7-V output swing on a 5-V supply, as shown in Figure 30.
R2
1kW
+
-
C1
50pF
V1
5V
1mF
R1
10kW
V+
OPA354-Q1
+
VIN
R3
10kW
-
1V In = 100mA
Out, as Shown
VRSHUNT
1W
R4
1kW
Laser Diode
Figure 30. Laser Diode Driver
For maximum reliability, TI does not recommend running a continuous dc current in excess of ±100 mA. See
Figure 20, Output Voltage Swing vs Output Current. A solution for supplying continuous output currents greater
than ±100 mA is operating OPAx354-Q1 family of devices in parallel, as shown in Figure 31.
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Feature Description (continued)
R2
10kW
C1
200pF
+5V
1mF
R1
100kW
R5
1W
OPA2354-Q1
R3
100kW
+
-
R6
1W
2V In = 200mA
Out, as Shown
RSHUNT
1W
OPA2354-Q1
R4
10kW
Laser Diode
Figure 31. Parallel Operation
The OPAx354-Q1 family of devices provides peak currents up to 200 mA, which corresponds to the typical shortcircuit current. Therefore, an on-chip thermal shutdown circuit protects the OPAx354-Q1 family of devices from
dangerously high junction temperatures. At 160°C, the protection circuit shuts down the amplifier. Normal
operation resumes when the junction temperature cools below 140°C.
7.3.5 Video
The OPAx354-Q1 output stage is capable of driving standard back-terminated 75-Ω video cables (see
Figure 32). A back-terminated transmission line does not exhibit a capacitive load to its driver. A properly backterminated 75-Ω cable does not appear as capacitance; it presents only a 150-Ω resistive load to the OPAx354Q1 output.
+5V
Video
In
75W
75W
OPA354-Q1
Video
Output
+2.5V
604W
604W
+2.5V
Figure 32. Single-Supply Video Line Driver
A use of the OPAx354-Q1 family of devices is as an amplifier for RGB graphic signals, which have a voltage of
zero at the video black level, by offsetting and ac-coupling the signal (see Figure 33).
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Feature Description (continued)
604W
+3V
+
V+
10nF
604W
75W
1/2
OPA2354-Q1
R1
Red(1)
1mF
Red
75W
R2
V+
R1
Green(1)
R2
75W
1/2
OPA2354-Q1
604W
Green
75W
604W
NOTE: (1) Source video signal offset
300 mV above ground to accomodate
op amp swing−to−ground capability.
604W
+3V
+
V+
Blue(1)
1mF
10nF
604W
75W
R1
Blue
OPA354-Q1
75W
R2
Figure 33. RGB Cable Driver
7.3.6 Driving Analog-to-Digital Converters
The OPAx354-Q1 family of op-amps offers a 60-ns settling time to 0.01%, making the devices a good choice for
driving high- and medium-speed sampling ADCs and reference circuits. The OPAx354-Q1 family of devices
provides an effective means of buffering the input capacitance and resulting charge injection of the ADC while
providing signal gain. The OPAx354-Q1 family of devices is ideal for applications requiring high DC accuracy.
Figure 34 shows the OPAx354-Q1 family of devices driving an ADC. With the OPAx354-Q1 family of devices in
an inverting configuration, use of a capacitor across the feedback resistor can filter high-frequency noise in the
signal.
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Feature Description (continued)
+5V
330pF
5kW
5kW
VIN
VREF
V+
ADS7816, ADS7861,
or ADS7864
12−Bit A/D Converter
+In
OPA354-Q1
+2.5V
-In
GND
VIN = 0V to -5V for 0V to 5V output.
NOTE: A/D Converter Input = 0V to VREF
Figure 34. OPA354-Q1 Inverting Configuration Driving the ADS7816
7.3.7 Capacitive Load and Stability
The OPAx354-Q1 family op-amps can drive a wide range of capacitive loads. However, all op-amps under
certain conditions can become unstable. Op-amp configuration, gain, and load value are just a few of the factors
to consider when determining stability. An op-amp in unity-gain configuration is most susceptible to the effects of
capacitive loading. The capacitive load reacts with the output resistance of the op-amp, along with any additional
load resistance, to create a pole in the small-signal response that degrades the phase margin. For details see
Figure 15, Frequency Response vs Capacitive Load.
The OPAx354-Q1 topology enhances the ability of the device to drive capacitive loads. In unity gain, these opamps perform well with large capacitive loads. For details see Figure 14, Recommended RS vs Capacitive Load,
and Figure 15, Frequency Response vs Capacitive Load.
One method of improving capacitive load drive in the unity-gain configuration is to insert a 10-Ω to 20-Ω resistor
in series with the output, as shown in Figure 35. This configuration significantly reduces ringing with large
capacitive loads—see Figure 15, Frequency Response vs Capacitive Load. However, if a resistive load is in
parallel with the capacitive load, RS creates a voltage divider. This configuration introduces a DC error at the
output and slightly reduces output swing. This error may be insignificant. For instance, with RL = 10 kΩ and RS =
20 Ω, the error at the output is only about a 0.2%.
V+
RS
VOUT
OPA354-Q1
VIN
RL
CL
Figure 35. Series Resistor in Unity-Gain Configuration Improves Capacitive Load Drive
7.3.8 Wideband Transimpedance Amplifier
Wide bandwidth, low-input bias current, and low input voltage and current noise make the OPAx354-Q1 family of
devices an ideal wideband photodiode transimpedance amplifier for low-voltage single-supply applications. Lowvoltage noise is important because photodiode capacitance causes the effective noise gain of the circuit to
increase at high frequency.
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Feature Description (continued)
The key elements to a transimpedance design, as shown in Figure 36, are the expected diode capacitance
(including the parasitic input common-mode and differential-mode input capacitance (2 + 2) pF for the OPAx354Q1), the desired transimpedance gain (RF), and the gain-bandwidth product (GBW) for the OPAx354-Q1 family of
devices (100 MHz). With these three variables set, the feedback capacitor value (CF) can be set to control the
frequency response.
CF
< 1pF
(prevents gain peaking)
RF
10MW
+V
l
CD
OPA354-Q1
VOUT
Figure 36. Transimpedance Amplifier
To achieve a maximally flat second-order Butterworth frequency response, set the feedback pole as shown in
Equation 1.
1
+
2pR FCF
GBP
Ǹ4pR
C
F
D
(1)
Typical surface-mount resistors have a parasitic capacitance of approximately 0.2 pF that required deduction
from the calculated feedback capacitance value.
Use Equation 2 to calculate the bandwidth.
f *3dB +
GBP Hz
Ǹ2pR
C
F
D
(2)
For even higher transimpedance bandwidth, use the high-speed CMOS OPA355-Q1 (200-MHz GBW) or the
OPA655-Q1 (400-MHz GBW).
7.4 Device Functional Modes
The OPAx354-Q1 family of devices is powered on when the supply is connected. The devices can be operated
as single supply operational amplifiers or dual supply amplifiers depending on the application. The devices can
also be used with asymmetrical supplies as long as the differential voltage (V– to V+) is at least 1.8 V and no
greater than 5.5 V (example: V– set to –3.5 V and V+ set to 1.5 V).
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8 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The OPAx354-Q1 family of devices is a CMOS, rail-to-rail I/O, high-speed, voltage-feedback operational amplifier
designed for video, high-speed, and other applications. The OPAx354-Q1 family of devices is available as a
single, dual, or quad op-amp.
The amplifier features a 100-MHz gain bandwidth, and 150 V/μs slew rate, but it is unity-gain stable and can be
operated as a 1-V/V voltage follower.
8.2 Typical Applications
8.2.1 Transimpedance Amplifier
Wide gain bandwidth, low input bias current, low input voltage, and current noise make the OPAx354-Q1 family
of devices an ideal wideband photodiode transimpedance amplifier. Low-voltage noise is important because
photodiode capacitance causes the effective noise gain of the circuit to increase at high frequency.
The key elements to a transimpedance design, as shown in Figure 37, are the expected diode capacitance
(C(D)), which should include the parasitic input common-mode and differential-mode input capacitance (4 pF + 5
pF); the desired transimpedance gain (R(FB)); and the gain-bandwidth (GBW) for the OPAx354-Q1 family of
devices (20 MHz). With these three variables set, the feedback capacitor value (C(FB)) can be set to control the
frequency response. C(FB) includes the stray capacitance of R(FB), which is 0.2 pF for a typical surface-mount
resistor.
(1)
C(F)
< 1 pF
R(F)
10 MΩ
V(V+)
l
C(D)
OPA354-Q1
VO
V(V–)
(1) C(FB) is optional to prevent gain peaking. C(FB) includes the stray capacitance of R(FB).
Figure 37. Dual-Supply Transimpedance Amplifier
8.2.1.1 Design Requirements
PARAMETER
18
VALUE
Supply voltage V(V+)
2.5 V
Supply voltage V(V–)
–2.5 V
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8.2.1.2 Detailed Design Procedure
To achieve a maximally-flat, second-order Butterworth frequency response, the feedback pole should be set to:
1
=
2 ´ p ´ R(FB) ´ C(FB)
GBW
4 ´ p ´ R(FB) ´ C(D)
(3)
Use Equation 4 to calculate the bandwidth.
ƒ(–3 dB) =
GBW
2 ´ p ´ R(FB) ´ C(D)
(4)
For other transimpedance bandwidths, consider the high-speed CMOS OPA380 (90-MHz GBW), OPA354 (100MHz GBW), OPA300 (180-MHz GBW), OPA355 (200-MHz GBW), or OPA656 and OPA657 (400-MHz GBW).
For single-supply applications, the +INx input can be biased with a positive DC voltage to allow the output to
reach true zero when the photodiode is not exposed to any light, and respond without the added delay that
results from coming out of the negative rail; this configuration is shown in Figure 38. This bias voltage also
appears across the photodiode, providing a reverse bias for faster operation.
0.5 pF
100 k
±
OPAx354-Q1
VOUT
+
13.7 k
SFH213
1 F
280
5V
Figure 38. Single-Supply Transimpedance Amplifier
For additional information, refer to the application bulletin from TI, Compensate Transimpedance Amplifiers
Intuitively (SBOA055).
8.2.1.2.1 Optimizing The Transimpedance Circuit
To achieve the best performance, components should be selected according to the following guidelines:
1. For lowest noise, select R(FB) to create the total required gain. Using a lower value for R(FB) and adding gain
after the transimpedance amplifier generally produces poorer noise performance. The noise produced by
R(FB) increases with the square-root of R(FB), whereas the signal increases linearly. Therefore, signal-to-noise
ratio improves when all the required gain is placed in the transimpedance stage.
2. Minimize photodiode capacitance and stray capacitance at the summing junction (inverting input). This
capacitance causes the voltage noise of the op amp to be amplified (increasing amplification at high
frequency). Using a low-noise voltage source to reverse-bias a photodiode can significantly reduce the
capacitance. Smaller photodiodes have lower capacitance. Use optics to concentrate light on a small
photodiode.
3. Noise increases with increased bandwidth. Limit the circuit bandwidth to only that required. Use a capacitor
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across the R(FB) to limit bandwidth, even if not required for stability.
4. Circuit board leakage can degrade the performance of an otherwise well-designed amplifier. Clean the circuit
board carefully. A circuit board guard trace that encircles the summing junction and is driven at the same
voltage can help control leakage.
For additional information, refer to the following application bulletins from TI: Noise Analysis of FET
Transimpedance Amplifiers (SBOA060), and Noise Analysis for High-Speed Op Amps (SBOA066).
8.2.1.3 Application Curve
105
100
Gain (dB, V/A)
95
90
85
80
75
70
65
60
1000
10000
100000
1000000
Frequency (Hz)
1E+7
5E+7
D001
–3 dB bandwidth is 4.56 MHz
Figure 39. AC Transfer Function
8.2.2 High-Impedance Sensor Interface
Many sensors have high source impedances that may range up to 10 MΩ, or even higher. The output signal of
sensors often must be amplified or otherwise conditioned by means of an amplifier. The input bias current of this
amplifier can load the sensor output and cause a voltage drop across the source resistance, as shown in
Figure 40, where (V(+INx) = VS – I(BIAS) × R(S)). The last term, I(BIAS) × R(S), shows the voltage drop across R(S). To
prevent errors introduced to the system as a result of this voltage, an op amp with very low input bias current
must be used with high impedance sensors. This low current keeps the error contribution by I(BIAS) × R(S) less
than the input voltage noise of the amplifier, so that it does not become the dominant noise factor. The
OPAx354-Q1 family of devices series of op amps feature very low input bias current (typically 200 fA), and are
therefore ideal choices for such applications.
R(S)
100 kΩ
IIB
V(+INx)
V(V+)
Device
V(V–)
VO
R(F)
R(G)
Figure 40. Noise as a Result of I(BIAS)
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8.2.3 Driving ADCs
The OPAx354-Q1 op amps are well-suited for driving sampling analog-to-digital converters (ADCs) with sampling
speeds up to 1 MSPS. The zero-crossover distortion input stage topology allows the OPAx354-Q1 family of
devices to drive ADCs without degradation of differential linearity and THD.
The OPAx354-Q1 family of devices can be used to buffer the ADC switched input capacitance and resulting
charge injection while providing signal gain. Figure 41 shows the OPAx354-Q1 family of devices configured to
drive the ADS8326.
5V
C1
100 nF
5V
(1)
R1
100 Ω
V(V+)
+INx
OPAx354-Q1
(1)
C3
1 nF
V(V–)
VI
0 to 4.096 V
–INx
ADS8326
16-Bit
250kSPS
REF IN
Optional
(2)
R2
50 kΩ
5V
SD1
BAS40
–5 V
C2
100 nF
REF3240
4.096 V
C4
100 nF
(1) Suggested value; may require adjustment based on specific application.
(2) Single-supply applications lose a small number of ADC codes near ground as a result of op amp output swing limitation. If a negative
power supply is available, this simple circuit creates a –0.3-V supply to allow output swing to true ground potential.
Figure 41. Driving the ADS8326
8.2.4 Active Filter
The OPAx354-Q1 family of devices is well-suited for active filter applications that require a wide bandwidth, fast
slew rate, low-noise, single-supply operational amplifier. Figure 42 shows a 500 kHz, second-order, low-pass
filter using the multiple-feedback (MFB) topology. The components have been selected to provide a maximallyflat Butterworth response. Beyond the cutoff frequency, roll-off is –40 dB/dec. The Butterworth response is ideal
for applications requiring predictable gain characteristics, such as the anti-aliasing filter used in front of an ADC.
One point to observe when considering the MFB filter is that the output is inverted, relative to the input. If this
inversion is not required, or not desired, a noninverting output can be achieved through one of the following
options:
1. Adding an inverting amplifier
2. Adding an additional second-order MFB stage
3. Using a noninverting filter topology, such as the Sallen-Key (see Figure 43).
MFB and Sallen-Key, low-pass and high-pass filter synthesis is quickly accomplished using TI’s FilterPro™
program. This software is available as a free download at www.ti.com.
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R3
549 Ω
C2
150 pF
R1
549 Ω
R2
1.24 kΩ
V(V+)
VI
VO
Device
C1
1 nF
V(V–)
Figure 42. Second-Order Butterworth 500-kHz Low-Pass Filter
220 pF
1.8 kΩ
19.5 kΩ
V(V+)
150 kΩ
VI = 1 VRMS
3.3 nF
47 pF
Device
VO
V(V–)
Figure 43. OPAx354-Q1 Configured as a Three-Pole, 20-kHz, Sallen-Key Filter
9 Power Supply Recommendations
The OPAx354-Q1 family of devices is specified for operation from 2.5 to 5.5 V (±1.25 to ±2.75 V); many
specifications apply from –40°C to 125°C. Parameters that can exhibit significant variance with regard to
operating voltage or temperature are shown in the Typical Characteristics section.
CAUTION
Supply voltages larger than 7.5 V can permanently damage the device (see the
Absolute Maximum Ratings table).
Place 0.1-μF bypass capacitors close to the power-supply pins to reduce errors coupling in from noisy or
highimpedance power supplies. For more detailed information on bypass capacitor placement, refer to the Layout
Guidelines section.
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9.1 Power Dissipation
Power dissipation depends on power-supply voltage, signal and load conditions. With dc signals, power
dissipation is equal to the product of output current times the voltage across the conducting output transistor,
VS – VO. Minimize power dissipation by using the lowest possible power-supply voltage necessary to assure the
required output voltage swing.
For resistive loads, the maximum power dissipation occurs at a dc output voltage of one-half the power-supply
voltage. Dissipation with ac signals is lower. Application bulletin AB-039 (SBOA022), Power Amplifier Stress and
Power Handling Limitations, explains how to calculate or measure power dissipation with unusual signals and
loads, and can be found at www.ti.com.
Any tendency to activate the thermal protection circuit indicates excessive power dissipation or an inadequate
heatsink. For reliable operation, limit junction temperature to 150°C, maximum. To estimate the margin of safety
in a complete design, increase the ambient temperature to trigger the thermal protection at 160°C. The thermal
protection should trigger more than 35°C above the maximum expected ambient condition of the application.
10 Layout
10.1 Layout Guidelines
Use good high-frequency printed circuit board (PCB) layout techniques for the OPAx354-Q1 family of devices.
Generous use of ground planes, short and direct signal traces, and a suitable bypass capacitor located at the V+
pin assure clean stable operation. Large areas of copper also provides a means of dissipating heat that is
generated in normal operation. Sockets are not recommended for use with any high-speed amplifier. A 10-nF
ceramic bypass capacitor is the minimum recommended value; adding a 1-μF or larger tantalum capacitor in
parallel can be beneficial when driving a low-resistance load. Providing adequate bypass capacitance is essential
to achieving very low harmonic and intermodulation distortion.
For best operational performance of the device, use good PCB layout practices, including:
• Noise can propagate into analog circuitry through the power pins of the circuit as a whole and the
operational amplifier. Bypass capacitors are used to reduce the coupled noise by providing lowimpedance power sources local to the analog circuitry.
– Connect low-ESR, 0.1-µF ceramic bypass capacitors between each supply pin and ground, placed as
close to the device as possible. A single bypass capacitor from V+ to ground is applicable for singlesupply applications.
• Separate grounding for analog and digital portions of the circuitry is one of the simplest and most
effective methods of noise suppression. One or more layers on multilayer PCBs are usually devoted to
ground planes. A ground plane helps distribute heat and reduces EMI noise pickup. Make sure to
physically separate digital and analog grounds, paying attention to the flow of the ground current. For
more detailed information, refer to Circuit Board Layout Techniques, SLOA089.
• To reduce parasitic coupling, run the input traces as far away from the supply or output traces as
possible. If these traces cannot be kept separate, crossing the sensitive trace perpendicularly is much
better than crossing in parallel with the noisy trace.
• Place the external components as close to the device as possible. Keeping RF and RG close to the
inverting input minimizes parasitic capacitance, as shown in Figure 44.
• Keep the length of input traces as short as possible. Always remember that the input traces are the most
sensitive part of the circuit.
• Consider a driven, low-impedance guard ring around the critical traces. A guard ring can significantly
reduce leakage currents from nearby traces that are at different potentials.
Copyright © 2009–2014, Texas Instruments Incorporated
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Product Folder Links: OPA354-Q1 OPA2354-Q1 OPA4354-Q1
23
OPA354-Q1, OPA2354-Q1, OPA4354-Q1
SBOS492B – JUNE 2009 – REVISED DECEMBER 2014
www.ti.com
10.2 Layout Example
RIN
+
VIN
VOUT
RG
RF
(Schematic Representation)
Run the input traces
as far away from
the supply lines
as possible
Place components
close to device and to
each other to reduce
parasitic errors
VS+
RF
NC
NC
±IN
V+
+IN
OUT
V±
NC
RG
GND
VIN
GND
RIN
Only needed for
dual-supply
operation
GND
VS±
(or GND for single supply)
Use low-ESR, ceramic
bypass capacitor
VOUT
Ground (GND) plane on another layer
Figure 44. Operational Amplifier Board Layout for Noninverting Configuration
24
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Copyright © 2009–2014, Texas Instruments Incorporated
Product Folder Links: OPA354-Q1 OPA2354-Q1 OPA4354-Q1
OPA354-Q1, OPA2354-Q1, OPA4354-Q1
www.ti.com
SBOS492B – JUNE 2009 – REVISED DECEMBER 2014
11 Device and Documentation Support
11.1 Documentation Support
11.1.1 Related Documentation
For related documentation see the following:
• ADS8326 16-Bit, High-Speed, 2.7V to 5.5V microPower Sampling ANALOG-TO-DIGITAL CONVERTER,
SBAS343
• Circuit Board Layout Techniques, SLOA089
• Compensate Transimpedance Amplifiers Intuitively, SBOA055
• FilterPro™ User's Guide, SBFA001
• NOISE ANALYSIS OF FET TRANSIMPEDANCE AMPLIFIERS, SBOA060
• Noise Analysis for High-Speed Op Amps, SBOA066
• OPA380 and OPA2380 Precision, High-Speed Transimpedance Amplifier, SBOS291
• OPA354, OPA2354, and OPA4354 250MHz, Rail-to-Rail I/O, CMOS OPERATIONAL AMPLIFIERS,
SBOS233
• OPA355, OPA2355, and OPA3355 200MHz, CMOS OPERATIONAL AMPLIFIER WITH SHUTDOWN,
SBOS195
• OPA656 Wideband, Unity-Gain Stable, FET-Input OPERATIONAL AMPLIFIER, SBOS196
• POWER AMPLIFIER STRESS AND POWER HANDLING LIMITATIONS, SBOA022
11.2 Related Links
The table below lists quick access links. Categories include technical documents, support and community
resources, tools and software, and quick access to sample or buy.
Table 2. Related Links
PARTS
PRODUCT FOLDER
SAMPLE & BUY
TECHNICAL
DOCUMENTS
TOOLS &
SOFTWARE
SUPPORT &
COMMUNITY
OPA354-Q1
Click here
Click here
Click here
Click here
Click here
OPA2354-Q1
Click here
Click here
Click here
Click here
Click here
OPA4354-Q1
Click here
Click here
Click here
Click here
Click here
11.3 Trademarks
FilterPro is a trademark of Texas Instruments Incorporated.
All other trademarks are the property of their respective owners.
11.4 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
11.5 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
Copyright © 2009–2014, Texas Instruments Incorporated
Submit Documentation Feedback
Product Folder Links: OPA354-Q1 OPA2354-Q1 OPA4354-Q1
25
PACKAGE OPTION ADDENDUM
www.ti.com
11-Jul-2015
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
Lead/Ball Finish
MSL Peak Temp
(2)
(6)
(3)
Op Temp (°C)
Device Marking
(4/5)
OPA2354AQDGKRQ1
ACTIVE
VSSOP
DGK
8
2500
Green (RoHS
& no Sb/Br)
CU NIPDAU |
CU NIPDAUAG
Level-2-260C-1 YEAR
-40 to 125
OSLQ
OPA354AQDBVRQ1
ACTIVE
SOT-23
DBV
5
3000
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 125
OSFQ
OPA4354AQPWRQ1
ACTIVE
TSSOP
PW
14
2000
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
-40 to 125
4354Q1
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3)
MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4)
There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5)
Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead/Ball Finish - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead/Ball Finish values may wrap to two lines if the finish
value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
Addendum-Page 1
Samples
PACKAGE OPTION ADDENDUM
www.ti.com
11-Jul-2015
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
OTHER QUALIFIED VERSIONS OF OPA4354-Q1 :
• Catalog: OPA4354
NOTE: Qualified Version Definitions:
• Catalog - TI's standard catalog product
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
17-Jun-2015
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
OPA2354AQDGKRQ1
VSSOP
DGK
OPA354AQDBVRQ1
SOT-23
OPA4354AQPWRQ1
TSSOP
SPQ
Reel
Reel
A0
Diameter Width (mm)
(mm) W1 (mm)
8
2500
330.0
DBV
5
3000
PW
14
2000
B0
(mm)
K0
(mm)
P1
(mm)
12.4
5.3
3.4
1.4
8.0
179.0
8.4
3.2
3.2
1.4
330.0
12.4
6.9
5.6
1.6
Pack Materials-Page 1
W
Pin1
(mm) Quadrant
12.0
Q1
4.0
8.0
Q3
8.0
12.0
Q1
PACKAGE MATERIALS INFORMATION
www.ti.com
17-Jun-2015
*All dimensions are nominal
Device
Package Type
Package Drawing
Pins
SPQ
Length (mm)
Width (mm)
Height (mm)
OPA2354AQDGKRQ1
VSSOP
DGK
8
2500
367.0
367.0
35.0
OPA354AQDBVRQ1
SOT-23
DBV
5
3000
195.0
200.0
45.0
OPA4354AQPWRQ1
TSSOP
PW
14
2000
367.0
367.0
35.0
Pack Materials-Page 2
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