LMH6715 www.ti.com SNOSA10C – MAY 2002 – REVISED APRIL 2013 LMH6715 Dual Wideband Video Op Amp Check for Samples: LMH6715 FEATURES DESCRIPTION • The LMH6715 combines TI's VIP10 high speed complementary bipolar process with TI's current feedback topology to produce a very high speed dual op amp. The LMH6715 provides 400MHz small signal bandwidth at a gain of +2V/V and 1300V/μs slew rate while consuming only 5.8mA per amplifier from ±5V supplies. 1 2 • • • • • • • • TA = 25°C, RL = 100Ω, Typical Values Unless Specified. Very Low Diff. Gain, Phase: 0.02%, 0.02° Wide Bandwidth: 480MHz (AV = +1V/V); 400MHz (AV = +2V/V) 0.1dB Gain Flatness to 100MHz Low Power: 5.8mA/Channel −70dB Channel-to-Channel Crosstalk (10MHz) Fast Slew Rate: 1300V/μs Unity Gain Stable Improved Replacement for CLC412 APPLICATIONS • • • • • • HDTV, NTSC & PAL Video Systems Video Switching and Distribution IQ Amplifiers Wideband Active Filters Cable Drivers DC Coupled Single-to-Differential Conversions The LMH6715 offers exceptional video performance with its 0.02% and 0.02° differential gain and phase errors for NTSC and PAL video signals while driving up to four back terminated 75Ω loads. The LMH6715 also offers a flat gain response of 0.1dB to 100MHz and very low channel-to-channel crosstalk of −70dB at 10MHz. Additionally, each amplifier can deliver 70mA of output current. This level of performance makes the LMH6715 an ideal dual op amp for high density, broadcast quality video systems. The LMH6715's two very well matched amplifiers support a number of applications such as differential line drivers and receivers. In addition, the LMH6715 is well suited for Sallen Key active filters in applications such as anti-aliasing filters for high speed A/D converters. Its small 8-pin SOIC package, low power requirement, low noise and distortion allow the LMH6715 to serve portable RF applications such as IQ channels. Differential Gain & Phase with Multiple Video Loads Figure 1. 1 2 Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. All trademarks are the property of their respective owners. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 2002–2013, Texas Instruments Incorporated LMH6715 SNOSA10C – MAY 2002 – REVISED APRIL 2013 www.ti.com Frequency Response vs. VOUT Figure 2. These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates. Absolute Maximum Ratings (1) (2) ESD Tolerance (3) Human Body Model 2000V Machine Model 150V VCC ±6.75V IOUT See (4) Common-Mode Input Voltage ±VCC Differential Input Voltage 2.2V Maximum Junction Temperature +150°C −65°C to +150°C Storage Temperature Range Lead Temperature (Soldering 10 sec) (1) (2) (3) (4) +300°C Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not ensured. For ensured specifications, see the Electrical Characteristics tables. If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/ Distributors for availability and specifications. Human body model, 1.5kΩ in series with 100pF. Machine model, 0Ω In series with 200pF. The maximum output current (IOUT) is determined by device power dissipation limitations. See the POWER DISSIPATION section for more details. Operating Ratings Thermal Resistance Package SOIC (θJC) (θJA) 65°C/W 145°C/W −40°C to +85°C Operating Temperature Range Nominal Operating Voltage 2 ±5V to ±6V Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 LMH6715 www.ti.com SNOSA10C – MAY 2002 – REVISED APRIL 2013 Electrical Characteristics (1) AV = +2, RF = 500Ω, VCC = ±5 V, RL = 100Ω; unless otherwise specified. Boldface limits apply at the temperature extremes. Symbol Parameter Conditions Min Typ Max Units 280 400 MHz 170 MHz dB Frequency Domain Response SSBW -3dB Bandwidth VOUT < 0.5VPP, RF = 300Ω LSBW -3dB Bandwidth VOUT < 4.0VPP, RF = 300Ω Gain Flatness VOUT < 0.5VPP GFP Peaking DC to 100MHz, RF = 300Ω 0.1 GFR Rolloff DC to 100MHz, RF = 300Ω 0.1 dB deg LPD Linear Phase Deviation DC to 100MHz, RF = 300Ω 0.25 DG Differential Gain RL = 150Ω, 4.43MHz 0.02 % DP Differential Phase RL = 150Ω, 4.43MHz 0.02 deg 0.5V Step Time Domain Response Tr Rise and Fall Time 1.4 ns 4V Step 3 ns Ts Settling Time to 0.05% 2V Step 12 ns OS Overshoot 0.5V Step 1 % SR Slew Rate 2V Step 1300 V/μs Distortion And Noise Response HD2 2nd Harmonic Distortion 2VPP, 20MHz −60 dBc HD3 3rd Harmonic Distortion 2VPP, 20MHz −75 dBc Equivalent Input Noise VN Non-Inverting Voltage >1MHz 3.4 nV/√Hz IN Inverting Current >1MHz 10.0 pA/√Hz INN Non-Inverting Current >1MHz 1.4 pA/√Hz SNF Noise Floor >1MHz −153 dB1Hz Input Referred 10MHz −70 dB XTLKA Crosstalk Static, DC Performance VIO Input Offset Voltage DVIO IBN Average Drift Input Bias Current DIBN IBI ±6 ±8 ±5 ±6 Average Drift μA ±12 ±20 ±30 Inverting mV μV/°C ±30 Non-Inverting Average Drift Input Bias Current DIBI ±2 nA/°C μA ±21 ±35 ±20 nA/°C PSRR Power Supply Rejection Ratio DC 46 44 60 dB CMRR Common Mode Rejection Ratio DC 50 47 56 dB ICC Supply Current per Amplifier RL = ∞ 4.7 4.1 5.8 7.6 8.1 mA Miscellaneous Performance RIN Input Resistance Non-Inverting 1000 kΩ CIN Input Capacitance Non-Inverting 1.0 pF ROUT Output Resistance Closed Loop .06 Ω (1) Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very limited self-heating of the device such that TJ = TA. No specification of parametric performance is indicated in the electrical tables under conditions of internal self heating where TJ > TA. See Application Section for information on temperature de-rating of this device." Min/Max ratings are based on product characterization and simulation. Individual parameters are tested as noted. Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 3 LMH6715 SNOSA10C – MAY 2002 – REVISED APRIL 2013 www.ti.com Electrical Characteristics(1) (continued) AV = +2, RF = 500Ω, VCC = ±5 V, RL = 100Ω; unless otherwise specified. Boldface limits apply at the temperature extremes. Symbol VO Parameter Output Voltage Range VOL Conditions Min RL = ∞ RL = 100Ω CMIR Input Voltage Range IO Output Current ±3.5 ±3.4 Common Mode Typ Max Units ±4.0 V ±3.9 V ±2.2 V 70 mA Connection Diagram Figure 3. 8-Pin SOIC, Top View 4 Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 LMH6715 www.ti.com SNOSA10C – MAY 2002 – REVISED APRIL 2013 Typical Performance Characteristics (TA = 25°C, VCC = ±5V, AV = ±2V/V, RF = 500Ω, RL = 100Ω, unless otherwise specified). Non-Inverting Freq·uency Response Inverting Frequency Response Figure 4. Figure 5. Non-Inverting Frequency Response vs. VOUT Small Signal Channel Matching Figure 6. Figure 7. Frequency Response vs. Load Resistance Non-Inverting Frequency Response vs. RF Figure 8. Figure 9. Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 5 LMH6715 SNOSA10C – MAY 2002 – REVISED APRIL 2013 www.ti.com Typical Performance Characteristics (continued) (TA = 25°C, VCC = ±5V, AV = ±2V/V, RF = 500Ω, RL = 100Ω, unless otherwise specified). 6 Small Signal Pulse Response Large Signal Pulse Response Figure 10. Figure 11. Input-Referred Crosstalk Settling Time vs. Accuracy Figure 12. Figure 13. −3dB Bandwidth vs. VOUT DC Errors vs. Temperature Figure 14. Figure 15. Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 LMH6715 www.ti.com SNOSA10C – MAY 2002 – REVISED APRIL 2013 Typical Performance Characteristics (continued) (TA = 25°C, VCC = ±5V, AV = ±2V/V, RF = 500Ω, RL = 100Ω, unless otherwise specified). Open Loop Transimpedance, Z(s) Equivalent Input Noise vs. Frequency Figure 16. Figure 17. Differential Gain & Phase vs. Load Differential Gain vs. Frequency Figure 18. Figure 19. Differential Phase vs. Frequency Gain Flatness & Linear Phase Deviation Figure 20. Figure 21. Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 7 LMH6715 SNOSA10C – MAY 2002 – REVISED APRIL 2013 www.ti.com Typical Performance Characteristics (continued) (TA = 25°C, VCC = ±5V, AV = ±2V/V, RF = 500Ω, RL = 100Ω, unless otherwise specified). 2nd Harmonic Distortion vs. Output Voltage 3rd Harmonic Distortion vs. Output Voltage Figure 22. Figure 23. Closed Loop Output Resistance PSRR & CMRR Figure 24. Figure 25. Suggested RS vs. CL Figure 26. 8 Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 LMH6715 www.ti.com SNOSA10C – MAY 2002 – REVISED APRIL 2013 APPLICATION SECTION Figure 27. Non-Inverting Configuration with Power Supply Bypassing Figure 28. Inverting Configuration with Power Supply Bypassing Application Introduction Offered in an 8-pin package for reduced space and cost, the wideband LMH6715 dual current-feedback op amp provides closely matched DC and AC electrical performance characteristics making the part an ideal choice for wideband signal processing. Applications such as broadcast quality video systems, IQ amplifiers, filter blocks, high speed peak detectors, integrators and transimedance amplifiers will all find superior performance in the LMH6715 dual op amp. FEEDBACK RESISTOR SELECTION One of the key benefits of a current feedback operational amplifier is the ability to maintain optimum frequency response independent of gain by using appropriate values for the feedback resistor (RF). The Electrical Characteristics and Typical Performance plots specify an RF of 500Ω, a gain of +2V/V and ±5V power supplies (unless otherwise specified). Generally, lowering RF from it's recommended value will peak the frequency response and extend the bandwidth while increasing the value of RF will cause the frequency response to roll off faster. Reducing the value of RF too far below it's recommended value will cause overshoot, ringing and, eventually, oscillation. Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 9 LMH6715 SNOSA10C – MAY 2002 – REVISED APRIL 2013 www.ti.com Frequency Response vs. RF Figure 29. Figure 29 shows the LMH6715's frequency response as RF is varied (RL = 100Ω, AV = +2). This plot shows that an RF of 200Ω results in peaking and marginal stability. An RF of 300Ω gives near maximal bandwidth and gain flatness with good stability, but with very light loads (RL > 300Ω) the device may show some peaking. An RF of 500Ω gives excellent stability with good bandwidth and is the recommended value for most applications. Since all applications are slightly different it is worth some experimentation to find the optimal RF for a given circuit. For more information see Application Note OA-13 (Literature Number SNOA366) which describes the relationship between RF and closed-loop frequency response for current feedback operational amplifiers. When configuring the LMH6715 for gains other than +2V/V, it is usually necessary to adjust the value of the feedback resistor. The two plots labeled shown in Figure 30 and Figure 31 provide recommended feedback resistor values for a number of gain selections. RF vs. Non-Inverting Gain Figure 30. Both plots show the value of RF approaching a minimum value (dashed line) at high gains. Reducing the feedback resistor below this value will result in instability and possibly oscillation. The recommended value of RF is depicted by the solid line, which begins to increase at higher gains. The reason that a higher RF is required at higher gains is the need to keep RG from decreasing too far below the output impedance of the input buffer. For the LMH6715 the output resistance of the input buffer is approximately 160Ω and 50Ω is a practical lower limit for RG. Due to the limitations on RG the LMH6715 begins to operate in a gain bandwidth limited fashion for gains of ±5V/V or greater. 10 Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 LMH6715 www.ti.com SNOSA10C – MAY 2002 – REVISED APRIL 2013 RF vs. Inverting Gain Figure 31. When using the LMH6715 as a replacement for the CLC412, identical bandwidth can be obtained by using an appropriate value of RF . The chart “Frequency Response vs. RF” (see Figure 29) shows that an RF of approximately 700Ω will provide bandwidth very close to that of the CLC412. At other gains a similar increase in RF can be used to match the new and old parts. CIRCUIT LAYOUT With all high frequency devices, board layouts with stray capacitances have a strong influence over AC performance. The LMH6715 is no exception and its input and output pins are particularly sensitive to the coupling of parasitic capacitances (to AC ground) arising from traces or pads placed too closely (<0.1”) to power or ground planes. In some cases, due to the frequency response peaking caused by these parasitics, a small adjustment of the feedback resistor value will serve to compensate the frequency response. Also, it is very important to keep the parasitic capacitance across the feedback resistor to an absolute minimum. The performance plots in the data sheet can be reproduced using the evaluation boards available from Texas Instruments. The LMH730036 board uses all SMT parts for the evaluation of the LMH6715. The board can serve as an example layout for the final production printed circuit board. Care must also be taken with the LMH6715's layout in order to achieve the best circuit performance, particularly channel-to-channel isolation. The decoupling capacitors (both tantalum and ceramic) must be chosen with good high frequency characteristics to decouple the power supplies and the physical placement of the LMH6715's external components is critical. Grouping each amplifier's external components with their own ground connection and separating them from the external components of the opposing channel with the maximum possible distance is recommended. The input (RIN) and gain setting resistors (RF) are the most critical. It is also recommended that the ceramic decoupling capacitor (0.1μF chip or radial-leaded with low ESR) should be placed as closely to the power pins as possible. POWER DISSIPATION Follow these steps to determine the Maximum power dissipation for the LMH6715: 1. Calculate the quiescent (no-load) power: PAMP = ICC (VCC - VEE) 2. Calculate the RMS power at the output stage: PO = (VCC -VLOAD)(ILOAD), where VLOAD and ILOAD are the voltage and current across the external load. 3. Calculate the total RMS power: Pt = PAMP + PO The maximum power that the LMH6715, package can dissipate at a given temperature can be derived with the following equation: Pmax = (150º - Tamb)/ θJA, where Tamb = Ambient temperature (°C) and θJA = Thermal resistance, from junction to ambient, for a given package (°C/W). For the SOIC package θJA is 145°C/W. (1) Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 11 LMH6715 SNOSA10C – MAY 2002 – REVISED APRIL 2013 www.ti.com MATCHING PERFORMANCE With proper board layout, the AC performance match between the two LMH6715's amplifiers can be tightly controlled as shown in Typical Performance plot labeled “Small-Signal Channel Matching”. The measurements were performed with SMT components using a feedback resistor of 300Ω at a gain of +2V/V. The LMH6715's amplifiers, built on the same die, provide the advantage of having tightly matched DC characteristics. SLEW RATE AND SETTLING TIME One of the advantages of current-feedback topology is an inherently high slew rate which produces a wider full power bandwidth. The LMH6715 has a typical slew rate of 1300V/µs. The required slew rate for a design can be calculated by the following equation: SR = 2πfVpk. Careful attention to parasitic capacitances is critical to achieving the best settling time performance. The LMH6715 has a typical short term settling time to 0.05% of 12ns for a 2V step. Also, the amplifier is virtually free of any long term thermal tail effects at low gains. When measuring settling time, a solid ground plane should be used in order to reduce ground inductance which can cause common-ground-impedance coupling. Power supply and ground trace parasitic capacitances and the load capacitance will also affect settling time. Placing a series resistor (Rs) at the output pin is recommended for optimal settling time performance when driving a capacitive load. The Typical Performance plot labeled “RS and Settling Time vs. Capacitive Load” provides a means for selecting a value of Rs for a given capacitive load. DC & NOISE PERFORMANCE A current-feedback amplifier's input stage does not have equal nor correlated bias currents, therefore they cannot be canceled and each contributes to the total DC offset voltage at the output by the following equation: (2) The input resistance is the resistance looking from the non-inverting input back toward the source. For inverting DC-offset calculations, the source resistance seen by the input resistor Rg must be included in the output offset calculation as a part of the non-inverting gain equation. Application note OA-07 (Literature Number SNOA365) gives several circuits for DC offset correction. The noise currents for the inverting and non-inverting inputs are graphed in the Typical Performance plot labeled “Equivalent Input Noise”. A more complete discussion of amplifier input-referred noise and external resistor noise contribution can be found in OA-12 (Literature Number SNOA375). DIFFERENTIAL GAIN & PHASE The LMH6715 can drive multiple video loads with very low differential gain and phase errors. Figure 19 and Figure 20 show performance for loads from 1 to 4. The Electrical Characteristics table also specifies performance for one 150Ω load at 4.43MHz. For NTSC video, the performance specifications also apply. Application note OA24 (Literature Number SNOA370) “Measuring and Improving Differential Gain & Differential Phase for Video”, describes in detail the techniques used to measure differential gain and phase. I/O VOLTAGE & OUTPUT CURRENT The usable common-mode input voltage range (CMIR) of the LMH6715 specified in the Electrical Characteristics table of the data sheet shows a range of ±2.2 volts. Exceeding this range will cause the input stage to saturate and clip the output signal. The output voltage range is determined by the load resistor and the choice of power supplies. With ±5 volts the class A/B output driver will typically drive ±3.9V into a load resistance of 100Ω. Increasing the supply voltages will change the common-mode input and output voltage swings while at the same time increase the internal junction temperature. 12 Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 LMH6715 www.ti.com SNOSA10C – MAY 2002 – REVISED APRIL 2013 Applications Circuits SINGLE-TO-DIFFERENTIAL LINE DRIVER The LMH6715's well matched AC channel-response allows a single-ended input to be transformed to highly matched push-pull driver. From a 1V single-ended input the circuit of Figure 32 produces 1V differential signal between the two outputs. For larger signals the input voltage divider (R1 = 2R2) is necessary to limit the input voltage on channel 2. Figure 32. Single-to-Differential Line Driver DIFFERENTIAL LINE RECEIVER Figure 33 and Figure 34 show two different implementations of an instrumentation amplifier which convert differential signals to single-ended. Figure 34 allows CMRR adjustment through R2. Figure 33. Differential Line Receiver Figure 34. Differential Line Receiver with CMRR Adjustment Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 13 LMH6715 SNOSA10C – MAY 2002 – REVISED APRIL 2013 www.ti.com NON-INVERTING CURRENT-FEEDBACK INTEGRATOR The circuit of Figure 35 achieves its high speed integration by placing one of the LMH6715's amplifiers in the feedback loop of the second amplifier configured as shown. Figure 35. Current Feedback Integrator LOW NOISE WIDE-BANDWIDTH TRANSIMPEDANCE AMPLIFIER Figure 36 implements a low noise transimpedance amplifier using both channels of the LMH6715. This circuit takes advantage of the lower input bias current noise of the non-inverting input and achieves negative feedback through the second LMH6715 channel. The output voltage is set by the value of RF while frequency compensation is achieved through the adjustment of RT. Figure 36. Low-Noise, Wide Bandwidth, Transimpedance Amp. 14 Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 LMH6715 www.ti.com SNOSA10C – MAY 2002 – REVISED APRIL 2013 REVISION HISTORY Changes from Revision B (April 2013) to Revision C • Page Changed layout of National Data Sheet to TI format .......................................................................................................... 14 Submit Documentation Feedback Copyright © 2002–2013, Texas Instruments Incorporated Product Folder Links: LMH6715 15 PACKAGE OPTION ADDENDUM www.ti.com 27-Jul-2016 PACKAGING INFORMATION Orderable Device Status (1) LMH6715 MDC Package Type Package Pins Package Drawing Qty ACTIVE DIESALE Y 0 400 Eco Plan Lead/Ball Finish MSL Peak Temp (2) (6) (3) Op Temp (°C) Green (RoHS & no Sb/Br) Call TI Level-1-NA-UNLIM -40 to 85 Device Marking (4/5) LMH6715MA NRND SOIC D 8 95 TBD Call TI Call TI -40 to 85 LMH6715MA/NOPB ACTIVE SOIC D 8 95 Green (RoHS & no Sb/Br) CU SN Level-1-260C-UNLIM -40 to 85 LMH67 15MA LMH6715MAX/NOPB ACTIVE SOIC D 8 2500 Green (RoHS & no Sb/Br) CU SN Level-1-260C-UNLIM -40 to 85 LMH67 15MA (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. (4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device. (5) Multiple Device Markings will be inside parentheses. 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Addendum-Page 2 PACKAGE MATERIALS INFORMATION www.ti.com 23-Sep-2013 TAPE AND REEL INFORMATION *All dimensions are nominal Device LMH6715MAX/NOPB Package Package Pins Type Drawing SOIC D 8 SPQ Reel Reel A0 Diameter Width (mm) (mm) W1 (mm) 2500 330.0 12.4 Pack Materials-Page 1 6.5 B0 (mm) K0 (mm) P1 (mm) 5.4 2.0 8.0 W Pin1 (mm) Quadrant 12.0 Q1 PACKAGE MATERIALS INFORMATION www.ti.com 23-Sep-2013 *All dimensions are nominal Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm) LMH6715MAX/NOPB SOIC D 8 2500 367.0 367.0 35.0 Pack Materials-Page 2 IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, enhancements, improvements and other changes to its semiconductor products and services per JESD46, latest issue, and to discontinue any product or service per JESD48, latest issue. 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