STMicroelectronics A5970AD 0808 Up to 1 a switch step down switching regulator for automotive application Datasheet

A5970AD
Up to 1 A switch step down switching regulator
for automotive applications
Features
■
Qualified following the AEC-Q100
requirements (temperature grade 3), see
PPAP for more details.
■
1 A DC output current
■
Operating input voltage from 4 V to 36 V
■
3.3 V / (±2 %) reference voltage
■
Output voltage adjustable from 1.235 V to 35 V
■
Low dropout operation: 100 % duty cycle
■
500 kHz internally fixed frequency
■
Voltage feedforward
■
Zero load current operation
■
Internal current limiting
■
Inhibit for zero current consumption
■
Synchronization
■
Protection against feedback disconnection
■
Thermal shutdown
SO-8
Description
The A5970AD is a step down monolithic power
switching regulator with a switch current limit of
1.35 A so it is able to deliver more than 1 A DC
current to the load depending on the application
conditions.
The output voltage can be set from 1.235 V
to 35 V. The device uses an internal P-channel
D-MOS transistor (with a typical RDS(on) of
250 mΩ) as switching element to avoid the use of
bootstrap capacitor and guarantee high efficiency.
An internal oscillator fixes the switching frequency
at 500 kHz to minimize the size of external
components. Having a minimum input voltage of
4 V only, it is particularly suitable for 5 V bus,
available in all computer related applications.
Applications
■
Dedicated to automotive applications
Pulse by pulse current limit with the internal
frequency modulation offers an effective constant
current short circuit protection.
Figure 1.
Application schematic
L1 15uH
VIN=4.4V to 35V
VCC
8
1
4
2
SYNCH
COMP
C4
C1
A5970AD
22nF
R1
STPS340U
5k6
C2
100uF
10V
5
6
35V
August 2008
D1
FB
10uF
CERAMIC
Vout=3.3V
OUT
C3
R3
220pF
4k7
VREF
3.3V
7
GND
3
INH
R2
3k3
Rev 2
1/16
www.st.com
1
A5970AD
Contents
Contents
1
2
Pin settings . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3
1.1
Pin connection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3
1.2
Pin description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3
Electrical data . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
2.1
Maximum ratings . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
2.2
Thermal data . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
3
Electrical characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5
4
Functional description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
5
6
4.1
Power supply and voltage reference . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
4.2
Voltages monitor . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
4.3
Oscillator and synchronizator . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
4.4
Current protection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9
4.5
Error amplifier . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
4.6
PWM comparator and power stage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
4.7
Inhibit function . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12
4.8
Thermal shutdown . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12
Additional features and protections . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
5.1
Feedback disconnection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
5.2
Output overvoltage protection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
5.3
Zero load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
Package mechanical data . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14
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A5970AD
1
Pin settings
1.1
Pin connection
Figure 1.
1.2
Pin connection (top view)
Pin description
Table 1.
Pin description
N°
Pin
1
OUT
Description
Regulator output.
SYNCH
Master/slave synchronization. When it is open, a signal synchronous
with the turn-off of the internal power is present at the pin. When
connected to an external signal at a frequency higher than the internal
one, then the device is synchronized by the external signal. Connecting
together the SYNC pin of two devices, the one with the higher frequency
works as master and the other one, works as slave.
3
INH
A logical signal (active high) disables the device. With IHN higher than
2.2 V the device is OFF and with INH lower than 0.8 V, the device is ON.
If INH is not used the pin must be grounded. When it is open, an internal
pull-up disables the device.
4
COMP
2
E/A output for frequency compensation.
Feedback input. Connecting directly to this pin results in an output
voltage of 1.235 V. An external resistive divider is required for higher
output voltages (the typical value for the resistor connected between this
pin and ground is 4.7 k).
5
FB
6
VREF
3.3 V VREF. No cap is requested for stability.
7
GND
Ground.
8
VCC
Unregulated DC input voltage.
3/16
A5970AD
2
Electrical data
2.1
Maximum ratings
Table 2.
Absolute maximum ratings
Symbol
Value
Unit
40
V
V
V
V8
Input voltage
V1
OUT pin DC voltage
OUT pin peak voltage at Δt = 0.1μs
-1 to 40
-5 to 40
I1
Maximum output current
int. limit.
V4, V5
Analog pins
4
V
-0.3 to VCC
V
-0.3 to 4
V
0.75
W
Operating junction temperature range
-40 to 150
°C
Storage temperature range
-55 to 150
°C
SO8
Unit
120 (1)
°C/W
V3
INH
V2
SYNCH
PTOT
TJ
TSTG
2.2
Parameter
Power dissipation at TA ≤ 70 °C
Thermal data
Table 3.
Thermal data
Symbol
RthJA
Parameter
Maximum thermal resistance junction-ambient
1. Package mounted on board
4/16
A5970AD
Electrical characteristics
Table 4.
Electrical characteristics
(TJ = -40 °C to 125 °C, VCC = 12 V, unless otherwise specified)
Symbol
VCC
RDS(on)
IL
fSW
Parameter
Test condition
Operating input
voltage range
Min
MOSFET on
resistance
Maximum limiting
current (1)
Typ
4
0.250
VCC = 5 V
1.35
1.8
VCC = 5 V, TJ = 25 °C
1.5
1.8
430
500
Switching frequency
Duty cycle
Max
Unit
36
V
0.5
Ω
A
0
570
kHz
100
%
1.25
V
Dynamic characteristics (see test circuit).
V5
Voltage feedback
4.4 V < VCC < 36 V
η
Efficiency
V0 = 5 V, VCC = 12 V
1.220
1.235
90
%
DC characteristics
Iqop
Total operating
quiescent current
Iq
Quiescent current
Duty cycle = 0; VFB = 1.5 V
Iqst-by
Total stand-by
quiescent current
Vinh > 2.2 V
5
50
7
mA
2.7
mA
100
μA
0.8
V
Inhibit
Device ON
INH threshold voltage
Device OFF
2.2
V
3.5
V
Error amplifier
VOH
High level output
voltage
VFB = 1 V
VOL
Low level output
voltage
VFB = 1.5 V
Io source
Io sink
Source output current
Sink output current
VCOMP = 1.9 V;
0.4
VCOMP = 1.9 V;
V
190
300
μA
1
1.5
mA
VFB = 1 V
VFB = 1 V
Ib
Source bias current
DC open loop gain
gm
Transconductance
2.5
RL=
8
3
ICOMP = -0.1 mA to 0.1 mA;
50
4
μA
57
dB
2.3
mS
VCOMP = 1.9 V
5/16
A5970AD
Table 4.
Electrical characteristics (continued)
(TJ = -40 °C to 125 °C, VCC = 12 V, unless otherwise specified)
Symbol
Parameter
Test condition
Min
Typ
Max
Unit
VREF
V
0.74
V
0.25
0.45
mA
Synch function
High input voltage
VCC = 4.4 to 36 V;
Low input voltage
VCC = 4.4 to 36 V;
Slave synch current
Vsynch = 0.74 V (2)
Vsynch = 2.33 V
2.5
0.11
0.21
Master output
amplitude
Isource= 3 mA
2.75
3
V
Output pulse width
No load, Vsynch= 1.65 V
0.20
0.35
μs
3.234
3.3
3.366
V
3.2
3.3
3.399
V
5
10
mV
8
15
mV
18
30
mA
Reference section
Reference voltage
IREF = 0 to 5 mA
VCC = 4.4 V to 36 V
Line regulation
IREF = 0 mA
VCC = 4.4 V to 36 V
Load regulation
Short circuit current
IREF = 0 mA
5
1. With TJ = 85 °C, Ilim_min = 1.5 A, assured by design, characterization and statistical correlation.
2. Guaranteed by design.
6/16
A5970AD
4
Functional description
The main internal blocks are shown in Figure 2, where is reported the device block diagram.
They are:
■
A voltage regulator that supplies the internal circuitry. From this regulator, a 3.3 V
reference voltage is externally available.
■
A voltage monitor circuit that checks the input and internal voltages.
■
A fully integrated sawtooth oscillator whose frequency is 500 kHz
■
Two embedded current limitations circuitries which control the current that flows through
the power switch. The pulse by pulse current limit forces the power switch OFF cycle by
cycle if the current reaches an internal threshold, while the frequency shifter reduces the
switching frequency in order to strongly reduce the duty cycle.
■
A transconductance error amplifier.
■
A pulse width modulator (PWM) comparator and the relative logic circuitry necessary to
drive the internal power.
■
An high side driver for the internal P-MOS switch.
■
An inhibit block for stand-by operation
■
A circuit to realize the thermal protection function.
Figure 2.
Block diagram
7/16
A5970AD
4.1
Power supply and voltage reference
The internal regulator circuit (shown in Figure 2) consists of a start-up circuit, an internal
voltage pre-regulator, the bandgap voltage reference and the bias block that provides
current to all the blocks.
The starter gives the start-up currents to the whole device when the input voltage goes high
and the device is enabled (inhibit pin connected to ground).
The preregulator block supplies the bandgap cell with a preregulated voltage VREG that has
a very low supply voltage noise sensitivity.
4.2
Voltages monitor
An internal block senses continuously the VCC, VREF and VBG. If the voltages go higher than
their thresholds, the regulator starts to work. There is also an hysteresis on the VCC (UVLO).
Figure 3.
4.3
Internal regulator circuit
Oscillator and synchronizer
Figure 4 shows the block diagram of the oscillator circuit.
The clock generator provides the switching frequency of the device that is internally fixed at
500 kHz. The frequency shifter block acts reducing the switching frequency in case of strong
overcurrent or short circuit. The clock signal is then used in the internal logic circuitry and is
the input of the ramp generator and Synchronizer blocks.
The ramp generator circuit provides the sawtooth signal, used to realize the PWM control
and the internal voltage feed forward, while the synchronizer circuit generates the
synchronization signal. In fact the device has a synchronization pin that can works both as
master and slave.
As master to synchronize external devices to the internal switching frequency.
8/16
A5970AD
As slave to synchronize itself by external signal.
In particular, connecting together two devices, the one with the lower switching frequency
works as slave and the other one works as master.
To synchronize the device, the SYNC pin has to pass from a low level to a level higher than
the synchronization threshold with a duty cycle that can vary approximately from 10 % to
90 %, depending also on the signal frequency and amplitude.
The frequency of the synchronization signal must be at least higher than the internal
switching frequency of the device (500 kHz).
Figure 4.
4.4
Oscillator circuit
Current protection
The A5970AD has two current limit protections, pulse by pulse and frequency fold back.
The schematic of the current limitation circuitry for the pulse by pulse protection is shown in
Figure 5.
The output power PDMOS transistor is split in two parallel PDMOS. The smallest one has a
resistor in series, RSENSE. The current is sensed through Rsense and if reaches the
threshold, the mirror is unbalanced and the PDMOS is switched off until the next falling edge
of the internal clock pulse.
Due to this reduction of the ON time, the output voltage decreases.
Since the minimum switch ON time (necessary to avoid false overcurrent signal) is not
enough to obtain a sufficiently low duty cycle at 500 kHz, the output current, in strong
overcurrent or short circuit conditions, could increase again. For this reason the switching
frequency is also reduced, so keeping the inductor current under its maximum threshold.
The frequency shifter (see Figure 4) depends on the feedback voltage. As the feedback
voltage decreases (due to the reduced duty cycle), the switching frequency decreases too.
9/16
A5970AD
Figure 5.
4.5
Current limitation circuitry
Error amplifier
The voltage error amplifier is the core of the loop regulation. It is a transconductance
operational amplifier whose non inverting input is connected to the internal voltage
reference (1.235 V), while the inverting input (FB) is connected to the external divider or
directly to the output voltage. The output (COMP) is connected to the external compensation
network.
The uncompensated error amplifier has the following characteristics:
Table 5.
Uncompensated error amplifier
Tranconductance
Low frequency gain
Minimum sink/source voltage
Output voltage swing
Input bias current
2300 μS
65 dB
1500 μA/300 μA
0.4 V/3.65 V
2.5 μA
Note:
The error amplifier output is compared with the oscillator sawtooth to perform PWM control.
4.6
PWM comparator and power stage
This block compares the oscillator sawtooth and the error amplifier output signals
generating the PWM signal for the driving stage. The power stage is a very critical block
cause it has to guarantee a correct turn on and turn OFF of the PDMOS. The turn ON of the
power element, or better, the rise time of the current at turn on, is a very critical parameter to
compromise.
At a first approach, it looks like the faster it is the rise time, the lower are the turn on losses.
But there is a limit introduced by the recovery time of the recirculation diode. In fact when the
current of the power element equals the inductor current, the diode turns off and the drain of
the power is free to go high. But during its recovery time, the diode can be considered as an
10/16
A5970AD
high value capacitor and this produces a very high peak current, responsible of many
problems:
●
Spikes on the device supply voltage that cause oscillations (and thus noise) due to the
board parasites.
●
Turn ON overcurrent causing a decrease of the efficiency and system reliability.
●
Big EMI problems.
●
Shorter freewheeling diode life.
The fall time of the current during the turn off is also critical. In fact it produces voltage
spikes (due to the parasites elements of the board) that increase the voltage drop across the
PDMOS.
In order to minimize all these problems, a new topology of driving circuit has been used and
its block diagram is shown in Figure 6.
The basic idea is to change the current levels used to turn on and off the power switch,
according with the PDMOS status and with the gate clamp status.
This circuitry allow to turn off and on quickly the power switch and to manage the above
question related to the freewheeling diode recovery time problem.
The gate clamp is necessary to avoid that Vgs of the internal switch goes higher than
Vgsmax. The ON/OFF control block avoids any cross conduction between the supply line
and ground.
Figure 6.
Driving circuitry
11/16
A5970AD
4.7
Inhibit function
The inhibit feature allows to put in stand-by mode the device. With INH pin higher than 2.2 V
the device is disabled and the power consumption is reduced to less than 100 μA. With INH
pin lower than 0.8 V, the device is enabled. If the INH pin is left floating, an internal pull up
ensures that the voltage at the pin reaches the inhibit threshold and the device is disabled.
The pin is also VCC compatible.
4.8
Thermal shutdown
The shutdown block generates a signal that turns off the power stage if the temperature of
the chip goes higher than a fixed internal threshold (150 °C). The sensing element of the
chip is very close to the PDMOS area, so ensuring an accurate and fast temperature
detection. An hysteresis of approximately 20 °C avoids that the devices turns on and off
continuously
12/16
A5970AD
5
Additional features and protections
5.1
Feedback disconnection
In case of feedback disconnection, the duty cycle increases versus the maximum allowed
value, bringing the output voltage close to the input supply. This condition could destroy the
load.
To avoid this dangerous condition, the device is turned off if the feedback pin remains
floating.
5.2
Output overvoltage protection
The overvoltage protection, OVP, is realized by using an internal comparator, which input is
connected to the feedback, that turns off the power stage when the OVP threshold is
reached. This threshold is typically 30 % higher than the feedback voltage.
When a voltage divider is requested for adjusting the output voltage (see test application
circuit), the OVP intervention will be set at:
Equation 1
R 1 + R2
V OVP = 1.3 × --------------------- × V FB
R2
Where R1 is the resistor connected between the output voltage and the feedback pin, while
R2 is between the feedback pin and ground.
5.3
Zero load
Due to the fact that the internal power is a PDMOS, no boostrap capacitor is required and
so, the device works properly also with no load at the output. In this condition it works in
burst mode, with random repetition rate of the burst.
13/16
A5970AD
6
Package mechanical data
In order to meet environmental requirements, ST offers these devices in ECOPACK®
packages. These packages have a lead-free second level interconnect. The category of
second level interconnect is marked on the package and on the inner box label, in
compliance with JEDEC Standard JESD97. The maximum ratings related to soldering
conditions are also marked on the inner box label. ECOPACK is an ST trademark.
ECOPACK specifications are available at: www.st.com
14/16
A5970AD
Table 6.
SO-8 mechanical data
mm
inch
Dim
Min
Typ
Max
Min
Typ
Max
A
1.35
1.75
0.053
0.069
A1
0.10
0.25
0.004
0.010
A2
1.10
1.65
0.043
0.065
B
0.33
0.51
0.013
0.020
C
0.19
0.25
0.007
0.010
D(1)
4.80
5.00
0.1890
0.197
E
3.80
4.00
0.15
0.157
e
1.27
0.050
H
5.80
6.20
0.228
0.244
h
0.25
0.50
0.010
0.020
L
0.40
1.27
0.016
0.050
k
0° (min), 8° (max)
ccc
Figure 7.
0.10
0.0039
Package dimensions
15/16
A5970AD
7
Revision history
7
Table 7.
Document revision history
Date
Revision
Changes
02-May-2008
1
Initial release
27-Aug-2008
2
Updated: Coverpage and Table 4 on page 5
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A5970AD
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