SGLS209 − NOVEMBER 2003 D PACKAGE (TOP VIEW) features D Qualification in Accordance With D D D D D D D D D AEC-Q100† Qualified for Automotive Applications Customer-Specific Configuration Control Can Be Supported Along With Major-Change Approval Low Distortion: 0.0003% at 1 khz Low Noise: 10 nV//Hz High Slew Rate: 25 V/µs Wide Gain-Bandwidth: 20 MHz Unity-Gain Stable Wide Supply Range: VS = ±4.5 to ±24 V Drives 600 W Loads † Contact factory for details. Q100 qualification data available on request. OUTPUT A −IN A +IN A V− 1 8 2 7 3 6 4 5 V+ OUTPUT B −IN B +IN B (8) V+ (+) (3, 5) (−) (2, 6) Distortion Rejection Circuitry* Output Stage* (1, 7) VO applications D D D D D D Professional Audio Equipment PCM DAC I/V Converter Spectral Analysis Equipment Active Filters Transducer Amplifier Data Acquisition (4) V− * Patents Granted: #5053718, 5019789 description The OPA2604 is a dual, FET-input operational amplifier designed for enhanced AC performance. Very low distortion, low noise and wide bandwidth provide superior performance in high quality audio and other applications requiring excellent dynamic performance. New circuit techniques and special laser trimming of dynamic circuit performance yield very low harmonic distortion. The result is an op amp with exceptional sound quality. The low-noise FET input of the OPA2604 provides wide dynamic range, even with high source impedance. Offset voltage is laser-trimmed to minimize the need for interstage coupling capacitors. The OPA2604 is available in a SO-8 surface-mount package, specified for the −40°C to +85°C temperature range. ORDERING INFORMATION TA PACKAGE‡ ORDERABLE PART NUMBER TOP-SIDE MARKING −40°C to 85°C SOIC - D Tape and reel OPA2604IDRQ1 2604Q1 ‡ Package drawings, standard packing quantities, thermal data, symbolization, and PCB design guidelines are available at www.ti.com/sc/package. Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. Copyright 2003, Texas Instruments Incorporated ! " #$%! " &$'(#! )!%* )$#!" # ! "&%##!" &% !+% !%" %," "!$%!" "!)) -!.* )$#! &#%""/ )%" ! %#%""(. #($)% !%"!/ (( &%!%"* POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 1 SGLS209 − NOVEMBER 2003 absolute maximum ratings over operating free-air temperature (unless otherwise noted)† Power supply voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±25 V Input voltage, VIN . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 〈V−) − 1 V to (V+) + 1 V Output short circuit to ground . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . Continuous Operating free-air temperature range, TA . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . −40°C to 100°C Storage temperature range, Tstg . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . −40°C to 125°C Package thermal impedance, θJA (see Note 1): D package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 90°C/W Lead temperature 1,6 mm (1/16 inch) from case for 3 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C Junction temperature, TJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150°C † Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. NOTES: 1. The package thermal impedance is calculated in accordance with JESD 51-7. recommended operating conditions MIN NOM MAX UNIT Operating voltage ±4.5 ±15 ±24 V Operating free-air temperature −40 85 °C 2 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 SGLS209 − NOVEMBER 2003 electrical characteristics, TA = 255C, VS = ±15 V (unless otherwise noted) PARAMETER TEST CONDITIONS MIN TYP MAX ±1 ±5 UNIT Offset Voltage Input offset voltage (VIO) Average drift Power supply rejection ratio (PSRR) VS = ±5 V to ±24 V 70 mV ±8 µV/°C 80 dB 100 pA ±4 pA Input Bias Current (See Note 1) Input bias current (IIB) Input offset current (IIO) VCM = 0 V VCM = 0 V Noise f = 10 Hz 25 f = 100 Hz 15 f = 1 kHz 11 f = 10 kHz 10 Voltage noise BW = 20 Hz to 20 kHz 1.5 Input bias current noise density f = 0.1 Hz to 20 kHz Input noise, voltage noise density nV/√Hz µVp-p fA/√Hz 6 Input Voltage Range Common-mode input voltage range (VICR) ±12 ±13 V 80 100 dB Input impedance, differential mode 1012 8 Ω pF Input impedance, common mode 1012 10 Ω pF 100 dB 20 MHz Common-mode rejection ratio (CMRR) VCM = ±12 V Input Impedance Open-loop Gain Open-loop voltage gain (AVOL) VO = ±10 V, RL = 1 kΩ 80 Frequency Response Gain bandwidth product G = 100 Slew rate 20 Vp-p, RL = 1 kΩ Settling time to 0.01% G = −1, 15 10 V step Settling time to 0.1% Total Harmonic Distortion + Noise (THD+N) G = 1, Channel separation f = 1 kHz, f = 1 kHz, VO = 3.5 Vrms, RL = 1 kΩ RL = 1 kΩ 25 V/µs 1.5 µs 1 µs 0.0003 % 142 dB Output Output voltage range (VOH, VOL) RL = 600 Ω Output current (IO) VO = ±12 V ±11 Output short circuit current (IOS) Open-loop output resistance ±12 V ±35 mA ±40 mA 25 Ω Power Supply Total current. both amplifiers (ICC) ±10.5 IO = 0 ±12 mA NOTE 1: Typical performance, measured fully warmed-up. POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 3 SGLS209 − NOVEMBER 2003 TYPICAL CHARACTERISTICS TOTAL HARMONIC DISTORTION + NOISE vs OUTPUT VOLTAGE TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY 1 THD + N (%) VO G = 100V/V 0.01 See ”Distortion Measurements” for description of test method. 1kΩ THD + N (%) VO = 3.5Vrms 1kΩ 0.1 0.1 Measurement BW = 80kHz See ”Distortion Measure− ments” for desription of test method. 0.01 f = 1kHz Measurement BW = 80kHz 0.001 G = 10V/V 0.001 G = 1V/V 0.0001 0.1 0.0001 20 100 1k 10k 20k 1 10 100 Output Voltage (Vp−p) Frequency (Hz) Figure 1 Figure 2 INPUT VOLTAGE AND CURRENT NOISE SPECTRAL DENSITY vs FREQUENCY OPEN−LOOP GAIN/PHASE vs FREQUENCY 0 120 1k 1k φ −90 60 40 −135 G 20 100 100 Voltage Noise 10 10 Current Noise (fA/ Hz) Voltage Gain (dB) −45 80 Phase Shift (Degrees) Voltage Noise (nV/ Hz) 100 −180 0 Current Noise −20 10 100 1k 10k 100k 1M 10M 1 10 100 Frequency (Hz) Input Bias Current 1nA 100 1nA 10 100 Input Offset Current 1 10 0 25 50 75 100 0.1 125 Input Bias Current (pA) 10nA 10nA −25 1nA Input Bias Current 1nA 10 Input Offset Current 10 −15 −10 −5 0 5 Common−Mode Voltage (V) Figure 5 Figure 6 POST OFFICE BOX 655303 100 100 Ambient Temperature (°C) 4 1 1M INPUT BIAS AND INPUT OFFSET CURRENT vs INPUT COMMON−MODE VOLTAGE Input Offset Current (pA) Input Bias Current (pA) 100nA −50 100k Figure 4 INPUT BIAS AND INPUT OFFSET CURRENT vs TEMPERATURE 1 −75 10k Frequency (Hz) Figure 3 10nA 1k • DALLAS, TEXAS 75265 10 1 15 Input Offset Current (pA) 1 1 SGLS209 − NOVEMBER 2003 TYPICAL CHARACTERISTICS COMMON−MODE REJECTION vs COMMON−MODE VOLTAGE INPUT BIAS CURRENT vs TIME FROM POWER TURN−ON 120 1nA Common−Mode Rejection (dB) Input Bias Current (pA) VS = ±24VDC VS = ±15VDC 100 VS = ±5VDC 10 1 2 3 4 100 90 80 −15 1 0 110 5 −10 −5 0 Figure 7 10 15 Figure 8 POWER SUPPLY AND COMMON−MODE REJECTION vs FREQUENCY AOL, PSR, AND CMR vs SUPPLY VOLTAGE 120 120 CMR 100 110 AOL, PSR, CMR (dB) PSR, CMR (dB) 5 Common−Mode Voltage (V) Time After Power Turn−On (min) 80 −PSR +PSR 60 40 CMR 100 AOL 90 80 20 PSR 0 10 70 100 1k 10k 100k 1M 10 5 10M 15 20 25 Supply Voltage (±VS) Frequency (Hz) Figure 9 Figure 10 GAIN−BANDWIDTH AND SLEW RATE vs TEMPERATURE GAIN−BANDWIDTH AND SLEW RATE vs SUPPLY VOLTAGE 28 28 33 30 29 Slew Rate 20 25 16 21 12 5 10 15 20 17 25 24 25 20 20 Gain−Bandwidth G = +100 16 15 12 −75 −50 −25 0 Slew Rate (V/us) Gain−Bandwidth G = +100 Gain−Bandwidth (MHz) 24 Slew Rate (V/us) Gain−Bandwidth (MHz) Slew Rate 25 50 75 100 10 125 Temperature (°C) Supply Voltage (±VS) Figure 11 Figure 12 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 5 SGLS209 − NOVEMBER 2003 TYPICAL CHARACTERISTICS CHANNEL SEPARATION vs FREQUENCY SETTLING TIME vs CLOSED−LOOP GAIN 160 5 VO = 10V Step RL = 1kΩ CL = 50pF RL = ∞ Channel Separation (dB) Settling Time (us) 4 3 0.01% 2 0.1% 1 140 RL = 1kΩ 120 100 VO = 20Vp−p A B RL Measured Output 80 0 −10 −1 −100 100 10 −1000 1k Figure 13 100k Figure 14 MAXIMUM OUTPUT VOLTAGE SWING vs FREQUENCY SUPPLY CURRENT vs TEMPERATURE 30 14 Total for Both Op Amps Supply Current (mA) VS = ± 15 V Output Voltage (Vp−p) 10k Frequency (Hz) Closed−Loop Gain (V/V) 20 10 0 VS = ±15VDC 12 VS = ±24VDC 10 VS = ±5VDC 8 6 10k 100k 1M 10M −50 −75 −25 Frequency (Hz) 0 25 50 75 100 125 Ambient Temperaturre (°C) Figure 15 Figure 16 SMALL−SIGNAL TRANSIENT RESPONSE LARGE−SIGNAL TRANSIENT RESPONSE +100 Output Voltage (mV) Output Voltage (V) +10 FPO Bleed to edge −10 0 6 5 10 −100 0 1 µs Time ( us) Time ( us) Figure 17 Figure 18 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 2 µs SGLS209 − NOVEMBER 2003 TYPICAL CHARACTERISTICS POWER DISSIPATION vs SUPPLY VOLTAGE SHORT−CIRCUIT CURRENT vs TEMPERATURE 1 60 Worst case sine wave RL = 600Ω (both channels) Power Dissipation (W) 50 40 30 0.8 Typical high−level music RL = 600Ω (both channels) 0.7 0.6 0.5 0.4 No signal or no load 0.3 0.2 0.1 20 −75 −50 −25 0 25 50 75 100 6 125 8 10 12 14 16 18 20 22 24 Supply Voltage, ±VS (V) Ambient Temperature (°C) Figure 19 Figure 20 MAXIMUM POWER DISSIPATION vs TEMPERATURE 1.4 Total Power Dissipation (W) Short−Circuit Current (mA) 0.9 ISC+ and ISC− θJ−A = 90°C/W Soldered to Circuit Board (see text) 1.2 1.0 0.8 0.6 Maximum Specified Operating Temperature 85°C 0.4 0.2 0 0 25 50 75 100 Ambient Temperature (°C) 125 150 Figure 21 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 7 SGLS209 − NOVEMBER 2003 APPLICATION INFORMATION The OPA2604 is unity-gain stable, making it easy to use in a wide range of circuitry. Applications with noisy or high impedance power supply lines may require decoupling capacitors close to the device pins. In most cases 1 µF tantalum capacitors are adequate. distortion measurements The distortion produced by the OPA2604 is below the measurement limit of virtually all commercially available equipment. A special test circuit, however, can be used to extend the measurement capabilities. Op amp distortion can be considered an internal error source which can be referred to the input. Figure 22 shows a circuit which causes the op amp distortion to be 101 times greater than normally produced by the op amp. The addition of R3 to the otherwise standard non-inverting amplifier configuration alters the feedback factor or noise gain of the circuit. The closed-loop gain is unchanged, but the feedback available for error correction is reduced by a factor of 101. This extends the measurement limit, including the effects of the signal-source purity, by a factor of 101. Note that the input signal and load applied to the op amp are the same as with conventional feedback without R3. Validity of this technique can be verified by duplicating measurements at high gain and/or high frequency where the distortion is within the measurement capability of the test equipment. Measurements for this data sheet were made with the Audio Precision System One which greatly simplifies such repetitive measurements. The measurement technique can, however, be performed with manual distortion measurement instruments. R1 R2 SIG. DIST. GAIN GAIN R3 R1 R2 R3 101 ∞ 5kΩ 50Ω 10 101 500Ω 5kΩ 500Ω 100 101 50Ω 5kΩ ∞ 1 12 VO = 10Vp−p (3.5Vrms) OPA2604 Generator Output Analyzer Input Audio Precision System One Analyzer* RL 1kΩ IBM PC or Compatible * Measurement BW = 80kHz Figure 22. Distortion Test Circuit capacitive loads The dynamic characteristics of the OPA2604 have been optimized for commonly encountered gains, loads and operating conditions. The combination of low closed-loop gain and capacitive load will decrease the phase margin and may lead to gain peaking or oscillations. Load capacitance reacts with the op amp’s open-loop output resistance to form an additional pole in the feedback loop. Figure 23 shows various circuits which preserve phase margin with capacitive load. Request Application Bulletin AB-028 for details of analysis techniques and applications circuits. For the unity-gain buffer, Figure a, stability is preserved by adding a phase-lead network, RC and CC. Voltage drop across RC will reduce output voltage swing with heavy loads. An alternate circuit, Figure b, does not limit the output with low load impedance. It provides a small amount of positive feed-back to reduce the net feedback factor. Input impedance of this circuit falls at high frequency as op amp gain rolloff reduces the bootstrap action on the compensation network. 8 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 SGLS209 − NOVEMBER 2003 Figures c and d show compensation techniques for noninverting amplifiers. Like the follower circuits, the circuit in Figure d eliminates voltage drop due to load current, but at the penalty of somewhat reduced input impedance at high frequency. Figures e and f show input lead compensation networks for inverting and difference amplifier configurations. POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 9 SGLS209 − NOVEMBER 2003 (a) (b) CC 820pF RC 12 12 eo OPA2604 ei 750Ω CL 5000pF CC 0.47uF CL 5000pF CC = eo OPA2604 R2 RC 2kΩ 10Ω ei 120 X 10−12 CL RC = CC = R2 4CL X 1010 − 1 CL X 103 RC (c) (d) R1 R2 R1 R2 10kΩ 10kΩ 2kΩ 2kΩ CC RC 20Ω 24pF eo OPA2604 ei 12 OPA2604 eo ei 25Ω CL 5000pF 50 CL R2 CC = CC 0.22uF RC 12 RC = CC = CL 5000pF R2 2CL X 1010 − (1 + R2/R1) CL X 103 RC (e) (f) R2 R1 R2 2kΩ 2kΩ e1 2kΩ R1 RC 20Ω ei 12 2kΩ 12 eo OPA2604 OPA2604 CC 0.22uF RC 20Ω CL 5000pF CC 0.22uF R3 R4 2kΩ 2kΩ e2 RC = R2 2CL X 1010 − (1 + R2/R1) R2 RC = CC = CL X 103 RC CC = 2CL X 1010 − (1 + R2/R1) CL X 103 RC Figure 23. Driving Large Capacitive Loads 10 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 eo CL 5000pF SGLS209 − NOVEMBER 2003 noise performance Op amp noise is described by two parameters − noise voltage and noise current. The voltage noise determines the noise performance with low source impedance. Low noise bipolar-input op amps such as the OPA27 and OPA37 provide very low voltage noise. But if source impedance is greater than a few thousand ohms, the current noise of bipolar-input op amps react with the source impedance and will dominate. At a few thousand ohms source impedance and above, the OPA2604 will generally provide lower noise. power dissipation The OPA2604 is capable of driving 600 Ω loads with power supply voltages up to ±24 V. Internal power dissipation is increased when operating at high power supply voltage. The typical performance curve, Power Dissipation vs Power Supply Voltage, shows quiescent dissipation (no signal or no load) as well as dissipation with a worst case continuous sine wave. Continuous high-level music signals typically produce dissipation significantly less than worst case sine waves. Copper leadframe construction used in the OPA2604 improves heat dissipation compared to conventional plastic packages. To achieve best heat dissipation, solder the device directly to the circuit board and use wide circuit board traces. output current limit Output current is limited by internal circuitry to approximately ±40 mA at 25°C. The limit current decreases with increasing temperature as shown in the typical curves. R4 22kΩ C3 R1 R2 R3 2.7kΩ 22kΩ 10kΩ VIN 100pF 12 C1 3000pF VO OPA2604 C2 2000pF fp = 20kHz Figure 24. Three-Pole Low-Pass Filter POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 11 SGLS209 − NOVEMBER 2003 12 R1 R5 VO OPA2604 VIN 6.04kΩ 2kΩ R2 4.02kΩ C3 1000pF R2 4.02kΩ Low−pass 3−pole Butterworth f−3dB = 40kHz 12 OPA2604 12 OPA2604 C1 1000pF R4 5.36kΩ See Application Bulletin AB−026 for information on GIC filters. C2 1000pF Figure 25. Three-Pole Generalized Immittance Converter (GIC) Low-Pass Filter C1* I−Out DAC R1 C2 2200pF 2kΩ 12 R2 R3 COUT 2.94kΩ 21kΩ OPA2604 C3 470pF ~ * C1 = COUT 2π R1 fc R1 = Feedback resistance = 2kΩ fc = Crossover frequency = 8MHz Figure 26. DAC I/V Amplifier and Low-Pass Filter 12 VO OPA2604 12 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 Low−pass 2−pole Butterworth f−3dB = 20kHz SGLS209 − NOVEMBER 2003 10kΩ 12 7.87kΩ 10kΩ OPA2604 − 12 100pF VIN VO G=1 OPA2604 + 12 7.87kΩ 100kHz Input Filter OPA2604 10kΩ 10kΩ Figure 27. Differential Amplifier with Low-Pass Filter 100Ω 10kΩ COUT * C1 ≈ 2π Rf fc Rf = Internal feedback resistance = 1.5kΩ fc = Crossover frequency = 8MHz G = 101 (40dB) 12 10 OPA2604 5 PCM63 20−bit 6 D/A 9 Converter Piezoelectric Transducer 1MΩ* C1* 12 OPA2604 VO = ±3Vp To low−pass filter. * Provides input bias current return path. Figure 29. Digital Audio DAC I-V Amplifier Figure 28. High Impedance Amplifier 1/2 OPA2604 A2 I2 R4 1/2 OPA2604 R3 51Ω 51Ω A1 VIN IL = I1 + I2 R2 i1 VOUT Load R1 VOUT = VIN (1 + R2/R1) Figure 30. Using the Dual OPA2604 Op Amp to Double the Output Current to a Load POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 13 PACKAGE OPTION ADDENDUM www.ti.com 18-Sep-2008 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Drawing OPA2604IDRQ1 OBSOLETE SOIC D Pins Package Eco Plan (2) Qty 8 TBD Lead/Ball Finish Call TI MSL Peak Temp (3) Call TI (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. 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