Fixed Frequency Current Mode Controller for Flyback Converters

NCP1235
Product Preview
Fixed Frequency Current
Mode Controller for Flyback
Converters
The NCP1235 is a new fixed−frequency current−mode controller
featuring Dynamic Self−Supply (DSS). This device is pin−to−pin
compatible with the previous NCP12xx families.
The DSS function greatly simplifies the design of the auxiliary
supply and the VCC capacitor by activating the internal startup current
source to supply the controller during transients.
Due to frequency foldback, the controller exhibits excellent
efficiency in light load condition while still achieving very low
standby power consumption. Internal frequency jittering, ramp
compensation, and a versatile latch input make this controller an
excellent candidate for converters where components cost is the key
constraints.
In addition, the controller includes a new high voltage circuitry that
combines a start−up current source and a brown−out detector able to
sense the input voltage either from the rectified ac line or the dc
filtered bulk voltage. The high voltage sensing circuitry is used for the
overpower protection purposes as well. Overpower protection,
overload protection, and next protective features increases safety level
of the final application.
Finally, due to a careful design, the precision of critical parameters
is well controlled over the entire temperature range (−40°C to
+125°C).
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MARKING
DIAGRAM
8
35A065
ALYWX
G
SOIC−7
CASE 751U
1
35A065 = Specific Device Code
A
= Assembly Location
L
= Wafer Lot
Y
= Year
W
= Work Week
G
= Pb−Free Package
PIN CONNECTIONS
Latch 1
8
HV
6
VCC
5
DRV
FB 2
CS 3
GND
4
(Top View)
Features
• Fixed−Frequency Current−Mode Operation with Built−In Ramp
•
•
•
•
•
•
•
ORDERING INFORMATION
Compensation
See detailed ordering and shipping information in the package
65 kHz Oscillator Frequency
dimensions section on page 33 of this data sheet.
Frequency Foldback then Skip Mode for Maximized Performance in
Light Load and Standby Conditions
Timer−Based Overload Protection then Device is Latched
High−voltage Current Source with Brown−Out
• Internal Thermal Shutdown
detection and Dynamic Self−Supply, Simplifying the
• Pin−to−Pin Compatible with the Existing NCP12xx
Design of the VCC Capacitor
Series
Frequency Modulation for Softened EMI Signature,
• These Devices are Pb−Free, Halogen Free/BFR Free
including during Frequency Foldback mode
and are RoHS Compliant
Adjustable Overpower Compensation
Typical Applications
Latch−off Input for Severe Fault Conditions, Allowing
• AC−DC Adapters for Notebooks, LCD, and Printers
Direct Connection of an NTC for Overtemperature
• Offline Battery Chargers
Protection (OTP)
• Consumer Electronic Power Supplies
VCC Operation up to 28 V, with Overvoltage Detection
• Auxiliary/Housekeeping Power Supplies
$500 mA Peak Source / Sink Current Drive Capability
•
•
• 4.0 ms Soft−Start
This document contains information on a product under development. ON Semiconductor
reserves the right to change or discontinue this product without notice.
© Semiconductor Components Industries, LLC, 2015
January, 2015 − Rev. P0
1
Publication Order Number:
NCP1235/D
NCP1235
TYPICAL APPLICATION EXAMPLE
VOUT
VIN
(dc)
LATCH
FB
HV
NCP1236
CS
VCC
GND
DRV
Figure 1. Flyback Converter Application Using the NCP1235
OPTIONS
Part
Option
Frequency
OCP Fault
Fault Timer
Autorecovery
Timer
NCP1235
A
65 kHz
Latched
128 ms
16 ms
PIN FUNCTION DESCRIPTION
Pin No
Pin Name
Function
1
LATCH
Latch−Off Input
2
FB
Feedback
3
CS
Current Sense
4
GND
5
DRV
Drive output
6
VCC
VCC input
8
HV
High−voltage pin
Pin Description
Pull the pin up or down to latch−off the controller. An internal current source
allows the direct connection of an NTC for over temperature detection
An optocoupler collector to ground controls the output regulation.
This Input senses the Primary Current for current−mode operation, and Offers
an overpower compensation adjustment.
IC Ground
Drives external MOSFET
This supply pin accepts up to 28 Vdc, with overvoltage detection
Connects to the bulk capacitor or the rectified AC line to perform the functions
of Start−up Current Source, Dynamic Self−Supply and brown−out detection
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2
NCP1235
SIMPLIFIED INTERNAL BLOCK SCHEMATIC
+
−
+
INTC
Latch
+
BO
HV sample
HV dc
blanking
tLatch(OVP)
VOVP
INTC
Brown−out
−
+
VDD
VCC OVP
−
+
HV
TSD
TSD
blanking
Dual HV
start−up
current source
tLatch(OTP)
1 kW
S
VOTP
Q
Latch
R
Vclamp
TSD HV current
Reset
UVLO
VCC
VDD
management
Start
OVP
Reset
UVLO
VDD
Soft−start
end
IC Start
VCC OVP
Brown−out
Reset
VCC
VFB(ref)
−
+
+
Vskip
20 kW
/5
slope
comp.
FB
HV sample
PWM
+
−
V to I
IOPC = 0.5m x
(VHV − 125)
Jitter
Sawtooth
Soft−start
+
−
Stop
Foldback
−
+
Oscillator
+
Soft−start ramp Start
t
End SSTART Reset
VFB(OPC)
DCMAX
IC Start
IC Stop
S
Soft−start end
blanking
tLEB
Clamp
DMAX
Q
R
CS
+
blanking
tBCS
DRV
+
−
ILIMIT
VILIM
IC stop
GND
UVLO
ILIMIT
DMAX
S
Q
R
+
Fault Flag
Brown−out
Protection
Mode
release
+
−
For
Autorecovery
protection
mode only
VCS(stop)
timer
PWM
tfault
timer
tautorec
Fault
Brown−out
Reset
Figure 2. Simplified Internal Block Schematic
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3
Latch
TSD
NCP1235
MAXIMUM RATINGS
Symbol
Value
Unit
Supply Pin (pin 6) (Note 2)
Voltage range
Current range
Rating
VCCMAX
ICCMAX
–0.3 to 28
$30
V
mA
High Voltage Pin (pin 8) (Note 2)
Voltage range
Current range
VHVMAX
IHVMAX
–0.3 to 500
$20
V
mA
Driver Pin (pin 5) (Note 2)
Voltage range
Current range
VDRVMAX
IDRVMAX
–0.3 to 20
$1000
V
mA
VMAX
IMAX
–0.3 to 10
$10
V
mA
All other pins (Note 2)
Voltage range
Current range
Thermal Resistance SOIC−7
Junction−to−Air, low conductivity PCB (Note 3)
Junction−to−Air, medium conductivity PCB (Note 4)
Junction−to−Air, high conductivity PCB (Note 5)
RθJ−A
°C/W
162
147
115
°C
Temperature Range
Operating Junction Temperature
Storage Temperature Range
TJMAX
TSTRGMAX
ESD Capability (Note 1)
Human Body Model (All pins except HV)
Machine Model
−40 to +150
−60 to +150
V
2000
200
Stresses exceeding those listed in the Maximum Ratings table may damage the device. If any of these limits are exceeded, device functionality
should not be assumed, damage may occur and reliability may be affected.
1. This device series contains ESD protection and exceeds the following tests:
Human Body Model 2000 V per JEDEC standard JESD22, Method A114E
Machine Model Method 200 V per JEDEC standard JESD22, Method A115A
2. This device contains latch−up protection and exceeds 100 mA per JEDEC Standard JESD78
3. As mounted on a 80 x 100 x 1.5 mm FR4 substrate with a single layer of 50 mm2 of 2 oz copper traces and heat spreading area. As specified
for a JEDEC 51−1 conductivity test PCB. Test conditions were under natural convection or zero air flow.
4. As mounted on a 80 x 100 x 1.5 mm FR4 substrate with a single layer of 100 mm2 of 2 oz copper traces and heat spreading area. As specified
for a JEDEC 51−2 conductivity test PCB. Test conditions were under natural convection or zero air flow.
5. As mounted on a 80 x 100 x 1.5 mm FR4 substrate with a single layer of 650 mm2 of 2 oz copper traces and heat spreading area. As specified
for a JEDEC 51−3 conductivity test PCB. Test conditions were under natural convection or zero air flow.
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4
NCP1235
ELECTRICAL CHARACTERISTICS
(For typical values TJ = 25°C, for min/max values TJ = −40°C to +125°C, VHV = 125 V, VCC = 11 V unless otherwise noted)
Characteristics
Test Condition
Symbol
Min
Typ
Max
Unit
VHV(min)
−
30
60
V
Istart1
Istart2
0.2
3
0.5
6
0.8
9
mA
Istart(off)
−
25
50
mA
Turn−on threshold level, VCC
going up
HV current source stop threshold
VCC(on)
11.0
12.0
13.0
V
HV current source restart threshold
VCC(min)
9.5
10.5
11.5
V
Turn−off threshold
VCC(off)
8.5
9.5
10.5
V
HIGH VOLTAGE CURRENT SOURCE
Minimum voltage for current
source operation
Current flowing out of VCC pin
VCC = 0 V
VCC = VCC(on) − 0.5 V
Off−state leakage current
VHV = 500 V
SUPPLY
Overvoltage threshold
VCC(ovp)
25
26.5
28
V
Blanking duration on VCC(off) and
VCC(ovp) detection (Note 7)
tVCC(blank)
7
10
13
ms
VCC decreasing level at which
the internal logic resets
VCC(reset)
3.6
5.0
6.0
V
VCC level for ISTART1 to ISTART2
transition
VCC(inhibit)
0.4
1.0
1.6
V
ICC1
ICC2
ICC3
ICC4
1.2
1.9
0.67
0.4
1.8
2.5
0.9
0.7
2.2
3.2
1.13
1.0
mA
VHV(start)
VHV(stop)
92
79
107
92
122
105
V
tHV
47
68
90
ms
Oscillator frequency
fOSC
60
92
65
100
70
108
kHz
Maximum duty cycle
DMAX
75
80
85
%
Frequency jittering amplitude, in
percentage of FOSC
Ajitter
−
±10
−
%
Frequency jittering modulation
frequency
Fjitter
85
125
165
Hz
Internal current consumption
(Note 6)
DRV open, VFB = 3 V
Cdrv = 1 nF, VFB = 3 V,
Off mode (skip or before start−up)
Fault mode (fault or latch)
BROWN−OUT
Brown−Out thresholds
VHV going up
VHV going down
Timer duration for line cycle
drop−out
OSCILLATOR
OUTPUT DRIVER
Rise time, 10% to 90 % of VCC
VCC = VCC(min) + 0.2 V, CDRV = 1 nF
trise
−
40
70
ns
Fall time, 90% to 10 % of VCC
VCC = VCC(min) + 0.2 V, CDRV = 1 nF
tfall
−
40
70
ns
Current capability
VCC = VCC(min) + 0.2 V, CDRV = 1 nF
DRV high, VDRV = 0 V
DRV low, VDRV = VCC
IDRV(source)
IDRV(sink)
−
−
500
500
−
−
mA
Clamping voltage (maximum
gate voltage)
VCC = VCCmax – 0.2 V, DRV high, RDRV
= 33 kW, Cload = 220 pF
VDRV(clamp)
11
13.5
16
V
High−state voltage drop
VCC = VCC(min) + 0.2 V, RDRV = 33 kW,
DRV high
VDRV(drop)
−
−
1
V
6. Internal supply current only, current in FB pin not included (current flowing in GND pin only).
7. Guaranteed by design.
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5
NCP1235
ELECTRICAL CHARACTERISTICS (continued)
(For typical values TJ = 25°C, for min/max values TJ = −40°C to +125°C, VHV = 125 V, VCC = 11 V unless otherwise noted)
Characteristics
Test Condition
Symbol
Min
Typ
Max
Unit
CURRENT SENSE
Input Bias Current
VCS = 0.7 V
Ibias
−
0.02
−
mA
Maximum internal current
setpoint
VFB > 3.5 V
VILIM
0.66
0.7
0.74
V
Propagation delay from VIlimit
detection to DRV off
VCS = VILIM
tdelay
−
80
110
ns
tLEB
190
250
310
ns
VCS(stop)
0.95
1.05
1.15
V
Leading Edge Blanking Duration
for VCS(stop)
tBCS
90
120
150
ns
Slope of the compensation ramp
Scomp(65kHz)
−26
−32.5
−39
mV /
ms
tSSTART
12
16
22
ms
KOPC
−
0.54
−
mA / V
Leading Edge Blanking Duration
for VILIM
Threshold for immediate fault
protection activation
Soft−start duration
From 1st pulse to VCS = VILIM
OVERPOWER COMPENSATION
VHV to IOPC conversion ratio
Current flowing out of CS pin
VHV = 125 V
VHV = 162 V
VHV = 325 V
VHV = 365 V
IOPC(125)
IOPC(162)
IOPC(325)
IOPC(365)
−
−
−
105
0
20
110
130
−
−
−
150
mA
FB voltage above which IOPC is
applied
VHV = 365 V
VFB(OPCF)
2.12
2.35
2.58
V
FB voltage below which is no
IOPC applied
VHV = 365 V
VFB(OPCE)
−
2.15
−
V
tWD(OPC)
−
32
−
ms
RFB(up)
15
20
25
kW
VFB to internal current setpoint
division ratio
KFB
4.7
5
5.3
−
Internal pull−up voltage on the
FB pin
VFB(ref)
4.3
5
5.7
V
Watchdog timer for dc operation
FEEDBACK
Internal pull−up resistor
TJ = 25°C
OVERCURRENT PROTECTION
Fault timer duration
From CS reaching VILIMIT to DRV stop
tfault
98
128
168
ms
Fault timer duration (for the C
version only)
From CS reaching VILIMIT to DRV stop
tfault
16
32
48
ms
Autorecovery mode latch−off
time duration
tautorec
0.85
1.00
1.35
s
Autorecovery mode latch−off
time duration (for the C version
only)
tautorec
1.0
1.5
2.0
s
VFB(foldS)
1.8
2.0
2.2
V
FREQUENCY FOLDBACK
Feedback voltage threshold
below which frequency foldback
starts
6. Internal supply current only, current in FB pin not included (current flowing in GND pin only).
7. Guaranteed by design.
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6
NCP1235
ELECTRICAL CHARACTERISTICS (continued)
(For typical values TJ = 25°C, for min/max values TJ = −40°C to +125°C, VHV = 125 V, VCC = 11 V unless otherwise noted)
Characteristics
Test Condition
Symbol
Min
Typ
Max
Unit
VFB(foldE)
1.22
1.35
1.48
V
VFB = Vskip(in) + 0.2
fOSC(min)
22
27
32
kHz
VFB going down
VFB going up
Vskip(in)
Vskip(out)
0.63
0.72
0.7
0.80
0.77
0.88
V
High threshold
VLatch going up
VOVP
2.35
2.5
2.65
V
Low threshold
VLatch going down
VOTP
0.76
0.8
0.84
V
Current source for direct NTC
connection
During normal operation
During soft−start
VLatch = 0 V
FREQUENCY FOLDBACK
Feedback voltage threshold
below which frequency foldback
is complete
Minimum switching frequency
SKIP−CYCLE MODE
Feedback voltage thresholds for
skip mode
LATCH−OFF INPUT
mA
INTC
INTC(SSTART)
65
130
95
190
105
210
Blanking duration on high latch
detection
tLatch(OVP)
35
50
70
ms
Blanking duration on low latch
detection
tLatch(OTP)
−
350
−
ms
Vclamp0(Latch)
Vclamp1(Latch)
1.0
2.0
1.2
2.4
1.4
3.0
V
TTSD
135
150
165
°C
TTSD(HYS)
20
30
40
°C
Clamping voltage
ILatch = 0 mA
ILatch = 1 mA
TEMPERATURE SHUTDOWN
Temperature shutdown (Note 7)
TJ going up
Temperature shutdown
hysteresis (Note 7)
TJ going down
6. Internal supply current only, current in FB pin not included (current flowing in GND pin only).
7. Guaranteed by design.
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7
NCP1235
TYPICAL PERFORMANCE CHARACTERISTICS
40.00
35
38.00
30
36.00
25
Istart(off) (V)
VHV(min) (V)
34.00
32.00
30.00
28.00
26.00
20
15
10
24.00
5
22.00
20.00
−50
−25
0
25
50
75
TEMPERATURE (°C)
100
0
−50
125
120
105
115
100
110
95
105
100
95
25
50
75
TEMPERATURE (°C)
100
125
90
85
80
90
−50
−25
0
25
50
75
100
125
75
−50
0
25
50
75
100
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 6. Brown−Out Device Stop Threshold
VHV(stop)
0.75
1.15
0.74
1.13
0.73
1.11
0.72
1.09
0.71
0.70
0.69
1.05
1.03
1.01
0.67
0.99
0.66
0.97
−25
0
25
50
75
100
125
0.95
−50
−25
0
25
50
75
100
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 7. Maximum Internal Current Setpoint
VILIM
Figure 8. Threshold for Immediate Fault
Protection Activation VCS(stop)
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8
125
1.07
0.68
0.65
−50
−25
Figure 5. Brown−out Device Start Threshold
VHV(start)
VCS(stop) (V)
VILIM (V)
0
Figure 4. Off−State Leakage Current Istart(off)
VHV(stop) (V)
VHV(start) (V)
Figure 3. Minimum Current Source Operation
VHV(min)
−25
125
NCP1235
TYPICAL PERFORMANCE CHARACTERISTICS
300
110
290
100
280
270
tLEB (ns)
tdelay (ns)
90
80
70
260
250
240
230
60
220
50
210
40
−50
−25
0
25
50
75
100
200
−50
125
−25
0
TEMPERATURE (°C)
25
50
75
100
125
TEMPERATURE (°C)
Figure 9. Propagation Delay tdelay
Figure 10. Leading Edge Blanking Duration
tLEB
24
5.30
23
5.20
5.10
VFB(ref) (V)
21
20
19
18
5.00
4.90
4.80
17
4.70
16
15
−50
−25
0
25
50
75
TEMPERATURE (°C)
100
4.60
−50
125
Figure 11. FB Pin Internal Pull−up Resistor
RFB(up)
−25
0
25
50
75
TEMPERATURE (°C)
69
68
67
66
65
64
63
62
61
60
−50
−25
0
100
Figure 12. FB Pin Open Voltage VFB(ref)
70
fOSC (kHz)
RFB(up) (kW)
22
25
50
75
TEMPERATURE (°C)
100
Figure 13. Oscillator Frequency fOSC
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9
125
125
NCP1235
TYPICAL PERFORMANCE CHARACTERISTICS
85
2.20
84
2.15
83
2.10
VFB(foldS) (V)
DMAX (%)
82
81
80
79
78
2.00
1.95
1.90
77
1.85
76
75
−50
2.05
−25
0
25
50
75
TEMPERATURE (°C)
100
1.80
−50
125
1.50
0.77
1.45
0.75
50
75
100
125
0.73
1.40
Vskip(in) (V)
VFB(foldE) (V)
25
Figure 15. FB Pin Voltage Below Which
Frequency Foldback Starts VFB(foldS)
1.35
1.30
0.71
0.69
0.67
1.25
0.65
−25
0
25
50
75
100
0.63
−50
125
−25
0
25
50
75
100
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 16. FB Pin Voltage Below Which
Frequency Foldback is Complete VFB(foldE)
Figure 17. FB Pin Skip−in Level Vskip(in)
0.88
30
0.86
29
125
28
fOSC(min) (kHz)
0.84
Vskip(out) (V)
0
TEMPERATURE (°C)
Figure 14. Maximum Duty Cycle DMAX
1.20
−50
−25
0.82
0.80
0.78
0.76
27
26
25
24
23
22
0.74
0.72
−50
21
20
−25
0
25
50
75
100
125
−50
TEMPERATURE (°C)
−25
0
25
50
75
100
TEMPERATURE (°C)
Figure 19. Minimum Switching Frequency
fOSC(min)
Figure 18. FB Pin Skip−Out Level Vskip(out)
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10
125
NCP1235
TYPICAL PERFORMANCE CHARACTERISTICS
2.60
150
2.55
145
2.50
2.45
VFB(OPCF) (V)
IOPC(365) (mA)
140
135
130
125
2.40
2.35
2.30
2.25
120
2.20
115
2.15
110
−50
−25
0
25
50
75
100
125
2.10
−50
−25
0
TEMPERATURE (°C)
25
50
75
TEMPERATURE (°C)
100
125
Figure 21. FB Pin Level VFB(OPCF) Above
Which is the Overpower Compensation
Applied
Figure 20. Maximum Overpower
Compensating Current IOPC(365) Flowing Out
of CS Pin
2.65
2.40
2.35
2.60
2.30
2.55
2.20
VOVP (V)
VFB(OPCE) (V)
2.25
2.15
2.10
2.50
2.45
2.05
2.00
2.40
1.95
2.35
1.90
−50
−25
0
25
50
75
TEMPERATURE (°C)
100
−50
125
Figure 22. FB Pin Level VFB(OPCE) Below
Which is No Overpower Compensation
Applied
0
25
50
75
TEMPERATURE (°C)
100
125
Figure 23. Latch Pin High Threshold VOVP
0.85
1.34
0.84
1.32
0.83
1.30
Vclamp0 (V)
0.82
VOTP (V)
−25
0.81
0.80
0.79
0.78
1.28
1.26
1.24
1.22
0.77
1.20
0.76
1.18
0.75
−50
−25
0
25
50
75
TEMPERATURE (°C)
100
125
−50
−25
0
25
50
75
TEMPERATURE (°C)
100
Figure 25. Latch Pin Open Voltage Vclamp0
Figure 24. Latch Pin Low Threshold VOTP
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11
125
NCP1235
110
2.70
105
2.60
100
2.50
95
INTC (mA)
2.80
2.40
2.30
90
85
2.20
80
2.10
75
2.00
−50
−25
0
25
50
75
TEMPERATURE (°C)
100
125
70
−50
−25
0
25
210
200
190
180
170
160
150
−25
75
100
Figure 27. Current INTC Sourced from the
Latch Pin, Allowing Direct NTC Connection
220
140
−50
50
TEMPERATURE (°C)
Figure 26. Latch Pin Voltage Vclamp1 (Latch−off
Pin is Sinking 1 mA)
INTC(SSTART) (mA)
Vclamp1 (V)
TYPICAL PERFORMANCE CHARACTERISTICS
0
25
50
75
100
TEMPERATURE (°C)
Figure 28. Current INTC(SSTART) Sourced from
the Latch Pin, During Soft−Start
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12
125
125
NCP1235
APPLICATION INFORMATION
Introduction
The NCP1235 includes all necessary features to build a safe
and efficient power supply based on a fixed−frequency
flyback converter. It is particularly well suited for
applications where low part count is a key parameter,
without sacrificing safety.
• Current−Mode Operation with slope compensation:
The primary peak current is permanently controlled by
the FB voltage, ensuring maximum safety: the DRV
turn−off event is dictated by the peak current setpoint.
It also ensures that the frequency response of the
system stays a first order if in DCM, which eases the
design of the FB loop. The controller can be also used
in CCM applications with a wide input voltage range
thanks to its fixed ramp compensation that prevents the
appearance of sub−harmonic oscillations.
• Fixed−Frequency Oscillator with Jittering: The
NCP1235 is available in different frequency options to
fit any application. The internal oscillator features a
low−frequency jittering that helps passing the EMI
limits by spreading out the energy content of frequency
peaks in quasi−peak and average mode of
measurement.
• Latched / Autorecovery Timer−Based Overload
Protection: The overload protection depends only on
the FB signal, making it able to work with any
transformer, even with very poor coupling or high
leakage inductance. When the fault timer elapses the
device can be permanently latched in version A or the
latch can be reset by an autorecovery restart of the
device in version B. The power supply has to be
stopped then restarted in order to resume operation,
even if the overload condition disapears, in case of
usage the A version of the NCP1235. The fault timer
duration is internally fixed. The controller also latches
off if the voltage on the CS pin reaches 1.5 times the
maximum internal setpoint (allowing to detect winding
short−circuits), with the same modes of releasing the
latch in A or B version.
• High Voltage Start−Up Current Source with
Brown−Out Detection: Due to ON Semiconductor’s
Very High Voltage technology, the NCP1235 can be
directly connected to the high input voltage. The
start−up current source ensures a clean start−up and the
Dynamic Self−Supply (DSS) restarting the start−up
current source to supply the controller if the VCC
•
•
•
•
•
•
•
voltage transiently drops. The high voltage pin also
features a high−voltage sensing circuitry, which is able
to turn the controller off if the input voltage is too low
(brown−out condition). This protection works either
with a DC input voltage or a rectified AC input voltage,
and is independent of the high voltage ripple.
Adjustable Overpower Compensation: The high
input voltage sensed on the HV pin is converted into a
current to build on the current sense voltage an offset
proportional to the input voltage. By choosing the value
of the resistor in series with the CS pin, the amount of
compensation can be adjusted to the application.
Frequency foldback then skip mode for light load
operation: In order to ensure a high efficiency under all
load conditions, the NCP1235 implements a frequency
foldback for light load condition and a skip mode for
extremely low load condition. The switching frequency
is decreased down to 27 kHz to reduce switching
losses.
Extended VCC range: The NCP1235 accepts a supply
voltage as high as 28 V, with an overvoltage threshold
VCC(ovp) (typically 26.5 V) that latches the controller
off.
Clamped Driver Stage: Despite the high maximum
supply voltage, the voltage on DRV pin is safely
clamped below 16 V, allowing the use of any standard
MOSFET, and reducing the current consumption of the
controller.
Dual Latch−off Input: The NCP1235 can be latched
off by 2 ways: The voltage increase applied to its Latch
pin (typically an overvoltage) or by a decrease this
voltage. Thanks to the internal precise pull−up current
source a NTC can be directly connected to the latch pin.
This NTC will provide an overtemperature protection
by decreasing its resistance and consequently the
voltage at Latch pin,
Soft−Start: At every start−up the peak current is
gradually increased during 4.0 ms to minimize the
stress on power components.
Temperature Shutdown: The NCP1235 is internally
protected against self−overheating: if the die
temperature is too high, the controller shuts all
circuitries down (including the HV start−up current
source), allowing the silicon to cool down before
attempting to restart. This ensures a safe behavior in
case of failure.
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NCP1235
Typical Operation
• Start−up: The HV start−up current source ensures the
•
•
•
charging of the VCC capacitor up to the start−up
threshold VCC(on), until the input voltage is high
enough (above VHV(start)) to allow the switching to
start. The controller then delivers pulses, starting with a
soft−start period tSSTART during which the peak current
linearly increases before the current−mode control takes
over. During the soft−start period, the low level latch is
ignored, and the latch current is double, to ensure a fast
pre−charge of the Latch pin decoupling capacitor.
Normal operation: As long as the feedback voltage is
within the regulation range and VCC is maintained
above VCC(min), the NCP1235 runs at a fixed frequency
(with jittering) in current−mode control. The peak
current (sensed on the CS pin) is set by the voltage on
the FB pin. Fixed ramp compensation is applied
internally to prevent sub−harmonic oscillations from
occurring.
Light load operation: When the FB voltage decreases
below VFB(foldS), typically corresponding to a load of
33 % of the maximum load (for a DCM design), the
switching frequency starts to decrease down to
fOSC(min). By lowering the switching losses, this feature
helps to improve the efficiency in light load conditions.
The frequency jittering is enabled in light load
operation as well.
No load operation: When the FB voltage decreases
below Vskip(in), typically corresponding to a load of 2
% of the maximum load, the controller enters skip
mode. By completely stopping the switching while the
feedback voltage is below Vskip(out), the losses are
•
•
•
further reduced. This allows minimizing the power
dissipation under extremely low load conditions. As the
skip mode is entered at very light loads, for which the
peak current is very small, there is no risk of audible
noise. VCC can be maintained between VCC(on) and
VCC(min) by the DSS, if the auxiliary winding does not
provide sufficient level of VCC voltage under this
condition.
Overload: The NCP1235 features timer−based
overload detection, solely dependent on the feedback
information: as soon as the internal peak current
setpoint hits the VILIM clamp, an internal timer starts to
count. When the timer elapses, the controller stops and
enter the protection mode, autorecovery for the B
version (the controller initiates a new start−up after
tautorec elapses), or latched for the A version (the latch
is released if a brown−out event occurs or VCC is reset).
Brown−out: The NCP1235 features a true AC line
monitoring circuitry. It includes a minimum start−up
threshold and an autorecovery brown−out protection;
both of them independent of the ripple on the input
voltage. It can even work with an unfiltered, rectified
AC input. The thresholds are fixed, but they are
designed to fit most of the standard AC−DC conversion
applications.
Latch−off: When the Latch input is pulled up (typically
by an over−voltage condition), or pulled down
(typically by an over−temperature condition, using the
provided current source with an NTC), the controller
latches off. A voltage higher than VCC(ovp) on the VCC
pin has the same effect. The latch is released when a
brown−out condition occurs, or when the VCC is reset.
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NCP1235
DETAILED DESCRIPTION
High−Voltage Current Source with Built−in Brown−out
Detection
The NCP1235 HV pin can be connected either to the
rectified bulk voltage, or to the ac line through a rectifier.
Start−up
HV
Istart
TSD
Control
IC Start
VCC
+
−
+
VCC(on)
R
Q
S
−
+
+
VCC(min)
blanking
−
+
+
UVLO
tUVLO(blank)
VCC(off )
−
+
+
Reset
VCC(reset)
Figure 29. HV Start−up Current Source Functional Schematic
condition, otherwise the power dissipation on the die would
be too much. As a result, an auxiliary voltage source is
needed to supply VCC during normal operation.
The DSS is useful to keep the controller alive when no
switching pulses are delivered, e.g. in brown−out condition,
or to prevent the controller from stopping during load
transients when the VCC might drop.
If the voltage increases above the overvoltage protection
threshold VCC(ovp), the controller is latched off.
At start−up, the current source turns on when the voltage
on the HV pin is higher than VHV(min), and turns off when
VCC reaches VCC(on), then turns on again when VCC reaches
VCC(min), until the input voltage is high enough to ensure a
proper start−up, i.e. when VHV reaches VHV(start). The
controller actually starts the next time VCC reaches VCC(on).
Even though the DSS is able to maintain the VCC voltage
between VCC(on) and VCC(min) by turning the HV start−up
current source on and off, it can only be used in light load
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NCP1235
VHV
VHV(start)
Waits
next
VCC(on)
before
starting
VHV(min)
time
VCC
VCC(on)
VCC(min)
HV
current
source =
Istart1
HV
current
source =
Istart2
VCC(inhibit)
time
DRV
Figure 30. Start−up Timing Diagram
time
the HV current source will always turn on and off to maintain
VCC between VCC(min) and VCC(on).
For safety reasons, the start−up current is lowered when
VCC is below VCC(inhibit), to reduce the power dissipation in
case the VCC pin is shorted to GND (in case of VCC capacitor
failure, or external pull−down on VCC to disable the
controller).
There are only two conditions for which the current source
doesn’t turn on when VCC reaches VCC(min): the voltage on
HV pin is too low (below VHV(min)), or a thermal shutdown
condition (TSD) has been detected. In all other conditions,
Brown−out protection
When the input voltage goes below VHV(stop), a
brown−out condition is detected, and the controller stops.
The HV current source alternatively turns on and off to
maintain VCC between VCC(on) and VCC(min) until the input
voltage is back above VHV(start).
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NCP1235
HV stop
Brown-out
or AC OVP
detected
Waits next
VCC(on) before
starting
VCC
time
VCC(on)
VCC(min)
time
DRV
time
Figure 31. Brown−out Timing Diagram
When VHV crosses the VHV(start) threshold, the controller
can start immediately. When it crosses VHV(stop), it triggers
a timer of duration tHV: this ensures that the controller
doesn’t stop in case of line cycle drop−out.
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NCP1235
VHV
Brown-out
VHV(start)
VHV(stop)
time
Starts at next
VCC(ON)
DRV
t HV
time
Figure 32. AC Input Brown−out Timing Diagram
Clamped Driver
Oscillator with Maximum Duty Cycle and Frequency
Jittering
The supply voltage for the NCP1235 can be as high as
28 V, but most of the MOSFETs that will be connected to the
DRV pin cannot accept more than 20 V on their gate. The
driver pin is therefore clamped safely below 16 V. This
driver has a typical current capability of $500 mA.
The NCP1235 includes an oscillator that sets the
switching frequency of 65 kHz with an accuracy of $7%.
The maximum duty cycle of the DRV pin is 80%, with an
accuracy of $7%.
In order to improve the EMI signature, the switching
frequency jitters $10% around its nominal value, with a
triangle−wave shape and at a frequency of 125 Hz. This
frequency jittering is active even when the frequency is
decreased to improve the EMI in light load condition.
VCC
Clamp
fOSC
DRV signal
fOSC + 6
Nominal fOSC
fOSC − 6
Figure 34. Clamped Driver
Time
8%
(125 Hz)
Figure 33. Frequency Jittering
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18
DRV
NCP1235
CURRENT−MODE CONTROL WITH OVERPOWER COMPENSATION AND SOFT−START
Current sensing
input of the PWM comparator through a 250 ns LEB block.
On the other input the FB voltage divided by 5 sets the
threshold: when the voltage ramp reaches this threshold, the
output driver is turned off.
The maximum value for the current sense is 0.7 V, and it
is set by a dedicated comparator.
NCP1235 is a current−mode controller, which means that
the FB voltage sets the peak current flowing in the
inductance and the MOSFET. This is done through a PWM
comparator: the current is sensed across a resistor and the
resulting voltage is applied to the CS pin. It is applied to one
VFB(ref)
KFB
+
−
RFB(up)
PWM
Jitter
Soft−start
+
−
Oscillator
Soft−start ramp
Start
tSSTART
Reset
FB
DCMAX
IC Start
IC Stop
S
Q
R
blanking
tLEB
CS
DRV Stage
+
−
+
VILIM
IC stop
UVLO
blanking
tBCS
+
−
+
Protection
Mode
VCS(stop)
HV stop
Latch
TSD
Fault
Figure 35. Current Sense Block Schematic
Each time the controller is starting, i.e. the controller was
off and starts – or restarts – when VCC reaches VCC(on), a
soft−start is applied: the current sense setpoint is linearly
increased from 0 (the minimum level can be higher than 0
because of the LEB and propagation delay) until it reaches
VILIM (after a duration of tSSTART), or until the FB loop
imposes a setpoint lower than the one imposed by the
soft−start (the 2 comparators outputs are OR’ed). The
soft−start ramp signal is generated by the D/A converter in
the NCP1235, that’s why there are observable 15 discrete
steps instead the truly linearly increasing current setpoint
ramp.
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NCP1235
VFB
VFB(fault)
Time
Soft-start ramp
VFB takes
over soft-start
VILIM
Time
tSSTART
CS Setpoint
VILIMI
Time
Figure 36. Soft−Start
Overpower compensation
Under some conditions, like a winding short−circuit for
instance, not all the energy stored during the on time is
transferred to the output during the off time, even if the on
time duration is at its minimum (imposed by the propagation
delay of the detector added to the LEB duration). As a result,
the current sense voltage keeps on increasing above VILIM,
because the controller is blind during the LEB blanking
time. Dangerously high current can grow in the system if
nothing is done to stop the controller. That’s what the
additional comparator, that senses when the current sense
voltage on CS pin reaches VCS(stop) (= 1.5 x VILIM), does:
as soon as this comparator toggles, the controller
immediately enters the protection mode (latched or
autorecovery according to the chosen option).
The power delivered by a flyback power supply is
proportional to the square of the peak current in the
discontinuous conduction mode:
P OUT +
1
@ h @ L p @ F SW @ I p
2
2
(eq. 1)
Unfortunately, due to the inherent propagation delay of
the logic, the actual peak current is higher at high input
voltage than at low input voltage, leading to a significant
difference in the maximum output power delivered by the
power supply.
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NCP1235
IP
IP to be
compensated
ILIMIT
High
Line
Low
Line
time
tdelay
tdelay
Figure 37. Line Compensation for True Overpower Protection
would be in the same order of magnitude. Therefore the
compensation current is only added when the FB voltage is
higher than VFB(OPCE).
However, because the HV pin can be connected to an ac
voltage, there is needed an additional circuitry to read or at
least closely estimate the actual voltage on the bulk
capacitor.
To compensate this and have an accurate overpower
protection, an offset proportional to the input voltage is
added on the CS signal by turning on an internal current
source: by adding an external resistor in series between the
sense resistor and the CS pin, a voltage offset is created
across it by the current. The compensation can be adjusted
by changing the value of the resistor.
But this offset is unwanted to appear when the current
sense signal is small, i.e. in light load conditions, where it
(68 ms)
S
Q
R
Q
Brown Out
HV Timer
HV
thv
(32 ms)
Watch
Dog
VHVstop
A/D 3 bit
Converter
+
Peak Detector
3 bit
Register
I Generator
I ctrl
FB
To CS
Block
Tblanking
LEB
CS
VFB (OPC)
Figure 38. Schematic Overpower Compensation Circuit
A 3 bit A/D converter with the peak detector senses the ac
input, and its output is periodically sampled and reset, in
order to follow closely the input voltage variations. The
sample and reset events are given by the VHV(stop)
comparator used for sampling detection for the AC line
input. If only the DC high voltage input is used, no reset
signal is generated by the VHV(stop) condition and the 32 ms
watch dog is used to generate the sampling events for
sampling the DC input high voltage line.
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NCP1235
IOPC
VHV
VFB(OPCE)
VFB
VFB(OPCF)
Figure 39. Overpower Compensation Current Relation to Feedback Voltage and Input Voltage
VHV
VHV(stop)
time
Sample/reset
signal
time
HV
timer
starts
One shot
HV
timer
restarts
HV
timer
restarts
HV
timer
restarts
t HV
time
Peak
detector
Reset
Reset
Reset
Reset
Reset
time
IOPC
Sample
Sample
Sample
Sample
Reset
time
Figure 40. Overpower Compensation
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NCP1235
VHV
VHV(stop)
time
twd
twd
twd
Peak
detector
Reset
time
IOPC
Sample
Sample
Reset
Sample
tHV
time
Figure 41. Overpower Compensation
Feedback with Slope Compensation
3.5 V. There is a pull−up resistor of 20 kW from FB pin to an
internal reference.
The ratio from the FB voltage to the current sense setpoint
is 5, meaning that the FB voltage corresponding to VILIM is
VFB(ref)
20 kW
FB
K FB
slope
comp.
+
PWM
−
CS
Oscillator
blanking
tLEB
Figure 42. FB Circuitry
In order to allow the NCP1235 to operate in CCM with a
duty cycle above 50 %, a fixed slope compensation is
internally applied to the current−mode control. The slope
appearing on the internal voltage setpoint for the PWM
comparator is −32.5 mV/ms typical for the 65 kHz version.
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NCP1235
Overcurrent protection with Fault timer
latched off (latched protection, version A), or it enters an
autorecovery mode (version B). The timer is reset when the
CS setpoint goes back below VILIM before the timer elapses.
The fault timer is also started if the driver signal is reset by
the max duty cycle.
When an overcurrent occurs on the output of the power
supply, the FB loop asks for more power than the controller
can deliver, and the CS setpoint reaches VILIMIT. When this
event occurs, an internal tfault timer is started: once the timer
elapsed, DRV pulses are stopped and the controller is either
Fault Flag
PWM
FB
+
−
/5
R
Q
S
timer
tfault
Protection
Mode
Reset DRV
release
Autorecovery
protection
mode only
blanking
CS
timer
tLEB
+
+
−
Brown−out
Reset
VILIM
DC MAX
DRV
Figure 43. Timer−Based Overcurrent Protection
In autorecovery mode, the controller tries to restart after
tautorec. If the fault has gone, the supply resumes operation;
if not, the system starts a new burst cycle.
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t autorec
NCP1235
Fault
disappears
Output Load Overcurrent
applied
Max Load
Fault Flag
time
Fault
timer
starts
VCC
time
VCC(on)
VCC(min)
Restart
At VCC(on)
(new burst
cycle if Fault
still present)
DRV
time
Controller
stops
Fault timer
time
tfault
tfault
tautorec
time
Figure 44. Autorecovery Timer−Based Protection Mode
In the latched version, the controller can restart only if a
brown−out or a VCC reset occurs, which in a real application
can only happen if the power supply is unplugged from the
mains line.
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NCP1235
Output Load
No restart
when fault
disappears
Overcurrent
applied
Max Load
Fault Flag
time
Fault
timer
starts
VCC
time
VCC(on)
VCC(min)
DRV
time
Controller
latches off
Fault timer
time
tfault
tfault
Figure 45. Latched Timer−Based Overcurrent Protection
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time
NCP1235
LOW LOAD OPERATION
Frequency Foldback
VFB(foldS), and is complete before VFB reaches Vskip(in),
whatever the nominal switching frequency option is. The
current−mode control is still active while the oscillator
frequency decreases. Note that the frequency foldback is
disabled if the controller runs at its maximum duty cycle.
In order to improve the efficiency in light load conditions,
the frequency of the internal oscillator is linearly reduced
from its nominal value down to fOSC(min). This frequency
foldback starts when the voltage on FB pin goes below
fOSC
Nominal fOSC
Skip
fOSC(min)
Vskip(in)
FB
VFB(foldS)
VFB(foldE)
Figure 46. Frequency Foldback when the FB Voltage Decreases
Skip Cycle Mode
−
+
+
Vskip
S
Q
DRV stage
R
FB
KFB
CS
blanking
tLEB
+
−
Figure 47. Skip Cycle Schematic
When the FB voltage reaches Vskip(in) while decreasing,
skip mode is activated: the driver stops, and the internal
consumption of the controller is decreased. While VFB is
below Vskip(out), the controller remains in this state; but as
soon as VFB crosses the skip out threshold, the DRV pin
starts to pulse again.
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NCP1235
VFB
VFB(fold)
Vskip(out)
Vskip(in)
Exits
Exits
skip
Enters
Enters
skip
skip
Time
skip
DRV
Time
Figure 48. Skip Cycle Timing Diagram
Latch−off Input
VDD
+
INTC
blanking
+
−
tLatch(OVP)
VOVP
INTC
Latch
+
1 kW
−
+
blanking
tLatch(OTP)
S
Q
R
Latch
VOTP
Vclamp
Brown−out
Reset
Soft−start
end
Figure 49. Latch Detection Schematic
To avoid any false triggering, spikes shorter than 50 ms
(for the high latch) or 350 ms (for the low latch) are blanked
and only longer signals can actually latch the controller.
Reset occurs when a brown−out condition is detected or
the VCC is cycled down to a reset voltage, which in a real
application can only happen if the power supply is
unplugged from the AC line.
Upon start−up, the internal references take some time
before being at their nominal values; so one of the
comparators could toggle even if it should not. Therefore the
internal logic does not take the latch signal into account
before the controller is ready to start: once VCC reaches
VCC(on), the latch pin High latch state is taken into account
The Latch pin is dedicated to the latch−off function: it
includes two levels of detection that define a working
window, between a high latch and a low latch: within these
two thresholds, the controller is allowed to run; but as soon
as either the low or the high threshold is crossed, the
controller is latched off. The lower threshold is intended to
be used with an NTC thermistor, thanks to an internal current
source INTC.
An active clamp prevents the voltage from reaching the
high threshold if it is only pulled up by the INTC current. To
reach the high threshold, the pull−up current has to be higher
than the pull−down capability of the clamp (typically
1.5 mA at VOVP).
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NCP1235
and the DRV switching starts only if it is allowed; whereas
the Low latch (typically sensing an overtemperature) is
taken into account only after the soft−start is finished. In
addition, the NTC current is doubled to INTC(SSTART) during
the soft−start period, to speed up the charging of the Latch
pin capacitor. The maximum value of Latch pin capacitor is
given by the following formula (The standard start−up
condition is considered and the NTC current is neglected) :
C LATCHmax +
t SSTARTmin @ I NTC(SSTART)min
V clamp0min
(eq. 2)
2.8 @ 10 −3 @ 130 @ 10 −6
+
F + 364 nF
1.0
VCC
VCC(on)
VCC(min)
Start-up
initiated by
VCC(on)
Internal Latch Signal
Noise spike
ignored
(tLatch blanking)
Latch signal
high during
pre-start phase
time
time
DRV
Latch-off
Switching
allowed (no
latch event)
time
Figure 50. Latch−off Function Timing Diagram
Temperature Shutdown
instantaneously, and the HV current source is turned off.
Internal logic state is reset. When the temperature falls
below the low threshold, the HV start−up current source is
enabled, and a regular start−up sequence takes place.
The die includes a temperature shutdown protection with
a trip point guaranteed above 135°C and below 165°C, and
a typical hysteresis of 30°C. When the temperature rises
above the high threshold, the controller stops switching
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NCP1235
STATE DIAGRAMS
HV Start−up Current Source
VCC > VCC(inhibit)
Istart1
No TSD
Istart2
VCC < VCC(inhibit)
TSD
TSD
Stop
TSD
VCC < VCC(min)
VCC > VCC(on)
TSD
Off
Figure 51. HV Start−up Current Source State Diagram
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NCP1235
Controller Operation (Latched Version: A Option)
• High Latch
• VCC > VCC(ovp)
VCC > VCC(on)
Soft−start
• Brown−out
• TSD
Soft−start ends
• Brown−out
• TSD
Stopped
• Brown−out
• TSD
• Brown−out
• VCC reset
• Brown−out
• TSD
Skip
Skip in
Latch
• High Latch
• Low Latch
• VCC > VCC(ovp)
Skip out
Running
• Fault
• High Latch
• Low Latch
• VCC > VCC(ovp)
With Fault=
• tfault expires
• VCS > VCS(stop)
• VCC < VCC(off)
Figure 52. Controller Operation State Diagram (Latched Protection)
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NCP1235
Controller Operation (Autorecovery Version: B Option)
• High Latch
• VCC > VCC(ovp)
VCC > VCC(on)
Soft−start
• Brown−out
• TSD
• tautorec counting
• Brown−out
• TSD
Soft−start ends
Stopped
• Brown−out
• TSD
• Fault
• Brown−out
• TSD
Skip
• Brown−out
• VCC reset
Skip in
Latch
• High Latch
• Low Latch
• VCC > VCC(ovp)
Skip out
Running
• High Latch
• Low Latch
• VCC > VCC(ovp)
With Fault=
• tfault expires
• VCS > VCS(stop)
• VCC < VCC(off)
Figure 53. Controller Operation State Diagram (Autorecovery Protection)
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32
NCP1235
Table 1. ORDERING INFORMATION
Part No.
NCP1235AD065R2G
Switching
Frequency
Overload
Protection
Fault Timer
Package
Shipping†
65 kHz
Latched
128 ms
SOIC−7
(Pb−Free)
2500 / Tape & Reel
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specifications Brochure, BRD8011/D.
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33
NCP1235
PACKAGE DIMENSIONS
SOIC−7
CASE 751U
ISSUE E
−A−
8
NOTES:
1. DIMENSIONING AND TOLERANCING PER
ANSI Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DIMENSION A AND B ARE DATUMS AND T
IS A DATUM SURFACE.
4. DIMENSION A AND B DO NOT INCLUDE
MOLD PROTRUSION.
5. MAXIMUM MOLD PROTRUSION 0.15 (0.006)
PER SIDE.
5
−B− S
0.25 (0.010)
B
M
M
1
4
DIM
A
B
C
D
G
H
J
K
M
N
S
G
C
R
X 45 _
J
−T−
SEATING
PLANE
H
0.25 (0.010)
K
M
D 7 PL
M
T B
S
A
S
MILLIMETERS
MIN
MAX
4.80
5.00
3.80
4.00
1.35
1.75
0.33
0.51
1.27 BSC
0.10
0.25
0.19
0.25
0.40
1.27
0_
8_
0.25
0.50
5.80
6.20
INCHES
MIN MAX
0.189 0.197
0.150 0.157
0.053 0.069
0.013 0.020
0.050 BSC
0.004 0.010
0.007 0.010
0.016 0.050
0_
8_
0.010 0.020
0.228 0.244
SOLDERING FOOTPRINT*
1.52
0.060
7.0
0.275
4.0
0.155
0.6
0.024
1.270
0.050
SCALE 6:1
mm Ǔ
ǒinches
*For additional information on our Pb−Free strategy and soldering
details, please download the ON Semiconductor Soldering and
Mounting Techniques Reference Manual, SOLDERRM/D.
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC owns the rights to a number of patents, trademarks,
copyrights, trade secrets, and other intellectual property. A listing of SCILLC’s product/patent coverage may be accessed at www.onsemi.com/site/pdf/Patent−Marking.pdf. SCILLC
reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any
particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without
limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications
and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC
does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for
surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where
personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and
its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly,
any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture
of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT:
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Phone: 303−675−2175 or 800−344−3860 Toll Free USA/Canada
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Phone: 81−3−5817−1050
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34
ON Semiconductor Website: www.onsemi.com
Order Literature: http://www.onsemi.com/orderlit
For additional information, please contact your local
Sales Representative
NCP1235/D