31 May, 2011 IRS21867S HIGH AND LOW SIDE DRIVER Product Summary Features • • • • • • • • • • • • Floating channel designed for bootstrap operation Fully operational to +600V Tolerant to negative transient voltage, dV/dt immune Low VCC operation Gate drive supply range from 5V to 20V Undervoltage lockout for both channels 3.3V and 5V input logic compatible Matched propagation delay for both channels Logic and power ground +/- 5V offset Lower di/dt gate driver for better noise immunity Output source/sink current capability 4.0A (Typ.) Leadfree, RoHS compliant Topology Single-Phase VOFFSET ≤ 600V VOUT 10V – 20V Io+ & I o- (typical) 4.0A & 4.0A ton & toff (typical) 170ns & 170ns Package Options Applications • Battery powered equipment • Hand-tools • Fork-lifts • Golf-carts • RC Hobby Equipment • E-bike SOIC-8 Typical Connection Diagram IRS21867S Refer to Lead Assignment for correct pin Configuration. This diagrams show electrical Connections only. Please refer to our Application Notes and Design Tips for proper circuit board layout www.irf.com © 2008 International Rectifier IRS21867S Table of Contents Page Typical Connection Diagram 1 Description/Feature Comparison 3 Qualification Information 3 Absolute Maximum Ratings 4 Recommended Operating Conditions 4 Dynamic Electrical Characteristics 5 Static Electrical Characteristics 5 Functional Block Diagram 6 Input/Output Pin Equivalent Circuit Diagram 7 Lead Definitions 8 Lead Assignments 8 Application Information and Additional Details 9 Package Details 17 Tape and Reel Details 18 Part Marking Information 19 Ordering Information 20 www.irf.com © 2010 International Rectifier 2 IRS21867S Description The IRS21867 is a high voltage, high speed power MOSFET and IGBT driver with independent high and low side referenced output channels. Proprietary HVIC and latch immune CMOS technologies enable ruggedized monolithic construction. Low VCC operation allows use in battery powered applications. The logic input is compatible with standard CMOS or LSTTL output, down to 3.3 V logic. The output drivers feature a high pulse current buffer stage designed for minimum driver cross-conduction. The floating channel can be used to drive an N-channel power MOSFET or IGBT in the high-side configuration which operates up to 600V. † Qualification Information †† Industrial Comments: This family of ICs has passed JEDEC’s Industrial qualification. IR’s Consumer qualification level is granted by extension of the higher Industrial level. Qualification Level Moisture Sensitivity Level SOIC8N ††† MSL2 260°C (per IPC/JEDEC J-STD-020) Class A (per JEDEC standard JESD22-A115) Class 2 (per EIA/JEDEC standard EIA/JESD22-A114) Class I, Level A (per JESD78) Yes Machine Model ESD Human Body Model IC Latch-Up Test RoHS Compliant † †† Qualification standards can be found at International Rectifier’s web site http://www.irf.com/ Higher qualification ratings may be available should the user have such requirements. Please contact your International Rectifier sales representative for further information. ††† Higher MSL ratings may be available for the specific package types listed here. Please contact your International Rectifier sales representative for further information. www.irf.com © 2010 International Rectifier 3 IRS21867S Absolute Maximum Ratings Absolute Maximum Ratings indicate sustained limits beyond which damage to the device may occur. All voltage parameters are absolute voltages referenced to COM. The thermal resistance and power dissipation ratings are measured under board mounted and still air conditions. Symbol VB Definition Min Max High side floating absolute voltage -0.3 625 (Note 1) VB – 25 VS - 0.3 -0.3 -0.3 COM - 0.3 — — — — -50 — VB + 0.3 VB + 0.3 25 (Note 1) VCC + 0.3 VCC + 0.3 50 0.625 200 150 150 300 VS High side floating supply offset voltage VHO High side floating output voltage VCC Low side and logic fixed supply voltage VLO Low side output voltage VIN Logic input voltage (HIN & LIN) dVS/dt Allowable offset supply voltage transient PD Package power dissipation @ TA ≤ 25°C RthJA Thermal resistance, junction to ambient TJ Junction temperature TS Storage temperature TL Lead temperature (soldering, 10 seconds) Note 1: All supplies are fully tested at 25V. Units V V/ns W °C/W °C Recommended Operating Conditions For proper operation the device should be used within the recommended conditions. All voltage parameters are absolute voltages referenced to COM. The VS offset rating is tested with all supplies biased at (VCCCOM) = 15V. Symbol Definition Min Max Units VB High side floating supply absolute voltage VS + 10 VS + 20 VS High side floating supply offset voltage Note 2 600 VHO High side floating output voltage VS VB V VCC Low side and logic fixed supply voltage 10 20 VLO Low side output voltage 0 VCC VIN Logic input voltage (HIN & LIN) COM VCC TA Ambient temperature -40 125 °C † Note 2: Logic operational for VS of -5V to +600V. Logic state held for VS of -5V to –VBS. (Please refer to the Design Tip DT97-3 for more details). www.irf.com © 2010 International Rectifier 4 IRS21867S Dynamic Electrical Characteristics VCC = VBS = 15V, CL = 1000 pF, TA = 25°C unless otherwise specified. Symbol ton toff MT tr tf Min Typ Max Units Test Conditions Definition Turn-on propagation delay Turn-off propagation delay Delay matching | ton – toff | Turn-on rise time Turn-off fall time — — — — — 170 170 — 22 18 250 250 35 38 30 ns VS = 0V VS = 0V or 600V VS = 0V Static Electrical Characteristics VCC = VBS = 15V,, and TA = 25°C unless otherwise specified. The VIN, and IIN parameters are referenced to COM and are applicable to the respective input leads: HIN, and LIN. The VO, and IO parameters are referenced to VS/COM and are applicable to the respective output leads: HO and LO. Symbol VIH VIL VOH VOL ILK IQBS IQCC IIN+ IINVCCUV+ VBSUV+ VCCUVVBSUVVCCUVH VBSUVH Definition Logic “1” input voltage for HO & LO Logic “0” input voltage for HO & LO High level output voltage, VCC or VBS - VO Low level output voltage, VO Offset supply leakage current Quiescent VBS supply current Quiescent VCC supply current Logic “1” input bias current Logic “0” input bias current VCC and VBS supply undervoltage positive going threshold VCC and VBS supply undervoltage negative going threshold Min Typ Max Units Test Conditions 2.5 — — — — 20 50 — — — — — 0.8 — 1.4 — 0.15 — 50 60 150 120 240 250 — — 5.0 5.34 6 0.5 IO+ Output high short circuit pulsed current 4.0 IO- Output low short circuit pulsed current 4.0 VIN = 0V or 5V µA HIN = LIN = 5V HIN = LIN = 0V V A www.irf.com IO = 0mA IO = 20mA VB = VS = 600 V 6.66 4.90 5.50 6.10 VCC and VBS supply undervoltage Hysteresis VCC = 10V to 20V V VO = 0V, PW ≤ 10µs VO = 15V, PW ≤ 10µs © 2010 International Rectifier 5 IRS21867S Functional Block Diagrams IRS21867 www.irf.com © 2010 International Rectifier 6 IRS21867S Input/Output Pin Equivalent Circuit Diagrams VB ESD Diode 25V HO ESD Diode VS 600V VCC ESD Diode LO 25V ESD Diode COM COM/V SS COM www.irf.com © 2010 International Rectifier 7 IRS21867S Lead Definitions: IRS21867S Pin# 1 2 3 4 5 6 7 8 Symbol VCC HIN LIN COM LO VS HO VB Description Low-side and logic fixed supply Logic input for high-side gate driver output (HO), in phase with HO Logic input for low-side gate driver output (LO), in phase with LO Low-side return Low-side gate drive output High-side floating supply return High-side gate drive output High-side floating supply Lead Assignments 8 lead SOIC IRS21867S www.irf.com © 2010 International Rectifier 8 IRS21867S Application Information and Additional Details Informations regarding the following topics are included as subsections within this section of the datasheet. • • • • • • • • IGBT/MOSFET Gate Drive Switching and Timing Relationships Matched Propagation Delays Input Logic Compatibility Undervoltage Lockout Protection Negative VS Transient SOA PCB Layout Tips Additional Documentation IGBT/MOSFET Gate Drive The IRS21867 HVIC is designed to drive MOSFET or IGBT power devices. Figures 1 and 2 illustrate several parameters associated with the gate drive functionality of the HVIC. The output current of the HVIC, used to drive the gate of the power switch, is defined as IO. The voltage that drives the gate of the external power switch is defined as VHO for the high-side power switch and VLO for the low-side power switch; this parameter is sometimes generically called VOUT and in this case does not differentiate between the high-side or low-side output voltage. VB (or VCC) VB (or VCC) IO+ HO (or LO) HO (or LO) + IO- VHO (or VLO) VS (or COM) - VS (or COM) Figure 1: HVIC sourcing current Figure 2: HVIC sinking current www.irf.com © 2010 International Rectifier 9 IRS21867S Switching and Timing Relationships The relationships between the input and output signals of the IRS21867 are illustrated below in Figures 3, 4. From these figures, we can see the definitions of several timing parameters (i.e., PW IN, PW OUT, tON, tOFF, tR, and tF) associated with this device. LINx (or HINx) 50% 50% PWIN tON LOx (or HOx) tOFF tR tF PWOUT 90% 90% 10% 10% Figure 3: Switching time waveforms Figure 4: Input/output timing diagram Matched Propagation Delays The IRS21867 is designed with propagation delay matching circuitry. With this feature, the IC’s response at the output to a signal at the input requires approximately the same time duration (i.e., tON, tOFF) for both the low-side channels and the high-side channels; the maximum difference is specified by the delay matching parameter (MT). The propagation turn-on delay (tON) is matched to the propagation turn-on delay (tOFF). www.irf.com © 2010 International Rectifier 10 IRS21867S Figure 5: Delay Matching Waveform Definition Input Logic Compatibility The inputs of this IC are compatible with standard CMOS and TTL outputs. The IRS21867 has been designed to be compatible with 3.3 V and 5 V logic-level signals. Figure 8 illustrates an input signal to the IRS22867, its input threshold values, and the logic state of the IC as a result of the input signal. Input Signal (IRS23364D) V IH Input Logic Level VIL High Low Low Figure 6: HIN & LIN input thresholds www.irf.com © 2010 International Rectifier 11 IRS21867S Undervoltage Lockout Protection This IC provides undervoltage lockout protection on both the VCC (logic and low-side circuitry) power supply and the VBS (high-side circuitry) power supply. Figure 7 is used to illustrate this concept; VCC (or VBS) is plotted over time and as the waveform crosses the UVLO threshold (VCCUV+/- or VBSUV+/-) the undervoltage protection is enabled or disabled. Upon power-up, should the VCC voltage fail to reach the VCCUV+ threshold, the IC will not turn-on. Additionally, if the VCC voltage decreases below the VCCUV- threshold during operation, the undervoltage lockout circuitry will recognize a fault condition and shutdown the high- and low-side gate drive outputs. Upon power-up, should the VBS voltage fail to reach the VBSUV threshold, the IC will not turn-on. Additionally, if the VBS voltage decreases below the VBSUV threshold during operation, the undervoltage lockout circuitry will recognize a fault condition, and shutdown the high-side gate drive outputs of the IC. The UVLO protection ensures that the IC drives the external power devices only when the gate supply voltage is sufficient to fully enhance the power devices. Without this feature, the gates of the external power switch could be driven with a low voltage, resulting in the power switch conducting current while the channel impedance is high; this could result in very high conduction losses within the power device and could lead to power device failure. Figure 7: UVLO protection www.irf.com © 2010 International Rectifier 12 IRS21867S Tolerant to Negative VS Transients A common problem in today’s high-power switching converters is the transient response of the switch node’s voltage as the power switches transition on and off quickly while carrying a large current. A typical 3-phase inverter circuit is shown in Figure 8; here we define the power switches and diodes of the inverter. If the high-side switch (e.g., the IGBT Q1 in Figures 9 and 10) switches off, while the U phase current is flowing to an inductive load, a current commutation occurs from high-side switch (Q1) to the diode (D2) in parallel with the low-side switch of the same inverter leg. At the same instance, the voltage node VS1, swings from the positive DC bus voltage to the negative DC bus voltage. Figure 8: Three phase inverter DC+ BUS Q1 ON IU VS1 Q2 OFF D2 DC- BUS Figure 9: Q1 conducting Figure 10: D2 conducting Also when the V phase current flows from the inductive load back to the inverter (see Figures 11 and 12), and Q4 IGBT switches on, the current commutation occurs from D3 to Q4. At the same instance, the voltage node, VS2, swings from the positive DC bus voltage to the negative DC bus voltage. www.irf.com © 2010 International Rectifier 13 IRS21867S Figure 11: D3 conducting Figure 12: Q4 conducting However, in a real inverter circuit, the VS voltage swing does not stop at the level of the negative DC bus, rather it swings below the level of the negative DC bus. This undershoot voltage is called “negative VS transient”. The circuit shown in Figure 13 depicts one leg of the three phase inverter; Figures 14 and 15 show a simplified illustration of the commutation of the current between Q1 and D2. The parasitic inductances in the power circuit from the die bonding to the PCB tracks are lumped together in LC and LE for each IGBT. When the high-side switch is on, VS1 is below the DC+ voltage by the voltage drops associated with the power switch and the parasitic elements of the circuit. When the high-side power switch turns off, the load current momentarily flows in the low-side freewheeling diode due to the inductive load connected to VS1 (the load is not shown in these figures). This current flows from the DC- bus (which is connected to the COM pin of the HVIC) to the load and a negative voltage between VS1 and the DC- Bus is induced (i.e., the COM pin of the HVIC is at a higher potential than the VS pin). Figure 13: Parasitic Elements Figure 14: VS positive Figure 15: VS negative In a typical motor drive system, dV/dt is typically designed to be in the range of 3-5 V/ns. The negative VS transient voltage can exceed this range during some events such as short circuit and over-current shutdown, when di/dt is greater than in normal operation. International Rectifier’s HVICs have been designed for the robustness required in many of today’s demanding applications. An indication of the IRS21867’s robustness can be seen in Figure 16, where there is represented the IRS2607 Safe Operating Area at VBS=15V based on repetitive negative VS spikes. A negative VS transient voltage falling in the grey area (outside SOA) may lead to IC permanent damage; viceversa unwanted functional anomalies or permanent damage to the IC do not appear if negative Vs transients fall inside SOA. www.irf.com © 2010 International Rectifier 14 IRS21867S Figure 16: Negative VS transient SOA for IRS2607 @ VBS=15V Even though the IRS21867 has been shown able to handle these large negative VS transient conditions, it is highly recommended that the circuit designer always limit the negative VS transients as much as possible by careful PCB layout and component use. PCB Layout Tips Distance between high and low voltage components: It’s strongly recommended to place the components tied to the floating voltage pins (VB and VS) near the respective high voltage portions of the device. Please see the Case Outline information in this datasheet for the details. Ground Plane: In order to minimize noise coupling, the ground plane should not be placed under or near the high voltage floating side. Gate Drive Loops: Current loops behave like antennas and are able to receive and transmit EM noise (see Figure 17). In order to reduce the EM coupling and improve the power switch turn on/off performance, the gate drive loops must be reduced as much as possible. Moreover, current can be injected inside the gate drive loop via the IGBT collector-to-gate parasitic capacitance. The parasitic auto-inductance of the gate loop contributes to developing a voltage across the gate-emitter, thus increasing the possibility of a self turn-on effect. www.irf.com © 2010 International Rectifier 15 IRS21867S Figure 17: Antenna Loops Supply Capacitor: It is recommended to place a bypass capacitor (CIN) between the VCC and COM pins. A ceramic 1 µF ceramic capacitor is suitable for most applications. This component should be placed as close as possible to the pins in order to reduce parasitic elements. Routing and Placement: Power stage PCB parasitic elements can contribute to large negative voltage transients at the switch node; it is recommended to limit the phase voltage negative transients. In order to avoid such conditions, it is recommended to 1) minimize the high-side emitter to low-side collector distance, and 2) minimize the low-side emitter to negative bus rail stray inductance. However, where negative VS spikes remain excessive, further steps may be taken to reduce the spike. This includes placing a resistor (5 Ω or less) between the VS pin and the switch node (see Figure 18), and in some cases using a clamping diode between COM and VS (see Figure 19). See DT04-4 at www.irf.com for more detailed information. Figure 18: VS resistor Figure 19: VS clamping diode Additional Documentation Several technical documents related to the use of HVICs are available at www.irf.com; use the Site Search function and the document number to quickly locate them. Below is a short list of some of these documents. DT97-3: Managing Transients in Control IC Driven Power Stages DT04-4: Using Monolithic High Voltage Gate Drivers AN-978: HV Floating MOS-Gate Driver ICs www.irf.com © 2010 International Rectifier 16 IRS21867S Package Details: SOIC8N www.irf.com © 2010 International Rectifier 17 IRS21867S Tape and Reel Details: SOIC8N LOADED TAPE FEED DIRECTION A B H D F C NOTE : CONTROLLING DIM ENSION IN M M E G CARRIER TAPE DIMENSION FOR Metric Code Min Max A 7.90 8.10 B 3.90 4.10 C 11.70 12.30 D 5.45 5.55 E 6.30 6.50 F 5.10 5.30 G 1.50 n/a H 1.50 1.60 8SOICN Imperial Min Max 0.311 0.318 0.153 0.161 0.46 0.484 0.214 0.218 0.248 0.255 0.200 0.208 0.059 n/a 0.059 0.062 F D C B A E G H REEL DIMENSIONS FOR 8SOICN Metric Code Min Max A 329.60 330.25 B 20.95 21.45 C 12.80 13.20 D 1.95 2.45 E 98.00 102.00 F n/a 18.40 G 14.50 17.10 H 12.40 14.40 www.irf.com Imperial Min Max 12.976 13.001 0.824 0.844 0.503 0.519 0.767 0.096 3.858 4.015 n/a 0.724 0.570 0.673 0.488 0.566 © 2010 International Rectifier 18 IRS21867S Part Marking Information www.irf.com © 2010 International Rectifier 19 IRS21867S Ordering Information P/n IRS21867SPbF IRS21867STRPbF Package SOIC8 SOIC8 Packing Tube Tape & Reel www.irf.com Pcs 95 2500 © 2010 International Rectifier 20 IRS21867S The information provided in this document is believed to be accurate and reliable. However, International Rectifier assumes no responsibility for the consequences of the use of this information. International Rectifier assumes no responsibility for any infringement of patents or of other rights of third parties which may result from the use of this information. No license is granted by implication or otherwise under any patent or patent rights of International Rectifier. The specifications mentioned in this document are subject to change without notice. This document supersedes and replaces all information previously supplied. For technical support, please contact IR’s Technical Assistance Center http://www.irf.com/technical-info/ WORLD HEADQUARTERS: 233 Kansas St., El Segundo, California 90245 Tel: (310) 252-7105 Revision History Date 5/20/2010 6/10/2010 03/30/2011 05/27/2011 05/31/2011 Comment Initial Draft Changed ABS MAX to 25V, Updated Iin+ to 250uA(Typ) to reflect 20kohm pull-down, Removed Min spec (2A) from Io+/Io-, Updated Block Diagram based on IRS2188 D/S Add recommended operation condition note Add ESD and Latch up specs Add application info and ordering info www.irf.com © 2010 International Rectifier 21