EL5152, EL5153, EL5252, EL5455 ® Data Sheet October 3, 2005 FN7385.4 270MHz Ultra-Accurate Amplifiers Features The EL5152, EL5153, EL5252, and EL5455 are 270MHz bandwidth -3dB voltage mode feedback amplifiers with DC accuracy of <0.01%, 1mV offsets and 50kV/V open loop gains. These amplifiers are ideally suited for applications ranging from precision measurement instrumentation to high-speed video and monitor applications demanding higher linearity at higher frequency. Capable of operating with as little as 3.0mA of current from a single supply ranging from 5V to 12V dual supplies ranging from ±2.5V to ±5.0V these amplifiers are also well suited for handheld, portable and battery-powered equipment. • 270MHz -3dB bandwidth Single amplifiers are offered in SOT-23 packages and duals in a 10 Ld MSOP package for applications where board space is critical. Quad amplifiers are available in a 14 Ld SO package. Additionally, singles and duals are available in the industry-standard 8 Ld SO. All parts operate over the industrial temperature range of -40°C to +85°C. • Fast disable on the EL5152 and EL5252 • 180V/µs slew rate • ±1mV maximum VOS • Very high open loop gains 50kV/V • Low supply current = 3mA • 105mA output current • Single supplies from 5V to 12V • Dual supplies from ±2.5V to ±5V • Low cost • Pb-Free plus anneal available (RoHS compliant) Applications • Imaging • Instrumentation • Video • Communications devices Pinouts EL5152 (8 LD SO) TOP VIEW NC 1 IN- 2 IN+ 3 + VS- 4 8 CE OUT 1 7 VS+ VS- 2 6 OUT IN+ 3 INA+ 1 10 INA+ VS- 3 CEB 4 5 VS+ + 4 IN- 5 NC EL5252 (10 LD MSOP) TOP VIEW CEA 2 EL5153 (5 LD SOT-23) TOP VIEW + - OUTA 1 9 OUTA INA- 2 8 VS+ INA+ 3 7 OUTB 6 INB- INB+ 5 EL5455 (14 LD SO) TOP VIEW - + + - 11 VS- INB+ 5 OUTB 7 13 IND12 IND+ VS+ 4 INB- 6 1 14 OUTD 10 INC+ - + + - 9 INC8 OUTC CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright Intersil Americas Inc. 2004, 2005. All Rights Reserved All other trademarks mentioned are the property of their respective owners. EL5152, EL5153, EL5252, EL5455 Ordering Information PART NUMBER PART MARKING TAPE & REEL PACKAGE PKG. DWG. # EL5152IS 5152IS - 8 Ld SO MDP0027 EL5152IS-T7 5152IS 7” 8 Ld SO MDP0027 EL5152IS-T13 5152IS 13” 8 Ld SO MDP0027 EL5152ISZ (See Note) 5152ISZ - 8 Ld SO (Pb-free) MDP0027 EL5152ISZ-T7 (See Note) 5152ISZ 7” 8 Ld SO (Pb-free) MDP0027 EL5152ISZ-T13 (See Note) 5152ISZ 13” 8 Ld SO (Pb-free) MDP0027 EL5153IW-T7 BGAA 7” (3K pcs) 5 Ld SOT-23 MDP0038 EL5153IW-T7A BGAA 7” (250 pcs) 5 Ld SOT-23 MDP0038 EL5153IWZ-T7 (See Note) BAAL 7” (3K pcs) 5 Ld SOT-23 (Pb-free) MDP0038 EL5153IWZ-T7A (See Note) BAAL 7” (250 pcs) 5 Ld SOT-23 (Pb-free) MDP0038 EL5252IY BAGAA - 10 Ld MSOP MDP0043 EL5252IY-T7 BAGAA 7” 10 Ld MSOP MDP0043 EL5252IY-T13 BAGAA 13” 10 Ld MSOP MDP0043 EL5455IS 5455IS - 14 Ld SO MDP0027 EL5455IS-T7 5455IS 7” 14 Ld SO MDP0027 EL5455IS-T13 5455IS 13” 14 Ld SO MDP0027 EL5455ISZ (See Note) 5455ISZ - 14 Ld SO (Pb-free) MDP0027 EL5455ISZ-T7 (See Note) 5455ISZ 7” 14 Ld SO (Pb-free) MDP0027 EL5455ISZ-T13 (See Note) 5455ISZ 13” 14 Ld SO (Pb-free) MDP0027 NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020. 2 FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 Absolute Maximum Ratings (TA = 25°C) Supply Voltage between VS and GND. . . . . . . . . . . . . . . . . . . 13.2V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA Pin Voltages . . . . . . . . . . . . . . . . . . . . . . . . . GND -0.5V to VS +0.5V Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +125°C Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C Current into IN+, IN-, CE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5mA CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA VS+ = +5V, VS- = ±5V, RF = RG = 750Ω, RL = 150Ω, TA = 25°C, unless otherwise specified. Electrical Specifications PARAMETER DESCRIPTION CONDITIONS MIN TYP MAX UNIT AC PERFORMANCE BW -3dB Bandwidth AV = +1, RL = 500Ω, CL = 5.0pF 270 MHz AV = +2, RL = 150Ω 85 MHz GBWP Gain Bandwidth Product RL = 150Ω 165 MHz BW1 0.1dB Bandwidth AV = +1, RL = 500Ω 50 MHz SR Slew Rate VO = -3V to +3V, AV = +2 155 V/µs VO = -3V to +3V, AV = 1, RL = 500Ω 180 V/µs 30 ns 120 tS 0.1% Settling Time VOUT = -1V to +1V, AV = +2 dG Differential Gain Error AV = +2, RL = 150Ω 0.06 % dP Differential Phase Error AV = +2, RL = 150Ω 0.045 ° VN Input Referred Voltage Noise 12 nV/√Hz IN Input Referred Current Noise 1.8 pA/√Hz DC PERFORMANCE VOS Offset Voltage TCVOS Input Offset Voltage Temperature Coefficient Measured from TMIN to TMAX AVOL Open Loop Gain VO is from -2.5V to 2.5V (EL5152 & EL5153) VO is from -2.5V to 2.5V (EL5252 & EL5455) -1 0.5 1 mV -2 µV/°C 10 20 kV/V 15 50 kV/V INPUT CHARACTERISTICS CMIR Common Mode Input Range Guaranteed by CMRR test CMRR Common Mode Rejection Ratio VCM = 2.5 to -2.5 IB -2.5 2.5 V 85 110 dB Bias Current -0.4 0.12 +0.6 µA IOS Input Offset Current -80 12 80 nA RIN Input Resistance 25 60 MΩ CIN Input Capacitance 1 pF OUTPUT CHARACTERISTICS VOUT IOUT Output Voltage Swing Output Current RL = 150Ω to GND ±3.0 ±3.3 V RL = 500Ω to GND ±3.4 ±3.7 V RL = 10Ω to GND 60 105 mA ENABLE (SELECTED PACKAGES ONLY) tEN Enable Time 200 ns tDIS Disable Time 300 ns 3 FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 VS+ = +5V, VS- = ±5V, RF = RG = 750Ω, RL = 150Ω, TA = 25°C, unless otherwise specified. (Continued) Electrical Specifications PARAMETER DESCRIPTION CONDITIONS IIHCE CE Pin Input High Current CE = VS+ IILCE CE Pin Input Low Current CE = VS- VIHCE CE Input High Voltage for Power-down VILCE CE Input Low Voltage for Power-up MIN 5 TYP MAX UNIT 0 -1 µA 13 25 µA VS+ -1 V VS+ -3 V SUPPLY ISON Supply Current - Enabled (per amplifier) ISOFF PSRR No load, VIN = 0V, CE = +5V 2.46 3.0 3.43 mA Supply Current - Disabled (per amplifier) No load, VIN = 0V, CE = 5V 5 13 25 µA Power Supply Rejection Ratio DC, VS = ±3.0V to ±6.0V (EL5152 & EL5153) 85 116 dB DC, VS = ±3.0V to ±6.0V (EL5252 & EL5455) 80 95 dB Typical Performance Curves 90 60 3 30 2 AV=+1 1 0 AV=+2 -1 AV=+5 -2 -3 Supply=±5.0V -4 INPUT=-30dBm=20mV RL=500Ω -5 C =5pF L -6 100K 1M 10M PHASE (°) NORMALIZED GAIN (dB) 4 AV=+2 AV=+1 -30 -60 -90 -120 -150 -180 100M AV=+5 0 Supply=±5.0V INPUT=-30dBm=20mV RL=500Ω CL=5pF -210 100K 500M 1M FREQUENCY (Hz) FIGURE 1. EL5152 SMALL SIGNAL FREQUENCY FOR VARIOUS GAINS 4 3 5 10Ω CL=5pF AV=+1 50Ω 2 500Ω 150Ω 1 0 -1 -2 -3 4 3 AV=+1 RL=500Ω 12pF 10pF 2 4.7pF 3.3pF 1 0 -1 2.2pF -2 1pF -3 What should label be fore this curve? -4 -4 -5 100K 1M 10M 100M 500M FREQUENCY (Hz) FIGURE 3. FREQUENCY RESPONSE FOR VARIOUS RL 4 500M FIGURE 2. EL5152 SMALL SIGNAL FREQUENCY PHASE FOR VARIOUS GAINS NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 5 100M 10M FREQUENCY (Hz) -5 100K 1M 10M 100M 500M FREQUENCY (Hz) FIGURE 4. FREQUENCY RESPONSE FOR VARIOUS CL FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 Typical Performance Curves (Continued) 3 2 5 AV=+2 CL=5pF RF=500Ω 50Ω 100Ω 200Ω 1 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 4 0 250Ω 500Ω -1 -2 -3 -4 -5 4 3 AV=+2 RL=500Ω RF=500Ω 22pF 18pF 2 12pF 1 0 -1 4.7pF -2 2.7pF -3 -4 -6 100K 1M 100M 10M -5 100K 800M 1M FREQUENCY (Hz) FIGURE 5. FREQUENCY RESPONSE FOR VARIOUS RL 3 2 50Ω 200Ω 0 -1 500Ω -2 250Ω -3 -4 3 2 0 39pF 27pF -2 -3 18pF -4 -5 100M 50pF -1 -6 100K 10M 68pF 1 -6 100K 1M 87pF RL=500Ω AV=+5 RF=102Ω -5 1M FIGURE 7. FREQUENCY RESPONSE FOR VARIOUS RL 100M 500M FIGURE 8. FREQUENCY RESPONSE FOR VARIOUS CL 5 5 4.7pF RL=150Ω AV=+2 RF=500Ω NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 10M FREQUENCY (Hz) FREQUENCY (Hz) 3 500M 4 AV=+5 CL=5pF RF=102Ω 1 4 100M FIGURE 6. FREQUENCY RESPONSE FOR VARIOUS CL NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 4 10M FREQUENCY (Hz) 3.3pF 2 1 3.2pF 0 1pF -1 -2 -3 3 RL=500Ω CL=5pF AV=+2 RF=RG= 1500Ω 1000Ω 2 1 750Ω 0 500Ω -1 -2 -3 -4 -4 -5 100K 4 1M 10M 100M FREQUENCY (Hz) FIGURE 9. FREQUENCY RESPONSE FOR VARIOUS CIN 5 500M -5 100K 1M 10M 100M 500M FREQUENCY (Hz) FIGURE 10. FREQUENCY RESPONSE vs RF/RG FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 Typical Performance Curves (Continued) -5 NORMALIZED GAIN (dB) -3 5 RL=500Ω AV=+5 RF=102Ω NORMALIZED GAIN (dB) -4 34pF -2 22pF -1 0 -1 0pF -2 -3 4 3 2 Supply=±5.0V RL=500Ω AV=+2 RF=500Ω 1 -1 -2 -3 -4 -4 -5 100K -5 100K 1M 100M 300M 10M ±2.0V ±3.0V ±4.0V ±5.0V 0 1M FREQUENCY (Hz) FIGURE 11. FREQUENCY RESPONSE FOR VARIOUS CIN 500M FIGURE 12. FREQUENCY RESPONSE FOR VARIOUS POWER SUPPLY -30 0 AV=+1 -10 -40 -20 -50 -30 -60 CMRR (dB) PSRR (dB) 100M 10M FREQUENCY (Hz) -40 -50 -60 -70 ±2.5 -70 ±3.0 -80 ±5.0 -90 -100 -80 -110 -90 -120 -130 100 -100 1K 10K 1M 100K 10M 100M 1K 10K 100K 1M 10M 100M FREQUENCY (Hz) FREQUENCY (Hz) FIGURE 13. PSRR FIGURE 14. CMRR FOR VARIOUS POWER SUPPLY VALUES 1000 OUTPUT IMPEDANCE (Ω) AV=+1 100 AV=+1 RL=500Ω CL=0 10 CH 1 CH 2 1 0.01 328ns DISABLE 0.001 1K 10K 100K 1M 10M FREQUENCY (Hz) FIGURE 15. OUTPUT IMPEDANCE 6 216ns ENABLE 100M TIME (400ns/DIV) FIGURE 16. ENABLE/DISABLE RESPONSE FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 Typical Performance Curves (Continued) VOLTAGE (500mV/DIV) VOLTAGE (500mV/DIV) AV=+1 RL=500Ω CL=5pF 0V AV=+1 RL=500Ω CL=5pF 0V TIME (4ns/DIV) TIME (4ns/DIV) FIGURE 17. RISE TIME - LARGE SIGNAL RESPONSE VOLTAGE (100mV/DIV) VOLTAGE (100mV/DIV) AV=+1 RL=500Ω CL=5pF FIGURE 18. FALL TIME - LARGE SIGNAL RESPONSE 0V AV=+1 RL=500Ω CL=5pF 0V TIME (2ns/DIV) TIME (2ns/DIV) FIGURE 19. RISE TIME - SMALL SIGNAL RESPONSE FIGURE 20. FALL TIME - SMALL SIGNAL RESPONSE -10 -45 90 80 70 0 GAIN 45 50 40 30 90 PHASE 20 PHASE (°) GAIN (dB) 60 135 10 -30 AV=+1 RL-500Ω CL=0pF -40 IN #2 OUT #1 -50 -60 -70 IN #1 OUT #2 -80 -90 0 -10 1K CROSSTALK (dB) -20 10K 100K 1M 10M 180 100M 500M FREQUENCY (Hz) FIGURE 21. EL5152 SMALL SIGNAL OPEN LOOP GAIN vs FREQUENCY INVERTING 7 -100 100K 1M 10M 100M 1G FREQUENCY (Hz) FIGURE 22. EL5252 SMALL SIGNAL FREQUENCY vs CROSSTALK FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 Typical Performance Curves (Continued) 4 6 5 4 3 AV=+2 RL=500Ω CL=5pF 2 1 0 ±1 ±1.5 ±2 ±2.5 ±3 ±3.5 ±4 ±4.5 3 NORMALIZED GAIN (dB) SUPPLY CURRENT (mA) 7 2 RL=500Ω CL=0pF 1 ±2.0V ±3.0V ±4.0V ±5.0V 0 -1 -2 -3 -4 -5 -6 100K ±5 1M VOLTAGE (V) 100M 10M 800M FREQUENCY (Hz) FIGURE 23. SUPPLY CURRENT vs SUPPLY VOLTAGE FIGURE 24. FREQUENCY RESPONSE FOR VARIOUS VOLTAGE SUPPLY LEVELS NORMALIZED GAIN (dB) 5 4 3 AV=+1 RL-500Ω CL=0pF 2 1 CHANNEL #1 0 CHANNEL #2 -1 -2 -3 -4 -5 100K 1M 100M 10M 1G FREQUENCY (Hz) FIGURE 25. EL5252 SMALL SIGNAL FREQUENCY - CHANNEL TO CHANNEL JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD SO8 θJA=110°C/W 1 909mW 0.9 0.8 870mW MSOP8/10 θJA=115°C/W 0.6 0.4 435mW SOT23-5/6 θJA=230°C/W 0.2 0 0 25 1 SO14 θJA=88°C/W 1.2 1.136W POWER DISSIPATION (W) POWER DISSIPATION (W) 1.4 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 26. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE 8 JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD SO14 0.9 0.8 833mW 0.7 0.6 625mW 0.5 486mW 0.4 0.3 391mW 0.2 SOT23-5/6 0.1 θ =256°C/W JA 0 0 25 50 θJA=120°C/W SO8 θJA=160°C/W MSOP8/10 θJA=206°C/W 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 27. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 EL5152 Product Description The EL5152, EL5153, EL5252, and EL5455 are wide bandwidth, low power, low offset voltage feedback operational amplifiers capable of operating from a single or dual power supplies. This family of operational amplifiers are internally compensated for closed loop gain of +1 or greater. Connected in voltage follower mode, driving a 500Ω load members of this amplifier family demonstrate a -3dB bandwidth of about 270MHz. With the loading set to accommodate typical video application, 150Ω load and gain set to +2, bandwidth reduces to about 180MHz with a 600V/µs slew rate. Power down pins on the EL5152 and EL5252 reduce the already low power demands of this amplifier family to 17µA typical while the amplifier is disabled. Input, Output and Supply Voltage Range The EL5152 and EL5153 families have been designed to operate with supply voltage ranging from 5V to 12V. Supply voltages range from ±2.5V to ±5V for split supply operation. Of course split supply operation can easily be achieved using single supplies by splitting off half of the single supply with a simple voltage divider as illustrated in the application circuit section. Input Common Mode Range These amplifiers have an input common mode voltage ranging from 1.5V above the negative supply (VS- pin) to 1.5V below the positive supply (VS+ pin). If the input signal is driven beyond this range the output signal will exhibit distortion. Maximum Output Swing & Load Resistance The outputs of the EL5152 and EL5153 families maximum output swing ranges from -4V to 4V for VS = ±5V with a load resistance of 500Ω. Naturally, as the load resistance becomes lower, the output swing lowers accordingly; for instance, if the load resistor is 150Ω, the output swing ranges from -3.5V to 3.5V. This response is a simple application of Ohms law indicating a lower value resistance results in greater current demands of the amplifier. Additionally, the load resistance affects the frequency response of this family as well as all operational amplifiers, as clearly indicated by the Gain vs Frequency for Various RL curves clearly indicate. In the case of the frequency response reduced bandwidth with decreasing load resistance is a function of load resistance in conjunction with the output zero response of the amplifier. Choosing a Feedback Resistor A feedback resistor is required to achieve unity gain; simply short the output pin to the inverting input pin. Gains greater than +1 require a feedback and gain resistor to set the desired gain. This gets interesting because the feedback resistor forms a pole with the parasitic capacitance at the inverting input. As the feedback resistance increases the 9 position of the pole shifts in the frequency domain, the amplifier's phase margin is reduced and the amplifier becomes less stable. Peaking in the frequency domain and ringing in the time domain are symptomatic of this shift in pole location. So we want to keep the feedback resistor as small as possible. You may want to use a large feedback resistor for some reason; in this case to compensate the shift of the pole and maintain stability a small capacitor in the few Pico farad range in parallel with the feedback resistor is recommended. For the gains greater than unity, it has been determined a feedback resistance ranging from 500Ω to 750Ω provides optimal response. Gain Bandwidth Product The EL5156 and EL5157 families have a gain bandwidth product of 210MHz for a gain of +5. Bandwidth can be predicted by the following equation: Gain × BW = GainBandwidthProduct Video Performance For good video performance, an amplifier is required to maintain the same output impedance and same frequency response as DC levels are changed at the output; this characteristic is widely referred to as “diffgain-diffphase”. Many amplifiers have a difficult time with this especially while driving standard video loads of 150Ω, as the output current has a natural tendency to change with DC level. The EL5152 dG and dP for these families is a respectable 0.006% and 0.04%, while driving 150Ω at a gain of 2. Driving high impedance loads would give a similar or better dG and dP performance as the current output demands placed on the amplifier lessen with increased load. Driving Capacitive Loads The EL5152 and EL5153 families can easily drive capacitive loads as demanding as 27pF in parallel with 500Ω while holding peaking to within 5dB of peaking at unity gain. Of course if less peaking is desired, a small series resistor (usually between 5Ω to 50Ω) can be placed in series with the output to eliminate most peaking. However, there will be a small sacrifice of gain which can be recovered by simply adjusting the value of the gain resistor. Driving Cables Both ends of all cables must always be properly terminated; double termination is absolutely necessary for reflection-free performance. Additionally, a back-termination series resistor at the amplifier's output will isolate the amplifier from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a backtermination resistor. Again, a small series resistor at the output can help to reduce peaking. FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 Disable/Power-Down For sinking: The EL5152 and EL5253 can be disabled with their output placed in a high impedance state. The turn off time is about 330ns and the turn on time is about 130ns. When disabled, the amplifier's supply current is reduced to 17µA typically; essentially eliminating power consumption. The amplifier's power down is controlled by standard TTL or CMOS signal levels at the ENABLE pin. The applied logic signal is relative to VS- pin. Letting the ENABLE pin float or the application of a signal that is less than 0.8V above VS- enables the amplifier. The amplifier is disabled when the signal at ENABLE pin is above VS+ -1.5V. Output Drive Capability The EL5152 and EL5153 families do not have internal short circuit protection circuitry. Typically, short circuit currents as high as 95mA and 70mA can be expected and naturally, if the output is shorted indefinitely the part can easily be damaged from overheating, or excessive current density may eventually compromise metal integrity. Maximum reliability is maintained if the output current is always held below ±40mA. This limit is set and limited by the design of the internal metal interconnect. Note that in transient applications, the part is extremely robust. Power Dissipation With the high output drive capability of the EL5152 and EL5153 families, it is possible to exceed the 125°C absolute maximum junction temperature under certain load current conditions. Therefore, it is important to calculate the maximum junction temperature for an application to determine if load conditions or package types need to be modified to assure operation of the amplifier in a safe operating area. The maximum power dissipation allowed in a package is determined according to: T JMAX – T AMAX PD MAX = -------------------------------------------Θ JA Where: TJMAX = Maximum junction temperature TAMAX = Maximum ambient temperature θJA = Thermal resistance of the package n ∑ ( VOUTi – VS ) × ILOADi PD MAX = V S × I SMAX + i=1 Where: VS = Supply voltage ISMAX = Maximum quiescent supply current VOUT = Maximum output voltage of the application RLOAD = Load resistance tied to ground ILOAD = Load current N = number of amplifiers (Max = 2) By setting the two PDMAX equations equal to each other, we can solve the output current and RLOAD to avoid the device overheat. Power Supply Bypassing Printed Circuit Board Layout As with any high frequency device, a good printed circuit board layout is necessary for optimum performance. Lead lengths should be as short as possible. The power supply pin must be well bypassed to reduce the risk of oscillation. For normal single supply operation, where the VS- pin is connected to the ground plane, a single 4.7µF tantalum capacitor in parallel with a 0.1µF ceramic capacitor from VS+ to GND will suffice. This same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. In this case, the VS- pin becomes the negative supply rail. See Figure 1 for a complete tuned power supply bypass methodology. Printed Circuit Board Layout For good AC performance, parasitic capacitance should be kept to minimum. Use of wire wound resistors should be avoided because of their additional series inductance. Use of sockets should also be avoided if possible. Sockets add parasitic inductance and capacitance that can result in compromised performance. Minimizing parasitic capacitance at the amplifier's inverting input pin is very important. The feedback resistor should be placed very close to the inverting input pin. Strip line design techniques are recommended for the signal traces. The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or: For sourcing: n PD MAX = V S × I SMAX + V OUTi ∑ ( VS – VOUTi ) × ---------------R Li i=1 10 FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 Application Circuits Sullen Key Low Pass Filter Sullen Key High Pass Filter A common and easy to implement filter taking advantage of the wide bandwidth, low offset and low power demands of the EL5152. A derivation of the transfer function is provided for convenience. (See Figure 28.) Again this useful filter benefits from the characteristics of the EL5152. The transfer function is very similar to the low pass so only the results are presented. (See Figure 29.) K = 1+ 5V 1 V1 R2C2s + 1 Vo V1 − Vi Vo − Vi 1 + K − V1 + =0 1 R1 R2 C1s K H(s) = R1C1R2C2s 2 + ((1 − K )R1C1 + R1C2 + R21C2)s + 1 1 H( jw ) = 2 1 − w R1C1R2C2 + jw ((1 − K )R1C1 + R1C2 + R2C2) V2 Vo = K L1 10µH R5 C3 1K 1n C6 1n C1 R1 1K V1 1n 3 U1A R2 + 1K 2 C2 1n Holp = K 4 1 V+ VOUT V- - R7 11 1K C5 RB RA 1K RB RA 1K wo = Q= 1 R1C1R2C2 1 R1C1 R1C2 R2C2 (1 − K ) + + R2C2 R2C1 R1C1 1n R6 1K L3 10µH C4 Holp = K 1 RC 1 Q= 3 −K wo = 1n Equations simplify if we let all components be equal R=C 5V V3 FIGURE 28. SULLEN KEY LOW PASS FILTER 11 FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 5V V2 L1 10µH R5 C3 1K 1n C6 1n Holp = K R8 V1 C7 C9 1n 1n 1K 3 U1A + 2 C2 1n wo = 4 1 V+ V- - Q= VOUT R7 11 1K 1 R1C1R2C2 1 R1C1 R1C2 R2C2 (1 − K ) + + R2C2 R2C1 R1C1 1K C5 RB RA 1K 1n R6 1K Holp = C4 K 4 −K Equations simplify if we let all components be equal R=C 2 wo = RC 1n L3 10µH Q= 2 4 −K 5V V3 FIGURE 29. SULLEN KEY HIGH PASS FILTER Differential Output Instrumentation Amplifier The addition of a third amplifier to the conventional three amplifier Instrumentation Amplifier introduces the benefits of differential signal realization, specifically the advantage of using common mode rejection to remove coupled noise and ground-potential errors inherent in remote transmission. This configuration also provides enhanced bandwidth, wider output swing and faster slew rate than conventional three amplifier solutions with only the cost of an additional amplifier and few resistors. e1 A1 + - R3 R3 A3 R2 + RG e2 + R3 R3 R3 A4 R2 A2 R3 + R3 e o3 = – ( 1 + 2R 2 ⁄ R G ) ( e 1 – e 2 ) eo3 + REF eo eo4 R3 e o4 = ( 1 + 2R 2 ⁄ R G ) ( e 1 – e 2 ) e o = – 2 ( 1 + 2R 2 ⁄ R G ) ( e 1 – e 2 ) 2f C1, 2 BW = ----------------A Di 12 A Di = – 2 ( 1 + 2R 2 ⁄ R G ) FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 Strain Gauge The strain gauge is an ideal application to take advantage of the moderate bandwidth and high accuracy of the EL5152. The operation of the circuit is very straight forward. As the strain variable component resistor in the balanced bridge is subjected to increasing strain its resistance changes resulting in an imbalance in the bridge. A voltage variation from the referenced high accuracy source is generated and translated to the difference amplifier through the buffer stage. This voltage difference as a function of the strain is converted into an output voltage. 5V V2 L1 10µH R5 C3 1K 1n C6 VARIABLE SUBJECT TO STRAIN 1n 1K V5 0V R15 R16 1K R14 1K 22 4 R17 4 1K R18 1K 22 3 U1A + 2 4 1 V+ VOUT (V1+V2+V3+V4) V- - RL 11 1K 1K 1K RF C12 1n R11 C11 1K 1n L4 10µH V4 13 5V FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 MSOP Package Outline Drawing 14 FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 SO Package Outline Drawing 15 FN7385.4 October 3, 2005 EL5152, EL5153, EL5252, EL5455 SOT-23 Package Outline Drawing NOTE: The package drawing shown here may not be the latest version. To check the latest revision, please refer to the Intersil website at http://www.intersil.com/design/packages/index.asp All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 16 FN7385.4 October 3, 2005