AD ADL5519ACPZ-R2 1 mhz to 10 ghz, 62 db dual log detector/controller Datasheet

1 MHz to 10 GHz, 62 dB Dual Log
Detector/Controller
ADL5519
COMR
VPSA
ADJA
VPSR
TEMP
CLPA
VSTA
23
22
21
20
19
18
17
ADL5519
TEMP
INHA 25
INLA 26
CHANNEL A
LOG DETECTOR
COMR 27
PWDN 28
OUTA
OUTB
COMR 29
COMR 30
INLB 31
CHANNEL B
LOG DETECTOR
INHB 32
16
NC
15
OUTA
14
FBKA
13
OUTP
12
OUTN
11
FBKB
10
OUTB
9
NC
3
4
5
6
7
8
VREF
VLVL
CLPB
VSTB
06198-001
2
ADJB
BIAS
1
VPSB
RF transmitter power amplifier linearization and
gain/power control
Power monitoring in radio link transmitters
Dual-channel wireless infrastructure radios
Antenna VSWR monitor
RSSI measurement in base stations, WLAN, WiMAX, radar
24
COMR
APPLICATIONS
FUNCTIONAL BLOCK DIAGRAM
COMR
Wide bandwidth: 1 MHz to 10 GHz
Dual-channel and channel difference output ports
Integrated accurate scaled temperature sensor
62 dB dynamic range (±3 dB)
>50 dB with ±1 dB up to 8 GHz
Stability over temperature: ±0.5 dB (−40oC to +85oC)
Low noise detector/controller outputs
Pulse response time: 6 ns/8 ns (fall time/rise time)
Supply operation: 3.3 V to 5.5 V @ 60 mA
Fabricated using high speed SiGe process
Small footprint, 5 mm × 5 mm, 32-lead LFCSP
Operating temperature range: −40oC to +125oC
COMR
FEATURES
Figure 1.
GENERAL DESCRIPTION
The ADL5519 is a dual-demodulating logarithmic amplifier that
incorporates two AD8317s. It can accurately convert an RF input
signal into a corresponding decibel-scaled output. The ADL5519
provides accurately scaled, independent, logarithmic output voltages for both RF measurement channels. The device has two
additional output ports, OUTP and OUTN, that provide the
measured differences between the OUTA and OUTB channels.
The on-chip channel matching makes the log amp outputs
insensitive to temperature and process variations.
The temperature sensor pin provides a scaled voltage that is
proportional to the temperature over the operating temperature
range of the device.
The ADL5519 maintains accurate log conformance for signals
from 1 MHz to 8 GHz and provides useful operation to 10 GHz.
The ±3 dB dynamic range is typically 62 dB and has a ±1 dB
dynamic range of >50 dB (re: 50 Ω). The ADL5519 has a response
time of 6 ns/8 ns (fall time/rise time) that enables RF burst detection to a pulse rate of greater than 50 MHz. The device provides
unprecedented logarithmic intercept stability vs. ambient
temperature conditions. A supply of 3.3 V to 5.5 V is required
to power the device. Current consumption is typically 60 mA,
and it decreases to less than 1 mA when the device is disabled.
The device is capable of supplying four log amp measurements
simultaneously. Linear-in-dB measurements are provided at OUTA
and OUTB with conveniently scaled slopes of −22 mV/dB. The log
amp difference between OUTA and OUTB is available as differential or single-ended signals at OUTP and OUTN. An optional
voltage applied to VLVL provides a common-mode reference level
to offset OUTP and OUTN above ground. The broadband output
pins can support many system solutions.
Any of the ADL5519 output pins can be configured to provide
a control voltage to a variable gain amplifier (VGA). Special
attention has been paid to minimize the broadband noise of the
output pins so that they can be used for controller applications.
The ADL5519 is fabricated on a SiGe bipolar IC process and is
available in a 5 mm × 5 mm, 32-lead LFCSP with an operating
temperature range of −40°C to +125°C.
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.461.3113
©2008 Analog Devices, Inc. All rights reserved.
ADL5519
TABLE OF CONTENTS
Features .............................................................................................. 1
Basis for Error Calculations ...................................................... 23
Applications....................................................................................... 1
Device Calibration ..................................................................... 24
Functional Block Diagram .............................................................. 1
Adjusting Accuracy Through Choice of Calibration Points...... 24
General Description ......................................................................... 1
Temperature Compensation Adjustment................................ 25
Revision History ............................................................................... 2
Altering the Slope....................................................................... 26
Specifications..................................................................................... 3
Channel Isolation ....................................................................... 26
Absolute Maximum Ratings............................................................ 9
Output Filtering.......................................................................... 27
ESD Caution.................................................................................. 9
Package Considerations............................................................. 27
Pin Configuration and Function Descriptions........................... 10
Operation Above 8 GHz............................................................ 27
Typical Performance Characteristics ........................................... 11
Applications Information .............................................................. 28
Theory of Operation ...................................................................... 19
Measurement Mode ................................................................... 28
Using the ADL5519 ........................................................................ 20
Controller Mode......................................................................... 28
Basic Connections ...................................................................... 20
Automatic Gain Control............................................................ 30
Input Signal Coupling................................................................ 20
Gain-Stable Transmitter/Receiver............................................ 32
Temperature Sensor Interface................................................... 22
Measuring VSWR....................................................................... 34
VREF Interface ........................................................................... 22
Evaluation Board ............................................................................ 36
Power-Down Interface............................................................... 22
Configuration Options .............................................................. 36
Setpoint Interface—VSTA, VSTB............................................. 22
Evaluation Board Schematic and Artwork ............................. 37
Output Interface—OUTA, OUTB............................................ 22
Outline Dimensions ....................................................................... 39
Difference Output—OUTP, OUTN......................................... 23
Ordering Guide .......................................................................... 39
Description of Characterization............................................... 23
REVISION HISTORY
1/08—Revision 0: Initial Version
Rev. 0 | Page 2 of 40
ADL5519
SPECIFICATIONS
Supply voltage, VP = VPSR = VPSA = VPSB = 5 V, CLPF = 1000 pF, TA = 25°C, 50 Ω termination resistor at INHA, INHB, unless otherwise noted.
Table 1.
Parameter
Conditions
SIGNAL INPUT INTERFACE
Specified Frequency Range
DC Common-Mode Voltage
MEASUREMENT MODE,
100 MHz OPERATION
INHA, INHB (Pin 25, Pin 32)
Min
Temperature Sensitivity
Max
Unit
10
VP − 0.7
GHz
V
1670||0.47
51
42
−1
−52
−22
22
0.7
1.37
50
44
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
dB
dB
±0.25
+0.16
−0.6
dB
dB
dB
±0.25
dB
±0.4
dB
±0.25
dB
±0.45
dB
80
60
dB
dB
60
dB
925||0.54
54
49
−2
−56
−22
20.3
0.67
1.34
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
0.001
ADJA (Pin 21) = 0.65 V, ADJB (Pin 4) = 0.7 V; OUTA, OUTB
(Pin 15, Pin 10) shorted to VSTA, VSTB (Pin 17, Pin 8);
OUTP, OUTN (Pin 13, Pin 12) shorted to FBKA, FBKB
(Pin 14, Pin 11), respectively; sinusoidal input signal;
error referred to best-fit line using linear regression
between PINHA, PINHB = −40 dBm and −10 dBm
Input Impedance
OUTA, OUTB ± 1 dB Dynamic Range
OUTA, OUTB Maximum Input Level
OUTA, OUTB Minimum Input Level
OUTA, OUTB, OUTP, OUTN Slope 1
OUTA, OUTB Intercept1
Output Voltage (High Power In)
Output Voltage (Low Power In)
OUTP, OUTN Dynamic Gain Range
Typ
−40°C < TA < +85°C
±1 dB error
±1 dB error
OUTA, OUTB @ PINHA, PINHB = −16 dBm
OUTA, OUTB @ PINHA, PINHB = −40 dBm
±1 dB error
−40°C < TA < +85°C
Deviation from OUTA, OUTB @ 25°C
−40°C < TA < +85°C, PINHA, PINHB = −16 dBm
25°C < TA < 85°C, PINHA, PINHB = −40 dBm
−40°C < TA < +25°C, PINHA, PINHB = −40 dBm
Distribution of OUTP, OUTN from 25°C
25°C < TA < 85°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = −0.09 dB
−40°C < TA < +25°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = 0.25 dB
25°C < TA < 85°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = 0.05 dB
−40°C < TA < +25°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = −0.23 dB
B
B
B
Input A-to-Input B Isolation
Input A-to-OUTB Isolation
Frequency separation = 1 kHz, PINHA = −50 dBm,
Input B-to-OUTA Isolation
Frequency separation = 1 kHz, PINHB = −50 dBm,
PINHA – PINHB when OUTB/Slope = 1 dB
PINHB – PINHA when OUTA/Slope = 1 dB
MEASUREMENT MODE,
900 MHz OPERATION
ADJA = 0.6 V, ADJB = 0.65 V; OUTA, OUTB shorted to
VSTA, VSTB; OUTP, OUTN shorted to FBKA, FBKB, respectively;
sinusoidal input signal; error referred to best fit line using
linear regression between PINHA, PINHB = −40 dBm and −10 dBm
B
Input Impedance
OUTA, OUTB ± 1 dB Dynamic Range
OUTA, OUTB Maximum Input Level
OUTA, OUTB Minimum Input Level
OUTA, OUTB, OUTP, OUTN Slope1
OUTA, OUTB Intercept1
Output Voltage (High Power In)
Output Voltage (Low Power In)
−40°C < TA < +85°C
±1 dB error
±1 dB error
OUTA, OUTB @ PINHA, PINHB = −10 dBm
OUTA, OUTB @ PINHA, PINHB = −40 dBm
Rev. 0 | Page 3 of 40
ADL5519
Parameter
OUTP, OUTN Dynamic Gain Range
Temperature Sensitivity
Conditions
Min
±1 dB error
−40°C < TA < +85°C
Deviation from OUTA, OUTB @ 25°C
−40°C < TA < +85°C, PINHA, PINHB = −16 dBm
25°C < TA < 85°C, PINHA, PINHB = −40 dBm
−40°C < TA < +25°C, PINHA, PINHB = −40 dBm
Distribution OUTP, OUTN from 25°C
25°C < TA < 85°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = −0.08 dB
−40°C < TA < +25°C, PINHA = −16 dBm, PINHB = −30 dBm
typical error = 0.3 dB
25°C < TA < 85°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = 0.17 dB
−40°C < TA < +25°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = −0.19 dB
B
B
B
Input A-to-Input B Isolation
Input A-to-OUTB Isolation
Frequency separation = 1 kHz, PINHA = −50 dBm,
Input B-to-OUTA Isolation
Frequency separation = 1 kHz, PINHB = −50 dBm,
Typ
Max
Unit
55
48
dB
dB
±0.25
+0.25
−0.5
dB
dB
dB
±0.25
dB
±0.4
dB
±0.25
dB
±0.4
dB
75
50
dB
dB
50
dB
525||0.36
55
49
−4
−59
−22
18
0.62
1.28
55
48
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
dB
dB
±0.2
+0.25
−0.5
dB
dB
dB
±0.3
dB
±0.4
dB
±0.3
dB
±0.4
dB
65
46
dB
dB
46
dB
PINHA – PINHB when OUTB/Slope = 1 dB
PINHB – PINHA when OUTA/Slope = 1 dB
MEASUREMENT MODE,
1.9 GHz OPERATION
ADJA = 0.5 V, ADJB = 0.55 V; OUTA, OUTB shorted to
VSTA, VSTB; OUTP, OUTN shorted to FBKA, FBKB, respectively;
sinusoidal input signal; error referred to best fit line using
linear regression between PINHA, PINHB = −40 dBm and −10 dBm
B
Input Impedance
OUTA, OUTB ± 1 dB Dynamic Range
OUTA, OUTB Maximum Input Level
OUTA, OUTB Minimum Input Level
OUTA, OUTB, OUTP, OUTN Slope1
OUTA, OUTB Intercept1
Output Voltage (High Power In)
Output Voltage (Low Power In)
OUTP, OUTN Dynamic Gain Range
Temperature Sensitivity
−40°C < TA < +85°C
±1 dB error
±1 dB error
OUTA, OUTB @ PINHA, PINHB = −10 dBm
OUTA, OUTB @ PINHA, PINHB = −40 dBm
±1 dB error
−40°C < TA < +85°C
Deviation from OUTA, OUTB @ 25°C
−40°C < TA < +85°C, PINHA, PINHB = −16 dBm
25°C < TA < 85°C, PINHA, PINHB = −40 dBm
−40°C < TA < +25°C, PINHA, PINHB = −40 dBm
Distribution of OUTP, OUTN from 25°C
25°C < TA < 85°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = −0.07 dB
−40°C < TA < +25°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = 0.23 dB
25°C < TA < 85°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = 0.16 dB
−40°C < TA < +25°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = −0.22 dB
B
B
B
Input A-to-Input B Isolation
Input A-to-OUTB Isolation
Frequency separation = 1 kHz, PINHA = −50 dBm,
Input B-to-OUTA Isolation
Frequency separation = 1 kHz, PINHB = −50 dBm,
PINHA – PINHB when OUTB/Slope = 1 dB
PINHB – PINHA when OUTA/Slope = 1 dB
Rev. 0 | Page 4 of 40
ADL5519
Parameter
Conditions
MEASUREMENT MODE,
2.2 GHz OPERATION
ADJA = 0.48 V, ADJB = 0.6 V; OUTA, OUTB shorted to
VSTA, VSTB; OUTP, OUTN shorted to FBKA, FBKB, respectively;
sinusoidal input signal; error referred to best fit line using
linear regression between PINHA, PINHB = −40 dBm and −10 dBm
Min
Typ
Max
Unit
B
Input Impedance
OUTA, OUTB ± 1 dB Dynamic Range
OUTA, OUTB Maximum Input Level
OUTA, OUTB Minimum Input Level
OUTA, OUTB, OUTP, OUTN Slope1
OUTA, OUTB Intercept1
Output Voltage (High Power In)
Output Voltage (Low Power In)
OUTP, OUTN Dynamic Gain Range
Temperature Sensitivity
−40°C < TA < +85°C
±1 dB error
±1 dB error
OUTA, OUTB @ PINHA, PINHB = −10 dBm
OUTA, OUTB @ PINHA, PINHB = −40 dBm
±1 dB error
−40°C < TA < +85°C
Deviation from OUTA, OUTB @ 25°C
−40°C < TA < +85°C, PINHA, PINHB = −16 dBm
25°C < TA < 85°C, PINHA, PINHB = −40 dBm
−40°C < TA < +25°C, PINHA, PINHB = −40 dBm
Distribution of OUTP, OUTN from 25°C
25°C < TA < 85°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = −0.07 dB
−40°C < TA < +25°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = 0.25 dB
25°C < TA < 85°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = 0.17 dB
−40°C < TA < +25°C, PINHA = −40 dBm, PINHB = −30 dBm
typical error = −0.22dB
B
B
B
Input A-to-Input B Isolation
Input A-to-OUTB Isolation
Frequency separation = 1 kHz, PINHA = −50 dBm,
Input B-to-OUTA Isolation
Frequency separation = 1 kHz, PINHB = −50 dBm,
408||0.34
55
50
−5
−60
−22
16.9
0.6
1.26
56
40
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
dB
dB
±0.28
+0.3
−0.5
dB
dB
dB
±0.25
dB
±0.4
dB
±0.25
dB
±0.4
dB
60
46
dB
dB
46
dB
187||0.66
54
44
−4
−58
−22.5
17
0.62
1.31
52
42
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
dB
dB
PINHA – PINHB when OUTB/Slope = 1 dB
PINHB – PINHA when OUTA/Slope = 1 dB
MEASUREMENT MODE,
3.6 GHz OPERATION
ADJA = 0.35 V ADJB = 0.42; OUTA, OUTB shorted to
VSTA, VSTB; OUTP, OUTN shorted to FBKA, FBKB, respectively;
sinusoidal input signal; error referred to best fit line using
linear regression between PINHA, PINHB = −40 dBm and −10 dBm
B
Input Impedance
OUTA, OUTB ± 1 dB Dynamic Range
OUTA, OUTB Maximum Input Level
OUTA, OUTB Minimum Input Level
OUTA, OUTB, OUTP, OUTN Slope1
OUTA, OUTB Intercept1
Output Voltage (High Power In)
Output Voltage (Low Power In)
OUTP, OUTN Dynamic Gain Range
−40°C < TA < +85°C
±1 dB error
±1 dB error
OUTA, OUTB @ PINHA, PINHB = −10 dBm
OUTA, OUTB @ PINHA, PINHB = −40 dBm
±1 dB error
−40°C < TA < +85°C
Rev. 0 | Page 5 of 40
ADL5519
Parameter
Temperature Sensitivity
Conditions
Min
Deviation from OUTA, OUTB @ 25°C
−40°C < TA < +85°C, PINHA, PINHB = −16 dBm
25°C < TA < 85°C, PINHA, PINHB = −40 dBm
−40°C < TA < +25°C, PINHA, PINHB = −40 dBm
Distribution of OUTP, OUTN from 25°C
25°C < TA < 85°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = −0.07 dB
−40°C < TA < +25°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = 0.27 dB
25°C < TA < 85°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = 0.31 dB
−40°C < TA < +25°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = −0.14 dB
B
B
B
Input A-to-Input B Isolation
Input A-to-OUTB Isolation
Frequency separation = 1 kHz, PINHA = −50 dBm,
Input B-to-OUTA Isolation
Frequency separation = 1 kHz, PINHB = −50 dBm,
Typ
Max
Unit
±0.4
+0.6
−0.45
dB
dB
dB
±0.25
dB
±0.45
dB
±0.3
dB
±0.5
dB
40
20
dB
dB
20
dB
28||1.19
53
45
−2
−55
−22.5
20
0.68
1.37
53
46
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
dB
dB
±0.25
+0.25
−0.4
dB
dB
dB
±0.3
dB
±0.4
dB
±0.3
dB
±0.5
dB
45
48
dB
dB
48
dB
PINHA – PINHB when OUTB/Slope = 1 dB
PINHB – PINHA when OUTA/Slope = 1 dB
MEASUREMENT MODE,
5.8 GHz OPERATION
ADJA = 0.58 V, ADJB = 0.7 V; OUTA, OUTB shorted to
VSTA, VSTB; OUTP, OUTN shorted to FBKA, FBKB respectively;
sinusoidal input signal; error referred to best fit line using
linear regression between PINHA, PINHB = −40 dBm and −20 dBm
B
Input Impedance
OUTA, OUTB ± 1 dB Dynamic Range
OUTA, OUTB Maximum Input Level
OUTA, OUTB Minimum Input Level
OUTA, OUTB, OUTP, OUTN Slope1
OUTA, OUTB Intercept1
Output Voltage (High Power In)
Output Voltage (Low Power In)
OUTP, OUTN Dynamic Gain Range
Temperature Sensitivity
−40°C < TA < +85°C
±1 dB error
±1 dB error
OUTA, OUTB @ PINHA, PINHB = −10 dBm
OUTA, OUTB @ PINHA, PINHB = −40 dBm
±1 dB error
−40°C < TA < +85°C
Deviation from OUTA, OUTB @ 25°C
−40°C < TA < +85°C, PINHA, PINHB = −16dBm
25°C < TA < 85°C, PINHA, PINHB = −40 dBm
−40°C < TA < +25°C, PINHA, PINHB = −40 dBm
Distribution of OUTP, OUTN from 25°C
25°C < TA < 85°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = 0.02 dB
−40°C < TA < +25°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = 0.25 dB
25°C < TA < 85°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = 0.13 dB
−40°C < TA < +25°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = 0.06 dB
B
B
B
Input A-to-Input B Isolation
Input A-to-OUTB Isolation
Frequency separation = 1 kHz, PINHA = −50 dBm,
Input B-to-OUTA Isolation
Frequency separation = 1 kHz, PINHB = −50 dBm,
PINHA – PINHB when OUTB/Slope = 1 dB
PINHB – PINHA when OUTA/Slope = 1 dB
Rev. 0 | Page 6 of 40
ADL5519
Parameter
Conditions
MEASUREMENT MODE,
8 GHz OPERATION
ADJA = 0.72 V, ADJB = 0.82 V to GND; OUTA, OUTB shorted
to VSTA, VSTB; OUTP, OUTN shorted to FBKA, FBKB, respectively;
sinusoidal input signal; error referred to best fit line using
linear regression between PINHA, PINHB = −40 dBm and −20 dBm
Min
Typ
Max
Unit
B
Input Impedance
OUTA, OUTB ± 1 dB Dynamic Range
OUTA, OUTB Maximum Input Level
OUTA, OUTB Minimum Input Level
OUTA, OUTB, OUTP, OUTN Slope1
OUTA, OUTB Intercept1
Output Voltage (High Power In)
Output Voltage (Low Power In)
OUTP, OUTN Dynamic Gain Range
Temperature Sensitivity
−40°C < TA < +85°C
±1 dB error
±1 dB error
OUTA, OUTB @ PINHA, PINHB = −10 dBm
OUTA, OUTB @ PINHA, PINHB = −40 dBm
±1 dB error
−40°C < TA < +85°C
Deviation from OUTA, OUTB @ 25°C
−40°C < TA < +85°C, PINHA, PINHB = −16 dBm
25°C < TA < 85°C, PINHA, PINHB = −40 dBm
−40°C < TA < +25°C, PINHA, PINHB = −40 dBm
Distribution of OUTP, OUTN from 25°C
25°C < TA < 85°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = 0.2dB
−40°C < TA < +25°C, PINHA = −16 dBm, PINHB = −30 dBm,
typical error = 0.09dB
25°C < TA < 85°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = −0.07dB
−40°C < TA < +25°C, PINHA = −40 dBm, PINHB = −30 dBm,
typical error = 0.17 dB
B
B
B
Input A-to-Input B Isolation
Input A-to-OUTB Isolation
Frequency separation = 1 kHz, PINHA = −50 dBm,
Input B-to-OUTA Isolation
Frequency separation = 1 kHz, PINHB = −50 dBm,
+10||−1.92
48
38
0
−48
−22
26
0.81
1.48
50
42
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
dB
dB
±0.4
−0.1
+0.5
dB
dB
dB
±0.3
dB
±0.5
dB
±0.3
dB
±0.5
dB
45
30
dB
dB
30
dB
0.3
VP − 0.4
0.09
VP − 0.15
10
1
10
V
V
V
V
mA
nF
nV/√Hz
12
ns
6
ns
16
ns
8
ns
10
MHz
0.38
1.6
40
V
V
kΩ
PINHA – PINHB when OUTB/Slope = 1 dB
PINHB – PINHA when OUTA/Slope = 1 dB
OUTPUT INTERFACE
OUTA, OUTB Voltage Range
OUTP, OUTN Voltage Range
Source/Sink Current
Capacitance Drive
Output Noise
Fall Time
Rise Time
Video Bandwidth
(or Envelope Bandwidth)
SETPOINT INTERFACE
Nominal Input Range
Input Resistance
OUTA, OUTB; OUTP, OUTN
VSTA, VSTB = 1.7 V, RF in = open
VSTA, VSTB = 0 V, RF in = open
FBKA, FBKB = open and OUTA < OUTB, RL ≥ 240 Ω to ground
FBKA, FBKB = open and OUTA > OUTB, RL ≥ 240 Ω to ground
Output held at 1 V to 1% change
INHA, INHB = 2.2 GHz, −10 dBm, fNOISE = 100 kHz,
CLPA, CLPB = open
Input level = no signal to −10 dBm, 80% to 20%,
CLPA, CLPB = 10 pF
Input level = no signal to −10 dBm, 80% to 20%,
CLPA, CLPB = open
Input level = −10 dBm to no signal, 20% to 80%,
CLPA, CLPB = 10 pF
Input level = −10 dBm to no signal, 20% to 80%,
CLPA, CLPB = open
VSTA, VSTB
Input level = 0 dBm, measurement mode
Input level = –50 dBm, measurement mode
Controller mode, sourcing 50 μA
Rev. 0 | Page 7 of 40
ADL5519
Parameter
Conditions
DIFFERENCE LEVEL ADJUST
Input Voltage
Input Resistance
TEMPERATURE COMPENSATION
Input Resistance
Disable Threshold Voltage
VOLTAGE REFERENCE
Output Voltage
Temperature Sensitivity
VLVL (Pin 6)
OUTP, OUTN = FBKA, FBKB
OUTP, OUTN = FBKA, FBKB
ADJA, ADJB
ADJA, ADJB = 0.9 V, sourcing 50 μA
ADJA, ADJB = open
VREF (Pin 5)
Current Limit Source/Sink
TEMPERATURE REFERENCE
Output Voltage
Temperature Sensitivity
Current Limit Source/Sink
POWER-DOWN INTERFACE
Logic Level to Enable
Logic Level to Disable
Input Current
Enable Time
Disable Time
POWER INTERFACE
Supply Voltage
Quiescent Current
vs. Temperature
Disable Current
1
Min
−40°C < TA < +25°C; relative TA = 25°C
25°C < TA < 85°C; relative TA = 25°C
Typ
Max
Unit
VP − 1
100
V
kΩ
13
VP − 0.4
kΩ
V
1.15
+26
−26
3/3
V
μV/°C
μV/°C
mA
1.36
4.5
4/50
V
mV/°C
mA/μA
0
VP − 0.2
2
20
0.4
V
V
μA
μA
μs
0.25
μs
TEMP (Pin 19)
−40°C < TA < +125°C
PWDN (Pin 28)
Logic low enables
Logic high disables
Logic high PWDN = 5 V
Logic low PWDN = 0 V
PWDN low to OUTA, OUTB at 100% final value,
CLPA, CLPB = open, RF in = −10 dBm
PWDN high to OUTA, OUTB at 10% final value,
CLPA, CLPB = open, RF in = 0 dBm
VPSA, VPSB, VPSR
3.3
−40°C ≤ TA ≤ +85°C
ADJA, ADJB = PWDN = VP
5.5
60
147
<1
Slope and intercept are determined by calculating the best-fit line between the power levels of −40 dBm and −10 dBm at the specified input frequency.
Rev. 0 | Page 8 of 40
V
mA
μA/°C
mA
ADL5519
ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter
Supply Voltage: VPSA, VPSB, VPSR
VSET Voltage: VSTA, VSTB
Input Power (Single-Ended, Re: 50 Ω)
INHA, INLA, INHB, INLB
Internal Power Dissipation
θJA
Maximum Junction Temperature
Operating Temperature Range
Storage Temperature Range
Lead Temperature (Soldering, 60 sec)
Rating
5.7 V
0 to VP
12 dBm
420 mW
42°C/W
142°C
−40°C to +125°C
−65°C to +150°C
260°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
ESD CAUTION
Rev. 0 | Page 9 of 40
ADL5519
32
31
30
29
28
27
26
25
INHB
INLB
COMR
COMR
PWDN
COMR
INLA
INHA
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
PIN 1
INDICATOR
ADL5519
TOP VIEW
(Not to Scale)
NC
OUTB
FBKB
OUTN
OUTP
FBKA
OUTA
NC
NC = NO CONNECT
24
23
22
21
20
19
18
17
COMR
COMR
VPSA
ADJA
VPSR
TEMP
CLPA
VSTA
06198-002
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
COMR
COMR
VPSB
ADJB
VREF
VLVL
CLPB
VSTB
Figure 2. Pin Configuration
Table 3. Pin Function Descriptions
Pin No.
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
Mnemonic
COMR
COMR
VPSB
ADJB
VREF
VLVL
CLPB
VSTB
NC
OUTB
FBKB
OUTN
OUTP
FBKA
OUTA
NC
VSTA
CLPA
TEMP
VPSR
ADJA
VPSA
COMR
COMR
INHA
INLA
COMR
PWDN
COMR
COMR
INLB
INHB
Paddle
Description
Connect via low impedance to common.
Connect via low impedance to common.
Positive Supply for Channel B. Apply 3.3 V to 5.5 V supply voltage.
Dual-Function Pin: Temperature Adjust Pin for Channel B and Power-Down Interface for OUTB.
Voltage Reference (1.15 V).
DC Common-Mode Adjust for Difference Output.
Loop Filter Pin for Channel B.
Setpoint Control Input for Channel B.
No Connect.
Output Voltage for Channel B.
Difference Op Amp Feedback Pin for OUTN Op Amp.
Difference Output (OUTB − OUTA + VLVL).
Difference Output (OUTA − OUTB + VLVL).
Difference Op Amp Feedback Pin for OUTP Op Amp.
Output Voltage for Channel A.
No Connect.
Setpoint Control Input for Channel A.
Loop Filter Pin for Channel A.
Temperature Sensor Output (1.3 V with 4.5 mV/°C Slope).
Positive Supply for Difference Outputs and Temperature Sensor. Apply 3.3 V to 5.5 V supply voltage.
Dual-Function Pin: Temperature Adjust Pin for Channel A and Power-Down Interface for OUTA.
Positive Supply for Channel A. Apply 3.3 V to 5.5 V supply voltage.
Connect via low impedance to common.
Connect via low impedance to common.
AC-Coupled RF Input for Channel A.
AC-Coupled RF Common for Channel A.
Connect via low impedance to common.
Power-Down for Difference Output and Temperature Sensor.
Connect via low impedance to common.
Connect via low impedance to common.
AC-Coupled RF Common for Channel B.
AC-Coupled RF Input for Channel B.
Internally connected to COMR.
Rev. 0 | Page 10 of 40
ADL5519
TYPICAL PERFORMANCE CHARACTERISTICS
1.25
0.5
1.00
0
0.75
–0.5
0.50
–1.0
0.25
–1.5
0
–60
–50
–40
–30
–20
–10
–2.0
10
0
OUTP
PIN (dBm)
Figure 3. OUTA, OUTB Voltage and Log Conformance vs. Input Amplitude
at 100 MHz, Typical Device, ADJA, ADJB = 0.65 V, 0.7 V, Sine Wave,
Single-Ended Drive
0
1.0
P
–1.0
0.5
0
–60
–50
–40
–30
–20
–10
–2.0
10
0
PIN (dBm)
Figure 6. OUTP, OUTN Gain Error and Voltage vs. Input Amplitude at 100 MHz,
Typical Device, ADJA, ADJB = 0.65 V, 0.7, Sine Wave, Single-Ended Drive,
PINHB = −30 dBm, Channel A Swept
B
2.0
1.5
OUTP – OUTN OUTPUT VOLTAGE (V)
1.5
1.0
ERROR (dB)
1.0
N
2.0
0.5
0
–0.5
–1.0
–50
–40
–30
–20
–10
0
10
PIN (dBm)
1.0
Figure 4. Distribution of OUTA, OUTB Error over Temperature After Ambient
Normalization vs. Input Amplitude for 45 Devices, Frequency = 100 MHz,
ADJA, ADJB = 0.65 V, 0.7 V, Sine Wave, Single-Ended Drive
1.0
0.5
0
0
–0.5
–1.0
–1.0
–1.5
–2.0
–60
06198-004
–1.5
–2.0
–60
OUTN
1.5
ERROR (dB)
1.0
06198-006
1.50
ERROR (dB)
1.5
–2.0
–50
–40
–30
–20
–10
0
10
PIN (dBm)
06198-007
1.75
2.0
2.0
OUTP, OUTN OUTPUT VOLTAGE (V)
2.0
ERROR (dB)
2.00
06198-003
OUTPUT VOLTAGE (V)
VP = 5 V; TA = +25°C, −40°C, +85°C; CLPA, CLPB = 1 μF. Colors: +25°C black, −40°C blue, +85°C red.
Figure 7. Distribution of [OUTP − OUTN] Gain Error and Voltage vs. Input
Amplitude over Temperature, After Ambient Normalization for 45 Devices from
a Nominal Lot, Frequency = 100 MHz, ADJA, ADJB = 0.65 V, 0.7 V, Sine Wave,
Single-Ended Drive, PINHB = −30 dBm, Channel A Swept
1.5
1.75
1.5
1.0
1.50
1.0
1.25
0.5
1.00
0
0.75
–0.5
0.50
–1.0
0.25
–1.5
0.5
0
–0.5
–1.0
–2.0
–60
–50
–40
–30
–20
PIN (dBm)
–10
0
10
0
–60
06198-005
–1.5
Figure 5. Distribution of [OUTA − OUTB] Voltage Difference over Temperature
for 45 Devices from a Nominal Lot, Frequency = 100 MHz,
ADJA, ADJB = 0.65 V, 0.7 V, Sine Wave, Single-Ended Drive
–50
–40
–30
–20
–10
0
ERROR (dB)
2.0
–2.0
10
PIN (dBm)
Figure 8. OUTA, OUTB Voltage and Log Conformance vs. Input Amplitude
at 900 MHz, Typical Device, ADJA, ADJB = 0.6 V, 0.65 V, Sine Wave,
Single-Ended Drive
Rev. 0 | Page 11 of 40
06198-008
2.00
OUTPUT VOLTAGE (V)
OUTA – OUTB (V)
B
2.0
ADL5519
–1.0
–50
–40
–30
–20
–10
0
10
PIN (dBm)
0.5
0
0
–0.5
–1.0
–1.0
–1.5
–2.0
–60
06198-009
–2.0
–60
1.0
1.0
ERROR (dB)
0
1.5
–50
–40
–30
–20
–10
–2.0
10
0
06198-012
1.0
ERROR (dB)
2.0
2.0
OUTP – OUTN OUTPUT VOLTAGE (V)
2.0
PIN (dBm)
Figure 9. Distribution of OUTA, OUTB Error over Temperature After Ambient
Normalization vs. Input Amplitude for 45 Devices, Frequency = 900 MHz,
ADJA, ADJB = 0.6 V, 0.65 V, Sine Wave, Single-Ended Drive
Figure 12. Distribution of [OUTP − OUTN] Gain Error and Voltage vs. Input
Amplitude over Temperature, After Ambient Normalization for 45 Devices
from a Nominal Lot, Frequency = 900 MHz, ADJA, ADJB = 0.6 V, 0.65 V, Sine
Wave, Single-Ended Drive, PINHB = −30 dBm, Channel A Swept
0.20
2.0
2.0
1.5
1.0
1.0
0
0.5
–1.0
OUTPUT VOLTAGE (V)
OUTA – OUTB (V)
0.10
0.05
0
–0.05
–0.10
ERROR (dB)
0.15
–0.15
–40
–30
–20
–10
0
10
PIN (dBm)
0
–60
–30
–20
–10
–2.0
10
0
PIN (dBm)
2.0
2.0
1.0
1.0
OUTN
1.5
0.5
0
–60
–1.0
–1.0
–50
–40
–30
–20
–10
0
0
–2.0
10
–2.0
–60
PIN (dBm)
Figure 11. OUTP, OUTN Gain Error and Voltage vs. Input Amplitude at
900 MHz, Typical Device, ADJA, ADJB = 0.6 V, 0.65 V, Sine Wave,
Single-Ended Drive; PINHB = −30 dBm, Channel A Swept
–50
–40
–30
–20
PIN (dBm)
–10
0
10
06198-014
0
P
ERROR (dB)
1.0
ERROR (dB)
N
06198-011
OUTP, OUTN OUTPUT VOLTAGE (V)
OUTP
–40
Figure 13. OUTA, OUTB Voltage and Log Conformance vs. Input Amplitude at
1.9 GHz, Typical Device, ADJA, ADJB = 0.5 V, 0.55 V, Sine Wave,
Single-Ended Drive
Figure 10. Distribution of [OUTA − OUTB] Voltage Difference over
Temperature for 45 Devices from a Nominal Lot, Frequency = 900 MHz,
ADJA, ADJB = 0.6 V, 0.65 V, Sine Wave, Single-Ended Drive
2.0
–50
06198-013
–50
06198-010
–0.20
–60
Figure 14. Distribution of OUTA, OUTB Error over Temperature After Ambient
Normalization vs. Input Amplitude for 45 Devices, Frequency = 1.9 GHz,
ADJA, ADJB = 0.5 V, 0.55 V, Sine Wave, Single-Ended Drive
Rev. 0 | Page 12 of 40
ADL5519
0.20
2.0
2.0
1.5
1.0
1.0
0
0.5
–1.0
OUTPUT VOLTAGE (V)
OUTA – OUTB (V)
0.10
0.05
0
–0.05
–0.10
ERROR (dB)
0.15
–0.15
–40
–30
–20
–10
0
10
0
–60
PIN (dBm)
–30
–20
–10
–2.0
10
0
Figure 18. OUTA, OUTB Voltage and Log Conformance vs. Input Amplitude at
2.2 GHz, Typical Device, ADJA, ADJB = 0.48 V, 0.6 V, Sine Wave,
Single-Ended Drive
2.0
2.0
1.0
1.0
OUTN
1.5
ERROR (dB)
0
P
0.5
0
–1.0
–1.0
0
–60
–50
–40
–30
–20
–10
–2.0
10
0
–2.0
–60
PIN (dBm)
Figure 16. OUTP, OUTN Gain Error and Voltage vs. Input Amplitude at
1.9 GHz, with B Input Held at −30 dBm and A Input Swept, Typical Device,
ADJA, ADJB = 0.5 V, 0.55 V, Sine Wave, Single-Ended Drive,
PINHB = −30 dBm, Channel A Swept
–50
–40
–30
–20
–10
0
10
PIN (dBm)
06198-019
1.0
ERROR (dB)
N
06198-016
OUTP, OUTN OUTPUT VOLTAGE (V)
OUTP
–40
PIN (dBm)
Figure 15. Distribution of [OUTA – OUTB] Voltage Difference over
Temperature for 45 Devices from a Nominal Lot, Frequency = 1.9 GHz,
ADJA, ADJB = 0.5 V, 0.55 V, Sine Wave, Single-Ended Drive
2.0
–50
06198-018
–50
06198-015
–0.20
–60
Figure 19. Distribution of OUTA, OUTB Error over Temperature After Ambient
Normalization vs. Input Amplitude for at Least 45 Devices from a Nominal Lot,
Frequency = 2.2 GHz, ADJA, ADJB = 0.48 V, 0.6 V, Sine Wave, Single-Ended Drive
B
2.0
0.20
0.15
1.5
1.0
0
0
–0.5
OUTA – OUTB (V)
0.5
0.10
ERROR (dB)
1.0
–1.0
–1.0
0
–0.05
–0.15
–50
–40
–30
–20
PIN (dBm)
–10
0
–2.0
10
Figure 17. Distribution of [OUTP − OUTN] Gain Error and Voltage vs. Input
Amplitude over Temperature, After Ambient Normalization for 45 Devices
from a Nominal Lot, Frequency = 1.9 GHz, ADJA, ADJB = 0.5 V, 0.55 V,
Sine Wave, Single-Ended Drive, PINHB = −30 dBm, Channel A Swept
B
Rev. 0 | Page 13 of 40
–0.20
–60
–50
–40
–30
–20
–10
0
10
PIN (dBm)
Figure 20. Distribution of [OUTA – OUTB] Voltage Difference over
Temperature for 45 Devices from a Nominal Lot, Frequency = 2.2 GHz,
ADJA, ADJB = 0.48 V, 0.6 V, Sine Wave, Single-Ended Drive
06198-020
–1.5
–60
0.05
–0.10
06198-017
OUTP – OUTN OUTPUT VOLTAGE (V)
2.0
ADL5519
OUTP
2.0
2.0
1.0
1.0
OUTN
1.5
ERROR (dB)
0
P
0.5
–1.0
–50
–40
–30
–20
–10
–1.0
–2.0
10
0
PIN (dBm)
Figure 21. OUTP, OUTN Gain Error and Voltage vs. Input Amplitude at 2.2 GHz,
Typical Device, ADJA, ADJB = 0.48 V, 0.6 V, Sine Wave, Single-Ended Drive,
PINHB = −30 dBm, Channel A Swept
–30
–20
–10
0
10
0.20
0.15
1.5
0.10
ERROR (dB)
0.5
0
0
–0.5
OUTA – OUTB (V)
1.0
1.0
0.05
0
–0.05
–0.10
–1.0
–1.0
–0.15
–50
–40
–30
–20
–10
0
–2.0
10
–0.20
–60
06198-022
–1.5
–60
–40
PIN (dBm)
2.0
2.0
–50
Figure 24. Distribution of OUTA, OUTB Error over Temperature After Ambient
Normalization vs. Input Amplitude for 45 Devices from a Nominal Lot,
Frequency = 3.6 GHz, ADJA, ADJB = 0.35 V, 0.42 V, Sine Wave,
Single-Ended Drive
B
OUTP – OUTN OUTPUT VOLTAGE (V)
–2.0
–60
PIN (dBm)
–50
–40
–30
–20
–10
0
06198-025
0
–60
0
06198-024
1.0
ERROR (dB)
N
06198-021
OUTP, OUTN OUTPUT VOLTAGE (V)
2.0
10
PIN (dBm)
Figure 25. Distribution of [OUTA – OUTB] Voltage Difference over
Temperature for 45 Devices from a Nominal Lot, Frequency = 3.6 GHz,
ADJA, ADJB = 0.35 V, 0.42 V, Sine Wave, Single-Ended Drive
Figure 22. Distribution of [OUTP − OUTN] Gain Error and Voltage vs. Input
Amplitude over Temperature, After Ambient Normalization for 45 Devices
from a Nominal Lot, Frequency = 2.2 GHz, ADJA, ADJB = 0.48 V, 0.6 V,
Sine Wave, Single-Ended Drive, PINHB = −30 dBm, Channel A Swept
0
1.0
–1.0
0.5
0
–60
–50
–40
–30
–20
PIN (dBm)
–10
0
–2.0
10
OUTP
Figure 23. OUTA, OUTB Voltage and Log Conformance vs. Input Amplitude
at 3.6 GHz, Typical Device, ADJA, ADJB = 0.35 V, 0.42 V, Sine Wave,
Single-Ended Drive
OUTN
1.5
1.0
N
1.0
0
P
0.5
0
–60
ERROR (dB)
1.0
2.0
–1.0
–50
–40
–30
–20
–10
0
–2.0
10
PIN (dBm)
Figure 26. OUTP, OUTN Gain Error and Voltage vs. Input Amplitude at
3.6 GHz, Typical Device, ADJA, ADJB = 0.35 V, 0.42 V, Sine Wave,
Single-Ended Drive; PINHB = −30 dBm, Channel A Swept
Rev. 0 | Page 14 of 40
06198-026
1.5
2.0
OUTP, OUTN OUTPUT VOLTAGE (V)
2.0
ERROR (dB)
2.0
06198-023
OUTPUT VOLTAGE (V)
B
ADL5519
2.0
0.20
0.15
1.0
0.10
1.0
ERROR (dB)
0
0
OUTA – OUTB (V)
0.5
–0.5
0.05
0
–0.05
–0.10
–1.0
–1.0
–1.5
–60
–50
–40
–30
–20
–10
–2.0
10
0
–0.20
–60
PIN (dBm)
–50
–40
–30
–20
–10
0
10
PIN (dBm)
Figure 27. Distribution of [OUTP − OUTN] Gain Error and Voltage vs. Input
Amplitude over Temperature, After Ambient Normalization for 45 Devices
from a Nominal Lot, Frequency = 3.6 GHz, ADJA, ADJB = 0.35 V, 0.42 V,
Sine Wave, Single-Ended Drive, PINHB = −30 dBm, Channel A Swept
06198-130
–0.15
06198-027
OUTP – OUTN OUTPUT VOLTAGE (V)
1.5
Figure 30. Distribution of [OUTA – OUTB] Voltage Difference over
Temperature for 45 Devices from a Nominal Lot, Frequency = 5.8 GHz,
ADJA, ADJB = 0.58 V, 0.7 V, Sine Wave, Single-Ended Drive
2.0
2.00
1.75
1.5
1.75
0.75
–0.5
0.50
–1.0
0.25
–1.5
0
–60
–50
–40
–30
–20
–10
–2.0
10
0
PIN (dBm)
N
–50
–40
–30
–20
PIN (dBm)
–10
0
10
06198-101
–2.0
–60
Figure 29. Distribution of OUTA, OUTB Error over Temperature After Ambient
Normalization vs. Input Amplitude for at Least 15 Devices from Multiple Lots,
Frequency = 5.8 GHz, ADJA, ADJB = 0.58 V, 0.7 V,
Sine Wave, Single-Ended Drive
0
0.75
–0.5
0.50
–1.0
0.25
–1.5
–50
–40
–30
–20
–10
0
–2.0
10
PIN (dBm)
Figure 31. OUTP, OUTN Gain Error and Voltage vs. Input Amplitude at
5.8 GHz, Typical Device, ADJA, ADJB = 0.58 V, 0.7 V, Sine Wave,
Single-Ended Drive, PINHB = −30 dBm, Channel A Swept
OUTP – OUTN OUTPUT VOLTAGE (V)
ERROR (dB)
–1.0
P
1.00
2.0
0
0.5
1.25
0
–60
Figure 28. OUTA, OUTB Voltage and Log Conformance vs. Input Amplitude at
5.8 GHz, Typical Device, ADJA, ADJB = 0.58 V, 0.7 V, Sine Wave,
Single-Ended Drive
1.0
1.0
1.50
ERROR (dB)
0
OUTN
2.0
2.0
1.5
1.5
1.0
1.0
0.5
0.5
0
0
–0.5
–0.5
–1.0
–1.0
–1.5
–1.5
–2.0
–60
–50
–40
–30
–20
PIN (dBm)
–10
0
–2.0
10
ERROR (dB)
1.00
1.5
OUTP
06198-105
0.5
1.25
ERROR (dB)
1.0
1.50
2.0
06198-131
OUTP, OUTN OUTPUT VOLTAGE (V)
2.00
06198-102
OUTPUT VOLTAGE (V)
B
Figure 32. Distribution of [OUTP − OUTN] Gain Error and Voltage vs. Input
Amplitude over Temperature, After Ambient Normalization for 45 Devices
from a Nominal Lot, Frequency = 5.8 GHz, ADJA, ADJB = 0.58 V, 0.7 V,
Sine Wave, Single-Ended Drive, PINHB = −30 dBm, Channel A Swept
Rev. 0 | Page 15 of 40
B
2.0
2.00
1.75
1.5
1.75
0
0.75
–0.5
0.50
–1.0
0.25
–1.5
0
–60
–50
–40
–30
–20
–10
–2.0
10
0
PIN (dBm)
Figure 33. OUTA, OUTB Voltage and Log Conformance vs. Input Amplitude at
8 GHz, Typical Device, ADJA, ADJB = 0.72 V, 0.82 V, Sine Wave,
Single-Ended Drive
1.25
0.5
1.00
0
P
0.75
–0.5
0.50
–1.0
0.25
–1.5
–50
–40
–30
–20
–10
–2.0
10
0
PIN (dBm)
Figure 36. OUTP, OUTN Gain Error and Voltage vs. Input Amplitude at 8 GHz,
Typical Device, ADJA, ADJB = 0.72 V, 0.82 V, Sine Wave, Single-Ended Drive,
PINHB = −30 dBm, Channel A Swept
B
2.0
1.5
OUTP – OUTN OUTPUT VOLTAGE (V)
1.5
1.0
ERROR (dB)
N
0
–60
2.0
0.5
0
–0.5
–1.0
–50
–40
–30
–20
–10
0
10
PIN (dBm)
Figure 34. Distribution of OUTA, OUTB Error over Temperature After Ambient
Normalization vs. Input Amplitude for 45 Devices from a Nominal Lot,
Frequency = 8 GHz, ADJA, ADJB = 0.72 V, 0.82 V, Sine Wave,
Single-Ended Drive
1.0
1.0
0.5
0
0
–0.5
–1.0
–1.0
–1.5
–2.0
–60
06198-106
–1.5
–2.0
–60
1.0
1.50
ERROR (dB)
1.00
OUTN
ERROR (dB)
0.5
1.5
OUTP
–50
–40
–30
–20
–10
–2.0
10
0
PIN (dBm)
Figure 37. Distribution of [OUTP − OUTN] Gain Error and Voltage vs. Input
Amplitude over Temperature, After Ambient Normalization for 45 Devices
from a Nominal Lot, Frequency = 8 GHz, ADJA, ADJB = 0.72 V, 0.82 V,
Sine Wave, Single-Ended Drive, PINHB = −30 dBm, Channel A Swept
B
0.20
j1
0.15
j2
j0.5
0.05
j0.2
0
100MHz
–0.05
0
–0.10
0.2
0.5
1
2
900MHz
1900MHz
2200MHz
–0.15
–40
–30
–20
PIN (dBm)
–10
0
10
3600MHz
06198-135
–j0.2
–50
3600MHz
–j0.5
Figure 35. Distribution of [OUTA − OUTB] Voltage Difference over
Temperature for 45 Devices from a Nominal Lot, Frequency = 8 GHz,
ADJA, ADJB = 0.72 V, 0.82 V, Sine Wave, Single-Ended Drive
–j1
–j2
06198-138
OUTA – OUTB (V)
0.10
–0.20
–60
06198-110
1.25
ERROR (dB)
1.0
1.50
2.0
06198-136
OUTP, OUTN OUTPUT VOLTAGE (V)
2.00
06198-107
OUTPUT VOLTAGE (V)
ADL5519
Figure 38. Single-Ended Input Impedance (S11) vs. Frequency; ZO = 50 Ω
Rev. 0 | Page 16 of 40
ADL5519
10µ
MEAN: 1.14986
1200
OUTPUT NOISE (V/ Hz)
1000
COUNT
800
600
400
INHA = 0dBm
INHB = 0dBm
INHA = –20dBm
INHB = –20dBm
INHA = –40dBm
INHB = –40dBm
INHA = OFF
INHB = OFF
1µ
100n
10n
1.12
1.14
1.16
1n
1k
06198-029
0
1.18
VREF (V)
10µ
MEAN: 1.36332
OUTPUT NOISE (V/ Hz)
1000
800
COUNT
100k
1M
10M
100M
FREQUENCY (Hz)
Figure 42. Noise Spectral Density of OUTA, OUTB; CLPA, CLPB = Open
Figure 39. Distribution of VREF Pin Voltage for 4000 Devices
1200
10k
06198-142
200
600
400
OUTN, INHA = 0dBm
OUTP, INHA = 0dBm
OUTN, INHA = –20dBm
OUTP, INHA = –20dBm
OUTN, INHA = –40dBm
OUTP, INHA = –40dBm
OUTN, INHA = OFF
OUTP, INHA = OFF
1µ
100n
10n
1.32
1.34
1.36
1.38
1.40
1.42
TEMP (V)
1n
1k
06198-030
0
1.30
100k
1M
10M
100M
FREQUENCY (Hz)
Figure 43. Noise Spectral Density of OUTP, OUTN; CLPA, CLPB = 0.1 μF,
Frequency = 2140 MHz
Figure 40. Distribution of TEMP Pin Voltage for 4000 Devices
10µ
1.170
1.165
OUTPUT NOISE (V/ Hz)
1.160
1.155
VREF (V)
10k
06198-143
200
1.150
1.145
1.140
1.135
INHA = 0dBm
INHB = 0dBm
INHA = –20dBm
INHB = –20dBm
INHA = –40dBm
INHB = –40dBm
INHA = OFF
INHB = OFF
1µ
100n
10n
1.130
–15
10
35
TEMPERATURE (°C)
60
85
1n
1k
06198-141
1.120
–40
Figure 41. Change in VREF Pin Voltage vs. Temperature for 45 Devices
10k
100k
1M
FREQUENCY (Hz)
10M
100M
06198-144
1.125
Figure 44. Noise Spectral Density of OUTA, OUTB; CLPA, CLPB = 0.1 μF,
Frequency = 2140 MHz
Rev. 0 | Page 17 of 40
–1.0
10.0
7.5
5.0
3.0
2.8
2.6
2.4
–2.5
2.2
0
–2.5
2.0
–2.0
1.8
2.5
1.6
–1.5
06198-148
–0.5
–0.4
6.0
TIME (ns)
06198-145
5.4
4.8
4.2
3.6
2.4
3.0
1.8
1.2
0
0.6
–1.2
–0.6
–1.8
–2.4
–3.0
–3.6
–6.0
0.25
–4.2
0.50
12.5
INHA, INHB = –40dBm
INHA, INHB = –30dBm
INHA, INHB = –20dBm
INHA, INHB = –10dBm
INHA, INHB = 0dBm
PWDN PULSE
0
1.4
INHA, INHB = –10dBm
0.5
1.2
0.75
15.0
1.0
INHA, INHB = –20dBm
17.5
1.0
0.8
1.00
1.5
0.6
INHA, INHB = –30dBm
20.0
0.4
1.25
2.0
0
INHA, INHB = –40dBm
22.5
0.2
1.50
2.5
–0.2
OUTPUT VOLTAGE OUTA, OUTB (V)
1.75
–5.4
–4.8
OUTPUT VOLTAGE OUTA, OUTB (V)
2.00
INPUT VOLTAGE PWDN PULSE (V)
ADL5519
TIME (µs)
Figure 48. Output Response Using Power-Down Mode for Various
RF Input Levels, Carrier Frequency = 900 MHz, CLPA = 0.1 μF
Figure 45. Output Response to RF Burst Input for Various RF Input Levels,
Carrier Frequency = 900 MHz, CLPA = Open
0.06
2.0
INCREASING
0.05
1.6
DECREASING
1.4
INHA, INHB = –40dBm
1.2
IINHA, INHB = –30dBm
1.0
SUPPLY CURRENT (A)
OUTPUT VOLTAGE OUTA, OUTB (V)
1.8
INHA, INHB = –20dBm
0.8
0.6
INHA, INHB = –10dBm
0.4
0.04
0.03
0.02
0.01
17.5
1.0
15.0
0.5
12.5
0
10.0
RF OFF
INHA, INHB = –40dBm
INHA, INHB = –30dBm
INHA, INHB = –20dBm
INHA, INHB = –10dBm
INHA, INHB = 0dBm
PWDN PULSE
–0.5
–1.0
–1.5
7.5
5.0
2.5
3.0
2.8
2.6
2.4
2.2
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
–2.5
0.2
–2.5
0
0
–0.2
–2.0
TIME (µs)
INPUT VOLTAGE PWDN PULSE (V)
1.5
06198-147
20.0
–0.4
OUTPUT VOLTAGE OUTA, OUTB (V)
22.5
2.0
3.4
3.6
3.8
4.0
4.2
4.4
4.6
PWDN, ADJA, ADJB VOLTAGE (V)
Figure 46. Output Response to RF Burst Input for Various RF Input Levels,
Carrier Frequency = 900 MHz, CLPA = 0.1 μF
2.5
3.2
Figure 47. Output Response Using Power-Down Mode for Various
RF Input Levels, Carrier Frequency = 900 MHz, CLPA = Open
Rev. 0 | Page 18 of 40
Figure 49. Supply Current vs. VPWDN, VADJA, VADJB
4.8
5.0
06198-150
TIME (µs)
0
3.0
06198-146
25
23
21
19
17
15
13
11
9
7
5
3
1
–1
–5
0
–3
0.2
ADL5519
THEORY OF OPERATION
COMR
COMR
VPSA
ADJA
VPSR
TEMP
CLPA
VSTA
The ADL5519 is a dual-channel, six-stage demodulating logarithmic amplifier that is specifically designed for use in RF
measurement and power control applications at frequencies
up to 10 GHz. The ADL5519 is a derivative of the AD8317
logarithmic detector/controller core. The ADL5519 maintains
tight intercept variability vs. temperature over a 50 dB range.
Each measurement channel offers performance equivalent to
that of the AD8317. The complete circuit block diagram is
shown in Figure 50.
24
23
22
21
20
19
18
17
ADL5519
TEMP
INHA 25
INLA 26
CHANNEL A
LOG DETECTOR
COMR 27
PWDN 28
OUTA
OUTB
COMR 29
COMR 30
CHANNEL B
LOG DETECTOR
INLB 31
The maximum input with ±1 dB log conformance error is typically
−5 dBm (re: 50 Ω). The noise spectral density referred to the input
is 1.15 nV/√Hz, which is equivalent to a voltage of 118 μV rms
in a 10.5 GHz bandwidth or a noise power of −66 dBm (re: 50 Ω).
This noise spectral density sets the lower limit of the dynamic
range. However, the low end accuracy of the ADL5519 is enhanced
by specially shaping the demodulating transfer characteristic to
partially compensate for errors due to internal noise. The common
pins provide a quality, low impedance connection to the printed
circuit board (PCB) ground. The package paddle, which is internally connected to the COMR pins, should also be grounded to
the PCB to reduce thermal impedance from the die to the PCB.
INHB 32
16
NC
15
OUTA
14
FBKA
13
OUTP
12
OUTN
11
FBKB
10
OUTB
9
NC
The logarithmic function is approximated in a piecewise fashion
by six cascaded gain stages. For a more comprehensive explanation of the logarithm approximation, refer to the AD8307 data
sheet. The cells have a nominal voltage gain of 9 dB each, with
a 3 dB bandwidth of 10.5 GHz. Using precision biasing, the gain
is stabilized over temperature and supply variations. The overall
dc gain is high because of the cascaded nature of the gain stages.
An offset compensation loop is included to correct for offsets
within the cascaded cells. At the output of each gain stage,
a square-law detector cell is used to rectify the signal.
5
6
7
8
VREF
VLVL
CLPB
VSTB
06198-041
4
ADJB
COMR
3
VPSB
2
COMR
BIAS
1
Figure 50. Block Diagram
Each measurement channel is a full differential design using
a proprietary, high speed SiGe process that extends high frequency
performance. Figure 51 shows the basic diagram of the Channel A
signal path; its functionality is identical to that of the Channel B
signal path.
DET
DET
DET
V
I
VSTA
I
V
OUTA
The RF signal voltages are converted to a fluctuating differential
current, having an average value that increases with signal level.
Along with the six gain stages and detector cells, an additional
detector is included at the input of each measurement channel,
providing a 54 dB dynamic range in total. After the detector
currents are summed and filtered, the following function is
formed at the summing node:
ID × log10(VIN/VINTERCEPT)
where:
ID is the internally set detector current.
VIN is the input signal voltage.
VINTERCEPT is the intercept voltage (that is, when VIN = VINTERCEPT,
the output voltage would be 0 V, if it were capable of going to 0 V).
DET
CLPA
06198-042
INHA
INLA
(1)
Figure 51. Single Channel Block Diagram
Rev. 0 | Page 19 of 40
ADL5519
USING THE ADL5519
BASIC CONNECTIONS
VPSA
The ADL5519 is specified for operation up to 10 GHz. As a result,
low impedance supply pins with adequate isolation between
functions are essential. A power supply voltage between 3.3 V
and 5.5 V should be applied to VPSA, VPSB, and VPSR. Power
supply decoupling capacitors of 100 pF and 0.1 μF should be
connected close to these power supply pins (see Figure 53).
INPUT SIGNAL COUPLING
The ADL5519 inputs are differential but were characterized
and are generally used single ended. When using the ADL5519
in single-ended mode, the INHA, INHB pins must be ac-coupled,
and INLA, INLB must be ac-coupled to ground. Suggested
coupling capacitors are 47 nF, ceramic 0402-style capacitors for
input frequencies of 1 MHz to 10 GHz. The coupling capacitors
should be mounted close to the INHA, INHB and INLA, INLB
pins. The coupling capacitor values can be increased to lower
the input stage high-pass cutoff frequency.
The high-pass corner is set by the input coupling capacitors and the
internal 10 pF high-pass capacitor. The dc voltage on INHA, INHB
and INLA, INLB is approximately one diode voltage drop below
the supply voltage.
18.7kΩ
5pF
FIRST
GAIN
STAGE
18.7kΩ
INHA
2kΩ
A = 9dB
INLA
Gm
STAGE
OFFSET
COMP
06198-044
The paddle of the LFCSP package is internally connected to
COMR. For optimum thermal and electrical performance, the
paddle should be soldered to a low impedance ground plane.
CURRENT
5pF
Figure 52. Single-Channel Input Interface
Although the input can be reactively matched, in general this
reactive matching is not necessary. An external 52.3 Ω shunt
resistor (connected on the signal side of the input coupling capacitors, as shown in Figure 53) combines with the relatively high
input impedance to give an adequate broadband match of 50 Ω.
The coupling time constant, 50 × CC/2, forms a high-pass corner
with a 3 dB attenuation at fHP = 1/(2π × 50 × CC ), where C1 =
C2 = C3 = C4 = CC. Using the typical value of 47 nF, this highpass corner is ~68 kHz. In high frequency applications, fHP should
be as large as possible to minimize the coupling of unwanted low
frequency signals. In low frequency applications, a simple RC
network forming a low-pass filter should be added at the input
for similar reasons. This low-pass filter should generally be placed
at the generator side of the coupling capacitors, thereby lowering
the required capacitance value for a given high-pass corner
frequency.
Rev. 0 | Page 20 of 40
ADL5519
VPSR
C15
0.1µF
ADJA
VPSA
C12
0.1µF
C7
100pF
C8
100pF
C4
47nF
INHA
C9
100pF
TEMP SENSOR
24
23
22
21
20
19
18
17
COMR
COMR
VPSA
ADJA
VPSR
TEMP
CLPA
VSTA
OUTPUT
VOLTAGE B
25 INHA
NC 16
26 INLA
OUTA 15
27 COMR
FBKA 14
R5
52.3Ω
C3
47nF
PWDN
28 PWDN
SETPOINT
VOLTAGE B
OUTP 13
DIFF OUT+
OUTN 12
DIFF OUT–
ADL5519ACPZ
EXPOSED PADDLE
29 COMR
30 COMR
FBKB 11
31 INLB
OUTB 10
32 INHB
NC 9
C2
47nF
R6
52.3Ω
C1
47nF
COMR
COMR
VPSB
ADJB
VREF
VLVL
CLPB
VSTB
1
2
3
4
5
6
7
8
SETPOINT
VOLTAGE B
C10
100pF
C16
100pF
C5
0.1µF
C11
0.1µF
VPOS
VPSA
VPSB
VPSB
ADJB
VREF
VLVL
Figure 53. Basic Connections for Operation in Measurement Mode
Rev. 0 | Page 21 of 40
VPSR
06198-043
INHB
OUTPUT
VOLTAGE B
ADL5519
TEMPERATURE SENSOR INTERFACE
SETPOINT INTERFACE—VSTA, VSTB
The ADL5519 provides a temperature sensor output capable of
driving 4 mA. The temperature scaling factor of the output voltage
is ~4.48 mV/°C. The typical absolute voltage at 27°C is approximately 1.36 V.
The VSTA, VSTB inputs are high impedance (40 kΩ) pins that
drive inputs of internal op amps. The VSET voltage appears across
the internal 1.5 kΩ resistor to generate a current, ISET. When a
portion of VOUT is applied to VSTA, VSTB, the feedback loop forces
VPSR
−ID × log10(VIN/VINTERCEPT) = ISET
INTERNAL
VPTAT
(2)
If VSET = VOUT/2x, then ISET = VOUT/(2x × 1.5 kΩ).
The result is
TEMP
12kΩ
VOUT = (−ID × 1.5 kΩ × 2x) × log10(VIN/VINTERCEPT)
ISET
COMR
06198-045
4kΩ
VSET
20kΩ
VSET
Figure 54. TEMP Interface Simplified Schematic
VREF INTERFACE
20kΩ
POWER-DOWN INTERFACE
The operating and stand-by currents for the ADL5519 at 27°C
are approximately 60 mA and less than 1 mA, respectively. To
completely power down the ADL5519, the PWDN and ADJA,
ADJB pins must be pulled within 200 mV of the supply voltage.
When powered on, the output reaches to within 0.1 dB of its
steady-state value in about 0.5 μs; the reference voltage is available to full accuracy in a much shorter time.
This wake-up response time varies, depending on the input
coupling network and the capacitance at the CLPA, CLPB pins.
PWDN disables the OUTP, OUTN, VREF, and TEMP pins. The
power-down pin, PWDN, is a high impedance pin.
The ADJA and ADJB pins, when pulled within 200 mV of the
supply voltage, disable OUTA and OUTB, respectively.
COMM
COMM
06198-048
1.5kΩ
The VREF pin provides a highly stable voltage reference. The
voltage on the VREF pin is 1.15 V, which is capable of driving
3 mA. An equivalent internal resistance is connected from
VREF to COMR for 3 mA sink capability.
Figure 55. VSTA, VSTB Interface Simplified Schematic
The slope is given by −ID × 2x × 1.5 kΩ = −22 mV/dB × x. For
example, if a resistor divider to ground is used to generate a VSET
voltage of VOUT/2, then x = 2. The slope is set to −880 V/decade
or −44 mV/dB. See the Altering the Slope section for additional
information.
OUTPUT INTERFACE—OUTA, OUTB
The OUTA, OUTB pins are driven by a push-pull output stage.
The rise time of the output is limited mainly by the slew on CLPA,
CLPB. The fall time is an RC-limited slew given by the load capacitance and the pull-down resistance at OUTA, OUTB. There is
an internal pull-down resistor of 1.6 kΩ The resistive load at
OUTA, OUTB can be placed in parallel with the internal pulldown resistor to reduce the discharge time. OUTA, OUTB can
source greater than 10 mA.
VPSA, VPSB
CLPA,
CLPB
1.2kΩ
OUTA,
OUTB
COMR
06198-049
400Ω
Figure 56. OUTA, OUTB Interface Simplified Schematic
Rev. 0 | Page 22 of 40
ADL5519
DIFFERENCE OUTPUT—OUTP, OUTN
DESCRIPTION OF CHARACTERIZATION
The ADL5519 incorporates two operational amplifiers with rail-torail output capability to provide a channel difference output.
The general hardware configuration used for most of the ADL5519
characterization is shown in Figure 59. The signal sources used
in this example are the E8251A from Agilent Technologies. The
INHA, INHB input pins are driven by Agilent signal sources,
and the output voltages are measured using a voltmeter.
VLVL
OUTA
OUTB
1kΩ
BASIS FOR ERROR CALCULATIONS
OUTP
FBKA
COMR
VLVL
VPSR
The input power and output voltage are used to calculate the
slope and intercept values. The slope and intercept are calculated
using linear regression over the input range from −40 dBm to
−10 dBm. The slope and intercept terms are used to generate an
ideal line. The error is the difference in measured output voltage
compared to the ideal output line. This is a measure of the linearity
of the device. Refer to the Device Calibration section for more
information on calculating slope, intercept, and error.
1kΩ
OUTN
1kΩ
1kΩ
FBKB
COMR
Figure 57. OUTP, OUTN Interface Simplified Schematic
If OUTP is connected to FBKA, OUTP is given as
OUTP = OUTA − OUTB + VLVL
(3)
If OUTN is connected to FBKB, OUTN is given as
OUTN = OUTB − OUTA + VLVL
(4)
14 FBKA
OUTA
OUTB
AGILENT
34970A
METER/
SWITCHING
Figure 59. General Characterization Configuration
06198-050
OUTA
–3dB
OUTA
OUTB
ADL5519
OUTP
CHARACTERIZATION
OUTN
BOARD
VREF
INB
TEMP
INA
COMPUTER
CONTROLLER
1kΩ
1kΩ
1kΩ
–3dB
SIGNAL
SOURCE
VPSR
1kΩ
OUTB
SIGNAL
SOURCE
06198-052
As in the case of the output drivers for OUTA, OUTB, the output
stages have the capability of driving greater than 10 mA. OUTA
and OUTB are internally connected through 1 kΩ resistors to the
inputs of each op amp. The VLVL pin is connected to the positive
terminal of both op amps through 1 kΩ resistors to provide
level shifting. The negative feedback terminal is also made
available through a 1 kΩ resistor. The input impedance of VLVL
is 1 kΩ, and the input impedance of FBKA, FBKB is 1 kΩ. See
Figure 57 for the connections of these pins.
Pulse response of the ADL5519 is 6 ns/8 ns rise/fall times. For
the fastest response time, the capacitance on OUTA, OUTB should
be kept to a minimum. Any capacitance on the output pins should
be counterbalanced with an equal capacitance on the CLPA, CLPB
pins to prevent ringing on the output.
13 OUTP
06198-051
12 OUTN
11 FBKB
Error from the linear response to the CW waveform is not
a measure of absolute accuracy because it is calculated using
the slope and intercept of each device. However, error verifies the
linearity and the effects of modulation on device response.
Similarly, at temperature extremes, error represents the output
voltage variations from the 25°C ideal line performance. Data
presented in the graphs is the typical error distribution observed
during characterization of the ADL5519.
Figure 58. Op Amp Connections (All Resistors Are 1 kΩ ± 20%)
In this configuration, all four measurements, OUTA, OUTB,
OUTP, and OUTN, are available simultaneously. A differential
output can be taken from OUTP − OUTN, and VLVL can be
used to adjust the common-mode level for an ADC connection.
This is convenient not only for driving a differential ADC but
also for removing any temperature variation on VLVL.
Rev. 0 | Page 23 of 40
ADL5519
DEVICE CALIBRATION
1.50
1.0
1.25
VOUT1
0.5
1.00
ADJUSTING ACCURACY THROUGH CHOICE OF
CALIBRATION POINTS
0
0.75
VOUT2
–0.5
0.50
–1.0
0.25
–1.5
0
–60
–50
–40
–30
–20
PIN (dBm)
PIN1
–10
0
–2.0
10
PIN2
Figure 60. Transfer Function at 2.2 GHz with Calibration Points
Because slope and intercept vary from device to device, boardlevel calibration must be performed to achieve the highest
accuracy. The equation for output voltage can be written as
VOUT = Slope × (PIN − Intercept)
(6)
where:
Slope is the change in output voltage divided by the change in
input power, PIN, expressed in decibels (dB).
Intercept is the calculated power at which the output voltage
would be 0 V. Note that an output voltage of 0 V can never be
achieved.
In general, calibration is performed by applying two known
signal levels to the ADL5519 input and measuring the corresponding output voltages. The calibration points are generally
chosen to be within the linear-in-dB operating range of the
device (see the Specifications section for more details).
Calculation of the slope and intercept is accomplished using the
following equations:
Slope = (VOUT1 − VOUT2)/(PIN1 − PIN2)
(7)
Intercept = PIN1 − (VOUT1/Slope)
(8)
Once slope and intercept are calculated, an equation can be
written that calculates the input power based on the output
voltage of the detector.
PIN (Unknown) = (VOUT1(MEASURED)/Slope) + Intercept
In some applications, very high accuracy is required at one
power level or over a reduced input range. For example, in a
wireless transmitter, the accuracy of the high power amplifier
(HPA) is most critical at or close to full power.
In applications like AGC control loops, good linearity and
temperature performance are necessary over a large input power
range. The temperature crossover point (the power level at which
there is no drift in performance from −40°C to −80°C) can be
shifted from high power levels to midpower levels using the
method shown in the Temperature Compensation Adjustment
section. This shift equalizes the temperature performance over
the complete power range. The linearity of the transfer function
can be equalized by changing the calibration points.
Figure 61 demonstrates this equalization by changing the calibration points used in Figure 60 to −46 dBm and −22 dBm. This
adjustment of the calibration points changes the linearity to greater
than ±0.25 dB over a 50 dB dynamic range at the expense of a
slight decrease in linearity at power levels between −40 dBm
and −25 dBm.
Calibration points should be chosen to suit the application at hand.
In general, however, do not choose calibration points in the
nonlinear portion of the log amp transfer function (greater than
−10 dBm or less than −40 dBm, in this example).
2.00
2.0
1.75
1.5
1.50
VOUT1
1.0
1.25
0.5
1.00
0
VOUT2
0.75
–0.5
0.50
–1.0
0.25
–1.5
0
–60
(9)
The log conformance error of the calculated power is given by
Error (dB) = (VOUT(MEASURED) − VOUT(IDEAL))/Slope
–50
–40
PIN1
(10)
Figure 60 includes a plot of the error at 25°C, the temperature
at which the log amp is calibrated. Note that the error is not 0 dB
over the full dynamic range. This is because the log amp does
–30
–20
PIN (dBm)
PIN2
–10
0
–2.0
10
ERROR (dB)
1.5
06198-055
1.75
Figure 60 also shows error plots for the output voltage at
−40°C and +85°C. These error plots are calculated using the
slope and intercept at 25°C. This is consistent with calibration
in a mass-production environment, where calibration over
temperature is not practical.
OUTPUT VOLTAGE (V)
2.0
ERROR (dB)
2.00
06198-053
OUTPUT VOLTAGE (V)
The measured transfer function of the ADL5519 at 2.2 GHz is
shown in Figure 60. The figure shows plots of both output voltage
vs. input power and calculated error vs. input power. As the input
power varies from −60 dBm to −5 dBm, the output voltage varies
from 1.7 V to about 0.5 V.
not perfectly follow the ideal VOUT vs. PIN equation, even within
its operating region. The error at the calibration points of −35
dBm and −11 dBm is equal to 0 dB, by definition.
Figure 61. Dynamic Range Extension by Choosing Calibration Points That
Are Close to the End of the Linear Range, 2.14 GHz
Rev. 0 | Page 24 of 40
ADL5519
2.0
1.75
1.5
1.50
1.0
1.25
0.5
1.00
0
0.75
–0.5
0.50
–1.0
0.25
–1.5
0
–60
–50
–40
–30
–20
–10
0
–2.0
10
PIN (dBm)
Compensating the device for temperature drift by using ADJA,
ADJB allows for great flexibility. To determine the optimal adjust
voltage, sweep ADJA, ADJB at ambient and at the desired
temperature extremes for a couple of power levels while
monitoring the output voltage. The point of intersection
determines the best adjust voltage. Some additional minor
tweaking may be required to achieve the highest level of temperature stability. With appropriate values, a temperature drift error
of typically ±0.5 dB over the entire rated temperature range can be
achieved.
Table 4. Recommended ADJA, ADJB Voltage Levels
ERROR (dB)
2.00
06198-056
OUTPUT VOLTAGE (V)
Another way of presenting the error function of a log amp detector
is shown in Figure 62. In this example, the decibel (dB) error at
hot and cold temperatures is calculated with respect to the output
voltage at ambient. This is a key difference when compared to the
previous plots, in which all errors have been calculated with respect
to the ideal transfer function at ambient.
Figure 62. Error vs. Temperature with Respect to Output Voltage at 25°C,
2.14 GHz (Removes Transfer Function Nonlinearities at 25°C)
With this alternative technique, the error at ambient becomes,
by definition, equal to 0 (see Figure 62). This value would be
valid if the device transfer function perfectly followed the ideal
of the VOUT = Slope × (PIN − Intercept) equation.
However, because an rms amp, in practice, never perfectly follows
this equation (especially outside of its linear operating range),
this plot tends to artificially improve linearity and extend the
dynamic range, unless enough calibration points are taken to
remove the error.
Frequency
100 MHz
900 MHz
1.9 GHz
2.2 GHz
3.6 GHz
5.8 GHz
8 GHz
Recommended ADJA, ADJB Voltage (V)
0.65, 0.7
0.6, 0.65
0.5, 0.55
0.48, 0.6
0.35, 0.42
0.58, 0.7
0.72, 0.82
Proprietary techniques are used to compensate for the temperature
drift. The absolute value of compensation varies with frequency
and circuit board material.
ADJA, ADJB are high impedance pins. The applied ADJA, ADJB
voltages can be supplied from VREF through a resistor divider.
Figure 63 shows a simplified schematic representation of the
ADJA, ADJB interface.
VREF
ADL5519
VTADJ
ICOMP
ADJA, ADJB
TEMPERATURE COMPENSATION ADJUSTMENT
COMR
The ADL5519 temperature performance has been optimized to
ensure that the output voltage has minimum temperature drift
at −10 dBm input power. The applied voltage for the ADJA and
ADJB pins for some specified frequencies is listed in Table 4.
However, not all frequencies are represented in Table 4, and
experimentation may be required.
Rev. 0 | Page 25 of 40
COMR
Figure 63. ADJA, ADJB Interface Simplified Schematic
06198-057
Figure 62 is a useful tool for estimating temperature drift at
a particular power level with respect to the (nonideal) output
voltage at ambient.
ADL5519
ALTERING THE SLOPE
As discussed in the Setpoint Interface—VSTA, VSTB section,
the slope can readily be increased by scaling the amount of
output voltage at OUTA, OUTB that is fed back to the setpoint
interface, VSTA, VSTB. When the full signal from OUTA,
OUTB is applied to VSTA, VSTB, the slope has a nominal value of
−22 mV/dB. This value can be increased by including a voltage
divider between the OUTA, OUTB and VSTA, VSTB pins, as
shown in Figure 64.
ADL5519
VOUT
OUTA, OUTB
R1
VSTA, VSTB
The lowest detectable power point of the ADL5519 has little
variation from part to part. This equalizes the signals on both
channels at their lowest possible power level, which reduces the
overall isolation requirements and possibly adds attenuators to the
RF inputs of the device, reducing the RF channel input isolation
requirements.
Measuring the RF channel input to the other RF channel input
isolation is straightforward and is done by measuring the loss
on a network analyzer from one input to the other input. The
outcome is shown in the Specifications section of the data sheet.
Note that adding an attenuator in series with the RF signal
increases the channel input-to-input isolation by the value of
the attenuator.
06198-058
R2
Figure 64. External Network to Raise Slope
The approximate input resistance for VSTA, VSTB is 40 kΩ.
Scaling resistor values should be carefully selected to minimize
errors. Keep in mind that these resistors also load the output
pins and reduce the load-driving capabilities.
Equation 11 can be used to calculate the resistor values.
S
R1 = R2' ⎛⎜ D − 1⎞⎟
⎝ − 22 ⎠
In most applications, the designer has the ability to adjust the
power going into the ADL5519 through the use of temperaturestable couplers and accurate temperature-stable attenuators of
different values. When isolation is a concern, it is useful to
adjust the input power so the lowest expected detectable power
is not far from the lowest detectable power of the ADL5519 at
the frequency of operation.
(11)
where:
SD is the desired slope, expressed in millivolts/decibels (mV/dB).
R2' is the value of R2 in parallel with 40 kΩ.
For example, using R1 = 1.65 kΩ and R2 = 1.69 kΩ (R2' = 1.62 kΩ),
the nominal slope is increased to −44 mV/dB.
When the slope is increased, the loop capacitor, CLPA, CLPB,
may need to be raised to ensure stability and to preserve a chosen
averaging time. The slope can be lowered by placing a voltage
divider after the output pin, following standard practices.
CHANNEL ISOLATION
Isolation must be considered when using both channels of the
ADL5519 at the same time. The two isolation requirements that
should be considered are the isolation from one RF channel input
to the other RF channel input and the isolation from one RF
channel input to the other channel output. When using both
channels of the ADL5519, care should be taken in the layout to
isolate the RF inputs, INHA and INHB, from each other. Coupling
on the PC board affects both types of isolation.
The isolation between one RF channel input and the other channel
output is a little more complicated. The easiest approach (which
was used in this datasheet) to measuring this isolation is to have
one channel set to the lowest power level it is expected to have
on its input (approximately −50 dBm in this data sheet) and
then increasing the power level on the other channel input until
the output of the low power channel changes by 22 mV. Because
−50 dBm is in the linear region of the detector, 22 mV equates
to a 1 dB change in the output.
If the inputs to both RF channels are at the same frequency, the
isolation also depends on the phase shift between the RF signals
put into the ADL5519. This relationship can be demonstrated by
placing a high power signal on one RF channel input and a low
power signal slightly offset in frequency to the other RF channel.
If the output of the low power channel is observed with an
oscilloscope, it has a ripple that looks similar to a full-wave
rectified sine wave with a frequency equal to the frequency
difference between the two channels, that is, a beat tone. The
magnitude of the ripple reflects the isolation at a specific phase
offset (note that two signals of slightly different frequencies act
like two signals with a constantly changing phase), and the
frequency of that ripple is directly related to the frequency offset.
The data shown in the Specifications section assumes worst-case
amplitude and phase offset. If the RF signals on Channel A and
Channel B are at significantly different frequencies, the input-tooutput isolation increases, depending on the capacitors placed on
CLPA, CLPB and the frequency offset of the two signals, due to
the response roll-off within the ADL5519.
Rev. 0 | Page 26 of 40
ADL5519
OUTPUT FILTERING
PACKAGE CONSIDERATIONS
Accurate power detection for signals with RF bursts is achieved
when the ADL5519 is able to respond quickly to the change in
RF power. For applications in which maximum video bandwidth
and, consequently, fast rise time are desired, it is essential that
the CLPA, CLPB pins have very little capacitance on them (some
capacitance reduces the ringing).
The ADL5519 uses a compact, 32-lead LFCSP. A large exposed
paddle on the bottom of the device provides both a thermal
benefit and a low inductance path to ground for the circuit.
To make proper use of this packaging feature, the PCB RF/dc
common-ground reference needs to make contact with the paddle
with as many vias as possible to lower inductance and thermal
impedance.
The nominal output video bandwidth of 10 MHz can be reduced
by connecting a ground-referenced capacitor (CFLT) to the CLPA,
CLPB pins, as shown in Figure 65. This is generally done to
reduce output ripple (at twice the input frequency for a
symmetric input waveform, such as a sinusoidal signal).
ADL5519
CLPA, CLPB
CFLT
Implementing an impedance match for frequencies greater than
8 GHz can improve the sensitivity of the ADL5519 and its measurement range.
Figure 65. Lowering the Post Demodulation Bandwidth
CFLT is selected using the following equation:
CFLT
1
=
(π × 1.5 kΩ × Video Bandwidth ) − 3.5 pF
(12)
The video bandwidth should typically be set to a frequency less
than or equal to approximately 1/10 the minimum input frequency.
There are no problems with putting large capacitor values on the
CLPA, CLPB pins. These large capacitor values ensure that the
output ripple of the demodulated log output, which is at twice
the input frequency, is well filtered. Signals with modulation
may need additional filtering (a larger CFLT capacitance) to
remove modulation bleedthrough.
2.00
4.0
1.75
3.0
1.50
2.0
1.25
1.0
1.00
0
0.75
–1.0
0.50
–2.0
0.25
–3.0
0
–40
ERROR (dB)
3.5pF
–4.0
–35
–30
–25
–20
–15
–10
–5
0
PIN (dBm)
Figure 66. VOUT and Log Conformance vs. Input Amplitude at 10 GHz,
Over Temperature, ADJA, ADJB = 1.8 V, 1.8 V
Rev. 0 | Page 27 of 40
06198-169
1.5kΩ
OUTA, OUTB
The ADL5519 is specified for operation up to 8 GHz, but it
provides useful measurement accuracy over a reduced dynamic
range of up to 10 GHz. Figure 66 shows the performance of the
ADL5519 over temperature for a input frequency of 10 GHz. This
high frequency performance is achieved using the configuration
shown in Figure 53. The dynamic range shown is reduced from the
typical device performance, but the ADL5519 can provide 30 dB of
measurement range with less than 3 dB of linearity error.
OUTPUT VOLTAGE (V)
+4
06198-059
ILOGA,
ILOGB
OPERATION ABOVE 8 GHz
ADL5519
APPLICATIONS INFORMATION
For a square wave input signal in a 200 Ω system
MEASUREMENT MODE
The ADL5519 is placed in measurement mode by connecting
OUTA, OUTB to VSTA, VSTB, respectively. The part has an offset
voltage, a negative slope, and a VOUTA, VOUTB measurement intercept at the high end of its input signal range.
The output voltage vs. input signal voltage of the ADL5519 is
linear-in-dB over a multidecade range. The equation for this
function is of the following form:
VOUT = x × VSLOPE/DEC × log10(VIN/VINTERCEPT) =
(13)
x × VSLOPE/dB × 20 × log10(VIN/VINTERCEPT)
(14)
where:
x is the feedback factor in VSET = VOUT/x.
VSLOPE/DEC is nominally −440 mV/decade or −22 mV/dB.
VINTERCEPT is the x-axis intercept of the linear-in-dB portion of
the VOUT vs. VIN curve.
VINTERCEPT is 2 dBV for a sinusoidal input signal.
An offset voltage, VOFFSET, of 0.45 V is internally added to
the detector signal so that the minimum value for VOUT is
x × VOFFSET. If x = 1, the minimum VOUT value is 0.45 V.
The slope is very stable vs. process and temperature variation.
When Base-10 logarithms are used, VSLOPE/DEC represents the
volts/decade. A decade corresponds to 20 dB; VSLOPE/DEC/20 =
VSLOPE/dB represents the slope in V/dB.
B
As noted in Equation 13 and Equation 14, the VOUT voltage has
a negative slope. This is also the correct slope polarity to control
the gain of many VGAs in a negative feedback configuration.
Because both the slope and intercept vary slightly with frequency,
see the Specifications section for application-specific values for
slope and intercept.
Although demodulating log amps respond to input signal
voltage and not input signal power, it is customary to discuss
the amplitude of high frequency signals in terms of power. In
this case, the characteristic impedance of the system, Z0, must
be known to convert voltages to their corresponding power levels.
The following equations are used to perform this conversion:
P (dBm) = 10 × log10(Vrms2/(Z0 × 1 mW))
(15)
P (dBV) = 20 × log10(Vrms/1 Vrms)
(16)
P (dBm) = P (dBV) − 10 × log10(Z0 × 1 mW/1 Vrms2)
(17)
PINTERCEPT (dBm) =
−1 dBV − 10 × log10[(200 Ω × 1 mW/1Vrms2)] = +6 dBm
More information about the intercept variation dependence upon
waveform can be found in the AD8313 and AD8307 data sheets.
As the input signals to Channel A and Channel B are swept over
their nominal input dynamic range of −5 dBm to −55 dBm, the
output swings from 0.5 V to 1.6 V. The voltages of OUTA, OUTB
are also internally applied to a difference amplifier with a gain
of 1. When the input power is swept, OUTP swings from approximately 0.5 V to 1.75 V, and OUTN swings from 1.75 V to 0.5 V.
The VLVL pin sets the common-mode voltage for OUTP, OUTN.
An output common-mode voltage of ≤1.15 V can be set using
a resistor divider between the VREF and VLVL pins. Measurement
of large differences between INHA, INHB can be affected by
on-chip signal leakage.
CONTROLLER MODE
In addition to being a measurement device, the ADL5519 can
also be configured to set and control signal levels. Each of the two
log detectors can be separately configured to set and control the
output power level of a VGA or variable voltage attenuator (VVA).
See the Controller Mode section of the AD8317 datasheet for more
information on running a single channel in controller mode.
Alternatively, the two log detectors can be configured to measure
and control the gain of an amplifier or signal chain. The channel
difference outputs can be used to control a feedback loop to the
ADL5519 RF inputs. A capacitor connected between FBKA and
OUTP forms an integrator, keeping in mind that the on-chip 1 kΩ
feedback resistor forms a 0. (The value of the on-chip resistors can
vary as much as ±20% with manufacturing process variation.)
If Channel A is driven and Channel B has a feedback loop from
OUTP through a VGA, OUTP integrates to a voltage value
such that
OUTB = (OUTA + VLVL)/2
(18)
The output value from OUTN may or may not be useful. It is
given by
OUTN = 0 V
(19)
for VLVL < OUTA/3.
Otherwise,
For example, PINTERCEPT, for a sinusoidal input signal expressed
in terms of dBm (decibels referred to 1 mW), in a 50 Ω system is
PINTERCEPT (dBm) =
PINTERCEPT (dBV) − 10 × log10(Z0 × 1 mW/1 Vrms2) =
2 dBV − 10 × log10(50 × 10−3) = 15 dBm
Rev. 0 | Page 28 of 40
OUTN = (3 × VLVL − OUTA)/2
(20)
ADL5519
If an inversion is necessary in the feedback loop, OUTN can be
used as the integrator by placing a capacitor between OUTN,
OUTP. This changes the output equation for OUTB and OUTP to
If VLVL is connected to the OUTA pin, OUTB is forced to equal
OUTA through the feedback loop. This flexibility provides the
capability to measure one channel operating at a given power
level and frequency while forcing the other channel to a desired
power level at another frequency. The voltages applied to the
ADJA, ADJB pins should be selected carefully to minimize
temperature drift of the output voltage. The temperature drift is
the statistical sum of the drift from Channel A and Channel B.
As stated previously, VLVL can be used to force the slaved
channel to operate at a different power from the other channel.
For VLVL < OUTA/2,
If the two channels are forced to operate at different power levels,
some static offset occurs due to voltage drops across metal wiring
in the IC.
Equation 18 to Equation 23 are valid when Channel A is driven
and Channel B is slaved through a feedback loop. When Channel B
is driven and Channel A is slaved, these equations can be altered
by changing OUTB to OUTA and OUTN to OUTP.
OUTB = 2 × OUTA − VLVL
OUTN = 0 V
(21)
(22)
Otherwise,
OUTN = 2 × VLVL − OUTA
Rev. 0 | Page 29 of 40
(23)
ADL5519
AUTOMATIC GAIN CONTROL
Figure 67 shows how the ADL5519 can be connected to provide
automatic gain control to an amplifier or signal chain. Additional
pins are omitted for clarity. In this configuration, both detectors
are connected in measurement mode with appropriate filtering
being used on CLPA, CLPB to provide adequate filtering of the
demodulated log output. OUTA, however, is also connected to
the VLVL pin of the on-board difference amplifier. In addition,
the OUTP output of the difference amplifier drives a variable gain
element (either VVA or VGA) and is connected back to the FBKA
input via a capacitor so that it is operating as an integrator.
Assume that OUTA is much bigger than OUTB. Because OUTA
also drives VLVL, this voltage is also present on the noninverting
input of the op amp driving OUTP. This results in a current flow
from OUTP through the integrating capacitor into the FBKA input.
This results in the voltage on OUTP increasing. If the gain control
transfer function of the VGA/VVA is positive, this increases the
gain, which in turn increases the input signal to INHA. The
output voltage on the integrator continues to increase until the
power on the two input channels is equal, resulting in a signal
chain gain of unity.
If a gain other than 0 dB is required, an attenuator can be used
in one of the RF paths, as shown in Figure 67. Alternatively,
power splitters or directional couplers of different coupling
factors can be used. Another convenient option is to apply a
voltage on VLVL other than OUTA. Refer to Equation 18 and
the Controller Mode section for more detail.
If the VGA/VVA has a negative gain control sense, the OUTN
output of the difference amplifier can be used with the integrating
capacitor tied back to FBKB. Alternatively, the inputs could be
swapped.
The choice of the integrating capacitor affects the response time
of the AGC loop. Small values give a faster response time but
may result in instability, whereas larger values reduce the response
time. Capacitors that are too large can also cause oscillations due
to the capacitive drive capability of the op amp. In automatic gain
control, the capacitors on CLPA and CLPB, which perform the
filtering of the demodulated log output, must still be used and
also affect loop response time.
Rev. 0 | Page 30 of 40
ADL5519
DIRECTIONAL
OR
POWER SPLITTER
VGA/VVA
DIRECTIONAL
OR
POWER SPLITTER
CLPA
ADL5519
VSTA
0.1µF
INHA
50Ω
INLA
OUTA
CHANNEL A
LOG DETECTOR
FBKA
0.1µF
CINT
ATTENUATOR
OUTP
DIFF OUT +
OUTN
0.1µF
FBKB
INLB
50Ω
INHB
OUTB
CHANNEL B
LOG DETECTOR
0.1µF
VSTB
CLPB
06198-063
VLVL
Figure 67. Operation in Controller Mode for Automatic Gain Control
Rev. 0 | Page 31 of 40
ADL5519
In controller mode, the ADL5519 can be used to hold the receiver
gain constant over a broad input power/temperature range. In this
application, the difference outputs are used to hold the receiver gain
constant. Figure 69 shows an example of how this can be done.
The RF input is connected to INHB, using a 19 dB coupler, and
the down-converted output from the signal chain is connected
to INHA, using a 19 dB coupler. A 100 pF capacitor is connected
between FBKA and OUTP, forming an integrator. OUTA is
connected to VLVL, forcing OUTP to adjust the VGA so that
OUTB is equal to OUTA. The circuit gain is set by the difference
in the coupling values of the input and output couplers and the
differences in path losses to the detector. Because they are operating
at different frequencies, the appropriate voltages on the ADJA,
ADJB pins must be supplied. ADJA is set to 0.6 V and ADJB is
set to 0.65 V to set the −40oC/+85oC crossover point toward the
center of the input power range. Using the suggested ADJA value
for 80 MHz would put the crossover point at a higher power level.
4.0
GAIN +85°C
GAIN +25°C
GAIN –40°C
3.5
3.0
Rev. 0 | Page 32 of 40
2.5
2.0
1.5
1.0
0.5
0
–50
–40
–30
–20
–10
0
PIN (dBm)
Figure 68. Performance of Gain-Stable Receiver
10
06198-171
There are many applications for a transmitter or receiver with
a highly accurate temperature-stable gain. For example, a multicarrier, base station high power amplifier (HPA) using digital
predistortion can have a power detector and an auxiliary receiver.
The power detector and all parts associated with it can be removed
if the auxiliary receiver has a highly accurate temperature-stable
gain. With a set gain receiver, the ADC on the auxiliary receiver
can determine not only the overall power being transmitted but
also the power in each carrier for a multicarrier HPA. Without the
use of a detector, the auxiliary receiver is very difficult to calibrate
accurately over temperature due to the part-to-part variation of the
components in the auxiliary receiver.
Figure 68 shows the results of the circuit in Figure 69. The input
power is swept from −47 dBm to +8 dBm. The output power is
measured, and the gain is calculated at +25°C, −40°C and +85°C.
With equal valued couplers used on the input and output, the
expected gain is about 0 dB. Due to path loss differences and
differences due to using two separate frequencies, the average
gain is about 2.5 dB. In this configuration, approximately 50 dB of
control range with 0.2 dB drift over temperature is obtained. For
an auxiliary receiver, less than 5 dB of variation is expected over
temperature. If the power levels are chosen to coincide with the
temperature crossover point, approximately 0.1 dB of temperature
variation can be expected. Most of the gain change over input
power level is caused by performance differences at different
frequencies.
GAIN (dB)
GAIN-STABLE TRANSMITTER/RECEIVER
ADL5519
RFIN
900MHz
0Ω
AD8342
0Ω
0Ω
IFOUT
80MHz
0Ω
ADL5330
454Ω
454Ω
90MHz
LPF
19dB
COUPLING
19dB
COUPLING
820MHZ
MODE SEL
0V TO 1.2V
POWER DOWN
52.3
INHB
0.65V
2
30
31
INLB
32
1
29
27
28
25
26
INHA
100PF
5V
C12
C7
100PF 0.1UF
INLA
0.1UF
52.3
47NF
47NF
PWDN
C11
47NF
R31
C1
C3
47NF
COMR
C16
C2
C4
R30
5V
3
0.6V
24
23
22
VPSB
VPSA
4
5
VREF
ADJB
21
ADJA
ADL5519
VREF
20
VPSR
6
7
VLVL
C8
100PF
19
EXPOSED PADDLE
C15
0.1UF
TEMP
CLPB
18
CLPA
VSTB
9
10
11
12
13
14
OUTA
FBKA
OUTP
OUTN
17
FBKB
8
OUTB
C10
0.1 UF
15
VSTA
C9
0.1 UF
16
TEMPERATURE
SENSOR OUT
100 PF
06198-172
B CHANNEL OUT
DIFF OUT–
Figure 69. Gain-Stable Receiver Circuit
Rev. 0 | Page 33 of 40
ADL5519
Measurement of reflected power in wireless transmitters is a critical
auxiliary function that is often overlooked. The power reflected
back from an antenna is specified using either the voltage standing
wave ratio (VSWR) or the reflection coefficient (also referred to
as the return loss). Poor VSWR can cause shadowing in a TV
broadcast system because the signal reflected off the antenna
reflects again off the power amplifier and is then rebroadcast. In
wireless communications systems, shadowing produces multipathlike phenomena. Poor VSWR can degrade transmission quality;
the catastrophic VSWR that results from damage to a co-axial
cable or to an antenna can, at its worst, destroy the transmitter.
The ADL5519 delivers an output voltage proportional to the log
of the input signal over a large dynamic range. A log-responding
device offers a key advantage in VSWR measurement applications.
To compute gain or reflection loss, the ratio of the two signal
powers (either OUTPUT/INPUT or REVERSE/FORWARD)
must be calculated. An analog divider must be used to perform
this calculation with a linear-responding diode detector, but
only simple subtraction is required when using a log-responding
detector (because log(A/B) = log(A) − log(B)).
A dual RF detector has an additional advantage compared to
a discrete implementation. There is a natural tendency for two
devices (RF detectors, in this case) to behave similarly when they
are fabricated on a single piece of silicon, with both devices having
similar temperature drift characteristics, for example. At the
summing node, this drift cancels to yield a result that is more
temperature stable.
In Figure 71, two directional couplers are used, one to measure
forward power and one to measure reverse power. Additional
attenuation is required before applying these signals to the
detectors. The ADL5519 dual detector has a measurement range
of 50 dB in each detector. Care must be taken in setting the attenuation levels so the reflection coefficient can be measured over the
desired output power range.
The level planning used in this example is graphically depicted
in Figure 70. In this example, the expected output power range
from the HPA is 30 dB, from 20 dBm to 50 dBm. Over this
power range, the ADL5519 can accurately measure reflection
coefficients from 0 dB (short, open, or load) to −20 dB.
Each ADL5519 detector has a nominal input range from −5 dBm
to −55 dBm. In this example, the maximum forward power of
+50 dBm is attenuated to −10 dBm at the detector input (this
attenuation is achieved through the combined coupling factor
of the directional coupler and the subsequent attenuation). This
puts the maximum power at the detector comfortably within its
linear operating range. Also, when the HPA is transmitting at its
lowest power level of +20 dBm, the detector input power is
−40 dBm, which is still within its input operating range.
50dBm
40dBm
30dBm
FORWARD
POWER
RANGE
55dB
ATTENUATION
20dBm
10dBm
0dBm
REVERSE
POWER
RANGE
60dB
ATTENUATION
DECTOR A/B
INPUT RANGE
–10dBm
–20dBm
POWER
AT INPUT A
–30dBm
POWR
AT INPUT B
–40dBm
–50dBm
06198-075
MEASURING VSWR
–60dBm
Figure 70. ADL5519 VSWR Level Planning
Careful level planning should be used to match the input power
levels in a dual detector and to place these power levels within
the linear operating range of the detectors. The power from the
reverse path is attenuated by 55 dB, which means that the detector
is capable of measuring reflected power up to 0 dB. In most applications, the system is designed to shut down when the reflection
coefficient degrades below a certain minimum (for example,
10 dB). Full reflection is allowed when using the ADL5519 because
of its large dynamic range. In the case of very little reflection
(a return loss of 20 dB) and the HPA is transmitting +20 dBm, the
reverse path detector has an input power of −55 dBm.
The application circuit in Figure 71 provides a direct reading of
return loss, forward power, and reverse power. If the forward and
reverse phase difference (phase angle) is needed to optimize the
power delivered to the antenna, the AD8302 should be used.
It provides one output that represents the return loss and one
output that represents the phase difference between the two
signals. However, the AD8302 does not provide the absolute
forward or reverse power.
Rev. 0 | Page 34 of 40
ADL5519
POUT = 20dBm TO 50dBm
HPA
VSTA
35dB
20dB
ADL5519
40dB
TEMP
0.1µF
INHA
52.3Ω
OUTA
CHANNEL A
LOG DETECTOR
ADC
FBKA
OUTP
PIN = –10dBm TO
–40dBm
FORWARD
POWER
OUTA
OUTB
RETURN
LOSS
ADC
MICROPROCESSOR/
DSP
OUTN
ADC
FBKB
CHANNEL B
LOG DETECTOR
OUTB
REVERSE
POWER
0.1µF
INHB
52.3Ω
BIAS
PIN = –5dBm TO
–55dBm
VSTB
Figure 71. ADL5519 Configuration for Measuring Reflection Coefficients
Rev. 0 | Page 35 of 40
06198-074
20dB
ADL5519
EVALUATION BOARD
CONFIGURATION OPTIONS
Table 5. Evaluation Board (Rev. A) Configuration Options
Component
VPOS, VPSB, VPSR,
GND, GND1, GND3
R0A, R0B, R5, R6,
R30, R31, C1, C2,
C3, C4
R14
R13, R17, R18,
R19, R27, R28,
R29
R8, R12, R15, R16,
R20, R21, R22,
R23, C13, C14
Description
Supply and Ground Connections.
VPOS, VPSB, and VPSR are internally connected.
GND, GND1, and GND3 are internally connected.
Input Interface.
The 52.3 Ω resistors in the R30 and R31 positions combine with the ADL5519
internal input impedance to give a broadband input impedance of about 50 Ω.
C1, C2, C3, and C4 are dc-blocking capacitors. A reactive impedance match can
be implemented by replacing R5, R6, R30, and R31 with an inductor and by
replacing C1, R0A and C4, R0B with appropriately valued capacitors.
Temperature Sensor Interface.
Temperature sensor output voltage is available at the test point labeled TEMP.
R14 can be used as a pull-down resistor.
Temperature Compensation Interface.
A voltage source at ADJA, ADJB can be used to optimize the temperature
performance for various input frequencies. The pads for R27/R28 or R27/R29 can
be used for voltage dividers from the VREF node to set the ADJA, ADJB voltages
at different frequencies. The individual log channels can be disabled by installing
0 Ω resistors at R18 and R19.
Output Interface, Measurement Mode.
In measurement mode, a portion of the output voltage is fed back to VSTA, VSTB via
R8, R12. The magnitude of the slope of the OUTA, OUTB output voltage response
can be increased by reducing the portion of VOUTA, VOUTB that is fed back to VSTA,
VSTB. The slope can be decreased by implementing a voltage divider by using
R20 and R16 or R21 and R15. R20 and R21 can also be used as a back-terminating
resistor or as part of a single-pole, low-pass filter.
Output Interface, Controller Mode.
In this mode, the 0 Ω resistors must be removed, leaving R8 and R12 open. In
controller mode, the ADL5519 can control the gain of an external component.
A setpoint voltage is applied to VSTA, VSTB, the value of which corresponds to
the desired RF input signal level applied to the corresponding ADL5519 RF input.
A sample of the RF output signal from this variable-gain component is selected,
typically via a directional coupler, and applied to ADL5519 RF input. The voltage
at OUTA, OUTB is applied to the gain control of the variable gain element. A control
voltage is applied to VSTA, VSTB. The magnitude of the control voltage can
optionally be attenuated via the voltage divider comprising R8, R12 and R22,
R23; or a capacitor can be installed in the R22, R23 position to form a low-pass
filter along with R8, R12.
Power Supply Decoupling.
The nominal supply decoupling consists of a 100 pF filter capacitor placed
physically close to the ADL5519 and a 0.1 μF capacitor placed nearer to each
power supply input pin.
Output Interface, Difference.
R9 and R10 can be replaced with a capacitor to form an integrator for constant
gain controller mode
Filter Capacitor.
The low-pass corner frequency of the circuit that drives OUTA, OUTB can be
lowered by placing a capacitor between CLPA, CLPB and ground. Increasing this
capacitor increases the overall rise/fall time of the ADL5519 for pulsed input
signals. See the Output Filtering section for more details.
VLVL Interface.
VREF can be used to drive VLVL through a voltage divider formed using R7 and C6.
Default Conditions
Not applicable
R30, R31 = 52.3 Ω (Size 0402),
C1 to C4 = 47 nF (Size 0402)
R0A, R0B = 0 Ω
R5, R6 = open
R14 = open (Size 0603)
R13, R17, R18, R19, R28, R29 = open
(Size 0603)
R27 = 0 Ω (Size 0603)
R8, R12, R20, R21 = 0 Ω (Size 0603)
R15, R16, R22, R23 = open (Size 0603)
C13, C14 = open (Size 0603)
B
R8, R12, R22, R23
R3, R4, R11, R24,
R25, R26, C7, C8,
C11, C12, C15, C16
R1, R2, R9, R10
C9, C10
R7, C6
Rev. 0 | Page 36 of 40
R8, R12, R22, R23 = open (Size 0603)
R3, R4, R11, R24, R25, R26 = 0 Ω
(Size 0603)
C7, C8, C11 = 100 pF (Size 0603)
C12, C15, C16 = 0.1 μF (Size 0603)
R1, R2, R9, R10 = 0 Ω (Size 0603)
C9, C10 = 1000 pF (Size 0603)
R7 = open (Size 0603)
C6 = open (Size 0603)
VSTB
ADJB
RED
TESTLOOP
VLVL
RED
TESTLOOP
VREF
VPSB
SMASMT
VLVL
SMASMT
C0603
AGND
C0603
Open
C6
R0603
R0402
Open
R17
VSTB
R7
OPEN
0.1 uF
C5
AGND
VREF
ADJB
VREF
R27
0
R0603
AGND
R0603
R0603
R28
OPEN
C16
C0402
0.1UF
R0603
AGND
R22
Open
AGND
AGND
0
R11
C0603
1000PF
C10
R0402
C0603
Open
C14
AGND
R0402
Open
R19
C0402
100PF
C11
R0603
SMASMT
AGND
8
7
6
5
4
3
2
1
R0B
C0402
47NF
C4
C0402
9
VSTB
CLPB
VLVL
VREF
ADJB
VPSB
OUTB
0
AGND
PWDN
R0603
0
R2
R0603
SMASMT
25
0
R0603
16
15
R9
VSTA
CLPA
TEMP
VPSR
ADJA
VPSA
26
OUTP
R0603
0
R1
14
SMASMT
OUTN
13
32LFCSP5X5
C0402
47NF
C3
AGND
28 27
ADL5519
Z1
30 29
C0402
47NF
C2
AGND
11 12
31
R10
10
32
0 Ohm
R0A
17
18
19
20
21
22
23
24
R21
0
R8
0
R0402
R5
AGND
R0402
C7
Open
AGND
C0603
C13
R0603
C9
C0603
1000PF
R15
C0402
100PF
VPOS
Open
Open
R18
R0402
Open
AGND
SMASMT
R31
52.3
AGND
INHA
INHA
OUTA
C0402
47NF
C1
C0402
0 Ohm
SMASMT
OUTB
R20
0
R0402
R30
52.3
AGND
R12
0
AGND
Open
R16
R0402
R6
Open
INHB
INLB
R29
FBKB
INHB
PWDN
INLA
OPEN
COMR
OUTN
ADJB
R0603
R0603
OUTB
SMASMT
PWDN
OUTP
ADJA
OUTN
FBKA
INHA
OUTA
SMASMT
OUTP
R0603
R0603
Rev. 0 | Page 37 of 40
OUTA
Figure 72. Evaluation Board Schematic
AGND
AGND
AGND
0
R3
R0603
R23
Open
R0402
AGND
R0402
AGND
R13
Open
HTA_CSP5X5_GND
Z2
R0603
Open
R14
C0402
0.1UF
C12
RED
TESTLOOP
VPOS
R24
C8
C0402
100PF
R0603
R26
R0603
R25
R0603
0
0
0
TESTLOOP
R0402
BLACK
GND1
VSTA
TEMP
AGND
0
R4
ADJA
C0402
0.1UF
C15
TESTLOOP
BLACK
GND2
SMASMT
RED
TESTLOOP
TEMP
SMASMT
VPSA
RED
TESTLOOP
VPSR
RED
TESTLOOP
VPSB
VPSA
TESTLOOP
AGND
BLACK
GND3
VSTA
VPSR
ADJA
VPSR
VPSB
06198-068
INHB
ADL5519
EVALUATION BOARD SCHEMATIC AND ARTWORK
06198-071
06198-069
ADL5519
06198-072
Figure 75. Bottom Side Layout
06198-070
Figure 73. Top Side Layout
Figure 76. Bottom Side Silkscreen
Figure 74. Top Side Silkscreen
Rev. 0 | Page 38 of 40
ADL5519
OUTLINE DIMENSIONS
5.00
BSC SQ
0.60 MAX
0.60 MAX
25
24
TOP
VIEW
0.50
BSC
4.75
BSC SQ
0.50
0.40
0.30
1.00
0.85
0.80
SEATING
PLANE
12° MAX
2.85
2.70 SQ
2.55
EXPOSED
PAD
(BOT TOM VIEW)
17
16
PIN 1
INDICATOR
9 8
0.20 MIN
3.50 REF
0.80 MAX
0.65 TYP
0.05 MAX
0.02 NOM
0.30
0.25
0.18
0.20 REF
COPLANARITY
0.08
COMPLIANT TO JEDEC STANDARDS MO-220-VHHD-2
032807-A
PIN 1
INDICATOR
32 1
Figure 77. 32-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
5 mm × 5 mm Body, Very Thin Quad Lead
(CP-32-8)
Dimensions shown in millimeters
ORDERING GUIDE
Model
ADL5519ACPZ-R71
ADL5519ACPZ-R21
ADL5519ACPZ-WP1, 2
ADL5519-EVALZ1
1
2
Temperature Range
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
Package Description
32-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
32-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
32-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
Evaluation Board
Z = RoHS Compliant Part.
WP = waffle pack.
Rev. 0 | Page 39 of 40
Package Option
CP-32-8
CP-32-8
CP-32-8
ADL5519
NOTES
©2008 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D06198-0-1/08(0)
Rev. 0 | Page 40 of 40