Bidirectional, Zero Drift, Current Sense Amplifier AD8417 Data Sheet FEATURES GENERAL DESCRIPTION Typical 0.1 µV/°C offset drift Maximum ±400 µV voltage offset over full temperature range 2.7 V to 5.5 V power supply operating range Electromagnetic interference (EMI) filters Included High common-mode input voltage range −2 V to +70 V continuous −4 V to +85 V survival Initial gain = 60 V/V Wide operating temperature range: −40°C to +125°C Bidirectional operation Available in 8-lead SOIC and 8-lead MSOP Common-mode rejection ratio (CMRR): 86 dB, dc to 10 kHz Qualified for automotive applications The AD8417 is a high voltage, high resolution current shunt amplifier. It features an initial gain of 60 V/V, with a maximum ±0.3% gain error over the entire temperature range. The buffered output voltage directly interfaces with any typical converter. The AD8417 offers excellent input common-mode rejection from −2 V to +70 V. The AD8417 performs bidirectional current measurements across a shunt resistor in a variety of automotive and industrial applications, including motor control, power management, and solenoid control. The AD8417 offers breakthrough performance throughout the −40°C to +125°C temperature range. It features a zero drift core, which leads to a typical offset drift of 0.1 µV/°C throughout the operating temperature range and the common-mode voltage range. The AD8417 is qualified for automotive applications. The device includes EMI filters and patented circuitry to enable output accuracy with pulse-width modulation (PWM) type input common-mode voltages. The typical input offset voltage is ±200 µV. The AD8417 is offered in 8-lead MSOP and SOIC packages. APPLICATIONS High-side current sensing in Motor controls Solenoid controls Power management Low-side current sensing Diagnostic protection Table 1. Related Devices Part No. AD8205 AD8206 AD8207 AD8210 AD8418A Description Current sense amplifier, gain = 50 Current sense amplifier, gain = 20 High accuracy current sense amplifier, gain = 20 High speed current sense amplifier, gain = 20 High accuracy current sense amplifier, gain = 20 FUNCTIONAL BLOCK DIAGRAM VCM = –2V TO +70V VS = 2.7V TO 5.5V 70V VS VREF 1 AD8417 VCM +IN ISHUNT EMI FILTER OUT G = 60 RSHUNT 50A VOUT + 0V –IN VS VS/2 EMI FILTER – ISHUNT –50A VREF 2 11882-001 0V GND Figure 1. Rev. 0 Document Feedback Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 ©2013 Analog Devices, Inc. All rights reserved. Technical Support www.analog.com AD8417 Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 Unidirectional Operation .......................................................... 11 Applications ....................................................................................... 1 Bidirectional Operation ............................................................. 11 General Description ......................................................................... 1 External Referenced Output ..................................................... 12 Functional Block Diagram .............................................................. 1 Splitting the Supply .................................................................... 12 Revision History ............................................................................... 2 Splitting an External Reference ................................................ 12 Specifications..................................................................................... 3 Applications Information .............................................................. 13 Absolute Maximum Ratings ............................................................ 4 Motor Control ............................................................................. 13 ESD Caution .................................................................................. 4 Solenoid Control ........................................................................ 14 Pin Configuration and Function Descriptions ............................. 5 Outline Dimensions ....................................................................... 15 Typical Performance Characteristics ............................................. 6 Ordering Guide .......................................................................... 16 Theory of Operation ...................................................................... 10 Automotive Products ................................................................. 16 Output Offset Adjustment ............................................................. 11 REVISION HISTORY 11/13—Revision 0: Initial Version Rev. 0 | Page 2 of 16 Data Sheet AD8417 SPECIFICATIONS TA = −40°C to +125°C (operating temperature range), VS = 5 V, unless otherwise noted. Table 2. Parameter GAIN Initial Error Over Temperature Gain vs. Temperature VOLTAGE OFFSET Offset Voltage, Referred to the Input (RTI) Over Temperature (RTI) Offset Drift INPUT Input Bias Current Input Voltage Range Common-Mode Rejection Ratio (CMRR) OUTPUT Output Voltage Range Output Resistance DYNAMIC RESPONSE Small Signal −3 dB Bandwidth Slew Rate NOISE 0.1 Hz to 10 Hz (RTI) Spectral Density, 1 kHz (RTI) OFFSET ADJUSTMENT Ratiometric Accuracy 1 Accuracy, Referred to the Output (RTO) Output Offset Adjustment Range POWER SUPPLY Operating Range Quiescent Current Over Temperature Power Supply Rejection Ratio Temperature Range For Specified Performance 1 Test Conditions/Comments Min Typ Max Unit ±0.3 +10 V/V % ppm/°C ±400 +0.4 µV µV µV/°C 60 Specified temperature range −10 25°C Specified temperature range ±200 −0.4 +0.1 130 Common mode, continuous Specified temperature range, f = dc f = dc to 10 kHz −2 90 RL = 25 kΩ 0.045 Divider to supplies Voltage applied to VREF1 and VREF2 in parallel VS = 5 V 0.499 0.045 2.7 VOUT = 0.1 V dc +70 100 86 VS − 0.035 2 V Ω 250 1 kHz V/µs 2.3 110 µV p-p nV/√Hz 0.501 ±1 VS − 0.035 V/V mV/V V 5.5 4.1 V mA dB +125 °C 80 Operating temperature range −40 The offset adjustment is ratiometric to the power supply when VREF1 and VREF2 are used as a divider between the supplies. Rev. 0 | Page 3 of 16 µA V dB dB AD8417 Data Sheet ABSOLUTE MAXIMUM RATINGS Table 3. Parameter Supply Voltage Input Voltage Range Continuous Survival Differential Input Survival Reverse Supply Voltage ESD Human Body Model (HBM) Operating Temperature Range Storage Temperature Range Output Short-Circuit Duration Rating 6V −2 V to +70 V −4 V to +85 V ±5.5 V 0.3 V ±2000 V −40°C to +125°C −65°C to +150°C Indefinite Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. ESD CAUTION Rev. 0 | Page 4 of 16 Data Sheet AD8417 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS VREF 2 3 NC 4 8 +IN AD8417 7 VREF 1 TOP VIEW (Not to Scale) 6 VS 5 OUT 11882-002 –IN 1 GND 2 NC = NO CONNECT. DO NOT CONNECT TO THIS PIN. Figure 2. Pin Configuration Table 4. Pin Function Descriptions Pin No. 1 2 3 4 5 6 7 8 Mnemonic −IN GND VREF2 NC OUT VS VREF1 +IN Description Negative Input. Ground. Reference Input 2. No Connect. Do not connect to this pin. Output. Supply. Reference Input 1. Positive Input. Rev. 0 | Page 5 of 16 AD8417 Data Sheet TYPICAL PERFORMANCE CHARACTERISTICS 14 50 40 12 20 GAIN (dB) OFFSET VOLTAGE (µV) 30 10 8 6 10 0 –10 4 –20 2 –25 –10 5 20 35 50 65 80 95 110 125 TEMPERATURE (°C) –40 1000 11882-003 0 –40 100k 1M 10M FREQUENCY (Hz) Figure 3. Typical Offset Voltage Drift vs. Temperature Figure 6. Typical Small Signal Bandwidth (VOUT = 200 mV p-p) 120 10 9 TOTAL OUTPUT ERROR (%) 110 100 CMRR (dB) 10k 11882-006 –30 90 80 70 8 7 6 5 4 3 2 60 1k 10k 100k 1M FREQUENCY (Hz) 0 11882-004 100 0 5 10 15 20 25 30 35 40 DIFFERENTIAL INPUT VOLTAGE (mV) Figure 4. Typical CMRR vs. Frequency 11882-007 1 50 10 Figure 7. Total Output Error vs. Differential Input Voltage 500 0.5 NORMALIZED AT 25°C 400 BIAS CURRENT PER INPUT PIN (mA) 0.4 200 100 0 –100 –200 –300 –400 +IN 0.2 0.1 0 –IN –0.1 –0.2 –0.3 –25 –10 5 20 35 50 65 80 95 TEMPERATURE (°C) 110 125 VS = 2.7V –0.5 –4 0 4 8 12 16 20 24 28 32 36 40 44 48 52 56 60 64 68 VCM (V) 11882-008 –500 –40 0.3 –0.4 11882-005 GAIN ERROR (µV/V) 300 Figure 8. Bias Current per Input Pin vs. Common-Mode Voltage (VCM) Figure 5. Typical Gain Error vs. Temperature Rev. 0 | Page 6 of 16 Data Sheet AD8417 4.5 VS = 5V VS = 2.7V 4.0 INPUT 3.0 2.5 1V/DIV 2.0 5 10 15 20 25 30 35 40 45 50 55 60 65 70 INPUT COMMON-MODE VOLTAGE (V) VS = 2.7V 11882-012 0 11882-009 1.0 –5 VS = 5V 11882-013 OUTPUT 1.5 TIME (1µs/DIV) Figure 9. Supply Current vs. Input Common-Mode Voltage Figure 12. Fall Time (VS = 2.7 V) INPUT 25mV/DIV INPUT 25mV/DIV OUTPUT OUTPUT 500mV/DIV VS = 2.7V TIME (1µs/DIV) 11882-010 1V/DIV TIME (1µs/DIV) Figure 10. Rise Time (VS = 2.7 V) Figure 13. Fall Time (VS = 5 V) INPUT 25mV/DIV 25mV/DIV INPUT OUTPUT 500mV/DIV OUTPUT VS = 2.7V TIME (1µs/DIV) Figure 11. Rise Time (VS = 5 V) 11882-014 VS = 5V TIME (1µs/DIV) 1V/DIV 11882-011 SUPPLY CURRENT (mA) 25mV/DIV 3.5 Figure 14. Differential Overload Recovery, Rising (VS = 2.7 V) Rev. 0 | Page 7 of 16 AD8417 Data Sheet INPUT 50mV/DIV OUTPUT 100mV/DIV OUTPUT INPUT COMMON MODE 2V/DIV Figure 15. Differential Overload Recovery, Rising (VS = 5 V) 11882-018 VS = 5V TIME (1µs/DIV) 11882-015 40V/DIV TIME (4 µs/DIV) Figure 18. Input Common-Mode Step Response (VS = 5 V, Inputs Shorted) 25mV/DIV INPUT 1V/DIV OUTPUT TIME (1µs/DIV) 35 30 5V 25 2.7V 20 15 10 5 0 –40 11882-016 VS = 2.7V 40 –25 –10 5 20 35 50 65 80 95 110 125 11882-019 MAXIMUM OUTPUT SINK CURRENT (mA) 45 Figure 19. Maximum Output Sink Current vs. Temperature Figure 16. Differential Overload Recovery, Falling (VS = 2.7 V) 50mV/DIV INPUT 2V/DIV OUTPUT 30 5V 25 2.7V 20 15 10 5 0 –40 11882-017 VS = 5V TIME (1µs/DIV) 35 –25 –10 5 20 35 50 65 80 95 110 125 Figure 20. Maximum Output Source Current vs. Temperature Figure 17. Differential Overload Recovery, Falling (VS = 5 V) Rev. 0 | Page 8 of 16 11882-020 MAXIMUM OUTPUT SOURCE CURRENT (mA) 40 Data Sheet AD8417 0 0.15 NORMALIZED AT 25°C OUTPUT VOLTAGE RANGE FROM POSITIVE RAIL (mV) –50 0.10 –100 –150 CMRR (µV/V) 0.05 –200 –250 –300 0 –0.05 –350 –400 –0.10 0 1 2 3 4 5 6 7 8 9 10 OUTPUT SOURCE CURRENT (mA) –0.15 –40 –25 –10 Figure 21. Output Voltage Range from Positive Rail vs. Output Source Current 5 20 35 50 65 80 95 110 125 11882-024 –500 11882-021 –450 Figure 24. CMRR vs. Temperature 300 250 2100 1800 200 1500 HITS OUTPUT VOLTAGE RANGE FROM POSITIVE RAIL (mV) 2400 150 1200 900 100 600 50 0 1 2 3 4 5 6 7 8 9 10 OUTPUT SINK CURRENT (mA) Figure 22. Output Voltage Range from Ground vs. Output Sink Current 1800 1500 –40°C +25°C +125°C 900 600 300 0 –400 –300 –200 –100 0 100 200 VOSI WITH VCC = 5.0V (µV) 300 400 11882-023 HITS 1200 Figure 23. Offset Voltage Distribution Rev. 0 | Page 9 of 16 0 –8 –6 –4 –2 0 2 4 GAIN ERROR DRIFT (ppm/°C) Figure 25. Gain Error Drift Distribution 6 8 11882-125 0 11882-022 300 AD8417 Data Sheet THEORY OF OPERATION architecture that does not compromise bandwidth, which is typically rated at 250 kHz. The AD8417 is a single-supply, zero drift, difference amplifier that uses a unique architecture to accurately amplify small differential current shunt voltages in the presence of rapidly changing common-mode voltages. The reference inputs, VREF1 and VREF2, are tied through 100 kΩ resistors to the positive input of the main amplifier, which allows the output offset to be adjusted anywhere in the output operating range. The gain is 1 V/V from the reference pins to the output when the reference pins are used in parallel. When the pins are used to divide the supply, the gain is 0.5 V/V. In typical applications, the AD8417 measures current by amplifying the voltage across a shunt resistor connected to its inputs by a gain of 60 V/V (see Figure 26). The AD8417 design provides excellent common-mode rejection, even with PWM common-mode inputs that can change at very fast rates, for example, 1 V/ns. The AD8417 contains patented technology to eliminate the negative effects of such fast changing external common-mode variations. The AD8417 offers breakthrough performance without compromising any of the robust application needs typical of solenoid or motor control. The ability to reject PWM input common-mode voltages and the zero drift architecture providing low offset and offset drift allows the AD8417 to deliver total accuracy for these demanding applications. The AD8417 features an input offset drift of less than 0.4 µV/°C. This performance is achieved through a novel zero drift VCM = –2V TO +70V VS = 2.7V TO 5.5V 70V VS VREF 1 AD8417 VCM +IN ISHUNT EMI FILTER OUT G = 60 RSHUNT 50A VOUT + 0V –IN VS VS/2 EMI FILTER – ISHUNT VREF 2 –50A Figure 26. Typical Application Rev. 0 | Page 10 of 16 11882-225 0V GND Data Sheet AD8417 OUTPUT OFFSET ADJUSTMENT UNIDIRECTIONAL OPERATION Unidirectional operation allows the AD8417 to measure currents through a resistive shunt in one direction. The basic modes for unidirectional operation are ground referenced output mode and VS referenced output mode. VS Referenced Output Mode VS referenced output mode is set when both reference pins are tied to the positive supply. It is typically used when the diagnostic scheme requires detection of the amplifier and the wiring before power is applied to the load (see Figure 28). VS For unidirectional operation, the output can be set at the negative rail (near ground) or at the positive rail (near VS) when the differential input is 0 V. The output moves to the opposite rail when a correct polarity differential input voltage is applied. The required polarity of the differential input depends on the output voltage setting. If the output is set at the positive rail, the input polarity must be negative to decrease the output. If the output is set at ground, the polarity must be positive to increase the output. AD8417 R4 –IN VS + R2 VREF 1 R3 VREF 2 Figure 28. VS Referenced Output BIDIRECTIONAL OPERATION Bidirectional operation allows the AD8417 to measure currents through a resistive shunt in two directions. In this case, the output is set anywhere within the output range. Typically, it is set at half-scale for equal range in both directions. In some cases, however, it is set at a voltage other than half scale when the bidirectional current is nonsymmetrical. AD8417 R4 – OUT Adjusting the output is accomplished by applying voltage(s) to the referenced inputs. VREF1 and VREF2 are tied to internal resistors that connect to an internal offset node. There is no operational difference between the pins. + +IN OUT GND When using the AD8417 in ground referenced output mode, both referenced inputs are tied to ground, which causes the output to sit at the negative rail when there are zero differential volts at the input (see Figure 27). R1 – +IN Ground Referenced Output Mode –IN R1 11882-026 The output of the AD8417 can be adjusted for unidirectional or bidirectional operation. R2 VREF 1 R3 VREF 2 11882-025 GND Figure 27. Ground Referenced Output Rev. 0 | Page 11 of 16 AD8417 Data Sheet EXTERNAL REFERENCED OUTPUT VS Tying both pins together and to a reference produces an output equal to the reference voltage when there is no differential input (see Figure 29). The output decreases the reference voltage when the input is negative, relative to the −IN pin, and increases when the input is positive, relative to the −IN pin. AD8417 R4 –IN R1 – + +IN VS OUT R2 VREF 1 R3 VREF 2 R4 –IN R1 GND – OUT Figure 30. Split Supply + +IN 11882-028 AD8417 R2 SPLITTING AN EXTERNAL REFERENCE VREF 1 R3 VREF 2 GND 11882-027 2.5V Figure 29. External Referenced Output Use the internal reference resistors to divide an external reference by 2 with an accuracy of approximately 0.5%. Split an external reference by connecting one VREFx pin to ground and the other VREFx pin to the reference (see Figure 31). VS SPLITTING THE SUPPLY AD8417 R4 –IN R1 – OUT + +IN Rev. 0 | Page 12 of 16 R2 VREF 1 R3 VREF 2 GND Figure 31. Split External Reference 5V 11882-029 By tying one reference pin to VS and the other to the ground pin, the output is set at half of the supply when there is no differential input (see Figure 30). The benefit of this configuration is that an external reference is not required to offset the output for bidirectional current measurement. Tying one reference pin to VS and the other to the ground pin creates a midscale offset that is ratiometric to the supply, which means that if the supply increases or decreases, the output remains at half the supply. For example, if the supply is 5.0 V, the output is at half scale or 2.5 V. If the supply increases by 10% (to 5.5 V), the output increases to 2.75 V. Data Sheet AD8417 APPLICATIONS INFORMATION MOTOR CONTROL 3-Phase Motor Control The AD8417 is ideally suited for monitoring current in 3-phase motor applications. The 250 kHz typical bandwidth of the AD8417 provides instantaneous current monitoring. Additionally, the typical low offset drift of 0.1 µV/°C means that the measurement error between the two motor phases is at a minimum over temperature. The AD8417 rejects PWM input common-mode voltages in the −2 V to +70 V (with a 5 V supply) range. Monitoring the current on the motor phase allows sampling of the current at any point and provides diagnostic information, such as a short to GND and battery. Refer to Figure 33 for the typical phase current measurement setup with the AD8417. amp because ground is not typically a stable reference voltage in this type of application. The instability of the ground reference causes inaccuracies in the measurements that can be made with a simple ground referenced op amp. The AD8417 measures current in both directions as the H-bridge switches and the motor changes direction. The output of the AD8417 is configured in an external referenced bidirectional mode (see the Bidirectional Operation section). CONTROLLER 5V +IN MOTOR VREF 1 VS OUT AD8417 SHUNT –IN GND VREF 2 NC 5V 2.5V 11882-030 H-Bridge Motor Control Another typical application for the AD8417 is to form part of the control loop in H-bridge motor control. In this case, place the shunt resistor in the middle of the H-bridge to accurately measure current in both directions by using the shunt available at the motor (see Figure 32). Using an amplifier and shunt in this location is a better solution than a ground referenced op Figure 32. H-Bridge Motor Control V+ IU IV IW M 5V 5V V– OPTIONAL DEVICE FOR OVERCURRENT PROTECTION AND FAST (DIRECT) SHUTDOWN OF POWER STAGE INTERFACE CIRCUIT AD8417 AD8417 CONTROLLER BIDIRECTIONAL CURRENT MEASUREMENT REJECTION OF HIGH PWM COMMON-MODE VOLTAGE (–2V TO +70V) AMPLIFICATION HIGH OUTPUT DRIVE Figure 33. 3-Phase Motor Control Rev. 0 | Page 13 of 16 11882-031 AD8214 AD8417 Data Sheet SOLENOID CONTROL +IN + OUTPUT 5 11882-033 4 –IN 3 11882-032 8 NC = NO CONNECT. GND In the high rail, current sensing configuration, the shunt resistor is referenced to the battery. High voltage is present at the inputs of the current sense amplifier. When the shunt is battery referenced, the AD8417 produces a linear ground referenced analog output. Additionally, the AD8214 provides an overcurrent detection signal in as little as 100 ns (see Figure 36). This feature is useful in high current systems where fast shutdown in overcurrent conditions is essential. NC 2 VREF 2 1 –IN SWITCH 4 High Rail Current Sensing AD8417 SHUNT 3 Figure 35. High-Side Switch NC GND 6 2 1 7 OUT OUT VS VREF 1 +IN 7 8 INDUCTIVE LOAD NC = NO CONNECT. – GND BATTERY 5 AD8417 –IN CLAMP DIODE 5V INDUCTIVE LOAD 6 – SHUNT In this circuit configuration, when the switch is closed, the common-mode voltage decreases to near the negative rail. When the switch is open, the voltage reversal across the inductive load causes the common-mode voltage to be held one diode drop above the battery by the clamp diode. CLAMP DIODE 7 8 OUTPUT NC BATTERY VREF 2 In the case of a high-side current sense with a low-side switch, the PWM control switch is ground referenced. Tie an inductive load (solenoid) to a power supply and place a resistive shunt between the switch and the load (see Figure 34). An advantage of placing the shunt on the high side is that the entire current, including the recirculation current, is measurable because the shunt remains in the loop when the switch is off. In addition, diagnostics are enhanced because shorts to ground are detected with the shunt on the high side. + VREF 1 SWITCH OUT High-Side Current Sense with a Low-Side Switch VS 5V OVERCURRENT DETECTION (<100ns) OUTPUT 5 6 AD8214 Figure 34. Low-Side Switch Rev. 0 | Page 14 of 16 4 NC 3 CLAMP DIODE –IN GND VREF 2 1 8 2 AD8417 3 TOP VIEW (Not to Scale) NC 4 7 6 5 NC = NO CONNECT. + +IN INDUCTIVE LOAD VREF 1 VS OUT – BATTERY SHUNT 5V SWITCH 11882-034 When using a high-side switch, the battery voltage is connected to the load when the switch is closed, causing the common-mode voltage to increase to the battery voltage. In this case, when the switch is open, the voltage reversal across the inductive load causes the common-mode voltage to be held one diode drop below ground by the clamp diode. 2 VREG The high-side current sense with a high-side switch configuration minimizes the possibility of unexpected solenoid activation and excessive corrosion (see Figure 35). In this case, both the switch and the shunt are on the high side. When the switch is off, the battery is removed from the load, which prevents damage from potential shorts to ground while still allowing the recirculating current to be measured and to provide diagnostics. Removing the power supply from the load for the majority of the time that the switch is open minimizes the corrosive effects that can be caused by the differential voltage between the load and ground. VS 1 +IN High-Side Current Sense with a High-Side Switch Figure 36. High Rail Current Sensing Data Sheet AD8417 OUTLINE DIMENSIONS 5.00 (0.1968) 4.80 (0.1890) 8 4.00 (0.1574) 3.80 (0.1497) 5 1 6.20 (0.2441) 5.80 (0.2284) 4 1.27 (0.0500) BSC 0.25 (0.0098) 0.10 (0.0040) 1.75 (0.0688) 1.35 (0.0532) 0.51 (0.0201) 0.31 (0.0122) COPLANARITY 0.10 SEATING PLANE 0.50 (0.0196) 0.25 (0.0099) 45° 8° 0° 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157) 012407-A COMPLIANT TO JEDEC STANDARDS MS-012-AA CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 37. 8-Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-8) Dimensions shown in millimeters and (inches) 3.20 3.00 2.80 8 3.20 3.00 2.80 1 5.15 4.90 4.65 5 4 PIN 1 IDENTIFIER 0.65 BSC 0.95 0.85 0.75 15° MAX 1.10 MAX 0.40 0.25 6° 0° 0.23 0.09 COMPLIANT TO JEDEC STANDARDS MO-187-AA Figure 38. 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters Rev. 0 | Page 15 of 16 0.80 0.55 0.40 10-07-2009-B 0.15 0.05 COPLANARITY 0.10 AD8417 Data Sheet ORDERING GUIDE Model 1, 2 AD8417BRMZ AD8417BRMZ-RL AD8417WBRMZ AD8417WBRMZ-RL AD8417WBRZ AD8417WBRZ-RL 1 2 Temperature Range −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C Package Description 8-Lead MSOP 8-Lead MSOP, 13” Tape and Reel 8-Lead MSOP 8-Lead MSOP, 13” Tape and Reel 8-Lead SOIC_N 8-Lead SOIC_N, 13” Tape and Reel Package Option RM-8 RM-8 RM-8 RM-8 R-8 R-8 Branding Y4Y Y4Y Y4X Y4X Z = RoHS Compliant Part. W = Qualified for Automotive Applications. AUTOMOTIVE PRODUCTS The AD8417W models are available with controlled manufacturing to support the quality and reliability requirements of automotive applications. Note that these automotive models may have specifications that differ from the commercial models; therefore, designers should review the Specifications section of this data sheet carefully. Only the automotive grade products shown are available for use in automotive applications. Contact your local Analog Devices account representative for specific product ordering information and to obtain the specific Automotive Reliability reports for these models. ©2013 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D11882-0-11/13(0) Rev. 0 | Page 16 of 16