AD ADP3000AR-5 Micropower step-up/step-down fixed 3.3 v, 5 v, 12 v and adjustable high frequency switching regulator Datasheet

a
Micropower Step-Up/Step-Down
Fixed 3.3 V, 5 V, 12 V and Adjustable
High Frequency Switching Regulator
ADP3000
FEATURES
Operates at Supply Voltages from 2 V to 30 V
Works in Step-Up or Step-Down Mode
Very Few External Components Required
High Frequency Operation Up to 400 kHz
Low Battery Detector on Chip
User Adjustable Current Limit
Fixed and Adjustable Output Voltage
8-Pin DIP and SO-8 Package
Small Inductors and Capacitors
FUNCTIONAL BLOCK DIAGRAM
SET
A0
A1
VIN
ILIM
GAIN BLOCK/
ERROR AMP
1.245V
REFERENCE
SW1
400kHz
OSCILLATOR
DRIVER
ADP3000
R1
R2
GND
SENSE
6.8µH
GENERAL DESCRIPTION
VIN
2V–3.2V
The ADP3000 is a versatile step-up/step-down switching
regulator that operates from an input supply voltage of 2 V to
12 V in step-up mode and up to 30 V in step-down mode.
100µF
10V
IN5817
3.3V @
180mA
120Ω
1
ILIM
2
VIN
SW1 3
ADP3000-3.3V
The ADP3000 operates in Pulse Frequency Mode (PFM) and
consumes only 500 µA, making it highly suitable for applications that require low quiescent current.
FB
8
(SENSE)
GND
SW2
5
4
The ADP3000 can deliver an output current of 100 mA at
3 V from a 5 V input in step-down configuration and 180 mA at
3.3 V from a 2 V input in step-up configuration.
+
C1
100µF
10V
C1, C2: AVX TPS D107 M010R0100
L1: SUMIDA CD43-6R8
The auxiliary gain amplifier can be used as a low battery detector,
linear regulator undervoltage lockout or error amplifier.
The ADP3000 operates at 400 kHz switching frequency. This
allows the use of small external components (inductors and
capacitors), making the device very suitable for space constrained
designs.
SW2
COMPARATOR
APPLICATIONS
Notebook, Palmtop Computers
Cellular Telephones
Hard Disk Drives
Portable Instruments
Pagers
Figure 1. Typical Application
VIN
5V–6V
C1
100µF
10V
RLIM
120Ω
1
ILIM
2
3
VIN
SW1
FB 8
ADP3000
L1
10µH
SW2 4
GND
5
D1
1N5818
CL +
100µF
10V
R2
150kΩ
1%
VOUT
3V
100mA
R1
110kΩ
1%
C1, C2: AVX TPS D107 M010R0100
L1: SUMIDA CD43-100
Figure 2. Step-Down Mode Operation
REV. 0
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700
World Wide Web Site: http://www.analog.com
Fax: 617/326-8703
© Analog Devices, Inc., 1997
ADP3000–SPECIFICATIONS (08C ≤ T ≤ +708C, V
A
IN
= 3 V unless otherwise noted)*
Parameter
Conditions
Symbol
Min
INPUT VOLTAGE
Step-Up Mode
Step-Down Mode
VIN
2.0
SHUTDOWN QUIESCENT CURRENT
VFB > 1.43 V; VSENSE > 1.1 × VOUT
IQ
1
COMPARATOR TRIP POINT
VOLTAGE
ADP3000
OUTPUT SENSE VOLTAGE
ADP3000-3.32
ADP3000-52
ADP3000-122
VOUT
ADP3000
Typ
Max
12.6
30.0
Units
V
V
µA
500
1.20
1.245
1.30
V
3.135
4.75
11.40
3.3
5.00
12.00
3.465
5.25
12.60
V
V
V
COMPARATOR HYSTERESIS
ADP3000
8
12.5
mV
OUTPUT HYSTERESIS
ADP3000-3.3
ADP3000-5
ADP3000-12
32
32
75
50
50
120
mV
mV
mV
450
kHz
OSCILLATOR FREQUENCY
fOSC
350
400
DUTY CYCLE
VFB > VREF
D
65
80
SWITCH ON TIME
ILIM Tied to VIN, VFB = 0
tON
1.5
2
2.55
µs
SWITCH SATURATION VOLTAGE
STEP-UP MODE
TA = +25°C
VIN = 3.0 V, ISW = 650 mA
VIN = 5.0 V, ISW = 1 A
VIN = 12 V, ISW = 650 mA
VSAT
0.5
0.8
1.1
0.75
1.1
1.5
V
V
V
STEP-DOWN MODE
%
FEEDBACK PIN BIAS CURRENT
ADP3000 VFB = 0 V
IFB
160
330
nA
SET PIN BIAS CURRENT
VSET = VREF
ISET
200
400
nA
GAIN BLOCK OUTPUT LOW
ISINK = 300 µA
VSET = 1.00 V
VOL
0.15
0.4
V
REFERENCE LINE REGULATION
5 V ≤ VIN ≤ 30 V
2 V ≤ VIN ≤ 5 V
0.02
0.2
0.15
0.6
%/V
%/V
GAIN BLOCK GAIN
RL = 100 kΩ3
AV
GAIN BLOCK CURRENT SINK
VSET ≤ 1 V
CURRENT LIMIT
220 Ω from ILIM to VIN
CURRENT LIMIT TEMPERATURE
COEFFICIENT
SWITCH OFF LEAKAGE CURRENT
Measured at SW1 Pin
VSW1 = 12 V, TA = +25°C
MAXIMUM EXCURSION BELOW GND
TA = +25°C
ISW1 ≤ 10 µA, Switch Off
1000
6000
V/V
ISINK
300
µA
ILIM
400
mA
–0.3
%/°C
1
10
µA
–400
–350
mV
NOTES
1
This specification guarantees that both the high and low trip point of the comparator fall within the 1.20 V to 1.30 V range.
2
The output voltage waveform will exhibit a sawtooth shape due to the comparator hysteresis. The output voltage on the fixed output versions will always be within the
specified range.
3
100 kΩ resistor connected between a 5 V source and the AO pin.
*All limits at temperature extremes are guaranteed via correlation using standard statistical methods.
Specifications subject to change without notice.
–2–
REV. 0
ADP3000
PIN DESCRIPTIONS
Mnemonic
ILIM
ABSOLUTE MAXIMUM RATINGS
Function
For normal conditions this pin is connected to
VIN. When lower current is required, a resistor
should be connected between ILIM and VIN.
Limiting the switch current to 400 mA is
achieved by connecting a 220 Ω resistor.
Input Voltage.
Collector of power transistor. For step-down
configuration, connect to VIN. For step-up
configuration, connect to an inductor/diode.
Emitter of power transistor. For step-down
configuration, connect to inductor/diode.
For step-up configuration, connect to ground.
Do not allow this pin to go more than a diode
drop below ground.
Ground.
Auxiliary Gain (GB) output. The open collector can sink 300 µA. It can be left open
if not used.
SET Gain amplifier input. The amplifier’s
positive input is connected to SET pin and its
negative input is connected to 1.245 V. It can
be left open if not used.
On the ADP3000 (adjustable) version, this pin
is connected to the comparator input. On the
ADP3000-3.3, ADP3000-5 and ADP3000-12,
the pin goes directly to the internal resistor
divider that sets the output voltage.
VIN
SW1
SW2
GND
AO
SET
FB/SENSE
Input Supply Voltage, Step-Up Mode . . . . . . . . . . . . . . . 15 V
Input Supply Voltage, Step-Down Mode . . . . . . . . . . . . . 36 V
SW1 Pin Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 50 V
SW2 Pin Voltage . . . . . . . . . . . . . . . . . . . . . . . . –0.5 V to VIN
Feedback Pin Voltage (ADP3000) . . . . . . . . . . . . . . . . . .5.5 V
Switch Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .1.5 A
Maximum Power Dissipation . . . . . . . . . . . . . . . . . . 500 mW
Operating Temperature Range . . . . . . . . . . . . . 0°C to +70°C
Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C
Lead Temperature (Soldering, 10 sec) . . . . . . . . . . . . +300°C
Thermal Impedance
SO-8 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 170°C/W
N-8 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 120°C/W
PIN CONFIGURATIONS
8-Lead Plastic DIP
8-Lead SOIC
(N-8)
(SO-8)
8 FB (SENSE)*
ILIM 1
VIN 2
ADP3000
7 SET
ADP3000
7 SET
TOP VIEW
SW1 3 (Not to Scale) 6 AO
VIN 2
TOP VIEW
SW1 3 (Not to Scale) 6 AO
5 GND
SW2 4
8 FB (SENSE)*
ILIM 1
5 GND
SW2 4
* FIXED VERSIONS
* FIXED VERSIONS
ORDERING GUIDE
Output
Voltage
3.3 V
3.3 V
5V
5V
12 V
12 V
Adjustable
Adjustable
Model
ADP3000AN-3.3
ADP3000AR-3.3
ADP3000AN-5
ADP3000AR-5
ADP3000AN-12
ADP3000AR-12
ADP3000AN
ADP3000AR
Package
Option
N-8
SO-8
N-8
SO-8
N-8
SO-8
N-8
SO-8
N = plastic DIP, SO = small outline package.
SET
SET
A0
A2
VIN
1.245V
REFERENCE
A1
A0
A1
VIN
ILIM
GAIN BLOCK/
ERROR AMP
SW1
1.245V
REFERENCE
OSCILLATOR
DRIVER
COMPARATOR
DRIVER
SW2
COMPARATOR
SW2
ADP3000
R1
FB
GND
Figure 3a. Functional Block Diagram for Adjustable Version
R2
SENSE
Figure 3b. Functional Block Diagram for Fixed Version
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the ADP3000 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
REV. 0
SW1
OSCILLATOR
ADP3000
GND
ILIM
GAIN BLOCK/
ERROR AMP
–3–
WARNING!
ESD SENSITIVE DEVICE
ADP3000–Typical Characteristics
2.5
QUIESCENT CURRENT – µA
VIN = 5V @ TA = +25°C
1.0
0.4 0.6 0.8 1.0 1.2
SWITCH CURRENT – A
1.4
0.0
0.1
1.5
Figure 4. Switch ON Voltage vs.
Switch Current in Step-Up Mode
0.8
OSCILLATOR FREQUENCY –
@ TA = +25°C
405
0.2
0.3
0.4
0.5
0.6
SWITCH CURRENT – A
0.8
SWITCH CURRENT – A
403
402
401
400
399
TA = +25°C
0.6
TA = +85°C
0.5
0.4
0.3
0.2
4
6
Figure 7. Oscillator Frequency vs.
Input Voltage
1.8
1.2
TA = 0°C
TA = +25°C
1.0
TA = +85°C
0.8
0.6
0.4
0.2
100
10
1
10
100
1k
RLIM – Ω
Figure 8c. Maximum Switch Current
vs. RLIM in Step-Up Mode (3 V)
TA = 0°C
1.4
1.2
TA = +85°C
1.0
0.8
0.6
0.4
1
1k
Figure 8a. Maximum Switch Current
vs. RLIM in Step-Down Mode (5 V)
2.30
2.25
420
2.20
410
2.15
390
380
370
2.10
2.05
2.00
1.95
360
1.90
350
330
–40
1k
Figure 8b. Maximum Switch Current
vs. RLIM in Step-Down Mode (12 V)
430
400
100
10
RLIM – Ω
440
1.85
340
0
30
TA = +25°C
VIN = 12V
RLIM – Ω
OSCILLATOR FREQUENCY – kHz
1.4
9 12 15 18 21 24 27
INPUT VOLTAGE – V
0
1
VIN = 3V
1.6
6
0.2
0
8 10 12 15 18 21 24 27 30
INPUT VOLTAGE – V
3
1.6
ON TIME – µs
2
400
1.8
TA = 0°C
VIN = 5V
0.1
396
600
Figure 6. Quiescent Current vs.
Input Voltage
0.7
404
800
0
1.5
0.9
Figure 5. Saturation Voltage vs.
Switch Current in Step-Down Mode
406
QUIESCENT CURRENT @ TA = +25°C
1000
200
0.2
VIN = 2V @ TA = +25°C
0.2
0.6
0.4
VIN = 3V @ TA = +25°C
0
0.1
VIN = 12V @ TA = +25°C
0.8
SWITCH CURRENT – A
1.5
VCE(SAT) – V
ON VOLTAGE – V
1200
1.0
0.5
OSCILLATOR FREQUENCY – kHz
VIN = 5V @ TA = +25°C
1.2
2.0
SWITCH CURRENT – A
1400
1.4
25
70
0
TEMPERATURE – °C (TA)
85
Figure 9. Oscillator Frequency vs.
Temperature
–4–
1.80
–40
25
70
0
TEMPERATURE – °C (TA)
85
Figure 10. Switch ON Time vs.
Temperature
REV. 0
ADP3000
SATURATION VOLTAGE – V
90
DUTY CYCLE – %
80
70
60
50
40
30
20
1.25
0.54
1.20
0.52
1.15
VIN = 12V @ ISW = 0.65A
0.50
0.48
VIN = 3V @ ISW = 0.65A
0.46
0.44
10
0
–40
0.56
ON VOLTAGE – V
100
25
70
0
TEMPERATURE – °C (TA)
0.42
–40
85
Figure 11. Duty Cycle vs.
Temperature
1.05
1.00
0.95
25
70
0
TEMPERATURE – °C (TA)
0.90
–40
85
0
25
70
85
TEMPERATURE – °C (TA)
Figure 12. Saturation Voltage vs.
Temperature in Step-Up Mode
250
1.10
Figure 13. Switch ON Voltage vs.
Temperature in Step-Down Mode
700
350
VIN = 20V
600
150
100
50
300
BIAS CURRENT – µA
QUIESCENT CURRENT – µA
BIAS CURRENT – µA
200
500
400
300
200
100
0
–40
25
70
0
TEMPERATURE – °C (TA)
85
Figure 14. Feedback Bias Current
vs. Temperature
REV. 0
0
–40
250
200
150
100
50
0
25
70
TEMPERATURE – °C (TA)
Figure 15. Quiescent Current vs.
Temperature
–5–
85
0
–40
0
25
70
TEMPERATURE – °C (TA)
85
Figure 16. Set Pin Bias Current vs.
Temperature
ADP3000
THEORY OF OPERATION
APPLICATIONS INFORMATION
The ADP3000 is a versatile, high frequency, switch mode
power supply (SMPS) controller. The regulated output
voltage can be greater than the input voltage (boost or step-up
mode) or less than the input (buck or step-down mode). This
device uses a gated oscillator technique to provide high performance with low quiescent current.
COMPONENT SELECTION
Inductor Selection
For most applications the inductor used with the ADP3000 will
fall in the range between 4.7 µH to 33 µH. Table I shows
recommended inductors and their vendors.
When selecting an inductor, it is very important to make sure
that the inductor used with the ADP3000 is able to handle a
current that is higher than the ADP3000’s current limit without
saturation.
A functional block diagram of the ADP3000 is shown in
Figure 3a. The internal 1.245 V reference is connected to one
input of the comparator, while the other input is externally
connected (via the FB pin) to a resistor divider connected to
the regulated output. When the voltage at the FB pin falls below
1.245 V, the 400 kHz oscillator turns on. A driver amplifier
provides base drive to the internal power switch and the switching
action raises the output voltage. When the voltage at the FB
pin exceeds 1.245 V, the oscillator is shut off. While the
oscillator is off, the ADP3000 quiescent current is only 500 µA.
The comparator’s hysteresis ensures loop stability without
requiring external components for frequency compensation.
As a rule of thumb, powdered iron cores saturate softly, whereas
Ferrite cores saturate abruptly. Rod or “open” drum core
geometry inductors saturate gradually. Inductors that saturate
gradually are easier to use. Even though rod or drum core
inductors are attractive in both price and physical size, these
types of inductors must be handled with care because they have
high magnetic radiation. Toroid or “closed” core geometry
should be used when minimizing EMI is critical.
In addition, inductor dc resistance causes power loss. It is best
to use low dc resistance inductors so that power loss in the
inductor is kept to the minimum. Typically, it is best to use an
inductor with a dc resistance lower than 0.2 Ω.
The maximum current in the internal power switch can be set
by connecting a resistor between VIN and the ILIM pin. When
the maximum current is exceeded, the switch is turned OFF.
The current limit circuitry has a time delay of about 0.3 µs. If
an external resistor is not used, connect ILIM to VIN. This
yields the maximum feasible current limit. Further information
on ILIM is included in the “Applications” section of this data
sheet. The ADP3000 internal oscillator provides typically 1.7
µs ON and 0.8 µs OFF times.
Table I. Recommended Inductors
An uncommitted gain block on the ADP3000 can be connected as a low battery detector. The inverting input of the
gain block is internally connected to the 1.245 V reference.
The noninverting input is available at the SET pin. A resistor
divider, connected between VIN and GND with the junction
connected to the SET pin, causes the AO output to go LOW
when the low battery set point is exceeded. The AO output is
an open collector NPN transistor that can sink in excess of
300 µA.
Vendor
Series
Core Type
Phone Numbers
Coiltronics
Coiltronics
OCTAPAC
UNIPAC
Toroid
Open
(407) 241-7876
(407) 241-7876
Sumida
Sumida
CD43, CD54
Open
CDRH62, CDRH73, Semi-Closed
CDRH64
Geometry
(847) 956-0666
(847) 956-0666
Capacitor Selection
For most applications, the capacitor used with the ADP3000
will fall in the range between 33 µF to 220 µF. Table II shows
recommended capacitors and their vendors.
The ADP3000 provides external connections for both the
collector and emitter of its internal power switch, which permits
both step-up and step-down modes of operation. For the stepup mode, the emitter (Pin SW2) is connected to GND and the
collector (Pin SW1) drives the inductor. For step-down mode,
the emitter drives the inductor while the collector is connected
to VIN.
For input and output capacitors, use low ESR type capacitors
for best efficiency and lowest ripple. Recommended capacitors
include AVX TPS series, Sprague 595D series, Panasonic HFQ
series and Sanyo OS-CON series.
The output voltage of the ADP3000 is set with two external
resistors. Three fixed voltage models are also available:
ADP3000–3.3 (+3.3 V), ADP3000–5 (+5 V) and ADP3000–12
(+12 V). The fixed voltage models include laser-trimmed
voltage-setting resistors on the chip. On the fixed voltage models
of the ADP3000, simply connect the feedback pin (Pin 8)
directly to the output voltage.
It is best to protect the input capacitor from high turn-on current charging surges by derating the capacitor voltage by 2:1.
For very low input or output voltage ripple requirements,
Sanyo OS-CON series capacitors can be used since this type of
capacitor has very low ESR. Alternatively, two or more tantalum capacitors can be used in parallel.
When selecting a capacitor, it is important to make sure the
maximum capacitor ripple current rms rating is higher than the
ADP3000’s rms switching current.
–6–
REV. 0
ADP3000
Table II. Recommended Capacitors
Vendor
Series
Type
Phone Numbers
AVX
Sanyo
Sprague
Panasonic
TPS
OS-CON
595D
HFQ
Surface Mount
Through-Hole
Surface Mount
Through-Hole
(803) 448-9411
(619) 661-6835
(603) 224-1961
(201) 348-5200
DIODE SELECTION
The ADP3000’s high switching speed demands the use of
Schottky diodes. Suitable choices include the 1N5817, 1N5818,
1N5819, MBRS120LT3 and MBR0520LT1. Do not use fast
recovery diodes because their high forward drop lowers efficiency. Neither general-purpose diodes nor small signal diodes
should be used.
PROGRAMMING THE SWITCHING CURRENT LIMIT
OF THE POWER SWITCH
The ADP3000’s RLIM pin permits the cycle by cycle switch
current limit to be programmed with a single external resistor.
This feature offers major advantages which ultimately decrease
the component cost and P.C.B. real estate. First, it allows the
ADP3000 to use low value, low saturation current and physically small inductors. Additionally, it allows the ADP3000 to
use a physically small surface mount tantalum capacitor with a
typical ESR of 0.1 Ω to achieve an output ripple as low as 40
mV to 80 mV, as well as low input ripple.
As a rule of thumb, the current limit is usually set to approximately
3 to 5 times the full load current for boost applications and
about 1.5–3 times of the full load current in buck applications.
The delay through the current limiting circuit is approximately
0.3 µs. If the switch ON time is reduced to less than 1.7 µs,
accuracy of the current trip-point is reduced. Attempting to
program a switch ON time of 0.3 µs or less will produce
spurious responses in the switch ON time. However, the
ADP3000 will still provide a properly regulated output voltage.
PROGRAMMING THE GAIN BLOCK
The gain block of the ADP3000 can be used as a low battery
detector, error amplifier or linear post regulator. The gain block
consists of an op amp with PNP inputs and an open-collector
NPN output. The inverting input is internally connected to the
ADP3000’s 1.245 V reference, while the noninverting input is
available at the SET pin. The NPN output transistor will sink in
excess of 300 µA.
Figure 18 shows the gain block configured as a low battery
monitor. Resistors R1 and R2 should be set to high values to
reduce quiescent current, but not so high that bias current in
the SET input causes large errors. A value of 33 kΩ for R2 is a
good compromise. The value for R1 is then calculated from the
formula:
R1 =
where VLOBATT is the desired low battery trip point. Since the
gain block output is an open-collector NPN, a pull-up resistor
should be connected to the positive logic power supply.
5V
The internal structure of the ILIM circuit is shown in Figure 17.
Q1 is the ADP3000’s internal power switch, which is paralleled
by sense transistor Q2. The relative sizes of Q1 and Q2 are
scaled so that IQ2 is 0.5% of IQ1. Current flows to Q2 through
both an internal 80 Ω resistor and the RLIM resistor. The voltage
on these two resistors biases the base-emitter junction of the
oscillator-disable transistor, Q3. When the voltage across R1
and RLIM exceeds 0.6 V, Q3 turns on and terminates the output
pulse. If only the 80 Ω internal resistor is used (i.e. the ILIM pin
is connected directly to VIN), the maximum switch current will
be 1.5 A. Figure 8a gives values for lower current-limit values.
ADP3000
400kHz
OSC
TO
PROCESSOR
GND
RHYS
VLB = BATTERY TRIP POINT
Figure 18. Setting the Low Battery Detector Trip Point
80Ω
(INTERNAL)
IQ1
200
SW1
Q1
Q2
POWER
SWITCH
SW2
Figure 17. ADP3000 Current Limit Operation
REV. 0
AO
VLB – 1.245V
R1 =
37.7µA
Q3
DRIVER
RL
47kΩ
1.6MΩ
ILIM
ADP3000
1.245V
REF
VIN
SET
R2
33kΩ
VIN
R1
R1
VBATT
RLIM
(EXTERNAL)
VIN
V LOBATT – 1.245 V
1.245 V
R2
–7–
ADP3000
The circuit of Figure 18 may produce multiple pulses when
approaching the trip point due to noise coupled into the SET
input. To prevent multiple interrupts to the digital logic,
hysteresis can be added to the circuit (Figure 18). Resistor RHYS,
with a value of 1 MΩ to 10 MΩ, provides the hysteresis. The
addition of RHYS will change the trip point slightly, so the new
value for R1 will be:
R1=
Step-Down

P D =  I SW VCESAT

 1  
VO
1+ β   V – V

   IN
CE ( SAT )
  2 IO 

 + IQ VIN
  I SW 
[ ][ ]
where: ISW is ILIMIT in the case of current limit is programmed
externally or maximum inductor current in the case of
current limit is not programmed eternally.
V LOBATT –1.245V
1.245V  V L −1.245V 
 R2  −  R + R


  L
HYS 
VCE(SAT) = Check this value by applying ISW to Figure 8b.
1.2 V is typical value.
D = 0.75 (Typical Duty Ratio for a Single Switching
Cycle).
where VL is the logic power supply voltage, RL is the pull-up
resistor, and RHYS creates the hysteresis.
VO = Output Voltage.
POWER TRANSISTOR PROTECTION DIODE IN STEPDOWN CONFIGURATION
IO = Output Current.
When operating the ADP3000 in the step-down mode, the
output voltage is impressed across the internal power switch’s
emitter-base junction when the switch is off. In order to protect
the switch, a Schottky diode must be placed in a series with
SW2 when the output voltage is set to higher than 6 V. Figure
19 shows the proper way to place the protection diode, D2.
The selection of this diode is identical to the step-down commuting diode (see Diode Selection section for information).
IQ = 500 µA (Typical Shutdown Quiescent Current).
VIN = Input Voltage.
β = 30 (Typical Forced Beta).
The temperature rise can be calculated from:
∆T = P D × θ JA
where:
∆T = Temperature Rise.
PD = Device Power Dissipation.
VIN
C2
+
θJA = Thermal Resistance (Junction-to-Ambient).
D1, D2 = 1N5818 SCHOTTKY DIODES
R3
1
2
3
ILIM
VIN
SW1
As example, consider a boost converter with the following
specifications:
VOUT > 6V
FB 8
ADP3000
GND
5
D2
L1
VIN = 2 V, IO = 180 mA, VO = 3.3 V.
ISW = 0.8 A (Externally Programmed).
R2
SW2 4
D1
C1
+
R1
With Step-Up Power Dissipation Equation:


(2)(0.8) 
2   (4) 0.18 
P D = 0.82 × 1+
 0.75 1– 3.3   0.8  + 500 E − 6 2
30





[
Figure 19. Step-Down Model VOUT > 6.0 V
]
[
][ ]
= 185 mW
THERMAL CONSIDERATIONS
Using the SO-8 Package: ∆T = 185 mW (170°C/W) = 31.5°C.
Power dissipation internal to the ADP3000 can be approximated
with the following equations.
Using the N-8 Package: ∆T = 185 mW (120°C/W) = 22.2°C.
At a 70°C ambient, die temperature would be 101.45°C for
SO-8 package and 92.2°C for N-8 package. These junction
temperatures are well below the maximum recommended
junction temperature of 125°C.
Step-Up

V I   V   4I 
2
P D =  I SW R + IN SW  D 1– IN   O  + IQ V IN
β
  V O   I SW 

[ ][
]
Finally, the die temperature can be decreased up to 20% by
using a large metal ground plate as ground pickup for the
ADP3000.
where: ISW is ILIMIT in the case of current limit programmed
externally, or maximum inductor current in the case of
current limit not programmed externally.
R = 1 Ω (Typical RCE(SAT)).
D = 0.75 (Typical Duty Ratio for a Single Switching
Cycle).
VO = Output Voltage.
IO = Output Current.
VIN = Input Voltage.
IQ = 500 µA (Typical Shutdown Quiescent Current).
β = 30 (Typical Forced Beta)
–8–
REV. 0
ADP3000
Typical Application Circuits
L1
6.8µH
VIN
2V → 3.2V
+
C1
100µF
10V
1N5817
VIN
4.5V → 5.5V
VOUT
3.3V
180mA
120Ω
1
2
ILIM
VIN
L1
15µH
+
C1
100µF
10V
SW1 3
+
4
C2
100µF
10V
L1
6.8µH
VIN
C1
100µF
10V
GND
SW2
5
4
C1 +
100µF
10V
VOUT
5V
100mA
120Ω
1
2
ILIM
VIN
120Ω
1
2
ILIM
GND
SW2
5
4
ADP3000-ADJ
L1
6.8µH
VIN
L1 = SUMIDA CD43-100
C1, C2 = AVX TPS D107 M010R100
TYPICAL EFFICIENCY = 75%
VIN
VIN
10V → 13V
C1 +
33µF
20V
SW1 3
1
4
+
3
L1
10µH
5
C2
100µF
10V
L1 = SUMIDA CD43-100
C1 = AVX TPS D336 M020R0200
C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 77%
L1 = SUMIDA CD43-6R8
C1, C2 = AVX TPS D107 M010R100
TYPICAL EFFICIENCY = 80%
D1
IN5817
+
C2
100µF
10V
VOUT
5V
250mA
Figure 25. 10 V to 5 V/250 mA Step-Down Converter
Figure 22. 2.7 V to 5 V/150 mA Step-Up Converter
REV. 0
R1
110kΩ
GND SW2 4
SENSE 8
5
2
VIN SW1
SENSE 8
ADP3000-5V
ADP3000-5V
SW2
C2 +
100µF
10V
250Ω
ILIM
GND
D1
IN5817
VOUT
3V
100mA
Figure 24. 5 V to 3 V/100 mA Step-Down Converter
VOUT
5V
150mA
ILIM
R2
150kΩ
5
C2
100µF
10V
1N5817
120Ω
2
L1
10µH
GND SW2 4
+
Figure 21. 2 V to 5 V/100 mA Step-Up Converter
1
3
VIN SW1
FB 8
SW1 3
L1 = SUMIDA CD43-6R8
C1, C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 80%
C1
100µF
10V
C2
100µF
16V
VIN
SENSE 8
+
+
5V → 6V
1N5817
ADP3000-5V
2.7V → 4.5V
SW1 3
Figure 23. 4.5 V to 12 V/ 50 mA Step-Up Converter
Figure 20. 2 V to 3.3 V/180 mA Step-Up Converter
+
2
VIN
L1 = SUMIDA CD54-150
C1 = AVX TPS D107 M010R0100
C2 = AVX TPS E107 M016R0100
TYPICAL EFFICIENCY = 75%
L1 = SUMIDA CD43-6R8
C1, C2 = AVX TPS D107 M010R100
TYPICAL EFFICIENCY = 75%
2V → 3.2V
1
ILIM
SENSE 8
SENSE 8
SW2
5
VOUT
12V
50mA
124Ω
ADP3000-12V
ADP3000-3.3V
GND
1N5817
–9–
ADP3000
VIN
5V
C1 +
47µF
16V
240Ω
1
2
ILIM
VIN
3
SW1
SENSE 8
L1
15µH
ADP3000-5V
GND
SW2 4
C2 +
100µF
10V
5
D1
IN5817
VOUT
–5V
100mA
L1 = SUMIDA CD53-150
C1 = AVX TPS D476 M016R0150
C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 60%
Figure 26. 5 V to –5 V/100 mA Inverter
2.5V → 4.2V
(SUMIDA – CDRH62)
100kΩ
–
6.8µH
2N2907
100µF
10V
AVX-TPS
ILIM
IN5817
VIN
100kΩ
SET
1MΩ
90kΩ
1µF
6V
(MLC)
IN2
33nF
90kΩ
348kΩ
1%
+ 100µF
10V
– AVX-TPS
FB
AO
VO1
IN1
10kΩ
SW1
ADP3000
ADP3302AR1
SD
200kΩ
1%
GND SW2
GND
VO2
3V
100mA
1µF
6V
(MLC)
3V
100mA
Figure 27. 1 Cell LI-ION to 3 V/200 mA Converter with Shutdown at VIN ≤ 2.5 V
AT VIN ≤ 2.5V
80
% EFFICIENCY
+
330kΩ
120Ω
SHDN IQ = 500µA
IO = 50mA + 50mA
75
IO = 100mA + 100mA
70
65
VIN
2.6
3.0
3.4
3.8
4.2
(V)
Figure 28. Typical Efficiency of the Circuit of Figure 27
–10–
REV. 0
ADP3000
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Lead Plastic DIP
(N-8)
8-Lead SOIC
(SO-8)
0.1968 (5.00)
0.1890 (4.80)
0.430 (10.92)
0.348 (8.84)
8
5
0.1574 (4.00)
0.1497 (3.80)
0.280 (7.11)
0.240 (6.10)
1
4
PIN 1
0.210 (5.33)
MAX
0.060 (1.52)
0.015 (0.38)
0.160 (4.06)
0.115 (2.93)
0.022 (0.558) 0.100 0.070 (1.77)
0.014 (0.356) (2.54) 0.045 (1.15)
BSC
REV. 0
0.130
(3.30)
MIN
SEATING
PLANE
8
5
1
4
0.2440 (6.20)
0.2284 (5.80)
0.325 (8.25)
0.300 (7.62)
PIN 1
0.195 (4.95)
0.115 (2.93)
0.0098 (0.25)
0.0040 (0.10)
0.015 (0.381)
0.008 (0.204)
SEATING
PLANE
–11–
0.0688 (1.75)
0.0532 (1.35)
0.0500 0.0192 (0.49)
(1.27) 0.0138 (0.35)
BSC
0.0196 (0.50)
x 45°
0.0099 (0.25)
0.0098 (0.25)
0.0075 (0.19)
8°
0°
0.0500 (1.27)
0.0160 (0.41)
–12–
PRINTED IN U.S.A.
C2223–12–1/97
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