AD AD9548BCPZ-REEL7 Quad/octal input network clock generator/synchronizer Datasheet

Quad/Octal Input Network Clock
Generator/Synchronizer
AD9548
FEATURES
APPLICATIONS
Supports Stratum 2 stability in holdover mode
Supports reference switchover with phase build-out
Supports hitless reference switchover
Auto/manual holdover and reference switchover
4 pairs of reference input pins with each pair configurable as
a single differential input or as 2 independent singleended inputs
Input reference frequencies from 1 Hz to 750 MHz
Reference validation and frequency monitoring (1 ppm)
Programmable input reference switchover priority
30-bit programmable input reference divider
4 pairs of clock output pins with each pair configurable as a
single differential LVDS/LVPECL output or as 2 singleended CMOS outputs
Output frequencies up to 450 MHz
30-bit integer and 10-bit fractional programmable feedback
divider
Programmable digital loop filter covering loop bandwidths
from 0.001 Hz to 100 kHz
Optional low noise LC-VCO system clock multiplier
Optional crystal resonator for system clock input
On-chip EEPROM to store multiple power-up profiles
Software controlled power-down
88-lead LFCSP package
Network synchronization
Cleanup of reference clock jitter
GPS 1 pulse per second synchronization
SONET/SDH clocks up to OC-192, including FEC
Stratum 2 holdover, jitter cleanup, and phase transient
control
Stratum 3E and Stratum 3 reference clocks
Wireless base station controllers
Cable infrastructure
Data communications
GENERAL DESCRIPTION
The AD9548 provides synchronization for many systems,
including synchronous optical networks (SONET/SDH). The
AD9548 generates an output clock synchronized to one of up to
four differential or eight single-ended external input references.
The digital PLL allows for reduction of input time jitter or phase
noise associated with the external references. The AD9548
continuously generates a clean (low jitter), valid output clock
even when all references have failed by means of a digitally
controlled loop and holdover circuitry.
The AD9548 operates over an industrial temperature range of
−40°C to +85°C.
FUNCTIONAL BLOCK DIAGRAM
ANALOG
FILTER
STABLE
SOURCE
AD9548
CLOCK DISTRIBUTION
CLOCK
MULTIPLIER
CHANNEL 0
DIVIDER
CHANNEL 1
DIVIDER
DIGITAL
PLL
CHANNEL 2
DIVIDER
DAC
REFERENCE INPUTS
AND
MONITOR MUX
CHANNEL 3
DIVIDER
SYNC
EEPROM
STATUS AND
CONTROL PINS
08022-001
SERIAL CONTROL INTERFACE
(SPI or I2C)
Figure 1.
Rev. 0
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©2009 Analog Devices, Inc. All rights reserved.
AD9548
TABLE OF CONTENTS
Features .............................................................................................. 1
Digital PLL (DPLL) Core .......................................................... 32
Applications ....................................................................................... 1
Direct Digital Synthesizer ......................................................... 34
General Description ......................................................................... 1
Tuning Word Processing ........................................................... 35
Functional Block Diagram .............................................................. 1
Loop Control State Machine ..................................................... 36
Revision History ............................................................................... 3
System Clock Inputs................................................................... 37
Specifications..................................................................................... 4
SYSCLK PLL Multiplier............................................................. 38
Supply Voltage ............................................................................... 4
Clock Distribution ..................................................................... 39
Supply Current .............................................................................. 4
Status and Control .......................................................................... 44
Power Dissipation ......................................................................... 4
Multifunction Pins (M0 to M7) ............................................... 44
Logic Inputs (M7 to M0, RESET, TDI, TCLK, TMS) .............. 5
IRQ Pin ........................................................................................ 45
Logic Outputs (M7 to M0, IRQ, TDO) ..................................... 5
Watchdog Timer ......................................................................... 46
System Clock Inputs (SYSCLKP/SYSCLKN) ........................... 5
EEPROM ..................................................................................... 46
Distribution Clock Inputs (CLKINP/CLKINN) ...................... 6
Serial Control Port ......................................................................... 51
Reference Inputs (REFA/REFAA to REFD/REFDD) .............. 7
SPI/I2C Port Selection................................................................ 51
Reference Monitors ...................................................................... 7
SPI Serial Port Operation .......................................................... 51
Reference Switchover Specifications .......................................... 8
I2C Serial Port Operation .......................................................... 55
Distribution Clock Outputs (OUT0 to OUT3) ........................ 8
I/O Programming Registers .......................................................... 58
DAC Output Characteristics (DACOUTP/DACOUTN) ....... 9
Buffered/Active Registers .......................................................... 58
Time Duration of Digital Functions ........................................ 10
Autoclear Registers..................................................................... 58
Digital PLL .................................................................................. 10
Register Access Restrictions...................................................... 59
Digital PLL Lock Detection ...................................................... 10
Register Map ................................................................................... 60
Holdover Specifications ............................................................. 10
Register Map Bit Descriptions ...................................................... 70
Serial Port Specifications—SPI Mode ...................................... 11
Serial Port Specifications—I C Mode ...................................... 11
Serial Port Configuration (Register 0000 to
Register 0005) ............................................................................. 70
Jitter Generation ......................................................................... 12
System Clock (Register 0100 to Register 0108) ...................... 71
Absolute Maximum Ratings.......................................................... 14
General Configuration (Register 0200 to Register 0214) ..... 72
ESD Caution ................................................................................ 14
DPLL Configuration (Register 0300 to Register 031B)......... 75
Pin Configuration and Function Descriptions ........................... 15
Clock Distribution Output Configuration (Register 0400 to
Register 0419) ............................................................................. 77
2
Typical Performance Characteristics ........................................... 18
Input/Output Termination Recommendations .......................... 23
Reference Input Configuration (Register 0500 to Register
0507)............................................................................................. 81
Getting Started ................................................................................ 24
Profile Registers (Register 0600 to Register 07FF) ................ 83
Power-On Reset .......................................................................... 24
Operational Controls (Register 0A00 to Register 0A10) ...... 92
Initial Pin Programming ........................................................... 24
Status Readback (Register 0D00 to Register 0D19) ............... 97
Device Register Programming .................................................. 24
Nonvolatile Memory (EEPROM) Control (Register 0E00 to
Register 0E03) ........................................................................... 100
Theory of Operation ...................................................................... 26
Overview...................................................................................... 26
Reference Clock Inputs .............................................................. 27
EEPROM Storage Sequence (Register 0E10 to
Register 0E3F) ........................................................................... 101
Reference Monitors .................................................................... 27
Power Supply Partitions............................................................... 105
Reference Profiles ....................................................................... 28
3.3 V Supplies............................................................................ 105
Reference Switchover ................................................................. 30
1.8 V Supplies............................................................................ 105
Rev. 0 | Page 2 of 112
AD9548
Thermal Performance .................................................................. 106
Calculation of the γ Register Values .......................................109
Calculating Digital Filter Coefficients ....................................... 107
Calculation of the δ Register Values .......................................109
Calculation of the α Register Values ..................................... 108
Outline Dimensions ......................................................................110
Calculation of the β Register Values ...................................... 108
Ordering Guide .........................................................................110
REVISION HISTORY
5/09—Revision 0: Initial Version
Rev. 0 | Page 3 of 112
AD9548
SPECIFICATIONS
Minimum (min) and maximum (max) values apply for the full range of supply voltage and operating temperature variations. Typical (typ)
values apply for AVDD3 = DVDD_I/O = 3.3 V; AVDD = DVDD = 1.8 V; TA= 25°C; IDAC = 20 mA (full scale), unless otherwise noted.
SUPPLY VOLTAGE
Table 1.
Parameter
SUPPLY VOLTAGE
DVDD3
DVDD
AVDD3
3.3 V Supply (Typical)
1.8 V Supply (Alternative)
AVDD
Min
Typ
Max
Unit
Test Conditions/Comments
3.135
1.71
3.135
3.135
1.71
1.71
3.30
1.80
3.30
3.30
1.80
1.80
3.465
1.89
3.465
3.465
1.89
1.89
V
V
V
V
V
V
Pin 7, Pin 82
Pin 1, Pin 6, Pin 12, Pin 14, Pin 15, Pin 77, Pin 83, Pin 88
Pin 21, Pin 22, Pin 47, Pin 60, Pin 66, Pin 67, Pin 73
Pin 31, Pin 37, Pin 38, Pin 44
Pin 31, Pin 37, Pin 38, Pin 44
Pin 23, Pin 24, Pin 29, Pin 34, Pin 41, Pin 50, Pin 55, Pin 59,
Pin 63, Pin 70, Pin 74
SUPPLY CURRENT
The test conditions for the maximum (max) supply current are the same as the test conditions for the All Blocks Running parameter of Table 3.
The test conditions for the typical (typ) supply current are the same as the test conditions for the Typical Configuration parameter of Table 3.
Table 2.
Parameter
SUPPLY CURRENT
IDVDD3
IDVDD
IAVDD3
IAVDD3
3.3 V Supply (Typical)
1.8 V Supply (Alternative)
IAVDD
Min
Typ
Max
Unit
Test Conditions/Comments
1.5
190
52
3
215
75
mA
mA
mA
Pin 7, Pin 82
Pin 1, Pin 6, Pin 12, Pin 14, Pin 15, Pin 77, Pin 83, Pin 88
Pin 21, Pin 22, Pin 47, Pin 60, Pin 66, Pin 67, Pin 73
24
24
135
110
110
163
mA
mA
mA
Pin 31, Pin 37, Pin 38, Pin 44
Pin 31, Pin 37, Pin 38, Pin 44
Pin 23, Pin 24, Pin 29, Pin 34, Pin 41, Pin 50, Pin 55, Pin 59,
Pin 63, Pin 70, Pin 74
Typ
Max
Unit
Test Conditions/Comments
800
1100
mW
All Blocks Running
900
1400
mW
Full Power-Down
13
fSYSCLK = 20 MHz 1 ; fS = 1 GHz 2 ; fDDS = 122.88 MHz 3 ; one
LVPECL clock distribution output running at 122.88 MHz
(all others powered down); one input reference running
at 100 MHz (all others powered down)
fSYSCLK = 20 MHz1; fS = 1 GHz2; fDDS = 399 MHz3; all clock
distribution outputs configured as LVPECL at 399 MHz; all
input references configured as differential at 100 MHz;
fractional-N active (R = 10, S = 39, U = 9, V = 10)
Conditions = typical configuration; no external pull-up or
pull-down resistors
POWER DISSIPATION
Table 3.
Parameter
POWER DISSIPATION
Typical Configuration
Min
mW
Rev. 0 | Page 4 of 112
AD9548
Parameter
Incremental Power Dissipation
Min
Typ
SYSCLK PLL Off
Input Reference On
Differential
Single-Ended
Output Distribution Driver On
LVDS
LVPECL
CMOS
Max
Unit
−105
mW
7
13
mW
mW
70
75
65
mW
mW
mW
Test Conditions/Comments
Conditions = typical configuration; table values show the
change in power due to the indicated operation.
fSYSCLK = 1 GHz1; high frequency direct input mode.
A single 3.3 V CMOS output with a 10 pF load.
1
fSYSCLK is the frequency at the SYSCLKP and SYSCLKN pins.
fS is the sample rate of the output DAC.
3
fDDS is the output frequency of the DDS.
2
LOGIC INPUTS (M7 TO M0, RESET, TDI, TCLK, TMS)
Table 4.
Parameter
LOGIC INPUTS (M7 to M0, RESET, TDI, TCLK, TMS)
Input High Voltage (VIH)
Input Low Voltage (VIL)
Input Current (IINH, IINL)
Input Capacitance (CIN)
Min
Typ
Max
Unit
0.8
±200
V
V
μA
pF
Max
Unit
Test Conditions/Comments
0.4
V
V
1
1
μA
μA
IOH = 1 mA
IOL = 1 mA
Open-drain mode
VOH = 3.3 V
VOL =-0 V
2.1
±80
3
Test Conditions/Comments
LOGIC OUTPUTS (M7 TO M0, IRQ, TDO)
Table 5.
Parameter
LOGIC OUTPUTS (M7 to M0, IRQ, TDO)
Output High Voltage (VOH)
Output Low Voltage (VOL)
IRQ Leakage Current
Active Low Output Mode
Active High Output Mode
Min
Typ
2.7
SYSTEM CLOCK INPUTS (SYSCLKP/SYSCLKN)
Table 6.
Parameter
SYSTEM CLOCK PLL BYPASSED
Input Frequency Range
Minimum Input Slew Rate
Duty Cycle
Common-Mode Voltage
Differential Input Voltage Sensitivity
Input Capacitance
Input Resistance
Min
Typ
500
1000
40
Max
Unit
1000
MHz
V/μs
1.2
60
%
V
mV p-p
2
2.5
pF
kΩ
100
Rev. 0 | Page 5 of 112
Test Conditions/Comments
Minimum limit imposed for jitter
performance
Internally generated
Minimum voltage across pins required to
ensure switching between logic states;
the instantaneous voltage on either pin
must not exceed the supply rails; can
accommodate single-ended input by ac
grounding unused input
Single-ended, each pin
AD9548
Parameter
SYSTEM CLOCK PLL ENABLED
PLL Output Frequency Range
Phase-Frequency Detector (PFD) Rate
Frequency Multiplication Range
VCO Gain
High Frequency Path
Input Frequency Range
Minimum Input Slew Rate
Frequency Divider Range
Common-Mode Voltage
Differential Input Voltage Sensitivity
Input Capacitance
Input Resistance
Low Frequency Path
Input Frequency Range
Minimum Input Slew Rate
Common-Mode Voltage
Differential Input Voltage Sensitivity
Input Capacitance
Input Resistance
Crystal Resonator Path
Crystal Resonator Frequency Range
Maximum Crystal Motional Resistance
Min
Typ
900
6
Max
Unit
1000
150
255
MHz
MHz
Test Conditions/Comments
Assumes valid system clock and PFD rates
70
MHz/V
100.1
200
500
1
MHz
V/μs
8
1
V
mV p-p
3
2.5
pF
kΩ
100
3.5
50
100
MHz
V/μs
1.2
V
mV p-p
3
4
pF
kΩ
100
10
50
100
MHz
Ω
Minimum limit imposed for jitter
performance
Binary steps (M = 1, 2, 4, 8)
Internally generated
Minimum voltage across pins required to
ensure switching between logic states;
the instantaneous voltage on either pin
must not exceed the supply rails; can
accommodate single-ended input by ac
grounding unused input
Single-ended, each pin
Minimum limit imposed for jitter
performance
Internally generated
Minimum voltage across pins required to
ensure switching between logic states;
the instantaneous voltage on either pin
must not exceed the supply rails; can
accommodate single-ended input by ac
grounding unused input
Single-ended, each pin
Fundamental mode, AT cut
See the System Clock Inputs section for
recommendations
DISTRIBUTION CLOCK INPUTS (CLKINP/CLKINN)
Table 7.
Parameter
DISTRIBUTION CLOCK INPUTS (CLKINP/CLKINN)
Input Frequency Range
Minimum Slew Rate
Min
Typ
62.5
75
Max
Unit
500
MHz
V/μs
Common-Mode Voltage
Differential Input Voltage Sensitivity
100
mV
mV p-p
Differential Input Power Sensitivity
−15
dBm
Input Capacitance
Input Resistance
700
3
5
Rev. 0 | Page 6 of 112
pF
kΩ
Test Conditions/Comments
Minimum limit imposed for jitter
performance.
Internally generated.
Capacitive coupling required; can
accommodate single-ended input
by ac grounding unused input; the
instantaneous voltage on either pin
must not exceed the supply rails.
The same as voltage sensitivity but
specified as power into a 50 Ω load.
Each pin has a 2.5 kΩ internal dcbias resistance.
AD9548
REFERENCE INPUTS (REFA/REFAA TO REFD/REFDD)
Table 8.
Parameter
DIFFERENTIAL OPERATION
Frequency Range
Sinusoidal Input
LVPECL Input
LVDS Input
Minimum Input Slew Rate
Min
Typ
10
1
1
40
Max
Unit
750
750 × 106
750 × 106
MHz
Hz
Hz
V/μs
Common-Mode Input Voltage
Differential Input Voltage Sensitivity
2
±65
V
mV
Input Resistance
Input Capacitance
25
3
kΩ
pF
Minimum Pulse Width High
Minimum Pulse Width Low
SINGLE-ENDED OPERATION
Frequency Range (CMOS)
Minimum Input Slew Rate
620
620
Minimum limit imposed for jitter
performance
Internally generated
Minimum differential voltage across
pins required to ensure switching
between logic levels; the
instantaneous voltage on either pin
must not exceed the supply rails
ps
ps
250 ×106
1
40
Input Voltage High (VIH)
1.2 V to 1.5 V Threshold Setting
1.8 V to 2.5 V Threshold Setting
3.0 V to 3.3 V Threshold Setting
Input Voltage Low (VIL)
1.2 V to 1.5 V Threshold Setting
1.8 V to 2.5 V Threshold Setting
3.0 V to 3.3 V Threshold Setting
Input Resistance
Input Capacitance
Minimum Pulse Width High
Minimum Pulse Width Low
Test Conditions/Comments
0.9
1.2
1.9
Hz
V/μs
Minimum limit imposed for jitter
performance
V
V
V
0.27
0.5
1.0
V
V
V
kΩ
pF
ns
ns
45
3
1.5
1.5
REFERENCE MONITORS
Table 9.
Parameter
REFERENCE MONITORS
Reference Monitor
Loss of Reference Detection
Time
Frequency Out-of Range Limits
Validation Timer
Redetect Timer
1
Min
9.54 × 10−7
0.001
0.001
Typ
Max
Unit
Test Conditions/Comments
1.2
sec
0.1
65.535
65.535
Δf/fREF
sec
sec
Calculated using the nominal phase detector period
(NPDP = R/fREF) 1
Programmable (lower bound subject to quality of SYSCLK)
Programmable in 1 ms increments
Programmable in 1 ms increments
fREF is the frequency of the active reference; R is the frequency division factor determined by the R-divider.
Rev. 0 | Page 7 of 112
AD9548
REFERENCE SWITCHOVER SPECIFICATIONS
Table 10.
Parameter
REFERENCE SWITCHOVER SPECIFICATIONS
Maximum Output Phase Perturbation (Phase
Build-Out Switchover)
Maximum Time/Time Slope (Hitless
Switchover)
Min
Max
Unit
Test Conditions/Comments
40
200
ps
65,535
ns/sec
Assumes a jitter-free reference; satisfies
Telcordia GR-1244-CORE requirements
Minimum/maximum values are
programmable upper bounds; a minimum
value ensures <10% error; satisfies
Telcordia GR-1244-CORE requirements
315
Time Required to Switch to a New Reference
Hitless Switchover
Phase Build-Out Switchover
1
Typ
5
sec
3
sec
Calculated using the nominal phase
detector period (NPDP = R/fREF) 1
Calculated using the nominal phase
detector period (NPDP = R/fREF)1
fREF is the frequency of the active reference; R is the frequency division factor determined by the R-divider.
DISTRIBUTION CLOCK OUTPUTS (OUT0 TO OUT3)
Table 11.
Parameter
LVPECL MODE
Maximum Output Frequency
Rise/Fall Time (20% to 80%)
Duty Cycle
Differential Output Voltage Swing
Common-Mode Output Voltage
Min
Typ
725
180
45
630
AVDD3
− 1.5
770
AVDD3 − 1.3
Max
Unit
315
55
910
MHz
ps
%
mV
AVDD3 −
1.05
V
LVDS MODE
Maximum Output Frequency
Rise/Fall Time 1 (20% to 80%)
Duty Cycle
Differential Output Voltage Swing
Balanced, VOD
Short-Circuit Output Current
CMOS MODE
Maximum Output Frequency
3.3 V Supply
Strong Drive Strength Setting
Weak Drive Strength Setting
1.8 V Supply
100 Ω termination across output pins
Magnitude of voltage across pins; output
driver static
Output driver static
Using internal current setting resistor
(nominal 3.12 kΩ)
725
200
40
350
60
MHz
ps
%
247
454
mV
50
mV
1.375
50
V
mV
24
mA
Unbalanced, ΔVOD
Offset Voltage
Common-Mode, VOS
Common-Mode Difference, ΔVOS
Test Conditions/Comments
Using internal current setting resistor
1.125
13
100 Ω termination across the output pair
Voltage swing between output pins;
output driver static
Absolute difference between voltage
swing of normal pin and inverted pin;
output driver static
Output driver static
Voltage difference between pins; output
driver static
Output driver static
Weak drive option not supported for
operating the CMOS drivers using a 1.8 V
supply
10 pF load
250
25
150
MHz
MHz
MHz
Rev. 0 | Page 8 of 112
AD9548
Parameter
Rise/Fall Time1 (20% to 80%)
3.3 V Supply
Strong Drive Strength Setting
Weak Drive Strength Setting
1.8 V Supply
Duty Cycle
Output Voltage High (VOH)
AVDD3 = 3.3 V, IOH = 10 mA
AVDD3 = 3.3 V, IOH = 1 mA
AVDD3 = 1.8 V, IOH = 1 mA
Output Voltage Low (VOL)
Min
Max
Unit
0.5
8
1.5
2
14.5
2.5
60
ns
ns
ns
%
40
2.6
2.9
1.5
AVDD3 = 3.3 V, IOL = 10 mA
AVDD3 = 3.3 V, IOL = 1 mA
AVDD3 = 1.8 V, IOL = 1 mA
OUTPUT TIMING SKEW
Between LVPECL Outputs
Between LVDS Outputs
Between CMOS 3.3 V Outputs
Strong Drive Strength Setting
Weak Drive Strength Setting
Between CMOS 1.8 V Outputs
Between LVPECL Outputs and LVDS
Outputs
Between LVPECL Outputs and CMOS
Outputs
ZERO-DELAY TIMING SKEW
1
Typ
Test Conditions/Comments
10 pF load
10 pF load
Output driver static; strong drive strength
setting
V
V
V
Output driver static; strong drive strength
setting
0.3
0.1
0.1
V
V
V
14
13
125
138
ps
ps
23
24
40
14
240
ps
ps
ps
ps
140
19
ps
±5
ns
10 pF load
Rising edge only; any divide value
Rising edge only; any divide value
Weak drive not supported at 1.8 V
Output relative to active input reference;
output distribution synchronization to
active reference feature enabled; assumes
manual phase offset compensation of
deterministic latency
The listed values are for the slower edge (rise or fall).
DAC OUTPUT CHARACTERISTICS (DACOUTP/DACOUTN)
Table 12.
Parameter
DAC OUTPUT CHARACTERISTICS
(DACOUTP/DACOUTN)
Frequency Range
Output Offset Voltage
Voltage Compliance Range
Output Resistance
Min
62.5
VSS − 0.5
Output Capacitance
Full-Scale Output Current
Gain Error
Typ
0.5
50
Max
Unit
450
15
MHz
mV
VSS + 0.5
V
Ω
5
20
−12
pF
mA
+12
Rev. 0 | Page 9 of 112
% FS
Test Conditions/Comments
This is the single-ended voltage at
either DAC output pin (no external
load) when the internal DAC code
implies that no current is delivered
to that pin.
Single-ended, each pin has an
internal 50 Ω termination to VSS.
Programmable (8 mA to 31 mA; see
the DAC Output section).
AD9548
TIME DURATION OF DIGITAL FUNCTIONS
Table 13.
Parameter
TIME DURATION OF DIGITAL FUNCTIONS
EEPROM-to-Register Download Time
Min
Typ
Max
Unit
Test Conditions/Comments
25
ms
Register-to-EEPROM Upload Time
200
ms
Minimum Power-Down Exit Time
Maximum Time from Assertion of the RESET
pin to the M0 to M7 Pins Entering High
Impedance State
10.5
45
μs
ns
Using default EEPROM storage
sequence (see Register 0E10 to
Register 0E3F)
Using default EEPROM storage
sequence (see Register 0E10 to
Register 0E3F
Dependent on loop-filter bandwidth
DIGITAL PLL
Table 14.
Parameter
DIGITAL PLL
Phase-Frequency Detector (PFD)
Input Frequency Range
Loop Bandwidth
Phase Margin
Reference Input (R) Division Factor
Integer Feedback (S) Division Factor
Fractional Feedback Divide Ratio
Min
Typ
Max
Unit
Test Conditions/Comments
1
107
Hz
Maximum fPFD 1 : fS/100 2
0.001
105
Hz
30
1
8
0
89
230
230
0.999
Degrees
Programmable design parameter; maximum
fLOOP = fREF/(20R) 3
Programmable design parameter
1, 2, …, 1,073,741,824
8, 9, …, 1,073,741,824
Maximum value: 1022/1023.
1
fPFD is the frequency at the input to the phase-frequency detector.
fS is the sample rate of the output DAC.
3
fREF is the frequency of the active reference; R is the frequency division factor determined by the R-divider.
2
DIGITAL PLL LOCK DETECTION
Table 15.
Parameter
PHASE LOCK DETECTOR
Threshold Programming Range
Threshold Resolution
FREQUENCY LOCK DETECTOR
Threshold Programming Range
Threshold Resolution
Min
Typ
0.001
Max
Unit
65.5
ns
ps
16,700
ns
ps
Reference-to-feedback period difference
Max
Unit
Test Conditions/Comments
ppm
Excludes frequency drift of SYSCLK source;
excludes frequency drift of input reference prior
to entering holdover
1
0.001
1
Test Conditions/Comments
HOLDOVER SPECIFICATIONS
Table 16.
Parameter
HOLDOVER SPECIFICATIONS
Frequency Accuracy
Min
Typ
<0.01
Rev. 0 | Page 10 of 112
AD9548
SERIAL PORT SPECIFICATIONS—SPI MODE
Table 17.
Parameter
CS
Input Logic 1 Voltage
Input Logic 0 Voltage
Input Logic 1 Current
Input Logic 0 Current
Input Capacitance
SCLK
Input Logic 1 Voltage
Input Logic 0 Voltage
Input Logic 1 Current
Input Logic 0 Current
Input Capacitance
SDIO
As an Input
Input Logic 1 Voltage
Input Logic 0 Voltage
Input Logic 1 Current
Input Logic 0 Current
Input Capacitance
As an Output
Output Logic 1 Voltage
Output Logic 0 Voltage
SDO
Output Logic 1 Voltage
Output Logic 0 Voltage
TIMING
SCLK
Clock Rate, 1/tCLK
Pulse Width High, tHI
Pulse Width Low, tLO
SDIO to SCLK Setup, tDS
SCLK to SDIO Hold, tDH
SCLK to Valid SDIO and SDO, tDV
CS to SCLK Setup (tS)
CS to SCLK Hold (tC)
CS Minimum Pulse Width High
Min
Typ
Max
Unit
2.0
0.8
30
110
2
V
V
μA
μA
pF
2.0
0.8
1
1
2
V
V
μA
μA
pF
2.0
0.8
1
1
2
V
V
μA
μA
pF
Test Conditions/Comments
Internal 30 kΩ pull-up resistor
Internal 30 kΩ pull-down resistor
2.7
0.4
V
V
1 mA load current
1 mA load current
0.4
V
V
1 mA load current
1 mA load current
2.7
40
MHz
ns
ns
ns
ns
ns
ns
ns
ns
8
12
3
0
14
10
0
6
SERIAL PORT SPECIFICATIONS—I2C MODE
Table 18.
Parameter
SDA, SCL (AS INPUT)
Input Logic 1 Voltage
Input Logic 0 Voltage
Input Current
Hysteresis of Schmitt Trigger Inputs
Pulse Width of Spikes That Must Be
Suppressed by the Input Filter, tSP
Min
Typ
Max
Unit
0.3 × DVDD3
+10
V
V
μA
50
ns
0.7 × DVDD3
−10
0.015 × DVDD3
Rev. 0 | Page 11 of 112
Test Conditions/Comments
No internal pull-up/down resistor.
For VIN = 10% to 90% DVDD3
AD9548
Parameter
SDA (AS OUTPUT)
Output Logic 0 Voltage
Output Fall Time from VIHmin to VILmax
TIMING
SCL Clock Rate
Bus-Free Time Between a Stop and Start
Condition, tBUF
Repeated Start Condition Setup Time,
tSU; STA
Repeated Hold Time Start Condition, tHD; STA
Stop Condition Setup Time, tSU; STO
Low Period of the SCL Clock, tLO
High Period of the SCL Clock, tHI
SCL/SDA Rise Time, tR
SCL/SDA Fall Time, tF
Data Setup Time, tSU; DAT
Data Hold Time, tHD; DAT
Capacitive Load for Each Bus Line, Cb1
1
Min
Typ
Max
Unit
Test Conditions/Comments
0.4
250
V
ns
IO = 3 mA.
10 pF ≤ Cb ≤ 400 pF.
400
1.3
kHz
μs
0.6
μs
0.6
μs
0.6
1.3
0.6
20 + 0.1 Cb1
20 + 0.1 Cb1
100
100
μs
μs
μs
ns
ns
ns
ns
pF
20 + 0.1 Cb 1
300
300
400
After this period, the first clock
pulse is generated.
Cb is the capacitance (pF) of a single bus line.
JITTER GENERATION
Table 19.
Parameter
JITTER GENERATION
fREF = 1 Hz 1 ; fDDS = 122.88 MHz 2 ; fLOOP = 0.01 Hz 3
Min
Typ
Max
Unit
Bandwidth: 100 Hz to 61 MHz
Bandwidth: 5 kHz to 20 MHz
Bandwidth: 20 kHz to 80 MHz
Bandwidth: 50 kHz to 80 MHz
Bandwidth: 4 MHz to 80 MHz
fREF = 8 kHz1; fDDS = 155.52 MHz2; fLOOP = 100 Hz3
0.81
0.73
0.79
0.78
0.37
ps rms
ps rms
ps rms
ps rms
ps rms
Bandwidth: 100 Hz to 77 MHz
Bandwidth: 5 kHz to 20 MHz
Bandwidth: 20 kHz to 80 MHz
Bandwidth: 50 kHz to 80 MHz
Bandwidth: 4 MHz to 80 MHz
fREF = 19.44 MHz1; fDDS = 155.52 MHz2; fLOOP = 1 kHz3
0.71
0.34
0.43
0.43
0.31
ps rms
ps rms
ps rms
ps rms
ps rms
1.05
0.34
0.43
0.43
0.32
ps rms
ps rms
ps rms
ps rms
ps rms
Bandwidth: 100 Hz to 77 MHz
Bandwidth: 5 kHz to 20 MHz
Bandwidth: 20 kHz to 80 MHz
Bandwidth: 50 kHz to 80 MHz
Bandwidth: 4 MHz to 80 MHz
Rev. 0 | Page 12 of 112
Test Conditions/Comments
fSYSCLK = 20 MHz 4 OCXO; fS = 1 GHz 5 ; Qdivider = 1; default SysClk PLL charge pump
current; results valid for LVPECL, LVDS, and
CMOS output logic types
Random jitter
Random jitter
Random jitter
Random jitter
Random jitter
fSYSCLK = 50 MHz4 crystal;
fS = 1 GHz5; Q-divider = 1; default SYSCLK
PLL charge pump current; results valid for
LVPECL, LVDS, and CMOS output logic types
Random jitter
Random jitter
Random jitter
Random jitter
Random jitter
fSYSCLK = 50 MHz4 crystal;
fS = 1 GHz5; Q-divider = 1; default SYSCLK
PLL charge pump current; results valid for
LVPECL, LVDS, and CMOS output logic types
Random jitter
Random jitter
Random jitter
Random jitter
Random jitter
AD9548
Parameter
fREF = 19.44 Hz1; fDDS = 311.04 MHz2; fLOOP = 1 kHz3
Bandwidth: 100 Hz to 100 MHz
Bandwidth: 5 kHz to 20 MHz
Bandwidth: 20 kHz to 80 MHz
Bandwidth: 50 kHz to 80 MHz
Bandwidth: 4 MHz to 80 MHz
Min
Typ
Max
0.67
0.31
0.33
0.33
0.16
1
fREF is the frequency of the active reference.
fDDS is the output frequency of the DDS.
3
fLOOP is the DPLL digital loop filter bandwidth.
4
fSYSCLK is the frequency at the SYSCLKP and SYSCLKN pins.
5
fS is the sample rate of the output DAC.
2
Rev. 0 | Page 13 of 112
Unit
ps rms
ps rms
ps rms
ps rms
ps rms
Test Conditions/Comments
fSYSCLK = 50 MHz4 crystal;
fS = 1 GHz5; Q-divider = 1; default SYSCLK
PLL charge pump current; results valid for
LVPECL, LVDS, and CMOS output logic types
Random jitter
Random jitter
Random jitter
Random jitter
Random jitter
AD9548
ABSOLUTE MAXIMUM RATINGS
Table 20.
Parameter
Analog Supply Voltage (AVDD)
Digital Supply Voltage (DVDD)
Digital I/O Supply Voltage (DVDD3)
DAC Supply Voltage (AVDD3)
Maximum Digital Input Voltage
Storage Temperature Range
Operating Temperature Range
Lead Temperature
(Soldering 10 sec)
Junction Temperature
Rating
2V
2V
3.6 V
3.6 V
−0.5 V to DVDD3 + 0.5 V
−65°C to +150°C
−40°C to +85°C
300°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
ESD CAUTION
150°C
Rev. 0 | Page 14 of 112
AD9548
88
87
86
85
84
83
82
81
80
79
78
77
76
75
74
73
72
71
70
69
68
67
DVDD
M7
M6
M5
M4
DVDD
DVDD3
M3
M2
M1
M0
DVDD
IRQ
NC
AVDD
AVDD3
REFDD
REFD
AVDD
REFCC
REFC
AVDD3
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
AD9548
TOP VIEW
(Not to Scale)
88-LEAD LFCSP
12mm × 12mm
0.5mm PITCH
66
65
64
63
62
61
60
59
58
57
56
55
54
53
52
51
50
49
48
47
46
45
AVDD3
REFBB
REFB
AVDD
REFAA
REFA
AVDD3
AVDD
TDC_VRT
TDC_VRB
NC
AVDD
VSS
SYSCLKP
SYSCLKN
VSS
AVDD
SYSCLK_LF
SYSCLK_VREG
AVDD3
NC
NC
NOTES
1. NC = NO CONNECT.
2. THE EXPOSED PAD MUST BE CONNECTED TO GROUND (VSS).
08022-002
AVDD
AVDD
VSS
CLKINN
CLKINP
VSS
AVDD
OUT_RSET
AVDD3
OUT0P
OUT0N
AVDD
OUT1P
OUT1N
AVDD3
AVDD3
OUT2P
OUT2N
AVDD
OUT3P
OUT3N
AVDD3
23
24
25
26
27
28
29
30
31
32
33
34
35
36
37
38
39
40
41
42
43
44
DVDD
SCLK/SCL
SDIO
SDO
CS/SDA
DVDD
DVDD3
TCLK
TMS
TDO
TDI
DVDD
RESET
DVDD
DVDD
NC
VSS
DACOUTP
DACOUTN
VSS
AVDD3
AVDD3
Figure 2. 88-Lead LFCSP Pin Configuration
Table 21. Pin Function Descriptions
Pin No.
1, 6, 12, 77,
83, 88
2
3
Mnemonic
DVDD
Input/
Output
I
Pin Type
Power
Description
1.8 V Digital Supply.
SCLK/SCL
SDIO
I
I/O
3.3 V CMOS
3.3 V CMOS
4
SDO
O
3.3 V CMOS
5
CS/SDA
I
3.3 V CMOS
7, 82
8
9
10
11
13
DVDD3
TCLK
TMS
TDO
TDI
RESET
I
I
I
O
I
I
Power
14, 15
16, 45, 46
17, 20, 25,
28, 51, 54
18
DVDD
NC
VSS
I
Power
O
Ground
Serial Programming Clock. Data clock for serial programming.
Serial Data Input/Output. When the device is in 4-wire mode, data is written via
this pin. In 3-wire mode, both data reads and writes occur on this pin. There is no
internal pull-up/pull-down resistor on this pin.
Serial Data Output. Use this pin to read data in 4-wire mode (high impedance in
3-wire mode). There is no internal pull-up/pull-down resistor on this pin.
Chip Select (SPI). Active low. When programming a device, this pin must be held
low. In systems where more than one AD9548 is present, this pin enables
individual programming of each AD9548 (in I2C® mode, this is a serial data pin).
This pin has an internal 10 kΩ pull-up resistor but only in SPI mode.
3.3 V I/O Digital Supply.
JTAG Clock. Internal pull-down resistor; no connection if JTAG is not used.
JTAG Mode. Internal pull-up resistor; no connection if JTAG is not used.
JTAG Output. No connection if JTAG is not used
JTAG Input. Internal pull-up resistor; no connection if JTAG is not used.
Chip Reset. When this active high pin is asserted, the chip goes into reset.
This pin has an internal 50 kΩ pull-down resistor.
1.8 V DAC Decode Digital Supply. Keep isolated from the 1.8 V core digital supply.
No Connect.
Analog Ground. Connect to ground.
DACOUTP
O
19
DACOUTN
O
21, 22
AVDD3
I
Differential
output
Differential
output
Power
3.3 V CMOS
DAC Output. DACOUTP contains an internal 50 Ω pull-down resistor.
Complementary DAC Output. DACOUTN contains an internal 50 Ω pull-down
resistor.
3.3 V Analog (DAC) Power Supply.
Rev. 0 | Page 15 of 112
AD9548
Pin No.
23, 24
26
Mnemonic
AVDD
CLKINN
Input/
Output
I
I
27
CLKINP
I
29
30
AVDD
OUT_RSET
I
O
31, 37, 38,
44
AVDD3
I
32
OUT0P
O
LVPECL,
LVDS, or
CMOS
33
OUT0N
O
34, 41
35
AVDD
OUT1P
I
O
LVPECL,
LVDS, or
CMOS
Power
LVPECL,
LVDS, or
CMOS
36
OUT1N
O
39
OUT2P
O
40
OUT2N
O
42
OUT3P
O
43
OUT3N
O
47
48
AVDD3
SYSCLK_VREG
I
I
49
SYSCLK_LF
O
50, 55
52
AVDD
SYSCLKN
I
I
Pin Type
Power
Differential
input
Differential
input
Power
Current set
resistor
Power
LVPECL,
LVDS, or
CMOS
LVPECL,
LVDS, or
CMOS
LVPECL,
LVDS, or
CMOS
LVPECL,
LVDS, or
CMOS
LVPECL,
LVDS, or
CMOS
Power
Power
Differential
input
Description
1.8 V Analog (DAC) Power Supply.
Clock Distribution Input. In standard operating mode, this pin is connected to the
filtered DACOUTN output. This internally biased input is typically ac-coupled and,
when configured as such, can accept any differential signal whose single-ended
swing is at least 400 mV.
Clock Distribution Input. In standard operating mode, this pin is connected to the
filtered DACOUTP output
1.8 V Analog (Input Receiver) Power Supply.
Connect an optional 3.12 kΩ resistor from this pin to ground (see the Output
Current Control with an External Resistor section).
Analog Supply for Output Driver. These pins are normally 3.3 V but can be 1.8 V.
Pin 31 powers Out0x. Pin 37 powers OUT1x. Pin 38 powers OUT2x. Pin 44 powers
OUT3x. Apply power to these pins even if the corresponding outputs (OUT0P/
OUT0N, OUT1P/ OUT1N, OUT2P/ OUT2N, and OUT3P/ OUT3N) are not used. See
the Power Supply Partitions section.
Output 0. This output can be configured as LVPECL, LVDS, or single-ended CMOS.
LVPECL and LVDS operation require a 3.3 V output driver power supply. CMOS
operation can be either 1.8 V or 3.3 V, depending on the output driver power
supply.
Complementary Output 0. This output can be configured as LVPECL, LVDS, or
single-ended CMOS.
1.8 V Analog (Output Divider) Power Supply.
Output 1. This output can be configured as LVPECL, LVDS, or single-ended CMOS.
LVPECL and LVDS operation require a 3.3 V output driver power supply. CMOS
operation can be either 1.8 V or 3.3 V, depending on the output driver power
supply.
Complementary Output 1. This output can be configured as LVPECL, LVDS, or
single-ended CMOS.
Output 2. This output can be configured as LVPECL, LVDS, or single-ended CMOS.
LVPECL and LVDS operation require a 3.3 V output driver power supply. CMOS
operation can be either 1.8 V or 3.3 V, depending on the output driver power
supply.
Complementary Output 2. This output can be configured as LVPECL, LVDS, or
single-ended CMOS.
Output 3. This output can be configured as LVPECL, LVDS, or single-ended CMOS.
LVPECL and LVDS operation require a 3.3 V output driver power supply. CMOS
operation can be either 1.8 V or 3.3 V, depending on the output driver power
supply.
Complementary Output 3. This output can be configured as LVPECL, LVDS, or
single-ended CMOS.
3.3 V Analog (System Clock) Power Supply.
System Clock Loop Filter Voltage Regulator. Connect a 0.1 μF capacitor from this
pin to ground. This pin is also the ac ground reference for the integrated SYSCLK
PLL multiplier’s external loop filter (see the SYSCLK PLL Multiplier section).
System Clock Multiplier Loop Filter. When using the frequency multiplier to drive
the system clock, an external loop filter can be attached to this pin.
1.8 V Analog (System Clock) Power Supply.
Complementary System Clock Input. Complementary signal to SYSCLKP. SYSCLKN
contains internal dc biasing and should be ac-coupled with a
0.01 μF capacitor, except when using a crystal, in which case connect the crystal
across SYSCLKP and SYSCLKN.
Rev. 0 | Page 16 of 112
AD9548
Input/
Output
I
Pin No.
53
Mnemonic
SYSCLKP
56, 75
59
57, 58
NC
AVDD
TDC_VRB,
TDC_VRT
AVDD3
I
I
I
Power
I
Power
3.3 V Analog (Reference Input) Power Supply.
REFA
I
Differential
input
62
REFAA
I
63, 70, 74
64
AVDD
REFB
I
I
Differential
input
Power
Differential
input
65
REFBB
I
68
REFC
I
69
REFCC
I
71
REFD
I
72
REFDD
I
76
78, 79, 80,
81, 84, 85,
86, 87
EP
IRQ
M0, M1, M2,
M3, M4, M5,
M6, M7
VSS
O
I/O
Reference A Input. This internally biased input is typically ac-coupled and, when
configured as such, can accept any differential signal with single-ended swing up
to 3.3 V. If dc-coupled, input can be LVPECL, CMOS, or LVDS.
Complementary Reference A Input. Complementary signal to the input provided
on Pin 61. The user can configure this pin as a separate single-ended input.
1.8 V Analog (Reference Input) Power Supply.
Reference B Input. This internally biased input is typically ac-coupled and, when
configured as such, can accept any differential signal with single-ended swing up
to 3.3 V. If dc-coupled, input can be LVPECL, CMOS, or LVDS.
Complementary Reference B Input. Complementary signal to the input provided
on Pin 64. The user can configure this pin as a separate single-ended input.
Reference C Input. This internally biased input is typically ac-coupled and, when
configured as such, can accept any differential signal with single-ended swing up
to 3.3 V. If dc-coupled, input can be LVPECL, CMOS, or LVDS.
Complementary Reference C Input. Complementary signal to the input provided
on Pin 68. The user can configure this pin as a separate single-ended input.
Reference D Input. This internally biased input is typically ac-coupled and, when
configured as such, can accept any differential signal with single-ended swing up
to 3.3 V. If dc-coupled, input can be LVPECL, CMOS, or LVDS.
Complementary Reference D Input. Complementary signal to the input provided
on Pin 71. The user can configure this pin as a separate single-ended input.
Interrupt Request Line.
Configurable I/O Pins. These pins are configured under program control.
60, 66, 67,
73
61
O
Pin Type
Differential
input
Differential
input
Differential
input
Differential
input
Differential
input
Differential
input
Logic
3.3 V CMOS
Exposed
pad
Description
System Clock Input. SYSCLKP contains internal dc biasing and should be accoupled with a 0.01 μF capacitor, except when using a crystal, in which case
connect the crystal across SYSCLKP and SYSCLKN. Single-ended 1.8 V CMOS is
also an option but can introduce a spur if the duty cycle is not 50%. When using
SYSCLKP as a single-ended input, connect a 0.01 μF capacitor from SYSCLKN to
ground.
No Connection. These pins should be left floating.
1.8 V Analog Power Supply.
Use capacitive decoupling on these pins (see Figure 38).
The exposed pad must be connected to ground (VSS).
Rev. 0 | Page 17 of 112
AD9548
TYPICAL PERFORMANCE CHARACTERISTICS
fR = input reference clock frequency; fO = clock frequency; fSYS = SYSCLK input frequency; fS = internal system clock frequency; LBW =
DPLL loop bandwidth; PLL off = SYSCLK PLL bypassed; PLL on = SYSCLK PLL enabled; ICP = SYSCLK PLL charge pump current; LF =
SYSCLK PLL loop filter. AVDD, AVDD3, and DVDD at nominal supply voltage, fS = 1 GHz, ICP = automatic mode, LF = internal, unless
otherwise noted.
–70
–70
INTEGRATED RMS JITTER (PHASE NOISE):
5kHz TO 20MHz: 173fs (–75.4dBc)
20kHz TO 80MHz: 315fs (–70.2dBc) (EXTRAPOLATED)
–80
–100
–110
–120
–130
–100
–110
–120
–130
–140
–140
–150
–150
–160
100
1k
10k
100k
1M
10M
100M
FREQUENCY OFFSET (Hz)
–160
100
1k
Figure 3. Additive Phase Noise (Output Driver = LVPECL),
fR = 19.44 MHz, fO = 155.52 MHz,
LBW = 1 kHz, fSYS = 1 GHz, PLL Off
100k
1M
10M
100M
Figure 5. Additive Phase Noise (Output Driver = LVPECL),
fR = 19.44 MHz, fO = 311.04 MHz,
LBW = 1 kHz, fSYS = 1 GHz, PLL Off
–70
–70
INTEGRATED RMS JITTER (PHASE NOISE):
5kHz TO 20MHz: 333fs (–69.8dBc)
20kHz TO 80MHz: 430fs (–67.6dBc) (EXTRAPOLATED)
–80
10k
FREQUENCY OFFSET (Hz)
08022-066
PHASE NOISE (dBc/Hz)
–90
08022-068
INTEGRATED RMS JITTER (PHASE NOISE):
5kHz TO 20MHz: 310fs (–64.4dBc)
20kHz TO 80MHz: 330fs (–63.9dBc)
–80
–90
PHASE NOISE (dBc/Hz)
–90
–100
–110
–120
–130
–100
–110
–120
–130
–140
–150
–150
–160
100
1k
10k
100k
1M
10M
100M
FREQUENCY OFFSET (Hz)
08022-056
–140
–160
100
1k
10k
100k
1M
10M
100M
FREQUENCY OFFSET (Hz)
Figure 6. Additive Phase Noise (Output Driver = LVPECL),
fR = 19.44 MHz, fO = 311.04 MHz,
LBW = 1 kHz, fSYS = 50 MHz (Crystal), PLL On
Figure 4. Additive Phase Noise (Output Driver = LVPECL),
fR = 19.44 MHz, fO = 155.52 MHz,
LBW = 1 kHz, fSYS = 50 MHz (Crystal), PLL On
Rev. 0 | Page 18 of 112
08022-067
PHASE NOISE (dBc/Hz)
–90
PHASE NOISE (dBc/Hz)
INTEGRATED RMS JITTER (PHASE NOISE):
5kHz TO 20MHz: 103fs (–74.0dBc)
20kHz TO 80MHz: 160fs (–70.1dBc)
–80
AD9548
–70
–70
INTEGRATED RMS JITTER (PHASE NOISE):
5kHz TO 20MHz: 361fs (–69.0dBc)
20kHz TO 80MHz: 441fs (–67.3dBc) (EXTRAPOLATED)
–80
–80
50MHz CRYSTAL
–100
–110
–120
–130
–130
–140
–150
10k
100k
1M
10M
100M
FREQUENCY OFFSET (Hz)
Figure 7. Additive Phase Noise (Output Driver = LVPECL),
fR = 19.44 MHz, fO = 155.52 MHz,
LBW = 1 kHz, fSYS = 50 MHz, PLL On
–160
100
ROHDE & SCHWARZ
SMA100 (1GHz)
1k
10k
100k
1M
10M
100M
FREQUENCY (Hz)
Figure 10. Additive Phase Noise Comparison of SYSCLK Input Options
(Output Driver = LVPECL),
fR = 19.44 MHz, fO = 311.04 MHz, LBW = 1 kHz
–70
–70
INTEGRATED RMS JITTER (PHASE NOISE):
5kHz TO 10MHz: 717fs (–65.1dBc)
12kHz TO 20MHz: 725fs (–65.0dBc)
20kHz TO 80MHz: 790fs (–64.3dBc)
–80
–80
–90
INTEGRATED RMS JITTER (PHASE NOISE):
5kHz TO 20MHz: 356fs (–69.2dBc)
20kHz TO 80MHz: 435fs (–67.4dBc) (EXTRAPOLATED)
–100
–110
–120
–130
–100
–110
–120
–130
–140
–140
–150
–150
–160
10
100
1k
10k
100k
1M
10M
100M
FREQUENCY OFFSET (Hz)
–160
100
1k
10k
100k
1M
10M
100M
FREQUENCY OFFSET (Hz)
Figure 8. Additive Phase Noise (Output Driver = LVPECL),
fR = 1 Hz, fO = 122.88 MHz,
LBW = 0.05 Hz, fSYS = 20 MHz (OCXO), PLL On
08022-054
PHASE NOISE (dBc/Hz)
–90
08022-044
Figure 11. Additive Phase Noise (Output Driver = LVPECL),
fR = 1 Hz, fO = 155.52 MHz,
LBW = 0.05 Hz, fSYS = 50 MHz, PLL On
–70
–70
INTEGRATED RMS JITTER (PHASE NOISE):
5kHz TO 20MHz: 336fs (–69.7dBc)
20kHz TO 80MHz: 425fs (–67.6dBc) (EXTRAPOLATED)
–80
–80
–90
INTEGRATED RMS JITTER (PHASE NOISE):
5kHz TO 20MHz: 245fs (–72.4dBc)
20kHz TO 80MHz: 300fs (–64.3dBc) (EXTRAPOLATED)
PHASE NOISE (dBc/Hz)
–90
–100
–110
–120
–130
–100
–110
–120
–130
–140
–150
–150
–160
100
1k
10k
100k
1M
10M
100M
FREQUENCY OFFSET (Hz)
08022-052
–140
Figure 9. Additive Phase Noise (Output Driver = LVPECL),
fR = 8 kHz, fO = 155.52 MHz,
LBW = 100 Hz, fSYS = 50 MHz (Crystal), PLL On
–160
100
1k
10k
100k
1M
10M
100M
FREQUENCY OFFSET (Hz)
Figure 12. Additive Phase Noise (Output Driver = LVPECL) ,
fR = 19.44 MHz, fO = 155.52 MHz,
LBW = 1 kHz, fSYS = 50 MHz (Crystal), PLL On with
2x Frequency Multiplier, ICP = 375 μA, LF = External (350 kHz)
Rev. 0 | Page 19 of 112
08022-051
PHASE NOISE (dBc/Hz)
–120
–150
1k
ROHDE & SCHWARZ
SMA100 (50MHz)
–110
–140
–160
100
PHASE NOISE (dBc/Hz)
–100
08022-058
PHASE NOISE (dBc/Hz)
–90
08022-069
PHASE NOISE (dBc/Hz)
–90
AD9548
–90
10
–100
0
–110
–10
CLOSED-LOOP GAIN (dB)
–120
–130
ROHDE & SCHWARZ
SMA100 (1GHz)
–140
20MHz OCXO
–150
–20
–30
–40
–50
–60
–160
ROHDE & SCHWARZ
SMA100 (50MHz)
1k
10k
100k
1M
10M
FREQUENCY OFFSET (Hz)
–70
10
08022-053
–170
100
100
1k
10k
Figure 16. Jitter Transfer Bandwidth, Output Driver = LVPECL,
fR = 19.44 MHz, fO = 155.52 MHz,
LBW = 100 Hz (Phase Margin = 88°), fSYS = 1 GHz, PLL Off
Figure 13. Phase Noise of SYSCLK Input Sources
2.0
1.0
5pF LOAD
0.8
AMPLITUDE (V)
LVPECL
AMPLITUDE (V)
100k
FREQUENCY OFFSET (Hz)
08022-047
PHASE NOISE (dBc/Hz)
CLOSED-LOOP PEAKING: 0.04dB
0.6
0.4
LVDS
1.5
20pF LOAD
1.0
10pF LOAD
0
100
200
300
400
500
600
700
FREQUENCY (MHz)
0.5
08022-049
0
0
50
Figure 14. Amplitude vs. Toggle Rate,
LVPECL and LVDS
150
200
250
Figure 17. Amplitude vs. Toggle Rate,
1.8 V CMOS
4.0
4.0
3.5
3.5
10pF LOAD
5pF LOAD
AMPLITUDE (V)
3.0
2.5
20pF LOAD
2.0
1.5
3.0
10pF LOAD
2.5
2.0
1.0
0
100
200
300
400
FREQUENCY (MHz)
500
1.0
0
10
20
30
40
FREQUENCY (MHz)
Figure 18. Amplitude vs. Toggle Rate,
3.3 V CMOS (Weak Mode)
Figure 15. Amplitude vs. Toggle Rate,
3.3 V CMOS (Strong Mode)
Rev. 0 | Page 20 of 112
50
08022-063
1.5
08022-055
AMPLITUDE (V)
100
FREQUENCY (MHz)
08022-062
0.2
AD9548
40
140
130
20pF LOAD
35
120
LVPECL
10pF LOAD
POWER (mW)
POWER (mW)
110
100
90
80
5pF LOAD
30
25
LVDS
70
20
0
100
200
300
400
500
FREQUENCY (MHz)
15
08022-064
50
0
150
200
Figure 22. Power Consumption vs. Frequency,
1.8 V CMOS
160
34
140
32
120
30
10pF LOAD
5pF LOAD
10pF LOAD
80
28
20pF LOAD
60
24
40
22
20
0
50
100
150
200
250
300
350
FREQUENCY (MHz)
5pF LOAD
26
20
10
15
20
25
30
35
40
08022-059
100
5
08022-048
POWER (mW)
20pF LOAD
08022-060
POWER (mW)
100
FREQUENCY (MHz)
Figure 19. Power Consumption vs. Frequency,
LVPECL and LVDS
(Single Channel)
FREQUENCY (MHz)
Figure 23. Power Consumption vs. Frequency,
3.3 V CMOS (Weak Mode)
Figure 20. Power Consumption vs. Frequency,
3.3 V CMOS (Strong Mode)
0.5
0.8
0.4
0.6
0.3
DIFFERENTIAL AMPLITUDE (V)
1.0
0.4
0.2
0
–0.2
–0.4
–0.6
0.2
0.1
0
–0.1
–0.2
–0.3
–0.4
–0.8
–1.0
0
1
2
3
TIME (ns)
4
5
08022-050
DIFFERENTIAL AMPLITUDE (V)
50
08022-061
60
–0.5
0
1
2
3
TIME (ns)
Figure 24. Output Waveform,
LVDS (400 MHz)
Figure 21. Output Waveform,
LVPECL (400 MHz)
Rev. 0 | Page 21 of 112
4
AD9548
3.5
3.5
10pF LOAD
5pF LOAD
3.0
3.0
20pF LOAD
2.5
1.5
1.0
1.0
0.5
0
0
0
2
4
6
8
10
12
14
16
TIME (ns)
2.0
10pF LOAD
1.5
20pF LOAD
1.0
0.5
–0.5
4
6
8
10
TIME (ns)
12
14
16
08022-065
0
2
–0.5
0
10
20
30
40
50
60
TIME (ns)
Figure 27. Output Waveform,
3.3 V CMOS (20 MHz, Weak Mode)
Figure 25. Output Waveform,
3.3 V CMOS (100 MHz, Strong Mode)
0
20 pF LOAD
1.5
0.5
–0.5
AMPLITUDE (V)
2.0
Figure 26. Output Waveform,
1.8 V CMOS (100 MHz)
Rev. 0 | Page 22 of 112
70
80
08022-046
AMPLITUDE (V)
2.0
08022-057
AMPLITUDE (V)
2.5
AD9548
INPUT/OUTPUT TERMINATION RECOMMENDATIONS
0.1µF
100Ω
100Ω
HIGH
IMPEDANCE
INPUT
DOWNSTREAM
DEVICE
0.1µF
AD9548
SELF-BIASED
SYSCLK
INPUT
08022-006
08022-003
0.1µF
(OPTIONAL)
AD9548
3.3V LVDS
OUTPUT
0.1µF
Figure 28. AC-Coupled LVDS or LVPECL Output Driver
Figure 31. SYSCLKx Input
AD9548
100Ω
DOWNSTREAM
DEVICE
100Ω
3.3V
LVPECLCOMPATIBLE
OUTPUT
AD9548
SELF-BIASED
CLKINx
INPUT
08022-007
08022-004
0.1µF
(OPTIONAL)
0.1µF
Figure 29. DC-Coupled LVDS or LVPECL Output Driver
Figure 32. CLKINx Input
AD9548
SELF-BIASED
REFERENCE
INPUT
08022-005
0.1µF
(OPTIONAL)
100Ω
0.1µF
Figure 30. Reference Input
Rev. 0 | Page 23 of 112
AD9548
GETTING STARTED
POWER-ON RESET
The AD9548 monitors the voltage on the power supplies at
power-up. When DVDD3 is greater than 2.35 V ± 0.1 V and
DVDD (Pin 1, Pin 6, Pin 12, Pin 77, Pin 83, and Pin 88) is
greater than 1.4 V ± 0.05 V, the device generates a 75 ns reset
pulse. The power-up reset pulse is internal and independent of
the RESET pin. This internal power-up reset sequence eliminates
the need for the user to provide external power supply sequencing.
Within 45 ns after the leading edge of the internal reset pulse,
the M0 to M7 multifunction pins behave as high impedance
digital inputs and remain so until programmed otherwise.
It is essential to program the system clock period because many
of the AD9548 subsystems rely on this value. It is highly
recommended to program the system clock stability timer, as
well. This is especially important when using the system clock
PLL but also applies if using an external system clock source,
especially if the external source is not expected to be completely
stable when power is applied to the AD9548.
Initialize the System Clock
After the system clock functionality is programmed, issue an
I/O update using Register 0005, Bit 0 to invoke the system clock
settings.
INITIAL PIN PROGRAMMING
Calibrate the System Clock (Only if Using SYSCLK PLL)
During a device reset (either via the power-up reset pulse or the
RESET pin), the multifunction pins (M0 to M7) behave as high
impedance inputs, but upon removal of the reset condition,
level-sensitive latches capture the logic pattern present on the
multifunction pins. The AD9548 requires that the user supply
the desired logic state to the M0 to M7 pins by means of pull-up
and/or pull-down resistors (nominally 10 kΩ to 30 kΩ).
Set the calibrate system clock bit in the sync/cal register
(Address 0A02, Bit 0) and issue an I/O update. Then clear the
calibrate system clock bit and issue another I/O update. This
action allows time for the calibration to proceed while programming the remaining device registers.
The initial state of the M0 to M7 pins following a reset is
referred to as FncInit, Bits[7:0]. Bits[7:0] of FncInit map directly
to the logic states of M7:0, respectively. The three LSBs of
FncInit (FncInit, Bits[2:0]) determine whether the serial port
interface behaves according to the SPI or I2C protocol.
Specifically, FncInit, Bits[2:0] = 000 selects the SPI interface,
while any other value selects the I2C port with the three LSBs of
the I2C bus address set to the value of FncInit, Bits[2:0].
The five MSBs of FncInit (FncInit, Bits[7:3]) determine the
operation of the EEPROM loader. On the falling edge of RESET,
if FncInit, Bits[7:3] = 00000, then the EEPROM contents are not
transferred to the control registers and the device registers
assume their default values. However, if FncInit, Bits[7:3] ≠
00000, then the EEPROM controller transfers the contents of
the EEPROM to the control registers with condition = FncInit,
Bits[7:3] (see the EEPROM section).
DEVICE REGISTER PROGRAMMING
The initial state of the M0 to M7 pins establishes the serial I/O
port protocol (SPI or I2C). Using the appropriate serial port
protocol, and assuming that an EEPROM download is not used,
program the device according to the recommended sequence
described in the Program the System Clock Functionality
section through the Generate the Output Clock section.
Program the System Clock Functionality
The system clock parameters reside in the 0100 register address
space. They include the following:
•
•
•
System clock PLL controls
System clock period
System clock stability timer
Program the Multifunction Pins (Optional)
This step is required only if the user intends to use any of the
multifunction pins for status or control. The multifunction pin
parameters resides in the 0200 to 0207 register address space.
The default configuration of the multifunction pins is as an
undesignated high impedance input pin.
Program the IRQ Functionality (Optional)
This step is required only if the user intends to use the IRQ feature.
IRQ control resides in the 0200 to 0207 register address space. It
includes the following:
•
•
IRQ pin mode control
IRQ mask
The IRQ mask default values prevent interrupts from being
generated. The IRQ pin mode default is open-drain NMOS.
Program the Watchdog Timer (Optional)
This step is required only if the user intends to use it. Watchdog
timer control resides in the 0200 register address space. The
watchdog timer is disabled by default.
Program the DAC Full-Scale Current (Optional)
This step is required only if the user intends to use a full-scale
current setting other than the default value. DAC full-scale
current control resides in the 0200 register address space.
Program the Digital Phase-Locked Loop (DPLL)
The DPLL parameters reside in the 0300 register address space.
They include the following:
•
•
•
•
•
Rev. 0 | Page 24 of 112
Free-run frequency (DDS frequency tuning word)
DDS phase offset
DPLL pull-in range limits
DPLL closed-loop phase offset
Phase slew control (for hitless reference switching)
AD9548
•
Tuning word history control (for holdover operation)
Program the Clock Distribution Outputs
The clock distribution parameters reside in the 0400 register
address space. They include the following:
•
•
•
•
•
Output power-down control
Output enable (disabled by default)
Output synchronization
Output mode control
Output divider functionality
Program the Reference Inputs
The reference input parameters reside in the 0500 register
address space. They include the following:
•
•
•
•
Reference power-down
Reference logic family
Reference profile assignment control
Phase build-out control
Program the Reference Profiles
The reference profile parameters reside in the 0600 to 0700
register address space. They include the following:
•
•
•
•
•
•
Reference priority
Reference period
Reference period tolerance
Reference validation timer
Reference redetect timer
Digital loop-filter coefficients
•
•
•
Reference prescaler (R-divider)
Feedback dividers (S, U, and V)
Phase and frequency lock detector controls
Generate the Reference Acquisition
After the registers are programmed, issue an I/O update using
Register 0005, Bit 0 to invoke all of the register settings
programmed up to this point.
If the settings are programmed for manual profile assignment,
the DPLL locks to the first available reference that has the
highest priority. If the settings are programmed for automatic
profile assignment, then write to the reference profile detect
register (Address 0A0D) to select the state machines that
require starting. Next, issue an I/O update (Address 0005, Bit 0)
to start the selected state machines. Upon completion of the
reference detection sequence, the DPLL locks to the first
available reference with the highest priority.
Generate the Output Clock
If the registers are programmed for automatic clock distribution
synchronization via DPLL phase or frequency lock, the synthesized output signal appears at the clock distribution outputs
(assuming the output is enabled and that the DDS output signal
has been routed to the CLKIN input pins). Otherwise, set and
then clear the sync distribution bit (Address 0A02, Bit 1) or use
a multifunction pin input (if programmed accordingly) to
generate a clock distribution sync pulse, which causes the
synthesized output signal to appear at the clock distribution
outputs.
Rev. 0 | Page 25 of 112
AD9548
THEORY OF OPERATION
OUT_RSET
AD9548
REFA
REFAA
DIFFERENTIAL
OR
SINGLE-ENDED
REFB
REFBB
REFC
REFCC
DIGITAL PLL CORE
÷S
REFD
REFDD
TDC/PFD
÷R
PROG.
DIGITAL
LOOP
FILTER
POST
DIV
OUT1P
OUT1N
POST
DIV
OUT2P
OUT2N
POST
DIV
OUT3P
OUT3N
TW CLAMP
AND
HISTORY
DDS/DAC
EXTERNAL
ANALOG
FILTER
INPUT
REF
MONITOR
IRQ AND
STATUS
LOGIC
CLKINN
CLOCK
DISTRIBUTION
HOLDOVER
LOGIC
PHASE
CONTROLLER
IRQ
OUT0P
OUT0N
CLKINP
4 OR 8
M0 TO M7
POST
DIV
LOW NOISE
CLOCK
MULTIPLIER
CONTROL
LOGIC
AMP
SYSCLKN SYSCLKP
DIGITAL
INTERFACE
08022-009
SYSCLK PORT
Figure 33. Detailed Block Diagram
OVERVIEW
The AD9548 provides clocking outputs directly related in phase
and frequency to the selected (active) reference but with jitter
characteristics primarily governed by the system clock. The
AD9548 supports up to eight reference inputs and a wide range
of reference frequencies. The core of this product is a digital
phase-locked loop (DPLL). The DPLL has a programmable
digital loop filter that greatly reduces jitter transferred from the
active reference to the output. The AD9548 supports both
manual and automatic holdover. While in holdover, the
AD9548 continues to provide an output as long as the DAC
sample clock is present. The holdover output frequency is a
time average of the output frequency history just prior to the
transition to the holdover condition.
The device offers manual and automatic reference switchover
capability if the active reference is degraded or fails completely.
A direct digital synthesizer (DDS) and integrated DAC constitute a digitally controlled oscillator (DCO). The DCO output is
a sinusoidal signal (450 MHz maximum) at a frequency determined by the active reference frequency and the programmed
values of the reference prescaler (R) and feedback divider (S).
Although not explicitly shown in Figure 33, the S-divider has
both an integer and fractional component, which is similar to a
fractional-N synthesizer.
The SYSCLKx input provides the sample clock for the DAC,
which is either a directly applied high frequency source or a low
frequency source coupled with the integrated PLL-based
frequency multiplier. The low frequency option also allows for
the use of a crystal resonator connected directly across the
SYSCLKx inputs.
The DAC output routes directly off-chip, where an external
filter removes the sampling artifacts before returning the signal
on-chip at the CLKINx inputs. Once on-chip, an integrated
comparator converts the filtered sinusoidal signal to a clock
signal (square wave) with very fast rise and fall times.
The clock distribution section provides four output drivers.
Each driver is programmable either as a single differential
LVPECL/LVDS output or as a dual single-ended CMOS output.
Furthermore, each of the four outputs has a dedicated 30-bit
programmable postdivider. The clock distribution section
operates at up to 725 MHz. This enables use of a band-pass
reconstruction filter (for example, a SAW filter) to extract a
Nyquist image from the DAC output spectrum, thereby
allowing output frequencies that exceed the typical 450 MHz
limit at the DAC output.
Rev. 0 | Page 26 of 112
AD9548
REFERENCE CLOCK INPUTS
Four pairs of pins provide access to the reference clock receivers.
Each pair is configurable either as a single differential receiver
or as two independent single-ended receivers. To accommodate
input signals with slow rising and falling edges, both the
differential and single-ended input receivers employ hysteresis.
Hysteresis also ensures that a disconnected or floating input
does not cause the receiver to oscillate spontaneously.
When configured for differential operation, the input receivers
accommodate either ac- or dc-coupled input signals. The
receiver is internally dc biased in order to handle ac-coupled
operation.
When configured for single-ended operation, the input
receivers exhibit a pull-down load of 45 kΩ (typical). Three
user-programmable threshold voltage ranges are available for
each single-ended receiver.
REFERENCE MONITORS
The reference monitors depend on a known and accurate
system clock period. Therefore, the functioning of the reference
monitors is not reliable until the system clock is stable. To avoid
an incorrect valid indication, the reference monitors indicate
fault status until the system clock stability timer expires (see the
System Clock Stability Timer section).
Reference Period Monitor
Each reference input has a dedicated monitor that repeatedly
measures the reference period. The AD9548 uses the reference
period measurements to determine the validity of the reference
based on a set of user provided parameters in the profile
register area of the register map (see the Profile Registers
(Register 0600 to Register 07FF) section). The AD9548 also
uses the reference period monitor to assign a particular
reference to a profile when the user programs the device for
automatic profile assignment.
The monitor works by comparing the measured period of a
particular reference input with the parameters stored in the
profile register assigned to that same reference input. The
parameters include the reference period, an inner tolerance, and
an outer tolerance. A 50-bit number defines the reference
period in units of femtoseconds. The 50-bit range allows for a
reference period entry of up to 1.125 sec. However, an actual
reference signal with a period in excess of 1 sec is beyond the
recommended operating range of the device. A
20-bit number defines the inner and outer tolerances. The value
stored in the register is the reciprocal of the tolerance
specification. For example, a tolerance specification of 50 ppm
yields a register value of 1/(50 ppm) = 1/0.000050 = 20,000
(0x04E20).
The use of two tolerance values provides hysteresis for the
monitor decision logic. The inner tolerance applies to a
previously faulted reference and specifies the largest period
tolerance that a previously faulted reference can exhibit before it
qualifies as nonfaulted. The outer tolerance applies to an already
nonfaulted reference. It specifies the largest period tolerance
that a nonfaulted reference can exhibit before being faulted.
To produce decision hysteresis, the inner tolerance must be less
than the outer tolerance. That is, a faulted reference must meet
tighter requirements to become nonfaulted than a nonfaulted
reference must meet to become faulted.
Reference Validation Timer
Each reference input has a dedicated validation timer. The
validation timer establishes the amount of time that a
previously faulted reference must remain fault free before the
AD9548 declares it nonfaulted. The timeout period of the
validation timer is programmable via a 16-bit register (see the
validation register contained within each of the eight profile
registers in the register map, Address 0600 to Address 07FF).
The 16-bit number stored in the validation register represents
units of milliseconds, which yields a maximum timeout period
of 65,535 ms.
Note that a validation period of 0 must be programmed to
disable the validation timer. With the validation timer disabled,
the user must validate a reference manually via the force
validation timeout register (Address 0A0E).
Reference Redetect Timer
Each reference input has a dedicated redetect timer. The
redetect timer is useful only with the device programmed for
automatic profile selection. The redetect timer establishes the
amount of time that a reference must remain faulted before the
AD9548 attempts to reassign it to a new profile. The timeout
period of the redetect timer is programmable via a 16-bit
register (see the redetect timeout register contained within each
of the eight profile registers in the register map, Address 0600 to
Address 07FF). The 16-bit number stored in the redetect
timeout register represents units of milliseconds, which yields a
maximum timeout period of 65,535 ms.
Note that a timeout period of 0 must be programmed to disable
the redetect timer.
Reference Validation Override Control
Register 0A0E to Register 0A10 provide the user with the ability
to override the reference validation logic enabling a certain level
of troubleshooting capability. Each of the eight input references
has a dedicated block of validation logic as shown in Figure 34.
The state of the valid signal at the output is what defines a
particular reference as valid (1) or not (0), which includes the
validation period (if activated) as prescribed by the validation
timer. The override controls are the three control bits on the left
side of the diagram.
Rev. 0 | Page 27 of 112
AD9548
REGISTER CONTROL BITS
REFERENCE VALIDATION LOGIC
(8 COPIES, 1 PER REFERENCE INPUT)
D Q
VALID
FORCE VALIDATION
TIMEOUT
VALIDATION TIMER
REF MONITOR
BYPASS
REF MONITOR
OVERRIDE
R
1
EN
R
TIMEOUT
FAULTED
REFERENCE
MONITOR
08022-010
0
REF FAULT
Figure 34. Reference Validation Override
The main feature to note is that any time faulted = 1, the output
latch is reset, which forces valid = 0 (indicating an invalid reference) regardless of the state of any other signal. Under the
default condition (that is, all three control bits are 0), the
reference monitor is the primary source of the validation
process. This is because, under the default condition, the ref
fault signal from the reference monitor is identically equal to
the faulted signal.
The function of the faulted signal is fourfold.
•
•
•
•
Any time faulted = 1, then valid = 0, regardless of the state
of any other control signal. Therefore, faulted = 1 indicates
an invalid reference.
Any time the faulted signal transitions from 0 to 1 (that is,
from nonfaulted to faulted), the validation timer is
momentarily reset, which means that, once it is enabled, it
must exhaust its full counting sequence before it expires.
When faulted = 0 (that is, the reference is not faulted), the
validation timer is allowed to perform its timing sequence.
When faulted = 1 (that is, the reference is faulted), the
validation timer is reset and halted.
The faulted signal passes through an inverter, converting it
to a nonfaulted signal, which appears at the input of the
valid latch. This allows the valid latch to capture the state
of the nonfaulted signal when the validation timer expires.
The ref monitor bypass control bit enables bypassing of the ref
fault signal generated by the reference monitor. When ref
monitor bypass = 1, the state of the faulted signal is dictated by
the ref monitor override control bit. This is useful when the
user relies on an external reference monitor rather than the
internal monitor resident in the device. The user programs the
ref monitor override bit based on the status of the external
monitor. On the other hand, when ref monitor bypass = 0, the
ref monitor override control bit allows the user to manually test
the operation of both the valid latch and the validation timer. In
this case, the user relies on the signal generated by the internal
reference monitor (ref fault) but uses the ref monitor override
bit to emulate a faulted reference. That is, when ref monitor
override = 1, then faulted = 1, but when ref monitor override =
0, then faulted = ref fault.
In addition, the user has the ability to emulate a timeout of the
validation timer via the appropriate force validation timeout
control bit in Register 0A0E. Writing a Logic 1 to any of these
autoclearing bits triggers the valid latch, which is identically
equivalent to a timeout of the validation timer.
REFERENCE PROFILES
The AD9548 has eight independent profile registers. A profile
register contains 50 bytes that establish a particular set of device
parameters. Each of the eight input references can be assigned
to any one of the eight profiles (that is, more than one reference
can be assigned to the same profile). The profiles allow the user
to prescribe the specific device functionality that should take
effect when one of the input references (assigned to the profile)
becomes the active reference. Each profile register has the same
format and stores the following device parameters:
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
Reference priority
Reference period value (in femtoseconds)
Inner tolerance value (1/tolerance)
Outer tolerance value (1/tolerance)
Validation timer value (milliseconds)
Redetect timer value (milliseconds)
Digital loop filter coefficients
Reference prescaler setting (R-divider)
Feedback divider settings (S, U, and V)
DPLL phase lock detector threshold level
DPLL phase lock detector fill rate
DPLL phase lock detector drain rate
DPLL frequency lock detector threshold level
DPLL frequency lock detector fill rate
DPLL frequency lock detector drain rate
Reference-to-Profile Assignment Control
The user can manually assign a reference to a profile or let the
device make the assignment automatically. The manual
reference profile selection register (Address 0503 to Address
0506) is where the user programs whether a reference-to-profile
assignment is manual or automatic. The manual reference
profile selection register is a 4-byte register partitioned into
eight half bytes (or nibbles). The eight nibbles form a one-toone correspondence with the eight reference inputs: one nibble
for REF A, the next for REF AA, and so on. For a reference
configured as a differential input, however, the device ignores
the nibble associated with the two-letter input. For example, if
Rev. 0 | Page 28 of 112
AD9548
the B reference is differential, then only the REFB nibble
matters (the device ignores the REFBB nibble).
The MSB of each nibble is the manual profile bit, whereas the
three LSBs of each nibble identify one of the eight profiles
(0 to 7). A Logic 1 for the manual profile bit assigns the
associated reference to the profile identified by the three LSBs of
the nibble. A Logic 0 for the manual profile bit configures the
associated reference for automatic reference-to-profile
assignment (the three LSBs are ignored in this case). Note that
references configured for automatic reference-to-profile
assignment require activation (see the Reference-to-Profile
Assignment State Machine section).
Reference-to-Profile Assignment State Machine
The functional flexibility of the AD9548 resides in the way that
it assigns a particular input reference to one of the eight
reference profiles. The reference-to-profile assignment state
machine effectively builds a reference-to-profile table that maps
the index of each input reference to a profile (see Table 22).
Each entry in the profile column consists of a profile number
(0 to 7) or a null value. A null value appears when a referenceto-profile assignment does not exist for a particular reference
input (following a reset, for example). The information in
Table 22 appears in the register map (Register 0D0C to Register
0D13) so that the user has access to the reference-to-profile
assignments on a real-time basis. Register 0D0C contains the
information for REF A, Register 0D0D contains the information for REF AA, and so on to Register 0D13 for REF DD. Bit 7
of each register is the null indicator for that particular reference.
If Bit 7 = 0, then the profile assignment for that particular
reference is null. If Bit 7 = 1, then that particular reference is
assigned to the profile (0 to 7) identified by Bits[6:4]. Note that
Bits[6:4] are meaningless unless Bit 7 = 1.
Table 22. Reference-to-Profile Table
Reference
Input
A
Reference
Index
0
Profile
Profile number (or null value)
AA
1
Profile number (or null value)
B
2
Profile number (or null value)
BB
3
Profile number (or null value)
C
4
Profile number (or null value)
CC
5
Profile number (or null value)
D
6
Profile number (or null value)
DD
7
Profile number (or null value)
Following a reset, the reference-to-profile assignment state
machine is inactive to avoid improperly assigning a reference to
a profile before the system clock stabilizes. The reason is that
the state machine relies on accurate information from the
reference monitors, which, in turn, rely on a stable system clock.
Because the reference-to-profile assignment state machine is
inactive at power-up, the user must initiate it manually by
writing to the reference profile detect register (Address 0A0D).
The state machine activates immediately, unless the system
clock is not stabilized, in which case, activation occurs upon
expiration of the system clock stability timer. Note that
initialization of the state machine is on a per-reference basis.
That is, each reference input is associated with an independent
initialization control bit.
Once initialized for processing a reference, the state machine
continuously monitors that reference until the occurrence of a
device reset. This is true even when the user programs a
reference for manual profile selection, in which case, the state
machine associated with that particular reference operates with
its activity masked. The masked background activity allows for
seamless operation if the user subsequently reprograms the
reference for automatic profile selection.
Reference-to-Profile Assignment
When a reference is programmed for manual profile assignment
(see Register 0503 to Register 0506), the reference-to-profile
assignment state machine simply puts the programmed manual
profile number into the profile column of the reference-toprofile table (see Table 22) in the row associated with the appropriate reference. However, when the user programs a reference
for automatic profile assignment, the state machine must figure
out which profile to assign to the reference.
As long as a null entry appears in the reference-to-profile table
for a particular input reference, the validation logic for that
reference enters a period estimation mode. Note that a null
entry is the default state following a reset, but it also occurs
when a reference redetect timer expires. The period estimation
mode enables the validation logic to make a blind estimate of
the period of the input reference with a tolerance of 0.1%. The
validation logic remains in the period estimation mode until it
successfully estimates the reference period.
Upon a successful reference period measurement by the
validation logic, the state machine compares the measured
period to the nominal reference period programmed into each
of the eight profiles. The state machine assigns the reference to
the profile with the closest match to the measured period. If
more than one profile exactly matches the reference period,
then the state machine chooses the profile with the lowest
numeric index. For example, if the reference period in both
Profile 3 and Profile 5 matches the measured period, then
Profile 3 is given the assignment.
To safeguard against making a poor reference-to-profile
assignment, the state machine ensures that the measured
reference period is within 6.25% of the nominal reference
period that appears in the closest match profile. Otherwise, the
state machine does not make a profile assignment and leaves
the null entry in the reference-to-profile table.
As long as there are input references programmed for automatic
profile assignment, and for which the profile assignment is null,
the state machine continues to cycle through those references
searching for a profile match. Furthermore, unless an input
Rev. 0 | Page 29 of 112
AD9548
reference is assigned to a profile, it is considered invalid and
excluded as a candidate for a reference switchover.
REFERENCE SWITCHOVER
An attractive feature of the AD9548 is its versatile reference
switchover capability. The flexibility of the reference switchover
functionality resides in a sophisticated prioritization algorithm
coupled with register-based controls. This scheme provides the
user with maximum control over the state machine that handles
reference switchover.
The main reference switchover control resides in the loop
mode register (Address 0A01). The user selection mode bits
(Register 0A01, Bits[4:3]) allow the user to select one of the
reference switchover state machine’s four operating modes, as
follows:
•
•
•
•
Automatic mode (Address A01, Bits[4:3] = 00)
Fallback mode (Address 0A01, Bits[4:3] = 01)
Holdover mode (Address 0A01, Bits[4:3] = 10)
Manual mode (Address 0A01, Bits[4:3] = 11)
In automatic mode, a fully automatic priority-based algorithm
selects which reference is the active reference. When programmed
for automatic mode, the device ignores the user selection
reference bits (Register 0A01, Bits[2:0]). However, when programmed for any of the other three modes, the device makes
use of the user reference bits. These bits specify a particular
input reference (000 = REF A, 001 = REF AA ..., 111 = REF DD).
In fallback mode, the user reference is the active reference
whenever it is valid. Otherwise, the device switches to a new
reference using the automatic, priority-based algorithm.
In holdover mode, the user reference is the active reference
whenever it is valid. Otherwise, the device switches to holdover
mode.
In manual mode, the user reference is the active reference
whether it is valid or not. Note that, when using this mode, the
user must program the reference-to-profile assignment (see
register 0503 to Register 0506) as manual for the particular
reference declared as the user reference. The reason is that if the
user reference fails and its redetect timer expires, then its profile
assignment (shown in Table 22) becomes null. This means that
the active reference (user reference) does not have an assigned
profile, which places the AD9548 into an undefined state.
The user also has the option to force the device directly into
holdover or free-run operation via the user holdover and user
free-run bits (Register 0A01, Bit 6 and Bit 5, respectively]). In
free-run mode, the free running frequency tuning word register
(Address 0300 to Address 0305) defines the DDS output
frequency. In holdover mode, the DDS output frequency
depends on the holdover control settings (see the Holdover
section).
Automatic Priority-Based Reference Switchover
The AD9548 has a two-tiered, automatic, priority-based
algorithm that is in effect for both automatic and fallback
reference switchover. The algorithm relies on the fact that each
reference profile contains both a selection priority and a
promoted priority. The selection and promoted priority values
range from 0 (highest priority) to 7 (lowest priority). The
selection priority determines the order in which references are
chosen as the active reference. The promoted priority is a
separate priority value given to a reference only after it becomes
the active reference.
An automatic reference switchover occurs on failure of the
active reference or when a previously failed reference becomes
valid and its selection priority is higher than the promoted
priority of the currently active reference (assuming that the
automatic or fallback reference switchover is in effect). When
performing an automatic reference switchover, the AD9548
chooses a reference based on the priority settings within the
profiles. That is, the device switches to the reference with the
highest selection priority (lowest numeric priority value). It
does so by using the reference-to-profile table (see Table 22) to
determine the reference associated with the profile exhibiting
the highest priority.
If multiple references share the same profile, then the device
chooses the reference having the lowest index value. For
example, if the A, B, and CC references (Index 0, Index 2, and
Index 5, respectively) share the same profile, then a switchover
to Reference A occurs because Reference A has the lowest index
value. Note, however, that only valid references are included in
switchover of the selection process. The switchover control logic
ignores any reference with a status indication of invalid.
The promoted priority parameter allows the user to assign a
higher priority to a reference after it becomes the active
reference. For example, suppose four references have a selection
priority of 3 and a promoted priority of 1, and the remaining
references have a selection priority or 2 and a promoted priority
of 2. Now, assume that one of the Priority 3 references becomes
active because all of the Priority 2 references have failed. Sometime later, however, a Priority 2 reference becomes valid. The
switchover logic normally attempts to automatically switch over
to the Priority 2 reference because it has higher priority than the
presently active Priority 3 reference. However, because the
Priority 3 reference is active, its promoted priority of 1 is in
effect. This is a higher priority than the newly validated
reference’s priority of 2, so the switchover does not occur. This
mechanism enables the user to give references preferential
treatment while they are selected as the active reference. An
example of promoted vs. nonpromoted priority switching
appears in state diagram form in Figure 35. Figure 36 shows a
block diagram of the interrelationship between the reference
inputs, monitors, validation logic, profile selection, and priority
selection functionality.
Rev. 0 | Page 30 of 112
AD9548
A
ACTIVE
ALL VALID
A VALID
PRIORITY TABLE
INPUT
PRIORITY
PROMOTED
A
0
0
B
1
0
C
2
1
D
3
2
A FAULTED
B
ACTIVE
B VALID
COMMON
WITHOUT PROMOTION
WITH PROMOTION
A VALID
B FAULTED
C
ACTIVE
B VALID
08022-011
INITIAL
STATE
Figure 35. Example of Priority Promotion
PROFILE
SELECTION
VALIDATION
LOGIC
PRIORITY
SELECTION
LOOP
CONTROLLER
… …
MONITORS
÷R
TDC
08022-012
…
B/BB
C/CC
………
A/AA
D/DD
Figure 36. Reference Clock Block Diagram
Phase Build-Out Reference Switching
Phase build-out reference switching is the term given to a
reference switchover that completely masks any phase
difference between the previous reference and the new
reference. That is, there is virtually no phase change detectable
at the output when a phase build-out switchover occurs.
The AD9548 handles phase build-out switching based on
whether the new reference is a phase master. A phase master is
any reference with a selection priority value that is less than the
phase master threshold priority value (that is, higher priority).
The phase master threshold priority value resides in the phase
build-out switching register (Address 0507), whereas the
selection priority resides in the profile registers (Address 0600
to Address 07FF). By default, the phase master threshold
priority is 0; therefore, no references can be phase masters until
the user changes the phase master threshold priority.
Whenever the AD9548 switches from one reference to another,
it compares the selection priority value stored in the profile
assigned to the new reference with the phase master threshold
priority. The AD9548 performs a phase build-out switchover
only if the new reference is not a phase master.
Hitless Reference Switching (Phase Slew Control)
Hitless reference switching is the term given to a reference
switchover that limits the rate of change of the phase of the
output clock while the PLL is in the process of acquiring phase
lock. This prevents the output frequency offset from becoming
excessive.
The all-digital nature of the DPLL core (see the Digital PLL
(DPLL) Core section) gives the user numerical control of the
rate at which phase changes occur at the DPLL output. When
enabled, a phase slew controller monitors the phase difference
between the feedback and reference inputs to the DPLL. The
phase slew controller has the ability to place a user-specified
limit on the rate of change of phase, thus providing a
mechanism for hitless reference switching.
The user sets a limit on the rate of change of phase by storing
the appropriate value in the 16-bit phase slew rate limit register
(Address 0316 to Address 0317). The 16-bit word (representing
ns/sec) puts an upper bound on the rate of change of the phase
at the output of the DPLL during a reference switchover. A
phase slew rate value of 0 (default) disables the phase slew
controller.
The accuracy of the phase slew controller depends on both the
phase slew limit value and the system clock frequency.
Generally, an increase in the phase slew rate limit value or a
decrease in the system clock frequency tends to reduce the
error. As such, the accuracy is best for the largest phase slew
limit value and the lowest system clock frequency. For example,
assuming the use of a 1 GHz system clock, a phase slew limit
value of 315 ns/sec (or more) ensures an error of less than 10%,
whereas a phase slew rate limit value above ~3100 ns/sec
ensures an error of less than 1%. On the other hand, assuming
the use of a 500 MHz system clock, the same phase slew rate
limit values ensure an error of less than 5% or 0.5%,
respectively.
Rev. 0 | Page 31 of 112
AD9548
The DPLL includes a feedback divider that causes the DDS to
operate at an integer-plus-fractional multiple (S + 1 + U/V) of
fTDC. S is the 30-bit value stored in the profile register and has
a range of 7 ≤ S ≤ 1,073,741,823. U and V are the 10-bit numerator and denominator values of the optional fractional divide
component and are also stored in the profile register. Together
they establish the nominal DDS frequency (fDDS), given by
DIGITAL PLL (DPLL) CORE
DPLL Overview
A diagram of the digital PLL core of the AD9584 appears in
Figure 37. The phase/frequency detector, feedback path, lock
detectors, phase offset, and phase slew rate limiting that
comprise this second generation DPLL are all digital
implementations.
PHASE SLEW
LIMIT
f DDS =
DPPL CORE
CLOSED-LOOP
PHASE OFFSET
REF A
R+1
REF DD
fTDC
TDC
AND
PFD
DIGITAL
LOOP
FILTER
DDS/
DAC
fDDS
2
DACOUT
08022-013
fR
S + 1 + U/V
Figure 37. Digital PLL Core
The start of the DPLL signal chain is the reference signal, fR,
which is the frequency of the reference input. A reference
prescaler reduces the frequency of this signal by an integer factor,
R + 1, where R is the 30-bit value stored in the appropriate
profile register and 0 ≤ R ≤ 1,073,741,823. Therefore, the frequency at the output of the R-divider (or the input to TDC) is
f TDC =
fR
R +1
A time-to-digital converter (TDC) samples the output of the
R-divider. The TDC/PFD produces a time series of digital
words and delivers them to the digital loop filter. The digital
loop filter offers the following advantages:
•
•
•
•
fR ⎛
U⎞
⎜S +1+ ⎟
R +1⎝
V⎠
Normally, fractional-N designs exhibit distinctive phase noise
and spurious artifacts resulting from the modulation of the
integer divider based on the fractional value. Such is not the
case for the AD9548 because it uses a purely digital means to
determine phase errors. Because the phase errors incurred by
modulating the feedback divider are deterministic, it is possible
to compensate for them digitally. The result is a fractional-N
PLL with no discernable modulation artifacts.
TDC/PFD
The TDC is a highly integrated functional block that incorporates both analog and digital circuitry. There are two pins
associated with the TDC that the user must connect to external
components. Figure 38 shows the recommended component
values and their connections.
For best performance, place components as close as possible to
the device pins. Components with low effective series resistance
(ESR) and low parasitic inductance yield the best results.
AD9548
58
57
Determination of the filter response by numeric
coefficients rather than by discrete component values
The absence of analog components (R/L/C), which
eliminates tolerance variations due to aging
The absence of thermal noise associated with analog
components
The absence of control node leakage current associated
with analog components (a source of reference feedthrough spurs in the output spectrum of a traditional
analog PLL)
TDC_VRB
TDC_VRT
0.1µF
10µF
0.1µF
0.1µF
08022-014
LOCK
DETECT
Figure 38. TDC Pin Connections
The digital loop filter produces a time series of digital words at
its output and delivers them to the frequency tuning input of a
DDS, with the DDS replacing the function of the VCO in an
analog PLL. The digital words from the loop filter tend to steer
the DDS frequency toward frequency and phase lock with the
input signal (fTDC). The DDS provides an analog output signal
via an integrated DAC, effectively mimicking the operation of
an analog VCO.
The phase-frequency detector (PFD) is an all-digital block. It
compares the digital output from the TDC (which relates to the
active reference edge) with the digital word from the feedback
block (which relates to the rollover edge of the DDS
accumulator after division by the feedback divider). It uses a
digital code pump and digital integrator (rather than a
conventional charge pump and capacitor) to generate the error
signal that steers the DDS frequency toward phase lock.
Closed-Loop Phase Offset
The all-digital nature of the TDC/PFD provides for numerical
control of the phase offset between the reference and feedback
edges. This allows the user to adjust the relative timing of the
distribution output edges relative to the reference input edges
by programming the 40-bit fixed phase lock offset register
Rev. 0 | Page 32 of 112
AD9548
(Address 030F to Address 0313). The 40-bit word is a signed
(twos complement) number that represents units of picoseconds.
In addition, the user can adjust the closed-loop phase offset
(positive or negative) in incremental fashion. To do so, program
the desired step size in the 16-bit incremental phase lock offset
step size register (Address 0314 to Address 0315). This is an
unsigned number that represents units of picoseconds. The
programmed step size is added to the current closed-loop phase
offset each time the user writes a Logic 1 to the increment phase
offset bit (Register 0A0C, Bit 0). Conversely, the programmed
step size is subtracted from the current closed-loop phase offset
each time the user writes a Logic 1 to the decrement phase offset
bit (Register 0A0C, Bit 1). The serial I/O port control logic clears
both of these bits automatically. The user can remove the incrementally accumulated phase by writing a Logic 1 to the reset
incremental phase offset bit (Register 0A0C, Bit 2), which is
also cleared automatically. Alternatively, rather than using the
serial I/O port, the multifunction pins can be set up to perform
the increment, decrement, and clear functions.
Note that the incremental phase offset is completely independent of the offset programmed into the fixed phase lock offset
register. However, if the phase slew limiter is active (see the
Hitless Reference Switching (Phase Slew Control) section), then
any instantaneous change in closed-loop phase offset (fixed or
incremental) will be subject to possible slew limitation by the
action of the phase slew limiter.
Programmable Digital Loop Filter
The AD9548 loop filter is a third order digital IIR filter that is
analogous to the third order analog loop shown in Figure 39.
C1
R2
C3
C2
08022-015
R3
Figure 39. Third Order Analog Loop Filter
The filter requires four coefficients as shown in Figure 40. The
AD9548 evaluation board software automatically generates the
required loop filter coefficient values based on the user’s design
criteria. The Calculating Digital Filter Coefficients section
contains the design equations for calculating the loop filter
coefficients manually.
FRACTIONAL
(16-BIT)
1/2x
(6-BIT)
FRACTIONAL
(17-BIT)
2x
(4-BIT)
1/2x
(6-BIT)
51
IN
FRACTIONAL
(17-BIT)
FRACTIONAL
(15-BIT)
1/2x
(6-BIT)
1/2x
(5-BIT)
LOOP FILTER
(THIRD ORDER IIR)
48
OUT
Figure 40. Third Order Digital IIR Loop Filter
Each coefficient has a fractional component representing a
value from 0 up to, but not including, unity. Each coefficient
08022-016
2x
(3-BIT)
also has an exponential component representing a power of 2
with a negative exponent. That is, the user enters a positive
number (x) that the hardware interprets as a negative exponent
of two (2−x). Thus, the β, γ, and δ coefficients always represent
values less than unity. The α coefficient, however, has two
additional exponential components, but the hardware interprets
these as a positive exponent of 2 (that is, 2x). This allows the α
coefficient to be a value greater than unity. The positive
exponent appears as two separate terms in order to provide
sufficient dynamic range.
DPLL Phase Lock Detector
The DPLL contains an all-digital phase lock detector. The user
controls the threshold sensitivity and hysteresis of the phase
detector via the profile registers.
The phase lock detector behaves in a manner analogous to
water in a tub (see Figure 41). The total capacity of the tub is
4096 units with −2048 denoting empty, 0 denoting the 50%
point, and +2048 denoting full. The tub also has a safeguard to
prevent overflow. Furthermore, the tub has a low water mark at
−1024 and a high water mark at +1024. To change the water
level, the user adds water with a fill bucket or removes water
with a drain bucket. The user specifies the size of the fill and
drain buckets via the 8-bit fill rate and drain rate values in the
profile registers.
The water level in the tub is what the lock detector uses to
determine the lock and unlock conditions. Whenever the water
level is below the low water mark (−1024), the detector
indicates an unlock condition. Conversely, whenever the water
level is above the high water mark (+1024), the detector indicates
a lock condition. While the water level is between the marks,
the detector simply holds its last condition. This concept appears
graphically in Figure 41, with an overlay of an example of the
instantaneous water level (vertical) vs. time (horizontal) and the
resulting lock/unlock states.
During any given PFD phase error sample, the detector either
adds water with the fill bucket or removes water with the drain
bucket (one or the other but not both). The decision of whether
to add or remove water depends on the threshold level specified
by the user. The phase lock threshold value is a 16-bit number
stored in the profile registers and is expressed in picoseconds.
Thus, the phase lock threshold extends from 0 ns to ±65.535 ns
and represents the magnitude of the phase error at the output of
the PFD.
The phase lock detector compares each phase error sample at
the output of the PFD to the programmed phase threshold
value. If the absolute value of the phase error sample is less than
or equal to the programmed phase threshold value, then the
detector control logic dumps one fill bucket into the tub.
Otherwise, it removes one drain bucket from the tub. Notice
that it is not the polarity of the phase error sample, but its
magnitude relative to the phase threshold value, that determines
whether to fill or drain. If more filling is taking place than
Rev. 0 | Page 33 of 112
AD9548
draining, the water level in the tub eventually rises above the
high water mark (+1024), which causes the phase lock detector
to indicate lock. If more draining is taking place than filling,
then the water level in the tub eventually falls below the low
water mark (−1024), which causes the phase lock detector to
indicate unlock. The ability to specify the threshold level, fill
rate, and drain rate enables the user to tailor the operation of
the phase lock detector to the statistics of the timing jitter
associated with the input reference signal.
LOCKED
DDS Overview
One of the primary building blocks of the digital PLL is a direct
digital synthesizer (DDS). The DDS behaves like a sinusoidal
signal generator. The frequency of the sinusoid generated by the
DDS is determined by a frequency tuning word (FTW), which
is a digital (that is, numeric) value. Unlike an analog sinusoidal
generator, a DDS uses digital building blocks and operates as a
sampled system. Thus, it requires a sampling clock (fS) that
serves as the fundamental timing source of the DDS. The
accumulator behaves as a modulo-248 counter with a
programmable step size (FTW). A block diagram of the DDS
appears in Figure 42.
UNLOCKED
2048
LOCK LEVEL
1024
DRAIN
RATE
UNLOCK LEVEL
–1024
The input to the DDS is the 48-bit FTW. The FTW serves as a
step size value. On each cycle of fS, the accumulator adds the
value of the FTW to the running total at its output. For
example, given FTW = 5, the accumulator counts by fives,
incrementing on each fS cycle. Over time, the accumulator
reaches the upper end of its capacity (248 in this case), at which
point, it rolls over but retains the excess. The average rate at
which the accumulator rolls over establishes the frequency of
the output sinusoid. The average rollover rate of the accumulator
establishes the output frequency (fDDS) of the DDS and is given by
08022-017
0
FILL
RATE
–2048
Figure 41. Lock Detector Diagram
Note that whenever the AD9548 enters the free-run or holdover
mode, the DPLL phase lock detector indicates unlocked. In
addition, whenever the AD9548 performs a reference switchover, the state of the lock detector prior to the switch is
preserved during the transition period.
DPLL Frequency Lock Detector
⎛ FTW ⎞
f DDS = ⎜ 48 ⎟ f S
⎝ 2 ⎠
The operation of the frequency lock detector is identical to that
of the phase lock detector. The only difference is that the fill or
drain decision is based on the period deviation between the
reference and feedback signals of the DPLL instead of the phase
error at the output of the PFD.
Solving this equation for FTW yields
⎡ ⎛f
FTW = round ⎢2 48 ⎜ DDS
⎢⎣ ⎜⎝ f S
The frequency lock detector uses a 24-bit frequency threshold
register specified in units of picoseconds. Thus, the frequency
threshold value extends from 0 μs to ±16.777215 μs. It represents
the magnitude of the difference in period between the reference
and feedback signals at the input to the DPLL. For example, if
the reference signal is 1.25 MHz and the feedback signal is 1.38
MHz, then the period difference is approximately 75.36 ns
(|1/1,250,000 − 1/1,380,000| ≈ 75.36 ns).
48-BIT ACCUMULATOR
48
FREQUENCY
TUNING WORD
(FTW)
48
⎞⎤
⎟⎥
⎟⎥
⎠⎦
For example, given that fS = 1 GHz and fDDS = 155.52 MHz, then
FTW = 437,749,988,378,041 (0x27D028A1DFB9).
Note that the minimum DAC output frequency is 62.5 MHz;
therefore, normal operation requires an FTW that yields an
output frequency in excess of this lower bound.
PHASE
OFFSET
16
19
48
D
Q
19
ANGLE TO
AMPLITUDE
CONVERSION
14
DAC+
DAC
(14-BIT)
DAC–
fS
Figure 42. DDS Block Diagram
Rev. 0 | Page 34 of 112
08022-018
PREVIOUS
STATE
DIRECT DIGITAL SYNTHESIZER
AD9548
The relative phase of the sinusoid generated by the DDS is
numerically controlled by adding a phase offset word to the output
of the DDS accumulator. This is accomplished via the open loop
phase offset register (Address 030D to Address 030E), which is
a programmable 16-bit value (Δphase). The resulting phase offset,
ΔΦ (in radians), is given by
⎛ Δphase ⎞
ΔΦ = 2π ⎜
⎟
16
⎝ 2
⎠
DAC Output
The output of the digital core of the DDS is a time series of
numbers representing a sinusoidal waveform. The DAC
translates the numeric values to an analog signal. The DAC
output signal appears at two pins that constitute a balanced
current source architecture (see Figure 43).
AVDD3
22
CURRENT
MIRROR
CODE
214 – 1
FROM DIGITAL
LOOP FILTER
LOWER
TUNING
WORD
TO DDS
UPPER
TUNING
WORD
When the DPLL is in free-run mode, the DDS tuning word is
the value stored in the free running frequency tuning word
register (Address 0300 to Address 0305). When the DPLL is
operating normally (closed loop), the DDS tuning word comes
from the output of the digital loop filter, which changes
dynamically in order to maintain phase lock with the input
reference signal (assuming that the device has not performed an
automatic switch to holdover mode). When the DPLL is in
holdover mode, the DDS tuning word depends on a historical
record of past tuning words during the time that the DPLL
operated in closed-loop mode.
Frequency Clamp
IFS
IFS (
TUNING
WORD
CLAMP
TUNING
WORD
ROUTING
CONTROL
TUNING WORD
UPDATE
However, regardless of the operating mode, the DDS output
frequency is ultimately subject to the boundary conditions
imposed by the frequency clamp logic, as explained in the
Frequency Clamp section.
21
10
FREE-RUN
TUNING WORD
Figure 44. Tuning Word Processing
Phase offset and relative time offset are directly related. The
time offset is (Δphase/216)/fDDS (in seconds), where fDDS is the
output frequency of the DDS (in hertz).
ISCALE
TUNING WORD
HISTORY
PROCESSOR
TUNING WORD
HISTORY
08022-070
DDS Phase Offset
CURRENT
SWITCH
ARRAY
)
DACOUTP 18
IFS (1–
)
19 DACOUTN
SWITCH
CONTROL
50Ω
CODE
214 – 1
The user controls the frequency clamp boundaries via the pullin range limits registers (Address 0307 to Address 030C). These
registers allow the user to fix the DDS output frequency
between an upper and lower bound with a granularity of 24 bits.
Note that these upper and lower bounds apply regardless of the
frequency tuning word that appears at the input to the DDS.
The register value relates to the absolute upper or lower
frequency bound (fCLAMP) as
14
50Ω
CODE
08022-019
GND
GND
fCLAMP = fS × (N/224)
Where N is the value stored in the upper- or lower-limit
register,and fS is the system sample rate.
Figure 43. DAC Output Pins
The value of IFS is programmable via the 10-bit DAC full-scale
current word in the DAC current register (Address 0213 to
Address 0214). The value of the 10-bit word (ISCALE) sets IFS
according to the following formula:
(
( )
3
I FS = 120 μA × 72 + 16 I SCALE
)
Even though the frequency clamp limits put a bound on the
DDS output frequency, the DPLL is still free to steer the DDS
frequency within the clamp limits. The default register values
set the clamp range from 0 Hz (dc) to fS, effectively eliminating
the frequency clamp functionality until the user alters the
register values.
TUNING WORD PROCESSING
Frequency Tuning Word History
The frequency tuning words that dictate the output frequency
of the DDS come from one of three sources (see Figure 44).
The AD9548 has the ability to track the history of the tuning
word samples generated by the DPLL digital loop filter output.
It does so by periodically computing the average tuning word
value over a user-specified interval. The user programs the
interval via the 24-bit history accumulation timer register
(Address 0318 to Address 031A). This 24-bit value represents
a time interval (TAVG) in milliseconds that extends from 1 ms to
a maximum of 4:39:37.215 (hr:min:sec).
•
•
•
The free running frequency tuning word register
The output of the digital loop filter
The output of the tuning word history processor
Rev. 0 | Page 35 of 112
AD9548
Note that history accumulation timer = 0 should not be
programmed because it may cause improper device operation.
The control logic performs a calculation of the average tuning
word during the TAVG interval and stores the result in the
holdover history register (Address 0D14 to Address 0D19).
Computation of the average for each TAVG interval is
independent of the previous interval (that is, the average is a
memoryless average as opposed to a true moving average). In
addition, at the end of each TAVG interval, the device generates
an internal strobe pulse. The strobe pulse sets the history
updated bit in the IRQ monitor register (assuming the bit is
enabled via the IRQ mask register). Furthermore, the strobe
pulse is available as an output signal via the multifunction pins
(see the Multifunction Pins (M0 to M7) section).
History accumulation begins whenever the device switches to a
new reference. By default, the device clears any previous history
when it switches to a new reference. Furthermore, the user can
clear the tuning word history under software control via
Register 0A03, Bit 2, or under hardware control via the
multifunction pins (see the Multifunction Pins (M0 to M7)
section). However, the user has the option of programming the
device to retain (rather than clear) the old history by setting the
persistent history bit (Register 031B, Bit 3).
Whenever the tuning word history is nonexistent (that is, after a
power-up, reset, or switchover to a new reference with the
persistent history bit cleared), the device waits for the history
accumulation timer (TAVG) to expire before storing the first
history value in the holdover history register.
In cases where TAVG is quite large (4½ hours, for example), a
problem arises in that the first averaged result does not become
available until the full TAVG interval passes. Thus, it is possible
that as much as 4½ hours can elapse before the first averaged
result is available. If the device has to switch to holdover mode
during this time, a tuning word history is not available.
To alleviate this problem, the user has access to the incremental
average bits in the history mode register (Register 031B,
Bits[2:0]). If the history has been cleared, then this 3-bit value,
K (0 ≤ K ≤ 7), specifies the number of intermediate averages to
take during the first, and only the first, TAVG interval. When
K = 0, no intermediate averages are calculated; therefore, the
first average occurs after interval TAVG (the default operating
mode). However, if K = 4, for example, four intermediate
averages are taken during the first TAVG interval.
These average computations occur at TAVG/16, TAVG/8, TAVG/4,
TAVG/2, and TAVG (notice that the denominator exhibits a
sequence of powers of 2 beginning with TAVG/2K). The calculation of intermediate averages occurs only during the first
TAVG interval. All subsequent average computations occur at
evenly spaced intervals of TAVG.
LOOP CONTROL STATE MACHINE
The loop control state machine is responsible for monitoring,
initiating, and sequencing changes to the DPLL loop. Generally,
it automatically controls the transition between input references
and the entry and exit of holdover mode. In controlling loop
state changes, the state machine also arbitrates the application
of new loop filter coefficients, divider settings, and phase
detector offsets based on the profile settings. The user can
manually force the device into holdover or free-run mode via
the loop mode register (Address 0A01), as well as force the
selection of a specific input reference.
Switchover
Switchover occurs when the loop controller switches directly
from one input reference to another. Functionally, the AD9548
handles a reference switchover by briefly entering holdover
mode and then immediately recovering. During the switchover
event, however, the AD9548 preserves the status of the lock
detectors to avoid phantom unlock indications.
Holdover
The holdover state of the DPLL is an open-loop operating
mode. That is, the device no longer operates as a closed-loop
system. Instead, the output frequency remains constant and is
dependent on the device programming and availability of
tuning word history.
If a tuning word history exists (see the Frequency Tuning Word
History section), then the holdover frequency is the average
frequency just prior to entering the holdover state. If there is no
tuning word history, then the holdover frequency depends on
the state of the single sample fallback bit in the history mode
register (Register 031B, Bit 4). If the single sample fallback bit is
Logic 0, then the holdover frequency is the frequency defined in
the free running frequency tuning word register (Address 0300
to Address 0305). If the single sample fallback bit is Logic 1, then
the holdover frequency is the last instantaneous frequency output
by the DDS just prior to the device entering holdover mode
(note that this is not the average frequency prior to holdover).
The initial holdover frequency accuracy depends on the loop
bandwidth of the DPLL and the time elapsed to compute a
tuning word history. The longer the historical average, the more
accurate the initial holdover frequency (assuming a drift-free
system clock). Furthermore, the stability of the system clock
establishes the stability and long-term accuracy of the holdover
output frequency. Another consideration is the 48-bit frequency
tuning resolution of the DDS and its relationship to fractional
frequency error, ΔfO/fO, as follows:
f
Δf O
= 49 S
fO
2 fO
where, fS is the sample rate of the output DAC, and fO is the DDS
output frequency.
Rev. 0 | Page 36 of 112
AD9548
The worst-case scenario is maximum fS (1 GHz) and minimum fO
(62.5 MHz), which yields ΔfO/fO = 2.8 × 10−14, less than one part
in 10 trillion.
Recovery from Holdover
When in holdover and a valid reference becomes available, the
device exits holdover operation. The loop state machine restores
the DPLL to closed-loop operation, locks to the selected
reference, and sequences the recovery of all the loop parameters
based on the profile settings for the active reference.
Note that, if the user holdover bit (Register 0A01, Bit 6) is set,
the device does not automatically exit holdover when a valid
reference is available. However, automatic recovery can occur
after clearing the user holdover bit.
SYSTEM CLOCK INPUTS
Functional Description
The system clock circuit provides a low jitter, stable, high
frequency clock for use by the rest of the chip. The user has the
option of directly driving the SYSCLKx inputs with a high
frequency clock source at the desired system clock rate.
Alternatively, the SYSCLKx input can be configured to operate
in conjunction with the internal SYSCLK PLL. The SYSCLK
PLL can synthesize the system clock by means of a crystal
resonator connected across the SYSCLKx input pins or by
means of direct application of a low frequency clock source.
The SYSCLKx inputs are internally biased to a dc level of ~1 V.
Take care to ensure that any external connections do not disturb
the dc bias because this may significantly degrade performance.
Generally, the recommendation is that the SYSCLKx inputs be
ac-coupled to the signal source (except when using a crystal
resonator).
LF
SYSCLKN 52
System Clock Period
Many of the user-programmable parameters of the AD9548 have
absolute time units. To make this possible, the AD9548 requires
a priori knowledge of the period of the system clock. To accommodate this requirement, the user programs the 21-bit nominal
system clock period in the nominal SYSCLK period register
(Address 0106 to Address 0108). The contents of this register
reflect the actual period of the system clock in femtoseconds.
The user must properly program this register to ensure proper
operation of the device because many of its subsystems rely on
this value.
System Clock Details
A block diagram of the system clock appears in Figure 45. The
signal at the SYSCLKx input pins becomes the internally
buffered DAC sampling clock (fS) via one of three paths.
•
•
•
High frequency direct (HF)
Low frequency synthesized (LF)
Crystal resonator synthesized (XTAL)
Note that both the LF and XTAL paths require the use of the
SYSCLK PLL (see the SYSCLK PLL Multiplier section).
The main purpose of the HF path is to allow the direct use of a
high frequency (500 MHz to 1 GHz) external clock source for
clocking the AD9548. This path is optimized for high frequency
and low noise floor. Note that the HF input also provides a path
to SYSCLK PLL (see the SYSCLK PLL Multiplier section),
which includes an input divider (M) programmable for divideby -1, -2, -4, or -8. The purpose of the divider is to limit the
frequency at the input to the PLL to less than 150 MHz (the
maximum PFD rate).
SYSCLK_VREG
SYSCLK_LF
48
49
2×
LOCK
DETECT
÷M
PFD
AND
CHARGE
PUMP
XTAL
SYSCLKP 53
VCO
CALIBRATION
LOOP
FILTER
÷N
SYSTEM
CLOCK
08022-020
HF
Figure 45. System Clock Block Diagram
Rev. 0 | Page 37 of 112
AD9548
The LF path permits the user to provide an LVPECL, LVDS,
CMOS, or sinusoidal low frequency clock for multiplication by
the integrated SYSCLK PLL. The LF path handles input
frequencies from 3.5 MHz up to 100 MHz. However, when
using a sinusoidal input signal, it is best to use a frequency in
excess of 20 MHz. Otherwise, the resulting low slew rate can
lead to substandard noise performance. Note that the LF path
includes an optional 2× frequency multiplier to double the rate
at the input to the SYSCLK PLL and potentially reduce the PLL
in-band noise. However, to avoid exceeding the maximum PFD
rate of 150 MHz, using the 2× frequency multiplier is valid only
for input frequencies below 125 MHz.
The XTAL path enables the connection of a crystal resonator
(typically 10 MHz to 50 MHz) across the SYSCLKx input pins.
An internal amplifier provides the negative resistance required
to induce oscillation. The internal amplifier expects a 3.2 mm ×
2.5 mm AT cut, fundamental mode crystal with a maximum
motional resistance of 100 Ω. The following crystals, listed in
alphabetical order, may meet these criteria. Note that, whereas
these crystals may meet the preceding criteria according to their
data sheets, Analog Devices, Inc., does not guarantee their
operation with the AD9548 nor does Analog Devices endorse
one crystal manufacturer/supplier over another.
AVX/Kyocera CX3225SB
ECS ECX-32
Epson/Toyocom TSX-3225
Fox FX3225BS
NDK NX3225SA
Siward SX-3225
SYSCLK PLL MULTIPLIER
The SYSCLK PLL multiplier is an integer-N design and relies on
an integrated LC tank and VCO. It provides a means to convert
a low frequency clock input to the desired system clock
frequency, fS (900 MHz to 1 GHz). The SYSCLK PLL multiplier
accepts input signals between 3.5 MHz and 500 MHz, but
frequencies in excess of 150 MHz require the M-divider to
ensure compliance with the maximum PFD rate (150 MHz).
The PLL contains a feedback divider (N) that is programmable
for divide values between 6 and 255. The nominal VCO gain is
70 MHz/V.
Lock Detector
The SYSCLK PLL phase detector operates at the PFD rate,
which is fVCO/N. Each PFD sample indicates whether the
reference and feedback signals are phase aligned (within a
certain threshold range).
While the PLL is in the process of acquiring a lock condition,
the PFD samples typically consist of an arbitrary sequence of
in-phase and out-of-phase indications. As the PLL approaches
complete phase lock, the number of consecutive in-phase PFD
samples grows larger. Thus, one way of indicating a locked
condition is to count the number of consecutive in-phase PFD
samples and if it exceeds a certain value, then declare the PLL
locked.
This is exactly the role of the lock detect divider bits. When the
lock detector is enabled (Register 0100, Bit 2 = 0), the lock detect
divider bits determine the number of consecutive in-phase
decisions required (128, 256, 512, or 1024) before the lock
detector declares a locked condition. The default setting is 128.
Charge Pump
The charge pump operates in either automatic or manual mode
based on the charge pump mode bit (Register 0100, Bit 6).
When Register 0100, Bit 6 = 0, the AD9548 automatically
selects the appropriate charge pump current based on the
N-divider value. Note that the user cannot control the charge
pump current bits (Register 0100, Bits[5:3]) in automatic mode.
When Register 0100, Bit 6 = 1, the user determines the charge
pump current via the charge pump current bits (Register 0100,
Bits[5:3]). The charge pump current varies from 125 μA to 1
mA in 125 μA steps. The default setting is 500 μA.
SYSCLK PLL Loop Filter
The AD9548 has an internal second order loop filter that establishes the loop dynamics for input signals between 12.5 MHz
and 100 MHz. By default, the device uses the internal loop filter.
However, an external loop filter option is available by setting the
external loop filter enable bit (Register 0100, Bit 7). This
bypasses the internal loop filter and allows the device to use an
externally connected second order loop filter, as shown in
Figure 46.
AD9548
The SYSCLK PLL has a built-in lock detector. Register 0100,
Bit 2 determines whether the lock detector is active. When
active (default), the user controls the sensitivity of the lock
detector via the lock detect divider bits (Register 0100, Bits[1:0]).
SYSCLK_VREG
SYSCLK_LF
48
49
R1
C1
C2
08022-021
•
•
•
•
•
•
Note that 0 must be written to the system clock stability timer
(Register 0106 to Register 0108) whenever the lock detector is
disabled (Register 0100, Bit 2 = 1).
Figure 46. External Loop Filter Schematic
Rev. 0 | Page 38 of 112
AD9548
To determine the external loop filter components, the user
decides on the desired open loop bandwidth (fOL) and phase
margin (φ). These parameters allow calculation of the loop filter
components, as follows:
C1 =
I CP KVCO tan(φ)
2
2 N (πfOL )
C2 =
I CP KVCO ⎛ 1 − sin (φ ) ⎞
⎟
⎜
2
N (2πf OL ) ⎜⎝ cos(φ ) ⎟⎠
CLOCK DISTRIBUTION
where KVCO = 7 × 107 V/ns (typical), ICP is the programmed
charge pump current (amperes), N is the programmed feedback
divider value, fOL is the desired open-loop bandwidth (in hertz),
and Φ is the desired phase margin (in radians).
The clock distribution block of the AD9548 provides an
integrated solution for generating multiple clock outputs based
on frequency dividing the DPLL output. The distribution
output consists of four channels (OUT0 to OUT3). Each of the
four output channels has a dedicated divider and output driver,
as appears in Figure 47.
CLKINP
CLKINN
For example, assuming that N = 40, ICP = 0.5 mA, fOL = 400 kHz,
and Φ = 50°, then the loop filter calculations yield R1 = 3.31
kΩ, C1 = 330 pF, and C2 = 50.4 pF.
SYNC
CONTROL
ENABLE
System Clock Stability Timer
4
The system clock stability timer (Register 0106 to Register 0108) is
a 20-bit value programmed in milliseconds. If the programmed
timer value is 0, then the timer immediately indicates that it has
timed out. If the programmed timer value is a nonzero value
and the SYSCLK PLL is enabled, then the timer starts timing
when the SYSCLK PLL lock detector indicates lock and times
out after the prescribed period. However, when the user
disables the SYSCLK PLL, then the timer ignores the SYSCLK
PLL lock detector and starts timing as soon as the SYSCLK PLL
is disabled. The user can monitor the status of the stability timer
via Register 0D01, Bit 4, via the multifunction pins or via the
IRQ pin.
Note that the system clock stability timer must be programmed
before the SYSCLK PLL is either activated or disabled.
SYSCLK PLL Calibration
When using the SYSCLK PLL, it is necessary to calibrate the LC
VCO to ensure that the PLL can remain locked to the system
clock input signal. Assuming the presence of either an external
SYSCLK input signal or a crystal resonator, the calibration
process executes after the user sets and then clears the calibrate
system clock bit in the cal/sync register (Register 0A02, Bit 0).
During the calibration process, the device calibrates the VCO
amplitude and frequency. The status of the system clock calibration process is user accessible via the system clock register
(Register 0D01, Bit 1). It is also available via the IRQ monitor
register (Register 0D02, Bit 1) provided the status bit is enabled
via the IRQ mask register.
When the calibration sequence is complete, the SYSCLK PLL
eventually attains a lock condition, at which point the system
clock stability timer begins its countdown sequence. Expiration
SYNC SOURCE
ENABLE n/MODEn
4
4
Q0
OUT_RSET
OUT0P
OUT0N
OUT0
OUT1
OUT1P
OUT1N
OUT2
OUT2P
OUT2N
OUT3
OUT3P
OUT3N
08022-022
1 ⎞
πNfOL ⎛
⎜1 +
⎟
I CP KVCO ⎜⎝ sin (φ ) ⎟⎠
Note that the monitors/detectors associated with the input
references (REFA/AA – REFD/DD) are internally disabled until
the SYSCLK PLL indicates that it is stable.
RESET
R1 =
of the timer indicates that the SYSCLK PLL is stable, which is
reflected in the system clock register (Register 0D01, Bit 4).
Figure 47. Clock Distribution
Clock Input (CLKINx)
The clock input handles input signals from a variety of logic
families (assuming proper terminations and sufficient voltage
swing). It also handles sine wave input signals such as those
delivered by the DAC reconstruction filter. Its default operating
frequency range is 62.5 MHz to 500 MHz.
Super-Nyquist Operation
Typically, the maximum usable frequency at the DAC output is
about 45% of the system clock frequency. However, because it is
a sampled DAC, its output spectrum contains Nyquist images.
Of particular interest are the images appearing in the first Nyquist
zone (50% to 100% of the system clock frequency). SuperNyquist operation takes advantage of these higher frequencies,
but this implies that the CLKINx input operates in excess of
500 MHz, which is outside of its default operating limits.
The CLKINx receiver actually consists of two separate receivers:
the default receiver and an optional high frequency receiver,
Rev. 0 | Page 39 of 112
AD9548
which handles input signals up to 800 MHz. To select the high
frequency receiver, write a Logic 1 to Register 0400, Bit 4.
•
Super-Nyquist operation requires a band-pass filter at the DAC
output instead of the usual low-pass reconstruction filter.
Super-Nyquist operation is viable as long as the image
frequency does not exceed the 800 MHz input range of the
receiver. Furthermore, to provide acceptable jitter performance,
which is a consideration for image signals with low amplitude,
the signal at the CLKINx input must meet the minimum slew
rate requirements.
Output Enable
The output clock distribution dividers are referred to as Q0 to
Q3, corresponding to the OUT0 to OUT3 output channels,
respectively. Each divider is programmable with 30 bits of
division depth. The actual divider ratio is one more than the
programmed register value; therefore, a register value of 3, for
example, results in a divide ratio of 4. Thus, each divider offers a
range of divide ratios from 1 to 230 (1 to 1,073,741,824).
With an even divide ratio, the output signal always exhibits a
50% duty cycle. When the clock divider is bypassed (a divide
ratio of 1), the output duty cycle is the same as the input duty
cycle. Odd output divide ratios (excluding 1) exhibit automatic
duty cycle correction given by
The user has independent control of the operating mode of
each of the four output channels via the distribution channel
modes register (Address 0404 to Address 0407). The operating
mode control includes
•
•
•
Logic family and pin functionality
Output drive strength
Output polarity
The three least significant bits of each of the four distribution
channel mode registers comprise the mode bits. The mode
value selects the desired logic family and pin functionality of an
output channel, as given in Table 23.
Table 23. Output Channel Logic Family and Pin
Functionality
N + 2 X −1
2N
where N (which must be an odd number) is the divide ratio and
X is the normalized fraction of the high portion of the input
period (that is, 0 < X < 1).
For example, if N = 5 and the input duty cycle is 20% (X = 0.2),
then the output duty cycle is 44%. Note that, when the user
programs an output as noninverting, then the device adjusts the
falling edge timing to accomplish the duty cycle correction.
Conversely, the device adjusts the rising edge timing for an
inverted output.
Output Power-Down
Each of the output channels offers independent control of
power-down functionality via the distribution settings register
(Address 0400). Each output channel has a dedicated powerdown bit for powering down the output driver. However, if all
four outputs are powered down, the entire distribution output
enters a deep sleep mode.
Even though each channel has a channel power-down control
signal, it may sometimes be desirable to power down an output
driver while maintaining the divider’s synchronization with the
other channel dividers. This is accomplished by either of the
following methods:
•
Each of the output channels offers independent control of enable/
disable functionality via the distribution enable register
(Address 0401). The distribution outputs use synchronization
logic to control enable/disable activity to avoid the production
of runt pulses and ensure that outputs with the same divide
ratios become active/inactive in unison.
Output Mode
Clock Dividers
Output Duty Cycle =
In LVDS/LVPECL mode, place the output in tristate mode
(this works in CMOS mode as well).
In CMOS mode, use the divider output enable control bit
to stall an output. This provides power savings while
maintaining dc drive at the output.
Mode Bits [2:0]
000
001
010
011
100
101
110
111
Logic Family and Pin Functionality
CMOS (both pins)
CMOS (positive pin); tristate (negative pin)
Tristate (positive pin); CMOS (negative pin)
Tristate (both pins)
LVDS
LVPECL
Unused
Unused
Regardless of the selected logic family, each is capable of dc
operation. However, the upper frequency is limited by the load
conditions, drive strength, and impedance matching inherent in
each logic family. Practical limitations set the maximum CMOS
frequency to approximately 250 MHz, whereas LVPECL and
LVDS are capable of 725 MHz.
In addition to the three mode bits, each of the four distribution
channel mode registers includes the following control bits:
•
•
•
Polarity invert
CMOS phase invert
Drive strength
The polarity invert bit enables the user to choose between
normal polarity and inverted polarity. Normal polarity is the
default state. Inverted polarity reverses the representation of
Logic 0 and Logic 1 regardless of the logic family.
The CMOS phase invert bit applies only when the mode bits
select the CMOS logic family. In CMOS mode, both output pins
Rev. 0 | Page 40 of 112
AD9548
of the channel have a dedicated CMOS driver. By default, both
drivers deliver identical signals. However, setting the CMOS
phase invert bit causes the signal on an OUTxN pin to be the
opposite of the signal appearing on the OUTxP pin.
The drive strength bit allows the user to control whether the
output uses weak (0) or strong (1) drive capability (applies to
CMOS and LVDS but not LVPECL). For the CMOS family, the
strong setting implies normal CMOS drive capability, whereas
the weak setting implies low capacitive loading and allows for
reduced EMI. For the LVDS family, the weak setting provides
3.5 mA drive current for standard LVDS operation, whereas the
strong setting provides 7 mA for double terminated or double
voltage LVDS operation. Note that 3.5 mA and 7 mA are the
nominal drive current values when using the internal current
setting resistor.
Output Current Control with an External Resistor
By default, the output drivers have an internal current setting
resistor (3.12 kΩ nominal) that establishes the nominal drive
current for the LVDS and LVPECL operating modes. Instead of
using the internal resistor, the user can set the external
distribution resistor bit (Register 0400, Bit 5) and connect an
external resistor to the OUT_RSET pin. Note that this feature
supports an external resistor value of 3.12 kΩ only, allowing for
tighter control of the output current than is possible by using
the internal current setting resistor. However, if the user elects
to use a nonstandard external resistance, the following
equations provide the output drive current as a function of the
external resistance (R):
I LVDS 0 =
10.8325
R
I LVDS1 =
21.665
R
I LVPECL =
24.76
R
Clock Distribution Synchronization
A block diagram of the distribution synchronization
functionality appears in Figure 48. The synchronization
sequence begins with the primary synchronization signal,
which ultimately results in delivery of a synchronization strobe
to the clock distribution logic.
As indicated, the primary synchronization signal originates
from four possible sources.
•
•
•
•
Direct sync source via the sync distribution bit (Register
0A02, Bit 1)
Automatic sync source based on frequency or phase lock
detection as controlled via the automatic synchronization
register (Address 0403)
Multifunction pin sync source via one of the multifunction
pins (M0 to M7)
EEPROM sync source via the EEPROM
All four sources of the primary synchronization signal are logic
OR’d, so any one of them can synchronize the clock distribution
output at any time. When using the multifunction pins, the
synchronization event is the falling edge of the selected signal.
When using the sync distribution bit, the user sets and then
clears the bit. The synchronization event is the clearing
operation; that is, the Logic 1 to Logic 0 transition of the bit.
The primary synchronization signal can synchronize the distribution output directly or it can enable a secondary synchronization
signal. This functionality depends on the two sync source bits in
the distribution synchronization register (Register 0402, Bits[5:4]).
When sync source = 00 (direct), the falling edge of the primary
synchronization signal synchronizes the distribution output
directly.
When sync source = 01, the rising edge of the primary synchronization signal triggers the circuitry that detects a rising edge
of the active input reference. The detection of the rising edge is
what synchronizes the distribution output.
The numeric subscript associated with the LVDS output current
corresponds to the logic state of the drive strength bit in the
distribution channel modes register (Address 0404 to Address
0407). For R = 3.12 kΩ, the equations yield ILVDS0 = 3.5 mA,
ILVDS1 = 7.0 mA, and ILVPECL = 8.0 mA. Note that the device
maintains a constant 1.238 V (nominal) across the external
resistor.
When sync source = 10, the rising edge of the primary synchronization signal triggers the circuitry that detects a rollover of
the DDS accumulator (after processing by the DPLL feedback
divider). This corresponds to the zero crossing of the output of
the phase-to-amplitude converter in the DDS (less the openloop phase offset stored in Register 030D to Register 030E). The
detection of the DPLL feedback edge is what synchronizes the
distribution output.
Rev. 0 | Page 41 of 112
AD9548
Active Reference Synchronization (Zero Delay)
Active reference synchronization is the term applied to the case
when sync source = 01 (Register 0402, Bits[5:4]). Referring to
Figure 48, this means that the active reference sync path is
active because Bit 4 = 1, enabling the lower AND gate and
disabling the upper AND gate. The edge detector in the active
reference sync block monitors the rising edges of the active
reference (the mux selects the active reference automatically).
The edge detector is armed via the primary synchronization
signal, which is one of the four inputs to the OR gate (typically
the direct sync source). As soon as the edge detector is armed,
its output goes high, which stalls the output dividers in the
clock distribution block. Furthermore, once armed, a rising
edge from the active reference forces the output of the edge
detector low. This restarts the output dividers, thereby
synchronizing the clock distribution block.
The term zero delay applies because it provides a means to edge
align the output signal with the active input reference signal.
Typically, zero-delay architectures use the output signal in the
REGISTER
0402[5]
PRIMARY
SYNCHRONIZATION
SIGNAL
DIRECT SYNC
AUTOMATIC SYNC
SOURCE
(REGISTER 0403)
EEPROM SYNC
SOURCE
TO MULTIFUNCTION
PIN STATUS LOGIC
0
TO CLOCK
DISTRIBUTION
SYNCHRONIZATION
CONTROL
1
EDGE
DETECT
MULTIFUNCTION PIN
SYNC SOURCE
The fact that an active reference edge triggers the falling edge of
the synchronization pulse means that the falling edge is
asynchronous to the signal that clocks the distribution output
dividers (CLKINx). Therefore, the output clock distribution
logic reclocks the internal synchronization pulse to synchronize
it with the CLKINx signal. This means that the output dividers
restart after a deterministic delay associated with the reclocking
circuitry. This deterministic delay has two components. The
first deterministic delay component is four or five periods of the
CLKINx signal. The one period uncertainty is due to the
unknown position of the asynchronous reference clock edge
relative to the CLKINx signal. The second deterministic delay
component is one output period of the distribution divider.
DPLL
FEEDBACK
EDGE
ARM
STALL
DIVIDERS
SYNC OUTPUT
DISTRIBUTION
EDGE
DETECT
SYSCLK/4
DPLL EDGE SYNC
REGISTER
0402[4]
RESET
ARM
REF A
REF AA
EDGE
DETECT
REF D
REF DD
ACTIVE REFERENCE SYNC
Figure 48. Output Synchronization Block Diagram
Rev. 0 | Page 42 of 112
08022-023
DIRECT SYNC
SOURCE
(REGISTER 0A02[1])
feedback loop of a PLL to track input/output edge alignment.
Active reference synchronization, however, operates open loop.
That is, synchronization of the output via the distribution
synchronization logic occurs on a single edge of the active
reference.
AD9548
The deterministic delay, expressed as tLATENCY in the following
equation is a function of the frequency division factor (Qn) of
the channel divider associated with the zero-delay channel.
tLATENCY = (Qn + 4) × tCLK_IN
or
tLATENCY = (Qn + 5) × tCLK_IN
In addition to deterministic delay, there is random delay (tPROP)
associated with the propagation of the reference signal through
the input reference receiver, as well as the propagation of the
clock signal through the clock distribution logic. The total delay is
tDELAY = tLATENCY + tPROP
The user can compensate for tDELAY by using the phase offset
controls of the device to move the edge timing of the
distribution output signal relative to the input reference edge.
One method is to use the open-loop phase offset registers
(Address 030D to Address 030E) for timing adjustment.
However, be sure to use sufficiently small phase increments to
make the adjustment. Too large a phase step can result in the
clock distribution logic missing a CLKINx edge, thus ruining the
edge alignment process. The appropriate phase increment
depends on the transient response of any external circuitry
connected between the DACOUTx and CLKINx pins.
To guarantee synchronization of the output dividers, it is
important to make any edge timing adjustments after the
synchronization event. Furthermore, when making timing
adjustments, the distribution outputs can be disabled and then
enabled after the adjustment is complete. This prevents the
device from generating output clock signals during the timing
adjustment process.
Note that the form of zero-delay synchronization described here
does not track propagation time variations within the distribution
clock input path or the reference input path (on or off chip)
over temperature, supply, and so on. It is strictly a one-time
synchronization event.
Synchronization Mask
Each output channel has dedicated synchronization mask bits
(Register 0402, Bits[3:0]). When the mask bit associated with a
particular channel is set, then that channel does not respond to
the synchronization signal. This allows the device to operate
with the masked channels active and the unmasked channels
stalled while they wait for a synchronization pulse.
The other method is to use the closed-loop phase offset registers
(Address 030F to Address 0315) for timing adjustment.
However, be sure to use a sufficiently small phase vs. time profile.
Changing the phase too quickly can cause the DPLL to lose
lock, thus ruining the edge alignment process. Note that the
AD9548 phase slew limit register (Address 0316 to Address 0317)
can be used to limit the rate of change of phase automatically,
thereby mitigating the potential loss-of-lock problem.
Rev. 0 | Page 43 of 112
AD9548
STATUS AND CONTROL
MULTIFUNCTION PINS (M0 TO M7)
The AD9548 has eight digital CMOS I/O pins (M0 to M7) that
are configurable for a variety of uses. The function of these pins
is programmable via the register map. Each pin can control or
monitor an assortment of internal functions based on the contents
of Register 0200 to Register 0207. To monitor an internal function
with a multifunction pin, write a Logic 1 to the most significant
bit of the register associated with the desired multifunction pin.
The value of the seven least significant bits of the register defines
the control function, as shown in Table 24.
Table 24. Multifunction Pin Output Functions, Register 0200
to Register 0207 (Bit 7 = 1)
Bits[6:0]
Value
0
1
2
3
4
5
6
7
8
9
10
11
12 to 15
16
17
18
19
20
21
22
23
24
25
26
27 to 31
32
33
Output Function
Static Logic 0
Static Logic 1
System clock divided
by 32
Watchdog timer
output
EEPROM upload in
progress
EEPROM download in
progress
EEPROM fault detected
SYSCLK PLL lock
detected
SYSCLK PLL calibration
in progress
Unused
Unused
SYSCLK PLL stable
Unused
DPLL free running
DPLL active
DPLL in holdover
DPLL in reference
switchover
Active reference: phase
master
DPLL phase locked
DPLL frequency locked
DPLL phase slew
limited
DPLL frequency
clamped
Tuning word history
available
Tuning word history
updated
Unused
Reference A fault
Reference AA fault
Source Proxy
Bits[6:0]
Value
34
35
36
37
38
39
40 to 47
48
49
50
51
52
53
54
55
56 to 63
64
65
Register 0D00, Bit 0
66
Register 0D00, Bit 1
67
Register 0D00, Bit 2
Register 0D01, Bit 0
68
Register 0D01, Bit 1
69
70
71
Register 0D01, Bit 4
Register 0D0A, Bit 0
Register 0D0A, Bit 1
Register 0D0A, Bit 2
Register 0D0A, Bit 3
Register 0D0A, Bit 6
Register 0D0A, Bit 4
Register 0D0A, Bit 5
Register 0D0A, Bit 7
Register 0D0B, Bit 7
Register 0D0B, Bit 6
Register 0D05, Bit 4
Register 0D0C, Bit 2
Register 0D0D, Bit 2
72 to 79
80
81 to 127
Output Function
Reference B fault
Reference BB fault
Reference C fault
Reference CC fault
Reference D fault
Reference DD fault
Unused
Reference A valid
Reference AA valid
Reference B valid
Reference BB valid
Reference C valid
Reference CC valid
Reference D valid
Reference DD valid
Unused
Reference A active
eference
Reference AA active
reference
Reference B active
reference
Reference BB active
reference
Reference C active
reference
Reference CC active
reference
Reference D active
reference
Reference DD active
reference
Unused
Clock distribution sync
pulse
Unused
Source Proxy
Register 0D0E, Bit 2
Register 0D0F, Bit 2
Register 0D10, Bit 2
Register 0D11, Bit 2
Register 0D12, Bit 2
Register 0D13, Bit 2
Register 0D0C, Bit 3
Register 0D0D, Bit 3
Register 0D0E, Bit 3
Register 0D0F, Bit 3
Register 0D10, Bit 3
Register 0D11, Bit 3
Register 0D12, Bit 3
Register 0D13, Bit 3
Register 0D0B, Bits[2:0]
Register 0D0B, Bits[2:0]
Register 0D0B, Bits[2:0]
Register 0D0B, Bits[2:0]
Register 0D0B, Bits[2:0]
Register 0D0B, Bits[2:0]
Register 0D0B, Bits[2:0]
Register 0D0B, Bits[2:0]
Register 0D03, Bit 3
To control an internal function with a multifunction pin, write a
Logic 0 to the most significant bit of the register associated with
the desired multifunction pin. The monitored function depends
on the value of the seven least significant bits of the register, as
shown in Table 25.
Table 25. Multifunction Pin Input Functions, Register 0200
to Register 0207 (Bit 7 = 0)
Bits[6:0]
Value
0
1
2
3
4
Rev. 0 | Page 44 of 112
Output Function
Unused (default)
I/O update
Full power-down
Watchdog reset
IRQ reset
Destination Proxy
Register 0005, Bit 0
Register 0A00, Bit 0
Register 0A03, Bit 0
Register 0A03, Bit 1
AD9548
Bits[6:0]
Value
5
6 to 15
16
17
18
19
20
21 to 31
32
33
34
35
36
37
38
39
40 to 47
48
49
50
51
52
53
54
55
56 to 63
64
65
66
67
68
69
70 to 127
Output Function
Tuning word history reset
Unused
Holdover
Free run
Reset incremental phase
offset
Increment incremental
phase offset
Decrement incremental
phase offset
Unused
Override Reference
Monitor A
Override Reference
Monitor AA
Override Reference
Monitor B
Override Reference
Monitor BB
Override Reference
Monitor C
Override Reference
Monitor CC
Override Reference
Monitor D
Override Reference
Monitor DD
Unused
Force validation
Timeout A
Force validation
Timeout AA
Force validation
Timeout B
Force validation
Timeout BB
Force validation
Timeout C
Force validation
Timeout CC
Force validation
Timeout D
Force validation
Timeout DD
Unused
Enable OUT0
Enable OUT1
Enable OUT2
Enable OUT3
Enable OUT0, OUT1,
OUT2, OUT3
Sync clock distribution
outputs
Unused
Destination Proxy
Register 0A03, Bit 2
Register 0A01, Bit 6
Register 0A01, Bit 5
Register 0A0C, Bit 2
Register 0A0C, Bit 0
Register 0A0C, Bit 1
If more than one multifunction pin operates on the same
control signal, then internal priority logic ensures that only one
multifunction pin serves as the signal source. The selected pin is
the one with the lowest numeric suffix. For example, if both M3
and M7 operate on the same control signal, then M3 is used as
the signal source and the redundant pins are ignored.
At power-up, the multifunction pins can be used to force the
device into certain configurations as defined in the initial pin
programming section. This functionality, however, is valid only
during power-up or following a reset, after which the pins can
be reconfigured via the serial programming port or via the
EEPROM.
Register 0A0F, Bit 0
IRQ PIN
Register 0A0F, Bit 1
The AD9548 has a dedicated interrupt request (IRQ) pin. The
IRQ pin output mode register (Register 0208, Bits[1:0]) controls
how the IRQ pin asserts an interrupt based on the value of the
two bits, as follows:
Register 0A0F, Bit 2
Register 0A0F, Bit 3
Register 0A0F, Bit 4
Register 0A0F, Bit 5
Register 0A0F, Bit 6
Register 0A0F, Bit 7
Register 0A0E, Bit 0
Register 0A0E, Bit 1
Register 0A0E, Bit 2
Register 0A0E, Bit 3
Register 0A0E, Bit 4
Register 0A0E, Bit 5
Register 0A0E, Bit 6
Register 0A0E, Bit 7
Register 0401, Bit 0
Register 0401, Bit 1
Register 0401, Bit 2
Register 0401, Bit 3
Register 0401,
Bits[3:0]
Register 0A02, Bit 1
00—The IRQ pin is high impedance when deasserted and active
low when asserted and requires an external pull-up resistor
(this is the default operating mode).
01—The IRQ pin is high impedance when deasserted and active
high when asserted and requires an external pull-down
resistor.
10—The IRQ pin is Logic 0 when deasserted and Logic 1 when
asserted.
11—The IRQ pin is Logic 1 when deasserted and Logic 0 when
asserted.
The AD9548 asserts the IRQ pin whenever any of the bits in the
IRQ monitor register (Address 0D02 to Address 0D09) are
Logic 1. Each bit in this register is associated with an internal
function capable of producing an interrupt. Furthermore, each
bit of the IRQ monitor register is the result of a logical AND of
the associated internal interrupt signal and the corresponding
bit in the IRQ mask register (Address 0209 to Address 0210).
That is, the bits in the IRQ mask register have a one-to-one
correspondence with the bits in the IRQ monitor register.
Whenever an internal function produces an interrupt signal
and the associated IRQ mask bit is set, then the corresponding
bit in the IRQ monitor register is set. The user should be aware
that clearing a bit in the IRQ mask register removes only the
mask associated with the internal interrupt signal. It does not
clear the corresponding bit in the IRQ monitor register.
The IRQ pin is the result of a logical OR of all the IRQ monitor
register bits. Thus, the AD9548 asserts the IRQ pin so long as
any of the IRQ monitor register bits are Logic 1. Note that it is
possible to have multiple bits set in the IRQ monitor register.
Therefore, when the AD9548 asserts the IRQ pin, it may
indicate an interrupt from several different internal functions.
The IRQ monitor register provides the user with a means to
interrogate the AD9548 to determine which internal function(s)
produced the interrupt.
Rev. 0 | Page 45 of 112
AD9548
If enabled, the timer runs continuously and generates a timeout
event whenever the timeout period expires. The user has access
to the watchdog timer status via the IRQ mechanism and the
multifunction pins (M0 to M7). In the case of the multifunction
pins, the timeout event of the watchdog timer is a pulse that
lasts 32 system clock periods.
The EEPROM provides the ability to upload and download
configuration settings to and from the register map. Figure 49
shows a functional diagram of the EEPROM.
Register 0E10 to Register 0E3F represent a 48-byte scratch pad
that enables the user to store a sequence of instructions for
transferring data to the EEPROM from the device settings
portion of the register map. Note that the default values for
these registers provide a sample sequence for saving/retrieving
all of the AD9548 EEPROM-accessible registers. Figure 49
shows the connectivity between the EEPROM and the controller
that manages data transfer between the EEPROM and the
register map.
The controller oversees the process of transferring EEPROM data
to and from the register map. There are two modes of operation
handled by the controller: saving data to the EEPROM (upload
mode) or retrieving data from the EEPROM (download mode).
In either case, the controller relies on a specific instruction set.
DATA
M7
M6
M5
M4
M3
DEVICE
SETTINGS
ADDRESS
POINTER
There are two ways to reset the watchdog timer (thereby
preventing it from causing a timeout event). The first is by
writing a Logic 1 to the autoclearing reset watchdog bit in the
reset function register (Register 0A03, Bit 0). Alternatively, the
user can program any of the multifunction pins to reset the
watchdog timer. This allows the user to reset the timer by
means of a hardware pin rather than by a serial I/O port operation.
Rev. 0 | Page 46 of 112
EEPROM
ADDRESS
POINTER
EEPROM
CONTROLLER
DEVICE SETTINGS
(0100 TO 0A10)
EEPROM
(000 TO 7FF)
SCRATCH PAD
ADDRESS
POINTER
SCRATCH PAD
(0E10 TO 0E3F)
REGISTER MAP
SERIAL
INPUT/OUTPUT
PORT
Figure 49. EEPROM Functional Diagram
08022-024
The watchdog timer is a general-purpose programmable timer.
To set the timeout period, the user writes to the 16-bit
watchdog timer register (Address 0211 to Address 0212). A
value of 0 in this register disables the timer. A nonzero value
sets the timeout period in milliseconds, giving the watchdog
timer a range of 1 ms to 65.535 sec. The relative accuracy of the
timer is approximately 0.1% with an uncertainty of 0.5 ms.
The AD9548 contains an integrated 2048-byte, electrically
erasable, programmable read-only memory (EEPROM). The
AD9548 can be configured to perform a download at power-up
via the multifunction pins (M3 to M7), but uploads and downloads can also be done on demand via the EEPROM control
register (Address 0E00 to Address 0E03).
DATA
WATCHDOG TIMER
EEPROM Overview
CONDITION
(0E01 [4:0])
It is also possible to collectively clear all of the IRQ monitor
register bits by setting the reset all IRQs bit in the reset function
register (Register 0A03, Bit 1). Note that this is an autoclearing
bit. Setting this bit results in deassertion of the IRQ pin.
Alternatively, the user can program any of the multifunction
pins to clear all IRQs. This allows the user to clear all IRQs by
means of a hardware pin rather than by a serial I/O port operation.
EEPROM
DATA
Typically, when the AD9548 asserts the IRQ pin, the user
interrogates the IRQ monitor register to identify the source of
the interrupt request. After servicing an indicated interrupt, the
user should clear the associated IRQ monitor register bit via the
IRQ clearing register (Address 0A04 to Address 0A0B). The bits
in the IRQ clearing register have a one-to-one correspondence
with the bits in the IRQ monitor register. Note that the IRQ
clearing register is autoclearing. The IRQ pin remains asserted
until the user clears all of the bits in the IRQ monitor register
that indicate an interrupt.
AD9548
Table 26. EEPROM Controller Instruction Set
Instruction
Value (Hex)
00 to 7F
Instruction Type
Data
Bytes
Required
3
80
I/O update
1
A0
Calibrate
1
A1
Distribution sync
1
B0 to CF
Condition
1
FE
Pause
1
FF
End
1
Description
A data instruction tells the controller to transfer data to or from the device settings
part of the register map. A data instruction requires two additional bytes that
together indicate a starting address in the register map. Encoded in the data
instruction is the number of bytes to transfer, which is one more than the
instruction value.
When the controller encounters this instruction while downloading from the
EEPROM, it issues a soft I/O update (see Register 0005 in Table 41).
When the controller encounters this instruction while downloading from the
EEPROM, it initiates a system clock calibration sequence (see Register 0A02 in Table
120).
When the controller encounters this instruction while downloading from the
EEPROM, it issues a sync pulse to the output distribution synchronization (see
Register 0A02 in Table 120).
B1 to CF are condition instructions and correspond to Condition 1 through
Condition 31, respectively. B0 is the null condition instruction. See the EEPROM
Conditional Processing section for details.
When the controller encounters this instruction in the scratch pad while uploading
to the EEPROM, it resets the scratch pad address pointer and holds the EEPROM
address pointer at its last value. This allows storage of more than one instruction
sequence in the EEPROM. Note that the controller does not copy this instruction to
the EEPROM during upload.
When the controller encounters this instruction in the scratch pad while uploading
to the EEPROM, it resets both the scratch pad address pointer and the EEPROM
address pointer and then enters an idle state.
When the controller encounters this instruction while downloading from the
EEPROM, it resets the EEPROM address pointer and then enters an idle state.
EEPROM Instructions
Table 26 lists the EEPROM controller instruction set. The
controller recognizes all instruction types whether it is in
upload or download mode, except for the pause instruction,
which it only recognizes in upload mode.
The I/O update, calibrate, distribution sync, and end instructtions are mostly self-explanatory. The others, however, warrant
further detail, as described in the following paragraphs.
Data instructions are those that have a value from 00 to 7F. A
data instruction tells the controller to transfer data between
the EEPROM and the register map. The controller needs the
following two parameters to carry out the data transfer:
•
•
The number of bytes to transfer
The register map target address
The controller decodes the number of bytes to transfer directly
from the data instruction itself by adding one to the value of the
instruction. For example, the data instruction, 1A, has a decimal
value of 26; therefore, the controller knows to transfer 27 bytes
(one more than the value of the instruction). Whenever the
controller encounters a data instruction, it knows to read the
next two bytes in the scratch pad because these contain the
register map target address.
Note that, in the EEPROM scratch pad, the two registers that
comprise the address portion of a data instruction have the
MSB of the address in the D7 position of the lower register
address. The bit weight increases left to right, from the lower
register address to the higher register address. Furthermore, the
starting address always indicates the lowest numbered register
map address in the range of bytes to transfer. That is, the
controller always starts at the register map target address and
counts upward regardless of whether the serial I/O port is
operating in I2C, SPI LSB-first, or SPI MSB-first mode.
As part of the data transfer process during an EEPROM upload,
the controller calculates a 1-byte checksum and stores it as the
final byte of the data transfer. As part of the data transfer process
during an EEPROM download, however, the controller again
calculates a 1-byte checksum value but compares the newly
calculated checksum with the one that was stored during the
upload process. If an upload/download checksum pair does not
match, the controller sets the EEPROM fault status bit. If the
upload/download checksums match for all data instructions
encountered during a download sequence, the controller sets
the EEPROM complete status bit.
Condition instructions are those that have a value from B0 to
CF. Condition instructions B1 to CF represent Condition 1 to
Condition 31, respectively. The B0 condition instruction is
Rev. 0 | Page 47 of 112
AD9548
special because it represents the null condition (see the
EEPROM Conditional Processing section).
A pause instruction, like an end instruction, is stored at the end
of a sequence of instructions in the scratch pad. When the
controller encounters a pause instruction during an upload
sequence, it keeps the EEPROM address pointer at its last value.
This way the user can store a new instruction sequence in the
scratch pad and upload the new sequence to the EEPROM. The
new sequence is stored in the EEPROM address locations
immediately following the previously saved sequence. This
process is repeatable until an upload sequence contains an end
instruction. The pause instruction is also useful when used in
conjunction with condition processing. It allows the EEPROM
to contain multiple occurrences of the same register(s), with
each occurrence linked to a set of conditions (see the EEPROM
Conditional Processing section).
EEPROM Upload
To upload data to the EEPROM, the user must first ensure that
the write enable bit (Register 0E00, Bit 0) is set. Then, on setting
the autoclearing save to EEPROM bit (Register 0E02, Bit 0), the
controller initiates the EEPROM data storage process.
Uploading EEPROM data requires that the user first write an
instruction sequence into the scratch pad registers. During the
upload process, the controller reads the scratch pad data byte by
byte, starting at Register 0E10 and incrementing the scratch pad
address pointer as it goes until it reaches a pause or End
instruction.
As the controller reads the scratch pad data, it transfers the data
from the scratch pad to the EEPROM (byte by byte) and
increments the EEPROM address pointer accordingly, unless it
encounters a data instruction. A data instruction tells the
controller to transfer data from the device settings portion of
the register map to the EEPROM. The number of bytes to
transfer is encoded within the data instruction, and the starting
address for the transfer appears in the next two bytes in the
scratch pad.
When the controller encounters a data instruction, it stores the
instruction in the EEPROM, increments the EEPROM address
pointer, decodes the number of bytes to be transferred, and
increments the scratch pad address pointer. Then it retrieves the
next two bytes from the scratch pad (the target address) and
increments the scratch pad address pointer by 2. Next, the
controller transfers the specified number of bytes from the
register map (beginning at the target address) to the EEPROM.
When it completes the data transfer, the controller stores an
extra byte in the EEPROM to serve as a checksum for the
transferred block of data. To account for the checksum byte, the
controller increments the EEPROM address pointer by one
more than the number of bytes transferred. Note that, when the
controller transfers data associated with an active register, it
actually transfers the buffered contents of the register (see the
Buffered/Active Registers section for details on the difference
between buffered and active registers). This allows for the transfer
of nonzero autoclearing register contents.
Note that conditional processing (see the EEPROM Conditional
Processing section) does not occur during an upload sequence.
EEPROM Download
An EEPROM download results in data transfer from the
EEPROM to the device register map. To download data, the
user sets the autoclearing load from EEPROM bit (Register
0E03, Bit 1). This commands the controller to initiate the
EEPROM download process. During download, the controller
reads the EEPROM data byte by byte, incrementing the
EEPROM address pointer as it goes, until it reaches an end
instruction. As the controller reads the EEPROM data, it
executes the stored instructions, which includes transferring
stored data to the device settings portion of the register map
whenever it encounters a data instruction.
Note that conditional processing (see the EEPROM Conditional
Processing section) is only applicable when downloading.
Automatic EEPROM Download
Following a power-up, an assertion of the RESET pin, or a soft
reset (Register 0000, Bit 5 = 1), if FncInit[7:3] ≠ 0 (see the Initial
Pin Programming section), then the instruction sequence
stored in the EEPROM executes automatically with condition =
FncInit[7:3]. In this way, a previously stored set of register values
downloads automatically on power-up or with a hard or soft
reset. See the EEPROM Conditional Processing section for
details regarding conditional processing and the way it modifies
the download process.
EEPROM Conditional Processing
The condition instructions allow conditional execution of
EEPROM instructions during a download sequence. During
an upload sequence, however, they are stored as is and have
no effect on the upload process.
Note that, during EEPROM downloads, the condition instructions
themselves and the end instruction always execute unconditionally.
Conditional processing makes use of two elements: the condition
(from Condition 1 to Condition 31) and the condition tag
board. The relationships among the condition, the condition tag
board, and the EEPROM controller appear schematically in
Figure 50.
Rev. 0 | Page 48 of 112
AD9548
CONDITION
TAG BOARD
EXAMPLE
CONDITION 3 AND
CONDITION 13
ARE TAGGED
M7
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
IF INSTRUCTION = B0,
THEN CLEAR ALL TAGS
EEPROM
WATCH FOR
OCCURRENCE OF
CONDITION
INSTRUCTIONS
DURING
DOWNLOAD.
IF {0E01, BITS[4:0] ≠ 0}
CONDITION = 0E01, BITS[4:0]
ELSE
CONDITION = FncInit, BITS[7:3]
ENDIF
COND ITION
EXECUTE/SKIP
INSTRUCTION(S)
DOWNLOAD
PROCEDURE
IF {NO TAGS} OR {CONDITION = 0}
EXECUTE INSTRUCTIONS
ELSE
IF {CONDITION IS TAGGED}
EXECUTE INSTRUCTIONS
ELSE
SKIP INSTRUCTIONS
ENDIF
ENDIF
08022-025
UPLOAD
PROCEDURE
5
5
CONDITION
HANDLER
SCRATCH
PAD
FncInit, BITS[7:3]
5
IF B1 ≤ INSTRUCTION ≤ CF,
THEN TAG DECODED CONDITION
STORE CONDITION
INSTRUCTIONS AS
THEY ARE READ FROM
THE SCRATCH PAD.
REGISTER
0E01, BITS[4:0]
M3
EEPROM CONTROLLER
Figure 50. EEPROM Conditional Processing
The condition is a 5-bit value with 32 possibilities. Condition = 0
is the null condition. When the null condition is in effect, the
EEPROM controller executes all instructions unconditionally.
The remaining 31 possibilities, condition = 1 through condition
= 31, modify the EEPROM controller’s handling of a download
sequence. The condition originates from one of two sources
(see Figure 50), as follows:
•
•
FncInit, Bits[7:3], which is the state of the M3 to M7
multifunction pins at power-up (see the Initial Pin
Programming section)
Register 0E01, Bits[4:0]
If Register 0E01, Bits[4:0] ≠ 0, then the condition is the value
stored in Register 0E01, Bits[4:0]; otherwise, the condition is
FncInit, Bits[7:3]. Note that a nonzero condition present in
Register 0E01, Bits[4:0] takes precedence over FncInit, Bits[7:3].
The condition tag board is a table maintained by the EEPROM
controller. When the controller encounters a condition instructtion, it decodes the B1 through CF instructions as condition = 1
through condition = 31, respectively, and tags that particular
condition in the condition tag board. However, the B0
condition instruction decodes as the null condition, for which
the controller clears the condition tag board, and subsequent
download instructions execute unconditionally (until the
controller encounters a new condition instruction).
During download, the EEPROM controller executes or skips
instructions depending on the value of condition and the
contents of the condition tag board. Note, however, that
condition instructions and the end instruction always execute
unconditionally during download. If condition = 0, then all
instructions during download execute unconditionally. If
condition ≠ 0 and there are any tagged conditions in the
condition tag board, then the controller executes instructions
only if the condition is tagged. If the condition is not tagged,
then the controller skips instructions until it encounters a
condition instruction that decodes as a tagged condition. Note
that the condition tag board allows for multiple conditions to be
tagged at any given moment. This conditional processing
mechanism enables the user to have one download instruction
sequence with many possible outcomes depending on the value
of the condition and the order in which the controller
encounters condition instructions.
Table 27 lists a sample EEPROM download instruction sequence.
It illustrates the use of condition instructions and how they alter
the download sequence. The table begins with the assumption
that no conditions are in effect. That is, the most recently executed
condition instruction is B0 or no conditional instructions have
been processed.
Rev. 0 | Page 49 of 112
AD9548
Reprogram the device control registers for the next desired
setup. Then store a new upload sequence in the EEPROM
scratch pad with the following general form:
Table 27. EEPROM Conditional Processing Example
Instruction
0x08
0x01
0x00
0xB1
0x19
0x04
0x00
0xB2
0xB3
0x07
0x05
0x00
0x0A
0xB0
0x80
0x0A
Action
Transfer the system clock register contents
regardless of the current condition.
1.
2.
Tag Condition 1
Transfer the clock distribution register contents
only if condition = 1
Tag Condition 2
Tag Condition 3
Transfer the reference input register contents only
if condition = 1, 2, or 3
Calibrate the system clock only if condition = 1, 2,
or 3
Clear the condition tag board
Execute an I/O update regardless of the value of
the condition
Calibrate the system clock regardless of the value
of the condition
Storing Multiple Device Setups in EEPROM
Conditional processing makes it possible to create a number of
different device setups, store them in EEPROM, and download
a specific setup on demand. To do so, first program the device
control registers for a specific setup. Then, store an upload
sequence in the EEPROM scratch pad with the following
general form:
1.
2.
3.
Condition instruction (B1 to CF) to identify the setup with
a specific condition (1 to 31)
Data instructions (to save the register contents) along with
any required calibrate and/or I/O update instructions
Pause instruction (FE)
With the upload sequence written to the scratch pad, perform
an EEPROM upload (Register 0E02, Bit 0).
3.
4.
Condition instruction (B0)
The next desired condition instruction (B1 to CF, but
different than the one used during the previous upload to
identify a new setup)
Data instructions (to save the register contents) along with
any required calibrate and/or I/O update instructions
Pause instruction (FE)
With the upload sequence written to the scratch pad, perform
an EEPROM upload (Register 0E02, Bit 0).
Repeat the process of programming the device control registers
for a new setup, storing a new upload sequence in the EEPROM
scratch pad (Step 1 through Step 4), and executing an EEPROM
upload (Register 0E02, Bit 0) until all of the desired setups have
been uploaded to the EEPROM.
Note that, on the final upload sequence stored in the scratch
pad, the pause instruction (FE) must be replaced with an end
instruction (FF).
To download a specific setup on demand, first store the
condition associated with the desired setup in Register 0E01,
Bits[4:0]. Then perform an EEPROM download (Register 0E03,
Bit 1). Alternatively, to download a specific setup at power-up,
apply the required logic levels necessary to encode the desired
condition on the M3 to M7 multifunction pins. Then power up
the device; an automatic EEPROM download occurs. The
condition (as established by the M3 to M7 multifunction pins)
guides the download sequence and results in a specific setup.
Keep in mind that the number of setups that can be stored
in the EEPROM is limited. The EEPROM can hold a total of
2048 bytes. Each nondata instruction requires one byte of
storage. Each data instruction, however, requires N + 4 bytes of
storage, where N is the number of transferred register bytes and
the other four bytes include the data instruction itself (one
byte), the target address (two bytes), and the checksum
calculated by the EEPROM controller during the upload
sequence (one byte).
Rev. 0 | Page 50 of 112
AD9548
SERIAL CONTROL PORT
SCLK/SCL
CS/SDA
SDIO
SDO
13-BIT ADDRESS
SPACE
SPI
READ ONLY
REGION
2
IC
EEPROM
POWER-ON RESET
EEPROM
CONTROLLER
MULTIFUNCTION
PIN CONTROL
LOGIC
READ/WRITE
REGION
ANALOG BLOCKS AND
DIGITAL CORE
400kHz
M7
M6
M5
M4
M3
M2
M1
M0
08022-026
SERIAL CONTROL ARBITER
Figure 51. Serial Port Functional Diagram
The AD9548 serial control port is a flexible, synchronous serial
communications port that provides a convenient interface to
many industry-standard microcontrollers and microprocessors.
The AD9548 serial control port is compatible with most
synchronous transfer formats, including Philips I2C, Motorola
SPI, and Intel SSR protocols. The serial control port allows
read/write access to the AD9548 register map.
In SPI mode, single or multiple byte transfers are supported.
The SPI port configuration is programmable via Register 0000.
This register is integrated into the SPI control logic rather than
in the register map and is distinct from the I2C Register 0000. It
is also inaccessible to the EEPROM controller.
A functional diagram of the serial control port, including its
relationship to the EEPROM, appears in Figure 51.
Although the AD9548 supports both the SPI and I2C serial port
protocols, only one is active following power-up (as determined
by the multifunction pins, M0 to M2, during the startup
sequence). That is, the only way to change the serial port
protocol is to reset the device (or cycle the device power
supply). Both protocols use a common set of control pins as
shown in Figure 52.
2
AD9548
SDIO
3
SDO
4
SERIAL
CONTROL
PORT
CSB/SDA
5
Table 28. Serial Port Mode Selection
M2
0
0
0
0
1
1
1
1
M1
0
0
1
1
0
0
1
1
M0
0
1
0
1
0
1
0
1
Serial Port Mode
SPI
I²C (address = 1001001)
I²C (address = 1001010)
I²C (address = 1001011)
I²C (address = 1001100)
I²C (address = 1001101)
I²C (address = 1001110)
I²C (address = 1001111)
SPI SERIAL PORT OPERATION
Pin Descriptions
The SCLK (serial clock) pin serves as the serial shift clock. This
pin is an input. SCLK synchronizes serial control port read and
write operations. The rising edge SCLK registers write data bits,
and the falling edge registers read data bits. The SCLK pin
supports a maximum clock rate of 40 MHz.
The SDIO (serial data input/output) pin is a dual-purpose pin
and acts as either an input only (unidirectional mode) or as
both an input and an output (bidirectional mode). The AD9548
default SPI mode is bidirectional.
The SDO (serial data output) pin is useful only in
unidirectional I/O mode. It serves as the data output pin for
read operations.
08022-027
SCLK/SCL
settings based on the startup logic pattern on the M0 to M2 pins
(see Table 28). Note that the four MSBs of the slave address are
hardware coded as 1011.
Figure 52. Serial Control Port
SPI/I²C PORT SELECTION
Because the AD9548 supports both SPI and I2C protocols, the
active serial port protocol depends on the logic state of the three
multifunction pins, M0 to M2, at startup. If all three pins are set
to Logic 0 at startup, then the SPI protocol is active. Otherwise,
the I2C protocol is active with seven different I2C slave address
The CS (chip select) pin is an active low control that gates read
and write operations. This pin is internally connected to a 30 kΩ
pull-up resistor. When CS is high, the SDO and SDIO pins go
into a high impedance state.
SPI Mode Operation
The SPI port supports both 3-wire (bidirectional) and 4-wire
(unidirectional) hardware configurations and both MSB-first
and LSB-first data formats. Both the hardware configuration
Rev. 0 | Page 51 of 112
AD9548
and data format features are programmable. By default, the
AD9548 uses the bidirectional MSB-first mode. The reason that
bidirectional is the default mode is so that the user can still
write to the device, if it is wired for unidirectional operation, to
switch to unidirectional mode.
Assertion (active low) of the CS pin initiates a write or read
operation to the AD9548 SPI port. For data transfers of three
bytes or fewer (excluding the instruction word), the device
supports the CS stalled high mode (see Table 29). In this mode,
the CS pin can be temporarily deasserted on any byte boundary,
allowing time for the system controller to process the next byte.
CS can be deasserted only on byte boundaries, however. This
applies to both the instruction and data portions of the transfer.
During stall high periods, the serial control port state machine
enters a wait state until all data is sent. If the system controller
decides to abort a transfer midstream, then the state machine must
be reset by either completing the transfer or by asserting the CS
pin for at least one complete SCLK cycle (but less than eight
SCLK cycles). Deasserting the CS pin on a nonbyte boundary
terminates the serial transfer and flushes the buffer.
In the streaming mode (see Table 29), any number of data bytes
can be transferred in a continuous stream. The register address
is automatically incremented or decremented. CS must be
deasserted at the end of the last byte transferred, thereby ending
the stream mode.
Table 29. Byte Transfer Count
W1
0
0
1
1
W0
0
1
0
1
Bytes to Transfer
1
2
3
Streaming mode
CS is asserted. Deasserting the CS pin on a nonbyte boundary
resets the serial control port. Reserved or blank registers are not
skipped over automatically during a write sequence. Therefore,
the user must know what bit pattern to write to the reserved
registers to preserve proper operation of the part. Generally, it
does not matter what data is written to blank registers, but it is
customary to write 0s.
Most of the serial port registers are buffered (see the
Buffered/Active Registers section for details on the difference
between buffered and active registers). Therefore, data written
into buffered registers does not take effect immediately. An
additional operation is needed to transfer buffered serial control
port contents to the registers that actually control the device.
This is accomplished with an I/O update operation, which is
performed in one of two ways. One is by writing a Logic 1 to
Register 0005, Bit 0 (this bit is self-clearing). The other is to use
an external signal via an appropriately programmed
multifunction pin. The user can change as many register bits as
desired before executing an I/O update. The I/O update operation
transfers the buffer register contents to their active register
counterparts.
Read
The AD9548 supports the long instruction mode only. If the
instruction word indicates a read operation, the next N × 8
SCLK cycles clock out the data from the address specified in the
instruction word. N is the number of data bytes read and
depends on the W0 and W1 bits of the instruction word. The
readback data is valid on the falling edge of SCLK. Blank
registers are not skipped over during readback.
A readback operation takes data from either the serial control
port buffer registers or the active registers, as determined by
Register 0004, Bit 0.
Communication Cycle—Instruction Plus Data
SPI Instruction Word (16 Bits)
The SPI protocol consists of a two-part communication cycle.
The first part is a 16-bit instruction word that is coincident with
the first 16 SCLK rising edges and a payload. The instruction
word provides the AD9548 serial control port with information
regarding the payload. The instruction word includes the R/W
bit that indicates the direction of the payload transfer (that is, a
read or write operation). The instruction word also indicates
the number of bytes in the payload and the starting register
address of the first payload byte.
The MSB of the 16-bit instruction word is R/W, which indicates
whether the instruction is a read or a write. The next two bits,
W1 and W0, indicate the number of bytes in the transfer (see Table
29). The final 13 bits are the register address (A12 to A0), which
indicates the starting register address of the read/write
operation (see Table 31).
Write
If the instruction word indicates a write operation, the payload
is written into the serial control port buffer of the AD9548. Data
bits are registered on the rising edge of SCLK. The length of the
transfer (1, 2, or 3 bytes or streaming mode) depends on the W0
and W1 bits (see Table 29) in the instruction byte. When not
streaming, CS can be deasserted after each sequence of eight
bits to stall the bus (except after the last byte, where it ends the
cycle). When the bus is stalled, the serial transfer resumes when
SPI MSB-/LSB-First Transfers
The AD9548 instruction word and payload can be MSB first or
LSB first. The default for the AD9548 is MSB first. The LSB-first
mode can be set by writing a 1 to Register 0000, Bit 6. Immediately after the LSB-first bit is set, subsequent serial control port
operations are LSB first.
When MSB-first mode is active, the instruction and data bytes
must be written from MSB to LSB. Multibyte data transfers in
MSB-first format start with an instruction byte that includes the
register address of the most significant payload byte. Subsequent
data bytes must follow in order from high address to low
address. In MSB-first mode, the serial control port internal
Rev. 0 | Page 52 of 112
AD9548
address generator decrements for each data byte of the multibyte transfer cycle.
Unused addresses are not skipped during multibyte I/O
operations; therefore, the user should write the default value to
a reserved register and 0s to unmapped registers. Note that it is
more efficient to issue a new write command than to write the
default value to more than two consecutive reserved (or
unmapped) registers.
When Register 0000, Bit 6 = 1 (LSB first), the instruction and
data bytes must be written from LSB to MSB. Multibyte data
transfers in LSB-first format start with an instruction byte that
includes the register address of the least significant payload byte
followed by multiple data bytes. The serial control port internal
byte address generator increments for each byte of the multibyte
transfer cycle.
Table 30. Streaming Mode (No Addresses Are Skipped)
Write Mode
LSB First
MSB First
For multibyte MSB-first (default) I/O operations, the serial
control port register address decrements from the specified
starting address toward Address 0000. For multibyte LSB-first
I/O operations, the serial control port register address
increments from the starting address toward Address 1FFF.
Address Direction
Increment
Decrement
Stop Sequence
0x0000 ... 0x1FFF
0x1FFF ... 0x0000
Table 31. Serial Control Port, 16-Bit Instruction Word, MSB First
MSB
I15
I14
I13
I12
I11
I10
I9
I8
I7
I6
I5
I4
I3
I2
I1
LSB
I0
R/W
W1
W0
A12
A11
A10
A9
A8
A7
A6
A5
A4
A3
A2
A1
A0
CS
SCLK DON'T CARE
SDIO DON'T CARE
R/W W1 W0 A12 A11 A10 A9
A8
A7
A6 A5
A4 A3 A2
A1 A0
D7 D6 D5
16-BIT INSTRUCTION HEADER
D4 D3
D2 D1
D0
REGISTER (N) DATA
D7
D6 D5
D4 D3 D2
D1 D0
DON'T CARE
REGISTER (N – 1) DATA
08022-029
DON'T CARE
Figure 53. Serial Control Port Write—MSB First, 16-Bit Instruction, Two Bytes of Data
CS
SCLK
DON'T CARE
SDIO
DON'T CARE
R/W W1 W0 A12 A11 A10 A9 A8 A7 A6 A5 A4 A3 A2 A1 A0
SDO DON'T CARE
REGISTER (N) DATA
REGISTER (N – 1) DATA
REGISTER (N – 2) DATA
REGISTER (N – 3) DATA
DON'T
CARE
Figure 54. Serial Control Port Read—MSB First, 16-Bit Instruction, Four Bytes of Data
tDS
tS
CS
DON'T CARE
SDIO
DON'T CARE
tC
tCLK
tLO
DON'T CARE
R/W
W1
W0
A12
A11
A10
A9
A8
A7
A6
A5
D4
D3
D2
D1
Figure 55. Serial Control Port Write—MSB First, 16-Bit Instruction, Timing Measurements
Rev. 0 | Page 53 of 112
D0
DON'T CARE
08022-031
SCLK
tHI
tDH
08022-030
D7 D6 D5 D4 D3 D2 D1 D0 D7 D6 D5 D4 D3 D2 D1 D0 D7 D6 D5 D4 D3 D2 D1 D0 D7 D6 D5 D4 D3 D2 D1 D0
16-BIT INSTRUCTION HEADER
AD9548
CS
SCLK
DATA BIT N
08022-032
tDV
SDIO
SDO
DATA BIT N – 1
Figure 56. Timing Diagram for Serial Control Port Register Read
CS
SCLK DON'T CARE
A0 A1 A2 A3
A4
A5 A6 A7
A8
A9 A10 A11 A12 W0 W1 R/W D0 D1 D2 D3 D4
16-BIT INSTRUCTION HEADER
D5 D6
REGISTER (N) DATA
D7
D0
D1 D2
D3 D4 D5
D6
D7
REGISTER (N + 1) DATA
Figure 57. Serial Control Port Write—LSB First, 16-Bit Instruction, Two Bytes of Data
CS
tS
tC
tCLK
tHI
tLO
tDS
SCLK
BIT N
BIT N + 1
Figure 58. Serial Control Port Timing—Write
Table 32. Serial Control Port Timing
Parameter
tDS
tDH
tCLK
tS
tC
tHI
tLO
tDV
Description
Setup time between data and the rising edge of SCLK
Hold time between data and the rising edge of SCLK
Period of the clock
Setup time between the CS falling edge and the SCLK rising edge (start of the communication cycle)
Setup time between the SCLK rising edge and CS rising edge (end of the communication cycle)
Minimum period that SCLK should be in a logic high state
Minimum period that SCLK should be in a logic low state
SCLK to valid SDIO and SDO (see Figure 56)
Rev. 0 | Page 54 of 112
08022-034
tDH
SDIO
DON'T CARE
08022-033
SDIO DON'T CARE
DON'T CARE
AD9548
I²C SERIAL PORT OPERATION
Table 33. I2C Bus Abbreviation Definitions
2
The I C interface has the advantage of requiring only two control
pins and is a de facto standard throughout the I2C industry. However,
its disadvantage is programming speed, which is 400 kbps maximum.
The AD9548 I2C port design is based on the I2C fast mode standard
from Philips, so it supports both the 100 kHz standard mode and
400 kHz fast mode. Fast mode imposes a glitch tolerance requirement
on the control signals. That is, the input receivers ignore pulses of
less than 50 ns duration.
The AD9548 I2C port consists of a serial data line (SDA) and a
serial clock line (SCL). In an I2C bus system, the AD9548 is
connected to the serial bus (data bus SDA and clock bus SCL)
as a slave device; that is, no clock is generated by the AD9548.
The AD9548 uses direct 16-bit memory addressing instead of
traditional 8-bit memory addressing.
Abbreviation
Definition
S
Start
Sr
Repeated start
P
Stop
A
Acknowledge
A
Nonacknowledge
W
Write
R
Read
The transfer of data is shown in Figure 59. One clock pulse is
generated for each data bit transferred. The data on the SDA line
must be stable during the high period of the clock. The high or
low state of the data line can only change when the clock signal on
the SCL line is low.
The AD9548 allows up to seven unique slave devices to occupy
the I2C bus. These are accessed via a 7-bit slave address
transmitted as part of an I2C packet. Only the device with a
matching slave address responds to subsequent I2C commands.
The device slave address is 1001xxx (the three right bits are
determined by the M0 to M2 pins). The four MSBs (1001) are
hard-wired, while the three LSBs (xxx, determined by the M0 to
M2 pins) are programmable via the power-up state of the
multifunction pins (see the Initial Pin Programming section).
SDA
SCL
CHANGE
OF DATA
ALLOWED
08022-035
DATA LINE
STABLE;
DATA VALID
Figure 59. Valid Bit Transfer
I2C Bus Characteristics
Start/stop functionality is shown in Figure 60. The start condition
is characterized by a high-to-low transition on the SDA line while
SCL is high. The start condition is always generated by the master
to initialize a data transfer. The stop condition is characterized by
a low-to-high transition on the SDA line while SCL is high. The
stop condition is always generated by the master to terminate a
data transfer. Every byte on the SDA line must be eight bits long. Each
byte must be followed by an acknowledge bit; bytes are sent MSB first.
A summary of the various I2C protocols appears in Table 33.
SDA
SCL
S
START CONDITION
08022-036
P
STOP CONDITION
Figure 60. Start and Stop Conditions
MSB
ACK FROM
SLAVE-RECEIVER
1
SCL
2
3 TO 7
8
9
ACK FROM
SLAVE-RECEIVER
1
S
Figure 61. Acknowledge Bit
Rev. 0 | Page 55 of 112
2
3 TO 7
8
9
10
P
08022-037
SDA
AD9548
Data is then sent over the serial bus in the format of nine clock
pulses, one data byte (eight bits) from either master (write mode)
or slave (read mode) followed by an acknowledge bit from the
receiving device. The number of bytes that can be transmitted per
transfer is unrestricted. In write mode, the first two data bytes
immediately after the slave address byte are the internal memory
(control registers) address bytes, with the high address byte first.
This addressing scheme gives a memory address of up to 216 − 1 =
65,535. The data bytes after these two memory address bytes are
register data written to or read from the control registers. In read
mode, the data bytes after the slave address byte are register data
written to or read from the control registers.
The acknowledge bit (A) is the ninth bit attached to any 8-bit data
byte. An acknowledge bit is always generated by the receiving
device (receiver) to inform the transmitter that the byte has been
received. It is done by pulling the SDA line low during the ninth
clock pulse after each 8-bit data byte.
The nonacknowledge bit (A) is the ninth bit attached to any 8-bit
data byte. A nonacknowledge bit is always generated by the
receiving device (receiver) to inform the transmitter that the byte
has not been received. It is done by leaving the SDA line high
during the ninth clock pulse after each 8-bit data byte.
Data Transfer Process
When all data bytes are read or written, stop conditions are
established. In write mode, the master (transmitter) asserts a
stop condition to end data transfer during the 10th clock pulse
following the acknowledge bit for the last data byte from the slave
device (receiver). In read mode, the master device (receiver)
receives the last data byte from the slave device (transmitter) but
does not pull SDA low during the ninth clock pulse. This is known
as a nonacknowledge bit. By receiving the nonacknowledge bit,
the slave device knows the data transfer is finished and enters idle
mode. The master then takes the data line low during the low
period before the 10th clock pulse, and high during the 10th clock
pulse to assert a stop condition.
The master initiates data transfer by asserting a start condition.
This indicates that a data stream follows. All I2C slave devices
connected to the serial bus respond to the start condition.
The master then sends an 8-bit address byte over the SDA line,
consisting of a 7-bit slave address (MSB first) plus an R/W bit.
This bit determines the direction of the data transfer, that is,
whether data is written to or read from the slave device (0 = write,
1 = read).
The peripheral whose address corresponds to the transmitted
address responds by sending an acknowledge bit. All other devices
on the bus remain idle while the selected device waits for data to
be read from or written to it. If the R/W bit is 0, the master
(transmitter) writes to the slave device (receiver). If the R/W bit is
1, the master (receiver) reads from the slave device (transmitter).
A start condition can be used in place of a stop condition.
Furthermore, a start or stop condition can occur at any time, and
partially transferred bytes are discarded.
The format for these commands is described in the Data Transfer
Format section
MSB
ACK FROM
SLAVE-RECEIVER
1
SCL
2
3 TO 7
8
9
ACK FROM
SLAVE-RECEIVER
1
2
3 TO 7
8
9
S
10
P
08022-038
SDA
Figure 62. Data Transfer Process (Master Write Mode, 2-Byte Transfer)
SDA
ACK FROM
MASTER-RECEIVER
1
2
3 TO 7
8
9
1
2
3 TO 7
S
8
9
10
P
Figure 63. Data Transfer Process (Master Read Mode, 2-Byte Transfer)
Rev. 0 | Page 56 of 112
08022-039
SCL
NON-ACK FROM
MASTER-RECEIVER
AD9548
Data Transfer Format
Write byte format—the write byte protocol is used to write a register address to the RAM starting from the specified RAM address.
S
Slave
address
A
W
RAM address
high byte
A
RAM address
low byte
A
RAM
Data 0
A
RAM
Data 1
A
RAM
Data 2
A
P
Send byte format—the send byte protocol is used to set up the register address for subsequent reads.
S
Slave address
A
W
RAM address high byte
A
RAM address low byte
A
P
Receive byte format—the receive byte protocol is used to read the data byte(s) from RAM starting from the current address.
S
Slave address
R
A
RAM Data 0
A
RAM Data 1
A
RAM Data 2
P
A
Read byte format—the combined format of the send byte and the receive byte.
S
Slave
Address
W
A
RAM
Address
High Byte
A
RAM
Address
Low Byte
A
Sr
Slave
Address
R
A
RAM
Data
0
A
RAM
Data
1
A
RAM
Data
2
I²C Serial Port Timing
SDA
tLO
tF
tR
tSU; DAT
tHD; STA
tSP
tBUF
tR
tF
tHD; STA
S
tHD; DAT
tHI
tSU; STO
tSU; STA
Sr
Figure 64. I²C Serial Port Timing
Table 34. I2C Timing Definitions
Parameter
fSCL
tBUF
tHD; STA
tSU; STA
tSU; STO
tHD; DAT
tSU; DAT
tLO
tHI
tR
tF
tSP
Description
Serial clock
Bus free time between stop and start conditions
Repeated hold time start condition
Repeated start condition setup time
Stop condition setup time
Data hold time
Date setup time
SCL clock low period
SCL clock high period
Minimum/maximum receive SCL and SDA rise time
Minimum/maximum receive SCL and SDA fall time
Pulse width of voltage spikes that must be suppressed by the input filter
Rev. 0 | Page 57 of 112
P
S
08022-040
SCL
A
P
AD9548
I/O PROGRAMMING REGISTERS
An S or C in the Opt column of the register map identifies a
register as an active register (otherwise, it is a buffer register).
An S entry means that the I/O update signal to the active register is
synchronized with the serial port clock or with an input signal
driving one of the multifunction pins. On the other hand, a C
entry means that the I/O update signal to the active register is
synchronized with a clock signal derived from the internal
system clock (fS/32), as shown in Figure 65.
In general, when a group of registers defines a control
parameter, the LSB of the value resides in the D0 position of the
register with the lowest address. The bit weight increases right
to left, from the lowest register address to the highest register
address. For example, the default value of the incremental phase
lock offset step size register (Address 0314 to Address 0315) is
the 16-bit hexadecimal number, 0x03E8 (not 0xE803).
When reading back a register that has both buffered and active
contents, the user can use Register 0004, Bit 0 to select whether
to read back the buffer or active contents. Readback of the
active contents occurs when Register 0004, Bit 0 = 0, whereas
readback of the buffer contents occurs when Register 0004,
Bit 0 = 1. Note that a read-only active register requires an
I/O update before reading its contents.
5
SDIO
3
SDO
4
SCLK/SCL
2
08022-041
CS/SDA
TO INTERNAL DEVICE FUNCTIONS
SERIAL
CONTROL
PORT
BUFFER REGISTERS
There are two broad categories of registers in the AD9548,
buffered and active (see Figure 65). Buffered registers are those
that can be written to directly from the serial port. They do not
need an I/O update to apply their contents to the internal device
functions. In contrast, active registers require an I/O update to
transfer data between the buffer registers and the internal
device functions. In operation, the user programs as many
buffer registers as desired and then issues an I/O update. The
I/O update occurs by writing to Register 0005, Bit 0 = 1 (or by
the external application of the necessary logic level to one of the
multifunction pins previously programmed as an I/O update
input). The contents of buffer registers connected directly to the
internal device functions affect those functions immediately.
The contents of buffer registers that connect to active registers
do not affect the internal device functions until the I/O update
event occurs.
fS/32
ACTIVE C
REGISTERS
BUFFERED/ACTIVE REGISTERS
EDGE
DETECT
ACTIVE S
REGISTERS
FROM
MULTIFUNCTION
PIN LOGIC
Note that the EEPROM storage sequence registers (Address
0E10 to Address 0E3F) are an exception to the above convention
(see the EEPROM Instructions section).
I/O UPDATE
The register map spans an address range from 0x0000 through
0x0E3F (0 to 3647, decimal). Each address provides access to 1
byte (eight bits) of data. Each individual register is identified by
its four-digit hexadecimal address (for example, Register 0A10).
In some cases, a group of addresses collectively define a register
(for example, the IRQ mask register consists of Register 0209,
Register 020A, Register 020B, Register 020C, Register 020D,
Register 020E, Register 020F, and Register 0210).
Figure 65. Buffered and Active Registers
AUTOCLEAR REGISTERS
An A in the Opt column of the register map identifies an autoclear register. Typically, the active value for an autoclear register
takes effect following an I/O update. The bit is cleared by the
internal device logic upon completion of the prescribed action.
Rev. 0 | Page 58 of 112
AD9548
REGISTER ACCESS RESTRICTIONS
Read and write access to the register map may be restricted
depending on the register in question, the source and direction
of access, and the current state of the device. Each register can
be classified into one or more access types. When more than
one type applies, the most restrictive condition that applies at
the moment is used.
Whenever access is denied to a register, all attempts to read the
register return a 0 byte, and all attempts to write to the register
are ignored. Access to nonexistent registers is handled in the
same way as for a denied register.
Regular Access
Registers with regular access do not fall into any other category.
Both read and write access to registers of this type can be from
either the serial ports or EEPROM controller. However, only
one of these sources can have access to a register at any given
time (access is mutually exclusive). Whenever the EEPROM
controller is active, either in load or store mode, it has exclusive
access to these registers.
Read-Only Access
An R in the Opt column of the register map identifies read-only
registers. Access is available at all times, including when the
EEPROM controller is active.
Exclusion from EEPROM Access
An E in the Opt column of the register map identifies a register
with contents that are inaccessible to the EEPROM. That is, the
contents of this type of register cannot be transferred directly to
the EEPROM or vice versa. Note that read-only registers (R) are
inaccessible to the EEPROM, as well.
Rev. 0 | Page 59 of 112
AD9548
REGISTER MAP
Table 35.
Addr
Opt
Name
D7
D6
0000
E
SPI control
0000
0001
0002
0003
0004
Dup
E
R
R
E
I2C control
Reserved
Reserved
Readback
UnidirecLSB first/
tional
Inc Addr
Unused
Unused
Silicon revision number
Device ID
Unused
0005
A, E
I/O update
Unused
0100
S
External
loop filter
enable
0101
0102
S
S
N-divider [7:0]
Unused
M-divider
reset
0103
0104
0105
0106
0107
0108
C
C
C
C
C
C
0200
0201
0202
0203
0204
0205
0206
0207
0208
S
S
S
S
S
S
S
S
C
0209
C
020A
C
Unused
020B
C
Switching
020C
C
Unused
020D
C
Ref AA
new profile
Ref AA
validated
020E
C
Ref BB
new profile
Ref BB
validated
020F
C
Ref CC
new profile
Ref CC
validated
Nom SYSCLK
period
System clock
stability
Charge
pump
mode
(auto/
man)
D5
D4
D3
D2
Serial port control and part identification
Soft reset
Long
Unused
instruction
Soft reset
Unused
D0
System clock
Charge pump current [2:0]
M-divider [1:0]
2×
frequency
multiplier
enable
00
Lock
detect
timer
disable
Lock detect divider [1:0]
PLL enable
SYSCLK reference select
[1:0]
Nominal system clock period (femtoseconds) [15:0]
[1 ns @ 1 ppm accuracy]
Unused
Nominal system clock period [20:16]
System clock stability period (milliseconds) [15:0]
M0 in/out
M1 in/out
M2 in/out
M3 in/out
M4 in/out
M5 in/out
M6 in/out
M7 in/out
Unused
System clock stability period (milliseconds) [19:16]
General configuration
M0 function [6:0]
M1 function [6:0]
M2 function [6:0]
M3 function [6:0]
M4 function [6:0]
M5 function [6:0]
M6 function [6:0]
M7 function [6:0]
Unused
SYSCLK
unlocked
Closed
Freerun
Ref AA
fault
cleared
Ref BB
fault
cleared
Ref CC
fault
cleared
SYSCLK
locked
Holdover
History
updated
Ref AA
fault
Ref BB
fault
Ref CC
fault
Rev. 0 | Page 60 of 112
Unused
Unused
Distribution
sync
Freq
unlocked
Frequency
unclamped
Ref A
new
profile
Ref B
new
profile
Ref C
new
profile
Watchdog
timer
Freq
locked
Frequency
clamped
Ref A
validated
Ref B
validated
Ref C
validated
Def
10
Read
buffer
register
I/O update
Unused
M0
M1
M2
M3
M4
M5
M6
M7
IRQ pin
output mode
IRQ mask
D1
IRQ pin output mode
[1:0]
SYSCLK Cal SYSCLK Cal
complete
started
EEPROM
EEPROM
fault
complete
Phase
Phase
unlocked
locked
Phase slew Phase slew
unlimited
limited
Ref A
Ref A
fault
fault
cleared
Ref B
Ref B
fault
fault
cleared
Ref C
Ref C
fault
fault
cleared
01
48
00
00
18
28
45
40
42
0F
01
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
AD9548
Addr
0210
Opt
C
Name
0211
0212
0213
0214
C
C
S
S
Watchdog
timer
0300
0301
0302
0303
0304
0305
0306
0307
0308
0309
030A
030B
030C
030D
030E
030F
0310
0311
0312
0313
0314
0315
0316
0317
0318
0319
031A
031B
C
C
C
C
C
C
A, C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
Free running
frequency
tuning word
Free running frequency tuning word [47:0]
Update TW
Pull-in
range limits
Unused
Pull-in range lower limit [23:0]
0400
DAC current
D7
Ref DD
new profile
D6
Ref DD
validated
D5
D4
Ref DD
Ref DD
fault
fault
cleared
Watchdog timer (ms) [15:0] [up to 65.5 sec]
D3
Ref D
new
profile
D2
Ref D
validated
DAC full-scale current [7:0]
DAC
Unused
shutdown
D1
Ref D
fault
cleared
D0
Ref D
fault
DAC full-scale current
[9:8]
Def
00
00
00
FF
01
DPLL
Update TW
Pull-in range upper limit [23:0]
Open loop
phase offset
DDS phase offset word [15:0]
Closed loop
phase offset
Fixed phase lock offset [39:0] (picoseconds; signed)
Incremental phase lock offset step size [15:0]
(picoseconds)
Phase slew
limit
Phase slew rate limit [15:0] (ns/sec)
History
accumulation
timer
History accumulation timer [23:0] (milliseconds)
History
mode
Unused
S
Distribution
settings
Unused
0401
S
Unused
0402
S
0403
C
0404
S
Distribution
enable
Distribution
synchronization
Automatic
synchronization
Distribution
channel
modes
0405
S
Unused
Single
Persistent
sample
history
fallback
Clock distribution output
External
Receiver
OUT3
distribution mode
powerresistor
down
OUT3
enable
Sync source [1:0]
OUT3
sync mask
Incremental average [2:0]
OUT2
powerdown
OUT2
enable
OUT2
sync mask
Unused
Unused
Unused
OUT1
powerdown
OUT1
enable
OUT1
sync mask
OUT0
powerdown
OUT0
enable
OUT0
sync mask
Automatic sync mode
[1:0]
OUT0
CMOS
phase
invert
OUT1
CMOS
phase
invert
00
00
00
00
00
00
00
00
00
00
FF
FF
FF
00
00
00
00
00
00
00
E8
03
00
00
30
75
00
00
00
00
00
00
OUT0
polarity
invert
OUT0
drive
strength
OUT0 mode
03
OUT1
polarity
invert
OUT1
drive
strength
OUT1 mode
03
Rev. 0 | Page 61 of 112
AD9548
Addr
0406
Opt
S
0407
S
0408
0409
040A
040B
040C
040D
040E
040F
0410
0411
0412
0413
0414
0415
0416
0417
S
S
S
S
S
S
S
S
S
S
S
S
S
S
S
S
Distribution
channel
dividers
0500
S
Reference
power-down
0501
0502
0503
S
S
C
Reference
logic family
0504
C
0505
C
0506
C
0507
C
0600
0601
0602
0603
0604
0605
0606
0607
0608
0609
060A
060B
060C
060D
060E
Name
D7
Unused
Unused
Manual
reference
profile
selection
Phase buildout switching
Priorities
Reference
period
Tolerance
D6
D5
OUT2
CMOS
phase
invert
OUT3
CMOS
phase
invert
D4
OUT2
polarity
invert
D3
OUT2
drive
strength
D2
D1
OUT2 mode
OUT3
polarity
invert
OUT3
drive
strength
OUT3 mode
Unused
Q1 [23:0]
Q0 [29:24]
Unused
Q2 [23:0]
Q1 [29:24]
Unused
Q3 [23:0]
Q2 [29:24]
Unused
Q3 [29:24]
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
Reference inputs
Ref A
Ref AA
Ref B
Ref BB
Ref C
Ref CC
Ref D
Ref DD
powerpowerpowerpowerpowerpowerpowerpowerdown
down
down
down
down
down
down
down
Ref BB logic family [1:0]
Ref B logic family [1:0]
Ref AA logic family [1:0]
Ref A logic family [1:0]
Ref DD logic family [1:0]
Ref D logic family [1:0]
Ref CC Logic Family [1:0]
Ref C Logic Family [1:0]
Ref A manual profile [2:0]
Ref AA manual profile [2:0]
Enable Ref
Enable Ref
A manual
AA manual
profile
profile
Enable Ref
Ref BB manual profile [2:0]
Enable Ref
Ref B manual profile [2:0]
BB Manual
B manual
Profile
profile
Enable Ref
Ref CC manual profile [2:0]
Enable Ref
Ref C manual profile [2:0]
CC Manual
C manual
Profile
profile
Enable Ref
Ref DD manual profile [2:0]
Enable Ref
Ref D manual profile [2:0]
DD Manual
D manual
Profile
profile
Unused
Phase master threshold priority [2:0]
Profile 0
Unused
Promoted priority [2:0]
Nominal period (femtoseconds) [47:0] (up to 1.125 sec)
Selection priority [2:0]
Unused
Inner tolerance (1/tolerance) [15:0] (removes fault status; 10% down to 1 ppm)
Unused
Validation timer (milliseconds) [15:0] (up to 65.5 sec)
Rev. 0 | Page 62 of 112
Def
03
03
Q0 [23:0]
Unused
Inner tolerance [19:16]
Outer tolerance (1/tolerance) [15:0] (indicates fault status; 10% down to 1 ppm)
Validation
D0
Outer tolerance [19:16]
Nominal period [49:48]
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
AD9548
Addr
060F
0610
0611
0612
0613
Opt
Name
D7
D6
D5
D4
Redetect
timeout
Redetect timer (milliseconds) [15:0] [up to 65.5 seconds]
Digital loop
filter
coefficients
Alpha-0 linear [15:0]
0614
0615
Alpha-2 exponent [1:0]
Beta-0 linear [6:0]
0616
0617
0618
0619
061A
Beta-0 linear [14:7]
Unused
Beta-1 exponent [4:0]
Gamma-0 linear [15:0]
Unused
061B
061C
061D
061E
061F
0620
0621
0622
0623
0624
0625
0626
0627
0628
0629
062A
062B
062C
062D
062E
062F
0630
0631
0632
0633
0634
0635
0636
0637
0638
0639
063A
063B
063C
06CD
063E
063F
0640
0641
Frequency
multiplication
Lock
detectors
D2
D1
D0
Alpha-1 exponent [5:0]
Alpha-2
exponent
[2]
Beta-0 linear [16:15]
Gamma-1 exponent [4:0]
Delta-0 linear [7:0]
Delta-0 linear [14:8]
Delta-1
exponent
[0]
Alpha-3 exponent [3:0]
R [23:0]
Unused
S [23:0]
D3
Gamma-0
linear [16]
Delta-1 exponent [4:1]
R [29:24]
Unused
S [29:24]
V [7:0]
U [3:0]
Unused
U [9:4]
Phase lock threshold (picoseconds) [15:0]
Unused
V [9:8]
Frequency lock fill rate [7:0]
Frequency lock drain rate [7:0]
Tolerance
Profile 1
Unused
Promoted priority [2:0]
Nominal period (femtoseconds) [47:0] (up to 1.125 sec)
Selection priority [2:0]
Unused
Inner tolerance (1/tolerance) [15:0] (removes fault status; 10% down to 1 ppm)
Unused
Inner tolerance [19:16]
Outer tolerance (1/tolerance) [15:0] (indicates fault status; 10% down to 1 ppm)
Validation
00
00
00
00
00
00
00
00
00
Phase lock fill rate [7:0]
Phase lock drain rate [7:0]
Frequency lock threshold (picoseconds) [23:0]
Priorities
Reference
period
Def
00
00
00
00
00
Unused
Validation timer (milliseconds) [15:0] (up to 65.5 sec)
Rev. 0 | Page 63 of 112
Outer tolerance [19:16]
Nominal period [49:48]
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
AD9548
Addr
0642
0643
0644
0645
0646
0647
Opt
Name
Redetect
timeout
D7
D6
D5
D4
Redetect timer (milliseconds) [15:0] (up to 65.5 sec)
Digital loop
filter
coefficients
Alpha-0 linear [15:0]
Alpha-2 exponent [1:0]
Beta-0 linear [6:0]
064D
064E
Delta-0 linear [7:0]
Delta-1 exDelta-0 linear [14:8]
ponent [0]
Alpha-3 exponent [3:0]
R [23:0]
0680
0681
0682
0683
0684
0685
0686
0687
0688
0689
068A
068B
068C
068D
068E
068F
Frequency
multiplication
Unused
S [23:0]
Lock
detectors
D1
D0
Alpha-2
exponent
[2]
Beta-0 linear [14:7]
Unused
Beta-1 exponent [4:0]
Gamma-0 linear [15:0]
064F
0650
0651
0652
0653
0654
0655
0656
0657
0658
0659
065A
065B
065C
065D
065E
065F
0660
0661
0662
0663
0664
to
067F
D2
Alpha-1 exponent [5:0]
0648
0649
064A
064B
064C
Unused
D3
Beta-0 linear [16:15]
Gamma-1 exponent [4:0]
Gamma-0
linear [16]
Delta-1 exponent [4:1]
R [29:24]
Unused
S [29:24]
V [7:0]
U [3:0]
Unused
U [9:4]
Phase lock threshold (picoseconds) [15:0]
Unused
V [9:8]
Frequency lock fill rate [7:0]
Frequency lock drain rate [7:0]
Unused
Tolerance
Profile 2
Unused
Promoted priority [2:0]
Nominal period (femtoseconds) [47:0] (up to 1.125 sec)
Selection priority [2:0]
Unused
Inner tolerance (1/tolerance) [15:0] (removes fault status; 10% down to 1 ppm)
Unused
Inner tolerance [19:16]
Outer tolerance (1/tolerance) [15:0] (indicates fault status; 10% down to 1 ppm)
Validation
00
00
00
00
00
00
00
Phase lock fill rate [7:0]
Phase lock drain rate [7:0]
Frequency lock threshold (picoseconds) [23:0]
Priorities
Reference
period
Def
00
00
00
00
00
00
Unused
Validation timer (milliseconds) [15:0] (up to 65.5 sec)
Rev. 0 | Page 64 of 112
Outer tolerance [19:16]
Nominal period [49:48]
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
AD9548
Addr
0690
0691
0692
0693
0694
0695
Opt
Name
Redetect
timeout
D7
D6
D5
D4
D3
Redetect timer (milliseconds) [15:0] (up to 65.5 seconds)
Digital loop
filter
coefficients
Alpha-0 linear [15:0]
0696
0697
0698
0699
069A
Unused
06B2
06B3
06B4
06B5
06B6
06B7
06B8
06B9
06BA
06BB
06BC
06BD
06BE
06BF
Frequency
multiplication
Lock
detectors
D0
Alpha-2
exponent
[2]
Beta-0 linear [16:15]
Gamma-1 exponent [4:0]
Delta-0 linear [7:0]
Delta-1
Delta-0 linear [14:8]
exponent
[0]
Alpha-3 exponent [3:0]
R [23:0]
Unused
S [23:0]
D1
Alpha-1 exponent [5:0]
Beta-0 linear [14:7]
Unused
Beta-1 exponent [4:0]
Gamma-0 linear [15:0]
069B
069C
069D
069E
069F
06A0
06A1
06A2
06A3
06A4
06A5
06A6
06A7
06A8
06A9
06AA
06AB
06AC
06AD
06AE
06AF
06B0
06B1
Alpha-2 exponent [1:0]
Beta-0 linear [6:0]
D2
Gamma-0
linear [16]
Delta-1 exponent [4:1]
R [29:24]
Unused
S [29:24]
V [7:0]
U [3:0]
Unused
U [9:4]
Phase lock threshold (picoseconds) [15:0]
Unused
V [9:8]
Frequency lock fill rate [7:0]
Frequency lock drain rate [7:0]
Tolerance
00
00
00
00
00
00
00
Phase lock fill rate [7:0]
Phase lock drain rate [7:0]
Frequency lock threshold (picoseconds) [23:0]
Priorities
Reference
period
Def
00
00
00
00
00
00
Profile 3
Unused
Promoted priority [2:0]
Nominal period (femtoseconds) [47:0] (up to 1.125 sec)
Selection priority [2:0]
Unused
Inner tolerance (1/tolerance) [15:0] (removes fault status; 10% down to 1 ppm)
Unused
Inner tolerance [19:16]
Outer tolerance (1/tolerance) [15:0] (indicates fault status; 10% down to 1 ppm)
Unused
Outer tolerance [19:16]
Rev. 0 | Page 65 of 112
Nominal period [49:48]
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
AD9548
Addr
06C0
06C1
06C2
06C3
06C4
06C5
06C6
06C7
Opt
Name
Validation
D7
D6
D5
D4
Validation timer (milliseconds) [15:0] (up to 65.5 sec)
Redetect
timeout
Redetect timer (milliseconds) [15:0] (up to 65.5 sec)
Digital loop
filter
coefficients
Alpha-0 linear [15:0]
Alpha-2 exponent [1:0]
Beta-0 linear [6:0]
06CA
06CB
06CC
Gamma-0 linear [15:0]
06CD
06CE
Delta-0 linear [7:0]
Delta-0 linear [14:8]
Delta-1
exponent
[0]
Alpha-3 exponent [3:0]
R [23:0]
Frequency
multiplication
D0
00
Gamma-0
linear [16]
Delta-1 exponent [4:1]
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
00
R [29:24]
Unused
S [29:24]
V [7:0]
U [3:0]
Unused
U [9:4]
Phase lock threshold (picoseconds) [15:0]
Unused
V [9:8]
Frequency lock fill rate [7:0]
Frequency lock drain rate [7:0]
Unused
Profile 4
through
Profile 7
00
00
00
00
00
Phase lock fill rate [7:0]
Phase lock drain rate [7:0]
Frequency lock threshold (picoseconds) [23:0]
070007FF
Def
00
00
00
00
00
00
00
00
00
Beta-0
linear
[16:15]
Gamma-1 exponent [4:0]
Unused
S [23:0]
Lock
detectors
D1
Alpha-2
exponent
[2]
Beta-0 linear [14:7]
Unused
Beta-1 exponent [4:0]
06CF
06D0
06D1
06D2
06D3
06D4
06D5
06D6
06D7
06D8
06D9
06DA
06DB
06DC
06DD
06DE
06DF
06E0
06E1
06E2
06E3
06E406FF
D2
Alpha-1 exponent [5:0]
06C8
06C9
Unused
D3
Profile 4 through Profile 7
The functionality of the Profile 4 through Profile 7 address locations (Address 0700 to Address 07FF) is identical
to that of the Profile 0 through Profile 3 address locations (Address 0600 to Address 06FF).
0A00
S
General
power-down
Reset Sans
regmap
Unused
0A01
C
Unused
User
holdover
0A02
S
Loop
mode
Cal/sync
SYSCLK
powerdown
User
freerun
Operational controls
TDC
Reference
powerpowerdown
down
User selection mode [1:0]
Unused
Rev. 0 | Page 66 of 112
Full
Dist
DAC
powerpowerpowerdown
down
down
User reference selection [2:0]
00
Sync
distribution
00
Calibrate
system
clock
00
AD9548
Addr
0A03
Opt
A, C
Name
ResetFunc
D7
Unused
0A04
A, C
IRQ clearing
Unused
0A05
A, C
Unused
0A06
A, C
Switching
0A07
A, C
Unused
0A08
A, C
Ref AA
new profile
Ref AA
validated
0A09
A, C
Ref BB
new profile
Ref BB
validated
0A0A
A, C
Ref CC
new profile
Ref CC
validated
0A0B
A, C
Ref DD
new profile
Ref DD
validated
0A0C
A, C
Incremental
phase offset
Unused
0A0D
A, C
Detect DD
Detect D
Detect CC
Detect C
Detect BB
0A0E
A, C
C
0A10
C
Force
Timeout
DD
Ref Mon
Override
DD
Ref Mon
Bypass DD
Force
Timeout
D
Ref Mon
Override
D
Ref Mon
Bypass D
Force
Timeout
CC
Ref Mon
Override
CC
Ref Mon
Bypass CC
Force
Timeout C
0A0F
Reference
profile detect
Force
validation
timeout
Reference
monitor
override
Reference
monitor
bypass
Force
Timeout
BB
Ref Mon
Override
BB
Ref Mon
Bypass BB
0D00
R
EEPROM
Unused
0D01
R
System clock
Unused
0D02
R
IRQ monitor
Unused
0D03
R
Unused
0D04
R
Switching
0D05
R
Unused
0D06
R
Ref AA
new profile
Ref AA
validated
0D07
R
Ref BB
new profile
Ref BB
validated
0D08
R
Ref CC
new profile
Ref CC
validated
0D09
R
Ref DD
new profile
Ref DD
validated
0D0A
R, C
0D0B
R, C
Offset slew
limiting
Frequency
Phase
build-out
History
DPLL status
D6
Clear LF
D5
Clear CCI
SYSCLK
unlocked
Closed
Closed
Freerun
Ref AA
fault
cleared
Ref BB
fault
cleared
Ref CC
fault
cleared
Ref DD
fault
cleared
D4
Clear
phase accumulator
SYSCLK
locked
Holdover
History
updated
Ref AA
fault
Ref BB
fault
Ref CC
fault
Ref DD
fault
Ref Mon
Override C
Ref Mon
Bypass C
D3
Reset auto
sync
D2
Reset
TW history
D1
Reset
all IRQs
D0
Reset
watchdog
Def
00
Unused
Unused
Watchdog
timer
Freq
locked
Freq
clamped
Ref A
validated
SYSCLK Cal
started
EEPROM
complete
Phase
locked
Phase slew
limited
Ref A
fault
00
Distribution sync
Freq
unlocked
Freq unclamped
Ref A
new
profile
Ref B
new
profile
Ref C
new
profile
Ref D
new
profile
SYSCLK Cal
complete
EEPROM
fault
Phase
unlocked
Phase slew
unlimited
Ref A
fault
cleared
Ref B
fault
cleared
Ref C
fault
cleared
Ref D
fault
cleared
Decrement
phase
offset
Detect AA
Ref B
validated
Ref C
validated
Ref D
validated
Reset
phase
offset
Detect B
Force
Timeout B
Ref Mon
Override B
Ref Mon
Bypass B
Force
Timeout
AA
Ref Mon
Override
AA
Ref Mon
Bypass AA
Status (read only; accessible during EEPROM transactions)
Fault
Load in
detected
progress
Stable
Unused
Unused
Cal
in progress
SYSCLK
SYSCLK
Unused
Unused
SYSCLK Cal
unlocked
locked
complete
DistribuWatchdog
EEPROM
tion sync
timer
fault
Freerun
Holdover
Freq
Freq
Phase
unlocked
locked
unlocked
History
Freq unFreq
Phase slew
updated
clamped
clamped
unlimited
Ref AA
Ref AA
Ref A
Ref A
Ref A
fault
fault
new
validated
fault
cleared
profile
cleared
Ref BB
Ref BB
Ref B
Ref B
Ref B
fault
fault
new
validated
fault
cleared
profile
cleared
Ref CC
Ref CC
Ref C new
Ref C
Ref C
fault
fault
profile
validated
fault
cleared
cleared
Ref DD
Ref DD
Ref D new
Ref D
Ref D
fault
fault
profile
validated
fault
cleared
cleared
Freq lock
Phase lock
Loop
Holdover
Active
switching
Active reference priority [3:0]
Active reference [3:0]
Rev. 0 | Page 67 of 112
00
00
00
00
Ref B
fault
00
Ref C
fault
00
Ref D
fault
00
Increment
phase
offset
Detect A
00
00
Force
Timeout A
00
Ref Mon
Override A
00
Ref Mon
Bypass A
00
Save in
progress
Lock
detected
SYSCLK Cal
started
EEPROM
complete
Phase
locked
Phase slew
limited
Ref A
fault
Ref B
fault
Ref C
fault
Ref D
fault
Free
running
AD9548
Addr
Opt
Name
0D0C
R, C
Ref A
0D0D
R, C
Ref AA
0D0E
R, C
Ref B
0D0F
R, C
Ref BB
0D10
R, C
Ref C
0D11
R, C
Ref CC
0D12
R. C
Ref D
0D13
R, C
Ref DD
0D14
0D15
0D16
0D17
0D18
0D19
R, C
R, C
R, C
R, C
R, C
R, C
Holdover
history
D7
D6
D5
clamped
available
Profile
Selected profile [2:0]
selected
Profile
Selected profile [2:0]
selected
Profile
Selected profile [2:0]
selected
Profile
Selected profile [2:0]
selected
Profile
Selected profile [2:0]
selected
Profile
Selected profile [2:0]
selected
Profile
Selected profile [2:0]
selected
Profile
Selected profile [2:0]
selected
Tuning word readback [47:0]
D4
D3
D2
D1
D0
Valid
Fault
Fast
Slow
Valid
Fault
Fast
Slow
Valid
Fault
Fast
Slow
Valid
Fault
Fast
Slow
Valid
Fault
Fast
Slow
Valid
Fault
Fast
Slow
Valid
Fault
Fast
Slow
Valid
Fault
Fast
Slow
Half rate
mode
Write
enable
Def
Nonvolatile memory (EEPROM) control
0E00
Write protect
Unused
0E01
0E02
E
A, E
Condition
Save
Unused
Unused
0E03
A, E
Load
Unused
0E10
0E11
0E12
0E13
0E14
E
E
E
E
E
System
clock
Data: 9 bytes
Address: 0x0100
Action: IO_Update
Action: calibrate system clock
0E15
0E16
0E17
0E18
0E19
0E1A
0E1B
0E1C
0E1D
0E1E
0E1F
0E20
0E21
0E22
0E23
0E24
E
E
E
E
E
E
E
E
E
E
E
E
E
E
E
E
I/O update
SYSCLK
calibrate
General
DPLL
Data: 28 bytes
Address: 0x0300
Clock
distribution
Data: 26 bytes
Address: 0x0400
I/O update
Reference
inputs
Action: IO_Update
Data: 8 bytes
Address: 0x0500
Profile 0 and
Profile 1
Data: 100 bytes
Address: 0x0600
Condition value [4:0]
Load from
EEPROM
Save to
EEPROM
Unused
00
00
00
00
EEPROM storage sequence
08
01
00
80
A0
Data: 21 bytes
Address: 0x0200
14
02
00
1B
03
00
19
04
00
80
07
05
00
63
06
00
Rev. 0 | Page 68 of 112
AD9548
Addr
0E25
0E26
0E27
0E28
0E29
0E2A
0E2B
0E2C
0E2D
0E2E
0E2F
0E30
0E31
0E32
0E33
0E34
to
0E3F
Opt
E
E
E
E
E
E
E
E
E
E
E
E
E
E
E
E
Name
Profile 2 and
Profile 3
D7
D6
Data: 100 bytes
Address: 0x0680
D5
Profile 4 and
Profile 5
Data: 100 bytes
Address: 0x0700
Profile 6 and
Profile 7
Data: 100 bytes
Address: 0x0780
I/O update
Operational
controls
Action: IO_Update
Data: 17 bytes
Address: 0x0A00
I/O update
End of data
Action: IO_Update
Action: end of data
Continuation of scratch pad area
D4
Rev. 0 | Page 69 of 112
D3
D2
D1
D0
Def
63
06
80
63
07
00
63
07
80
80
10
0A
00
80
FF
AD9548
REGISTER MAP BIT DESCRIPTIONS
SERIAL PORT CONFIGURATION (REGISTER 0000 TO REGISTER 0005)
Table 36. Serial Configuration
Address
0000
Bits
[7]
Bit Name
Unidirectional
[6]
LSB first
[5]
Soft reset
[4]
[0]
Long instruction
Unused
Description
Select SPI port SDO pin operating mode.
0 (default) = 3-wire.
1 = 4-wire (SDO pin enabled).
Bit order for SPI port.
0 (default) = most significant bit and byte first.
1 = least significant bit and byte first.
Device reset (invokes an EEPROM download if M[7:3] ≠ 0).
0 (default) = normal operation.
1 = reset.
16-bit mode (the only mode supported by the device). This bit is read only and reads back as Logic 1.
Table 37. Reserved Register
Address
0001
Bits
[7:0]
Bit Name
Unused
Description
Table 38. Silicon Revision Level (Read-Only)
Address
0002
Bits
[7:0]
Bit Name
Reserved
Description
Default = 0x01 = 0b00000001
Table 39. Device ID (Read Only)
Address
0003
Bits
[7:0]
Bit Name
Reserved
Description
Default = 0x48 = 0b01001000
Table 40. Register Readback Control
Address
0004
Bits
[7:1]
0
Bit Name
Unused
Read buffer register
Description
For buffered registers, serial port readback reads from actual (active) registers instead of
from the buffer.
0 (default) = reads values currently applied to the internal logic of the device.
1 = reads buffered values that take effect on the next assertion of the I/O update.
Table 41. Soft I/O Update
Address
0005
Bits
[7:1]
0
Bit Name
Unused
I/O update
Description
Writing a 1 to this bit transfers the data in the serial I/O buffer registers to the internal
control registers of the device. This is an autoclearing bit.
Rev. 0 | Page 70 of 112
AD9548
SYSTEM CLOCK (REGISTER 0100 TO REGISTER 0108)
Table 42. Charge Pump and Lock Detect Control
Address
0100
Bits
[7]
Bit Name
External loop filter
enable
[6]
Charge pump mode
[5:3]
Charge pump current
[2]
Lock detect timer
disable
[1:0]
Lock detect timer
Description
Enables use of an external SYSCLK PLL loop filter
0 (default) = internal loop filter
1 = external loop filter
Charge pump current control
0 (default) = automatic
1 = manual
Selects charge pump current when Bit 6 = 1
000 = 125 μA
001 = 250 μA
010 = 375 μA
011 (default) = 500 μA
100 = 625 μA
101 = 750 μA
110 = 875 μA
111 = 1000 μA
Enable the SYSCLK PLL lock detect timer
0 (default) = enable
1 = disable
Select lock detect timer depth
00 (default) = 128
01 = 256
10 = 512
11 = 1024
Table 43. N Divider
Address
0101
Bits
[7:0]
Bit Name
N-divider
Description
System clock PLL feedback divider value: 6 ≤ N ≤ 255 (default = 0x28 = 40)
Table 44. SYSCLK Input Options
Address
0102
Bits
[7]
[6]
Bit Name
Unused
M-divider reset
[5:4]
M-divider
[3]
2× frequency
multiplier enable
[2]
PLL enable
[1:0]
System clock source
Description
Reset the M-divider
0 = normal operation
1 (default) = reset
When not using the M-divider, program this bit to Logic 1.
System clock input divider
00 (default) = 1
01 = 2
10 = 4
11 = 8
Enable the 2× frequency multiplier
0 (default) = disable
1 = enable
Enable the SYSCLK PLL
0 = disable
1 (default) = enable
Input mode select for SYSCLKx pins
00 = crystal resonator
01 (default) = low frequency clock source
10 = high frequency (direct) clock source
11 = input receiver power-down
Rev. 0 | Page 71 of 112
AD9548
Table 45. Nominal System Clock (SYSCLK) Period 1
Address
0103
Bits
[7:0]
0104
[7:0]
0105
[7:5]
[4:0]
1
Bit Name
System clock period
(expressed in
femtoseconds)
Unused
System clock period
Description
System clock period, Bits[7:0]
System clock period, Bits[15:8]
System clock period, Bits[20:16]
Units are femtoseconds. The default value is 0x0F424 = 1,000,000 (1 ns) and implies a system clock frequency of 1 GHz.
Table 46. System Clock Stability Period 1
Address
0106
0107
0108
1
Bits
[7:0]
[7:0]
[7:4]
[3:0]
Bit Name
System clock stability
period
Description
System clock stability period, Bits[7:0] (default = 0x01)
System clock stability period, Bits[15:8] (default = 0x00)
Unused
System clock stability
period
System clock stability period, Bits[19:16] (default = 0x0)
(default period = 0x00001, or 1 ms)
Units are milliseconds. The default value is 0x000001 = 1 (1 ms).
GENERAL CONFIGURATION (REGISTER 0200 TO REGISTER 0214)
Register 0200 to Register 0207—Multifunction Pin Control (M0 to M7)
Table 47. Multifunction Pin (M0 to M7) Control 1
Address
0200
0201
0202
0203
0204
0205
0206
0207
1
Bits
[7]
Bit Name
M0 in/out
[6:0]
[7]
[6:0]
[7]
[6:0]
[7]
[6:0]
[7]
[6:0]
[7]
[6:0]
[7]
[6:0]
[7]
[6:0]
M0 function
M1 in/out
M1 function
M2 in/out
M2 function
M3 in/out
M3 function
M4 in/out
M4 function
M5 in/out
M5 function
M6 in/out
M6 function
M7 in/out
M7 function
Description
In/out control for the M0 pin
0 (default) = input (control pin)
1 = output (status pin)
See Table 24 and Table 25 (default = 0xb0000000)
In/out control for the M1 pin (same as M0)
See Table 24 and Table 25 (default = 0xb0000000)
In/out control for the M2 pin (same as M0)
See Table 24 and Table 25 (default = 0xb0000000)
In/out control for the M3 pin (same as M0)
See Table 24 and Table 25 (default = 0xb0000000)
In/out control for the M4 pin (same as M0)
See Table 24 and Table 25 (default = 0xb0000000)
In/out control for the M5 pin (same as M0)
See Table 24 and Table 25 (default = 0xb0000000)
In/out control for the M6 pin (same as M0)
See Table 24 and Table 25 (default = 0xb0000000)
In/out control for the M7 pin (same as M0)
See Table 24 and Table 25 (default = 0xb0000000)
The default setting for all the multifunction pins is as an unused control input pin.
Table 48. IRQ Pin Output Mode
Address
0208
Bits
[7:2]
[1:0]
Bit Name
Unused
IRQ pin output mode
Description
Select the output mode of the IRQ pin
00 (default) = NMOS, open drain (requires an external pull-up resistor)
01 = PMOS, open drain (requires an external pull-down resistor)
10 = CMOS, active high
11 = CMOS, active low
Rev. 0 | Page 72 of 112
AD9548
Register 0209 to Register 0210—IRQ Mask
The IRQ mask register bits form a one-to-one correspondence with the bits of the IRQ monitor register (Address 0D02 to Address 0D09).
When set to Logic 1, the IRQ mask bits enable the corresponding IRQ monitor bits to indicate an IRQ event. The default for all IRQ mask bits
is Logic 0, which prevents the IRQ monitor from detecting any internal interrupts.
Table 49. IRQ Mask for SYSCLK
Address
0209
Bits
[7:6]
[5]
[4]
[3:2]
[1]
[0]
Bit Name
Unused
SYSCLK unlocked
SYSCLK locked
Unused
SYSCLK Cal complete
SYSCLK Cal started
Description
Enables IRQ for indicating a SYSCLK PLL state transition from locked to unlocked
Enables IRQ for indicating a SYSCLK PLL state transition from unlocked to locked
Enables IRQ for indicating that SYSCLK calibration has completed
Enables IRQ for indicating that SYSCLK calibration has begun
Table 50. IRQ Mask for Distribution Sync, Watchdog Timer, and EEPROM
Address
020A
Bits
[7:4]
[3]
[2]
[1]
[0]
Bit Name
Unused
Distribution sync
Watchdog timer
EEPROM fault
EEPROM complete
Description
Enables IRQ for indicating a distribution sync event
Enables IRQ for indicating expiration of the watchdog timer
Enables IRQ for indicating a fault during an EEPROM load or save operation
Enables IRQ for indicating successful completion of an EEPROM load or save operation
Table 51. IRQ Mask for the Digital PLL
Address
020B
Bits
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
Bit Name
Switching
Closed
Freerun
Holdover
Freq unlocked
Freq locked
Phase unlocked
Phase locked
Description
Enables IRQ for indicating that the DPLL is switching to a new reference
Enables IRQ for indicating that the DPLL has entered closed-loop operation
Enables IRQ for indicating that the DPLL has entered free-run mode
Enables IRQ for indicating that the DPLL has entered holdover mode
Enables IRQ for indicating that the DPLL lost frequency lock
Enables IRQ for indicating that the DPLL has acquired frequency lock
Enables IRQ for indicating that the DPLL lost phase lock
Enables IRQ for indicating that the DPLL has acquired phase lock
Table 52. IRQ Mask for History Update, Frequency Limit, and Phase Slew Limit
Address
020C
Bits
[7:5]
[4]
[3]
Bit Name
Unused
History updated
Frequency unclamped
[2]
Frequency clamped
[1]
Phase slew unlimited
[0]
Phase slew limited
Description
Enables IRQ for indicating the occurrence of a tuning word history update
Enables IRQ for indicating a state transition frequency limiter from clamped to
unclamped
Enables IRQ for indicating a state transition of the frequency limiter from unclamped
to clamped
Enables IRQ for indicating a state transition of the phase slew limiter from slew
limiting to not slew limiting
Enables IRQ for indicating a state transition of the phase slew limiter from not slew
limiting to slew limiting
Rev. 0 | Page 73 of 112
AD9548
Table 53. IRQ Mask for Reference Inputs
Address
020D
020E
020F
0210
Bits
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
Bit Name
Ref AA new profile
Ref AA validated
Ref AA fault cleared
Ref AA fault
Ref A new profile
Ref A validated
Ref A fault cleared
Ref A fault
Ref BB new profile
Ref BB validated
Ref BB fault cleared
Ref BB fault
Ref B new profile
Ref B validated
Ref B fault cleared
Ref B fault
Ref CC new profile
Ref CC validated
Ref CC fault cleared
Ref CC fault
Ref C new profile
Ref C validated
Ref C fault cleared
Ref C fault
Ref DD new profile
Ref DD validated
Ref DD fault cleared
Ref DD fault
Ref D new profile
Ref D validated
Ref D fault cleared
Ref D fault
Description
Enables IRQ for indicating that Ref AA has switched to a new profile
Enables IRQ for indicating that Ref AA has been validated
Enables IRQ for indicating that Ref AA has been cleared of a previous fault
Enables IRQ for indicating that Ref AA has been faulted
Enables IRQ for indicating that Ref A has switched to a new profile
Enables IRQ for indicating that Ref A has been validated
Enables IRQ for indicating that Ref A has been cleared of a previous fault
Enables IRQ for indicating that Ref A has been faulted
Enables IRQ for indicating that Ref BB has switched to a new profile
Enables IRQ for indicating that Ref BB has been validated
Enables IRQ for indicating that Ref BB has been cleared of a previous fault
Enables IRQ for indicating that Ref BB has been faulted
Enables IRQ for indicating that Ref B has switched to a new profile
Enables IRQ for indicating that Ref B has been validated
Enables IRQ for indicating that Ref B has been cleared of a previous fault
Enables IRQ for indicating that Ref B has been faulted
Enables IRQ for indicating that Ref CC has switched to a new profile
Enables IRQ for indicating that Ref CC has been validated
Enables IRQ for indicating that Ref CC has been cleared of a previous fault
Enables IRQ for indicating that Ref CC has been faulted
Enables IRQ for indicating that Ref C has switched to a new profile
Enables IRQ for indicating that Ref C has been validated
Enables IRQ for indicating that Ref C has been cleared of a previous fault
Enables IRQ for indicating that Ref C has been faulted
Enables IRQ for indicating that Ref DD has switched to a new profile
Enables IRQ for indicating that Ref DD has been validated
Enables IRQ for indicating that Ref DD has been cleared of a previous fault
Enables IRQ for indicating that Ref DD has been faulted
Enables IRQ for indicating that Ref D has switched to a new profile
Enables IRQ for indicating that Ref D has been validated
Enables IRQ for indicating that Ref D has been cleared of a previous fault
Enables IRQ for indicating that Ref D has been faulted
Bit Name
Watchdog timer
Description
Watchdog timer, Bits[7:0] (default = 0x00)
Watchdog timer, Bits[15:8] (default = 0x00)
Table 54. Watchdog Timer 1
Address
0211
0212
1
Bits
[7:0]
[7:0]
The watchdog timer is expressed in milliseconds. The default value is 0 (disabled).
Table 55. Auxiliary DAC 1
Address
0213
0214
1
Bits
[7:0]
[7]
Bit Name
Full-scale current
DAC shutdown
[6:2]
[1:0]
Unused
Full-scale current
Description
Full scale current, Bits[7:0] (default = 0xFF)
Shut down the DAC current sources.
0 (default) = normal operation
1 = shut down
Full-scale current, Bits[9:8] (default = 0b01)
(default current = 0x1FF, or 20.1 mA)
The default DAC full-scale current value is 0x01FF = 511, which equates to 20.1375 mA.
Rev. 0 | Page 74 of 112
AD9548
DPLL CONFIGURATION (REGISTER 0300 TO REGISTER 031B)
Table 56. Free Running Frequency Tuning Word 1
Address
0300
0301
0302
0303
0304
0305
1
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
Bit Name
Frequency
(expressed as a 48-bit
frequency tuning
word)
Description
Free running frequency tuning word, Bits[7:0]
Free running frequency tuning word, Bits[15:8]
Free running frequency tuning word, Bits[23:9]
Free running frequency tuning word, Bits[31:24]
Free running frequency tuning word, Bits[39:32]
Free running frequency tuning word, Bits[47:40]
The default free running tuning word is 0x000000 = 0, which equates to 0 Hz.
Table 57. Update TW
Address
0306
Bits
[7:1]
[0]
Bit Name
Unused
Update TW
Description
A Logic 1 written to this bit transfers the free running frequency tuning word (Register
0300 to Register 0305) to the register imbedded in the tuning word processing logic.
Note that it is not necessary to write the update TW bit when the device is in free-run
mode. This is an autoclearing bit.
Table 58. Pull-In Range Lower Limit 1
Address
0307
Bits
[7:0]
0308
[7:0]
0309
[7:0]
030A
[7:0]
030B
[7:0]
030C
[7:0]
1
Bit Name
Pull-in range lower
limit (expressed as a
24-bit frequency
tuning word)
Description
Lower limit pull-in range, Bits[7:0]
Lower limit pull-in range, Bits[15:8]
Lower limit pull-in range, Bits[23:9]
Pull-in range upper
limit (expressed as a
24-bit frequency
tuning word)
Upper limit pull-in range, Bits[7:0]
Upper limit pull-in range, Bits[15:8]
Upper limit pull-in range, Bits[23:9]
The default pull-in range lower limit is 0 and the upper range limit is 0xFFFFFF, which effectively spans the full output frequency range of the DDS.
Table 59. DDS Phase Offset 1
Address
030D
Bits
[7:0]
030E
[7:0]
1
Bit Name
Open-loop phase
offset (expressed in
π/215 radians)
Description
DDS phase offset, Bits[7:0]
DDS phase offset, Bits[15:8]
The default DDS phase offset is 0.
Table 60. Fixed Closed-Loop Phase Lock Offset 1
Address
030F
0310
0311
0312
0313
1
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
Bit Name
Fixed phase lock offset
(expressed in picoseconds)
Description
Fixed phase lock offset, Bits[7:0]
Fixed phase lock offset, Bits[15:8]
Fixed phase lock offset, Bits[23:16]
Fixed phase lock offset, Bits[31:24]
Fixed phase lock offset, Bits[39:32]
The default fixed closed loop phase lock offset is 0.
Rev. 0 | Page 75 of 112
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Table 61. Incremental Closed-Loop Phase Lock Offset Step Size 1
Address
0314
Bits
[7:0]
0315
[7:0]
1
Bit Name
Incremental phase lock
offset step size
(expressed in picoseconds per step)
Description
Incremental phase lock offset step size, Bits[7:0]
Incremental phase lock offset step size, Bits[15:8]
The default incremental closed-loop phase lock offset step size value is 0x03E8 = 1000 (1 ns).
Table 62. Phase Slew Rate Limit 1
Address
0316
Bits
[7:0]
0317
[7:0]
1
Bit Name
Phase slew limit
(expressed in nanoseconds per second)
Description
Phase slew rate limit, Bits[7:0]
Phase slew rate limit, Bits[15:8]
The default phase slew rate limit is 0 (or disabled).
Table 63. History Accumulation Timer 1
Address
0318
Bits
[7:0]
0319
[7:0]
031A
[7:0]
1
Bit Name
History accumulation
timer (expressed in
milliseconds)
Description
History accumulation timer, Bits[7:0]
History accumulation timer, Bits[15:8]
History accumulation timer, Bits[23:16]
Do not program a timer value of 0. The history accumulation timer default value is 0x007530 = 30,000 (30 sec).
Table 64. History Mode
Address
031B
Bits
[7:5]
[4]
Bit Name
Unused
Single-sample fallback
[3]
Persistent history
[2:0]
Incremental average
Description
Controls the holdover history. If tuning word history is not available for the reference
that was active just prior to holdover, then
0 (default) = use the free running frequency tuning word register value.
1 = use the last tuning word from the DPLL.
Controls the holdover history initialization. When switching to a new reference
0 (default) = clear the tuning word history.
1 = retain the previous tuning word history.
History mode value from 0 to 7 (default = 0).
Rev. 0 | Page 76 of 112
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CLOCK DISTRIBUTION OUTPUT CONFIGURATION (REGISTER 0400 TO REGISTER 0419)
Table 65. Distribution Settings 1
Address
0400
1
Bits
[7:6]
[5]
Bit Name
Unused
External distribution
resistor
[4]
Receiver mode
[3]
OUT3 power-down
[2]
OUT2 power-down
[1]
OUT1 power-down
[0]
OUT0 power-down
Description
Output current control for the clock distribution outputs
0 (default) = internal current setting resistor
1 = external current setting resistor
Clock distribution receiver mode
0 (default) = normal operation
1 = high frequency mode (super-Nyquist)
Power-down clock distribution output OUT3
0 (default) = normal operation
1 = power-down
Power-down clock distribution output OUT2
0 (default) = normal operation
1 = power-down
Power-down clock distribution output OUT1
0 (default) = normal operation
1 = power-down
Power-down clock distribution output OUT0
0 (default) = normal operation
1 = power-down
When Bits[3:0] = 1111, the clock distribution output enters a deep sleep mode.
Table 66. Distribution Enable
Address
0401
Bits
[7:4]
[3]
Bit Name
Unused
OUT3 enable
[2]
OUT2 enable
[1]
OUT1 enable
[0]
OUT0 enable
Description
Enable the OUT3 driver.
0 (default) = disable.
1 = enable.
Enable the OUT2 driver.
0 (default) = disable.
1 = enable.
Enable the OUT1 driver.
0 (default) = disable.
1 = enable.
Enable the OUT0 driver.
0 (default) = disable.
1 = enable.
Rev. 0 | Page 77 of 112
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Table 67. Distribution Synchronization
Address
0402
Bits
[7:6]
[5:4]
Bit Name
Unused
Sync source
[3]
OUT3 sync mask
[2]
OUT2 sync mask
[1]
OUT1 sync mask
[0]
OUT0 sync mask
Description
Select the sync source for the clock distribution output channels.
00 (default) = direct.
01 = active reference.
10 = DPLL feedback edge.
11 = reserved.
Mask the synchronous reset to the OUT3 divider.
0 (default) = unmasked
1 = masked.
Mask the synchronous reset to the OUT2 divider.
0 (default) = unmasked.
1 = masked.
Mask the synchronous reset to the OUT1 divider.
0 (default) = unmasked.
1 = masked.
Mask the synchronous reset to the OUT0 divider.
0 (default) = unmasked.
1 = masked.
Table 68. Automatic Synchronization
Address
0403
Bits
[7:2]
[1:0]
Bit Name
Unused
Automatic sync mode
Description
Autosync mode
00 (default) = disabled
01 = sync on DPLL frequency lock
10 = sync on DPLL phase lock
11 = reserved
Table 69. Distribution Channel Modes
Address
0404
Bits
[7:6]
[5]
Bit Name
Unused
OUT0 CMOS phase
invert
[4]
OUT0 polarity invert
[3]
OUT0 drive strength
[2:0]
OUT0 mode
Description
When the output mode is CMOS, the bit inverts the relative phase between the two
CMOS output pins. Otherwise, this bit is nonfunctional.
0 (default) = not inverted.
1 = inverted.
Invert the polarity of OUT0.
0 (default) = not inverted.
1 = inverted.
OUT0 output drive capability control.
0 (default) = CMOS: low drive strength; LVDS: 3.5 mA nominal.
1 = CMOS: normal drive strength; LVDS: 7 mA nominal.
OUT0 operating mode select.
000 = CMOS (both pins)
001 = CMOS (positive pin), tristate (negative pin).
010 = tristate (positive pin), CMOS (negative pin).
011 (default) = tristate (both pins).
100 = LVDS.
101 = LVPECL.
110 = reserved.
111 = reserved.
Rev. 0 | Page 78 of 112
AD9548
Address
0405
0406
Bits
[7:6]
[5]
Bit Name
Unused
OUT1 CMOS phase
invert
[4]
OUT1 polarity invert
[3]
OUT1 drive strength
[2:0]
OUT1 mode
[7:6]
[5]
Unused
OUT2 CMOS phase
invert
[4]
OUT2 polarity invert
[3]
OUT2 drive strength
[2:0]
OUT2 mode
Description
When the output mode is CMOS, the bit inverts the relative phase between the two
CMOS output pins. Otherwise, this bit is nonfunctional.
0 (default) = not inverted.
1 = inverted.
Invert the polarity of OUT1.
0 (default) = not inverted.
1 = inverted.
OUT1 output drive capability control.
0 (default) = CMOS: low drive strength; LVDS: 3.5 mA nominal.
1 = CMOS: normal drive strength; LVDS: 7 mA nominal.
OUT1 operating mode select.
000 = CMOS (both pins).
001 = CMOS (positive pin), tristate (negative pin).
010 = tristate (positive pin), CMOS (negative pin).
011 (default) = tristate (both pins).
100 = LVDS.
101 = LVPECL.
110 = reserved.
111 = reserved.
When the output mode is CMOS, the bit inverts the relative phase between the two
CMOS output pins. Otherwise, this bit is nonfunctional.
0 (default) = not inverted.
1 = inverted.
Invert the polarity of OUT2.
0 (default) = not inverted.
1 = inverted.
OUT2 output drive capability control.
0 (default) = CMOS: low drive strength; LVDS: 3.5 mA nominal.
1 = CMOS: normal drive strength; LVDS: 7 mA nominal.
OUT2 operating mode select.
000 = CMOS (both pins).
001 = CMOS (positive pin), tristate (negative pin).
010 = tristate (positive pin), CMOS (negative pin).
011 (default) = tristate (both pins).
100 = LVDS.
101 = LVPECL.
110 = reserved.
111 = reserved.
Rev. 0 | Page 79 of 112
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Address
0407
Bits
[7:6]
[5]
Bit Name
Unused
OUT3 CMOS phase
invert
[4]
OUT3 polarity invert
[3]
OUT3 drive strength
[2:0]
OUT3 mode
Description
When the output mode is CMOS, the bit inverts the relative phase between the two
CMOS output pins. Otherwise, this bit is nonfunctional.
0 (default) = not inverted.
1 = inverted.
Invert the polarity of OUT3.
0 (default) = not inverted.
1 = inverted.
OUT3 output drive capability control.
0 (default) = CMOS: low drive strength; LVDS: 3.5 mA nominal.
1 = CMOS: normal drive strength; LVDS: 7 mA nominal.
OUT3 operating mode select.
000 = CMOS (both pins).
001 = CMOS (positive pin), tristate (negative pin).
010 = tristate (positive pin), CMOS (negative pin).
011 (default) = tristate (both pins).
100 = LVDS.
101 = LVPECL.
110 = reserved.
111 = reserved.
Register 0408 to Register 0417—Distribution Channel Dividers
Table 70. Q0 Divider 1
Address
0408
0409
040A
040B
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
Q0
Unused
Q0
Description
Q0 divider, Bits[7:0]
Q0 divider, Bits[15:8]
Q0 divider, Bits[23:16]
Q0 divider, Bits[29:24]
The default value is 0 (or divide by 1).
Table 71. Q1 Divider 1
Address
040C
040D
040E
040F
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
Q1
Unused
Q1
Description
Q1 divider, Bits[7:0]
Q1 divider, Bits[15:8]
Q1 divider, Bits[23:16]
Q1 divider, Bits[29:24]
The default value is 0 (or divide by 1).
Table 72. Q2 Divider 1
Address
0410
0411
0412
0413
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
Q2
Unused
Q2
Description
Q2 divider, Bits[7:0]
Q2 divider, Bits[15:8]
Q2 divider, Bits[23:16]
Q2 divider, Bits[29:24]
The default value is 0 (or divide by 1).
Rev. 0 | Page 80 of 112
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Table 73. Q3 Divider 1
Address
0414
0415
0416
0417
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
Q3
Unused
Q3
Description
Q3 divider, Bits[7:0]
Q3 divider, Bits[15:8]
Q3 divider, Bits[23:16]
Q3 divider, Bits[29:24]
The default value is 0 (or divide by 1).
REFERENCE INPUT CONFIGURATION (REGISTER 0500 TO REGISTER 0507)
Table 74. Reference Power-Down
When all bits are set, the reference receiver section enters a deep sleep mode.
Address
0500
Bits
[7]
Bit Name
Ref DD power-down
[6]
Ref D power-down
[5]
Ref CC power-down
[4]
Ref C power-down
[3]
Ref BB power-down
[2]
Ref B power-down
[1]
Ref AA power-down
[0]
Ref A power-down
Description
REF DD input receiver power-down
0 (default) = normal operation
1 = power-down
REF D input receiver power-down
0 (default) = normal operation
1 = power-down
REF CC input receiver power-down
0 (default) = normal operation
1 = power-down
REF C input receiver power-down
0 (default) = normal operation
1 = power-down
REF BB input receiver power-down
0 (default) = normal operation
1 = power-down
REF B input receiver power-down
0 (default) = normal operation
1 = power-down
REF AA input receiver power-down
0 (default) = normal operation
1 = power-down
REF A input receiver power-down
0 (default) = normal operation
1 = power-down
Rev. 0 | Page 81 of 112
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Table 75. Reference Logic Family
Address
0501
0502
Bits
[7:6]
Bit Name
Ref BB logic family
[5:4]
Ref B logic family
[3:2]
[1:0]
[7:6]
[5:4]
[3:2]
[1:0]
Ref AA logic family
Ref A logic family
Ref DD logic family
Ref D logic family
Ref CC logic family
Ref C logic family
Description
Select the logic family for the REF BB input receiver (ignored if Bits[5:4] = 00)
00 (default) = disabled
01 = 1.2 V to 1.5 V CMOS
10 = 1.8 V to 2.5 V CMOS
11 = 3.0 V to 3.3 V CMOS
Select logic family for REF B input receiver.
00 (default) = differential (REFB/BB is positive/negative input)
01 = 1.2 V to 1.5 V CMOS
10 = 1.8 V to 2.5 V CMOS
11 = 3.0 V to 3.3 V CMOS
The same as Register 0501, Bits[7:6] but for REF AA
The same as Register 0501, Bits[5:4] but for REF A
The same as Register 0501, Bits[7:6] but for REF DD
The same as Register 0501, Bits[5:4] but for REF D
The same as Register 0501, Bits[7:6] but for REF CC
The same as Register 0501, Bits[5:4] but for REF C
Table 76. Manual Reference Profile Selection
Address
0503
0504
Bits
[7]
Bit Name
Enable Ref AA manual
profile
[6:4]
Ref AA manual profile
[3]
Enable Ref A manual
profile
Ref A manual profile
Enable Ref BB manual
profile
Ref BB manual profile
Enable Ref B manual
profile
Ref B manual profile
Enable Ref CC manual
profile
Ref CC manual profile
Enable Ref C manual
profile
Ref C manual profile
Enable Ref DD M
manual profile
Ref DD manual profile
Enable Ref D manual
profile
Ref D manual profile
[2:0]
[7]
[6:4]
[3]
0505
[2:0]
[7]
[6:4]
[3]
0506
[2:0]
[7]
[6:4]
[3]
[2:0]
Description
Select manual or automatic reference profile assignment for REF AA
0 (default) = automatic
1 = manual
Manual profile assignment
000 (default) = Profile 0
001 = Profile 1
010 = Profile 2
011 = Profile 3
100 = Profile 4
101 = Profile 5
110 = Profile 6
111 = Profile 7
Same as Register 0503, Bit 7 but for REF A
Same as Register 0503, Bits[6:4] but for REF A
Same as Register 0503, Bit 7 but for REF B
Same as Register 0503, Bits[6:4] but for REF BB
Same as Register 0503, Bit 7 but for REF B
Same as Register 0503, Bits[6:4] but for REF B
Same as Register 0503, Bit 7 but for REF CC
Same as Register 0503, Bits[6:4] but for REF CC
Same as Register 050, Bit 7 but for REF C
Same as Register 0503, Bits[6:4] but for REF C
Same as Register 0503, Bit 7 but for REF DD
Same as Register 0503, Bits[6:4] but for REF DD
Same as Register 0503, Bit 7 but for REF D
Same as Register 0503, Bits[6:4] but for REF D
Rev. 0 | Page 82 of 112
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Table 77. Phase Build-Out Switching
Address
0507
Bits
[7:3]
[2:0]
Bit Name
Unused
Phase master
threshold priority
Description
Threshold priority level (a value of 0 to 7, with 0 (default) being the highest priority
level). References with a selection priority value lower than this value are treated as
phase masters (see the Profile Registers (Register 0600 to Register 07FF) section for
the selection priority value).
PROFILE REGISTERS (REGISTER 0600 TO REGISTER 07FF)
Note that the default value of every bit is 0 for Profile 0 to Profile 7.
Register 0600 to Register 0631—Profile 0
Table 78. Priorities—Profile 0
Address
0600
Bits
[7:6]
[5:3]
Bit Name
Unused
Promoted priority
[2:0]
Selection priority
Description
User-assigned priority level (0 to 7) of the reference associated with Profile 0 while
that reference is the active reference. The numeric value of the promoted priority
must be less than or equal to the numeric value of the selection priority.
User-assigned priority level (0 to 7) of the reference associated with Profile 0, which
ranks that reference relative to the others.
Table 79. Reference Period—Profile 0
Address
0601
0602
0603
0604
0605
0606
0607
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:2]
[1:0]
Bit Name
Reference period (in
femtoseconds)
Unused
Reference period
Description
Nominal reference period, Bits[7:0]
Nominal reference period, Bits[15:8]
Nominal reference period, Bits[23:16]
Nominal reference period, Bits[31:24]
Nominal reference period, Bits[39:32]
Nominal reference period, Bits[47:40]
Nominal reference period, Bits[49:48]
Table 80. Tolerance—Profile 0
Address
0608
0609
060A
060B
060C
060D
Bits
[7:0]
[7:0]
[7:4]
[3:0]
[7:0]
[7:0]
[7:4]
[3:0]
Bit Name
Inner tolerance
Unused
Inner tolerance
Outer tolerance
Unused
Outer tolerance
Description
Inner tolerance, Bits[7:0]
Inner tolerance, Bits[15:8]
Inner tolerance, Bits[19:16]
Outer tolerance, Bits[7:0]
Outer tolerance, Bits[5:8]
Outer tolerance, Bits[19:16]
Table 81. Validation Timer—Profile 0
Address
060E
060F
Bits
[7:0]
[7:0]
Bit Name
Validation timer
(in milliseconds)
Description
Validation timer, Bits[7:0]
Validation timer, Bits[15:8]
Table 82. Redetect Timer—Profile 0
Address
0610
0611
Bits
[7:0]
[7:0]
Bit Name
Redetect timer
(in milliseconds)
Description
Redetect timer, Bits[7:0]
Redetect timer, Bits[15:8]
Rev. 0 | Page 83 of 112
AD9548
Table 83. Digital Loop Filter Coefficients—Profile 0 1
Address
0612
0613
0614
0615
0616
0617
0618
0619
061A
061B
061C
061D
1
Bits
[7:0]
[7:0]
[7:6]
[5:0]
[7:1]
[0]
[7:0]
[7]
[6:2]
[1:0]
[7:0]
[7:0]
[7:6]
[5:1]
[0]
[7:0]
[7]
[6:0]
[7:4]
[3:0]
Bit Name
Alpha-0 linear
Description
Alpha-0 coefficient linear, Bits[7:0]
Alpha-0 coefficient linear, Bits[15:8]
Alpha-2 coefficient exponent, Bits[1:0]
Alpha-1 coefficient exponent, Bits[5:0]
Beta-0 coefficient linear, Bits[6:0]
Alpha-2 coefficient exponent, Bit 2
Beta-0 coefficient linear, Bits[14:7]
Alpha-2 exponent
Alpha-1 exponent
Beta-0 linear
Alpha-2 exponent
Beta-0 linear
Unused
Beta-1 exponent
Beta-0 linear
Gamma-0 linear
Beta-1 coefficient exponent, Bits[4:0]
Beta-0 coefficient linear, Bits[16:15]
Gamma-0 coefficient linear, Bits[7:0]
Gamma -0 coefficient linear, Bits[15:8]
Unused
Gamma-1 exponent
Gamma-0 linear
Delta-0 linear
Delta-1 exponent
Delta-0 linear
Alpha-3 exponent
Delta-1 exponent
Gamma-1 coefficient exponent, Bits[4:0]
Gamma-0 coefficient linear, Bit 16
Delta-0 coefficient linear, Bits[7:0]
Delta-1 coefficient exponent, Bit 0
Delta-0 coefficient linear, Bits[14:8]
Alpha-3 coefficient exponent, Bits[3:0]
Delta-1 coefficient exponent, Bits[4:1]
The digital loop filter coefficients (α, β, γ, and δ) have the general form: x(2y), where x is the linear component and y is the exponential component of the coefficient. The
value of the linear component (x) constitutes a fraction, where 0 ≤ x < 1. The exponential component (y) is an integer. See the Calculating Digital Filter Coefficients section
for details.
Table 84. R-Divider—Profile 0 1
Address
061E
061F
0620
0621
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
R
Unused
R
Description
R, Bits[7:0]
R, Bits[15:8]
R, Bits[23:16]
R, Bits[29:24]
The value stored in the R-divider register yields an actual divide ratio of one more than the programmed value.
Table 85. S-Divider—Profile 0 1
Address
0622
0623
0624
0625
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
S
Unused
S
Description
S, Bits[7:0]
S, Bits[15:8]
S, Bits[23:16]
S, Bits[29:24]
The value stored in the S-divider register yields an actual divide ratio of one more than the programmed value. Furthermore, the value of S must be at least 7.
Rev. 0 | Page 84 of 112
AD9548
Table 86. Fractional Feedback Divider—Profile 0
Address
0626
0627
0628
Bits
[7:0]
[7:4]
[3:2]
[1:0]
[7:6]
[5:0]
Bit Name
V
U
Unused
V
Unused
U
Description
V, Bits[7:0]
U, Bits[3:0]
V, Bits[9:8]
U, Bits[9:4]
Table 87. Lock Detectors—Profile 0
Address
0629
062A
062B
062C
062D
062E
062F
0630
0631
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
Bit Name
Phase lock threshold
(in picoseconds)
Phase lock fill rate
Phase lock drain rate
Frequency lock threshold (in picoseconds)
Frequency lock fill rate
Frequency lock drain
rate
Description
Phase lock threshold, Bits[7:0]
Phase lock threshold, Bits[15:8]
Phase lock fill rate, Bits[7:0]
Phase lock drain rate, Bits[7:0]
Frequency lock threshold, Bits[7:0]
Frequency lock threshold, Bits[15:8]
Frequency lock threshold, Bits[23:16]
Frequency lock fill rate, Bits[7:0]
Frequency lock drain rate, Bits[7:0]
Register 0632 to Register 067F—Profile 1
Table 88. Priorities—Profile 1
Address
0632
Bits
[7:6]
[5:3]
Bit Name
unused
Promoted priority
[2:0]
Selection priority
Description
User-assigned priority level (0 to 7) of the reference associated with Profile 1 while
that reference is the active reference. The numeric value of the promoted priority
must be less than or equal to the numeric value of the selection priority.
User-assigned priority level (0 to 7) of the reference associated with Profile 1, which
ranks that reference relative to the others.
Table 89. Reference Period—Profile 1
Address
0633
0634
0635
0636
0637
0638
0639
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:2]
[1:0]
Bit Name
Reference period (in
femtoseconds)
Unused
Reference period
Description
Nominal reference period, Bits[7:0]
Nominal reference period, Bits[15:8]
Nominal reference period, Bits[23:16]
Nominal reference period, Bits[31:24]
Nominal reference period, Bits[39:32]
Nominal reference period, Bits[47:40]
Nominal reference period, Bits[49:48]
Rev. 0 | Page 85 of 112
AD9548
Table 90. Tolerance—Profile 1
Address
063A
063B
063C
063D
063E
063F
Bits
[7:0]
[7:0]
[7:4]
[3:0]
[7:0]
[7:0]
[7:4]
[3:0]
Bit Name
Inner tolerance
Unused
Inner tolerance
Outer tolerance
Unused
Outer tolerance
Description
Inner tolerance, Bits[7:0]
Inner tolerance, Bits[15:8]
Inner tolerance, Bits[19:16]
Outer tolerance, Bits[7:0]
Outer tolerance, Bits[15:8]
Outer tolerance, Bits[19:16]
Table 91. Validation Timer—Profile 1
Address
0640
0641
Bits
[7:0]
[7:0]
Bit Name
Validation timer
(in milliseconds)
Description
Validation timer, Bits[7:0]
Validation timer, Bits[15:8]
Table 92. Redetect Timer—Profile 1
Address
0642
0643
Bits
[7:0]
[7:0]
Bit Name
Redetect timer
(in milliseconds)
Description
Redetect timer, Bits[7:0]
Redetect timer, Bits[15:8]
Table 93. Digital Loop Filter Coefficients—Profile 1 1
Address
0644
0645
0646
0647
0648
0649
064A
064B
064C
064D
064E
064F
1
Bits
[7:0]
[7:0]
[7:6]
[5:0]
[7:1]
[0]
[7:0]
[7]
[6:2]
[1:0]
[7:0]
[7:0]
[7:6]
[5:1]
[0]
[7:0]
[7]
[6:0]
[7:4]
[3:0]
Bit Name
Alpha-0 linear
Alpha-2 exponent
Alpha-1 exponent
Beta -0 linear
Alpha-2 exponent
Beta-0 linear
Unused
Beta-1 exponent
Beta-0 linear
Gamma-0 linear
Unused
Gamma-1 exponent
Gamma-0 linear
Delta-0 linear
Delta-1 exponent
Delta-0 linear
Alpha-3 exponent
Delta-1 exponent
Description
Alpha-0 coefficient linear, Bits[7:0]
Alpha-0 coefficient linear, Bits[15:8]
Alpha-2 coefficient exponent, Bits[1:0]
Alpha-1 coefficient exponent, Bits[5:0]
Beta-0 coefficient linear, Bits[6:0]
Alpha-2 coefficient exponent, Bit 2
Beta-0 coefficient linear, Bits[14:7]
Beta-1 coefficient exponent, Bits[4:0]
Beta-0 coefficient linear, Bits[16:15]
Gamma-0 coefficient linear, Bits[7:0]
Gamma-0 coefficient linear, Bits[15:8]
Gamma-1 coefficient exponent, Bits[4:0]
Gamma-0 coefficient linear, Bit 16
Delta-0 coefficient linear, Bits[7:0]
Delta-1 coefficient exponent, Bit 0
Delta-0 coefficient linear, Bits[14:8]
Alpha-3 coefficient exponent, Bits[3:0]
Delta-1 coefficient exponent, Bits[4:1]
The digital loop filter coefficients (α, β, γ, and δ) have the general form: x(2y), where x is the linear component and y is the exponential component of the coefficient. The
value of the linear component (x) constitutes a fraction, where 0 ≤ x < 1. The exponential component (y) is an integer. See the Calculating Digital Filter Coefficients section
for details.
Rev. 0 | Page 86 of 112
AD9548
Table 94. R-Divider—Profile 1 1
Address
0650
0651
0652
0653
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
R
Unused
R
Description
R, Bits[7:0]
R, Bits[15:8]
R, Bits[23:16]
R, Bits[29:24]
The value stored in the R-divider register yields an actual divide ratio of one more than the programmed value.
Table 95. S-Divider—Profile 1 1
Address
0654
0655
0656
0657
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
S
Unused
S
Description
S, Bits[7:0]
S, Bits[15:8]
S, Bits[23:16]
S, Bits[29:24]
The value stored in the S-divider register yields an actual divide ratio of one more than the programmed value. Furthermore, the value of S must be at least 7.
Table 96. Fractional Feedback Divider—Profile 1
Address
0658
0659
065A
Bits
[7:0]
[7:4]
[3:2]
[1:0]
[7:6]
[5:0]
Bit Name
V
U
Unused
V
Unused
U
Description
V, Bits[7:0]
U, Bits[3:0]
V, Bits[9:8]
U, Bits[9:4]
Table 97. Lock Detectors—Profile 1
Address
065B
065C
065D
065E
065F
0660
0661
0662
0663
0664 to 067F
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
Bit Name
Phase lock threshold
(in picoseconds)
Phase lock fill rate
Phase lock drain rate
Frequency lock threshold
(in picoseconds)
Frequency lock fill rate
Frequency lock drain rate
Unused
Description
Phase lock threshold, Bits[7:0]
Phase lock threshold, Bits[15:8]
Phase lock fill rate, Bits[7:0]
Phase lock drain rate, Bits[7:0]
Frequency lock threshold, Bits[7:0]
Frequency lock threshold, Bits[15:8]
Frequency lock threshold, Bits[23:16]
Frequency lock fill rate, Bits[7:0]
Frequency lock drain rate, Bits[7:0]
Register 0680 to Register 06B1—Profile 2
Table 98. Priorities—Profile 2
Address
0680
Bits
[7:6]
[5:3]
Bit Name
Unused
Promoted priority
[2:0]
Selection priority
Description
User-assigned priority level (0 to 7) of the reference associated with Profile 2 while
that reference is the active reference. The numeric value of the promoted priority
must be less than or equal to the numeric value of the selection priority.
User-assigned priority level (0 to 7) of the reference associated with Profile 2, which
ranks that reference relative to the others.
Rev. 0 | Page 87 of 112
AD9548
Table 99. Reference Period—Profile 2
Address
0681
0682
0683
0684
0685
0686
0687
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:2]
[1:0]
Bit Name
Reference period (in
femtoseconds)
Unused
Reference period
Description
Nominal reference period, Bits[7:0]
Nominal reference period, Bits[15:8]
Nominal reference period, Bits[23:16]
Nominal reference period, Bits[31:24]
Nominal reference period, Bits[39:32]
Nominal reference period, Bits[47:40]
Nominal reference period, Bits[49:48]
Table 100. Tolerance—Profile 2
Address
0688
0689
068A
068B
068C
068D
Bits
[7:0]
[7:0]
[7:4]
[3:0]
[7:0]
[7:0]
[7:4]
[3:0]
Bit Name
Inner tolerance
Unused
Inner tolerance
Outer tolerance
Unused
Outer tolerance
Description
Inner tolerance, Bits[7:0]
Inner tolerance, Bits[15:8]
Inner tolerance, Bits[19:16]
Outer tolerance, Bits[7:0]
Outer tolerance, Bits[15:8]
Outer tolerance, Bits[19:16]
Table 101. Validation Timer—Profile 2
Address
068E
068F
Bits
[7:0]
[7:0]
Bit Name
Validation timer
(in milliseconds)
Description
Validation timer, Bits[7:0]
Validation timer, Bits[15:8]
Table 102. Redetect Timer—Profile 2
Address
0690
0691
Bits
[7:0]
[7:0]
Bit Name
Redetect timer
(in milliseconds)
Description
Redetect timer, Bits[7:0]
Redetect timer, Bits[15:8]
Table 103. Digital Loop Filter Coefficients—Profile 2 1
Address
0692
0693
0694
0695
0696
0697
0698
0699
069A
069B
Bits
[7:0]
[7:0]
[7:6]
[5:0]
[7:1]
[0]
[7:0]
[7]
[6:2]
[1:0]
[7:0]
[7:0]
[7:6]
[5:1]
[0]
[7:0]
Bit Name
Alpha-0 linear
Alpha-2 exponent
Alpha-1 exponent
Beta-0 linear
Alpha-2 exponent
Beta 0-linear
Unused
Beta-1 exponent
Beta-0 linear
Gamma-0 linear
Unused
Gamma-1 exponent
Gamma-0 linear
Delta -0 linear
Description
Alpha-0 coefficient linear, Bits[7:0]
Alpha-0 coefficient linear, Bits[15:8]
Alpha-2 coefficient exponent, Bits[1:0]
Alpha-1 coefficient exponent, Bits[5:0]
Beta-0 coefficient linear, Bits[6:0]
Alpha-2 coefficient exponent, Bit 2
Beta-0 coefficient linear, Bits[14:7]
Beta-1 coefficient exponent, Bits[4:0]
Beta-0 coefficient linear, Bits[16:15]
Gamma-0 coefficient linear, Bits[7:0]
Gamma-0 coefficient linear, Bits[15:8]
Gamma-1 coefficient exponent, Bits[4:0]
Gamma-0 coefficient linear, Bit 6
Delta-0 coefficient linear, Bits[7:0]
Rev. 0 | Page 88 of 112
AD9548
Address
069C
069D
1
Bits
[7]
[6:0]
[7:4]
[3:0]
Bit Name
Delta-1 exponent
Delta-0 linear
Alpha-3 exponent
Delta-1 exponent
Description
Delta-1 coefficient exponent, Bit 0
Delta-0 coefficient linear, Bits[14:8]
Alpha-3 coefficient exponent, Bits[3:0]
Delta-1 coefficient exponent, Bits[4:1]
The digital loop filter coefficients (α, β, γ, and δ) have the general form: x(2y), where x is the linear component and y is the exponential component of the coefficient. The
value of the linear component (x) constitutes a fraction, where 0 ≤ x < 1. The exponential component (y) is an integer. See the Calculating Digital Filter Coefficients section
for details.
Table 104. R-Divider—Profile 2 1
Address
069E
069F
06A0
06A1
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
R
Unused
R
Description
R, Bits[7:0]
R, Bits[15:8]
R, Bits[23:16]
R, Bits[29:24]
The value stored in the R-divider register yields an actual divide ratio of one more than the programmed value.
Table 105. S-Divider—Profile 2 1
Address
06A2
06A3
06A4
06A5
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
S
Unused
S
Description
S, Bits[7:0]
S, Bits[15:8]
S, Bits[23:16]
S, Bits[29:24]
The value stored in the S-divider register yields an actual divide ratio of one more than the programmed value. Furthermore, the value of S must be at least 7.
Table 106. Fractional Feedback Divider—Profile 2
Address
06A6
06A7
06A8
Bits
[7:0]
[7:4]
[3:2]
[1:0]
[7:6]
[5:0]
Bit Name
V
U
Unused
V
Unused
U
Description
V, Bits[7:0]
U, Bits[3:0]
V, Bits[9:8]
U, Bits[9:4]
Table 107. Lock Detectors—Profile 2
Address
06A9
06AA
06AB
06AC
06AD
06AE
06AF
06B0
06B1
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
Bit Name
Phase lock threshold
(in picoseconds)
Phase lock fill rate
Phase lock drain rate
Frequency lock threshold (in picoseconds)
Frequency lock fill rate
Frequency lock drain
rate
Description
Phase lock threshold, Bits[7:0]
Phase lock threshold, Bits[15:8]
Phase lock fill rate, Bits[7:0]
Phase lock drain rate, Bits[7:0]
Frequency lock threshold, Bits[7:0]
Frequency lock threshold, Bits[15:8]
Frequency lock threshold, Bits[23:16]
Frequency lock fill rate, Bits[7:0]
Frequency lock drain rate, Bits[7:0]
Rev. 0 | Page 89 of 112
AD9548
Register 06B2 to Register 07FF—Profile 3
Table 108. Priorities—Profile 3
Address
06B2
Bits
[7:6]
[5:3]
Bit Name
Unused
Promoted priority
[2:0]
Selection priority
Description
User-assigned priority level (0 to 7) of the reference associated with Profile 3 while
that reference is the active reference. The numeric value of the promoted priority
must be less than or equal to the numeric value of the selection priority.
User-assigned priority level (0 to 7) of the reference associated with Profile 3, which
ranks that reference relative to the others.
Table 109. Reference Period—Profile 3
Address
06B3
06B4
06B5
06B6
06B7
06B8
06B9
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:2]
[1:0]
Bit Name
Reference period (in
femtoseconds)
Unused
Reference period
Description
Nominal reference period, Bits[7:0]
Nominal reference period, Bits[15:8]
Nominal reference period, Bits[23:16]
Nominal reference period, Bits[31:24]
Nominal reference period, Bits[39:32]
Nominal reference period, Bits[47:40]
Nominal reference period, Bits[49:48]
Table 110. Tolerance—Profile 3
Address
06BA
06BB
06BC
06BD
06BE
06BF
Bits
[7:0]
[7:0]
[7:4]
[3:0]
[7:0]
[7:0]
[7:4]
[3:0]
Bit Name
Inner tolerance
Unused
Inner tolerance
Outer tolerance
Unused
Outer tolerance
Description
Inner tolerance, Bits[7:0]
Inner tolerance, Bits[15:8]
Inner tolerance, Bits[19:16]
Outer tolerance, Bits[7:0]
Outer tolerance, Bits[15:8]
Outer tolerance, Bits[19:16]
Table 111. Validation Timer—Profile 3
Address
06C0
06C1
Bits
[7:0]
[7:0]
Bit Name
Validation timer
(in milliseconds)
Description
Validation timer, Bits[7:0]
Validation timer, Bits[15:8]
Table 112. Redetect Timer—Profile 3
Address
06C2
06C3
Bits
[7:0]
[7:0]
Bit Name
Redetect timer
(in milliseconds)
Description
Redetect timer, Bits[7:0]
Redetect timer, Bits[15:8]
Table 113. Digital Loop Filter Coefficients—Profile 3 1
Address
06C4
06C5
06C6
06C7
06C8
06C9
Bits
[7:0]
[7:0]
[7:6]
[5:0]
[7:1]
[0]
[7:0]
[7]
[6:2]
[1:0]
Bit Name
Alpha-0 linear
Alpha-2 exponent
Alpha-1 exponent
Beta-0 linear
Alpha-2 exponent
Beta-0 linear
Unused
Beta-1 exponent
Beta-0 linear
Description
Alpha-0 coefficient linear, Bits[7:0]
Alpha-0 coefficient linear, Bits[15:8]
Alpha-2 coefficient exponent, Bits[1:0]
Alpha-1 coefficient exponent, Bits[5:0]
Beta-0 coefficient linear, Bits[6:0]
Alpha-2 coefficient exponent, Bit 2
Beta-0 coefficient linear, Bits[14:7]
Beta-1 coefficient exponent, Bits[4:0]
Beta-0 coefficient linear, Bits[16:15]
Rev. 0 | Page 90 of 112
AD9548
Address
06CA
06CB
06CC
06CD
06CE
06CF
1
Bits
[7:0]
[7:0]
[7:6]
[5:1]
[0]
[7:0]
[7]
[6:0]
[7:4]
[3:0]
Bit Name
Gamma-0 linear
Unused
Gamma-1 exponent
Gamma-0 linear
Delta-0 linear
Delta-1 exponent
Delta-0 linear
Alpha-3 exponent
Delta-1 exponent
Description
Gamma-0 coefficient linear, Bits[7:0]
Gamma-0 coefficient linear, Bits[15:8]
Gamma-1 coefficient exponent, Bits[4:0]
Gamma-0 coefficient linear, Bit 16
Delta-0 coefficient linear, Bits[7:0]
Delta-1 coefficient exponent, Bit 0
Delta-0 coefficient linear, Bits[14:8]
Alpha-3 coefficient exponent, Bits[3:0]
Delta-1 coefficient exponent, Bits[4:1]
The digital loop filter coefficients (α, β, γ, and δ) have the general form: x(2y), where x is the linear component and y is the exponential component of the coefficient. The
value of the linear component (x) constitutes a fraction, where 0 ≤ x < 1. The exponential component (y) is an integer. See the Calculating Digital Filter Coefficients section
for details.
Table 114. R Divider—Profile 3 1
Address
06D0
06D1
06D2
06D3
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
R
Unused
R
Description
R, Bits[7:0]
R, Bits[15:8]
R, Bits[23:16]
R, Bits[29:24]
The value stored in the R-divider register yields an actual divide ratio of one more than the programmed value.
Table 115. S Divider—Profile 3 1
Address
06D4
06D5
06D6
06D7
1
Bits
[7:0]
[7:0]
[7:0]
[7:6]
[5:0]
Bit Name
S
Unused
S
Description
S, Bits[7:0]
S, Bits[15:8]
S, Bits[23:16]
S, Bits[29:24]
The value stored in the S-divider register yields an actual divide ratio of one more than the programmed value. Furthermore, the value of S must be at least 7.
Table 116. Fractional Feedback Divider—Profile 3
Address
06D8
06D9
06DA
Bits
[7:0]
[7:4]
[3:2]
[1:0]
[7:6]
[5:0]
Bit Name
V
U
Unused
V
Unused
U
Description
V, Bits[7:0]
U, Bits[3:0]
V, Bits[9:8]
U, Bits[9:4]
Rev. 0 | Page 91 of 112
AD9548
Table 117. Lock Detectors—Profile 3
Address
06DB
06DC
06DD
06DE
06DF
06E0
06E1
06E2
06E3
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
06E4 to 06FF
[7:0]
Bit Name
Phase lock threshold
(in picoseconds)
Phase lock fill rate
Phase lock drain rate
Frequency lock threshold (in picoseconds)
Frequency lock fill rate
Frequency lock drain
rate
Unused
Description
Phase lock threshold, Bits[7:0]
Phase lock threshold, Bits[15:8]
Phase lock fill rate, Bits[7:0]
Phase lock drain rate, Bits[7:0]
Frequency lock threshold, Bits[7:0]
Frequency lock threshold, Bits[15:8]
Frequency lock threshold, Bits[23:16]
Frequency lock fill rate, Bits[7:0]
Frequency lock drain rate, Bits[7:0]
Register 0700 to Register 07FF—Profile 4 to Profile 7
Profile 4 (Register 0700 to Register 0731) is identical to Profile 0 (Register 0600 to Register0631).
Profile 5 (Register 0732 to Register 077F) is identical to Profile 1 (Register 0632 to Register 067F).
Profile 6 (Register 0780 to Register 07B1) is identical to Profile 2 (Register 0680 to Register 06B1).
Profile 7 (Register 07B2 to Register 07FF) is identical to Profile 3 (Register 06B2 to Register 06FF).
OPERATIONAL CONTROLS (REGISTER 0A00 TO REGISTER 0A10)
Table 118. General Power-Down
Address
0A00
Bits
[7]
Bit Name
Reset sans reg map
[6]
[5]
Unused
SYSCLK power-down
[4]
Reference powerdown
[3]
TDC power-down
[2]
DAC power-down
[1]
Dist power-down
[0]
Full power-down
Description
Reset internal hardware but retain programmed register values.
0 (default) = normal operation.
1 = reset.
Place SYSCLK input and PLL in deep sleep mode.
0 (default) = normal operation.
1 = power-down.
Place reference clock inputs in deep sleep mode.
0 (default) = normal operation.
1 = power-down.
Place the time-to-digital converter in deep sleep mode.
0 (default) = normal operation.
1 = power-down.
Place the DAC in deep sleep mode.
0 (default) = normal operation.
1 = power-down.
Place the clock distribution outputs in deep sleep mode.
0 (default) = normal operation.
1 = power-down.
Place the entire device in deep sleep mode.
0 (default) = normal operation.
1 = power-down.
Rev. 0 | Page 92 of 112
AD9548
Table 119. Loop Mode
Address
0A01
Bits
[7]
[6]
Bit Name
Unused
User holdover
[5]
User freerun
[4:3]
User selection mode
[2:0]
User reference
selection
Description
Force the device into holdover mode.
0 (default) = normal operation.
1 = force device into holdover mode.
The device behaves as though all input references are faulted.
Force the device into free-run mode.
0 (default) = normal operation.
1 = force device into free-run mode.
The free running frequency tuning word register specifies the DDS output frequency.
Note that, when the user freerun bit is set, it overrides the user holdover bit.
Select the operating mode of the reference switching state machine.
00 (default) = automatic mode. The fully automatic priority-based algorithm selects the
active reference (Bits[2:0] are ignored).
01 = fallback mode. The active reference is the user reference (Bits[2:0]) as long as it is
valid. Otherwise, use the fully automatic priority-based algorithm to select the active
reference.
10 = holdover mode. The active reference is the user reference (Bits[2:0]) as long as it is
valid. Otherwise, enter holdover mode.
11 = manual mode. The active reference is always the user reference (Bits[2:0]). When
using manual mode, be sure that the reference declared as the user reference (Bits[2:0])
is programmed for manual reference-to-profile assignment in the appropriate manual
reference profile selection register (Address 0503 to Address 0506).
Input reference when user selection mode = 01, 10, or 11.
000 (default) = Input Reference A
001 = Input Reference AA
010 = Input Reference B
011 = Input Reference BB
100 = Input Reference C
101 = Input Reference CC
110 = Input Reference D
111 = Input Reference DD
Table 120. Cal/Sync
Address
0A02
Bits
[7:2]
[1]
Bit Name
unused
Sync distribution
[0]
Calibrate system clock
Description
Setting this bit (default = 0) initiates synchronization of the clock distribution output.
While this bit = 1, the clock distribution output stalls. Synchronization occurs on the 1 to
0 transition of this bit.
Setting this bit (default = 0) initiates an internal calibration of the SYSCLK PLL (assuming
it is enabled). The calibration routine automatically selects the proper VCO frequency
band and signal amplitude. The internal system clock stalls during the calibration
procedure, disabling the device until the calibration is complete (a few milliseconds).
Rev. 0 | Page 93 of 112
AD9548
Register 0A03—ResetFunc
Table 121. Reset Functions 1
Address
0A03
1
Bits
[7]
[6]
[5]
[4]
[3]
Bit Name
Unused
Clear LF
Clear CCI
Clear phase
accumulator
Reset auto sync
[2]
Reset TW history
[1]
Reset all IRQs
[0]
Reset watchdog
Description
Setting this bit (default = 0) clears the digital loop filter (intended as a debug tool).
Setting this bit (default = 0) clears the CCI filter (intended as a debug tool).
Setting this bit (default = 0) clears DDS phase accumulator (not a recommended
action).
Setting this bit (default = 0) resets the automatic synchronization logic
(see Register 0403).
Setting this bit (default = 0) resets the tuning word history logic (part of holdover
functionality).
Setting this bit (default = 0) clears the entire IRQ monitor register (Register 0D02 to
Register 0D09). It is the equivalent of setting all the bits of the IRQ clearing register
(Register 0A04 to Register 0A0B).
Setting this bit (default = 0) resets the watchdog timer (see Register 0211 to Register
0212). If the timer had timed out, it simply starts a new timing cycle. If the timer has not
yet timed out, it restarts at time zero without causing a timeout event. Continuously
resetting the watchdog timer at intervals less than its timeout period prevents the
watchdog timer from generating a timeout event.
All bits in this register are autoclearing.
Register 0A04 to Register 0A0B—IRQ Clearing
The IRQ clearing registers are identical in format to the IRQ monitor registers (Address 0D02 to Address 0D09). When set to Logic 1, an IRQ
clearing bit resets the corresponding IRQ monitor bit, thereby canceling the interrupt request for the indicated event. The IRQ clearing
register is an autoclearing register.
Table 122. IRQ Clearing for SYSCLK
Address
0A04
Bits
[7:6]
[5]
[4]
[3:2]
[1]
[0]
Bit Name
Unused
SYSCLK unlocked
SYSCLK locked
Unused
SYSCLK Cal complete
SYSCLK Cal started
Description
Clears SYSCLK unlocked IRQ
Clears SYSCLK locked IRQ
Clears SYSCLK calibration complete IRQ
Clears SYSCLK calibration started IRQ
Table 123. IRQ Clearing for Distribution Sync, Watchdog Timer, and EEPROM
Address
0A05
Bits
[7:4]
[3]
[2]
[1]
[0]
Bit Name
Unused
Distribution sync
Watchdog timer
EEPROM fault
EEPROM complete
Description
Clears distribution sync IRQ
Clears watchdog timer IRQ
Clears EEPROM fault IRQ
Clears EEPROM complete IRQ
Table 124. IRQ Clearing for the Digital PLL
Address
0A06
Bits
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
Bit Name
Switching
Closed
Freerun
Holdover
Freq unlocked
Freq locked
Phase unlocked
Phase locked
Description
Clears switching IRQ
Clears closed IRQ
Clears freerun IRQ
Clears holdover IRQ
Clears frequency unlocked IRQ
Clears frequency locked IRQ
Clears phase unlocked IRQ
Clears phase locked IRQ
Rev. 0 | Page 94 of 112
AD9548
Table 125. IRQ Clearing for History Update, Frequency Limit, and Phase Slew Limit
Address
0A07
Bits
[7:5]
[4]
[3]
[2]
[1]
[0]
Bit Name
Unused
History updated
Frequency unclamped
Frequency clamped
Phase slew unlimited
Phase slew limited
Description
Clears history updated IRQ
Clears frequency unclamped IRQ
Clears frequency clamped IRQ
Clears phase slew unlimited IRQ
Clears phase slew limited IRQ
Table 126. IRQ Clearing for Reference Inputs
Address
0A08
0A09
0A0A
0A0B
Bits
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
Bit Name
Ref AA new profile
Ref AA validated
Ref AA fault cleared
Ref AA fault
Ref A new profile
Ref A validated
Ref A fault cleared
Ref A fault
Ref BB new profile
Ref BB validated
Ref BB fault cleared
Ref BB fault
Ref B new profile
Ref B validated
Ref B fault cleared
Ref B fault
Ref CC new profile
Ref CC validated
Ref CC fault cleared
Ref CC fault
Ref C new profile
Ref C validated
Ref C fault cleared
Ref C fault
Ref DD new profile
Ref DD validated
Ref DD fault cleared
Ref DD fault
Ref D new profile
Ref D validated
Ref D fault cleared
Ref D fault
Description
Clears Ref AA new profile IRQ
Clears Ref AA validated IRQ
Clears Ref AA fault cleared IRQ
Clears Ref AA fault IRQ
Clears Ref A new profile IRQ
Clears Ref A validated IRQ
Clears Ref A fault cleared IRQ
Clears Ref A fault IRQ
Clears Ref BB new profile IRQ
Clears Ref BB validated IRQ
Clears Ref BB fault cleared IRQ
Clears Ref BB fault IRQ
Clears Ref B new profile IRQ
Clears Ref B validated IRQ
Clears Ref B fault cleared IRQ
Clears Ref B fault IRQ
Clears Ref CC new profile IRQ
Clears Ref CC validated IRQ
Clears Ref CC fault cleared IRQ
Clears Ref CC fault IRQ
Clears Ref C new profile IRQ
Clears Ref C validated IRQ
Clears Ref C fault cleared IRQ
Clears Ref C fault IRQ
Clears Ref DD new profile IRQ
Clears Ref DD validated IRQ
Clears Ref DD fault cleared IRQ
Clears Ref DD fault IRQ
Clears Ref D new profile IRQ
Clears Ref D validated IRQ
Clears Ref D fault cleared IRQ
Clears Ref D fault IRQ
Rev. 0 | Page 95 of 112
AD9548
Table 127. Incremental Phase Offset Control
Address
0A0C
Bits
[7:3]
[2]
Bit Name
Unused
Reset phase offset
[1]
Decr phase offset
[0]
Incr phase offset
Description
Resets the incremental phase offset to 0.
This is an autoclearing bit.
Decrements the incremental phase offset by the amount specified in the incremental
phase lock offset step size register (Register 0314 to Register 0315).
This is an autoclearing bit.
Increments the incremental phase offset by the amount specified in the incremental
phase lock offset step size register (Register 0314 to Register 0315).
This is an autoclearing bit.
Table 128. Reference Profile Selection State Machine Startup 1
Address
0A0D
1
Bits
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
Bit Name
Detect DD
Detect D
Detect CC
Detect C
Detect BB
Detect B
Detect AA
Detect A
Description
Setting this bit starts the profile selection state machine for Input Reference DD.
Setting this bit starts the profile selection state machine for Input Reference D.
Setting this bit starts the profile selection state machine for Input Reference CC.
Setting this bit starts the profile selection state machine for Input Reference C.
Setting this bit starts the profile selection state machine for Input Reference BB.
Setting this bit starts the profile selection state machine for Input Reference B.
Setting this bit starts the profile selection state machine for Input Reference AA.
Setting this bit starts the profile selection state machine for Input Reference A.
All bits in this register are autoclearing.
Table 129. Reference Validation Override Controls 1
Address
0A0E
Bits
[7]
Bit Name
Force Timeout DD
[6]
Force Timeout D
[5]
Force Timeout CC
[4]
Force Timeout C
[3]
Force Timeout BB
[2]
Force Timeout B
[1]
Force Timeout AA
[0]
Force Timeout A
Description
Setting this bit emulates a timeout of the validation timer for Reference DD.
This is an autoclearing bit.
Setting this bit emulates a timeout of the validation timer for Reference D.
This is an autoclearing bit.
Setting this bit emulates a timeout of the validation timer for Reference CC.
This is an autoclearing bit.
Setting this bit emulates a timeout of the validation timer for Reference C.
This is an autoclearing bit.
Setting this bit emulates a timeout of the validation timer for Reference BB.
This is an autoclearing bit.
Setting this bit emulates a timeout of the validation timer for Reference B.
This is an autoclearing bit.
Setting this bit emulates a timeout of the validation timer for Reference AA.
This is an autoclearing bit.
Setting this bit emulates a timeout of the validation timer for Reference A.
This is an autoclearing bit.
Rev. 0 | Page 96 of 112
AD9548
Address
0A0F
0A10
1
Bits
[7]
Bit Name
Ref Mon Override DD
[6]
Ref Mon Override D
[5]
Ref Mon Override CC
[4]
Ref Mon Override C
[3]
Ref Mon Override BB
[2]
Ref Mon Override B
[1]
Ref Mon Override AA
[0]
Ref Mon Override A
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
Ref Mon Bypass DD
Ref Mon Bypass D
Ref Mon Bypass CC
Ref Mon Bypass C
Ref Mon Bypass BB
Ref Mon Bypass B
Ref Mon Bypass AA
Ref Mon Bypass A
Description
Overrides the reference monitor REF fault signal for Reference DD (default = 0, not
overridden).
Overrides the reference monitor REF fault signal for Reference D (default = 0, not
overridden).
Overrides the reference monitor REF fault signal for Reference CC (default = 0, not
overridden).
Overrides the reference monitor REF fault signal for Reference C (default = 0, not
overridden).
Overrides the reference monitor REF fault signal for Reference BB (default = 0, not
overridden).
Overrides the reference monitor REF fault signal for Reference B (default = 0, not
overridden).
Overrides the reference monitor REF fault signal for Reference AA (default = 0, not
overridden).
Overrides the reference monitor REF fault signal for Reference A (default = 0, not
overridden).
Bypasses the reference monitor for Reference DD (default = 0, not bypassed).
Bypasses the reference monitor for Reference D (default = 0, not bypassed).
Bypasses the reference monitor for Reference CC (default = 0, not bypassed).
Bypasses the reference monitor for Reference C (default = 0, not bypassed).
Bypasses the reference monitor for Reference BB (default = 0, not bypassed).
Bypasses the reference monitor for Reference B (default = 0, not bypassed).
Bypasses the reference monitor for Reference AA (default = 0, not bypassed).
Bypasses the reference monitor for Reference A (default = 0, not bypassed).
See Figure 34 for details.
STATUS READBACK (REGISTER 0D00 TO REGISTER 0D19)
All bits in Register 0D00 to Register 0D19 are read only.
Table 130. EEPROM Status
Address
0D00
Bits
[7:3]
[2]
[1]
[0]
Bit Name
Unused
Fault detected
Load in progress
Save in progress
Description
An error occurred while saving data to or loading data from the EEPROM.
The control logic sets this bit while data is being read from the EEPROM.
The control logic sets this bit while data is being written to the EEPROM.
Table 131. SYSCLK Status
Address
0D01
Bits
[7:5]
[4]
Bit Name
Unused
Stable
[3:2]
[1]
[0]
Unused
Cal in progress
Lock detected
Description
The control logic sets this bit when the device considers the system clock to be stable
(see the System Clock Stability Timer section).
The control logic holds this bit set while the system clock calibration is in progress.
Indicates the status of the system clock PLL.
0 = unlocked.
1 = locked (or the PLL is disabled).
Rev. 0 | Page 97 of 112
AD9548
Register 0D02 to Register 0D09—IRQ Monitor
If not masked via the IRQ mask register (Address 0209 to Address 0210), then the appropriate IRQ monitor bit is set to a Logic 1 when the
indicated event occurs. These bits can only be cleared via the IRQ clearing register (Address 0A04 to Address 0A0B), the reset all IRQs bit
(Register 0A03, Bit 1), or a device reset.
Table 132. IRQ Monitor for SYSCLK
Address
0D02
Bits
[7:6]
[5]
[4]
[3:2]
[1]
[0]
Bit Name
Unused
SYSCLK unlocked
SYSCLK locked
Unused
SYSCLK Cal complete
SYSCLK Cal started
Description
Indicates a SYSCLK PLL state transition from locked to unlocked
Indicates a SYSCLK PLL state transition from unlocked to locked
Indicates that SYSCLK calibration has completed
Indicates that SYSCLK calibration has begun
Table 133. IRQ Monitor for Distribution Sync, Watchdog Timer, and EEPROM
Address
0D03
Bits
[7:4]
[3]
[2]
[1]
[0]
Bit Name
Unused
Distribution sync
Watchdog timer
EEPROM fault
EEPROM complete
Description
Indicates a distribution sync event
Indicates expiration of the watchdog timer
Indicates a fault during an EEPROM load or save operation
Indicates successful completion of an EEPROM load or save operation
Table 134. IRQ Monitor for the Digital PLL
Address
0D04
Bits
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
Bit Name
Switching
Closed
Freerun
Holdover
Freq unlocked
Freq locked
Phase unlocked
Phase locked
Description
Indicates that the DPLL is switching to a new reference
Indicates that the DPLL has entered closed-loop operation
Indicates that the DPLL has entered free-run mode
Indicates that the DPLL has entered holdover mode
Indicates that the DPLL lost frequency lock
Indicates that the DPLL has acquired frequency lock
Indicates that the DPLL lost phase lock
Indicates that the DPLL has acquired phase lock
Table 135. IRQ Monitor for History Update, Frequency Limit, and Phase Slew Limit
Address
0D05
Bits
[7:5]
[4]
[3]
[2]
[1]
[0]
Bit Name
Unused
History updated
Freq unclamped
Freq clamped
Phase slew unlimited
Phase slew limited
Description
Indicates the occurrence of a tuning word history update
Indicates a frequency limiter state transition from clamped to unclamped
Indicates a frequency limiter state transition from unclamped to clamped
Indicates a phase slew limiter state transition from slew limiting to not slew limiting
Indicates a phase slew limiter state transition from not slew limiting to slew limiting
Table 136. IRQ Monitor for Reference Inputs
Address
0D06
Bits
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
Bit Name
Ref AA new profile
Ref AA validated
Ref AA fault cleared
Ref AA fault
Ref A new profile
Ref A validated
Ref A fault cleared
Ref A fault
Description
Indicates that Ref AA has switched to a new profile
Indicates that Ref AA has been validated
Indicates that Ref AA has been cleared of a previous fault
Indicates that Ref AA has been faulted
Indicates that Ref A has switched to a new profile
Indicates that Ref A has been validated
Indicates that Ref A has been cleared of a previous fault
Indicates that Ref A has been faulted
Rev. 0 | Page 98 of 112
AD9548
Address
0D07
0D08
0D09
Bits
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
Bit Name
Ref BB new profile
Ref BB validated
Ref BB fault cleared
Ref BB fault
Ref B new profile
Ref B validated
Ref B fault cleared
Ref B fault
Ref CC new profile
Ref CC validated
Ref CC fault cleared
Ref CC fault
Ref C new profile
Ref C validated
Ref C fault cleared
Ref C fault
Ref DD new profile
Ref DD validated
Ref DD fault cleared
Ref DD fault
Ref D new profile
Ref D validated
Ref D fault cleared
Ref D fault
Description
Indicates that Ref BB has switched to a new profile
Indicates that Ref BB has been validated
Indicates that Ref BB has been cleared of a previous fault
Indicates that Ref BB has been faulted
Indicates that Ref B has switched to a new profile
Indicates that Ref B has been validated
Indicates that Ref B has been cleared of a previous fault
Indicates that Ref B has been faulted
Indicates that Ref CC has switched to a new profile
Indicates that Ref CC has been validated
Indicates that Ref CC has been cleared of a previous fault
Indicates that Ref CC has been faulted
Indicates that Ref C has switched to a new profile
Indicates that Ref C has been validated
Indicates that Ref C has been cleared of a previous fault
Indicates that Ref C has been faulted
Indicates that Ref DD has switched to a new profile
Indicates that Ref DD has been validated
Indicates that Ref DD has been cleared of a previous fault
Indicates that Ref DD has been faulted
Indicates that Ref D has switched to a new profile
Indicates that Ref D has been validated
Indicates that Ref D has been cleared of a previous fault
Indicates that Ref D has been faulted
Table 137. DPLL Status
Address
0D0A
0D0B
Bits
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
[7]
[6]
[5:3]
Bit Name
Offset slew limiting
Phase build-out
Freq lock
Phase lock
Loop switching
Holdover
Active
Free running
Frequency clamped
History available
Active reference
priority
[2:0]
Active reference
Description
The current closed-loop phase offset is rate limited.
A phase build-out transition was made to the currently active reference.
The DPLL has achieved frequency lock.
The DPLL has achieved phase lock.
The DPLL is in the process of a reference switchover.
The DPLL is in holdover mode.
The DPLL is active (that is, operating in a closed-loop condition)
The DPLL is free running (that is, operating in an open-loop condition)
The upper or lower frequency tuning word clamp is in effect.
There is sufficient tuning word history available for holdover operation.
Priority value of the currently active reference.
000 = highest priority.
111 = lowest priority.
Index of the currently active reference.
000 = Reference A.
001 = Reference AA.
010 = Reference B.
011 = Reference BB.
100 = Reference C.
101 = Reference CC.
110 = Reference D.
111 = Reference DD.
Rev. 0 | Page 99 of 112
AD9548
Table 138. Input Reference Status
Address
0D0C
0D0D
0D0E
0D0F
0D10
0D11
0D12
0D13
Bits
[7]
[6:4]
Bit Name
Profile selected
Selected profile
[3]
[2]
[1]
Valid
Fault
Fast
[0]
Slow
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
Description
The control logic sets this bit when it assigns Ref A to one of the eight profiles.
The index (0 to 7) of the profile assigned to Ref A.
Note that these bits are meaningless unless Bit 7 = 1.
Ref A is valid for use (it is unfaulted and its validation timer has expired).
Ref A is not valid for use.
If Bit 7 = 1, then this bit indicates that the frequency of Ref A is higher than allowed by
its profile settings.
If Bit 7 = 0, then this bit indicates that the frequency of Ref A is above the maximum
input reference frequency supported by the device.
If Bit 7 = 1, then this bit indicates that the frequency of Ref A is lower than allowed by its
profile settings.
If Bit 7 = 0, then this bit indicates that the frequency of Ref A is below the minimum
input reference frequency supported by the device.
Same as 0D0C but for REF AA instead of REF A.
Same as 0D0C but for REF B instead of REF A.
Same as 0D0C but for REF BB instead of REF A.
Same as 0D0C but for REF C instead of REF A.
Same as 0D0C but for REF CC instead of REF A.
Same as 0D0C but for REF D instead of REF A.
Same as 0D0C but for REF DD instead of REF A.
Table 139. Holdover History 1
Address
0D14
0D15
0D16
0D17
0D18
0D19
1
Bits
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
[7:0]
Bit Name
Holdover history
Description
Tuning word readback, Bits[7:0]
Tuning word readback, Bits[15:8]
Tuning word readack, Bits[23:9]
Tuning word readback, Bits[31:24]
Tuning word readback, Bits[39:32]
Tuning word readback, Bits[47:40]
These registers contain the current 48-bit DDS frequency tuning word generated by the tuning word history logic.
NONVOLATILE MEMORY (EEPROM) CONTROL (REGISTER 0E00 TO REGISTER 0E03)
Table 140. EEPROM Control
Address
0E00
0E01
0E02
0E03
Bits
[7:2]
[1]
Bit Name
Unused
Half rate mode
[0]
Write enable
[7:5]
[4:0]
Unused
Condition value
[7:1]
0
Unused
Save to EEPROM
[7:2]
[1]
[0]
Unused
Load from EEPROM
Unused
Description
EEPROM serial communication rate.
0 (default) = 400 kHz (normal).
1 = 200 kHz.
EEPROM write enable/protect.
0 (default) = EEPROM write protected.
1 = EEPROM write enabled.
When set to a nonzero value (default = 0), these bits establish the condition for EEPROM
downloads.
Upload data to the EEPROM based on the EEPROM storage sequence. This is an
autoclearing bit.
Download data from the EEPROM. This is an autoclearing bit.
Rev. 0 | Page 100 of 112
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EEPROM STORAGE SEQUENCE (REGISTER 0E10 TO REGISTER 0E3F)
The default settings of Register 0E10 to Register 0E33 embody a sample scratch pad instruction sequence. The following is a description of the
register defaults under the assumption that the controller has been instructed to carry out an EEPROM storage sequence.
Table 141. EEPROM Storage Sequence for System Clock Settings
Address
0E10
Bits
[7:0]
Bit Name
System clock
0E11
0E12
[7:0]
[7:0]
System clock
0E13
[7:0]
I/O update
Description
The default value of this register is 0x08, which the controller interprets as a data
instruction. Its decimal value is 8, which tells the controller to transfer nine bytes of
data (8 + 1) beginning at the address specified by the next two bytes. The controller
stores 0x08 in the EEPROM and increments the EEPROM address pointer.
The default value of these two registers is 0x0100. Note that Register 0E11 and
Register 0E12 are the most significant and least significant bytes of the target address,
respectively. Because the previous register contains a data instruction, these two
registers define a starting address (in this case, 0x0100). The controller stores 0x0100
in the EEPROM and increments the EEPROM pointer by 2. It then transfers nine bytes
from the register map (beginning at Address 0x0100) to the EEPROM and increments
the EEPROM address pointer by 10 (nine data bytes and one checksum byte). The nine
bytes transferred correspond to the system clock parameters in the register map.
The default value of this register is 0x80, which the controller interprets as an I/O
update instruction. The controller stores 0x80 in the EEPROM and increments the
EEPROM address pointer.
Table 142. EEPROM Storage Sequence for System Clock Calibration
Address
0E14
Bits
[7:0]
Bit Name
SYSCLK calibrate
Description
The default value of this register is 0xA0, which the controller interprets as a calibrate
instruction. The controller stores 0xA0 in the EEPROM and increments the EEPROM
address pointer.
Table 143. EEPROM Storage Sequence for General Configuration Settings
Address
0E15
Bits
[7:0]
Bit Name
General
Description
The default value of this register is 0x14, which the controller interprets as a data
instruction. Its decimal value is 20, which tells the controller to transfer 21 bytes of
data (20 + 1) beginning at the address specified by the next two bytes. The controller
stores 0x14 in the EEPROM and increments the EEPROM address pointer.
0E16
0E17
[7:0]
[7:0]
General
The default value of these two registers is 0x0200. Note that Register 0E16 and
Register 0E17 are the most significant and least significant bytes of the target
address, respectively. Because the previous register contains a data instruction,
these two registers define a starting address (in this case, 0x0200). The controller
stores 0x0200 in the EEPROM and increments the EEPROM pointer by 2. It then
transfers 21 bytes from the register map (beginning at Address 0x0200) to the
EEPROM and increments the EEPROM address pointer by 22 (21 data bytes and one
checksum byte). The 21 bytes transferred correspond to the general configuration
parameters in the register map.
Table 144. EEPROM Storage Sequence for DPLL Settings
Address
0E18
Bits
[7:0]
Bit Name
DPLL
0E19
0E1A
[7:0]
[7:0]
DPLL
Description
The default value of this register is 0x1B, which the controller interprets as a data
instruction. Its decimal value is 27, which tells the controller to transfer 28 bytes
of data (27 + 1) beginning at the address specified by the next two bytes. The
controller stores 0x1B in the EEPROM and increments the EEPROM address pointer.
The default value of these two registers is 0x0300. Note that Register 0E19 and
Register 0E1A are the most significant and least significant bytes of the target address,
respectively. Because the previous register contains a data instruction, these two
registers define a starting address (in this case, 0x0300). The controller stores 0x0300
in the EEPROM and increments the EEPROM pointer by 2. It then transfers 28 bytes
from the register map (beginning at Address 0x0300) to the EEPROM and increments
the EEPROM address pointer by 29 (28 data bytes and one checksum byte). The
28 bytes transferred correspond to the DPLL parameters in the register map.
Rev. 0 | Page 101 of 112
AD9548
Table 145. EEPROM Storage Sequence for Clock Distribution Settings
Address
0E1B
Bits
[7:0]
Bit Name
Clock distribution
0E1C
0E1D
[7:0]
[7:0]
Clock distribution
0E1E
[7:0]
I/O update
Description
The default value of this register is 0x19, which the controller interprets as a data
instruction. Its decimal value is 25, which tells the controller to transfer 26 bytes of
data (25 + 1) beginning at the address specified by the next two bytes. The controller
stores 0x19 in the EEPROM and increments the EEPROM address pointer.
The default value of these two registers is 0x0400. Note that Register 0E1C and
Register 0E1D are the most significant and least significant bytes of the target
address, respectively. Because the previous register contains a data instruction, these
two registers define a starting address (in this case, 0x0400). The controller stores
0x0400 in the EEPROM and increments the EEPROM pointer by 2. It then transfers
26 bytes from the register map (beginning at Address 0x0400) to the EEPROM and
increments the EEPROM address pointer by 27 (26 data bytes and one checksum
byte). The 26 bytes transferred correspond to the clock distribution parameters in the
register map.
The default value of this register is 0x80, which the controller interprets as an I/O
update instruction. The controller stores 0x80 in the EEPROM and increments the
EEPROM address pointer.
Table 146. EEPROM Storage Sequence for Reference Input Settings
Address
0E1F
Bits
[7:0]
Bit Name
Reference inputs
0E20
0E21
[7:0]
[7:0]
Reference inputs
Description
The default value of this register is 0x07, which the controller interprets as a data
instruction. Its decimal value is 7, which tells the controller to transfer eight bytes of
data (7 + 1) beginning at the address specified by the next two bytes. The controller
stores 0x07 in the EEPROM and increments the EEPROM address pointer.
The default value of these two registers is 0x0500. Note that Register 0E20 and
Register 0E21 are the most significant and least significant bytes of the target
address, respectively. Because the previous register contains a data instruction,
these two registers define a starting address (in this case, 0x0500). The controller
stores 0x0500 in the EEPROM and increments the EEPROM pointer by 2. It then
transfers eight bytes from the register map (beginning at Address 0x0500) to the
EEPROM and increments the EEPROM address pointer by nine (eight data bytes and
one checksum byte). The eight bytes transferred correspond to the reference inputs
parameters in the register map.
Table 147. EEPROM Storage Sequence for Profile 0 and Profile 1 Settings
Address
0E22
Bits
[7:0]
Bit Name
Profile 0 and Profile 1
0E23
0E24
[7:0]
[7:0]
Profile 0 and Profile 1
Description
The default value of this register is 0x63, which the controller interprets as a data
instruction. Its decimal value is 99, which this tells the controller to transfer 100 bytes
of data (99 + 1) beginning at the address specified by the next two bytes. The
controller stores 0x63 in the EEPROM and increments the EEPROM address pointer.
The default value of these two registers is 0x0600. Note that Register 0E23 and
Register 0E24 are the most significant and least significant bytes of the target
address, respectively. Because the previous register contains a data instruction,
these two registers define a starting address (in this case, 0x0600). The controller
stores 0x0600 in the EEPROM and increments the EEPROM pointer by 2. It then
transfers 100 bytes from the register map (beginning at Address 0x0600) to the
EEPROM and increments the EEPROM address pointer by 101 (100 data bytes and
one checksum byte). The 99 bytes transferred correspond to the Profile 0 and
Profile 1 parameters in the register map.
Rev. 0 | Page 102 of 112
AD9548
Table 148. EEPROM Storage Sequence for Profile 2 and Profile 3 Settings
Address
0E25
Bits
[7:0]
Bit Name
Profile 2 and Profile 3
0E26
0E27
[7:0]
[7:0]
Profile 2 and Profile 3
Description
The default value of this register is 0x63, which the controller interprets as a data
instruction. Its decimal value is 99, which tells the controller to transfer 100 bytes of
data (99 + 1) beginning at the address specified by the next two bytes. The controller
stores 0x63 in the EEPROM and increments the EEPROM address pointer.
The default value of these two registers is 0x0680. Note that Register 0E26 and
Register 0E27 are the most significant and least significant bytes of the target
address, respectively. Because the previous register contains a data instruction,
these two registers define a starting address (in this case, 0x0680). The controller
stores 0x0680 in the EEPROM and increments the EEPROM pointer by 2. It then
transfers 100 bytes from the register map (beginning at Address 0x0680) to the
EEPROM and increments the EEPROM address pointer by 101 (100 data bytes and
one checksum byte). The 99 bytes transferred correspond to the Profile 2 and
Profile 3 parameters in the register map.
Table 149. EEPROM Storage Sequence for Profile 4 and Profile 5 Settings
Address
0E28
Bits
[7:0]
Bit Name
Profile 4 and Profile 5
Description
The default value of this register is 0x63, which the controller interprets as a data
instruction. Its decimal value is 99, which this tells the controller to transfer 100 bytes
of data (99 + 1) beginning at the address specified by the next two bytes. The
controller stores 0x63 in the EEPROM and increments the EEPROM address pointer.
0E29
0E2A
[7:0]
[7:0]
Profile 4 and Profile 5
The default value of these two registers is 0x0700. Note that Register 0E29 and
Register 0E2A are the most significant and least significant bytes of the target
address, respectively. Because the previous register contains a data instruction,
these two registers define a starting address (in this case, 0x0700). The controller
stores 0x0700 in the EEPROM and increments the EEPROM pointer by 2. It then
transfers 100 bytes from the register map (beginning at Address 0x0700) to the
EEPROM and increments the EEPROM address pointer by 101 (100 data bytes and
one checksum byte). The 99 bytes transferred correspond to the Profile 4 and Profile 5
parameters in the register map.
Table 150. EEPROM Storage Sequence for Profile 6 and Profile 7 Settings
Address
0E2B
Bits
[7:0]
Bit Name
Profile 6 and Profile 7
0E2C
0E2D
[7:0]
[7:0]
Profile 6 and Profile 7
0E2E
[7:0]
I/O update
Description
The default value of this register is 0x63, which the controller interprets as a data
instruction. Its decimal value is 99, which this tells the controller to transfer 100 bytes
of data (99 + 1) beginning at the address specified by the next two bytes. The
controller stores 0x63 in the EEPROM and increments the EEPROM address pointer.
The default value of these two registers is 0x0780. Note that Register 0E2C and
Register 0E2C are the most significant and least significant bytes of the target
address, respectively. Because the previous register contains a data instruction,
these two registers define a starting address (in this case, 0x0780). The controller
stores 0x0780 in the EEPROM and increments the EEPROM pointer by 2. It then
transfers 100 bytes from the register map (beginning at Address 0x0780) to the
EEPROM and increments the EEPROM address pointer by 101 (100 data bytes and
one checksum byte). The 99 bytes transferred correspond to the Profile 6 and Profile 7
parameters in the register map.
The default value of this register is 0x80, which the controller interprets as an I/O
update instruction. The controller stores 0x80 in the EEPROM and increments the
EEPROM address pointer.
Rev. 0 | Page 103 of 112
AD9548
Table 151. EEPROM Storage Sequence for Operational Control Settings
Address
0E2F
Bits
[7:0]
Bit Name
Operational controls
0E30
0E31
[7:0]
[7:0]
Operational controls
0E32
[7:0]
I/O update
Description
The default value of this register is 0x10, which the controller interprets as a data
instruction. Its decimal value is 16, which this tells the controller to transfer 17 bytes of
data (16 + 1) beginning at the address specified by the next two bytes. The controller
stores 0x10 in the EEPROM and increments the EEPROM address pointer.
The default value of these two registers is 0x0A00. Note that Register 0E30 and
Register 0E31 are the most significant and least significant bytes of the target
address, respectively. Because the previous register contains a data instruction,
these two registers define a starting address (in this case, 0x0A00). The controller
stores 0x0A00 in the EEPROM and increments the EEPROM pointer by 2. It then
transfers 17 bytes from the register map (beginning at Address 0x0A00) to the
EEPROM and increments the EEPROM address pointer by 18 (17 data bytes and
one checksum byte). The 17 bytes transferred correspond to the operational
controls parameters in the register map.
The default value of this register is 0x80, which the controller interprets as an I/O
update instruction. The controller stores 0x80 in the EEPROM and increments the
EEPROM address pointer.
Table 152. EEPROM Storage Sequence for End of Data
Address
0E33
Bits
[7:0]
Bit Name
End of data
Description
The default value of this register is 0xFF, which the controller interprets as an end
instruction. The controller stores this instruction in the EEPROM, resets the EEPROM
address pointer, and enters an idle state. Note that, if this were a pause rather than an
end instruction, the controller actions would be the same except that the controller
would not reset the EEPROM address pointer.
Rev. 0 | Page 104 of 112
AD9548
POWER SUPPLY PARTITIONS
The AD9548 features multiple power supplies, and their power
consumption varies with the AD9548 configuration. This
section provides information about which power supplies can
be grouped together and how the power consumption of each
block varies with frequency.
The numbers quoted here are for comparison only. Please refer
to the Specifications section for exact numbers. With each group,
bypass capacitors of 1 μF in parallel with 10 μF should be used.
Upon applying power to the device, internal circuitry monitors
the 1.8 V digital core supply and the 3.3 V digital I/O supply.
When these supplies cross the desired threshold level, the device
generates an internal 10 μs reset pulse. This pulse does not
appear on the RESET pin.
3.3 V SUPPLIES
The 3.3 V supply domain consists of two main partitions, digital
(DVDD3) and analog (AVDD3). Take care to keep these two
supply domains separate.
and the rest of the AVDD3 supply connections. Generally, these
supply domains can be joined together. However, if an
application requires 1.8 V CMOS driver operation in the clock
distribution output block, then provide one 1.8 V supply
domain to power the clock distribution output block. Each
output driver has a dedicated supply pin, as shown in Table 153.
Table 153. Output Driver Supply Pins
Output Driver
OUT0
OUT1
OUT2
OUT3
Supply Pin
31
37
38
44
1.8 V SUPPLIES
The 1.8 V supply domain consists of two main partitions, digital
(DVDD) and analog (AVDD). These two supply domains must
be kept separate.
Furthermore, the AVDD3 consists of two subdomains: the clock
distribution output domain (Pin 31, Pin 37, Pin 38, and Pin 44)
Rev. 0 | Page 105 of 112
AD9548
THERMAL PERFORMANCE
Table 154. Thermal Parameters for the AD9548 88-Lead LFCSP Package
Symbol
θJA
θJMA
θJMA
θJB
θJC
ΨJT
1
2
Thermal Characteristic Using a JEDEC51-7 Plus JEDEC51-5 2S2P Test Board1
Junction-to-ambient thermal resistance, 0.0 m/s airflow per JEDEC JESD51-2 (still air)
Junction-to-ambient thermal resistance, 1.0 m/s airflow per JEDEC JESD51-6 (moving air)
Junction-to-ambient thermal resistance, 2.5 m/s airflow per JEDEC JESD51-6 (moving air)
Junction-to-board thermal resistance, 1.0 m/sec airflow per JEDEC JESD51-8 (moving air)
Junction-to-case thermal resistance (die-to-heat sink) per MIL-Std 883, Method 1012.1
Junction-to-top-of-package characterization parameter, 0 m/sec airflow per JEDEC JESD51-2 (still air)
Value2
18
16
14
9
1.0
0.1
Unit
°C/W
°C/W
°C/W
°C/W
°C/W
°C/W
The exposed pad on the bottom of the package must be soldered to ground to achieve the specified thermal performance.
Results are from simulations. The PCB is a JEDEC multilayer type. Thermal performance for actual applications requires careful inspection of the conditions in the
application to determine if they are similar to those assumed in these calculations.
The AD9548 is specified for a case temperature (TCASE). To ensure
that TCASE is not exceeded, an airflow source can be used. Use the
following equation to determine the junction temperature on the
application PCB:
TJ = TCASE + (ΨJT × PD)
Values of θJA are provided for package comparison and PCB
design considerations. θJA can be used for a first order approximation of TJ by the equation
TJ = TA + (θJA × PD)
where TA is the ambient temperature (°C).
where:
TJ is the junction temperature (°C).
TCASE is the case temperature (°C) measured by the customer at the
top center of the package.
ΨJT is the value as indicated in Table 154.
PD is the power dissipation (see the Power Dissipation section).
Values of θJC are provided for package comparison and PCB
design considerations when an external heat sink is required.
Values of θJB are provided for package comparison and PCB design
considerations.
Rev. 0 | Page 106 of 112
AD9548
CALCULATING DIGITAL FILTER COEFFICIENTS
The digital loop filter coefficients (α, β, γ, and δ (see Figure 40))
relate to the time constants (T1, T2, and T3) associated with the
equivalent analog circuit for a third order loop filter (Figure 66).
FROM
CHARGE
PUMP
R2
T2 =
TO
VCO
R3
C1
It can also be shown that the adjusted open-loop bandwidth leads
to T2 (the secondary time constant of the second order loop filter)
expressed as
C3
08022-042
Figure 66. Third Order Analog Loop Filter
K=
The design process begins by deciding on two design parameters
related to the second order loop filter shown in Figure 67: the
desired open-loop bandwidth (fP) and phase margin (θ).
30,517,578,125
2 33
D=S+
R2
08022-043
C2
U
+1
V
ω C 2 T2 D
(1 + (ω T ) )(1 + (ω T ) )
Figure 67. Second Order Analog Loop Filter
α=
An analysis of the second order loop filter leads to its primary
time constant, T1. It can be shown that T1 is expressible in terms of
fP and θ as
β=
− 32 ⎛ 1
1
⎜⎜ +
f S ⎝ T1 T2
γ=
− 32
f S T1
δ=
32
f S T3
T1 =
1 − sin(θ )
ω P cos(θ )
where ω P = 2πf P .
An analysis of the third order loop filter leads to the definition of
another time constant, T3. It can be shown that T3 is expressible in
terms of the desired amount of additional attenuation introduced
by R3 and C3 at some specified frequency offset (fOFFSET) from the
PLL output frequency.
ATTEN
10
fS
where S, U, and V are the integer and fractional feedback divider
values that reside in the profile registers. Keep in mind that the
desired integer feedback divide ratio is one more than the stored
value of S (hence, the +1 term in the equation for D in this
equation). This leads to the digital filter coefficients given by
TO
VCO
C1
ω C (T1 + T3 )
Calculation of the digital loop filter coefficients requires a scaling
constant, K (related to the system clock frequency, fS), and the PLL
feedback divide ratio, D.
C2
FROM
CHARGE
PUMP
1
2
2
C
1 + (ω C T2 )
T1 K
2
1
C
3
2
⎞
⎟⎟
⎠
Calculation of the coefficient register values requires the
application of some special functions described as follows:
The if() function
y = if(test_statement, true_value, false_value)
−1
where ω OFFSET = 2πf OFFSET .
where test_statement is a conditional expression (for example, x <
3), true_value is what y equals if the conditional expression is true,
and false_value is what y equals if the conditional expression is
false.
Note that ATTEN is the desired excess attenuation in decibels.
The round() function
T3 =
10
ω OFFSET
Furthermore, ATTEN and ωOFFSET should be chosen so that
T3 ≤
y = round(x)
1
5 fP
With an expression for T1 and T3, it is possible to define an
adjusted open-loop bandwidth (fC) that is slightly less than fP. It
can be shown that ωC (fC expressed as a radian frequency) is
expressible in terms of T1, T3, and θ (phase margin) as
ωC =
(T1 + T3 ) tan(θ ) ⎡⎢
2
T1T3 + (T1 + T3 ) ⎢⎣
1+
T1T3 + (T1 + T3 )
2
[(T1 + T3 ) tan(θ )]
2
⎤
− 1⎥
⎥⎦
Rev. 0 | Page 107 of 112
AD9548
If x is an integer, then y = x. Otherwise, y is the nearest integer to x.
For example, round(2.1) = 2, round(2.5) = 3, and round(−3.1) = −3.
decimal point of α0 to the left to accommodate small values of α.
Calculation of α1 is a two-step process, as follows:
w = if (α < 1, − ceil(log 2 (α )), 0)
The ceil() function
α1 = if (α < 1, min[63, max(0, w)], 0)
y = ceil(x)
If x is an integer, then y = x. Otherwise, y is the next integer to the
right on the number line. For example, ceil(2.8) = 3, whereas
ceil(−2.8) = −2.
The min() function
y = min(x0, x1, ... xn)
If gain is necessary (that is, α > 1), then it is beneficial to apply
most or all of it to the front-end gain (α2) implying that the
calculation of α2 is to be done before α3. Calculation of α2 is a
three-step process that leads directly to the calculation of α3.
x = if (α > 1, ceil(log 2 (α )), 0)
where x0 through xn is a list of real numbers, and the value of y is
the number in the list that is the farthest to the left on the number
line.
y = if (α > 1, min[22, max(0, x)], 0)
α 2 = if ( y ≥ 8, 7, y )
The max() function
α 3 = if ( y ≥ 8, y − 7, 0)
y = max(x0, x1, ... xn)
where x0 through xn is a list of real numbers, and the value of y is
the number in the list that is the farthest to the right on the
number line.
Calculation of α0 is a two-step process, as follows:
z = round(α × 216+α 1 −α 2 −α 3 )
α 0 = min[65,535 , max(1, z )]
The log2() function
log 2 ( x) =
Using the example value of α = 0.012735446 yields
ln ( x)
ln(2)
w = 6, so α1 = 6
where ln() is the natural log function and x is a positive, nonzero
number.
Assume that the coefficient calculations for α, β, γ, and δ yield the
following results:
α = 0.012735446
x = 0 and y = 0, so α2 = 0 and α3 = 0
z = 53,416.332099584, so α0 = 53,416
This leads to the following quantized value, which is very close to
the desired value of 0.012735446:
α quantized = 53416 × 2 −22 ≈ 0.01273566821
β = −6.98672 × 10 −5
CALCULATION OF THE β REGISTER VALUES
γ = −7.50373 × 10 −5
The quantized β coefficient consists of two components, β0 and β1
according to
δ = 0.002015399
These values are floating point numbers that must be quantized
according to the bit widths of the linear and exponential
components of the coefficients as they appear in the register map.
Note that the calculations that follow indicate a positive value for
the register entries of β and γ. The reason is that β and γ, which
are supposed to be negative values, are stored in the AD9548
registers as positive values. The AD9548 converts the stored values
to negative numbers within its signal processing core. A detailed
description of the register value computations for α, β, γ, and δ is
contained in the Calculation of the α Register Values section to
the Calculation of the δ Register Values section.
− β ≈ β quantized = β 0 × 2 − (17 + β1 )
where β0 and β1 are the register values. Calculation of β1 is a twostep process that leads to the calculation of β0, which is also a twostep process.
x = −ceil(log 2 ( β ))
β 1 = min[31, max(0, x)]
y = round( β × 217 + β1 )
β 0 = min[131,071 , max(1, y )]
CALCULATION OF THE α REGISTER VALUES
The quantized α coefficient consists of four components, α0, α1,
α2, and α3 according to
α ≈ α quantized = α 0 × 2
16−α 1 +α 2 +α 3
Using the example value of −β = 6.98672 × 10−5 yields
x = 13, so β1 = 13
y = 75,019.3347657728, so β0 = 75,019
where α0, α1, α2, and α3 are the register values. α2 provides frontend gain and α3 provides back-end gain, and α1 shifts the binary
Rev. 0 | Page 108 of 112
AD9548
This leads to the following quantized value, which is very close to
the desired value of 6.98672x10−5:
β quantized = 75,019 × 2 −30 ≈ 6.986688823 × 10 −5
CALCULATION OF THE δ REGISTER VALUES
The quantized δ coefficient consists of two components, δ0 and δ1,
according to
δ ≈ δ quantized = δ 0 × 2 − (15 + δ
CALCULATION OF THE γ REGISTER VALUES
The quantized γ coefficient consists of two components, γ0 and γ1
according to
− γ ≈ γ quantized = γ 0 × 2 − (17 + γ 1 )
1)
where δ0 and δ1 are the register values.
Calculation of δ1 is a two-step process that leads to the calculation
of δ0, which is also a two-step process.
x = −ceil(log 2 (δ ))
where γ0 and γ1 are the register values. Calculation of γ1 is a twostep process that leads to the calculation of γ0, which is also a twostep process.
δ 1 = min[31, max(0, x)]
y = round (δ × 215 + δ 1 )
x = −ceil(log 2 ( γ ))
δ 0 = min[32,767 , max(1, y )]
γ 1 = min[31, max(0, x)]
Given the example value of δ = 0.002015399, the preceding
formulas yield
y = round( γ × 217 + γ 1 )
γ 0 = min[131,071 , max(1, y )]
x = 8, δ1 = 8
y = 16,906.392174592, δ0 = 16,906
Using the example value of −γ = 7.50373 × 10−5 yields
This leads to the following quantized value, which is very close to
the desired value of 0.002015399:
x = 13, so γ1 = 13
y = 80,570.6873700352, so γ1 = 80,571
This leads to the following quantized value, which is very close to
the desired value of 7.50373x10−5:
γ quantized = 80571 × 2 −30 ≈ 7.503759116 × 10 −5
Rev. 0 | Page 109 of 112
δ quantized = 16906 × 2 −23 ≈ 0.0020153522 49
AD9548
OUTLINE DIMENSIONS
0.60 MAX
12.00
BSC SQ
0.60
MAX
88
67
66
1
PIN 1
INDICATOR
PIN 1
INDICATOR
11.75
BSC SQ
0.50
BSC
0.50
0.40
0.30
45
44
10.50
REF
0.70
0.65
0.60
12° MAX
22
0.05 MAX
0.01 NOM
0.30
0.23
0.18
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
SECTION OF THIS DATA SHEET.
0.20 REF
COMPLIANT TO JEDEC STANDARDS MO-220-VRRD.
032209-A
SEATING
PLANE
23
BOTTOM VIEW
TOP VIEW
0.90
0.85
0.80
6.15
6.00 SQ
5.85
EXPOSED PAD
Figure 68. 88-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
12 mm × 12 mm Body, Very Thin Quad
(CP-88-2)
Dimensions shown in millimeters
ORDERING GUIDE
Model
AD9548BCPZ 1
AD9548BCPZ-REEL71
AD9548/PCBZ1
1
Temperature Range
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
Package Description
88-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
88-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
Evaluation Board
Z = RoHS Compliant Part.
Rev. 0 | Page 110 of 112
Package Option
CP-88-2
CP-88-2
CP-88-2
AD9548
NOTES
Rev. 0 | Page 111 of 112
AD9548
NOTES
©2009 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D08022-0-5/09(0)
Rev. 0 | Page 112 of 112