Maxim MAX771ESA 5v/12v/15v or adjustable, high-efficiency, low iq, step-up dc-dc controller Datasheet

19-0202; Rev 2; 11/96
L
MANUA
ION KIT HEET
T
A
U
L
EVA
TA S
WS DA
FOLLO
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
________________________Applications
Palmtops/Handy-Terminals
High-Efficiency DC-DC Converters
Battery-Powered Applications
____________________________Features
♦ 90% Efficiency for 10mA to 1A Load Currents
♦ Up to 15W Output Power
♦ 110µA Max Supply Current
♦ 5µA Max Shutdown Current
♦ 2V to 16.5V Input Range
(MAX770/MAX771/MAX772)
♦ Internal Shunt Regulator for High Input Voltages
(MAX773)
♦ Preset or Adjustable Output Voltages
MAX770: 5V or Adjustable
MAX771: 12V or Adjustable
MAX772: 15V or Adjustable
MAX773: 5V, 12V, 15V, or Adjustable
♦ Current-Limited PFM Control Scheme
♦ 300kHz Switching Frequency
______________Ordering Information
PART
TEMP. RANGE
MAX770CPA
0°C to +70°C
MAX770CSA
MAX770C/D
MAX770EPA
MAX770ESA
MAX770MJA
0°C to +70°C
0°C to +70°C
-40°C to +85°C
-40°C to +85°C
-55°C to +125°C
PIN-PACKAGE
Plastic DIP
8 SO
Dice*
8 Plastic DIP
8 SO
8 CERDIP**
Ordering Information continued at end of data sheet.
*Contact factory for dice specifications.
**Contact factory for availability and processing to MIL-STD-883B.
Positive LCD-Bias Generators
Portable Communicators
Flash Memory Programmers
_________________Pin Configurations
__________Typical Operating Circuit
TOP VIEW
INPUT
2V TO VOUT
OUTPUT
12V
MAX771
ON/OFF
EXT
SHDN
CS
REF
N
EXT
1
8
CS
V+
2
7
GND
6
AGND
5
REF
FB 3
SHDN 4
MAX770
MAX771
MAX772
DIP/SO
FB AGND GND
V+
Pin Configurations continued at end of data sheet.
________________________________________________________________ Maxim Integrated Products
1
For free samples & the latest literature: http://www.maxim-ic.com, or phone 1-800-998-8800.
For small orders, phone 408-737-7600 ext. 3468.
MAX770–MAX773
_______________General Description
The MAX770–MAX773 step-up switching controllers provide 90% efficiency over a 10mA to 1A load. A
unique current-limited pulse-frequency-modulation (PFM)
control scheme gives these devices the benefits of
pulse-width-modulation (PWM) converters (high efficiency
at heavy loads), while using less than 110µA of supply
current (vs. 2mA to 10mA for PWM converters).
These ICs use tiny external components. Their high
switching frequencies (up to 300kHz) allow surfacemount magnetics of 5mm height and 9mm diameter.
The MAX770/MAX771/MAX772 accept input voltages
from 2V to 16.5V. Output voltages are preset at 5V,
(MAX770), 12V (MAX771), and 15V (MAX772); they can
also be adjusted using two resistors.
The MAX773 accepts inputs from 3V to 16.5V. For a wider
input range, it features an internal shunt regulator that
allows unlimited higher input voltages. The MAX773’s output can be set to 5V, 12V, or 15V, or it can be adjusted
with two resistors.
The MAX770–MAX773 drive external N-channel MOSFET
switches, allowing them to power loads up to 15W. If less
power is required, use the MAX756/MAX757 or
MAX761/MAX762 step-up switching regulators with onboard MOSFETs.
MAX770–MAX773
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
ABSOLUTE MAXIMUM RATINGS
Supply Voltages
V+ to GND.............................................................-0.3V to 17V
V+ to SGND.............................................................-0.3V to 7V
SGND........................................................-0.3V to (V+ + 0.3V)
EXT, CS, REF, LBO, LBI, SHDN, FB.............-0.3V to (V+ + 0.3V)
EXTH, EXTL ..................................................-0.3V to (V+ + 0.3V)
V5, V12, V15 .............................................................-0.3V to 17V
GND to AGND .........................................................0.1V to -0.1V
ISGND ..................................................................................50mA
Continuous Power Dissipation (TA = +70°C)
8-Pin Plastic DIP (derate 9.09mW/°C above +70°C)....727mW
8-Pin SO (derate 5.88mW/°C above +70°C) ................471mW
8-Pin CERDIP (derate 8.00mW/°C above +70°C) ........640mW
14-Pin Plastic DIP
(derate 10.00mW/°C above +70°C) .............................800mW
14-Pin SO (derate 8.33mW/°C above +70°C) ..............667mW
14-Pin CERDIP (derate 9.09mW/°C above +70°C) ......727mW
Operating Temperature Ranges
MAX77_C_ _ ........................................................0°C to +70°C
MAX77_E_ _......................................................-40°C to +85°C
MAX77_MJ_ ...................................................-55°C to +125°C
Junction Temperatures
MAX77_C_ _/E_ _ ..........................................................+150°C
MAX77_MJ_..................................................................+175°C
Storage Temperature Range .............................-65°C to +160°C
Lead Temperature (soldering, 10sec) .............................+300°C
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
ELECTRICAL CHARACTERISTICS
(V+ = 5V, ILOAD = 0mA, TA = TMIN to TMAX, unless otherwise noted. Typical values are at TA = +25°C.)
PARAMETER
SYMBOL
Input Voltage Range
Minimum Start-Up Voltage
MIN
2.0
16.5
MAX770–772C/E (external resistors)
3.0
16.5
MAX770–772MJA (external resistors)
3.1
16.5
MAX773C/E
3.0
16.5
MAX773MJD
3.1
MAX770/MAX771/MAX772
Supply Current
Standby Current
Output Voltage (Note 1)
TYP
MAX
UNITS
V
16.5
1.8
2.0
V
V+ = 16.5V, SHDN = 0V (normal operation)
85
110
µA
V+ = 10.0V, SHDN ≥ 1.6V (shutdown)
2
5
V+ = 16.5V, SHDN ≥ 1.6V (shutdown)
4
µA
V+ = 2.0V to 5.0V, over full load range
4.80
5.0
5.20
V+ = 2.0V to 12.0V, over full load range
11.52
12.0
12.48
V+ = 2.0V to 15.0V, over full load range
14.40
15.0
15.60
V
Output Voltage Line Regulation
(Note 2)
Figure 2a, V+ = 2.7V to 4.5V,
ILOAD = 700mA, VOUT = 5V
5
mV/V
Output Voltage Load Regulation
(Note 2)
Figure 2a, V+ = 3V, ILOAD = 30mA to 1A,
VOUT = 5V
20
mV/A
Maximum Switch On-Time
tON(max)
12
16
20
µs
Minimum Switch Off-Time
tOFF(min)
1.8
2.3
2.8
µs
MAX77_C
1.4700
1.5
1.5300
MAX77_E
1.4625
1.5
1.5375
MAX77_M
1.4550
1.5
1.5450
Efficiency
Reference Voltage
2
CONDITIONS
MAX770–772 (internal feedback resistors)
V+ = 4V, ILOAD = 500mA, VOUT = 5V
VREF
IREF = 0µA
87
_______________________________________________________________________________________
%
V
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
MAX770–MAX773
ELECTRICAL CHARACTERISTICS (continued)
(V+ = 5V, ILOAD = 0mA, TA = TMIN to TMAX, unless otherwise noted. Typical values are at TA = +25°C.)
PARAMETERS
SYMBOL
CONDITIONS
REF Load Regulation
0µA ≤ IREF ≤ 100µA
REF Line Regulation
3V ≤ V+ ≤ 16.5V
FB Trip-Point Voltage
FB Input Current
VFB
IFB
SHDN Input High Voltage
VIH
SHDN Input Low Voltage
VIL
TYP
MAX
MAX77_C/E
MIN
4
10
MAX77_M
4
15
40
100
MAX77_C
1.4700
1.50
1.5300
MAX77_E
1.4625
1.50
1.5375
MAX77_M
1.4550
1.50
1.5450
MAX77_C
±20
MAX77_E
±40
MAX77_M
±60
V+ = 2.0V to 16.5V
1.6
UNITS
mV
µV/V
V
nA
V
MAX77_C/E, V+ = 2.0V to 16.5V
0.4
MAX77_M, V+ = 2.0V to 16.5V
0.2
SHDN Input Current
V+ = 16.5V, SHDN = 0V or V+
±1
µA
LBI Input Current
MAX773, V+ = 16.5V, LBI = 1.5V
±20
nA
LBI Hysteresis
MAX773
LBI Delay
5mV overdrive
20
V
mV
2.5
µs
MAX77_C
1.4700
1.50
1.5300
MAX77_E
1.4625
1.50
1.5375
MAX77_M
1.4550
LBI Threshold Voltage
MAX773, LBI falling
1.50
1.5450
LBO Leakage Current
MAX773, V+ = 16.5V, VLBO = 16.5V
0.01
1.00
µA
0.1
0.4
V
200
230
mV
0.01
±1
µA
LBO Output Voltage Low
VOL
MAX773, V+ = 5V, LBO sinking 1mA
Current-Limit Trip Level
VCS
V+ = 5V to 16.5V
170
CS Input Current
V
EXT Rise Time
V+ = 5V, 1nF from EXT to ground (Note 3)
55
ns
EXT Fall Time
V+ = 5V, 1nF from EXT to ground (Note 3)
55
ns
Supply Voltage in
Shunt Mode
VSHUNT
MAX773, ISHUNT = 1mA to 20mA,
SGND = 0V, CSHUNT = 0.1µF
5.5
6.3
V
Note 1: Output voltage guaranteed using preset voltages. See Figures 7a–7d for output current capability versus input voltage.
Note 2: Output voltage line and load regulation depend on external circuit components.
Note 3: For the MAX773, EXT is EXTH and EXTL shorted together.
_______________________________________________________________________________________
3
__________________________________________Typical Operating Characteristics
(TA = +25°C, unless otherwise noted.)
MAX771
EFFICIENCY vs. OUTPUT CURRENT
(BOOTSTRAPPED)
50
0.1
1
EFFICIENCY (%)
60
VIN = 3V
50
0.001
0.01
MAX771
EFFICIENCY vs. OUTPUT CURRENT
(NON-BOOTSTRAPPED)
MAX770–3-04
VIN = 9V
90
VIN = 6V
VIN = 5V
80
VOUT = 12V
CIRCUIT OF
FIGURE 2b
50
0.1
1
0.1
VOUT = 5V
CIRCUIT OF
FIGURE 2a
500
400
300
ABOVE 3.4V,
THE CIRCUIT
STARTS UP
UNDER
MAXIMUM
LOAD
CONDITIONS
200
1.0
2
SCHOTTKY DIODE
LEAKAGE EXCLUDED
50
75 100 125
TEMPERATURE (°C)
4
ABOVE 3.5V
THE CIRCUIT
STARTS UP
UNDER
MAXIMUM
LOAD
CONDITIONS
200
0
0.4
0.2
2.5
2.0
3.5
BOOTSTRAPPED
CIRCUIT OF
FIGURE 2b
0.6
3.0
3.5
4.0
MINIMUM START-UP INPUT VOLTAGE (V)
EXT RISE/FALL TIME vs. SUPPLY VOLTAGE
250
200
CEXT = 2200pF
CEXT = 1000pF
150
CEXT = 446pF
CEXT = 100pF
100
NON-BOOTSTRAPPED
CIRCUIT OF FIGURE 2c
0
25
300
50
0
0
3.0
VOUT = 12V
SUPPLY CURRENT (mA)
ENTIRE
CIRCUIT
-75 -50 -25
2.5
SUPPLY CURRENT vs. SUPPLY VOLTAGE
3
1
2.0
VOUT = 12V
CIRCUIT OF
FIGURE 2b
400
100
0.8
MAX770–3-07
VOUT = 12V, VIN = 5V
CIRCUIT OF FIGURE 2b
BOOTSTRAPPED MODE
1.5
500
MINIMUM START-UP INPUT VOLTAGE (V)
SUPPLY CURRENT vs. TEMPERATURE
1
MAX771
LOAD CURRENT vs.
MINIMUM START-UP INPUT VOLTAGE
OUTPUT CURRENT (A)
4
0.1
MAX770
LOAD CURRENT vs.
MINIMUM START-UP INPUT VOLTAGE
600
10
0.01
OUTPUT CURRENT (A)
0
0.01
0.001
1
OUTPUT CURRENT (A)
100
70
0.001
VIN = 12V
VIN = 9V
VIN = 6V
VIN = 5V
VIN = 3V
60
700
LOAD CURRENT (mA)
EFFICIENCY (%)
VOUT = 12V
CIRCUIT OF
FIGURE 2c
70
VIN = 5V
OUTPUT CURRENT (A)
100
80
MAX770–3-09
0.01
70
EXT RISE/FALL TIME (ns)
0.001
80
MAX770–3-06
VOUT = 5V
CIRCUIT OF
FIGURE 2a
60
90
LOAD CURRENT (mA)
VIN = 3V
MAX770–3-02
90
VOUT = 15V, CIRCUIT OF FIGURE 2b
MAX772 SUBSTITUTED FOR MAX771
MAX770–3-05
VIN = 3.5V
70
100
MAX770–3-08
EFFICIENCY (%)
80
VIN = 6V
VIN = 9V
EFFICIENCY (%)
VIN = 4V
90
100
MAX770–3-01
100
MAX772
EFFICIENCY vs. OUTPUT CURRENT
(BOOTSTRAPPED)
MAX770–3-03
MAX770
EFFICIENCY vs. OUTPUT CURRENT
(BOOTSTRAPPED)
SUPPLY CURRENT (mA)
MAX770–MAX773
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
0
2
4
6
8
SUPPLY VOLTAGE (V)
10
12
2
4
6
8
V+ (V)
_______________________________________________________________________________________
10
12
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
REFERENCE OUTPUT RESISTANCE vs.
TEMPERATURE
REFERENCE vs. TEMPERATURE
200
1.504
10µA
REFERENCE (V)
1.502
150
100
50µA
1.500
1.498
1.496
100µA
50
MAX770–3-11
1.506
MAX770–3-10
REFERENCE OUTPUT RESISTANCE (Ω)
250
1.494
1.492
0
-60 -40 -20
-60 -40 -20
0 20 40 60 80 100 120 140
0 20 40 60 80 100 120 140
TEMPERATURE (°C)
TEMPERATURE (°C)
MAXIMUM SWITCH ON-TIME vs.
TEMPERATURE
SHUTDOWN CURRENT vs. TEMPERATURE
MAX770–3-12
4.0
MAX770–3-13
16.5
3.5
ICC (µA)
tON(MAX) (µs)
3.0
16.0
2.5
2.0
V+ = 15V
1.5
V+ = 8V
1.0
0.5
15.5
-60 -30
0
30
60
90
120 150
-60 -40 -20
0 20 40 60 80 100 120 140
TEMPERATURE (°C)
TEMPERATURE (°C)
MINIMUM SWITCH OFF-TIME vs.
TEMPERATURE
MAXIMUM SWITCH ON-TIME/
MINIMUM SWITCH OFF-TIME RATIO
vs. TEMPERATURE
2.25
2.20
MAX770–3-15
8.0
tON(MAX)/tOFF(MIN) RATIO
MAX770–3-14
2.30
tOFF(MIN) (µs)
V+ = 4V
0
7.5
7.0
6.5
6.0
-60 -30
0
30
60
90
TEMPERATURE (°C)
120 150
-60 -30
0
30
60
90
120 150
TEMPERATURE (°C)
_______________________________________________________________________________________
5
MAX770–MAX773
____________________________Typical Operating Characteristics (continued)
(TA = +25°C, unless otherwise noted.)
MAX770–MAX773
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
____________________________Typical Operating Characteristics (continued)
(Circuit of Figure 2a, TA = +25°C, unless otherwise noted.)
MAX770
LIGHT-LOAD SWITCHING WAVEFORMS
MAX770
HEAVY-LOAD SWITCHNG WAVEFORMS
VOUT
0
ILIM
A
A
ILIM
ILIM
2
B
2
B
0
0
C
C
20µs/div
V+ = 3V, IOUT = 165mA
A: EXT VOLTAGE, 5V/div
B: INDUCTOR CURRENT, 1A/div
C: VOUT RIPPLE 100mV/div, AC-COUPLED
20µs/div
VIN = 2.9V, IOUT = 0.9A
A: EXT VOLTAGE, 5V/div
B: INDUCTOR CURRENT 1A/div
C: VOUT RIPPLE 100mV/div, AC-COUPLED
MAX770
LINE-TRANSIENT RESPONSE
MAX770
LOAD-TRANSIENT RESPONSE
A
4.5V
2.7V
A
0
0
B
B
2ms/div
IOUT = 0.7A
A: VIN, 2.7V TO 4.5V, 2V/div
B: VOUT RIPPLE, 100mV/div, AC-COUPLED
6
2ms/div
VIN = 3V
A: LOAD CURRENT 0.5A/div (0A to 1A)
B: VOUT RIPPLE, 100mV/div, AC-COUPLED
_______________________________________________________________________________________
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
MAX770
EXITING SHUTDOWN
A
0
B
0
200µs/div
VIN = 3V, IOUT = 0.5A
A: SHDN, 2V/div
B: VOUT, 2V/div
______________________________________________________________Pin Description
PIN
MAX770
MAX771
MAX772
MAX773
1
NAME
FUNCTION
—
EXT
2
3
V+
3
6
FB
4
7
SHDN
5
8
REF
6
—
AGND
Gate drive for external N-channel power transistor
Power-supply input. Also acts as a voltage-sense point when in bootstrapped mode for the
MAX770/MAX771/MAX772, or as a shunt regulator when SGND is connected to ground for the
MAX773. Bypass to SGND with 0.1µF when using the shunt regulator.
Feedback input for adjustable-output operation. Connect to ground for fixed-output operation. Use
a resistor divider network to adjust the output voltage. See Setting the Output Voltage section.
Active-high TTL/CMOS logic-level shutdown input. In shutdown mode, VOUT is a diode drop
below V+ (due to the DC path from V+ to the output) and the supply current drops to 5µA
maximum. Connect to ground for normal operation.
1.5V reference output that can source 100µA for external loads. Bypass to GND with 0.1µF.
The reference is disabled in shutdown.
Analog ground
7
9
GND
8
11
CS
—
1
V12
—
2
V5
—
4
LBO
—
5
LBI
—
10
SGND
High-current ground return for the output driver
Positive input to the current-sense amplifier. Connect the current-sense resistor between CS and GND.
Input sense point for 12V-output operation. Connect VOUT to V12 for 12V-output operation.
Leave unconnected for adjustable-output operation.
Input sense point for 5V-output operation. Connect VOUT to V5 for 5V-output operation. Leave
unconnected for adjustable-output operation.
Low-battery output is an open-drain output that goes low when LBI is less than 1.5V. Connect to V+
through a pull-up resistor. Leave floating if not used. LBO is high impedance in shutdown mode.
Input to the internal low-battery comparator. Tie to GND or V+ if not used.
Shunt regulator ground. Leave unconnected if the shunt regulator is not used.
_______________________________________________________________________________________
7
MAX770–MAX773
____________________________Typical Operating Characteristics (continued)
(Circuit of Figure 2a, TA = +25°C, unless otherwise noted.)
MAX770–MAX773
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
_________________________________________________Pin Description (continued)
PIN
MAX770
MAX771
MAX772
MAX773
—
12
EXTL
—
13
EXTH
—
14
V15
NAME
FUNCTION
Low-level gate/base drive for external power transistor. Connect to the gate of an external
N-channel MOSFET or to the base of an external NPN transistor.
High-level gate/base drive for external power transistor. Connect to EXTL when using an external
N-channel MOSFET. When using an external NPN transistor, connect a resistor RBASE from
EXTH to the base of the NPN to set the maximum base-drive current.
Input sense point for 15V-output operation. Connect VOUT to V15 for 15V-output operation.
Leave unconnected for adjustable-output operation
_______________Detailed Description
The MAX770–MAX773 are BiCMOS, step-up, switchmode power-supply controllers that provide preset 5V,
12V, and 15V output voltages, in addition to adjustableoutput operation. Their unique control scheme combines the advantages of pulse-frequency modulation
(low supply current) and pulse-width modulation (high
efficiency with heavy loads), providing high efficiency
over a wide output current range, as well as increased
output current capability over previous PFM devices.
In addition, the external sense resistor and power
transistor allow the user to tailor the output current
capability for each application. Figure 1 shows the
MAX770–MAX773 block diagram.
The MAX770–MAX773 offer three main improvements
over prior pulse-skipping control solutions: 1) the converters operate with tiny (5mm height and less than
9mm diameter) surface-mount inductors due to their
300kHz switching frequency; 2) the current-limited PFM
control scheme allows 87% efficiencies over a wide
range of load currents; and 3) the maximum supply
current is only 110µA.
The MAX773 can be configured to operate from an
internal 6V shunt regulator, allowing very high input/output voltages. Its output can be configured for an
adjustable voltage or for one of three fixed voltages
(5V, 12V, or 15V), and it has a power-fail comparator for
low-battery detection.
All devices have shutdown capability, reducing the
supply current to 5µA max.
Bootstrapped/Non-Bootstrapped Modes
Figures 2 and 3 show standard application circuits for
bootstrapped and non-bootstrapped modes. In bootstrapped mode, the IC is powered from the output
(VOUT, which is connected to V+) and the input voltage
8
range is 2V to VOUT. The voltage applied to the gate of
the external power transistor is switched from VOUT to
ground, providing more switch gate drive and thus
reducing the transistor’s on resistance.
In non-bootstrapped mode, the IC is powered from the
input voltage (V+) and operates with minimum supply
current. In this mode, FB is the output voltage sense
point. Since the voltage swing applied to the gate of the
external power transistor is reduced (the gate swings
from V+ to ground), the power transistor’s on resistance
increases at low input voltages. However, the supply
current is also reduced because V+ is at a lower voltage, and because less energy is consumed while
charging and discharging the external MOSFET’s gate
capacitance. The minimum input voltage for the
MAX770–MAX773 is 3V when using external feedback
resistors. With supply voltages below 5V, bootstrapped
mode is recommended.
Note: When using the MAX770/MAX771/MAX772 in
non-bootstrapped mode, there is no preset output
operation because V+ is also the output voltage
sense point for fixed-output operation. External
resistors must be used to set the output voltage.
Use 1% external feedback resistors when operating
in adjustable-output mode (Figures 2c, 2d, 3b, 3d, 3e)
to achieve an overall output voltage accuracy of ±5%.
The MAX773 can be operated in non-bootstrapped
mode without using external feedback resistors
because V+ does not act as the output voltage sense
point with preset-output operation. To achieve highest efficiency, operate in bootstrapped mode whenever possible.
MAX773 Shunt-Regulator Operation
The MAX773 has an internal 6V shunt regulator that
allows the device to step up from very high input
voltages (Figure 4).
_______________________________________________________________________________________
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
V12
V5
MAX770–MAX773
LBO V15
FB
V+
DUAL-MODE
COMPARATOR
MAX773 ONLY
LBI
N
MAX770–MAX773
N
SHDN
200mV
BIAS
CIRCUITRY
1.5V
REFERENCE
REF
ERROR
COMPARATOR
ONE-SHOT
Q
TRIG
N
MAX770
MAX771
MAX772
V+
6V
SGND
F/F
S
Q
EXT
CONTROL
R
EXTH
LOW-VOLTAGE
OSCILLATOR
2.5V
ONE-SHOT
TRIG
MAX773
ONLY
EXTL
Q
CURRENT-SENSE
AMPLIFIER
0.2V
0.1V
EXT
MAX770
MAX771
MAX772
CS
Figure 1. Block Diagram
Floating the shunt-regulator ground (SGND) disables
the shunt regulator. To enable it, connect SGND to
GND. The shunt regulator requires 1mA minimum current for proper operation; the maximum current must
not exceed 20mA. The MAX773 operates in non-bootstrapped mode when the shunt regulator is used, and
EXT swings between the 6V shunt-regulator voltage
and GND.
When using the shunt regulator, use an N-channel power FET instead of an NPN power transistor as the power
switch. Otherwise, excessive base drive will collapse
the shunt regulator.
External Power-Transistor
Control Circuitry
PFM Control Scheme
The MAX770–MAX773 use a proprietary current-limited
PFM control scheme to provide high efficiency over a
wide range of load currents. This control scheme combines the ultra-low supply current of PFM converters (or
pulse skippers) with the high full-load efficiency of
PWM converters.
Unlike traditional PFM converters, the MAX770–
MAX773 use a sense resistor to control the peak inductor current. They also operate with high switching
_______________________________________________________________________________________
9
MAX770–MAX773
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
VIN = 5V
VIN = 3V
C2
0.1µF
V+
5 REF
C3
0.1µF
C2
0.1µF
2
4 SHDN
L1
22µH
MAX770
3 FB
C1
100µF
EXT
1
2
V+
5 REF
D1
1N5817
VOUT = 5V
@ 1A
C3
0.1µF
4 SHDN
MAX771
3 FB
N
EXT
1
CS
6 AGND
GND
C4
300µF
CS
8
RSENSE
100mΩ
GND
7
Figure 2b. 12V Preset Output, Bootstrapped
VIN = 4V
VIN = 5V
C1
68µF
C2
0.1µF
C2
0.1µF
2
L1
22µH
V+
5 REF
4 SHDN MAX770
MAX771
MAX772
6 AGND
EXT
CS
FB
1
2
D1
1N5817
VOUT = 12V
@ 0.5A
C4
200µF
N
5 REF
C3
0.1µF
3
4 SHDN MAX770
6
RSENSE
100mΩ
7
L1
20µH
V+
MAX771
MAX772
8
GND
R2 = (R1)
C4
200µF
7
Figure 2a. 5V Preset Output, Bootstrapped
C3
0.1µF
VOUT = 12V
@ 0.5A
Si9410DY
8
RSENSE
75mΩ
D1
1N5817
N
MTP3055EL
6 AGND
C1
68µF
L1
22µH
EXT
CS
AGND
FB
VREF = 1.5V
N
Si9410DY
R2 = (R1)
VOUT = 9V
C4
100µF
8
3
GND
7
R1
18k
REF
D1
1N5817
RSENSE
R2
127k
( VVOUT -1)
1
C1
47µF
R2
140k
R1
28k
( VVOUT -1)
REF
VREF = 1.5V
Figure 2c. 12V Output, Non-Bootstrapped
Figure 2d. 9V Output, Bootstrapped
frequencies (up to 300kHz), allowing the use of tiny
external components.
As with traditional PFM converters, the power transistor
is not turned on until the voltage comparator senses
that the output is out of regulation. However, unlike traditional PFM converters, the MAX770–MAX773 switch
using the combination of a peak current limit and a pair
of one-shots that set the maximum on-time (16µs) and
minimum off-time (2.3µs); there is no oscillator. Once
off, the minimum off-time one-shot holds the switch
off for 2.3µs. After this minimum time, the switch either
1) stays off if the output is in regulation, or 2) turns on
again if the output is out of regulation.
10
The control circuitry allows the ICs to operate in continuous-conduction mode (CCM) while maintaining high
efficiency with heavy loads. When the power switch is
______________________________________________________________________________________
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
1 V12
14 V15
SGND
8 REF
MAX773
C3
0.1µF
R3
10k
(1%)
C1
47µF
VIN
10
C1
100k
L1
22µH
D1
1N5817
LBO 4
VOUT
= 12V
Si9410DY
5 LBI
EXTH 13
10 SGND
4 LBO
C3
0.1µF
N
C4
CS 11
7
FB
LBI
RSENSE
GND
9
ZTX694B
CS 11
V15
14
V12
1
SHDN
FB
R4 = R3
RSENSE
0.4Ω
6
R1
34k
GND
9
NOMINAL MAX
11.0
11.4
C4
150µF
12
V5 2
VTRIP (V)
MIN
10.6
D1 VOUT = 24V
1N5818 @ 30mA
910Ω
EXTH 13
EXTL
8 REF
MAX773
5
EXTL 12
7 SHDN
6
L1
150µH
C2
0.1µF
3
V+
2 V5
R4
63.4k
(1%)
C2
0.1µF
3
V+
V
R2
510k
( VVOUT -1)
R2 = (R1)
-1)
( VTRIP
REF
REF
VREF = 1.5V
VREF = 1.5V
Figure 3a. 12V Preset Output, Bootstrapped, N-Channel
Power MOSFET
Figure 3b. 24V Output, Non-Bootstrapped, NPN Power
Transistor
VIN
VIN = 5V
C1
C1
C2
0.1µF
10 SGND
3
V+
4 LBO
7
6
5
D1
1N5817 VOUT = 15V
EXTH
13
N
EXTL
12
Si9410DY
4 LBO
C4
MAX773
RSENSE
SHDN
V15 14
FB
V12
1
V5
2
LBI
GND
9
7
10
EXTH
13
EXTL
12
VOUT = 16V
D1
1N5817
N
Si9410DY
C4
CS 11
8 REF
C3
0.1µF
5
L1
20µH
C2
0.1µF
3
V+
CS 11
8 REF
C3
0.1µF
L1
22µH
RSENSE
MAX773
V15 14
V12 1
LBI
SHDN
V5
2
R2
133k
FB 6
SGND
GND
9
R1
13.7k
R2 = (R1)
( VVOUT -1)
VREF = 1.5V
Figure 3c. 15V Preset Output, Non-Bootstrapped N-Channel
Power MOSFET
REF
Figure 3d. 16V Output, Bootstrapped, N-Channel
Power MOSFET
______________________________________________________________________________________
11
MAX770–MAX773
VIN = 5V
MAX770–MAX773
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
VIN = 24V TO 28V
C1
47µF
C2
0.1µF
RSHUNT
3k
D1
MUR115
3
10
4 LBO
RSHUNT
MAX773
EXTH
13
EXTL
12
N
Si9420DY
3 V+
C4
100µF
CS 11
8 REF
MAX773 V15 14
C2
0.1µF
RSENSE
1.0Ω
6V (typ)
V12 1
5 LBI
7
VOUT = 100V
@ 10mA
v+
SGND
C3
0.1µF
VIN
L1
250µH
V5 2
6
FB
SHDN
GND
9
10 SGND
R2
732k (1%)
R1
11.3k (1%)
RSHUNT =
R2 = (R1)
(
VREF = 1.5V
VOUT
-1
VREF
)
VIN (MIN) - VSHUNT (MAX)
I SHUNT *
* SEE TEXT FOR ISHUNT CALCULATION
Figure 3e. 100V Output, Shunt Regulator, N-Channel Power
MOSFET
Figure 4. MAX773 Shunt Regulator
turned on, it stays on until either 1) the maximum ontime one-shot turns it off (typically 16µs later), or 2) the
switch current reaches the peak current limit set by the
current-sense resistor.
Low-Voltage Start-Up Oscillator
The MAX770/MAX771/MAX772 feature a low input voltage start-up oscillator that guarantees start-up with no
load down to 2V when operating in bootstrapped mode
and using internal feedback resistors. At these low voltages, the supply voltage is not large enough for proper
error-comparator operation and internal biasing. The
start-up oscillator has a fixed 50% duty cycle and the
MAX770/MAX771/MAX772 disregard the error-comparator output when the supply voltage is less than
2.5V. Above 2.5V, the error-comparator and normal oneshot timing circuitry are used. The low voltage start-up
circuitry is disabled if non-bootstrapped mode is selected (FB is not tied to ground).
To increase light-load efficiency, the current limit for the
first two pulses is set to one-half the peak current limit.
If those pulses bring the output voltage into regulation,
the error comparator holds the MOSFET off and the
current limit remains at one-half the peak current limit. If
the output voltage is still out of regulation after two
pulses, the current limit for the next pulse is raised to
the peak current limit set by the external sense resistor
(see inductor current waveforms in the Typical
Operating Characteristics).
The MAX770–MAX773 switching frequency is variable
(depending on load current and input voltage), causing
variable switching noise. However, the subharmonic
noise generated does not exceed the peak current limit
times the filter capacitor equivalent series resistance
(ESR). For example, when generating a 12V output at
500mA from a 5V input, only 180mV of output ripple
occurs using the circuit of Figure 2b.
12
The MAX773 does not provide the low-voltage 50%
duty-cycle oscillator. Its minimum start-up voltage is 3V
for all modes.
External Transistor
An N-FET power switch is recommended for the
MAX770/MAX771/MAX772.
The MAX773 can drive either an N-channel MOSFET
(N-FET) or an NPN because it provides two separate
______________________________________________________________________________________
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
Shutdown Mode
When SHDN is high, the MAX770–MAX773 enter shutdown mode. In this mode, the internal biasing circuitry is turned off (including the reference) and V OUT
falls to a diode drop below VIN (due to the DC path
from the input to the output). In shutdown mode, the
supply current drops to less than 5µA. SHDN is a
TTL/CMOS logic-level input. Connect SHDN to GND for
normal operation.
The MAX773’s shunt regulator is not disabled in shutdown mode.
Low-Battery Detector
The MAX773 provides a low-battery comparator that
compares the voltage on LBI to the reference voltage.
When the LBI voltage is below VREF, LBO (an opendrain output) goes low. The low-battery comparator’s
20mV of hysteresis adds noise immunity, preventing
repeated triggering of LBO. Use a resistor-divider network
between V+, LBI, and GND to set the desired trip voltage
VTRIP. LBO is high impedance in shutdown mode.
__________________Design Procedure
Setting the Output Voltage
To set the output voltage, first determine the mode of
operation, either bootstrapped or non-bootstrapped.
Bootstrapped mode provides more output current
capability, while non-bootstrapped mode reduces the
supply current (see Typical Operating Characteristics).
If a decaying voltage source (such as a battery) is
used, see the additional notes in the Low Input Voltage
Operation section.
Use the MAX770/MAX771/MAX772 unless one or more
of the following conditions applies. If one or more of the
following is true, use the MAX773:
1) An NPN power transistor will be used as the power
switch
2) The LBI/LBO function is required
3) The shunt regulator must accommodate a high
input voltage
4) Preset-output non-bootstrapped operation is
desired—for example, to reduce the no-load
supply current in a 5V to 12V application.
R2
VOUT
FB
R1
MAX770
MAX771
MAX772
MAX773
R1 = 10k TO 500k
GND
R2 = R1
V
-1)
( VOUT
REF
VREF = 1.5V
Figure 5. Adjustable Output Circuit
See Table 1 for a summary of operating characteristics
and requirements for the ICs in bootstrapped and nonbootstrapped modes.
The MAX770–MAX773’s output voltage can be adjusted from very high voltages down to 3V, using external
resistors R1 and R2 configured as shown in Figure 5.
For adjustable-output operation, select feedback resistor R1 in the range of 10kΩ to 500kΩ. R2 is given by:
)
VOUT -1
R2 = (R1) –––––
VREF
(
where VREF equals 1.5V.
For preset-output operation, tie FB to GND (this
forces bootstrapped-mode operation for the
MAX770/MAX771/MAX772).
Configure the MAX773 for a preset voltage of 5V, 12V, or
15V by connecting the output to the corresponding
sense input pin (i.e., V5, V12, or V15). FB must be tied to
ground for preset-output operation. Leave all unused
sense input pins unconnected. Failure to do so will cause
an incorrect output voltage. The MAX773 can provide
a preset output voltage in both bootstrapped and nonbootstrapped modes.
Figures 2 and 3 show various circuit configurations for
bootstrapped/non-bootstrapped, preset/adjustable
operation.
Shunt-Regulator Operation
When using the shunt regulator, connect SGND to ground
and place a 0.1µF capacitor between V+ and SGND, as
close to the IC as possible. Increase C2 to 1.0µF to
improve shunt regulators performance with heavy loads.
Select RSHUNT such that 1mA ≤ ISHUNT ≤ 20mA.
______________________________________________________________________________________
13
MAX770–MAX773
drive outputs (EXTH and EXTL) that operate 180° out of
phase (Figures 3a and 3b). In Figure 3b, the resistor in
series with EXTH limits the base current, and EXTL (which
is connected directly to the base) turns the transistor off.
MAX770–MAX773
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
Table 1. Bootstrapped vs. Non-Bootstrapped Operation
PARAMETER
BOOTSTRAPPED*
NON-BOOTSTRAPPED
Gate Drive
GND to VOUT
GND to V+
FET On Resistance
Lower
Higher
Gate-Drive Capacitive Losses
Higher
Lower
No-Load Supply Current
Higher
2V to 16.5V (MAX770/MAX771/MAX772),
(internal feedback resistors)
3V to 16.5V (MAX770/MAX771/MAX772),
(external feedback resistors)
3V to 16.5V (MAX773)
Lower
Possible Input Voltage Range
3V to 16.5V
(MAX770/MAX771/MAX772),
3V and up (MAX773)
Normally Recommended Input
Voltage Range
2V to 5V (MAX770/MAX771/MAX772),
3V to 5V (MAX773)
5V to 16.5V
(MAX770/MAX771/MAX772),
5V and up (MAX773)
Fixed Output Available
MAX770–MAX773(N)
MAX773(N)/MAX773(S)
Adjustable Output Available
MAX770–MAX773(N)
MAX770/MAX771/MAX772/
MAX773(N)/MAX773(S)
*MAX773(S) indicates shunt mode; MAX773(N) indicates NOT in shunt mode.
Use an N-channel FET as the power switch when using
the shunt regulator (see MAX773 Shunt-Regulator
Operation in the Detailed Description). The shunt-regulator current powers the MAX773 and also provides the
FET gate-drive current, which depends largely on the
FET’s total gate charge at VGS = 5V. To determine the
shunt-resistor value, first determine the maximum shunt
current required.
ISHUNT = ISUPP + IGATE
See N-Channel MOSFETs in the Power-Transistor
Selection section to determine IGATE.
Determine the shunt-resistor value using the following
equation:
VIN
C2
0.1µF
RSHUNT
3
V+
SGND
EXTH
EXTL
10
L1
20µH
13
12
NPN
2N2222A
100Ω
CS
where VSHUNT(max) is 6.3V.
The shunt regulator is not disabled in shutdown
mode, and continues to draw the calculated shunt
current.
If the calculated shunt regulator current exceeds 20mA,
or if the shunt current exceeds 5mA and less shunt regulator current is desired, use the circuit of Figure 6 to
provide increased drive and reduced shunt current
when driving N-FETs with large gate capacitances.
Select ISHUNT = 3mA. This provides adequate biasing
current for this circuit, although higher shunt currents
can be used.
FB
D1
VOUT
N
PNP
2N2907A
MAX773
VIN(min) - VSHUNT(max)
RSHUNT(max) = ————————————
ISHUNT
14
C1
R2
C4
11
RSENSE
6
R1
Figure 6. Increased N-FET Gate Drive when Using the Shunt
Regulator
To prevent the shunt regulator from drawing current in
shutdown mode, place a switch in series with the shunt
resistor.
______________________________________________________________________________________
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
3.0
MAXIMUM OUTPUT CURRENT (A)
MAXIMUM OUTPUT CURRENT (A)
3.5
VOUT = 5V
L = 22µH
RSENSE = 40mΩ
2.5
RSENSE = 50mΩ
2.0
RSENSE = 75mΩ
1.5
1.0
RSENSE = 100mΩ
VOUT = 12V
L = 22µH
3.0
RSENSE = 40mΩ
RSENSE = 50mΩ
2.5
RSENSE = 75mΩ
2.0
1.5
1.0
RSENSE = 100mΩ
0.5
0.5
RSENSE = 200mΩ
RSENSE = 200mΩ
0
0
2
3
4
INPUT VOLTAGE (V)
3.5
2
5
Figure 7a. Maximum Output Current vs. Input Voltage
(VOUT = 5V)
RSENSE = 40mΩ
RSENSE = 75mΩ
2.0
10
12
VOUT = 24V
L =150µH
RSENSE = 50mΩ
2.5
6
8
INPUT VOLTAGE (V)
0.8
VOUT = 15V
L = 22µH
3.0
4
Figure 7b. Maximum Output Current vs. Input Voltage
(VOUT = 12V)
1.5
1.0
RSENSE = 100mΩ
MAXIMUM OUTPUT CURRENT (A)
MAXIMUM OUTPUT CURRENT (A)
MAX770–MAX773
3.5
0.6
RSENSE = 100mΩ
RSENSE = 200mΩ
0.4
0.2
0.5
RSENSE = 400mΩ
RSENSE = 200mΩ
0
0
2
4
6
8
10
12
INPUT VOLTAGE (V)
14
16
2
6
10
14
INPUT VOLTAGE (V)
Figure 7c. Maximum Output Current vs. Input Voltage
(VOUT = 15V)
Figure 7d. Maximum Output Current vs. Input Voltage
(VOUT = 24V)
Determining RSENSE
The Typical Operating Characteristics graphs show the
output current capability for various modes, sense
resistors, and input/output voltages. Use these graphs,
along with the theoretical output current curves shown
in Figures 7a-7d, to select RSENSE. These theoretical
curves assume that an external N-FET power switch is
used. They were derived using the minimum (worstcase) current-limit comparator threshold value, and the
inductance value. No tolerance was included for
R SENSE . The voltage drop across the diode was
assumed to be 0.5V, and the drop across the power
switch rDS(ON) and coil resistance was assumed to be
0.3V. To use the graphs, locate the graph with the
appropriate output voltage or the graph having the
nearest output voltage higher than the desired output
voltage. On this graph, find the curve for the largest
sense-resistor value with an output current that is adequate at the lowest input voltage.
Determining the Inductor (L)
Practical inductor values range from 10µH to 300µH.
20µH is a good choice for most applications. In applications with large input/output differentials, the IC’s
output current capability will be much less when the
inductance value is too low, because the IC will always
operate in discontinuous mode. If the inductor value
is too low, the current will ramp up to a high level
before the current-limit comparator can turn off the
switch. The minimum on-time for the switch (tON(min))
is approximately 2µs; select an inductor that allows
the current to ramp up to I LIM/2 in no less than 2µs.
Choosing a value of ILIM/2 allows the half-size current
pulses to occur, increasing light-load efficiency and
minimizing output ripple.
______________________________________________________________________________________
15
MAX770–MAX773
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
IC(PEAK)
MAX770
MAX771
MAX772
L
MAX773
IB
EXT
N
RBASE
EXTH
NPN
EXTL
CS
CS
RSENSE
RSENSE
Figure 8a. Use an N-Channel MOSFET with the
MAX770/MAX771/MAX772
L
MAX773
Figure 8c. Using an NPN Transistor with the MAX773
preferably under 20mΩ. To minimize radiated noise,
use a toroid, a pot core, or a shielded coil.
Table 2 lists inductor suppliers and specific recommended inductors.
Power Transistor Selection
EXTH
N
EXTL
CS
RSENSE
Figure 8b. Using an N-Channel MOSFET with the MAX773
The standard operating circuits use a 22µH inductor.
If a different inductance value is desired, select L
such that:
VIN(max) x tON(min)
L ≥ ——————————
ILIM / 2
Larger inductance values tend to increase the start-up
time slightly, while smaller inductance values allow the
coil current to ramp up to higher levels before the
switch turns off, increasing the ripple at light loads.
Inductors with a ferrite core or equivalent are recommended; powder iron cores are not recommended for
use with high switching frequencies. Make sure the
inductor’s saturation current rating (the current at which
the core begins to saturate and the inductance starts to
fall) exceeds the peak current rating set by RSENSE.
However, it is generally acceptable to bias the inductor
into saturation by approximately 20% (the point where
the inductance is 20% below the nominal value). For
highest efficiency, use a coil with low DC resistance,
16
Use an N-channel MOSFET power transistor with the
MAX770/MAX771/MAX772 (Figure 8a).
Use an N-FET whenever possible with the MAX773. An
NPN transistor can be used, but be extremely careful
when determining the base current (see NPN
Transistors section). An NPN transistor is not recommended when using the shunt regulator.
N-Channel MOSFETs
To ensure the external N-channel MOSFET (N-FET) is
turned on hard, use logic-level or low-threshold
N-FETs when the input drive voltage is less than 8V. This
applies even in bootstrapped mode, to ensure start-up.
N-FETs provide the highest efficiency because they do
not draw any DC gate-drive current, but they are typically more expensive than NPN transistors. When using
an N-FET with the MAX773, connect EXTH and EXTL to
the N-FET’s gate (Figure 8b).
When selecting an N-FET, three important parameters
are the total gate charge (Qg), on resistance (rDS(ON)),
and reverse transfer capacitance (CRSS).
Qg takes into account all capacitances associated with
charging the gate. Use the typical Qg value for best
results; the maximum value is usually grossly overspecified since it is a guaranteed limit and not the measured value. The typical total gate charge should be
50nC or less. With larger numbers, the EXT pins may
not be able to adequately drive the gate. The EXT
rise/fall time with various capacitive loads as shown in
the Typical Operating Characteristics.
______________________________________________________________________________________
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
Continuing with the example, ∆V+ = 17nC/0.1µF = 170mV.
Use I GATE when calculating the appropriate shunt
resistor. See the Shunt Regulator Operation section.
Figure 2a’s application circuit uses an MTD3055EL
logic-level N-FET with a guaranteed threshold voltage
(V TH) of 2V. Figure 2b’s application circuit uses an
8-pin Si9410DY surface-mount N-FET that has 50mΩ
on resistance with 4.5V VGS, and a guaranteed VTH of
less than 3V.
NPN Transistors
The MAX773 can drive NPN transistors, but be
extremely careful when determining the base-current
requirements. Too little base current can cause excessive power dissipation in the transistor; too much base
current can cause the base to oversaturate, so the transistor remains on continually. Both conditions can damage the transistor.
When using the MAX773 with an NPN transistor, connect EXTL to the transistor’s base, and connect RBASE
between EXTH and the base (Figure 8c).
To determine the required peak inductor current,
IC(PEAK), observe the Typical Operating Characteristics
efficiency graphs and the theoretical output current
capability vs. input voltage graphs to determine a
sense resistor that will allow the desired output current.
Divide the 170mV worst-case (smallest) voltage across
the current-sense amplifier VCS(max) by the senseresistor value. To determine IB, set the peak inductor
current (ILIM) equal to the peak transistor collector cur-
rent IC(PEAK). Calculate IB as follows:
IB = ILIM/ß
Use the worst-case (lowest) value for ß given in the
transistor’s electrical specification, where the collector
current used for the test is approximately equal to ILIM.
It may be necessary to use even higher base currents
(e.g., IB = ILIM /10), although excessive IB may impair
operation by extending the transistor’s turn-off time.
RBASE is determined by:
(VEXTH - VBE - VCS(min ))
RBASE = ————————————–
IB
Where V EXTH is the voltage at V+ (in bootstrapped
mode VEXTH is the output voltage), VBE is the 0.7V
transistor base-emitter voltage, VCS(min) is the voltage
drop across the current-sense resistor, and I B is the
minimum base current that forces the transistor into
saturation. This equation reduces to (V+ - 700mV 170mV) / IB.
For maximum efficiency, make RBASE as large as possible, but small enough to ensure the transistor is
always driven near saturation. Highest efficiency is
obtained with a fast-switching NPN transistor
(fT ≥ 150MHz) with a low collector-emitter saturation
voltage and a high current gain. A good transistor to
use is the Zetex ZTX694B.
Diode Selection
The MAX770–MAX773’s high switching frequency
demands a high-speed rectifier. Schottky diodes such
as the 1N5817–1N5822 are recommended. Make sure
that the Schottky diode’s average current rating
exceeds the peak current limit set by RSENSE, and that
its breakdown voltage exceeds VOUT. For high-temperature applications, Schottky diodes may be inadequate
due to their high leakage currents; high-speed silicon
diodes may be used instead. At heavy loads and high
temperatures, the benefits of a Schottky diode’s low forward voltage may outweigh the disadvantages of its
high leakage current.
Capacitor Selection
Output Filter Capacitor
The primary criterion for selecting the output filter
capacitor (C2) is low effective series resistance (ESR).
The product of the peak inductor current and the output
filter capacitor’s ESR determines the amplitude of the
ripple seen on the output voltage. An OS-CON 300µF,
6.3V output filter capacitor has approximately 50mΩ of
ESR and typically provides 180mV ripple when
stepping up from 3V to 5V at 1A (Figure 2a).
______________________________________________________________________________________
17
MAX770–MAX773
The two most significant losses contributing to the
N-FET’s power dissipation are I2R losses and switching
losses. Select a transistor with low r DS(ON) and low
CRSS to minimize these losses.
Determine the maximum required gate-drive current
from the Qg specification in the N-FET data sheet.
The MAX773’s maximum allowed switching frequency
during normal operation is 300kHz; but at start-up the
maximum frequency can be 500kHz, so the maximum
current required to charge the N-FET’s gate is
f(max) x Qg(typ). Use the typical Qg number from the
transistor data sheet. For example, the Si9410DY has a
Qg(typ) of 17nC (at VGS = 5V), therefore the current
required to charge the gate is:
IGATE (max) = (500kHz) (17nC) = 8.5mA.
The bypass capacitor on V+ (C2) must instantaneously
furnish the gate charge without excessive droop (e.g.,
less than 200mV):
Qg
∆V+ = ——
C2
MAX770–MAX773
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
Smaller capacitors are acceptable for light loads or in
applications that can tolerate higher output ripple.
Since the output filter capacitor’s ESR affects efficiency, use low-ESR capacitors for best performance. The
smallest low-ESR surface-mount tantalum capacitors
currently available are the Sprague 595D series. Sanyo
OS-CON organic semiconductor through-hole capacitors and the Nichicon PL series also exhibit low ESR.
See Table 2.
Input Bypass Capacitors
The input bypass capacitor (C1) reduces peak currents
drawn from the voltage source and also reduces noise
at the voltage source caused by the switching action of
the MAX770–MAX773. The input voltage source impedance determines the size of the capacitor required at
the V+ input. As with the output filter capacitor, a lowESR capacitor is recommended. For output currents up
to 1A, 150µF (C1) is adequate, although smaller
bypass capacitors may also be acceptable.
Bypass the IC with a 0.1µF ceramic capacitor (C2)
placed close to the V+ and GND pins.
Reference Capacitor
Bypass REF with a 0.1µF capacitor (C3). REF can
source up to 100µA of current.
Setting the Low-Battery-Detector Voltage
To set the low-battery detector’s falling trip voltage
(VTRIP(falling)), select R3 between 10kΩ and 500kΩ
(Figure 9), and calculate R4 as follows:
R4 = (R3)
V
-V
(———————
)
V
TRIP
REF
REF
where VREF = 1.5V.
The rising trip voltage is higher because of the comparator’s approximately 20mV of hysteresis, and is
determined by:
R4
VTRIP (rising) = (VREF + 20mV) (1 + ——)
R3
Connect a high value resistor (larger than R3 + R4)
between LBI and LBO if additional hysteresis is required.
Connect a pull-up resistor (e.g., 100kΩ) between LBO
and V+. Tie LBI to GND and leave LBO floating if the
low-battery detector is not used.
18
VIN
V+
R4
LBI
MAX773
R5
100k
LBO
R3
LOW-BATTERY
OUTPUT
GND
R4 = R3
V
( VTRIP -1)
REF
VREF = 1.5V
Figure 9. Input Voltage Monitor Circuit
__________Applications Information
MAX773 Operation with High
Input/Output Voltages
The MAX773’s shunt regulator input allows high voltages to be converted to very high voltages. Since the
MAX773 runs off the 6V shunt (bootstrapped operation
is not allowed), the IC will not see the high input voltage. Use an external logic-level N-FET as the power
switch, since only 6V of VGS are available. Also, make
sure all external components are rated for very high
output voltage. Figure 3e shows a circuit that converts
28V to 100V.
Low Input Voltage Operation
When using a power supply that decays with time
(such as a battery), the N-FET transistor will operate in
its linear region when the voltage at EXT approaches
the threshold voltage of the FET, dissipating excessive
power. Prolonged operation in this mode may damage
the FET. This effect is much more significant in nonbootstrapped mode than in bootstrapped mode, since
bootstrapped mode typically provides much higher
VGS voltages. To avoid this condition, make sure VEXT
is above the VTH of the FET, or use a voltage detector
(such as the MAX8211) to put the IC in shutdown mode
once the input supply voltage falls below a predetermined minimum value. Excessive loads with low input
voltages can also cause this condition.
______________________________________________________________________________________
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
Layout Considerations
Due to high current levels and fast switching waveforms, which radiate noise, proper PC board layout is
essential. Protect sensitive analog grounds by using a
star ground configuration. Minimize ground noise by
connecting GND, the input bypass capacitor ground
lead, and the output filter capacitor ground lead to a
single point (star ground configuration). Also, minimize
lead lengths to reduce stray capacitance, trace resistance, and radiated noise. Place input bypass capacitor C2 as close as possible to V+ and GND.
Excessive noise at the V+ input may falsely trigger the
timing circuitry, resulting in short pulses at EXT. If this
occurs it will have a negligible effect on circuit efficiency. If desired, place a 4.7µF directly across the V+ and
GND pins (in parallel with the 0.1µF C2 bypass capacitor) to reduce the noise at V+.
Table 2. Component Suppliers
PRODUCTION
INDUCTORS
CAPACITORS
TRANSISTORS
Surface Mount
Sumida
CD54 series
CDR125 series
Coiltronics
CTX20 series
Matsuo
267 series
Sprague
595D series
N-FET
Siliconix
Si9410DY
Si9420DY (high voltage)
Motorola
MTP3055EL
MTD20N03HDL
Through Hole
Sumida
RCH855 series
RCH110 series
Renco
RL1284-18
Sanyo
OS-CON series
Nichicon
PL series
United Chemi-Con
LXF series
NPN
Zetex
ZTX694B
SUPPLIER
PHONE
DIODES
Nihon
EC10 series
Motorola
1N5817–1N5822
MUR115 (high voltage)
FAX
Coiltronics
USA: (561) 241-7876
(561) 241-9339
Matsuo
USA: (714) 969-2491
Japan: 81-6-337-6450
(714) 960-6492
81-6-337-6456
Nichicon
USA: (847) 843-7500
(847) 843-2798
Nihon
USA: (805) 867-2555
(805) 867-2698
Renco
USA: (516) 586-5566
(516) 586-5562
Sanyo
USA: (619) 661-6835
Japan: 81-7-2070-6306
(619) 661-1055
81-7-2070-1174
Sumida
USA: (847) 956-0666
Japan: 81-3-3607-5111
81-3-3607-5144
United Chemi-Con
USA: (714) 255-9500
(714) 255-9400
Zetex
USA: (516) 543-7100
UK: 44-61-627-4963
(516) 864-7630
44-61-627-5467
______________________________________________________________________________________
19
MAX770–MAX773
Starting Up under Load
The Typical Operating Characteristics show the StartUp Voltage vs. Load Current graph for bootstrappedmode operation. This graph depends on the type
of power switch used. The MAX770–MAX773 are
not designed to start up under full load in bootstrapped mode with low input voltages.
MAX770–MAX773
5V/12V/15V or Adjustable, High-Efficiency,
Low IQ, Step-Up DC-DC Controllers
___Ordering Information (continued)
PART
TEMP. RANGE
MAX771CPA
0°C to +70°C
MAX771CSA
MAX771C/D
MAX771EPA
MAX771ESA
MAX771MJA
MAX772CPA
MAX772CSA
MAX772C/D
MAX772EPA
MAX772ESA
MAX772MJA
MAX773CPD
MAX773CSD
MAX773C/D
MAX773EPD
MAX773ESD
MAX773MJD
0°C to +70°C
0°C to +70°C
-40°C to +85°C
-40°C to +85°C
-55°C to +125°C
0°C to +70°C
0°C to +70°C
0°C to +70°C
-40°C to +85°C
-40°C to +85°C
-55°C to +125°C
0°C to +70°C
0°C to +70°C
0°C to +70°C
-40°C to +85°C
-40°C to +85°C
-55°C to +125°C
_________________Chip Topographies
MAX770/MAX771/MAX772
PIN-PACKAGE
8 Plastic DIP
8 SO
Dice*
8 Plastic DIP
8 SO
8 CERDIP
8 Plastic DIP
8 SO
Dice*
8 Plastic DIP
8 SO
8 CERDIP
14 Plastic DIP
14 SO
Dice*
14 Plastic DIP
14 Narrow SO
14 CERDIP
EXT
V+
CS
0.126"
(3.200mm)
GND
AGND
FB
SHDN
0.080"
REF
(2.032mm)
*Contact factory for dice specifications.
____Pin Configurations (continued)
TRANSISTOR COUNT: 501;
SUBSTRATE CONNECTED TO V+.
MAX773
TOP VIEW
V5
V12
V15
EXTH
V12 1
14 V15
V5 2
13 EXTH
V+ 3
12 EXTL
LBO 4
MAX773
LBI 5
EXTL
V+
LBO
CS
SGND
LBI
0.126"
11 CS
(3.200mm)
10 SGND
FB 6
9
SHDN 7
8
GND
GND
REF
GND
FB
DIP/SO
SHDN
0.080"
REF
(2.032mm)
TRANSISTOR COUNT: 501;
SUBSTRATE CONNECTED TO V+.
20
______________________________________________________________________________________