AD EVAL-CONTROLBRD2Z 16-bit, 1.5 lsb inl, 500 ksps pulsar differential adc in msop/qfn Datasheet

16-Bit, 1.5 LSB INL, 500 kSPS PulSAR™
Differential ADC in MSOP/QFN
AD7688
FEATURES
APPLICATION DIAGRAM
APPLICATIONS
Battery-powered equipment
Data acquisitions
Instrumentation
Medical instruments
Process controls
1.5
POSITIVE INL = +0.31LSB
NEGATIVE INL = –0.39LSB
1.0
0.5V TO 5V
VREF
0
IN+
IN–
VREF
5V
REF VDD VIO
SDI
AD7688
1.8V TO VDD
SCK
3- OR 4-WIRE INTERFACE
(SPI, DAISY CHAIN, CS)
SDO
GND
CNV
0
02973-002
16-bit resolution with no missing codes
Throughput: 500 kSPS
INL: ±0.4 LSB typ, ±1.5 LSB max (±23 ppm of FSR)
Dynamic range: 96.5 dB
SNR: 95.5 dB @ 20 kHz
THD: −118 dB @ 20 kHz
True differential analog input range
±VREF
0 V to VREF with VREF up to VDD on both inputs
No pipeline delay
Single-supply 5 V operation with
1.8 V/2.5 V/3 V/5 V logic interface
Serial interface SPI®/QSPI™/MICROWIRE™/DSP-compatible
Daisy-chain multiple ADCs and BUSY indicator
Power dissipation
3.75 mW @ 5 V/100 kSPS
3.75 μW @ 5 V/100 SPS
Standby current: 1 nA
10-lead MSOP (MSOP-8 size) and
3 mm × 3 mm QFN (LFCSP) (SOT-23 size)
Pin-for-pin compatible with AD7685, AD7686, and AD7687
Figure 2.
Table 1. MSOP, QFN (LFCSP)/SOT-23 16-Bit PulSAR ADC
Type
True Differential
Pseudo
Differential/Unipolar
Unipolar
100 kSPS
AD7684
AD7683
250 kSPS
AD7687
AD7685
AD7694
500 kSPS
AD7688
AD7686
AD7680
GENERAL DESCRIPTION
The AD7688 is a 16-bit, charge redistribution, successive
approximation, analog-to-digital converter (ADC) that operates
from a single 5 V power supply, VDD. It contains a low power,
high speed, 16-bit sampling ADC with no missing codes, an
internal conversion clock, and a versatile serial interface port.
The part also contains a low noise, wide bandwidth, short
aperture delay track-and-hold circuit. On the CNV rising edge,
it samples the voltage difference between IN+ and IN− pins.
The voltages on these pins usually swing in opposite phase
between 0 V and REF. The reference voltage, REF, is applied
externally and can be set up to the supply voltage.
Its power scales linearly with throughput.
INL (LSB)
0.5
The SPI-compatible serial interface also features the ability,
using the SDI input, to daisy-chain several ADCs on a single,
3-wire bus and provides an optional BUSY indicator. It is
compatible with 1.8 V, 2.5 V, 3 V, or 5 V logic, using the separate
supply VIO.
0
–0.5
02973-001
–1.0
–1.5
0
16384
32768
CODE
49152
The AD7688 is housed in a 10-lead MSOP or a 10-lead QFN
(LFCSP) with operation specified from −40°C to +85°C.
65535
Figure 1. Integral Nonlinearity vs. Code
Rev. A
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.461.3113 ©2007–2011 Analog Devices, Inc. All rights reserved.
AD7688
TABLE OF CONTENTS
Features .............................................................................................. 1
Driver Amplifier Choice ........................................................... 15
Applications....................................................................................... 1
Single-to-Differential Driver .................................................... 15
Application Diagram........................................................................ 1
Voltage Reference Input ............................................................ 15
General Description ......................................................................... 1
Power Supply............................................................................... 15
Revision History ............................................................................... 2
Supplying the ADC from the Reference.................................. 16
Specifications..................................................................................... 3
Digital Interface.......................................................................... 16
Timing Specifications....................................................................... 5
CS MODE 3-Wire, No BUSY Indicator .................................. 17
Absolute Maximum Ratings............................................................ 6
CS Mode 3-Wire with BUSY Indicator ................................... 18
Thermal Resistance ...................................................................... 6
CS Mode 4-Wire, No BUSY Indicator..................................... 19
ESD Caution.................................................................................. 6
CS Mode 4-Wire with BUSY Indicator ................................... 20
Pin Configuration and Function Descriptions............................. 7
Chain Mode, No BUSY Indicator ............................................ 21
Terminology ...................................................................................... 8
Chain Mode with BUSY Indicator........................................... 22
Typical Performance Characteristics ............................................. 9
Application Hints ........................................................................... 23
Circuit Information.................................................................... 12
Layout .......................................................................................... 23
Converter Operation.................................................................. 12
Evaluating the AD7688’s Performance.................................... 23
Typical Connection Diagram ................................................... 13
Outline Dimensions ....................................................................... 24
Analog Input ............................................................................... 14
Ordering Guide .......................................................................... 25
REVISION HISTORY
2/11—Rev. 0 to Rev. A
Deleted QFN in Development Note............................ Throughout
Changes to Table 5............................................................................ 6
Added Thermal Resistance Section and Table 6 .......................... 6
Changes to Figure 6 and Table 7..................................................... 7
Updated Outline Dimensions ....................................................... 24
Changes to Ordering Guide .......................................................... 25
4/05—Revision 0: Initial Version
Rev. A | Page 2 of 28
AD7688
SPECIFICATIONS
VDD = 4.5 V to 5.5 V, VIO = 2.3 V to VDD, VREF = VDD, TA = –40°C to +85°C, unless otherwise noted.
Table 2.
Parameter
RESOLUTION
ANALOG INPUT
Voltage Range
Absolute Input Voltage
Common-Mode Input Range
Analog Input CMRR
Leakage Current at 25°C
Input Impedance
ACCURACY
No Missing Codes
Differential Linearity Error
Integral Linearity Error
Transition Noise
Gain Error 2 , TMIN to TMAX
Gain Error Temperature Drift
Zero Error2, TMIN to TMAX
Zero Temperature Drift
Power Supply Sensitivity
THROUGHPUT
Conversion Rate
Transient Response
AC ACCURACY
Dynamic Range
Signal-to-Noise
Spurious-Free Dynamic Range
Total Harmonic Distortion
Signal-to-(Noise + Distortion)
Conditions
Min
16
IN+ − IN−
IN+, IN−
IN+, IN−
fIN = 250 kHz
Acquisition phase
−VREF
−0.1
0
Typ
Max
Unit
Bits
+VREF
VREF + 0.1
VREF/2 + 0.1
V
V
V
dB
nA
VREF/2
65
1
See the Analog Input section
16
−1
−1.5
REF = VDD = 5 V
VDD = 5V ± 5%
±0.4
±0.4
0.4
±2
±0.3
±0.1
±0.3
±0.05
0
Intermodulation Distortion 4
1
95.8
94
93.5
±6
±1.6
500
400
Full-scale step
VREF = 5 V
fIN = 20 kHz, VREF = 5 V
fIN = 20 kHz, VREF = 5 V
fIN = 20 kHz
fIN = 20 kHz
fIN = 20 kHz, VREF = 5 V
fIN = 20 kHz, VREF = 5 V, −60 dB input
+1
+1.5
96.5
95.5
92.5
−118
−118
95
36.5
115
Bits
LSB 1
LSB
LSB
LSB
ppm/°C
mV
ppm/°C
LSB
kSPS
ns
dB 3
dB
dB
dB
dB
dB
dB
dB
LSB means least significant bit. With the ±5 V input range, one LSB is 152.6 μV.
See the Terminology section. These specifications do include full temperature range variation but do not include the error contribution from the external reference.
All specifications in dB are referred to a full-scale input FS. Tested with an input signal at 0.5 dB below full-scale, unless otherwise specified.
4
fIN1 = 21.4 kHz, fIN2 = 18.9 kHz, each tone at −7 dB below full-scale.
2
3
Rev. A | Page 3 of 28
AD7688
VDD = 4.5 V to 5.5 V, VIO = 2.3 V to VDD, VREF = VDD, TA = –40°C to +85°C, unless otherwise noted.
Table 3.
Parameter
REFERENCE
Voltage Range
Load Current
SAMPLING DYNAMICS
−3 dB Input Bandwidth
Aperture Delay
DIGITAL INPUTS
Logic Levels
VIL
VIH
IIL
IIH
DIGITAL OUTPUTS
Data Format
Pipeline Delay
Conditions
VOL
VOH
POWER SUPPLIES
VDD
VIO
VIO Range
Standby Current 1, 2
Power Dissipation
ISINK = +500 μA
ISOURCE = −500 μA
TEMPERATURE RANGE 3
Specified Performance
Min
Typ
0.5
Max
Unit
VDD + 0.3
500 kSPS, REF = 5 V
100
V
μA
VDD = 5 V
9
2.5
MHz
ns
–0.3
0.7 × VIO
−1
−1
+0.3 × VIO
VIO + 0.3
+1
+1
Serial 16 bits twos complement
Conversion results available immediately
after completed conversion
0.4
VIO − 0.3
Specified performance
Specified performance
4.5
2.3
1.8
VDD and VIO = 5 V, 25°C
VDD = 5 V, 100 SPS throughput
VDD = 5 V, 100 kSPS throughput
VDD = 5 V, 500 kSPS throughput
TMIN to TMAX
1
3.75
3.75
−40
1
With all digital inputs forced to VIO or GND as required.
During acquisition phase.
3
Contact sales for extended temperature range.
2
Rev. A | Page 4 of 28
5.5
VDD + 0.3
VDD + 0.3
50
V
V
μA
μA
V
V
4.3
21.5
V
V
V
nA
μW
mW
mW
+85
°C
AD7688
TIMING SPECIFICATIONS
−40°C to +85°C, VDD = 4.5 V to 5.5 V, VIO = 2.3 V to 5.5 V or VDD + 0.3 V, whichever is the lowest, unless otherwise stated.
See Figure 3 and Figure 4 for load conditions.
Table 4.
Parameter
Conversion Time: CNV Rising Edge to Data Available
Acquisition Time
Time Between Conversions
CNV Pulse Width ( CS Mode )
SCK Period ( CS Mode )
SCK Period ( Chain Mode )
VIO Above 4.5 V
VIO Above 3 V
VIO Above 2.7 V
VIO Above 2.3 V
SCK Low Time
SCK High Time
SCK Falling Edge to Data Remains Valid
SCK Falling Edge to Data Valid Delay
VIO Above 4.5 V
VIO Above 3 V
VIO Above 2.7 V
VIO Above 2.3 V
CNV or SDI Low to SDO D15 MSB Valid (CS Mode)
VIO Above 4.5 V
VIO Above 2.7 V
VIO Above 2.3 V
CNV or SDI High or Last SCK Falling Edge to SDO High Impedance (CS Mode)
SDI Valid Setup Time from CNV Rising Edge (CS Mode)
SDI Valid Hold Time from CNV Rising Edge (CS Mode)
SCK Valid Setup Time from CNV Rising Edge (Chain Mode)
SCK Valid Hold Time from CNV Rising Edge (Chain Mode)
SDI Valid Setup Time from SCK Falling Edge (Chain Mode)
SDI Valid Hold Time from SCK Falling Edge (Chain Mode)
SDI High to SDO High (Chain Mode with BUSY indicator)
VIO Above 4.5 V
VIO Above 2.3 V
Rev. A | Page 5 of 28
Symbol
tCONV
tACQ
tCYC
tCNVH
tSCK
tSCK
tSCKL
tSCKH
tHSDO
tDSDO
Min
0.5
400
2
10
15
Typ
Max
1.6
17
18
19
20
7
7
5
Unit
μs
ns
μs
ns
ns
ns
ns
ns
ns
ns
ns
ns
14
15
16
17
ns
ns
ns
ns
15
18
22
25
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
15
26
ns
ns
tEN
tDIS
tSSDICNV
tHSDICNV
tSSCKCNV
tHSCKCNV
tSSDISCK
tHSDISCK
tDSDOSDI
15
0
5
5
3
4
AD7688
ABSOLUTE MAXIMUM RATINGS
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Table 5.
Parameter
Analog Inputs
IN+ 1 , IN−1
REF
Supply Voltages
VDD, VIO to GND
VDD to VIO
Digital Inputs to GND
Digital Outputs to GND
Storage Temperature Range
Junction Temperature
Lead Temperature Range
GND − 0.3 V to VDD + 0.3 V
or ±130 mA
GND − 0.3 V to VDD + 0.3 V
THERMAL RESISTANCE
−0.3 V to +7 V
±7 V
−0.3 V to VIO + 0.3 V
−0.3 V to VIO + 0.3 V
−65°C to +150°C
150°C
JEDEC J-STD-20
θJA is specified for the worst-case conditions, that is, a device
soldered in a circuit board for surface-mount packages.
Table 6. Thermal Resistance
Package Type
10-Lead QFN (LFCSP)
10-Lead MSOP
θJA
48.7
200
See the Analog Input section.
ESD CAUTION
500μA
IOL
1.4V
TO SDO
CL
50pF
500μA
02973-003
IOH
Figure 3. Load Circuit for Digital Interface Timing
70% VIO
30% VIO
tDELAY
tDELAY
2V OR VIO – 0.5V1
2V OR VIO – 0.5V1
0.8V OR 0.5V2
0.8V OR 0.5V2
12V IF VIO ABOVE 2.5V, VIO – 0.5V IF VIO BELOW 2.5V.
20.8V IF VIO ABOVE 2.5V, 0.5V IF VIO BELOW 2.5V.
Figure 4. Voltage Levels for Timing
Rev. A | Page 6 of 28
02973-004
1
Rating
θJC
2.96
44
Unit
°C
°C
AD7688
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
AD7688
9
SDI
IN+ 3
TOP VIEW
(Not to Scale)
8
SCK
7
SDO
6
CNV
IN– 4
GND 5
REF 1
VDD 2
IN+ 3
IN– 4
GND 5
10 VIO
AD7688
9 SDI
TOP VIEW
(Not to Scale)
8 SCK
7 SDO
6 CNV
NOTES
1. FOR THE LFCSP PACKAGE ONLY,
THE EXPOSED PADDLE MUST BE
CONNECTED TO GND.
02973-006
10 VIO
02973-005
REF 1
VDD 2
Figure 6. 10-Lead QFN (LFCSP) Pin Configuration
Figure 5. 10-Lead MSOP Pin Configuration
Table 7. Pin Function Descriptions
Pin No.
1
Mnemonic
REF
Type 1
AI
2
3
4
5
6
VDD
IN+
IN−
GND
CNV
P
AI
AI
P
DI
7
8
9
SDO
SCK
SDI
DO
DI
DI
10
VIO
P
EPAD
N/A
Function
Reference Input Voltage. The REF range is from 0.5 V to VDD. It is referred to the GND pin. This pin should
be decoupled closely to the pin with a 10 μF capacitor.
Power Supply.
Differential Positive Analog Input.
Differential Negative Analog Input.
Power Supply Ground.
Convert Input. This input has multiple functions. On its leading edge, it initiates the conversions and
selects the interface mode, chain or CS. In CS mode, it enables the SDO pin when low. In chain mode, the
data should be read when CNV is high.
Serial Data Output. The conversion result is output on this pin. It is synchronized to SCK.
Serial Data Clock Input. When the part is selected, the conversion result is shifted out by this clock.
Serial Data Input. This input provides multiple features. It selects the interface mode of the ADC as follows:
Chain mode is selected if SDI is low during the CNV rising edge. In this mode, SDI is used as a data input to
daisy-chain the conversion results of two or more ADCs onto a single SDO line. The digital data level on
SDI is output on SDO with a delay of 16 SCK cycles.
CS mode is selected if SDI is high during the CNV rising edge. In this mode, either SDI or CNV can enable
the serial output signals when low, and if SDI or CNV is low when the conversion is complete, the BUSY
indicator feature is enabled.
Input/Output Interface Digital Power. Nominally at the same supply as the host interface (1.8 V, 2.5 V, 3 V,
or 5 V).
For the LFCSP package only, the exposed paddle must be connected to GND.
1
AI = Analog Input, DI = Digital Input, DO = Digital Output, P = Power, and N/A = not applicable.
Rev. A | Page 7 of 28
AD7688
TERMINOLOGY
Integral Nonlinearity Error (INL)
It refers to the deviation of each individual code from a line
drawn from negative full scale through positive full scale. The
point used as negative full scale occurs ½ LSB before the first
code transition. Positive full scale is defined as a level 1½ LSB
beyond the last code transition. The deviation is measured from
the middle of each code to the true straight line (Figure 25).
Differential Nonlinearity Error (DNL)
In an ideal ADC, code transitions are 1 LSB apart. DNL is the
maximum deviation from this ideal value. It is often specified in
terms of resolution for which no missing codes are guaranteed.
Zero Error
It is the difference between the ideal midscale voltage, that is, 0
V, from the actual voltage producing the midscale output code,
that is, 0 LSB.
Gain Error
The first transition (from 100 . . . 00 to 100 . . . 01) should occur
at a level ½ LSB above nominal negative full scale (−4.999924 V
for the ±5 V range). The last transition (from 011…10 to
011…11) should occur for an analog voltage 1½ LSB below the
nominal full scale (+4.999771 V for the ±5 V range.) The gain
error is the deviation of the difference between the actual level
of the last transition and the actual level of the first transition
from the difference between the ideal levels.
Spurious-Free Dynamic Range (SFDR)
SFDR is the difference, in decibels (dB), between the rms
amplitude of the input signal and the peak spurious signal.
Effective Number of Bits (ENOB)
ENOB is a measurement of the resolution with a sine wave
input. It is related to S/(N+D) by the following formula
ENOB = (S/[N + D]dB − 1.76)/6.02
and is expressed in bits.
Total Harmonic Distortion (THD)
THD is the ratio of the rms sum of the first five harmonic
components to the rms value of a full-scale input signal and is
expressed in dB.
Dynamic Range
It is the ratio of the rms value of the full scale to the total rms
noise measured with the inputs shorted together. The value for
dynamic range is expressed in dB.
Signal-to-Noise Ratio (SNR)
SNR is the ratio of the rms value of the actual input signal to the
rms sum of all other spectral components below the Nyquist
frequency, excluding harmonics and dc. The value for SNR is
expressed in dB.
Signal-to-(Noise + Distortion) Ratio (S/[N+D])
S/(N+D) is the ratio of the rms value of the actual input signal
to the rms sum of all other spectral components below the
Nyquist frequency, including harmonics but excluding dc. The
value for S/(N+D) is expressed in dB.
Aperture Delay
Aperature delay is the measure of the acquisition performance.
It is the time between the rising edge of the CNV input and
when the input signal is held for a conversion.
Transient Response
It is the time required for the ADC to accurately acquire its
input after a full-scale step function was applied.
Rev. A | Page 8 of 28
AD7688
TYPICAL PERFORMANCE CHARACTERISTICS
1.5
1.5
POSITIVE DNL = +0.37LSB
NEGATIVE DNL = –0.21LSB
1.0
0.5
0.5
DNL (LSB)
1.0
0
–0.5
–0.5
–1.0
–1.0
–1.5
0
16384
32768
CODE
49152
02973-009
0
02973-001
INL (LSB)
POSITIVE INL = +0.31LSB
NEGATIVE INL = –0.39LSB
–1.5
65535
0
Figure 7. Integral Nonlinearity vs. Code
16384
32768
CODE
49152
65535
Figure 10. Differential Nonlinearity vs. Code
300000
160000
VDD = REF = 5V
256159
136187
VDD = REF = 5V
140000
250000
124933
120000
200000
COUNTS
COUNTS
100000
150000
80000
60000
100000
40000
50000
2930
2031
0
0
0
6F
70
71
72
73
CODE IN HEX
74
20000
0
71
72
0
0
75
76
0
75
Figure 8. Histogram of a DC Input at the Code Center
73
74
CODE IN HEX
Figure 11. Histogram of a DC Input at the Code Transition
100
0
16384 POINT FFT
VDD = REF = 5V
FS = 500KSPS
FIN = 2kHz
SNR = 95.6dB
THD = –117.7dB
SFDR = –117.9dB
2nd HARM = –125dB
3rd HARM = –119dB
–40
–60
–80
99
98
97
96
SNR (dB)
–20
–100
95
94
–120
93
–140
–160
–180
0
25
50
75
100 125 150 175
FREQUENCY (kHz)
200
225
250
02973-011
92
02973-008
AMPLITUDE (dB of Full Scale)
0
02973-010
0
02973-007
0
91
90
–10
–8
–6
–4
INPUT LEVEL (dB)
Figure 12. SNR vs. Input Level
Figure 9. FFT Plot
Rev. A | Page 9 of 28
–2
0
AD7688
100
17.0
–100
–105
SNR
16.0
S/[N + D]
70
2.3
2.7
3.1
3.5
3.9
4.3
4.7
REFERENCE VOLTAGE (V)
5.1
13.0
5.5
–115
THD
–120
SFDR
–125
–130
2.3
02973-015
14.0
85
THD, SFDR (dB)
15.0
90
ENOB (Bits)
–110
ENOB
02973-012
SNR, S/(N + D) (dB)
95
2.7
3.1
3.5
3.9
4.3
4.7
REFERENCE VOLTAGE (V)
–90
100
VREF = 5V
VREF = 5V
–100
THD (dB)
95
90
–110
–120
80
–55
02973-013
85
–35
–15
5
25
45
65
TEMPERATURE (°C)
85
105
–130
–55
125
02973-016
SNR (dB)
5.5
Figure 16. THD, SFDR vs. Reference Voltage
Figure 13. SNR, S/(N + D), and ENOB vs. Reference Voltage
–35
–15
5
25
45
65
TEMPERATURE (°C)
85
105
125
Figure 17. THD vs. Temperature
Figure 14. SNR vs. Temperature
–60
100
VREF = 5V, –10dB
–70
90
–80
THD (dB)
95
VREF = 5V, –1dB
–90
VREF = 5V, –1dB
80
–100
75
–110
70
0
50
100
FREQUENCY (kHz)
150
VREF = 5V, –10dB
02973-017
85
02973-014
S/(N + D) (dB)
5.1
–120
200
0
50
100
FREQUENCY (kHz)
Figure 18. THD vs. Frequency
Figure 15. S/(N + D) vs. Frequency
Rev. A | Page 10 of 28
150
200
AD7688
6
1000
fS = 100kSPS
4
750
OFFSET, GAIN ERROR (LSB)
OPERATING CURRENT (μA)
VDD
500
250
GAIN ERROR
2
0
–2
OFFSET ERROR
VIO
0
4.50
4.75
5.00
SUPPLY (V)
5.25
–6
–55
5.5
–15
5
25
45
65
TEMPERATURE (°C)
85
105
125
25
1000
20
750
TDSDO DELAY (ns)
500
15
VDD = 5V, 85°C
10
VDD = 5V, 25°C
250
5
0
–55
–35
–15
5
25
45
65
TEMPERATURE (°C)
85
02973-019
VDD + VIO
105
125
1000
fS = 100kSPS
VDD
750
500
02973-020
250
VIO
–35
–15
5
25
45
65
TEMPERATURE (°C)
85
0
0
20
40
60
80
SDO CAPACITIVE LOAD (pF)
100
Figure 23. tDSDO Delay vs. Capacitance Load and Supply
Figure 20. Power-Down Currents vs. Temperature
0
–55
02973-022
POWER-DOWN CURRENT (nA)
–35
Figure 22. Offset and Gain Error vs. Temperature
Figure 19. Operating Currents vs. Supply
OPERATING CURRENT (μA)
02973-021
02973-018
–4
105
125
Figure 21. Operating Currents vs. Temperature
Rev. A | Page 11 of 28
120
AD7688
IN+
SWITCHES CONTROL
MSB
32,768C 16,384C
LSB
4C
2C
C
SW+
C
BUSY
REF
COMP
GND
32,768C 16,384C
4C
2C
C
CONTROL
LOGIC
OUTPUT CODE
C
MSB
LSB
SW–
02973-023
CNV
IN–
Figure 24. ADC Simplified Schematic
CIRCUIT INFORMATION
CONVERTER OPERATION
The AD7688 is a fast, low power, single-supply, precise 16-bit
ADC using a successive approximation architecture.
The AD7688 is a successive approximation ADC based on a
charge redistribution DAC. Figure 24 shows the simplified
schematic of the ADC. The capacitive DAC consists of two
identical arrays of 16 binary weighted capacitors, which are
connected to the two comparator inputs.
The AD7688 is capable of converting 500,000 samples per
second (500 kSPS) and powers down between conversions.
When operating at 100 SPS, for example, it consumes 3.75 μW
typically, ideal for battery-powered applications.
The AD7688 provides the user with an on-chip track-and-hold
and does not exhibit any pipeline delay or latency, making it
ideal for multiple multiplexed channel applications.
The AD7688 is specified from 4.5 V to 5.5 V and can be
interfaced to any of the 1.8 V to 5 V digital logic family. It is
housed in a 10-lead MSOP or a tiny 10-lead QFN (LFCSP) that
combines space savings and allows flexible configurations.
It is pin-for-pin-compatible with the AD7685, AD7686, and
AD7687.
During the acquisition phase, terminals of the array tied to the
comparator’s input are connected to GND via SW+ and SW−.
All independent switches are connected to the analog inputs.
Thus, the capacitor arrays are used as sampling capacitors and
acquire the analog signal on the IN+ and IN− inputs. When the
acquisition phase is complete and the CNV input goes high, a
conversion phase is initiated. When the conversion phase
begins, SW+ and SW− are opened first. The two capacitor
arrays are then disconnected from the inputs and connected to
the GND input. Therefore, the differential voltage between the
inputs IN+ and IN− captured at the end of the acquisition phase
is applied to the comparator inputs, causing the comparator to
become unbalanced. By switching each element of the capacitor
array between GND and REF, the comparator input varies by
binary weighted voltage steps (VREF/2, VREF/4 . . . VREF/65536).
The control logic toggles these switches, starting with the MSB,
in order to bring the comparator back into a balanced
condition. After the completion of this process, the part returns
to the acquisition phase and the control logic generates the
ADC output code and a BUSY signal indicator.
Because the AD7688 has an on-board conversion clock, the
serial clock, SCK, is not required for the conversion process.
Rev. A | Page 12 of 28
AD7688
TYPICAL CONNECTION DIAGRAM
The ideal transfer characteristic for the AD7688 is shown in
Figure 25 and Table 8.
Figure 26 shows an example of the recommended connection
diagram for the AD7688 when multiple supplies are available.
ADC CODE (TWOS COMPLEMENT)
Transfer Functions
011...111
011...110
011...101
100...010
100...001
–FSR + 1 LSB
+FSR – 1 LSB
+FSR – 1.5 LSB
–FSR + 0.5 LSB
02973-024
100...000
–FSR
ANALOG INPUT
Figure 25. ADC Ideal Transfer Function
Table 8. Output Codes and Ideal Input Voltages
Description
FSR – 1 LSB
Midscale + 1 LSB
Midscale
Midscale – 1 LSB
–FSR + 1 LSB
–FSR
Analog Input
VREF = 5 V
+4.999847 V
+152.6 μV
0V
−152.6 μV
−4.999847 V
−5 V
Digital Output Code Hexa
7FFF1
0001
0000
FFFF
8001
80002
1.
This is also the code for an overranged analog input (VIN+ − VIN− above VREF −
VGND).
2.
This is also the code for an underranged analog input (VIN+ − VIN− below −VREF
+ VGND).
≥7V
REF1
5V
10μF2
100nF
≥7V
1.8V TO VDD
100nF
33Ω
REF
0 TO VREF
VDD
IN+
3
≤–2V
≥7V
VIO
SDI
2.7nF
SCK
AD7688
4
IN–
33Ω
3- OR 4-WIRE INTERFACE5
SDO
CNV
GND
VREF TO 0
3
≤–2V
2.7nF
1SEE REFERENCE SECTION FOR REFERENCE SELECTION.
2C
REF IS USUALLY A 10μF CERAMIC CAPACITOR (X5R).
3SEE DRIVER AMPLIFIER CHOICE SECTION.
4OPTIONAL FILTER. SEE ANALOG INPUT SECTION.
5SEE DIGITAL INTERFACE FOR MOST CONVENIENT INTERFACE
MODE.
Figure 26. Typical Application Diagram with Multiple Supplies
Rev. A | Page 13 of 28
02973-025
4
AD7688
ANALOG INPUT
Figure 27 shows an equivalent circuit of the input structure of
the AD7688.
The two diodes, D1 and D2, provide ESD protection for the
analog inputs IN+ and IN−. Care must be taken to ensure that
the analog input signal never exceeds the supply rails by more
than 0.3 V because this causes these diodes to begin to forwardbias and start conducting current. These diodes can handle a
forward-biased current of 130 mA maximum. For instance,
these conditions could eventually occur when the input buffer’s
(U1) supplies are different from VDD. In such a case, an input
buffer with a short-circuit current limitation can be used to
protect the part.
VDD
D1
IN+
OR IN–
CPIN
CIN
RIN
02973-026
D2
GND
During the acquisition phase, the impedance of the analog
inputs (IN+ or IN−) can be modeled as a parallel combination
of capacitor, CPIN, and the network formed by the series
connection of RIN and CIN. CPIN is primarily the pin capacitance.
RIN is typically 600 Ω and is a lumped component made up of
some serial resistors and the on resistance of the switches. CIN is
typically 30 pF and is mainly the ADC sampling capacitor.
During the conversion phase, where the switches are opened,
the input impedance is limited to CPIN. RIN and CIN make a
1-pole, low-pass filter that reduces undesirable aliasing effects
and limits the noise.
When the source impedance of the driving circuit is low, the
AD7688 can be driven directly. Large source impedances
significantly affect the ac performance, especially total
harmonic distortion (THD). The dc performances are less
sensitive to the input impedance. The maximum source
impedance depends on the amount of THD that can be
tolerated. The THD degrades as a function of the source
impedance and the maximum input frequency, as shown in
Figure 29.
–60
Figure 27. Equivalent Analog Input Circuit
80
–70
–80
THD (dB)
The analog input structure allows the sampling of the true
differential signal between IN+ and IN−. By using these
differential inputs, signals common to both inputs are rejected,
as shown in Figure 28, which represents the typical CMRR over
frequency.
–90
RS = 250Ω
–100
RS = 100Ω
RS = 50Ω
–110
–120
70
0
25
50
FREQUENCY (kHz)
75
Figure 29. THD vs. Analog Input Frequency and Source Resistance
02973-027
CMRR (dB)
02973-028
RS = 33Ω
VDD = 5V
60
1
10
100
FREQUENCY (kHz)
1000
10000
Figure 28. Analog Input CMRR vs. Frequency
Rev. A | Page 14 of 28
100
AD7688
DRIVER AMPLIFIER CHOICE
SINGLE-TO-DIFFERENTIAL DRIVER
Although the AD7688 is easy to drive, the driver amplifier
needs to meet the following requirements:
For applications using a single-ended analog signal, either
bipolar or unipolar, a single-ended-to-differential driver
allows for a differential input into the part. The schematic is
shown in Figure 30. When provided a single-ended input signal,
this configuration produces a differential ±VREF with midscale
at VREF/2.
The noise generated by the driver amplifier needs to be
kept as low as possible in order to preserve the SNR and
transition noise performance of the AD7688. Note that the
AD7688 has a noise much lower than most of the other
16-bit ADCs and, therefore, can be driven by a noisier op
amp while preserving the same or better system performance. The noise coming from the driver is filtered by the
AD7688 analog input circuit 1-pole, low-pass filter made
by RIN and CIN or by the external filter, if one is used.
Because the typical noise of the AD7688 is 53 μV rms,
the SNR degradation due to the amplifier is
SNR LOSS
⎛
⎜
53
= 20log ⎜⎜
π
⎜⎜ 53 2 + f −3dB (Ne N ) 2
2
⎝
VREF
10μF
100nF
590Ω
IN+ REF
590Ω
10kΩ
U2
AD7688
IN–
VREF
10kΩ
100nF
Figure 30. Single-Ended-to-Differential Driver Circuit
where:
VOLTAGE REFERENCE INPUT
f–3dB is the input bandwidth in MHz of the AD7688
(9 MHz) or the cutoff frequency of the input filter, if one
is used.
The AD7688 voltage reference input, REF, has a dynamic input
impedance and should therefore be driven by a low impedance
source with efficient decoupling between the REF and GND
pins, as explained in the Layout section.
eN is the equivalent input noise voltage of the op amp,
in nV/√Hz.
•
U1
VREF
⎞
⎟
⎟
⎟
⎟⎟
⎠
N is the noise gain of the amplifier (for example, +1 in
buffer configuration).
•
590Ω
ANALOG INPUT
(±10V, ±5V, ..)
02973-029
•
For ac applications, the driver should have a THD
performance commensurate with the AD7688. Figure 18
shows the THD vs. frequency that the driver should
exceed.
For multichannel multiplexed applications, the driver
amplifier and the AD7688 analog input circuit must settle
for a full-scale step onto the capacitor array at a 16-bit level
(0.0015%, 15 ppm). In the amplifier’s data sheet, settling at
0.1% to 0.01% is more commonly specified. This could
differ significantly from the settling time at a 16-bit level
and should be verified prior to driver selection.
When REF is driven by a very low impedance source, for
example, a reference buffer using the AD8031 or the AD8605, a
10 μF (X5R, 0805 size) ceramic chip capacitor is appropriate for
optimum performance.
If an unbuffered reference voltage is used, the decoupling value
depends on the reference used. For instance, a 22 μF (X5R,
1206 size) ceramic chip capacitor is appropriate for optimum
performance using a low temperature drift ADR43x reference.
If desired, smaller reference decoupling capacitor values down
to 2.2 μF can be used with a minimal impact on performance,
especially DNL.
Regardless, there is no need for an additional lower value
ceramic decoupling capacitor (for example, 100 nF) between the
REF and GND pins.
Table 9. Recommended Driver Amplifiers
POWER SUPPLY
Amplifier
AD8021
AD8022
OP184
AD8605, AD8615
AD8519
AD8031
The AD7688 is specified at 4.5 V to 5.5 V. It has, unlike other
low voltage converters, a low enough noise to design a 16-bit
resolution system with low supply and respectable performance.
It uses two power supply pins: a core supply VDD and a digital
input/output interface supply VIO. VIO allows direct interface
with any logic between 1.8 V and VDD. To reduce the supplies
needed, the VIO and VDD can be tied together. The AD7688 is
independent of power supply sequencing between VIO and
VDD. Additionally, it is very insensitive to power supply
variations over a wide frequency range, as shown in Figure 31,
which represents PSRR over frequency.
Typical Application
Very low noise and high frequency
Low noise and high frequency
Low power, low noise, and low frequency
5 V single-supply, low power
Small, low power and low frequency
High frequency and low power
Rev. A | Page 15 of 28
AD7688
95
5V
5V
90
10Ω
5V
1μF
AD8031
10μF
1μF
1
80
REF
VDD
VIO
75
AD7688
70
1OPTIONAL
02973-030
65
60
1
10
100
FREQUENCY (kHz)
1000
10000
Figure 31. PSRR vs. Frequency
The AD7688 powers down automatically at the end of each
conversion phase and, therefore, the power scales linearly with
the sampling rate, as shown in Figure 32. This makes the part
ideal for low sampling rate (even a few Hz) and low batterypowered applications.
1000
10
VIO
0.1
0.001
10
Figure 33. Example of Application Circuit
DIGITAL INTERFACE
Though the AD7688 has a reduced number of pins, it offers
flexibility in its serial interface modes.
The AD7688, when in CS mode, is compatible with SPI, QSPI,
digital hosts, and DSPs, e.g., Blackfin® ADSP-BF53x or ADSP219x. This interface can use either 3-wire or 4-wire. A 3-wire
interface using the CNV, SCK, and SDO signals minimizes
wiring connections useful, for instance, in isolated applications.
A 4-wire interface using the SDI, CNV, SCK, and SDO signals
allows CNV, which initiates the conversions, to be independent
of the readback timing (SDI). This is useful in low jitter
sampling or simultaneous sampling applications.
The AD7688, when in chain mode, provides a daisy chain
feature using the SDI input for cascading multiple ADCs on a
single data line similar to a shift register.
02973-031
OPERATING CURRENT (μA)
VDD
REFERENCE BUFFER AND FILTER.
02973-032
PSRR (dB)
85
10kΩ
100
1000
10000
SAMPLING RATE (SPS)
100000
1000000
Figure 32. Operating Currents vs. Sampling Rate
SUPPLYING THE ADC FROM THE REFERENCE
For simplified applications, the AD7688, with its low operating
current, can be supplied directly using the reference circuit
shown in Figure 33. The reference line can be driven by either:
•
The system power supply directly.
•
A reference voltage with enough current output capability,
such as the ADR43x.
•
A reference buffer, such as the AD8031, which can also
filter the system power supply, as shown in Figure 33.
The mode in which the part operates depends on the SDI level
when the CNV rising edge occurs. The CS mode is selected if
SDI is high and the chain mode is selected if SDI is low. The
SDI hold time is such that when SDI and CNV are connected
together, the chain mode is always selected.
In either mode, the AD7688 offers the flexibility to optionally
force a start bit in front of the data bits. This start bit can be
used as a BUSY signal indicator to interrupt the digital host and
trigger the data reading. Otherwise, without a BUSY indicator,
the user must time out the maximum conversion time prior to
readback.
The BUSY indicator feature is enabled as:
• In the CS mode, if CNV or SDI is low when the ADC
conversion ends (Figure 37 and Figure 41).
• In the chain mode, if SCK is high during the CNV rising edge
(Figure 45).
Rev. A | Page 16 of 28
AD7688
to capture the data, a digital host using the SCK falling edge
allows a faster reading rate provided it has an acceptable hold
time. After the 16th SCK falling edge or when CNV goes high,
whichever is earlier, SDO returns to high impedance.
CS MODE 3-WIRE, NO BUSY INDICATOR
This mode is usually used when a single AD7688 is connected
to an SPI-compatible digital host. The connection diagram is
shown in Figure 34 and the corresponding timing is given in
Figure 35.
CONVERT
With SDI tied to VIO, a rising edge on CNV initiates a
conversion, selects the CS mode, and forces SDO to high
impedance. Once a conversion is initiated, it continues to
completion irrespective of the state of CNV. For instance, it
could be useful to bring CNV low to select other SPI devices,
such as analog multiplexers, but CNV must be returned high
before the minimum conversion time and held high until the
maximum conversion time to avoid the generation of the BUSY
signal indicator. When the conversion is complete, the AD7688
enters the acquisition phase and powers down. When CNV
goes low, the MSB is output onto SDO. The remaining data bits
are then clocked by subsequent SCK falling edges. The data is
valid on both SCK edges. Although the rising edge can be used
DIGITAL HOST
CNV
VIO
SDI
AD7688
DATA IN
SDO
02973-033
SCK
CLK
Figure 34. CS Mode 3-Wire, No BUSY Indicator
Connection Diagram (SDI High)
SDI = 1
tCYC
tCNVH
CNV
ACQUISITION
tCONV
tACQ
CONVERSION
ACQUISITION
tSCK
tSCKL
1
2
3
14
tHSDO
16
tSCKH
tDSDO
tEN
SDO
15
D15
D14
D13
tDIS
D1
Figure 35. CS Mode 3-Wire, No BUSY Indicator Serial Interface Timing (SDI High)
Rev. A | Page 17 of 28
D0
02973-034
SCK
AD7688
a digital host using the SCK falling edge allows a faster reading
rate provided it has an acceptable hold time. After the optional
17th SCK falling edge, or when CNV goes high, whichever is
earlier, SDO returns to high impedance.
CS MODE 3-WIRE WITH BUSY INDICATOR
This mode is usually used when a single AD7688 is connected
to an SPI-compatible digital host having an interrupt input.
The connection diagram is shown in Figure 36 and the
corresponding timing is given in Figure 37.
If multiple AD7688s are selected at the same time, the SDO
output pin handles this contention without damage or induced
latch-up. Meanwhile, it is recommended to keep this contention
as short as possible to limit extra power dissipation.
With SDI tied to VIO, a rising edge on CNV initiates a
conversion, selects the CS mode, and forces SDO to high
impedance. SDO is maintained in high impedance until the
completion of the conversion irrespective of the state of CNV.
Prior to the minimum conversion time, CNV could be used to
select other SPI devices, such as analog multiplexers, but CNV
must be returned low before the minimum conversion time and
held low until the maximum conversion time to guarantee the
generation of the BUSY signal indicator. When the conversion
is complete, SDO goes from high impedance to low. With a
pull-up on the SDO line, this transition can be used as an
interrupt signal to initiate the data reading controlled by the
digital host. The AD7688 then enters the acquisition phase and
powers down. The data bits are then clocked out, MSB first, by
subsequent SCK falling edges. The data is valid on both SCK
edges. Although the rising edge can be used to capture the data,
CONVERT
VIO
CNV
VIO
DIGITAL HOST
47kΩ
AD7688
DATA IN
SDO
SCK
IRQ
02973-035
SDI
CLK
Figure 36. CS Mode 3-Wire with BUSY Indicator
Connection Diagram (SDI High)
SDI = 1
tCYC
tCNVH
CNV
ACQUISITION
tCONV
tACQ
CONVERSION
ACQUISITION
tSCK
tSCKL
1
2
3
tHSDO
15
16
17
tSCKH
tDSDO
SDO
tDIS
D15
D14
D1
Figure 37. CS Mode 3-Wire with BUSY Indicator Serial Interface Timing (SDI High)
Rev. A | Page 18 of 28
D0
02973-036
SCK
AD7688
time and held high until the maximum conversion time to
avoid the generation of the BUSY signal indicator. When the
conversion is complete, the AD7688 enters the acquisition
phase and powers down. Each ADC result can be read by
bringing low its SDI input which consequently outputs the MSB
onto SDO. The remaining data bits are then clocked by
subsequent SCK falling edges. The data is valid on both SCK
edges. Although the rising edge can be used to capture the data,
a digital host using the SCK falling edge allows a faster reading
rate provided it has an acceptable hold time. After the 16th SCK
falling edge, or when SDI goes high, whichever is earlier, SDO
returns to high impedance and another AD7688 can be read.
CS MODE 4-WIRE, NO BUSY INDICATOR
This mode is usually used when multiple AD7688s are
connected to an SPI-compatible digital host.
A connection diagram example using two AD7688s is shown in
Figure 38 and the corresponding timing is given in Figure 39.
With SDI high, a rising edge on CNV initiates a conversion,
selects the CS mode, and forces SDO to high impedance. In this
mode, CNV must be held high during the conversion phase and
the subsequent data readback (if SDI and CNV are low, SDO is
driven low). Prior to the minimum conversion time, SDI could
be used to select other SPI devices, such as analog multiplexers,
but SDI must be returned high before the minimum conversion
CS2
CS1
CONVERT
CNV
AD7688
SDO
SDI
AD7688
SCK
SDO
SCK
02973-037
SDI
DIGITAL HOST
CNV
DATA IN
CLK
Figure 38. CS Mode 4-Wire, No BUSY Indicator Connection Diagram
tCYC
CNV
ACQUISITION
tCONV
tACQ
CONVERSION
ACQUISITION
tSSDICNV
SDI(CS1)
tHSDICNV
SDI(CS2)
tSCK
tSCKL
SCK
1
2
14
3
tHSDO
16
17
18
30
31
32
tSCKH
tDSDO
tEN
D15
D14
D13
tDIS
D1
D0
D15
D14
D1
D0
02973-038
SDO
15
Figure 39. CS Mode 4-Wire, No BUSY Indicator Serial Interface Timing
Rev. A | Page 19 of 28
AD7688
as an interrupt signal to initiate the data readback controlled by
the digital host. The AD7688 then enters the acquisition phase
and powers down. The data bits are then clocked out, MSB first,
by subsequent SCK falling edges. The data is valid on both SCK
edges. Although the rising edge can be used to capture the data,
a digital host using the SCK falling edge allows a faster reading
rate provided it has an acceptable hold time. After the optional
17th SCK falling edge, or SDI going high, whichever is earlier,
the SDO returns to high impedance.
CS MODE 4-WIRE WITH BUSY INDICATOR
This mode is usually used when a single AD7688 is connected
to an SPI-compatible digital host, which has an interrupt input,
and it is desired to keep CNV, which is used to sample the
analog input, independent of the signal used to select the data
reading. This requirement is particularly important in
applications where low jitter on CNV is desired.
The connection diagram is shown in Figure 40 and the
corresponding timing is given in Figure 41.
CS1
CONVERT
With SDI high, a rising edge on CNV initiates a conversion,
selects the CS mode, and forces SDO to high impedance. In this
mode, CNV must be held high during the conversion phase and
the subsequent data readback (if SDI and CNV are low, SDO is
driven low). Prior to the minimum conversion time, SDI could
be used to select other SPI devices, such as analog multiplexers,
but SDI must be returned low before the minimum conversion
time and held low until the maximum conversion time to
guarantee the generation of the BUSY signal indicator. When
the conversion is complete, SDO goes from high impedance to
low. With a pull-up on the SDO line, this transition can be used
VIO
CNV
DIGITAL HOST
47kΩ
AD7688
DATA IN
SDO
SCK
IRQ
02973-039
SDI
CLK
Figure 40. CS Mode 4-Wire with BUSY Indicator Connection Diagram
tCYC
CNV
ACQUISITION
tCONV
tACQ
CONVERSION
ACQUISITION
tSSDICNV
SDI
tSCK
tHSDICNV
tSCKL
1
2
3
tHSDO
15
16
17
tSCKH
tDSDO
tDIS
tEN
SDO
D15
D14
D1
Figure 41. CS Mode 4-Wire with BUSY Indicator Serial Interface Timing
Rev. A | Page 20 of 28
D0
02973-040
SCK
AD7688
onto SDO and the AD7688 enters the acquisition phase and
powers down. The remaining data bits stored in the internal
shift register are then clocked by subsequent SCK falling edges.
For each ADC, SDI feeds the input of the internal shift register
and is clocked by the SCK falling edge. Each ADC in the chain
outputs its data MSB first, and 16 × N clocks are required to
readback the N ADCs. The data is valid on both SCK edges.
Although the rising edge can be used to capture the data, a
digital host using the SCK falling edge allows a faster reading
rate and, consequently more AD7688s in the chain, provided
the digital host has an acceptable hold time. The maximum
conversion rate may be reduced due to the total readback time.
For instance, with a 3 ns digital host set-up time and 3 V
interface, up to four AD7688s running at a conversion rate of
360 kSPS can be daisy-chained on a 3-wire port.
CHAIN MODE, NO BUSY INDICATOR
This mode can be used to daisy-chain multiple AD7688s on a 3wire serial interface. This feature is useful for reducing
component count and wiring connections, for example, in
isolated multiconverter applications or for systems with a
limited interfacing capacity. Data readback is analogous to
clocking a shift register.
A connection diagram example using two AD7688s is shown in
Figure 42 and the corresponding timing is given in Figure 43.
When SDI and CNV are low, SDO is driven low. With SCK low,
a rising edge on CNV initiates a conversion, selects the chain
mode, and disables the BUSY indicator. In this mode, CNV is
held high during the conversion phase and the subsequent data
readback. When the conversion is complete, the MSB is output
CONVERT
SDI
CNV
AD7688
SDO
DIGITAL HOST
AD7688
SDI
A
B
SCK
SCK
SDO
DATA IN
02973-041
CNV
CLK
Figure 42. Chain Mode, No BUSY Indicator Connection Diagram
SDIA = 0
tCYC
CNV
ACQUISITION
tCONV
tACQ
CONVERSION
ACQUISITION
tSCK
tSCKL
tSSCKCNV
SCK
1
tHSCKCNV
2
3
14
15
tSSDISCK
16
17
18
DA15
DA14
30
31
32
DA1
DA0
tSCKH
SDOA = SDIB
DA15
DA14
DA13
DA 1
DA 0
DB15
DB14
DB13
DB 1
DB 0
tHSDO
tDSDO
SDOB
Figure 43. Chain Mode, No BUSY Indicator Serial Interface Timing
Rev. A | Page 21 of 28
02973-042
tHSDISC
tEN
AD7688
Figure 44) SDO is driven high. This transition on SDO can be
used as a BUSY indicator to trigger the data readback controlled
by the digital host. The AD7688 then enters the acquisition
phase and powers down. The data bits stored in the internal
shift register are then clocked out, MSB first, by subsequent
SCK falling edges. For each ADC, SDI feeds the input of the
internal shift register and is clocked by the SCK falling edge.
Each ADC in the chain outputs its data MSB first, and 16 × N +
1 clocks are required to readback the N ADCs. Although the
rising edge can be used to capture the data, a digital host using
the SCK falling edge allows a faster reading rate and
consequently more AD7688s in the chain, provided the digital
host has an acceptable hold time. For instance, with a 3 ns
digital host setup time and 3 V interface, up to four AD7688s
running at a conversion rate of 360 kSPS can be daisy-chained
to a single 3-wire port.
CHAIN MODE WITH BUSY INDICATOR
This mode can also be used to daisy-chain multiple AD7688s
on a 3-wire serial interface while providing a BUSY indicator.
This feature is useful for reducing component count and wiring
connections, for example, in isolated multiconverter
applications or for systems with a limited interfacing capacity.
Data readback is analogous to clocking a shift register.
A connection diagram example using three AD7688s is shown
in Figure 44 and the corresponding timing is given in Figure 45.
When SDI and CNV are low, SDO is driven low. With SCK
high, a rising edge on CNV initiates a conversion, selects the
chain mode, and enables the BUSY indicator feature. In this
mode, CNV is held high during the conversion phase and the
subsequent data readback. When all ADCs in the chain have
completed their conversions, the nearend ADC (ADC C in
CONVERT
SDI
AD7688
CNV
SDO
AD7688
SDI
DIGITAL HOST
CNV
SDO
SDI
AD7688
A
B
C
SCK
SCK
SCK
DATA IN
SDO
IRQ
02973-043
CNV
CLK
Figure 44. Chain Mode with BUSY Indicator Connection Diagram
tCYC
ACQUISITION
tCONV
tACQ
ACQUISITION
CONVERSION
tSSCKCNV
SCK
tSCKH
1
tHSCKCNV
2
tSSDISCK
tEN
SDOA = SDIB
3
4
tSCK
15
16
18
19
31
32
33
34
35
tSCKL
tHSDISC
DA15 DA14 DA13
17
DA1
SDOB = SDIC
49
DA0
tDSDOSDI
DB15 DB14 DB13
DB1
DB0 DA15 DA14
DA1
DA0
tDSDOSDI
SDOC
48
tDSDOSDI
tHSDO
tDSDO
tDSDOSDI
47
tDSDOSDI
DC15 DC14 DC13
DC1
DC0 DB15 DB14
DB1
DB0 DA15 DA14
Figure 45. Chain Mode with BUSY Indicator Serial Interface Timing
Rev. A | Page 22 of 28
DA1
DA0
02973-044
CNV = SDIA
AD7688
APPLICATION HINTS
LAYOUT
The printed circuit board that houses the AD7688 should be
designed so that the analog and digital sections are separated
and confined to certain areas of the board. The pinout of the
AD7688, with all its analog signals on the left side and all its
digital signals on the right side, eases this task.
Avoid running digital lines under the device because these
couple noise onto the die, unless a ground plane under the
AD7688 is used as a shield. Fast switching signals, such as CNV
or clocks, should never run near analog signal paths. Crossover
of digital and analog signals should be avoided
The AD7688 voltage reference input REF has a dynamic input
impedance and should be decoupled with minimal parasitic
inductances. This is done by placing the reference decoupling
ceramic capacitor close to, and ideally right up against, the REF
and GND pins and connecting it with wide, low impedance
traces.
02973-045
At least one ground plane should be used. It could be common
or split between the digital and analog sections. In the latter
case, the planes should be joined underneath the AD7688s.
Figure 46. Example of Layout of the AD7688 (Top Layer)
Finally, the power supplies VDD and VIO of the AD7688
should be decoupled with ceramic capacitors (typically 100 nF)
placed close to the AD7688 and connected using short and wide
traces to provide low impedance paths and reduce the effect of
glitches on the power supply lines.
02973-046
An example of layout following these rules is shown in
Figure 46 and Figure 47.
EVALUATING THE AD7688’S PERFORMANCE
Other recommended layouts for the AD7688 are outlined
in the documentation of the evaluation board for the AD7688
(EVAL-AD7688). The evaluation board package includes
a fully assembled and tested evaluation board, documentation,
and software for controlling the board from a PC via the
EVAL-CONTROL BRD3.
Rev. A | Page 23 of 28
Figure 47. Example of Layout of the AD7688 (Bottom Layer)
AD7688
OUTLINE DIMENSIONS
3.10
3.00
2.90
10
3.10
3.00
2.90
1
5.15
4.90
4.65
6
5
PIN 1
IDENTIFIER
0.50 BSC
0.95
0.85
0.75
15° MAX
1.10 MAX
0.30
0.15
0.70
0.55
0.40
0.23
0.13
6°
0°
091709-A
0.15
0.05
COPLANARITY
0.10
COMPLIANT TO JEDEC STANDARDS MO-187-BA
Figure 48.10-Lead Mini Small Outline Package [MSOP]
(RM-10)
Dimensions shown in millimeters
2.48
2.38
2.23
3.10
3.00 SQ
2.90
0.50 BSC
6
0.50
0.40
0.30
5
TOP VIEW
0.80
0.75
0.70
SEATING
PLANE
1.74
1.64
1.49
EXPOSED
PAD
0.05 MAX
0.02 NOM
0.30
0.25
0.20
1
BOTTOM VIEW
PIN 1
INDICATOR
(R 0.15)
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
SECTION OF THIS DATA SHEET.
0.20 REF
Figure 49. 10-Lead Lead Frame Chip Scale Package [QFN (LFCSP_WD)]
3 mm × 3 mm Body, Very Very Thin, Dual Lead
(CP-10-9)
Dimensions shown in millimeters
Rev. A | Page 24 of 28
121009-A
PIN 1 INDEX
AREA
10
AD7688
ORDERING GUIDE
Model 1, 2, 3
AD7688BRMZ
AD7688BRMZRL7
AD7688BCPZRL
AD7688BCPZRL7
EVAL-AD7688CBZ
EVAL-CONTROL BRD2Z
EVAL-CONTROL BRD3Z
1
2
3
Integral
Nonlinearity
±1.5 LSB max
±1.5 LSB max
±1.5 LSB max
±1.5 LSB max
Temperature Range
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
Transport Media,
Quantity
Tube, 50
Reel, 1,000
Reel, 5,000
Reel, 1,500
Package
Description
10-Lead MSOP
10-Lead MSOP
10-Lead QFN (LFCSP_WD)
10-Lead QFN (LFCSP_WD)
Evaluation Board
Controller Board
Controller Board
Package
Option
RM-10
RM-10
CP-10-9
CP-10-9
Branding
C3K
C3K
#C04
#C04
Z = RoHS Compliant Part, # denotes RoHS compliant product, may be top or bottom marked.
The EVAL-AD7688CB can be used as a standalone evaluation board or in conjunction with the EVAL-CONTROL BRDx for evaluation/demonstration purposes.
The EVAL-CONTROL BRD2 and EVAL-CONTROL BRD3 allow a PC to control and communicate with all Analog Devices evaluation boards ending in the CB designators.
Rev. A | Page 25 of 28
AD7688
NOTES
Rev. A | Page 26 of 28
AD7688
NOTES
Rev. A | Page 27 of 28
AD7688
NOTES
©2007–2011 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D02973-0-2/11(A)
Rev. A | Page 28 of 28