TI1 ADS1254E/2K5G4 24-bit, 20khz, low power analog-to-digital converter Datasheet

ADS1254
ADS
125
4
SBAS213B – JUNE 2001 – REVISED JUNE 2006
24-Bit, 20kHz, Low Power
ANALOG-TO-DIGITAL CONVERTER
FEATURES
DESCRIPTION
● 24 BITS—NO MISSING CODES
● 19 BITS EFFECTIVE RESOLUTION UP TO
20kHz DATA RATE
● LOW NOISE: 1.8ppm
● FOUR DIFFERENTIAL INPUTS
● INL: 15ppm (max)
● EXTERNAL REFERENCE (0.5V to 5V)
● POWER-DOWN MODE
● SYNC MODE
● LOW POWER: 4mW at 20kHz
● SEPARATE DIGITAL INTERFACE SUPPLY 1.8V
to 3.6V
The ADS1254 is a precision, wide dynamic range, deltasigma, Analog-to-Digital (A/D) converter with 24-bit resolution. The delta-sigma architecture is used for wide dynamic
range and to ensure 24 bits of no missing codes performance. An effective resolution of 19 bits (1.8ppm of rms
noise) is achieved for conversion rates up to 20kHz.
The ADS1254 is designed for high-resolution measurement
applications in cardiac diagnostics, smart transmitters, industrial process control, weight scales, chromatography, and
portable instrumentation. The converter includes a flexible,
two-wire synchronous serial interface for low-cost isolation.
The ADS1254 is a multi-channel converter and is offered in
an SSOP-20 package.
APPLICATIONS
●
●
●
●
●
●
CARDIAC DIAGNOSTICS
DIRECT THERMOCOUPLE INTERFACES
BLOOD ANALYSIS
INFRARED PYROMETERS
LIQUID/GAS CHROMATOGRAPHY
PRECISION PROCESS CONTROL
ADS1254
VREF
CH1+
CH1–
CLK
CH2+
CH2–
Mux
CH3+
4th-Order
∆Σ
Modulator
Digital
Filter
Serial
Interface
CH3–
SCLK
DOUT/DRDY
AVDD
CH4+
AGND
CH4–
Control
DVDD
DGND
CHSEL0 CHSEL1
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
Copyright © 2001-2006, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of Texas Instruments
standard warranty. Production processing does not necessarily include
testing of all parameters.
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ELECTROSTATIC
DISCHARGE SENSITIVITY
ABSOLUTE MAXIMUM RATINGS(1)
Analog Input: Current (Momentary) .............................................. ±100mA
(Continuous) ............................................... ±10mA
Voltage ................................... GND – 0.3V to VDD + 0.3V
AVDD to AGND ....................................................................... –0.3V to 6V
DVDD to AVDD .......................................................................... –6V to +6V
DVDD to DGND ....................................................................... –0.3V to 6V
VREF Voltage to AGND ............................................. –0.3V to VDD + 0.3V
Digital Input Voltage to DGND ................................. –0.3V to VDD + 0.3V
Digital Output Voltage to DGND .............................. –0.3V to VDD + 0.3V
Lead Temperature (soldering, 10s) .............................................. +300°C
Power Dissipation (any package) ................................................. 500mW
NOTE: (1) Stresses above these ratings may cause permanent damage.
Exposure to absolute maximum conditions for extended periods may degrade
device reliability.
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with
appropriate precautions. Failure to observe proper handling
and installation procedures can cause damage.
ESD damage can range from subtle performance degradation
to complete device failure. Precision integrated circuits may
be more susceptible to damage because very small parametric
changes could cause the device not to meet its published
specifications.
PACKAGE/ORDERING INFORMATION
For the most current package and ordering information, see
the Package Option Addendum at the end of this document,
or see the TI website at www.ti.com.
PIN CONFIGURATION
PIN DESCRIPTIONS
Top View
SSOP-20
NAME
PIN DESCRIPTION
1
CH1+
2
CH1–
3
CH2+
4
CH2–
5
CH3+
Analog Input: Positive Input of the Differential
Analog Input
Analog Input: Negative Input of the Differential
Analog Input
Analog Input: Positive Input of the Differential
Analog Input
Analog Input: Negative Input of the Differential
Analog Input
Analog Input: Positive Input of the Differential
Analog Input
Analog Input: Negative Input of the Differential
Analog Input
Input: Analog Power Supply Voltage, +5V
Digital Input: Device System Clock. The system
clock is in the form of a CMOS-compatible
clock. This is a Schmitt-Trigger input
Input: Digital Power Supply Voltage
No Connection
No Connection
Input: Digital Ground
Digital Output: Serial Data Output/Data Ready.
This output indicates that a new output word is
available from the ADS1254 data output register. The serial data is clocked out of the serial
data output shift register using SCLK.
Digital Input: Serial Clock. The serial clock is in
the form of a CMOS-compatible clock. The
serial clock operates independently from the
system clock; therefore, it is possible to run
SCLK at a higher frequency than CLK. The
normal state of SCLK is LOW. Holding SCLK
HIGH will either initiate a modulator reset for
synchronizing multiple converters or enter powerdown mode. This is a Schmitt-Trigger input.
Digital Input: Used to select analog input channel. This is a Schmitt-Trigger Input
Digital Input: Used to select analog input channel. This is a Schmitt-Trigger Input
Input: Analog Ground
Analog Input: Reference Voltage Input
Analog Input: Negative Input of the Differential
Analog Input
Analog Input: Positive Input of the Differential
Analog Input
CH1+
1
20
CH4+
6
CH3–
CH1–
2
19
CH4–
7
8
AVDD
CLK
CH2+
3
18 VREF
9
10
11
12
13
DVDD
NC
NC
DGND
DOUT/DRDY
14
SCLK
15
CHSEL1
16
CHSEL0
17
18
19
AGND
VREF
CH4–
20
CH4+
CH2–
4
CH3+
5
CH3–
17 AGND
16
CHSEL0
6
15
CHSEL1
AVDD
7
14 SCLK
CLK
8
13 DOUT/DRDY
DVDD 9
NC
2
PIN
10
ADS1254E
12 DGND
11 NC
ADS1254
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SBAS213B
ELECTRICAL CHARACTERISTICS
All specifications at TMIN to TMAX, AVDD = +5V, DVDD = +1.8V. CLK = 8MHz, and VREF = 4.096, unless otherwise specified.
ADS1254E
PARAMETER
ANALOG INPUT
Input Voltage Range
Input Impedance
Input Capacitance
Input Leakage
DYNAMIC CHARACTERISTICS
Data Rate
Bandwidth
Serial Clock (SCLK)
System Clock Input (CLK)
ACCURACY
Integral Non-Linearity(1)
THD
Noise
Resolution
No Missing Codes
Common-Mode Rejection
Gain Error
Offset Error
Gain Sensitivity to VREF
Power-Supply Rejection Ratio
CONDITIONS
MIN
TYP
AGND
CLK = 3,840Hz
CLK = 1MHz
CLK = 8MHz
At +25°C
At TMIN to TMAX
Quiescent Current
±VREF
V
MΩ
MΩ
kΩ
pF
pA
nA
50
1
20.8
–3dB
4.24
8
8
±0.0002
105
1.8
24
24
102
0.1
±30
1:1
88
1kHz Input; 0.1dB below FS
60Hz, AC
90
70
±0.0015
2.7
1
±100
0.5
kHz
kHz
MHz
MHz
% of FSR
dB
ppm of FSR, rms
Bits
Bits
dB
% of FSR
ppm of FSR
dB
0.07
0.4
VOLTAGE REFERENCE
VREF
Load Current
POWER-SUPPLY REQUIREMENTS
Power Supply Voltage
UNITS
260
1
125
6
5
PERFORMANCE OVER TEMPERATURE
Offset Drift
Gain Drift
DIGITAL INPUT/OUTPUT
Logic Family
Logic Level: VIH
VIL
VOH
VOL
Input (SCLK, CLK, CHSEL0, CHSEL1) Hysteresis
Data Format
MAX
ppm/°C
ppm/°C
4.096
32
VDD
V
µA
DVDD + 0.3
0.35 • DVDD
V
V
V
V
V
CMOS
IOH = –500µA
IOL = 500µA
0.65 • DVDD
–0.3
DVDD –0.4
0.4
0.6
Offset Binary Two’s Complement
DVDD
AVDD
AVDD = +5V
DVDD = +1.8V
1.8
4.75
Operating Power
Power-Down Current
TEMPERATURE RANGE
Operating
Storage
–40
–60
5
0.8
0.2
4.3
0.4
3.6
5.25
1.15
0.4
6.5
1
VDC
VDC
mA
mA
mW
µA
+85
+150
°C
°C
NOTE: (1) Applies to full-differential signals.
ADS1254
SBAS213B
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3
TYPICAL CHARACTERISTICS
At TA = +25°C, AVDD = +5V, DVDD = +1.8V, CLK = 8MHz, and VREF = 4.096, unless otherwise specified.
EFFECTIVE RESOLUTION vs DATA OUTPUT RATE
20.0
1.9
19.8
1.8
19.6
Effective Resolution (Bits)
RMS Noise (ppm of FS)
RMS NOISE vs DATA OUTPUT RATE
2.0
1.7
1.6
1.5
1.4
1.3
1.2
1.1
19.4
19.2
19.0
18.8
18.6
18.4
18.2
1.0
100
1k
10k
18.0
100k
100
1k
Data Ouput Rate (Hz)
20.0
1.8
19.8
1.6
19.6
Effective Resolution (Bits)
RMS Noise (ppm of FS)
2.0
1.4
1.2
1.0
0.8
0.6
0.4
19.4
19.2
19.0
18.8
18.6
18.4
18.2
0.2
18.0
0.0
–40
–20
0
20
40
60
80
–40
100
–20
0
20
40
60
80
100
Temperature (°C)
Temperature (°C)
RMS NOISE vs VREF VOLTAGE
RMS NOISE vs VREF VOLTAGE
18
14
16
12
RMS Noise (ppm of FS)
14
RMS Noise (µV)
100k
EFFECTIVE RESOLUTION vs TEMPERATURE
RMS NOISE vs TEMPERATURE
12
10
8
6
4
10
8
6
4
2
2
0
0
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
VREF Voltage (V)
VREF Voltage (V)
4
10k
Data Ouput Rate (Hz)
ADS1254
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SBAS213B
TYPICAL CHARACTERISTICS (Cont.)
At TA = +25°C, AVDD = +5V, DVDD = +1.8V, CLK = 8MHz, and VREF = 4.096, unless otherwise specified.
INTEGRAL NONLINEARITY vs TEMPERATURE
RMS NOISE vs INPUT VOLTAGE
2.5
2.0
RMS Noise (ppm of FS)
2.0
INL (ppm of FS)
1.5
1.0
0.5
1.5
1.0
0.5
0
0
–5
–4
–3
–2
–1
0
1
2
3
4
–40
5
–20
0
20
40
60
80
100
80
100
7
8
Temperature (°C)
Input Voltage (V)
OFFSET vs TEMPERATURE
INTEGRAL NONLINEARITY vs DATA OUTPUT RATE
20
6
18
DC Offset (ppm of FS)
INL (ppm of FS)
5
4
3
2
1
16
14
12
10
8
6
4
2
0
0
100
1k
10k
–40
100k
–20
0
20
40
60
Temperature (°C)
Data Output Rate (Hz)
GAIN ERROR vs TEMPERATURE
PSR vs CLK FREQUENCY
600
–0
–10
–20
–30
560
PSR (dB)
Gain Error (ppm of FS)
580
540
520
–40
–50
–60
–70
500
–80
480
–100
–90
–60
–40
–20
0
20
40
60
80
100
1
Temperature (°C)
3
4
5
6
Clock Frequency (MHz)
ADS1254
SBAS213B
2
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5
TYPICAL CHARACTERISTICS (Cont.)
At TA = +25°C, AVDD = +5V, DVDD = +1.8V, CLK = 8MHz, and VREF = 4.096, unless otherwise specified.
CMR vs COMMON-MODE FREQUENCY
CMR AT 60Hz vs CLK FREQUENCY
–70
–50
–75
–80
CMR (dB)
CMR at 60Hz (dB)
–60
–70
–80
–85
–90
–90
–95
–100
–100
–110
–105
0
1
2
3
4
5
6
7
8
10
100
0.8
4.0
0.7
3.5
0.6
AVDD (5V)
DVDD (1.8V)
0.4
0.3
0.2
0.1
3.0
Analog (5V)
Digital (3.3V)
Digital (1.8V)
2.5
2.0
1.5
1.0
0
–20
0
20
40
60
80
100
0
1
2
Temperature (°C)
3
4
5
6
7
8
Clock Frequency (MHz)
TYPICAL FFT
(1kHz input at 0.1dB less than full-scale)
VREF CURRENT vs CLK FREQUENCY
35
0
30
–20
Relative Magnitude (dB)
VREF Current (µA)
100k
0.5
0
–40
25
20
15
10
5
–40
–60
–80
–100
–120
–140
–160
0
0
1
2
3
4
5
6
7
0
8
1
2
3
4
5
6
7
8
9
10
11
Input Signal Frequency (kHz)
Clock Frequency (MHz)
6
10k
POWER DISSIPATION vs CLK FREQUENCY
4.5
Power Dissipation (mW)
Current (mA)
CURRENT vs TEMPERATURE
0.9
0.5
1k
Common-Mode Signal Frequency (Hz)
Clock Frequency (MHz)
ADS1254
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SBAS213B
THEORY OF OPERATION
The ADS1254 is a precision, high-dynamic range, 24-bit,
delta-sigma, A/D converter capable of achieving very
high-resolution digital results at high data rates.
The analog-input signal is sampled at a rate determined by the
frequency of the system clock (CLK). The sampled analog
input is modulated by the delta-sigma A/D modulator, which
is followed by a digital filter. A Sinc5 digital low-pass filter
processes the output of the delta-sigma modulator and writes
the result into the data-output register. The DOUT/DRDY pin
is pulled LOW, indicating that new data is available to be read
by the external microcontroller/microprocessor. As shown in
the block diagram, the main functional blocks of the ADS1254
are the fourth-order delta-sigma modulator, a digital filter,
control logic, and a serial interface. Each of these functional
blocks is described below.
ANALOG INPUT
The ADS1254 contains a fully differential analog input. In order
to provide low system noise, common-mode rejection of 102dB,
and excellent power-supply rejection, the design topology is
based on a fully differential switched-capacitor architecture. The
bipolar input voltage range is from –4.096V to +4.096V, when
the reference input voltage equals +4.096V. The bipolar range is
with respect to –VIN, and not with respect to GND.
Figure 1 shows the basic input structure of the ADS1254.
The impedance is directly related to the sampling frequency
of the input capacitor that is set by the CLK rate. Higher
CLK rates result in lower impedance, and lower CLK rates
result in higher impedance.
RSW
(1300Ω typical)
Internal
Circuitry
AIN
Modulator Frequency
= fMOD
CINT
(6pF typical)
VCM
FIGURE 1. Analog-Input Structure.
20.8kHz with a –3dB frequency of 4.24kHz. The –3dB
frequency scales with the system clock frequency.
To ensure the best linearity of the ADS1254, a fully differential signal is recommended.
INPUT MULTIPLEXER
The CHSEL1 and CHSEL0 pins are used to select the analog
input channel, as shown in Table I. The recommended
method for changing channels is to change them after the
conversion from the previous channel has been completed
and read. When a channel is changed, internal logic senses
the change on the falling edge of CLK and resets the
conversion process. The conversion data from the new
channel is valid on the first DRDY after the channel change.
When multiplexing inputs, it is possible to achieve sample
rates close to 4kHz. This is due to the fact that it requires five
internal conversion cycles for the data to fully settle; the data
also must be read before the channel is changed. The DRDY
signal indicates a valid result after the five cycles have
occurred.
BIPOLAR INPUT
CHSEL1
CHSEL0
CHANNEL
0
0
1
1
0
1
0
1
CH1
CH2
CH3
CH4
TABLE I. Channel Selection.
Each of the differential inputs of the ADS1254 must stay
between AGND and AVDD. With a reference voltage at less
than half of AVDD, one input can be tied to the reference
voltage, and the other input can range from AGND to
2 • VREF. By using a three op amp circuit featuring a single
amplifier and four external resistors, the ADS1254 can be
configured to accept bipolar inputs referenced to ground.
The conventional ±2.5V, ±5V, and ±10V input ranges can
be interfaced to the ADS1254 using the resistor values
shown in Figure 2.
The input impedance of the analog input changes with the
ADS1254 system clock frequency (CLK). The relationship is:
R1
10kΩ
AIN Impedance (Ω) = (8MHz/CLK) • 125,000
With regard to the analog-input signal, the overall analog
performance of the device is affected by three items: first, the
input impedance can affect accuracy. If the source impedance
of the input signal is significant, or if there is passive filtering
prior to the ADS1254, a significant portion of the signal can be
lost across this external impedance. The magnitude of the
effect is dependent on the desired system performance.
Second, the current into or out of the analog inputs must be
limited. Under no conditions should the current into or out
of the analog inputs exceed 10mA.
Third, to prevent aliasing of the input signal, the analog-input
signal must be band limited. The bandwidth of the A/D
converter is a function of the system clock frequency. With a
system clock frequency of 8MHz, the data-output rate is
–IN
ADS1254
VREF
R2
OPA4350
OPA4350
BIPOLAR INPUT
±10V
±5V
±2.5V
R1
R2
2.5kΩ
5kΩ
10kΩ
5kΩ
10kΩ
20kΩ
REF
2.5V
FIGURE 2. Level Shift Circuit for Bipolar Input Ranges.
ADS1254
SBAS213B
+IN
OPA4350
20kΩ
Bipolar
Input
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7
DELTA-SIGMA MODULATOR
REFERENCE INPUT
The ADS1254 operates from a nominal system clock frequency of 8MHz. The modulator frequency is fixed in
relation to the system clock frequency. The system clock
frequency is divided by 6 to derive the modulator frequency.
Therefore, with a system clock frequency of 8MHz, the
modulator frequency is 1.333MHz. Furthermore, the
oversampling ratio of the modulator is fixed in relation to the
modulator frequency. The oversampling ratio of the modulator is 64, and with the modulator frequency running at
1.333MHz, the data rate is 20.8kHz. Using a slower system
clock frequency will result in a lower data output rate, as
shown in Table II.
Reference input takes an average current of 32µA with a
8MHz system clock. This current will be proportional to the
system clock. A buffered reference is recommended for the
ADS1254. The recommended reference circuit is shown in
Figure 3.
Reference voltages higher than 4.096V will increase the
full-scale range, while the absolute internal circuit noise of
the converter remains the same. This will decrease the noise
in terms of ppm of full scale, which increases the effective
resolution (see the typical characteristic curve, RMS Noise
vs VREF Voltage).
CLK (MHz)
DATA OUTPUT RATE (Hz)
8(1)
7.372800(1)
6.144000(1)
6.000000(1)
4.915200(1)
3.686400(1)
3.072000(1)
2.457600(1)
1.843200(1)
0.921600
0.460800
0.384000
0.192000
0.038400
0.023040
0.019200
0.011520
0.009600
0.007680
0.006400
0.005760
0.004800
0.003840
20,833
19,200
16,000
15,625
12,800
9,600
8,000
6,400
4,800
2,400
1,200
1,000
500
100
60
50
30
25
20
16.67
15
12.50
10
DIGITAL FILTER
The digital filter of the ADS1254, referred to as a sinc5 filter,
computes the digital result based on the most recent outputs
from the delta-sigma modulator. At the most basic level, the
digital filter can be thought of as simply averaging the
modulator results in a weighted form and presenting this
average as the digital output. The digital output rate, or data
rate, scales directly with the system CLK frequency. This
allows the data output rate to be changed over a very wide
range (five orders of magnitude) by changing the system
CLK frequency. However, it is important to note that the
–3dB point of the filter is 0.2035 times the data output rate,
so the data output rate should allow for sufficient margin to
prevent attenuation of the signal of interest.
Since the conversion result is essentially an average, the
data-output rate determines the location of the resulting
notches in the digital filter (see Figure 4). Note that the first
notch is located at the data-output rate frequency, and
subsequent notches are located at integer multiples of the
data-output rate to allow for rejection of not only the
fundamental frequency, but also harmonic frequencies. In
this manner, the data-output rate can be used to set specific
notch frequencies in the digital filter response.
For example, if the rejection of power-line frequencies is
desired, then the data-output rate can simply be set to the
power-line frequency. For 50Hz rejection, the system CLK
NOTE: (1) Standard Clock Oscillator.
TABLE II. CLK Rate versus Data Output Rate.
+5V
+5V
0.10µF
7
4.99kΩ
2
To VREF
Pin 18 of
the ADS1254
6
10kΩ
3
1
OPA350
+
+
LM404-4.1
10µF
0.10µF
10µF
0.1µF
4
FIGURE 3. Recommended External Voltage Reference Circuit for Best Low-Noise Operation with the ADS1254.
8
ADS1254
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SBAS213B
DIGITAL FILTER RESPONSE
0
–20
–20
–40
–40
–60
–60
–80
–80
Gain (dB)
Gain (dB)
NORMALIZED DIGITAL FILTER RESPONSE
0
–100
–120
–100
–120
–140
–140
–160
–160
–180
–180
–200
–200
0
1
2
3
4
5
6
7
8
9
0
10
50
100
FIGURE 4. Normalized Digital Filter Response.
250
300
DIGITAL FILTER RESPONSE
0
0
–20
–20
–40
–40
–60
–60
–80
Gain (dB)
Gain (dB)
200
FIGURE 5. Digital Filter Response (50Hz).
DIGITAL FILTER RESPONSE
–100
–120
–80
–100
–120
–140
–140
–160
–160
–180
–180
–200
–200
0
50
100
150
200
250
0
300
10
20
30
Frequency (Hz)
40
50
60
70
80
90
100
53
54
55
Frequency (Hz)
FIGURE 6. Digital Filter Response (60Hz).
FIGURE 7. Digital Filter Response (10Hz).
DIGITAL FILTER RESPONSE
DIGITAL FILTER RESPONSE
0
0
–20
–20
–40
–40
–60
–60
–80
Gain (dB)
Gain (dB)
150
Frequency (Hz)
Frequency (Hz)
–100
–120
–80
–100
–120
–140
–140
–160
–160
–180
–180
–200
–200
45
46
47
48
49
50
51
52
53
54
55
45
Frequency (Hz)
47
48
49
50
51
52
Frequency (Hz)
FIGURE 8. Expanded Digital Filter Response (50Hz with a
50Hz Data Output Rate).
FIGURE 9. Expanded Digital Filter Response (50Hz with a
10Hz Data Output Rate).
ADS1254
SBAS213B
46
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9
DIGITAL FILTER RESPONSE
0
–20
–20
–40
–40
–60
–60
–80
–80
Gain (dB)
Gain (dB)
DIGITAL FILTER RESPONSE
0
–100
–120
–100
–120
–140
–140
–160
–160
–180
–180
–200
–200
55
56
57
58
59
60
61
62
63
64
55
65
56
57
58
59
60
61
62
63
64
65
Frequency (Hz)
Frequency (Hz)
FIGURE 10. Expanded Digital Filter Response (60Hz with
a 60Hz Data Output Rate).
FIGURE 11. Expanded Digital Filter Response (60Hz with
a 10Hz Data Output Rate).
frequency should be 19.200kHz, this will set the data-output
rate to 50Hz (see Table II and Figure 5). For 60Hz rejection,
the system CLK frequency should be 23.040kHz; this will set
the data-output rate to 60Hz (see Table II and Figure 6).
If both 50Hz and 60Hz rejection are required, then the system
CLK should be 3.840kHz; this will set the data-output rate
to 10Hz and reject both 50Hz and 60Hz (See Table II and
Figure 7).
There is an additional benefit in using a lower data-output
rate. It provides better rejection of signals in the frequency
band of interest. For example, with a 50Hz data-output rate,
a significant signal at 75Hz may alias back into the passband
at 25Hz. This is due to the fact that rejection at 75Hz may only
be 66dB in the stopband—frequencies higher than the firstnotch frequency (see Figure 5). However, setting the dataoutput rate to 10Hz will provide 135dB rejection at 75Hz (see
Figure 7). A similar benefit is gained at frequencies near the
data-output rate (see Figures 8, 9, 10, and 11). For example,
with a 50Hz data-output rate, rejection at 55Hz may only be
105dB (see Figure 8). However, with a 10Hz data-output rate,
rejection at 55Hz will be 122dB (see Figure 9). If a slower
data-output rate does not meet the system requirements, then
the analog front end can be designed to provide the needed
attenuation to prevent aliasing. Additionally, the data-output
rate may be increased and additional digital filtering may be
done in the processor or controller.
The digital filter is described by the following transfer function:
10
5
 π • f • 64 
sin

 fMOD 
H( f ) =
 π•f 
64 • sin

 fMOD 
or
 1 – z –64
H( z ) = 
 64 • 1 – z –1

(
)




5
The digital filter requires five conversions to fully settle. The
modulator has an oversampling ratio of 64; therefore, it
requires 5 • 64, or 320 modulator results, or clocks, to fully
settle. Since the modulator clock is derived from the system
clock (CLK) (modulator clock = CLK ÷ 6), the number of
system clocks required for the digital filter to fully settle is
5 • 64 • 6, or 1920 CLKs. This means that any significant
step change at the analog input requires five full conversions
to settle. However, if the step change at the analog input
occurs asynchronously to the DOUT/DRDY pulse, six conversions are required to ensure full settling.
ADS1254
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SBAS213B
CONTROL LOGIC
defined by t4. If more than 24 SCLKs were provided during
DOUT mode, the DOUT/DRDY line would stay LOW until
the time defined by t4.
The internal data pointer for shifting data out on
DOUT/DRDY is reset on the falling edge of the time defined
by t1 and t4. This ensures that the first bit of data shifted out
of the ADS1254 after DRDY mode is always the MSB of
new data.
The control logic is used for communications and control of
the ADS1254.
Power-Up Sequence
Prior to power-up, all digital and analog-input pins must be
LOW. During power-up, these signal inputs should never
exceed +AVDD or +DVDD.
Once the ADS1254 powers up, the DOUT/DRDY line will
pulse LOW on the first conversion for which the data is valid
from the analog input signal.
SYNCHRONIZING MULTIPLE CONVERTERS
The normal state of SCLK is LOW; however, by holding
SCLK HIGH, multiple ADS1254s can be synchronized. This
is accomplished by holding SCLK HIGH for at least four, but
less than twenty, consecutive DOUT/DRDY cycles (see Figure 14). After the ADS1254 circuitry detects that SCLK has
been held HIGH for four consecutive DOUT/DRDY cycles,
the DOUT/DRDY pin will pulse LOW for 3 CLK cycles and
then be held HIGH, and the modulator will be held in a reset
state. The modulator will be released from reset and synchronization will occur on the falling edge of SCLK. With
multiple converters, the falling edge transition of SCLK must
occur simultaneously on all devices. It is important to note
that prior to synchronization, the DOUT/DRDY pulse of
multiple ADS1254s in the system could have a difference in
timing up to one DRDY period. Therefore, to ensure synchronization, the SCLK should be held HIGH for at least five
DRDY cycles. The first DOUT/DRDY pulse after the falling
edge of SCLK will occur at t14. The first DOUT/DRDY pulse
indicates valid data.
DOUT/DRDY
The DOUT/DRDYoutput signal alternates between two
modes of operation. The first mode of operation is the Data
Ready mode (DRDY) to indicate that new data has been
loaded into the data-output register and is ready to be read.
The second mode of operation is the Data Output (DOUT)
mode and is used to serially shift data out of the Data Output
Register (DOR). The time domain partitioning of the DRDY
and DOUT function as shown in Figure 12.
See Figure 13 for the basic timing of DOUT/DRDY. During
the time defined by t2, t3, and t4, the DOUT/DRDY pin
functions in DRDY mode. The state of the DOUT/DRDY
pin would be HIGH prior to the internal transfer of new data
to the DOR. The result of the A/D conversion would be
written to the DOR from MSB to LSB in the time defined by
t1 (see Figures 12 and 13). The DOUT/DRDY line would
then pulse LOW for the time defined by t2, and then drive the
line HIGH for the time defined by t3 to indicate that new data
was available to be read. At this point, the function of the
DOUT/DRDY pin would change to DOUT mode. Data
would be shifted out on the pin after t7. If the MSB is high
(because of a negative result) the DOUT/DRDY signal will
stay HIGH after the end of time t3. The device communicating with the ADS1254 can provide SCLKs to the ADS1254
after the time defined by t6. The normal mode of reading
data from the ADS1254 would be for the device reading the
ADS1254 to latch the data on the rising edge of SCLK (since
data is shifted out of the ADS1254 on the falling edge of
SCLK). In order to retrieve valid data, the entire DOR must
be read before the DOUT/DRDY pin reverts back to DRDY
mode.
If SCLKs were not provided to the ADS1254 during the
DOUT mode, the MSB of the DOR would be present on the
DOUT/DRDY line until the beginning of the time defined
by t4. If an incomplete read of the ADS1254 took place
while in DOUT mode (that is, fewer than 24 SCLKs were
provided), the state of the last bit read would be present on
the DOUT/DRDY line until the beginning of the time
DOUT Mode
DRDY Mode
DOUT Mode
t2
t4
DOUT/DRDY
POWER-DOWN MODE
The normal state of SCLK is LOW, however, by holding
SCLK HIGH, the ADS1254 will enter power-down mode.
This is accomplished by holding SCLK HIGH for at least
twenty consecutive DOUT/DRDY periods (see Figure 15).
After the ADS1254 circuitry detects that SCLK has been
held HIGH for four consecutive DOUT/DRDY cycles, the
DOUT/DRDY pin will pulse LOW for 3 CLK cycles and
then be held HIGH, and the modulator will be held in a
reset state. If SCLK is held HIGH for an additional sixteen
DOUT/DRDY periods, the ADS1254 will enter
power-down mode. The part will be released from powerdown mode on the falling edge of SCLK. It is important to
note that the DOUT/DRDY pin will be held HIGH after four
DOUT/DRDY cycles, but power-down mode will not be
entered for an additional sixteen DOUT/DRDY periods. The
first DOUT/DRDY pulse after the falling edge of SCLK
will occur at t16 and will indicate valid data. Subsequent
DOUT/DRDY pulses will occur normally.
DATA
DRDY Mode
t3
DATA
DATA
t1
FIGURE 12. DOUT/DRDY Partitioning.
ADS1254
SBAS213B
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11
SERIAL INTERFACE
The ADS1254 includes a simple serial interface that can be
connected to microcontrollers and digital signal processors
in a variety of ways. Communications with the ADS1254
can commence on the first detection of the DOUT/DRDY
pulse after power up.
It is important to note that the data from the ADS1254 is a
24-bit result transmitted MSB-first in Offset Two’s Complement format, as shown in Table IV.
The data must be clocked out before the ADS1254 enters
DRDY mode to ensure reception of valid data, as described
in the DOUT/DRDY section of this data sheet.
ISOLATION
The serial interface of the ADS1254 provides for simple
isolation methods. The CLK signal can be local to the
ADS1254, which then only requires two signals (SCLK and
DOUT/DRDY) to be used for isolated data acquisition. The
channel select signals (CHSEL0, CHSEL1) will also need to
be isolated unless a counter is used to auto multiplex the
channels.
DIFFERENTIAL VOLTAGE INPUT
DIGITAL OUTPUT (HEX)
+Full Scale
Zero
–Full Scale
7FFFFFH
000000H
800000H
TABLE IV. ADS1254 Data Format (Offset Two's Complement).
SYMBOL
tOSC
tDRDY
DRDY Mode
DOUT Mode
t1
t2
t3
t4
t5
t6
t7
t8
t9
t10
t11
t12
t13
t14
t15
t16
t17
t18
DESCRIPTION
MIN
CLK Period
Conversion Cycle
DRDY Mode
DOUT Mode
DOR Write Time
DOUT/DRDY LOW Time
DOUT/DRDY HIGH Time (Prior to Data Out)
DOUT/DRDY HIGH Time (Prior to Data Ready)
Rising Edge of CLK to Falling Edge of DOUT/DRDY
End of DRDY Mode to Rising Edge of First SCLK
End of DRDY Mode to Data Valid (Propagation Delay)
Falling Edge of SCLK to Data Valid (Hold Time)
Falling Edge of SCLK to Next Data Out Valid (Propagation Delay)
SCLK Setup Time for Synchronization or Power Down
DOUT/DRDY Pulse for Synchronization or Power Down
Rising Edge of SCLK Until Start of Synchronization
Synchronization Time
Falling Edge of CLK (After SCLK Goes Low) Until Start of DRDY Mode
Rising Edge of SCLK Until Start of Power Down
Falling Edge of CLK (After SCLK Goes Low) Until Start of DRDY Mode
Falling Edge of Last DOUT/DRDY to Start of Power Down
DOUT/DRDY High Time After Mux Change.
125
TYP
MAX
384 • tOSC
36 • tOSC
348 • tOSC
6 • tOSC
6 • tOSC
6 • tOSC
24 • tOSC
60
30
60
5
60
30
3 • tOSC
1537 • CLK
0.5 • CLK
7679 • CLK
6143.5 • CLK
2042.5 • CLK
7681 • CLK
2318.5 • tOSC
6144.5 • tOSC
2043.5 • tosc
UNITS
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
NOTE: 30pF Load.
TABLE III. Digital Timing.
t18
DOUT/DRDY
DATA
DATA
CHSEL0, CHSEL1
MUX CHANGE
FIGURE 13. Multiplexer Operation.
12
ADS1254
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SBAS213B
ADS1254
SBAS213B
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13
t4
t1
t10
t2
t3
tDRDY
t10
t2
t3
FIGURE 16. Power-Down Mode.
DOUT/DRDY
SCLK
CLK
tDRDY
FIGURE 15. Synchronization Mode.
DOUT/DRDY
SCLK
CLK
FIGURE 14. DOUT/DRDY Timing.
DOUT/DRDY
SCLK
CLK
t2
DOUT
Mode
DATA
DOUT
Mode
DATA
t4
t4
DRDY Mode
t5
4 tDRDY
4 tDRDY
t12
t3
t15
t11
MSB
t7
t6
DATA
DATA
t8
t9
tDRDY
t11
t11
t17
t13
t16
Power Down Occurs Here
t14
Synchronization Begins Here
Synchronization Mode Starts Here
DOUT Mode
LSB
t2
t2
t3
t3
DATA
DATA
tDRDY
DOUT
Mode
tDRDY
DOUT
Mode
t4
t4
LAYOUT
POWER SUPPLY
The power supply should be well regulated and low noise.
For designs requiring very high resolution from the ADS1254,
power-supply rejection will be a concern. Avoid running
digital lines under the device as they may couple noise onto
the die. High-frequency noise can capacitively couple into
the analog portion of the device and will alias back into the
passband of the digital filter, affecting the conversion result.
This clock noise will cause an offset error.
GROUNDING
The analog and digital sections of the system design should
be carefully and cleanly partitioned. Each section should
have its own ground plane with no overlap between them.
AGND should be connected to the analog ground plane, as
well as all other analog grounds. Do not join the analog and
digital ground planes on the board, but instead connect the
two with a moderate signal trace. For multiple converters,
connect the two ground planes at one location as central to
all of the converters as possible. In some cases, experimentation may be required to find the best point to connect the
two planes together. The printed circuit board can be designed to provide different analog/digital ground connections via short jumpers. The initial prototype can be used to
establish which connection works best.
DECOUPLING
Good decoupling practices should be used for the ADS1254
and for all components in the design. All decoupling capacitors, and specifically the 0.1µF ceramic capacitors, should
be placed as close as possible to the pin being decoupled. A
1µF to 10µF capacitor, in parallel with a 0.1µF ceramic
capacitor, should be used to decouple Supply to ground.
SYSTEM CONSIDERATIONS
The recommendations for power supplies and grounding
will change depending on the requirements and specific
design of the overall system. Achieving 24 bits of noise
performance is a great deal more difficult than achieving 12
bits of noise performance. In general, a system can be
broken up into four different stages:
•
•
•
•
Analog Processing
Analog Portion of the ADS1254
Digital Portion of the ADS1254
Digital Processing
High resolution will be very difficult to achieve for this
design. The approach would be to break the system into as
many different parts as possible. For example, each ADS1254
may have its own “analog” processing front end.
DEFINITION OF TERMS
An attempt has been made to be consistent with the terminology used in this data sheet. In that regard, the definition
of each term is given as follows:
Analog-Input Differential Voltage—for an analog signal
that is fully differential, the voltage range can be compared
to that of an instrumentation amplifier. For example, if both
analog inputs of the ADS1254 are at 2.048V, the differential voltage is 0V. If one analog input is at 0V and the other
analog input is at 4.096V, then the differential voltage
magnitude is 4.096V. This is the case regardless of which
input is at 0V and which is at 4.096V. The digital-output
result, however, is quite different. The analog-input differential voltage is given by the following equation:
+VIN – (–VIN)
A positive digital output is produced whenever the
analog-input differential voltage is positive, while a negative digital output is produced whenever the differential is
negative. For example, a positive full-scale output is produced when the converter is configured with a 4.096V
reference, and the analog-input differential is 4.096V. The
negative full-scale output is produced when the differential
voltage is –4.096V. In each case, the actual input voltages
must remain within the –0.3V to +AVDD range.
Actual Analog-Input Voltage—the voltage at any one
analog input relative to AGND.
Full-Scale Range (FSR)—as with most A/D Converters,
the full-scale range of the ADS1254 is defined as the “input”
that produces the positive full-scale digital output minus the
“input” that produces the negative full-scale digital output.
For example, when the converter is configured with a 4.096V
reference, the differential full-scale range is:
[4.096V (positive full scale) – (–4.096V) (negative full scale)] =
8.192V
For the simplest system consisting of minimal analog signal
processing (basic filtering and gain), a microcontroller, and
one clock source, one can achieve high resolution by powering all components by a common power supply. In addition, all components could share a common ground plane.
Thus, there would be no distinctions between “analog”
power and ground, and “digital” power and ground. The
layout should still include a power plane, a ground plane,
and careful decoupling. In a more extreme case, the design
14
could include:
• Multiple ADS1254s
• Extensive Analog Signal Processing
• One or More Microcontrollers, Digital Signal Processors,
or Microprocessors
• Many Different Clock Sources
• Interconnections to Various Other Systems
Least Significant Bit (LSB) Weight—this is the theoretical amount of voltage that the differential voltage at the
analog input would have to change in order to observe a
change in the output data of one least significant bit. It is
computed as follows:
LSB Weight =
Full – Scale Range 2 • VREF
= N
2N – 1
2 –1
where N is the number of bits in the digital output.
ADS1254
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SBAS213B
Conversion Cycle—as used here, a conversion cycle refers
to the time period between DOUT/DRDY pulses.
Effective Resolution (ER)—of the ADS1254 in a particular
configuration can be expressed in two different units:
bits rms (referenced to output) and µVrms (referenced to
input). Computed directly from the converter's output data,
each is a statistical calculation based on a given number of
results. Noise occurs randomly; the rms value represents a
statistical measure that is one standard deviation. The ER in
bits can be computed as follows:
2 • VREF 
20 • log
 Vrms noise 
ER in bits rms =
6.02
Noise Reduction—for random noise, the ER can be improved with averaging. The result is the reduction in noise by
the factor √N, where N is the number of averages, as shown
in Table V. This can be used to achieve true 24-bit performance at a lower data rate. To achieve 24 bits of resolution,
more than 24 bits must be accumulated. A 36-bit accumulator
is required to achieve an ER of 24 bits. Table V uses VREF =
4.096V, with the ADS1254 outputting data at 20kHz, a 4096
point average will take 204.8ms. The benefits of averaging
will be degraded if the input signal drifts during that 200ms.
N
(Number
of Averages)
NOISE
REDUCTION
FACTOR
ER
IN
µVrms
ER
IN
BITS rms
1
2
4
8
16
32
64
128
256
512
1024
2048
4096
1
1.414
2
2.82
4
5.66
8
11.3
16
22.6
32
45.25
64
14.6µV
10.3µV
7.3µV
5.16µV
3.65µV
2.58µV
1.83µV
1.29µV
0.91µV
0.65µV
0.46µV
0.32µV
0.23µV
19.1
19.6
20.1
20.6
21.1
21.6
22.1
22.6
23.1
23.6
24.1
24.6
25.1
The 2 • VREF figure in each calculation represents the
full-scale range of the ADS1254. This means that both units
are absolute expressions of resolution—the performance in
different configurations can be directly compared, regardless of the units.
fMOD—frequency of the modulator and the frequency the
input is sampled.
fMOD =
CLK Frequency
6
TABLE V. Averaging.
fDATA—Data output rate.
fDATA =
fMOD CLK Frequency
=
64
384
ADS1254
SBAS213B
www.ti.com
15
Revision History
DATE
REVISION
PAGE
SECTION
6/06
B
11
DOUT/DRDY
DESCRIPTION
Text changes to DOUT/DRDY section.
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
16
ADS1254
www.ti.com
SBAS213B
PACKAGE OPTION ADDENDUM
www.ti.com
11-Apr-2013
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
Lead/Ball Finish
(2)
MSL Peak Temp
Op Temp (°C)
Top-Side Markings
(3)
(4)
ADS1254E
ACTIVE
SSOP
DBQ
20
50
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
ADS1254E
ADS1254E/2K5
ACTIVE
SSOP
DBQ
20
2500
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
ADS1254E
ADS1254E/2K5G4
ACTIVE
SSOP
DBQ
20
2500
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
ADS1254E
ADS1254EG4
ACTIVE
SSOP
DBQ
20
50
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
ADS1254E
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4)
Multiple Top-Side Markings will be inside parentheses. Only one Top-Side Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a
continuation of the previous line and the two combined represent the entire Top-Side Marking for that device.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
Samples
PACKAGE OPTION ADDENDUM
www.ti.com
11-Apr-2013
OTHER QUALIFIED VERSIONS OF ADS1254 :
• Enhanced Product: ADS1254-EP
NOTE: Qualified Version Definitions:
• Enhanced Product - Supports Defense, Aerospace and Medical Applications
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
16-Aug-2012
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
ADS1254E/2K5
Package Package Pins
Type Drawing
SSOP
DBQ
20
SPQ
Reel
Reel
A0
Diameter Width (mm)
(mm) W1 (mm)
2500
330.0
16.4
Pack Materials-Page 1
6.5
B0
(mm)
K0
(mm)
P1
(mm)
9.0
2.1
8.0
W
Pin1
(mm) Quadrant
16.0
Q1
PACKAGE MATERIALS INFORMATION
www.ti.com
16-Aug-2012
*All dimensions are nominal
Device
Package Type
Package Drawing
Pins
SPQ
Length (mm)
Width (mm)
Height (mm)
ADS1254E/2K5
SSOP
DBQ
20
2500
367.0
367.0
38.0
Pack Materials-Page 2
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that may be provided by TI. Buyer represents and agrees that it has all the necessary expertise to create and implement safeguards which
anticipate dangerous consequences of failures, monitor failures and their consequences, lessen the likelihood of failures that might cause
harm and take appropriate remedial actions. Buyer will fully indemnify TI and its representatives against any damages arising out of the use
of any TI components in safety-critical applications.
In some cases, TI components may be promoted specifically to facilitate safety-related applications. With such components, TI’s goal is to
help enable customers to design and create their own end-product solutions that meet applicable functional safety standards and
requirements. Nonetheless, such components are subject to these terms.
No TI components are authorized for use in FDA Class III (or similar life-critical medical equipment) unless authorized officers of the parties
have executed a special agreement specifically governing such use.
Only those TI components which TI has specifically designated as military grade or “enhanced plastic” are designed and intended for use in
military/aerospace applications or environments. Buyer acknowledges and agrees that any military or aerospace use of TI components
which have not been so designated is solely at the Buyer's risk, and that Buyer is solely responsible for compliance with all legal and
regulatory requirements in connection with such use.
TI has specifically designated certain components as meeting ISO/TS16949 requirements, mainly for automotive use. In any case of use of
non-designated products, TI will not be responsible for any failure to meet ISO/TS16949.
Products
Applications
Audio
www.ti.com/audio
Automotive and Transportation
www.ti.com/automotive
Amplifiers
amplifier.ti.com
Communications and Telecom
www.ti.com/communications
Data Converters
dataconverter.ti.com
Computers and Peripherals
www.ti.com/computers
DLP® Products
www.dlp.com
Consumer Electronics
www.ti.com/consumer-apps
DSP
dsp.ti.com
Energy and Lighting
www.ti.com/energy
Clocks and Timers
www.ti.com/clocks
Industrial
www.ti.com/industrial
Interface
interface.ti.com
Medical
www.ti.com/medical
Logic
logic.ti.com
Security
www.ti.com/security
Power Mgmt
power.ti.com
Space, Avionics and Defense
www.ti.com/space-avionics-defense
Microcontrollers
microcontroller.ti.com
Video and Imaging
www.ti.com/video
RFID
www.ti-rfid.com
OMAP Applications Processors
www.ti.com/omap
TI E2E Community
e2e.ti.com
Wireless Connectivity
www.ti.com/wirelessconnectivity
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