Electrical Specifications Subject to Change LT3990 60V, 350mA Step-Down Regulator with 2.5µA Quiescent Current and Integrated Diodes FEATURES DESCRIPTION n The LT®3990 is an adjustable frequency monolithic buck switching regulator that accepts a wide input voltage range up to 60V, and consumes only 2.5μA of quiescent current. A high efficiency switch is included on the die along with the catch diode, boost diode, and the necessary oscillator, control and logic circuitry. Low ripple Burst Mode operation maintains high efficiency at low output currents while keeping the output ripple below 5mV in a typical application. Current mode topology is used for fast transient response and good loop stability. A catch diode current limit provides protection against shorted outputs and overvoltage conditions. An enable pin with accurate threshold is available, producing a low shutdown current of 0.7μA. A power good flag signals when VOUT reaches 90% of the programmed output voltage. The LT3990 is available in small 10-pin MSOP and 3mm × 2mm DFN packages. n n n n n n n n n n n Low Ripple Burst Mode® Operation 2.5μA IQ at 12VIN to 3.3VOUT Output Ripple < 5mVP-P Wide Input Voltage Range: 4.2V to 60V Operating Adjustable Switching Frequency: 200kHz to 2.2MHz Integrated Boost and Catch Diodes 350mA Output Current Accurate 1V Enable Pin Threshold Low Shutdown Current: IQ = 0.7μA Internal Sense Limits Catch Diode Current Power Good Flag Output Voltage: 1.21V to 25V Internal Compensation Small 10-Pin MSOP and (3mm × 2mm) DFN Packages APPLICATIONS n n n Automotive Battery Regulation Power for Portable Products Industrial Supplies L, LT, LTC, LTM, Burst Mode, Linear Technology and the Linear logo are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. TYPICAL APPLICATION 5V Step-Down Converter Efficiency 90 VIN = 12V VIN 6V TO 60V 0.22μF LT3990 OFF ON 22μH EN PG SW RT FB 226k f = 600kHz VOUT 5V 350mA BD 22pF 2.2μF 80 BOOST GND 1M 22μF 316k 3990 TA01a EFFICIENCY (%) VIN 70 60 50 40 30 0.01 0.1 1 10 LOAD CURRENT (mA) 100 3990 TA01b 3990p 1 LT3990 ABSOLUTE MAXIMUM RATINGS (Note 1) VIN, EN Voltage .........................................................60V BOOST Pin Voltage ...................................................75V BOOST Pin Above SW Pin.........................................30V FB, RT Voltage.............................................................6V PG, BD Voltage .........................................................30V Operating Junction Temperature Range (Note 2) LT3990E ............................................. –40°C to 125°C LT3990I .............................................. –40°C to 125°C Storage Temperature Range................... –65°C to 150°C Lead Temperature (Soldering, 10 sec) MS Only ............................................................ 300°C PIN CONFIGURATION TOP VIEW FB 1 10 RT EN 2 9 PG 8 BD GND 4 7 BOOST GND 5 6 SW VIN 3 11 TOP VIEW FB EN VIN GND GND 10 9 8 7 6 1 2 3 4 5 RT PG BD BOOST SW MS PACKAGE 10-LEAD PLASTIC MSOP DDB PACKAGE 10-LEAD (3mm s 2mm) PLASTIC DFN θJA = 100°C/W θJA = 76°C/W EXPOSED PAD (PIN 11) IS GND, MUST BE SOLDERED TO PCB ORDER INFORMATION LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LT3990EDDB#PBF LT3990EDDB#TRPBF LFCZ 10-Lead (3mm × 2mm) Plastic DFN –40°C to 125°C LT3990IDDB#PBF LT3990IDDB#TRPBF LFCZ 10-Lead (3mm × 2mm) Plastic DFN –40°C to 125°C LT3990EMS#PBF LT3990EMS#TRPBF LTFDB 10-Lead Plastic MSOP –40°C to 125°C LT3990IMS#PBF LT3990IMS#TRPBF LTFDB 10-Lead Plastic MSOP –40°C to 125°C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. Consult LTC Marketing for information on non-standard lead based finish parts. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ 3990p 2 LT3990 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 12V, VBD = 3.3V unless otherwise noted. (Note 2) PARAMETER CONDITIONS MIN l Minimum Input Voltage Quiescent Current from VIN VEN Low VEN High VEN High l Feedback Voltage l 1.195 1.185 l TYP MAX 4 4.2 V 0.7 1.7 0.98 2.7 3.5 μA μA μA 1.21 1.21 1.225 1.235 V V 0.1 20 nA 0.0002 0.01 %/V 1.76 640 160 2.25 800 200 2.64 960 240 MHz kHz kHz VIN = 5V, VFB = 0V 535 700 865 mA VIN = 5V 350 400 500 mA FB Pin Bias Current (Note 3) FB Voltage Line Regulation 4.2V < VIN < 60V Switching Frequency RT = 41.2k, VIN = 6V RT = 158k, VIN = 6V RT = 768k, VIN = 6V Switch Current Limit Catch Schottky Current Limit Switch VCESAT ISW = 200mA 300 Switch Leakage Current 0.05 ISCH = 100mA, VIN = VBD = NC 650 Catch Schottky Reverse Leakage VSW = 12V 0.05 Boost Schottky Forward Voltage ISCH = 50mA, VIN = NC, VBOOST = 0V 875 Boost Schottky Reverse Leakage VREVERSE = 12V Catch Schottky Forward Voltage l Minimum Boost Voltage (Note 4) VIN = 5V BOOST Pin Current ISW = 200mA, VBOOST = 15V EN Pin Current VEN = 12V EN Voltage Threshold EN Rising, VIN ≥ 4.2V l 0.95 EN Voltage Hysteresis PG Threshold Offset from Feedback Voltage PG Sink Current VFB Rising 80 2 VPG = 3V 2 VPG = 0.4V VIN = 10V Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The LT3990E is guaranteed to meet performance specifications from 0°C to 125°C junction temperature. Specifications over the –40°C to 125°C operating junction temperature range are assured by design, characterization, and correlation with statistical process controls. The LT3990I is guaranteed over the full –40°C to 125°C operating junction temperature range. l 40 μA mV 0.02 2 1.4 1.8 5.5 8 mA 1 30 nA 1 1.05 V 120 0.01 l μA mV μA V mV 160 12 Minimum Switch On-Time Minimum Switch Off-Time mV 30 PG Hysteresis PG Leakage UNITS mV mV 1 μA 80 μA 90 ns 100 160 ns Note 3: Bias current flows into the FB pin. Note 4: This is the minimum voltage across the boost capacitor needed to guarantee full saturation of the switch. 3990p 3 LT3990 TYPICAL PERFORMANCE CHARACTERISTICS TA = 25°C, unless otherwise noted. Efficiency, VOUT = 3.3V Efficiency, VOUT = 5V VFB vs Temperature 90 90 1.220 FRONT PAGE APPLICATION 80 VIN = 12V EFFICIENCY (%) VIN = 36V 60 50 FRONT PAGE APPLICATION VOUT = 3.3V R1 = 1M R2 = 576k 40 30 0.01 0.1 1 10 LOAD CURRENT (mA) 70 1.210 VIN = 36V 60 1.205 50 1.200 40 30 0.01 100 0.1 1 10 LOAD CURRENT (mA) No-Load Supply Current 3.0 2.5 2.0 12 SUPPLY CURRENT (μA) SUPPLY CURRENT (µA) 3.5 Maximum Load Current 550 FRONT PAGE APPLICATION VIN = 12V VOUT = 3.3V R1 = 1M R2 = 576k 9 6 FRONT PAGE APPLICATION VOUT = 3.3V TYPICAL 500 MINIMUM 450 400 3 1.5 1.0 5 10 25 30 15 20 INPUT VOLTAGE (V) 35 0 –50 –25 40 0 Maximum Load Current 500 LOAD CURRENT (mA) TYPICAL 500 MINIMUM 450 400 5 10 15 20 25 30 INPUT VOLTAGE (V) 35 40 3990 G07 30 15 20 25 INPUT VOLTAGE (V) 300 35 40 Load Regulation 0.20 0.15 LIMITED BY CURRENT LIMIT 400 LIMITED BY MAXIMUM JUNCTION TEMPERATURE; QJA = 76°C/W 200 100 350 10 3990 G06 600 FRONT PAGE APPLICATION VOUT = 5V 550 5 3990 G05 Maximum Load Current 600 350 25 50 75 100 125 150 TEMPERATURE (°C) 3990 G04 LOAD CURRENT (mA) 25 50 75 100 125 150 TEMPERATURE (°C) 3990 G03 No-Load Supply Current 15 FRONT PAGE APPLICATION VOUT = 3.3V R1 = 1M R2 = 576k 0 3990 G02 3990 G01 4.0 1.195 –50 –25 100 LOAD REGULATION (%) EFFICIENCY (%) 70 1.215 VIN = 12V VIN = 24V VFB (V) VIN = 24V LOAD CURRENT (mA) 80 FRONT PAGE APPLICATION VIN = 12V VOUT = 5V 0 –50 –25 50 25 75 0 TEMPERATURE (°C) 100 125 0.10 0.05 0 –0.05 –0.10 –0.15 FRONT PAGE APPLICATION REFERENCED FROM VOUT AT 100mA LOAD –0.20 50 100 150 200 250 300 350 0 LOAD CURRENT (mA) 3990 G08 3990 G09 3990p 4 LT3990 TYPICAL PERFORMANCE CHARACTERISTICS TA = 25°C, unless otherwise noted. Switch Current Limit Switch Current Limit 800 Switching Frequency 2.4 800 2.2 600 500 CATCH DIODE VALLEY CURRENT LIMIT 400 300 700 2.0 1.8 FREQUENCY (MHz) SWITCH PEAK CURRENT LIMIT SWITCH CURRENT LIMIT (mA) SWITCH CURRENT LIMIT (mA) SWITCH PEAK CURRENT LIMIT 700 600 500 CATCH DIODE VALLEY CURRENT LIMIT 400 1.6 1.4 1.2 1.0 0.8 0.6 300 0.4 0.2 200 0 20 40 60 DUTY CYCLE (%) 200 –50 –25 100 80 0 3990 G10 3990 G12 Switch VCESAT (ISW = 200mA) vs Temperature Switch VCESAT 350 LOAD CURRENT = 175mA 500 160 140 MINIMUM OFF-TIME 120 100 80 MINIMUM ON-TIME 60 SWITCH VCESAT (mV) 400 SWITCH VCESAT (mV) 300 250 40 300 200 100 20 0 200 –50 –25 25 50 75 100 125 150 TEMPERATURE (°C) 0 0 25 50 75 100 125 150 TEMPERATURE (°C) 5.0 14 6.5 4.5 INPUT VOLTAGE (V) 6 4 300 400 200 SWITCH CURRENT (mA) 500 Minimum Input Voltage, VOUT = 5V FRONT PAGE APPLICATION VOUT = 3.3V 12 8 100 3990 G15 Minimum Input Voltage, VOUT = 3.3V BOOST Pin Current 10 0 3990 G14 3990 G13 FRONT PAGE APPLICATION VOUT = 5V 6.0 INPUT VOLTAGE (V) SWITCH ON-TIME/SWITCH OFF-TIME (ns) 25 50 75 100 125 150 TEMPERATURE (°C) 180 0 –50 –25 BOOST PIN CURRENT (mA) 0 3990 G11 Minimum Switch On-Time/Switch Off-Time 200 0 –50 –25 25 50 75 100 125 150 TEMPERATURE (oC) TO START 4.0 TO RUN 3.5 3.0 TO START 5.5 TO RUN 5.0 4.5 2 0 0 100 200 300 400 SWITCH CURRENT (mA) 500 3990 G16 2.5 0 50 100 150 200 250 LOAD CURRENT (mA) 300 350 3990 G17 4.0 0 50 100 150 200 250 LOAD CURRENT (mA) 300 350 3990 G17 3990p 5 LT3990 TYPICAL PERFORMANCE CHARACTERISTICS TA = 25°C, unless otherwise noted. Boost Diode Forward Voltage Catch Diode Forward Voltage CATCH DIODE VF (V) BOOST DIODE VF (V) 1.0 0.8 0.6 0.4 –50°C 25°C 125°C 150°C 0.2 0 0 50 100 150 BOOST DIODE CURRENT (mA) 20 0.8 16 0.6 0.4 –50°C 25°C 125°C 150°C 0.2 0 200 100 300 200 CATCH DIODE CURRENT (mA) 0 3990 G19 400 VR = 12V 12 8 4 0 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3990 G20 Power Good Threshold 3990 G21 Transient Load Response; Load Current is Stepped from 10mA (Burst Mode Operation) to 110mA EN Threshold 1.050 THRESHOLD VOLTAGE (V) 92 91 THRESHOLD (%) Catch Diode Leakage 1.0 CATCH DIODE LEAKAGE (μA) 1.2 90 89 88 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 1.025 VOUT 100mV/DIV 1.000 IL 100mA/DIV 100μs/DIV FRONT PAGE APPLICATION VIN = 12V VOUT = 5V 0.975 0.950 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3990 G22 3990 G23 Transient Load Response; Load Current is Stepped from 100mA to 200mA VOUT 100mV/DIV IL 100mA/DIV 100μs/DIV FRONT PAGE APPLICATION VIN = 12V VOUT = 5V 3990 G25 3990 G24 Switching Waveforms, Burst Mode Operation Switching Waveforms, Full Frequency Continuous Operation VSW 5V/DIV VSW 5mV/DIV IL 100mA/DIV IL 200mA/DIV VOUT 5mV/DIV VOUT 5mV/DIV 2μs/DIV FRONT PAGE APPLICATION VIN = 12V VOUT = 5V ILOAD = 10mA 3990 G26 1μs/DIV FRONT PAGE APPLICATION VIN = 12V VOUT = 5V ILOAD = 350mA 3990 G27 3990p 6 LT3990 PIN FUNCTIONS FB (Pin 1): The LT3990 regulates the FB pin to 1.21V. Connect the feedback resistor divider tap to this pin. EN (Pin 2): The part is in shutdown when this pin is low and active when this pin is high. The hysteretic threshold voltage is 1V going up and 0.97V going down. Tie to VIN if shutdown feature is not used. The EN threshold is accurate only when VIN is above 4.2V. If VIN is lower than 4.2V, ground EN to place the part in shutdown. VIN (Pin 3): The VIN pin supplies current to the LT3990’s internal circuitry and to the internal power switch. This pin must be locally bypassed. BOOST (Pin 7): This pin is used to provide a drive voltage, higher than the input voltage, to the internal bipolar NPN power switch. BD (Pin 8): This pin connects to the anode of the boost diode. This pin also supplies current to the LT3990’s internal regulator when BD is above 3.2V. PG (Pin 9): The PG pin is the open-drain output of an internal comparator. PG remains low until the FB pin is within 10% of the final regulation voltage. PG is valid when VIN is above 4.2V and EN is high. GND (Pins 4, 5): Ground. RT (Pin 10): A resistor is tied between RT and ground to set the switching frequency. SW (Pin 6): The SW pin is the output of an internal power switch. Connect this pin to the inductor. Exposed Pad (Pin 11, DFN Only): Ground. Must be soldered to PCB. BLOCK DIAGRAM 3 VIN C1 VIN INTERNAL 1.21V REF 1V 2 EN – + 8 + SHDN – BD DBOOST SLOPE COMP BOOST SWITCH LATCH 7 R 10 RT 9 RT PG OSCILLATOR 200kHz TO 2.2MHz + + 1.09V ERROR AMP – – GND (4, 5) VC Q C3 S SW Burst Mode DETECT DCATCH L1 VOUT 6 C2 FB R2 1 R1 3990 BD 3990p 7 LT3990 OPERATION The LT3990 is a constant frequency, current mode stepdown regulator. An oscillator, with frequency set by RT, sets an RS flip-flop, turning on the internal power switch. An amplifier and comparator monitor the current flowing between the VIN and SW pins, turning the switch off when this current reaches a level determined by the voltage at VC (see Block Diagram). An error amplifier measures the output voltage through an external resistor divider tied to the FB pin and servos the VC node. If the error amplifier’s output increases, more current is delivered to the output; if it decreases, less current is delivered. Another comparator monitors the current flowing through the catch diode and reduces the operating frequency when the current exceeds the 410mA bottom current limit. This foldback in frequency helps to control the output current in fault conditions such as a shorted output with high input voltage. Maximum deliverable current to the output is therefore limited by both switch current limit and catch diode current limit. An internal regulator provides power to the control circuitry. The bias regulator normally draws power from the VIN pin, but if the BD pin is connected to an external voltage higher than 3.2V, bias power will be drawn from the external source (typically the regulated output voltage). This improves efficiency. If the EN pin is low, the LT3990 is shut down and draws 0.7μA from the input. When the EN pin exceeds 1V, the switching regulator will become active. The switch driver operates from either VIN or from the BOOST pin. An external capacitor is used to generate a voltage at the BOOST pin that is higher than the input supply. This allows the driver to fully saturate the internal bipolar NPN power switch for efficient operation. To further optimize efficiency, the LT3990 automatically switches to Burst Mode operation in light load situations. Between bursts, all circuitry associated with controlling the output switch is shut down reducing the input supply current to 1.7μA. The LT3990 contains a power good comparator which trips when the FB pin is at 90% of its regulated value. The PG output is an open-drain transistor that is off when the output is in regulation, allowing an external resistor to pull the PG pin high. Power good is valid when the LT3990 is enabled and VIN is above 4.2V. 3990p 8 LT3990 APPLICATIONS INFORMATION FB Resistor Network The output voltage is programmed with a resistor divider between the output and the FB pin. Choose the 1% resistors according to: ⎛V ⎞ R1= R2 ⎜ OUT – 1⎟ ⎝ 1.21 ⎠ Reference designators refer to the Block Diagram. Note that choosing larger resistors will decrease the quiescent current of the application circuit. Setting the Switching Frequency The LT3990 uses a constant frequency PWM architecture that can be programmed to switch from 200kHz to 2.2MHz by using a resistor tied from the RT pin to ground. A table showing the necessary RT value for a desired switching frequency is in Table 1. Table 1. Switching Frequency vs RT Value SWITCHING FREQUENCY (MHz) RT VALUE (kΩ) 0.2 0.3 0.4 0.5 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 768 499 357 280 226 158 124 100 80.6 68.1 57.6 49.9 42.2 Operating Frequency Trade-Offs Selection of the operating frequency is a trade-off between efficiency, component size, minimum dropout voltage and maximum input voltage. The advantage of high frequency operation is that smaller inductor and capacitor values may be used. The disadvantages are lower efficiency, lower maximum input voltage, and higher dropout voltage. The highest acceptable switching frequency (fSW(MAX)) for a given application can be calculated as follows: fSW(MAX ) = VOUT + VD tON(MIN) ( VIN – VSW + VD ) where VIN is the typical input voltage, VOUT is the output voltage, VD is the integrated catch diode drop (~0.7V), and VSW is the internal switch drop (~0.5V at max load). This equation shows that slower switching frequency is necessary to accommodate high VIN/VOUT ratio. Lower frequency also allows a lower dropout voltage. The input voltage range depends on the switching frequency because the LT3990 switch has finite minimum on and off times. The switch can turn on for a minimum of ~150ns and turn off for a minimum of ~160ns (note that the minimum on-time is a strong function of temperature). This means that the minimum and maximum duty cycles are: DCMIN = fSW • tON(MIN) DCMAX = 1 – fSW • tON(MIN) where fSW is the switching frequency, the tON(MIN) is the minimum switch on-time (~150ns), and the tOFF(MIN) is the minimum switch off-time (~160ns). These equations show that duty cycle range increases when switching frequency is decreased. A good choice of switching frequency should allow adequate input voltage range (see next section) and keep the inductor and capacitor values small. Input Voltage Range The minimum input voltage is determined by either the LT3990’s minimum operating voltage of 4.2V or by its maximum duty cycle (as explained in previous section). The minimum input voltage due to duty cycle is: VIN(MIN) = VOUT + VD –V +V 1– fSW • tOFF(MIN) D SW where VIN(MIN) is the minimum input voltage, VOUT is the output voltage, VD is the catch diode drop (~0.7V), VSW is the internal switch drop (~0.5V at max load), fSW is the switching frequency (set by RT), and tOFF(MIN) is the minimum switch off-time (160ns). Note that higher switching frequency will increase the minimum input voltage. If a lower dropout voltage is desired, a lower switching frequency should be used. 3990p 9 LT3990 APPLICATIONS INFORMATION The highest allowed V IN during normal operation (VIN(OP-MAX)) is limited by minimum duty cycle and can be calculated by the following equation: VIN(OP-MAX ) = VOUT + VD –V +V fSW • tON(MIN) D SW where tON(MIN) is the minimum switch on-time (~150ns). However, the circuit will tolerate inputs up to the absolute maximum ratings of the VIN and BOOST pins, regardless of chosen switching frequency. During such transients where VIN is higher than VIN(OP-MAX), the switching frequency will be reduced below the programmed frequency to prevent damage to the part. The output voltage ripple and inductor current ripple may also be higher than in typical operation, however the output will still be in regulation. Inductor Selection For a given input and output voltage, the inductor value and switching frequency will determine the ripple current. The ripple current increases with higher VIN or VOUT and decreases with higher inductance and faster switching frequency. A good starting point for selecting the inductor value is: L=3 VOUT + VD fSW Table 2. Inductor Vendors where VD is the voltage drop of the catch diode (~0.7V), L is in μH and fSW is in MHz. The inductor’s RMS current rating must be greater than the maximum load current and its saturation current should be about 30% higher. For robust operation in fault conditions (start-up or short circuit) and high input voltage (>30V), the saturation current should be above 500mA. To keep the efficiency high, the series resistance (DCR) should be less than 0.1Ω, and the core material should be intended for high frequency applications. Table 2 lists several vendors and suitable types. This simple design guide will not always result in the optimum inductor selection for a given application. As a general rule, lower output voltages and higher switching frequency will require smaller inductor values. If the application requires less than 350mA load current, then a lesser inductor value may be acceptable. This allows use of a physically smaller inductor, or one with a lower DCR resulting in higher efficiency. There are several graphs in the Typical Performance Characteristics section of this data sheet that show the maximum load current as a function of input voltage for several popular output voltages. Low inductance may result in discontinuous mode operation, which is acceptable but reduces maximum load current. For details of maximum output current and discontinuous mode operation, see Linear Technology Application Note 44. Finally, for duty cycles greater than 50% (VOUT/VIN > 0.5), there is a minimum inductance required to avoid subharmonic oscillations. See Application Note 19. VENDOR URL Coilcraft www.coilcraft.com Input Capacitor Sumida www.sumida.com Toko www.tokoam.com Würth Elektronik www.we-online.com Coiltronics www.cooperet.com Murata www.murata.com Bypass the input of the LT3990 circuit with a ceramic capacitor of X7R or X5R type. Y5V types have poor performance over temperature and applied voltage, and should not be used. A 1μF to 4.7μF ceramic capacitor is adequate to bypass the LT3990 and will easily handle 3990p 10 LT3990 APPLICATIONS INFORMATION Step-down regulators draw current from the input supply in pulses with very fast rise and fall times. The input capacitor is required to reduce the resulting voltage ripple at the LT3990 and to force this very high frequency switching current into a tight local loop, minimizing EMI. A 1μF capacitor is capable of this task, but only if it is placed close to the LT3990 (see the PCB Layout section). A second precaution regarding the ceramic input capacitor concerns the maximum input voltage rating of the LT3990. A ceramic input capacitor combined with trace or cable inductance forms a high quality (under damped) tank circuit. If the LT3990 circuit is plugged into a live supply, the input voltage can ring to twice its nominal value, possibly exceeding the LT3990’s voltage rating. This situation is easily avoided (see the Hot Plugging Safely section). Output Capacitor and Output Ripple The output capacitor has two essential functions. It stores energy in order to satisfy transient loads and stabilize the LT3990’s control loop. Ceramic capacitors have very low equivalent series resistance (ESR) and provide the best ripple performance. A good starting value is: 50 COUT = VOUT • fSW where fSW is in MHz and COUT is the recommended output capacitance in μF. Use X5R or X7R types. This choice will provide low output ripple and good transient response. Transient performance can be improved with a higher value capacitor if combined with a phase lead capacitor (typically 22pF) between the output and the feedback pin. A lower value of output capacitor can be used to save space and cost but transient performance will suffer. The second function is that the output capacitor, along with the inductor, filters the square wave generated by the LT3990 to produce the DC output. In this role it determines the output ripple, so low impedance (at the switching frequency) is important. The output ripple decreases with increasing output capacitance, down to approximately 1mV. See Figure 1. Note that a larger phase lead capacitor should be used with a large output capacitor. 18 WORST-CASE OUTPUT RIPPLE (mV) the ripple current. Note that larger input capacitance is required when a lower switching frequency is used (due to longer on-times). If the input power source has high impedance, or there is significant inductance due to long wires or cables, additional bulk capacitance may be necessary. This can be provided with a low performance electrolytic capacitor. FRONT PAGE APPLICATION CLEAD = 47pF FOR COUT ≥ 47μF 16 14 12 10 8 6 4 VIN = 24V 2 VIN = 12V 0 0 20 60 40 COUT (μF) 80 100 3990 F01 Figure 1. Worst-Case Output Ripple Across Full Load Range When choosing a capacitor, look carefully through the data sheet to find out what the actual capacitance is under operating conditions (applied voltage and temperature). A physically larger capacitor or one with a higher voltage rating may be required. Table 3 lists several capacitor vendors. Table 3. Recommended Ceramic Capacitor Vendors MANUFACTURER WEBSITE AVX www.avxcorp.com Murata www.murata.com Taiyo Yuden www.t-yuden.com Vishay Siliconix www.vishay.com TDK www.tdk.com Ceramic Capacitors Ceramic capacitors are small, robust and have very low ESR. However, ceramic capacitors can cause problems when used with the LT3990 due to their piezoelectric nature. When in Burst Mode operation, the LT3990’s switching frequency depends on the load current, and at very light loads the LT3990 can excite the ceramic capacitor at audio frequencies, generating audible noise. Since the LT3990 3990p 11 LT3990 APPLICATIONS INFORMATION A final precaution regarding ceramic capacitors concerns the maximum input voltage rating of the LT3990. As previously mentioned, a ceramic input capacitor combined with trace or cable inductance forms a high quality (under damped) tank circuit. If the LT3990 circuit is plugged into a live supply, the input voltage can ring to twice its nominal value, possibly exceeding the LT3990’s rating. This situation is easily avoided (see the Hot Plugging Safely section). FRONT PAGE APPLICATION 600 500 400 300 200 100 0 0 50 100 150 200 250 LOAD CURRENT (mA) 300 350 3990 F03 Figure 3. Switching Frequency in Burst Mode Operation Low Ripple Burst Mode Operation To enhance efficiency at light loads, the LT3990 operates in low ripple Burst Mode operation which keeps the output capacitor charged to the proper voltage while minimizing the input quiescent current. During Burst Mode operation, the LT3990 delivers single cycle bursts of current to the output capacitor followed by sleep periods where the output power is delivered to the load by the output capacitor. Because the LT3990 delivers power to the output with single, low current pulses, the output ripple is kept below 5mV for a typical application. See Figure 2. As the load current decreases towards a no load condition, the percentage of time that the LT3990 operates in sleep mode increases and the average input current is greatly reduced resulting in high efficiency even at very low loads. Note that during Burst Mode operation, the switching frequency will be lower than the programmed switching frequency. See Figure 3. VSW 5V/DIV IL 100mA/DIV VOUT 5mV/DIV 2μs/DIV FRONT PAGE APPLICATION VIN = 12V VOUT = 5V ILOAD = 10mA 700 SWITCHING FREQUENCY (kHz) operates at a lower current limit during Burst Mode operation, the noise is typically very quiet to a casual ear. If this is unacceptable, use a high performance tantalum or electrolytic capacitor at the output. 3990 G26 Figure 2. Burst Mode Operation At higher output loads (above ~45mA for the front page application) the LT3990 will be running at the frequency programmed by the RT resistor, and will be operating in standard PWM mode. The transition between PWM and low ripple Burst Mode is seamless, and will not disturb the output voltage. BOOST and BD Pin Considerations Capacitor C3 and the internal boost Schottky diode (see the Block Diagram) are used to generate a boost voltage that is higher than the input voltage. In most cases a 0.22μF capacitor will work well. Figure 4 shows two ways to arrange the boost circuit. The BOOST pin must be more than 1.9V above the SW pin for best efficiency. For outputs of 2.2V and above, the standard circuit (Figure 4a) is best. For outputs between 2.2V and 2.5V, use a 0.47μF boost capacitor. For output voltages below 2.2V, the boost diode can be tied to the input (Figure 4b), or to another external supply greater than 2.2V. However, the circuit in Figure 4a is more efficient because the BOOST pin current and BD pin quiescent current come from a lower voltage source. Also, be sure that the maximum voltage ratings of the BOOST and BD pins are not exceeded. The minimum operating voltage of an LT3990 application is limited by the minimum input voltage (4.2V) and by the maximum duty cycle as outlined in a previous section. For proper start-up, the minimum input voltage is also limited by the boost circuit. If the input voltage is ramped slowly, the boost capacitor may not be fully charged. Because 3990p 12 LT3990 APPLICATIONS INFORMATION VOUT 5.0 FRONT PAGE APPLICATION VOUT = 3.3V BD VIN BOOST 4.5 C3 LT3990 INPUT VOLTAGE (V) VIN SW GND (4a) For VOUT ≥ 2.2V VIN TO RUN 3.5 3.0 2.5 BD VIN TO START 4.0 0 50 BOOST C3 LT3990 SW 6.5 VOUT 100 150 200 250 LOAD CURRENT (mA) 300 350 300 350 FRONT PAGE APPLICATION VOUT = 5V GND 3990 F04 (4b) For VOUT < 2.2V; VIN < 27V Figure 4. Two Circuits for Generating the Boost Voltage the boost capacitor is charged with the energy stored in the inductor, the circuit will rely on some minimum load current to get the boost circuit running properly. This minimum load will depend on input and output voltages, and on the arrangement of the boost circuit. The minimum load generally goes to zero once the circuit has started. Figure 5 shows a plot of minimum load to start and to run as a function of input voltage. In many cases the discharged output capacitor will present a load to the switcher, which will allow it to start. The plots show the worst-case situation where VIN is ramping very slowly. For lower start-up voltage, the boost diode can be tied to VIN; however, this restricts the input range to one-half of the absolute maximum rating of the BOOST pin. Enable Pin The LT3990 is in shutdown when the EN pin is low and active when the pin is high. The rising threshold of the EN comparator is 1V, with a 30mV hysteresis. This threshold is accurate when VIN is above 4.2V. If VIN is lower than 4.2V, tie EN pin to GND to place the part in shutdown. INPUT VOLTAGE (V) 6.0 TO START 5.5 TO RUN 5.0 4.5 4.0 0 50 100 150 200 250 LOAD CURRENT (mA) 3990 F05 Figure 5. The Minimum Input Voltage Depends on Output Voltage, Load Current and Boost Circuit Adding a resistor divider from VIN to EN programs the LT3990 to regulate the output only when VIN is above a desired voltage (see Figure 6). This threshold voltage, VIN(EN), can be adjusted by setting the values R3 and R4 such that they satisfy the following equation: VIN(EN) = R3 + R4 • 1V R4 where output regulation should not start until VIN is above VIN(EN). Note that due to the comparator’s hysteresis, regulation will not stop until the input falls slightly below VIN(EN). 3990p 13 LT3990 APPLICATIONS INFORMATION 160 LT3990 VIN R3 1V EN + – INPUT CURRENT (μA) VIN SHDN R4 VIN(EN) = 6V R3 = 5M R4 = 1M 120 80 40 0 3990 F06 4 OUTPUT VOLTAGE (V) Figure 6. Enable Be aware that while VIN is below 4.2V, the input current may rise up to several hundred μA and the part may begin to switch while the internal circuitry starts up. Figure 7 shows the startup behavior of a typical application with different programmed VIN(EN). 3 2 1 0 0 1 2 3 4 5 6 160 INPUT CURRENT (μA) Shorted and Reversed Input Protection 8 VIN(EN) = 12V R3 = 11M R4 = 1M 120 80 40 0 4 OUTPUT VOLTAGE (V) If the inductor is chosen so that it won’t saturate excessively, a LT3990 buck regulator will tolerate a shorted output. There is another situation to consider in systems where the output will be held high when the input to the LT3990 is absent. This may occur in battery charging applications or in battery backup systems where a battery or some other supply is diode ORed with the LT3990’s output. If the VIN pin is allowed to float and the EN pin is held high (either by a logic signal or because it is tied to VIN), then the LT3990’s internal circuitry will pull its quiescent current through its SW pin. This is fine if the system can tolerate a few μA in this state. If the EN pin is grounded, the SW pin current will drop to 0.7μA. However, if the VIN pin is grounded while the output is held high, regardless of EN, parasitic diodes inside the LT3990 can pull current from the output through the SW pin and the VIN pin. Figure 8 shows a circuit that will run only when the input voltage is present and that protects against a shorted or reversed input. 7 INPUT VOLTAGE (V) 3 2 1 0 0 2 4 6 8 10 12 14 INPUT VOLTAGE (V) 3990 F07 Figure 7. VIN Start-Up of Front Page Application with VOUT = 3.3V, No-Load Current, and VIN(EN) programmed as in Figure 6. D4 MBRS140 VIN BD VIN BOOST LT3990 EN SW GND FB VOUT + BACKUP 3990 F08 Figure 8. Diode D4 Prevents a Shorted Input from Discharging a Backup Battery Tied to the Output. It Also Protects the Circuit from a Reversed Input. The LT3990 Runs Only when the Input is Present 3990p 14 LT3990 APPLICATIONS INFORMATION PCB Layout For proper operation and minimum EMI, care must be taken during printed circuit board layout. Figure 9 shows the recommended component placement with trace, ground plane and via locations. Note that large, switched currents flow in the LT3990’s VIN and SW pins, the internal catch diode and the input capacitor. The loop formed by these components should be as small as possible. These components, along with the inductor and output capacitor, should be placed on the same side of the circuit board, and their connections should be made on that layer. Place a local, unbroken ground plane below these components. The SW and BOOST nodes should be as small as possible. Finally, keep the FB nodes small so that the ground traces will shield them from the SW and BOOST nodes. The Exposed Pad on the bottom of the DFN package must be soldered to ground so that the pad acts as a heat sink. To keep thermal resistance low, extend the ground plane as much as possible, and add thermal vias under and near the LT3990 to additional ground planes within the circuit board and on the bottom side. GND GND 1 10 EN 2 9 VIN 3 8 4 7 5 6 PG VOUT GND VIAS TO LOCAL GROUND PLANE VIAS TO VOUT 3990 F09 Figure 9. A Good PCB Layout Ensures Proper, Low EMI Operation Hot Plugging Safely The small size, robustness and low impedance of ceramic capacitors make them an attractive option for the input bypass capacitor of LT3990 circuits. However, these capacitors can cause problems if the LT3990 is plugged into a live supply. The low loss ceramic capacitor, combined with stray inductance in series with the power source, forms an under damped tank circuit, and the voltage at the VIN pin of the LT3990 can ring to twice the nominal input voltage, possibly exceeding the LT3990’s rating and damaging the part. If the input supply is poorly controlled or the user will be plugging the LT3990 into an energized supply, the input network should be designed to prevent this overshoot. See Linear Technology Application Note 88 for a complete discussion. High Temperature Considerations For higher ambient temperatures, care should be taken in the layout of the PCB to ensure good heat sinking of the LT3990. The Exposed Pad on the bottom of the DFN package must be soldered to a ground plane. This ground should be tied to large copper layers below with thermal vias; these layers will spread the heat dissipated by the LT3990. Placing additional vias can reduce thermal resistance further. In the MSOP package, the copper lead frame is fused to GND (Pin 5) so place thermal vias near this pin. The maximum load current should be derated as the ambient temperature approaches the maximum junction rating. Power dissipation within the LT3990 can be estimated by calculating the total power loss from an efficiency measurement and subtracting inductor loss. The die temperature is calculated by multiplying the LT3990 power dissipation by the thermal resistance from junction to ambient. Finally, be aware that at high ambient temperatures the internal Schottky diode will have significant leakage current (see Typical Performance Characteristics) increasing the quiescent current of the LT3990 converter. Other Linear Technology Publications Application Notes 19, 35 and 44 contain more detailed descriptions and design information for buck regulators and other switching regulators. The LT1376 data sheet has a more extensive discussion of output ripple, loop compensation and stability testing. Design Note 100 shows how to generate a bipolar output supply using a buck regulator. 3990p 15 LT3990 TYPICAL APPLICATIONS 3.3V Step-Down Converter VIN 4.2V TO 60V 5V Step-Down Converter VIN 6V TO 60V C3 0.22μF VIN BOOST OFF ON EN PG BD RT 226k R1 1M OFF ON R2 576k VOUT 5V 350mA SW BD RT R1 1M FB GND 226k 3990 TA02 f = 600kHz EN PG L1 22μH 22pF C1 2.2μF C2 22μF FB GND BOOST LT3990 VOUT 3.3V 350mA SW 22pF C1 2.2μF VIN L1 22μH LT3990 C3 0.22μF R2 316k C2 22μF 3990 TA03 f = 600kHz 2.5V Step-Down Converter VIN 4.2V TO 60V C3 0.47μF VIN BOOST LT3990 OFF ON EN PG SW RT FB L1 15μH BD 47pF C1 2.2μF VOUT 2.5V 350mA GND 226k R1 1M R2 931k C2 47μF 3990 TA04 f = 600kHz 1.8V Step-Down Converter VIN 4.2V TO 27V C3 0.22μF VIN BOOST LT3990 OFF ON C1 2.2μF EN BD PG f = 600kHz VOUT 1.8V 350mA SW 47pF RT 226k L1 10μH R1 487k FB GND R2 1M C2 47μF 3990 TA05 3990p 16 LT3990 TYPICAL APPLICATIONS 12V Step-Down Converter VIN 14V TO 60V 5V, 2MHz Step-Down Converter VIN 8.5V TO 16V TRANSIENTS TO 60V C3 0.1μF VIN BOOST L1 33μH LT3990 OFF ON EN PG SW RT FB R1 1M 22pF C1 2.2μF GND 226k VIN VOUT 12V 350mA BD BOOST LT3990 OFF ON EN PG L1 10μH C1 1μF BD RT 49.9k VOUT 5V 350mA SW 22pF C2 22μF R2 113k C3 0.1μF R1 1M C2 10μF FB GND R2 316k 3990 TA06 f = 600kHz f = 2MHz 3990 TA07 5V Step-Down Converter with Reduced Input Current During Start-Up VIN 6V TO 60V kΩ + 0.22μF VIN 5M – BOOST LT3990 22μH SW 1M EN PG 2.2μF RT FB BD 22pF 226k 1M 22μF GND 316k 3990 TA08a f = 600kHz Input Current During Start-Up VOUT 5V 350mA Start-Up from High Impedance Input Source 4.5 EN PROGRAMMED TO 6V 4.0 INPUT CURRENT (mA) 3.5 3.0 2.5 2.0 INPUT CURRENT DROPOUT CONDITIONS VIN 5V/DIV FRONT PAGE APPLICATION VOUT 2V/DIV FRONT PAGE APPLICATION WITH EN PROGRAMMED TO 6V 1.5 1.0 0.5 5ms/DIV FRONT PAGE APPLICATION VOUT = 5V 1k INPUT SOURCE RESISTANCE 2.5mA LOAD 0 3990 TA08c –0.5 0 2 6 8 4 INPUT VOLTAGE (V) 10 12 3990 TA08b 3990p 17 LT3990 PACKAGE DESCRIPTION DDB Package 10-Lead Plastic DFN (3mm × 2mm) (Reference LTC DWG # 05-08-1722 Rev Ø) 0.64 p0.05 (2 SIDES) 0.70 p0.05 2.55 p0.05 1.15 p0.05 PACKAGE OUTLINE 0.25 p 0.05 0.50 BSC 2.39 p0.05 (2 SIDES) RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS 3.00 p0.10 (2 SIDES) R = 0.05 TYP R = 0.115 TYP 6 0.40 p 0.10 10 2.00 p0.10 (2 SIDES) PIN 1 BAR TOP MARK (SEE NOTE 6) 0.200 REF 0.75 p0.05 0 – 0.05 0.64 p 0.05 (2 SIDES) 5 0.25 p 0.05 PIN 1 R = 0.20 OR 0.25 s 45o CHAMFER 1 (DDB10) DFN 0905 REV Ø 0.50 BSC 2.39 p0.05 (2 SIDES) BOTTOM VIEW—EXPOSED PAD NOTE: 1. DRAWING CONFORMS TO VERSION (WECD-1) IN JEDEC PACKAGE OUTLINE M0-229 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 3990p 18 LT3990 PACKAGE DESCRIPTION MS Package 10-Lead Plastic MSOP (Reference LTC DWG # 05-08-1661 Rev E) 0.889 p 0.127 (.035 p .005) 5.23 (.206) MIN 3.20 – 3.45 (.126 – .136) 3.00 p 0.102 (.118 p .004) (NOTE 3) 0.50 0.305 p 0.038 (.0197) (.0120 p .0015) BSC TYP RECOMMENDED SOLDER PAD LAYOUT 0.254 (.010) 10 9 8 7 6 3.00 p 0.102 (.118 p .004) (NOTE 4) 4.90 p 0.152 (.193 p .006) DETAIL “A” 0.497 p 0.076 (.0196 p .003) REF 0o – 6o TYP GAUGE PLANE 1 2 3 4 5 0.53 p 0.152 (.021 p .006) DETAIL “A” 0.86 (.034) REF 1.10 (.043) MAX 0.18 (.007) SEATING PLANE 0.17 – 0.27 (.007 – .011) TYP 0.50 (.0197) BSC 0.1016 p 0.0508 (.004 p .002) MSOP (MS) 0307 REV E NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 3990p Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 19 LT3990 RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LT3689 36V, 60V Transient Protection, 800mA, 2.2MHz High Efficiency Micropower Step-Down DC/DC Converter with POR Reset and Watchdog Timer VIN: 3.6V to 36V, Transient to 60V, VOUT(MIN) = 0.8V, IQ = 75μA, ISD < 1μA, 3mm × 3mm QFN16 LT3682 36V, 60VMAX, 1A, 2.2MHz High Efficiency Micropower Step-Down DC/DC Converter VIN: 3.6V to 36V, VOUT(MIN) = 0.8V, IQ = 75μA, ISD < 1μA, 3mm × 3mm DFN12 LT3480 36V with Transient Protection to 60V, 2A (IOUT), 2.4MHz, High Efficiency Step-Down DC/DC Converter with Burst Mode® Operation VIN: 3.6V to 38V, VOUT(MIN) = 0.78V, IQ = 70μA, ISD < 1μA, 3mm × 3mm DFN10, MSOP10E LT3685 36V with Transient Protection to 60V, 2A (IOUT), 2.4MHz, High Efficiency Step-Down DC/DC Converter VIN: 3.6V to 38V, VOUT(MIN) = 0.78V, IQ = 70μA, ISD < 1μA, 3mm × 3mm DFN10, MSOP10E LT3481 34V with Transient Protection to 36V, 2A (IOUT), 2.8MHz, High Efficiency Step-Down DC/DC Converter with Burst Mode Operation VIN: 3.6V to 34V, VOUT(MIN) = 1.26V, IQ = 50μA, ISD < 1μA, 3mm × 3mm DFN10, MSOP10E LT3684 34V with Transient Protection to 36V, 2A (IOUT), 2.8MHz, High Efficiency Step-Down DC/DC Converter VIN: 3.6V to 34V, VOUT(MIN) = 1.26V, IQ = 850μA, ISD < 1μA, 3mm × 3mm DFN10, MSOP10E LT3508 36V with Transient Protection to 40V, Dual 1.4A (IOUT), 3MHz, High Efficiency Step-Down DC/DC Converter VIN: 3.7V to 37V, VOUT(MIN) = 0.8V, IQ = 4.6mA, ISD < 1μA, 4mm × 4mm QFN24, TSSOP16E LT3505 36V with Transient Protection to 40V, 1.4A (IOUT), 3MHz, High Efficiency Step-Down DC/DC Converter VIN: 3.6V to 34V, VOUT(MIN) = 0.78V, IQ = 2mA, ISD < 2μA, 3mm × 3mm DFN8, MSOP8E LT3500 36V, 40VMAX, 2A, 2.5MHz High Efficiency Step-Down DC/DC Converter and LDO Controller VIN: 3.6V to 36V, VOUT(MIN) = 0.8V, IQ = 2.5mA, ISD < 10μA, 3mm × 3mm DFN10 LT3507 36V 2.5MHz, Triple (2.4A + 1.5A + 1.5A (IOUT)) with LDO Controller High Efficiency Step-Down DC/DC Converter VIN: 4V to 36V, VOUT(MIN) = 0.8V, IQ = 7mA, ISD < 1μA, 5mm × 7mm QFN38 LT3437 60V, 400mA (IOUT), Micropower Step-Down DC/DC Converter with Burst Mode Operation VIN: 3.3V to 60V, VOUT(MIN) = 1.25V, IQ = 100μA, ISD < 1μA, 3mm × 3mm DFN10, TSSOP16E LT1976/LT1977 60V, 1.2A (IOUT), 200/500kHz, High Efficiency Step-Down DC/DC Converter with Burst Mode Operation VIN: 3.3V to 60V, VOUT(MIN) = 1.20V, IQ = 100μA, ISD < 1μA, TSSOP16E LT3434/LT3435 60V, 2.4A (IOUT), 200/500kHz, High Efficiency Step-Down DC/DC Converter with Burst Mode Operation VIN: 3.3V to 60V, VOUT(MIN) = 1.20V, IQ = 100μA, ISD < 1μA, TSSOP16E LT1936 36V, 1.4A (IOUT) , 500kHz High Efficiency Step-Down DC/DC Converter VIN: 3.6V to 36V, VOUT(MIN) = 1.2V, IQ = 1.9mA, ISD < 1μA, MS8E LT3493 36V, 1.4A (IOUT), 750kHz High Efficiency Step-Down DC/DC Converter VIN: 3.6V to 36V, VOUT(MIN) = 0.8V, IQ = 1.9mA, ISD < 1μA, 2mm × 3mm DFN6 LT1766 60V, 1.2A (IOUT), 200kHz, High Efficiency Step-Down DC/DC Converter VIN: 5.5V to 60V, VOUT(MIN) = 1.20V, IQ = 2.5mA, ISD = 25μA, TSSOP16E LT3508 36V with Transient Protection to 40V, Dual 1.4A (IOUT), 3MHz, High Efficiency Step-Down DC/DC Converter VIN: 3.7V to 37V, VOUT(MIN) = 0.8V, IQ = 4.6mA, ISD < 1μA, 4mm × 4mm QFN24, TSSOP16E LT3500 36V, 40VMAX, 2A, 2.5MHz High Efficiency Step-Down DC/DC Converter and LDO Controller VIN: 3.6V to 36V, VOUT(MIN) = 0.8V, IQ = 2.5mA, ISD < 10μA, 3mm × 3mm DFN10 LT3507 36V 2.5MHz, Triple (2.4A + 1.5A + 1.5A (IOUT)) with LDO Controller High Efficiency Step-Down DC/DC Converter VIN: 4V to 36V, VOUT(MIN) = 0.8V, IQ = 7mA, ISD < 1μA, 5mm × 7mm QFN38 Burst Mode is a registered trademark of Linear Technology Corporation. 3990p 20 Linear Technology Corporation LT 0709 • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com © LINEAR TECHNOLOGY CORPORATION 2009