LINER LT1807 Gain-bandwidth product: 325mhz Datasheet

LT1806/LT1807
325MHz, Single/Dual,
Rail-to-Rail Input and Output, Low Distortion,
Low Noise Precision Op Amps
DESCRIPTION
FEATURES
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Gain-Bandwidth Product: 325MHz
Slew Rate: 140V/μs
Wide Supply Range: 2.5V to 12.6V
Large Output Current: 85mA
Low Distortion, 5MHz: –80dBc
Low Voltage Noise: 3.5nV/√Hz
Input Common Mode Range Includes Both Rails
Output Swings Rail-to-Rail
Input Offset Voltage (Rail-to-Rail): 550μV Max
Common Mode Rejection: 106dB Typ
Power Supply Rejection: 105dB Typ
Unity-Gain Stable
Power Down Pin (LT1806)
Operating Temperature Range: – 40°C to 85°C
Single in SO-8 and 6-Pin Low Profile (1mm)
ThinSOT™ Packages
Dual in SO-8 and 8-Pin MSOP Packages
The LT®1806/LT1807 are single/dual low noise rail-to-rail
input and output unity-gain stable op amps that feature a
325MHz gain-bandwidth product, a 140V/μs slew rate and
a 85mA output current. They are optimized for low voltage,
high performance signal conditioning systems.
The LT1806/LT1807 have a very low distortion of – 80dBc
at 5MHz, a low input referred noise voltage of 3.5nV/√Hz
and a maximum offset voltage of 550μV that allows them to
be used in high performance data acquisition systems.
The LT1806/LT1807 have an input range that includes
both supply rails and an output that swings within 20mV
of either supply rail to maximize the signal dynamic range
in low supply applications.
The LT1806/LT1807 maintain their performance for supplies
from 2.5V to 12.6V and are specified at 3V, 5V and ±5V
supplies. The inputs can be driven beyond the supplies
without damage or phase reversal of the output.
APPLICATIONS
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Low Voltage, High Frequency Signal Processing
Driving A/D Converters
Rail-to-Rail Buffer Amplifiers
Active Filters
Video Line Driver
L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear
Technology Corporation. ThinSOT is a trademark of Linear Technology Corporation. All other
trademarks are the property of their respective owners.
The LT1806 is available in an 8-pin SO package with the
standard op amp pinout and a 6-pin TSOT-23 package. The
LT1807 features the standard dual op amp pinout and is
available in 8-pin SO and MSOP packages.These devices
can be used as plug-in replacements for many op amps
to improve input/output range and performance.
TYPICAL APPLICATION
Gain of 20 Differential A/D Driver
4096 Point FFT Response
0
+
1/2 LT1807
VIN
–20
R2
909Ω
5V
R5
49.9Ω
R1
100Ω
C1 5.6pF
C2 5.6pF
C3
470pF
+AVIN
LTC®1420
PGA GAIN = 1
–AVIN VREF = 4.096V
R6
49.9Ω
R3
100Ω
12 BITS
10Msps
AMPLITUDE (dB)
–
VS = p5V
AV = 20
fSAMPLE = 10Msps
fIN = 1.4086MHz
SFDR = 83dB
NONAVERAGED
VIN = 200mVP-P
–40
–60
–80
–100
18067 TA01
–
R4
1k
1/2 LT1807
+
–5V
–120
0
1
2
3
FREQUENCY (MHz)
4
5
18067 TA02
18067fc
1
LT1806/LT1807
ABSOLUTE MAXIMUM RATINGS
(Note 1)
Total Supply Voltage (V+ to V –) ............................. 12.6V
Input Voltage (Note 2) .............................................. ±VS
Input Current (Note 2) ..........................................±10mA
Output Short-Circuit Duration (Note 3) ............ Indefinite
Operating Temperature Range (Note 4) ...– 40°C to 85°C
Specified Temperature Range (Note 5) ....– 40°C to 85°C
Junction Temperature ........................................... 150°C
Storage Temperature Range ..................– 65°C to 150°C
Lead Temperature (Soldering, 10 sec)................... 300°C
PIN CONFIGURATION
TOP VIEW
TOP VIEW
V– 2
SHDN 1
8
NC
–IN 2
7
V+
6
OUT
5
NC
5 SHDN
+IN 3
+
–
6 V+
OUT 1
+IN 3
4 –IN
V–
4
S6 PACKAGE
6-LEAD PLASTIC TSOT-23
S8 PACKAGE
8-LEAD PLASTIC SO
TJMAX = 150°C, θJA = 160°C/W (Note 9)
TJMAX = 150°C, θJA = 100°C/W (Note 9)
TOP VIEW
TOP VIEW
1
2
3
4
8
7
6
5
OUT A 1
V+
OUT B
–IN B
+IN B
–IN A 2
+IN A 3
V– 4
MS8 PACKAGE
8-LEAD PLASTIC MSOP
+
–
OUT A
–IN A
+IN A
V–
–
+
8
V+
7
OUT B
6
–IN B
5
+IN B
S8 PACKAGE
8-LEAD PLASTIC SO
TJMAX = 150°C, θJA = 135°C/W (Note 9)
TJMAX = 150°C, θJA = 100°C/W (Note 9)
ORDER INFORMATION
LEAD FREE FINISH
TAPE AND REEL
PART MARKING
PACKAGE DESCRIPTION
SPECIFIED TEMPERATURE RANGE
LT1806CS6#PBF
LT1806CS6#TRPBF
LTNK
6-Lead Plastic TSOT-23
0°C to 70°C
LT1806IS6#PBF
LT1806IS6#TRPBF
LTNL
6-Lead Plastic TSOT-23
–40°C to 85°C
LT1806CS8#PBF
LT1806CS8#TRPBF
1806
8-Lead Plastic SO
0°C to 70°C
LT1806IS8#PBF
LT1806IS8#TRPBF
1806I
8-Lead Plastic SO
–40°C to 85°C
LT1807CMS8#PBF
LT1807CMS8#TRPBF
LTTT
8-Lead Plastic MSOP
0°C to 70°C
LT1807IMS8#PBF
LT1807IMS8#TRPBF
LTTV
8-Lead Plastic MSOP
–40°C to 85°C
LT1807CS8#PBF
LT1807CS8#TRPBF
1807
8-Lead Plastic SO
0°C to 70°C
LT1807IS8#PBF
LT1807IS8#TRPBF
1807I
8-Lead Plastic SO
–40°C to 85°C
Consult LTC Marketing for parts specified with wider operating temperature ranges.
Consult LTC Marketing for information on non-standard lead based finish parts.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/
18067fc
2
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
TA = 25°C. VS = 5V, 0V; VS = 3V, 0V; VSHDN = open; VCM = VOUT = half supply, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
VOS
Input Offset Voltage
ΔVOS
Input Offset Voltage Shift
VCM = V +
VCM = V –
VCM = V + (LT1806 SOT-23)
VCM = V – (LT1806 SOT-23)
VCM = V – to V+
VCM = V – to V+ (LT1806 SOT-23)
VCM = V – to V+
Input Offset Voltage Match (Channel-to-Channel)
(Note 10)
IB
ΔIB
Input Bias Current
VCM = V +
VCM = V – + 0.2V
MIN
–13
TYP
MAX
UNITS
100
100
100
100
550
550
700
700
μV
μV
μV
μV
50
100
550
700
μV
μV
200
1000
μV
1
–5
4
μA
μA
Input Bias Current Shift
VCM = V – to V+
6
17
μA
Input Bias Current Match (Channel-to-Channel)
(Note 10)
0.03
0.05
1.2
3.0
μA
μA
0.03
0.05
0.6
1.5
μA
μA
0.08
2.1
μA
IOS
Input Offset Current
ΔIOS
Input Offset Current Shift
VCM = V +
VCM = V – + 0.2V
VCM = V +
VCM = V – + 0.2V
VCM = V – + 0.2V to V +
Input Noise Voltage
0.1Hz to 10Hz
800
en
Input Noise Voltage Density
f = 10kHz
3.5
nV/√Hz
in
Input Noise Current Density
f = 10kHz
1.5
pA/√Hz
CIN
Input Capacitance
AVOL
Large-Signal Voltage Gain
VS = 5V, VO = 0.5V to 4.5V, RL = 1k to VS/2
VS = 5V, VO = 1V to 4V, RL = 100 to VS/2
VS = 3V, VO = 0.5V to 2.5V, RL = 1k to VS/2
75
9
60
220
22
150
V/mV
V/mV
V/mV
CMRR
Common Mode Rejection Ratio
VS = 5V, VCM = V – to V +
VS = 3V, VCM = V – to V +
79
74
100
95
dB
dB
CMRR Match (Channel-to-Channel) (Note 10)
VS = 5V, VCM = V – to V +
VS = 3V, VCM = V – to V +
73
68
100
95
dB
dB
2
V–
Input Common Mode Range
PSRR
nVP-P
pF
V+
V
Power Supply Rejection Ratio
VS = 2.5V to 10V, VCM = 0V
90
105
dB
PSRR Match (Channel-to-Channel) (Note 10)
VS = 2.5V to 10V, VCM = 0V
84
105
dB
Minimum Supply Voltage (Note 6)
2.3
2.5
V
VOL
Output Voltage Swing Low (Note 7)
No Load
ISINK = 5mA
ISINK = 25mA
8
50
170
50
130
375
mV
mV
mV
VOH
Output Voltage Swing High (Note 7)
No Load
ISOURCE = 5mA
ISOURCE = 25mA
15
85
350
65
180
650
mV
mV
mV
18067fc
3
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
TA = 25°C. VS = 5V, 0V; VS = 3V, 0V; VSHDN = open; VCM = VOUT = half supply, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
ISC
Short-Circuit Current
VS = 5V
VS = 3V
±35
±30
±85
±65
IS
Supply Current per Amplifier
ISHDN
MAX
UNITS
mA
mA
9
13
mA
Disable Supply Current
VS = 5V, VSHDN = 0.3V
VS = 3V, VSHDN = 0.3V
0.40
0.22
0.9
0.7
mA
mA
SHDN Pin Current
VS = 5V, VSHDN = 0.3V
VS = 3V, VSHDN = 0.3V
150
100
350
300
μA
μA
Shutdown Output Leakage Current
VSHDN = 0.3V
0.1
75
μA
0.3
V
VL
SHDN Pin Input Voltage LOW
VH
SHDN Pin Input Voltage HIGH
tON
Turn-On Time
VSHDN = 0.3V to 4.5V, RL = 100Ω
80
ns
tOFF
Turn-Off Time
VSHDN = 4.5V to 0.3V, RL = 100Ω
50
ns
GBW
Gain-Bandwidth Product
Frequency = 6MHz
325
MHz
SR
Slew Rate
VS = 5V, AV = –1, RL = 1k, VO = 4V
125
V/μs
FPBW
Full-Power Bandwidth
VS = 5V, VOUT = 4VP-P
10
MHz
HD
Harmonic Distortion
VS = 5V, AV = 1, RL = 1k, VO = 2VP-P, fC = 5MHz
–78
dBc
tS
Settling Time
0.01%, VS = 5V, VSTEP = 2V, AV = 1, RL = 1k
60
ns
ΔG
Differential Gain (NTSC)
VS = 5V, AV = 2, RL = 150
0.015
%
Δθ
Differential Phase (NTSC)
VS = 5V, AV = 2, RL = 150
0.05
Deg
V+ – 0.5
V
The l denotes the specifications which apply over the 0°C < TA < 70°C temperature range. VS = 5V, 0V; VS = 3V, 0V; VSHDN = open;
VCM = VOUT = half supply, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
TYP
MAX
UNITS
VOS
Input Offset Voltage
l
l
l
l
200
200
200
200
700
700
850
850
μV
μV
μV
μV
VOS TC
Input Offset Voltage Drift (Note 8)
l
l
1.5
1.5
5
5
ΔVOS
Input Offset Voltage Shift
VCM = V +
VCM = V –
VCM = V + (LT1806 SOT-23)
VCM = V – (LT1806 SOT-23)
VCM = V +
VCM = V –
VCM = V – to V+
VCM = V – to V+ (LT1806 SOT-23)
VCM = V –, VCM = V+
l
l
100
100
700
850
μV
μV
l
300
1200
μV
VCM = V + – 0.2V
VCM = V – + 0.4V
l
l
1
–5
5
μA
μA
VCM = V – + 0.4V to V+ – 0.2V
l
6
20
μA
Input Offset Voltage Match (Channel-to-Channel)
(Note 10)
IB
ΔIB
Input Bias Current
Input Bias Current Shift
MIN
–15
μV/°C
μV/°C
18067fc
4
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the 0°C < TA < 70°C
temperature range. VS = 5V, 0V; VS = 3V, 0V; VSHDN = open; VCM = VOUT = half supply, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
Input Bias Current Match (Channel-to-Channel)
(Note 10)
VCM = V + – 0.2V
VCM = V – + 0.4V
VCM = V + – 0.2V
VCM = V – + 0.4V
VCM = V – + 0.4V to V+ – 0.2V
MIN
TYP
MAX
UNITS
l
l
0.03
0.05
1.5
3.5
μA
μA
l
l
0.03
0.05
0.75
1.80
μA
μA
l
0.08
2.55
μA
IOS
Input Offset Current
ΔIOS
Input Offset Current Shift
AVOL
Large-Signal Voltage Gain
VS = 5V, VO = 0.5V to 4.5V, RL = 1k to VS/2
VS = 5V, VO = 1V to 4V, RL = 100Ω to VS/2
VS = 3V, VO = 0.5V to 2.5V, RL = 1k to VS/2
l
l
l
60
7.5
45
175
20
140
V/mV
V/mV
V/mV
CMRR
Common Mode Rejection Ratio
VS = 5V, VCM = V – to V +
VS = 3V, VCM = V – to V +
l
l
77
72
94
89
dB
dB
CMRR Match (Channel-to-Channel) (Note 10)
VS = 5V, VCM = V – to V +
VS = 3V, VCM = V – to V +
l
l
71
66
94
89
dB
dB
l
V–
Input Common Mode Range
V+
V
Power Supply Rejection Ratio
VS = 2.5V to 10V, VCM = 0V
l
88
105
dB
PSRR Match (Channel-to-Channel) (Note 10)
VS = 2.5V to 10V, VCM = 0V
l
82
105
dB
Minimum Supply Voltage (Note 6)
VCM = VO = 0.5V
l
2.3
2.5
V
VOL
Output Voltage Swing Low (Note 7)
No Load
ISINK = 5mA
ISINK = 25mA
l
l
l
12
60
180
60
140
425
mV
mV
mV
VOH
Output Voltage Swing High (Note 7)
No Load
ISOURCE = 5mA
ISOURCE = 25mA
l
l
l
30
110
360
120
220
700
mV
mV
mV
ISC
Short-Circuit Current
VS = 5V
VS = 3V
l
l
IS
Supply Current per Amplifier
PSRR
ISHDN
±30
±25
±65
±55
mA
mA
l
10
14
mA
Disable Supply Current
VS = 5V, VSHDN = 0.3V
VS = 3V, VSHDN = 0.3V
l
l
0.40
0.22
1.1
0.9
mA
mA
SHDN Pin Current
VS = 5V, VSHDN = 0.3V
VS = 3V, VSHDN = 0.3V
l
l
160
110
400
350
μA
μA
Shutdown Output Leakage Current
VSHDN = 0.3V
l
1
VL
SHDN Pin Input Voltage Low
VH
SHDN Pin Input Voltage High
l
l
μA
0.3
V + – 0.5
V
V
tON
Turn-On Time
VSHDN = 0.3V to 4.5V, RL = 100Ω
l
80
ns
tOFF
Turn-Off Time
VSHDN = 4.5V to 0.3V, RL = 100Ω
l
50
ns
GBW
Gain-Bandwidth Product
Frequency = 6MHz
l
300
MHz
SR
Slew Rate
VS = 5V, AV = –1, RL= 1k, VO = 4V
l
100
V/μs
FPBW
Full-Power Bandwidth
VS = 5V, VO = 4VP-P
l
8
MHz
18067fc
5
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the –40°C < TA < 85°C
temperature range. VS = 5V, 0V; VS = 3V, 0V; VSHDN = open; VCM = VOUT = half supply, unless otherwise noted. (Note 5)
SYMBOL
PARAMETER
CONDITIONS
TYP
MAX
UNITS
VOS
Input Offset Voltage
VCM = V +
VCM = V –
VCM = V + (LT1806 SOT-23)
VCM = V – (LT1806 SOT-23)
l
l
l
l
200
200
200
200
800
800
950
950
μV
μV
μV
μV
VOS TC
Input Offset Voltage Drift (Note 8)
VCM = V +
VCM = V –
l
l
1.5
1.5
5
5
ΔVOS
Input Offset Voltage Shift
VCM = V – to V +
VCM = V – to V + (LT1806 SOT-23)
l
l
100
100
800
950
μV
μV
l
200
1400
μV
1
–5
6
μA
μA
Input Offset Voltage Match (Channel-to-Channel) VCM = V –, VCM = V+
(Note 10)
IB
ΔIB
MIN
μV/°C
μV/°C
VCM = V + – 0.2V
VCM = V – + 0.4V
l
l
Input Bias Current Shift
VCM = V – + 0.4V to V+ – 0.2V
l
6
22
μA
Input Bias Current Match (Channel-to-Channel)
(Note 10)
VCM = V + – 0.2V
VCM = V – + 0.4V
VCM = V + – 0.2V
VCM = V – + 0.4V
VCM = V – + 0.4V to V + – 0.2V
l
l
0.02
0.05
1.8
4
μA
μA
l
l
0.02
0.05
0.9
2.1
μA
μA
l
0.07
3
μA
Input Bias Current
–16
IOS
Input Offset Current
ΔIOS
Input Offset Current Shift
AVOL
Large-Signal Voltage Gain
VS = 5V, VO = 0.5V to 4.5V, RL = 1k to VS/2
VS = 5V, VO = 1V to 4V, RL = 100Ω to VS/2
VS = 3V, VO = 0.5V to 2.5V, RL = 1k to VS/2
l
l
l
50
6
35
140
16
100
V/mV
V/mV
V/mV
CMRR
Common Mode Rejection Ratio
VS = 5V, VCM = V – to V+
VS = 3V, VCM = V – to V+
l
l
75
71
94
89
dB
dB
CMRR Match (Channel-to-Channel) (Note 10)
VS = 5V, VCM = V – to V+
VS = 3V, VCM = V – to V+
l
l
69
65
94
89
dB
dB
Input Common Mode Range
l
V–
86
105
dB
80
105
dB
V+
V
Power Supply Rejection Ratio
VS = 2.5V to 10V, VCM = 0V
l
PSRR Match (Channel-to-Channel) (Note 10)
VS = 2.5V to 10V, VCM = 0V
l
Minimum Supply Voltage (Note 6)
VCM = VO = 0.5V
l
2.3
2.5
V
VOL
Output Voltage Swing Low (Note 7)
No Load
ISINK = 5mA
ISINK = 20mA
l
l
l
15
65
170
70
150
400
mV
mV
mV
VOH
Output Voltage Swing High (Note 7)
No Load
ISOURCE = 5mA
ISOURCE = 20mA
l
l
l
30
110
350
130
240
700
mV
mV
mV
ISC
Short-Circuit Current
VS = 5V
VS = 3V
l
l
IS
Supply Current per Amplifier
PSRR
Disable Supply Current
VS = 5V, VSHDN = 0.3V
VS = 3V, VSHDN = 0.3V
±22
±20
±45
±40
mA
mA
l
11
16
mA
l
l
0.4
0.3
1.2
1
mA
mA
18067fc
6
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the –40°C < TA < 85°C
temperature range. VS = 5V, 0V; VS = 3V, 0V; VSHDN = open; VCM = VOUT = half supply, unless otherwise noted. (Note 5)
SYMBOL
PARAMETER
CONDITIONS
TYP
MAX
UNITS
ISHDN
SHDN Pin Current
VS = 5V, VSHDN = 0.3V
VS = 3V, VSHDN = 0.3V
l
l
MIN
170
120
450
400
μA
μA
Shutdown Output Leakage Current
VSHDN = 0.3V
l
1.2
μA
VL
SHDN Pin Input Voltage Low
VH
SHDN Pin Input Voltage High
tON
Turn-On Time
VSHDN = 0.3V to 4.5V, RL = 100Ω
l
80
ns
tOFF
Turn-Off Time
VSHDN = 4.5V to 0.3V, RL = 100Ω
l
50
ns
l
l
0.3
V + – 0.5
V
V
GBW
Gain-Bandwidth Product
Frequency = 6MHz
l
250
MHz
SR
Slew Rate
VS = 5V, AV = –1, RL= 1k, VO = 4V
l
80
V/μs
FPBW
Full-Power Bandwidth
VS = 5V, VO = 4VP-P
l
6
MHz
TA = 25°C. VS = ±5V, VSHDN = open; VCM = 0V, VOUT = 0V, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
VOS
Input Offset Voltage
ΔVOS
Input Offset Voltage Shift
VCM = V +
VCM = V –
VCM = V + (LT1806 SOT-23)
VCM = V – (LT1806 SOT-23)
VCM = V – to V +
VCM = V – to V + (LT1806 SOT-23)
VCM = V –, VCM = V+
Input Offset Voltage Match (Channel-to-Channel)
(Note 10)
IB
Input Bias Current
VCM = V +
VCM = V – + 0.2V
MIN
–14
TYP
MAX
UNITS
100
100
100
100
700
700
750
750
μV
μV
μV
μV
50
50
700
750
μV
μV
200
1200
μV
1
–5
5
μA
μA
Input Bias Current Shift
VCM = V – + 0.2V to V +
6
19
μA
Input Bias Current Match (Channel-to-Channel)
(Note 10)
VCM = V +
VCM = V – + 0.2V
0.03
0.05
1.4
3.2
μA
μA
IOS
Input Offset Current
VCM = V +
VCM = V – + 0.2V
0.03
0.04
0.7
1.6
μA
μA
ΔIOS
Input Offset Current Shift
VCM = V – + 0.2V to V +
0.07
2.3
Input Noise Voltage
0.1Hz to 10Hz
800
nVp-p
en
Input Noise Voltage Density
f = 10kHz
3.5
nV/√Hz
in
Input Noise Current Density
f = 10kHz
1.5
pA/√Hz
CIN
Input Capacitance
f = 10kHz
2
AVOL
Large-Signal Voltage Gain
VO = –4V to 4V, RL = 1k
VO = –2.5V to 2.5V, RL = 100Ω
ΔIB
100
10
300
27
μA
pF
V/mV
V/mV
18067fc
7
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
TA = 25°C. VS = ±5V, VSHDN = open; VCM = 0V, VOUT = 0V, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
CMRR
Common Mode Rejection Ratio
VCM = V – to V +
83
106
= V – to V +
77
106
CMRR Match (Channel-to-Channel) (Note 10)
VCM
V–
Input Common Mode Range
MAX
UNITS
dB
dB
V+
V
Power Supply Rejection Ratio
V + = 2.5V to 10V, V – = 0V
90
105
dB
PSRR Match (Channel-to-Channel) (Note 10)
V + = 2.5V to 10V, V – = 0V
84
105
dB
VOL
Output Voltage Swing Low (Note 7)
No Load
ISINK = 5mA
ISINK = 25mA
14
55
180
60
140
450
mV
mV
mV
VOH
Output Voltage Swing High (Note 7)
No Load
ISOURCE = 5mA
ISOURCE = 25mA
20
90
360
70
200
700
mV
mV
mV
ISC
Short-Circuit Current
IS
Supply Current per Amplifier
PSRR
ISHDN
±40
±85
mA
11
16
mA
Disable Supply Current
VSHDN = 0.3V
0.4
1.2
mA
SHDN Pin Current
VSHDN = 0.3V
150
350
μA
Shutdown Output Leakage Current
VSHDN = 0.3V
0.3
75
μA
0.3
V
VL
SHDN Pin Input Voltage Low
VH
SHDN Pin Input Voltage High
tON
Turn-On Time
VSHDN = 0.3V to 4.5V, RL = 100Ω
80
ns
tOFF
Turn-Off Time
VSHDN = 4.5V to 0.3V, RL = 100Ω
50
ns
GBW
Gain-Bandwidth Product
Frequency = 6MHz
170
325
MHz
SR
Slew Rate
AV = –1, RL = 1k, VO = ±4V, Measured at VO = ±3V
70
140
V/μs
V + – 0.5
V
FPBW
Full-Power Bandwidth
VO = 8VP-P
5.5
MHz
HD
Harmonic Distortion
AV = 1, RL = 1k, VO = 2VP-P , fC = 5MHz
– 80
dBc
tS
Settling Time
0.01%, VSTEP = 8V, AV = 1, RL = 1k
120
ns
ΔG
Differential Gain (NTSC)
AV = 2, RL = 150
0.01
%
Δθ
Differential Phase (NTSC)
AV = 2, RL = 150
0.01
Deg
18067fc
8
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the 0°C < TA < 70°C
temperature range. VS = ±5V, VSHDN = open; VCM = 0V, VOUT = 0V, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
TYP
MAX
UNITS
VOS
Input Offset Voltage
VCM = V +
VCM = V –
VCM = V + (LT1806 SOT-23)
VCM = V – (LT1806 SOT-23)
l
l
l
l
200
200
200
200
800
800
900
900
μV
μV
μV
μV
VOS TC
Input Offset Voltage Drift (Note 8)
VCM = V +
VCM = V –
l
l
1.5
1.5
5
5
ΔVOS
Input Offset Voltage Shift
VCM = V – to V +
VCM = V – to V + (LT1806 SOT-23)
l
l
100
100
800
900
μV
μV
l
300
1400
μV
1
–6
6
μA
μA
Input Offset Voltage Match (Channel-to-Channel) VCM = V –, VCM = V +
(Note 10)
IB
ΔIB
MIN
μV/°C
μV/°C
VCM = V + – 0.2V
VCM = V – + 0.4V
l
l
Input Bias Current Shift
VCM = V – + 0.4V to V + – 0.2V
l
7
21
μA
Input Bias Current Match (Channel-to-Channel)
(Note 10)
VCM = V + – 0.2V
VCM = V – + 0.4V
VCM = V + – 0.2V
VCM = V – + 0.4V
VCM = V – + 0.4V to V + – 0.2V
l
l
0.03
0.04
1.8
3.8
μA
μA
l
l
0.03
0.04
0.9
1.9
μA
μA
l
0.07
2.8
μA
Input Bias Current
–15
IOS
Input Offset Current
ΔIOS
Input Offset Current Shift
AVOL
Large-Signal Voltage Gain
VO = –4V to 4V, RL = 1k
VO = –2.5V to 2.5V, RL = 100Ω
l
l
80
8
250
25
V/mV
V/mV
CMRR
Common Mode Rejection Ratio
VCM = V – to V +
l
81
100
dB
= V – to V +
l
75
100
l
V–
CMRR Match (Channel-to-Channel) (Note 10)
VCM
Input Common Mode Range
dB
V+
V
Power Supply Rejection Ratio
V + = 2.5V to 10V, V – = 0V
l
88
105
dB
PSRR Match (Channel-to-Channel) (Note 10)
V + = 2.5V to 10V, V – = 0V
l
82
106
dB
VOL
Output Voltage Swing Low (Note 7)
No Load
ISINK = 5mA
ISINK = 25mA
l
l
l
18
60
185
80
160
500
mV
mV
mV
VOH
Output Voltage Swing High (Note 7)
No Load
ISOURCE = 5mA
ISOURCE = 25mA
l
l
l
40
110
360
140
240
750
mV
mV
mV
ISC
Short-Circuit Current
l
IS
Supply Current per Amplifier
l
14
20
mA
mA
PSRR
ISHDN
±35
±75
mA
Disable Supply Current
VSHDN = 0.3V
l
0.4
1.4
SHDN Pin Current
VSHDN = 0.3V
l
160
400
Shutdown Output Leakage Current
VSHDN = 0.3V
l
1
μA
μA
VL
SHDN Pin Input Voltage Low
VH
SHDN Pin Input Voltage High
tON
Turn-On Time
VSHDN = 0.3V to 4.5V, RL = 100Ω
l
tOFF
Turn-Off Time
VSHDN = 4.5V to 0.3V, RL = 100Ω
l
50
ns
GBW
Gain-Bandwidth Product
Frequency = 6MHz
l
150
300
MHz
SR
Slew Rate
AV = –1, RL = 1k, VO = ± 4V,
Measure at VO = ±3V
l
60
120
V/μs
FPBW
Full-Power Bandwidth
VO = 8VP-P
l
4.5
MHz
l
l
0.3
V + – 0.5
V
V
80
ns
18067fc
9
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the −40°C < TA < 85°C
temperature range. VS = ±5V, VSHDN = open; VCM = 0V, VOUT = 0V, unless otherwise noted. (Note 5)
SYMBOL
PARAMETER
CONDITIONS
TYP
MAX
UNITS
VOS
Input Offset Voltage
VCM = V +
VCM = V –
VCM = V + (LT1806 SOT-23)
VCM = V – (LT1806 SOT-23)
l
l
l
l
200
200
200
200
900
900
975
975
μV
μV
μV
μV
VOS TC
Input Offset Voltage Drift (Note 8)
VCM = V +
VCM = V –
l
l
1.5
1.5
5
5
ΔVOS
Input Offset Voltage Shift
VCM = V – to V +
VCM = V – to V + (LT1806 SOT-23)
l
l
100
100
900
975
μV
μV
l
300
1600
μV
1.2
–5
7
μA
μA
Input Offset Voltage Match (Channel-to-Channel) VCM = V –, VCM = V +
(Note 10)
IB
ΔIB
MIN
μV/°C
μV/°C
VCM = V + – 0.2V
VCM = V – + 0.4V
l
l
Input Bias Current Shift
VCM = V – + 0.4V to V + – 0.2V
l
6
23
μA
Input Bias Current Match (Channel-to-Channel)
(Note 10)
VCM = V + – 0.2V
VCM = V – + 0.4V
VCM = V + – 0.2V
VCM = V – + 0.4V
VCM = V – + 0.4V to V + – 0.2V
l
l
0.03
0.04
2
4.5
μA
μA
l
l
0.03
0.04
1.0
2.2
μA
μA
l
0.07
3.2
μA
Input Bias Current
–16
IOS
Input Offset Current
ΔIOS
Input Offset Current Shift
AVOL
Large-Signal Voltage Gain
VO = – 4V to 4V, RL = 1k
VO = –2V to 2V, RL =100Ω
l
l
60
7
175
17
V/mV
V/mV
CMRR
Common Mode Rejection Ratio
VCM = V – to V+
l
80
100
dB
= V – to V+
l
74
100
l
V–
l
86
105
dB
l
80
105
dB
CMRR Match (Channel-to-Channel) (Note 10)
VCM
Input Common Mode Range
PSRR
Power Supply Rejection Ratio
V + = 2.5V to 10V, V – = 0V
PSRR Match (Channel-to-Channel) (Note 10)
dB
V+
V
VOL
Output Voltage Swing Low (Note 7)
No Load
ISINK = 5mA
ISINK = 20mA
l
l
l
20
65
200
100
170
500
mV
mV
mV
VOH
Output Voltage Swing High (Note 7)
No Load
ISOURCE = 5mA
ISOURCE = 20mA
l
l
l
50
115
360
160
260
700
mV
mV
mV
ISC
Short-Circuit Current
l
IS
Supply Current per Amplifier
l
15
22
mA
mA
ISHDN
±25
±55
mA
Disable Supply Current
VSHDN = 0.3V
l
0.45
1.5
SHDN Pin Current
VSHDN = 0.3V
l
170
400
Shutdown Output Leakage Current
VSHDN = 0.3V
l
1.2
VL
SHDN Pin Input Voltage Low
VH
SHDN Pin Input Voltage High
tON
Turn-On Time
l
l
VSHDN = 0.3V to 4.5V, RL = 100Ω
l
0.3
V + – 0.5
μA
μA
V
V
80
ns
18067fc
10
LT1806/LT1807
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the −40°C < TA < 85°C
temperature range. VS = ±5V, VSHDN = open; VCM = 0V, VOUT = 0V, unless otherwise noted. (Note 5)
SYMBOL
PARAMETER
CONDITIONS
tOFF
Turn-Off Time
VSHDN = 4.5V to 0.3V, RL = 100Ω
l
GBW
Gain-Bandwidth Product
Frequency = 6MHz
l
SR
Slew Rate
A V = –1, RL = 1k, VO = ±4V,
Measure at VO = ±3V
l
FPBW
Full-Power Bandwidth
VO = 8VP-P
l
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: The inputs are protected by back-to-back diodes. If the differential
input voltage exceeds 1.4V, the input current should be limited to less
than 10mA. This parameter is guaranteed to meet specified performance
through design and/or characterization. It is not 100% tested.
Note 3: A heat sink may be required to keep the junction temperature below
the absolute maximum rating when the output is shorted indefinitely.
Note 4: The LT1806C/LT1806I and LT1807C/LT1807I are guaranteed
functional over the temperature range of –40°C and 85°C.
Note 5: The LT1806C/LT1807C are guaranteed to meet specified
performance from 0°C to 70°C. The LT1806C/LT1807C are designed,
MIN
TYP
MAX
UNITS
50
ns
125
290
MHz
50
100
V/μs
4
MHz
characterized and expected to meet specified performance from –40°C to
85°C but are not tested or QA sampled at these temperatures. The LT1806I/
LT1807I are guaranteed to meet specified performance from –40°C to 85°C.
Note 6: Minimum supply voltage is guaranteed by power supply rejection
ratio test.
Note 7: Output voltage swings are measured between the output and
power supply rails.
Note 8: This parameter is not 100% tested.
Note 9: Thermal resistance varies depending upon the amount of PC board
metal attached to the V – pin of the device. θJA is specified for a certain
amount of 2oz copper metal trace connecting to the V – pin as described in
the thermal resistance tables in the Applications Information section.
Note 10: Matching parameters are the difference between the two
amplifiers of the LT1807.
TYPICAL PERFORMANCE CHARACTERISTICS
VOS Distribution, VCM = 0V
(PNP Stage)
50
VS = 5V, 0V
VCM = 0V
30
20
10
0
–500
VS = 5V, 0V
VCM = 5V
40
PERCENT OF UNITS (%)
PERCENT OF UNITS (%)
40
ΔVOS Shift for VCM = 0V to 5V
50
30
20
10
–300
100
300
–100
INPUT OFFSET VOLTAGE (μV)
500
18067 G01
0
–500
VS = 5V, 0V
40
PERCENT OF UNITS (%)
50
VOS Distribution, VCM = 5V
(NPN Stage)
30
20
10
–300
100
300
–100
INPUT OFFSET VOLTAGE (μV)
500
18067 G02
0
–500
–300
100
300
–100
INPUT OFFSET VOLTAGE (μV)
500
18067 G03
18067fc
11
LT1806/LT1807
TYPICAL PERFORMANCE CHARACTERISTICS
Supply Current per Amp
vs Supply Voltage
Offset Voltage
vs Input Common Mode
5
500
400
300
OFFSET VOLTAGE (μV)
15
TA = 125°C
10
TA = 25°C
TA = –55°C
200
TA = 25°C
100
0
–100
TA = –55°C
–200
–300
0
0
1
2
3 4 5 6 7 8 9 10 11 12
TOTAL SUPPLY VOLTAGE (V)
–500
10
OUTPUT SATURATION VOLTAGE (V)
–2
–3
PNP ACTIVE
VS = 5V, 0V
VCM = 0V
–4
–5
–6
–7
–8
–50 –35 –20 –5 10 25 40 55
TEMPERATURE (°C)
70
85
10
1
0.1
TA = 125°C
0.01
TA = –55°C
0.001
0.01
TA = 25°C
0.1
1
10
LOAD CURRENT (mA)
OUTPUT SHORT-CIRCUIT CURRENT (mA)
0.6
0.4
TA = 125°C
0
–0.2
–0.4
TA = 25°C
–0.6
TA = –55°C
–0.8
1.0 1.5
2.0 2.5 3.0 3.5 4.0 4.5
TOTAL SUPPLY VOLTAGE (V)
5.0
18067 G10
TA = 125°C
TA = 25°C
0.01
TA = –55°C
0.1
1
10
LOAD CURRENT (mA)
18067 G09
18
100
100
Supply Current
vs SHDN Pin Voltage
TA = –55°C
16
TA = 125°C
14
VS = 5V, 0V
80
TA = 25°C
60
“SINKING”
40
20
0
–20
“SOURCING”
–40
TA = –55°C
–60
–80 TA = 25°C
TA = 125°C
1.5
4.0 4.5
2.0 2.5 3.0 3.5
POWER SUPPLY VOLTAGE (pV)
TA = 125°C
12
TA = 25°C
10
8
6
TA = –55°C
4
2
–100
–1.0
0.1
0.001
0.01
120
0.2
1
Output Short-Circuit Current
vs Power Supply Voltage
1.0
CHANGE IN OFFSET VOLTAGE (mV)
100
VS = p5V
18067 G08
Minimum Supply Voltage
6
Output Saturation Voltage
vs Load Current (Output High)
VS = p5V
18067 G07
0.8
4
5
1
2
3
COMMON MODE VOLTAGE (V)
18067 G06
SUPPLY CURRENT (mA)
INPUT BIAS (μA)
–1
0
–1
5
Output Saturation Voltage
vs Load Current (Output Low)
2
NPN ACTIVE
VS = 5V, 0V
VCM = 5V
TA = 125°C
TA = 25°C
TA = –55°C
18067 G05
Input Bias Current vs Temperature
0
–5
–10
1
3
4
2
INPUT COMMON MODE VOLTAGE (V)
0
18067 G04
1
TA = 125°C
TA = 25°C
TA = –55°C
0
VS = 5V, 0V
TYPICAL PART
–400
OUTPUT SATURATION VOLTAGE (V)
5
VS = 5V, 0V
TA = 125°C
INPUT BIAS CURRENT (μA)
20
SUPPLY CURRENT (mA)
Input Bias Current
vs Common Mode Voltage
5.0
18067 G11
0
0
1
4
3
2
SHDN PIN VOLTAGE (V)
5
18067 G12
18067fc
12
LT1806/LT1807
TYPICAL PERFORMANCE CHARACTERISTICS
SHDN Pin Current
vs SHDN Pin Voltage
20
VS = 5V, 0V
0
Open-Loop Gain
300
–80
TA = 25°C
–100
TA = –55°C
–120
200
INPUT VOLTAGE (μV)
TA = 125°C
–60
RL = 1k
100
0
–100
RL = 100Ω
–200
200
0
–100
–300
–400
–400
–180
–500
–500
3
4
2
SHDN PIN VOLTAGE (V)
0
5
0.5
1.5
2.0
1.0
OUTPUT VOLTAGE (V)
Warm-Up Drift
vs Time (LT1806S8)
Offset Voltage vs Output Current
300
OFFSET VOLTAGE (mV)
200
RL = 1k
RL = 100Ω
–200
40
TA = 125°C
1.5
100
45
VS = p5V
2.0
OFFSET VOLTAGE DRIFT (μV)
2.5
VS = p5V
400
–100
18067 G15
18067 G14
Open-Loop Gain
0
0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
OUTPUT VOLTAGE (V)
3.0
2.5
18067 G13
500
TA = 25°C
1.0
0.5
0
TA = –55°C
–0.5
–1.0
30
25
20
10
–400
–2.0
5
–2.5
–100 –80 –60 –40 –20 0 20 40 60 80 100
OUTPUT CURRENT (mA)
0
4
5
18067 G16
12
PNP ACTIVE
VCM = 2.5V
4
800
6
0
0
100
18067 G19
PNP ACTIVE
VCM = 2.5V
4
2
1
10
FREQUENCY (kHz)
600
8
2
0.1
40 60 80 100 120 140 160
TIME AFTER POWER-UP (SEC)
1000
VS = 5V, 0V
OUTPUT VOLTAGE (nV)
NOISE CURRENT (pA/•Hz)
NOISE VOLTAGE (nV/•Hz)
6
20
0.1Hz to 10Hz
Output Voltage Noise
10
10
NPN ACTIVE
VCM = 4.5V
0
18067 G18
Input Noise Current vs Frequency
VS = 5V, 0V
8
VS = p1.5V
18067 G17
Input Noise Voltage vs Frequency
12
VS = p2.5V
15
–1.5
–5 –4 –3 –2 –1 0 1 2 3
OUTPUT VOLTAGE (V)
VS = p5V
35
–300
–500
RL = 100Ω
–200
–160
1
RL = 1k
100
–300
0
VS = 5V, 0V
RL TO GND
400
300
–20
–40
–140
INPUT VOLTAGE (μV)
500
VS = 3V, 0V
RL TO GND
400
INPUT VOLTAGE (μV)
SHDN PIN CURRENT (μA)
Open-Loop Gain
500
400
200
0
–200
–400
–600
NPN ACTIVE
VCM = 4.5V
0.1
–800
1
10
FREQUENCY (kHz)
100
18067 G19
–1000
0
1
2
3
4 5 6
TIME (SEC)
7
8
9
10
18067 G21
18067fc
13
LT1806/LT1807
TYPICAL PERFORMANCE CHARACTERISTICS
55
50
50
45
35
30
GAIN BANDWIDTH PRODUCT
350
30
350
250
250
1
2 3 4 5 6 7 8
TOTAL SUPPLY VOLTAGE (V)
9
GBW PRODUCT
VS = p5V
400
300
0
Gain and Phase vs Frequency
Gain vs Frequency (AV = 2)
CL = 10pF
24 RL = 100Ω
135
18
15
90
12
12
6
9
45
30
PHASE
VS = 3V
0
GAIN (dB)
180
60
PHASE
VS = p5V
CL = 10pF
18 RL = 100Ω
0
VS = p5V
–45
0
–90
–12
–135
–18
–3
–180
–24
–6
–20 CL = 5pF
RL = 100Ω
–30
0.1
1
10
FREQUENCY (MHz)
GAIN
VS = 3V
–225
500
100
VS = 3V
–36
0.1
1
10
FREQUENCY (MHz)
100
100
COMMON MODE REJECTION RATIO (dB)
100
10
1
AV = 2
AV = 10
AV = 1
0.1
0.01
0.001
100k
1M
10M
FREQUENCY (Hz)
100M
–9
0.1
500
500M
18067 G28
1
10
FREQUENCY (MHz)
100
Power Supply Rejection Ratio
vs Frequency
VS = 5V, 0V
90
80
70
60
50
40
30
20
10
0
0.01
0.1
1
10
FREQUENCY (MHz)
100
500
18067 G27
Common Mode Rejection Ratio
vs Frequency
Output Impedance vs Frequency
VS = 5V, 0V
VS = 3V
18067 G26
18067 G25
600
3
0
500
18067 G29
100
POWER SUPPLY REJECTION RATIO (dB)
–10
–6
VS = p5V
6
10
GAIN
VS = p5V
5 25 45 65 85 105 125
TEMPERATURE (°C)
18067 G24
21
PHASE (DEG)
GAIN (dB)
75
–55 –35 –15
Gain vs Frequency (AV = 1)
50
OUTPUT IMPEDANCE (Ω)
VS = p2.5V
30
225
20
125
18067 G23
70
40
VS = p5V
100
5 25 45 65 85 105 125
TEMPERATURE (°C)
18067 G22
AV = –1
RF = RG = 1k
RL = 1k
150
GBW PRODUCT
VS = 3V
200
–55 –35 –15
10
40
35
300
200
45
PHASE MARGIN
VS = 3V
GAIN (dB)
400
PHASE MARGIN
VS = p5V
175
PHASE MARGIN (DEG)
40
PHASE MARGIN (DEG)
GAIN BANDWIDTH (MHz)
PHASE MARGIN
Slew Rate vs Temperature
55
GAIN BANDWIDTH (MHz)
TA = 25°C
Gain Bandwidth and Phase Margin
vs Temperature
SLEW RATE (μV/μs)
Gain Bandwidth and Phase Margin
vs Supply Voltage
VS = 5V, 0V
TA = 25°C
90
80
70
POSITIVE SUPPLY
60
50
40
NEGATIVE SUPPLY
30
20
10
0
0.001
0.01
0.1
1
FREQUENCY (MHz)
10
100
18067 G30
18067fc
14
LT1806/LT1807
TYPICAL PERFORMANCE CHARACTERISTICS
Series Output Resistor
vs Capacitive Load
Series Output Resistor
vs Capacitive Load
50
VS = 5V, 0V
45 AV = 2
ROS = 20Ω
30
25
20
15
10
35
25
20
ROS = 20Ω
15
0
100
CAPACITIVE LOAD (pF)
1000
100
CAPACITIVE LOAD (pF)
10
1000
18067 G31
Distortion vs Frequency
Distortion vs Frequency
–40
AV = 1
VOUT = 2VP-P
VS = p5V
–50
–70
RL = 100Ω, 2ND
RL = 100Ω, 3RD
RL = 1k, 3RD
–90
RL = 100Ω, 2ND
–80
RL = 1k, 2ND
–90
10
1
FREQUENCY (MHz)
10
4.6
–60
RL = 100Ω, 2ND
RL = 1k, 2ND
–80
RL = 1k, 3RD
–90
–100
–110
–120
0.3
RL = 1k, 3RD
–120
0.3
30
1
10
30
FREQUENCY (MHz)
18067 G36
Maximum Undistorted Output
Signal vs Frequency
AV = 2
VOUT = 2VP-P
VS = 5V, 0V RL = 100Ω, 3RD
–70
RL = 1k, 2ND
–90
18067 G35
Distortion vs Frequency
–50
RL = 100Ω, 2ND
FREQUENCY (MHz)
18067 G34
–40
–80
–110
–110
0.3
30
RL = 100Ω, 3RD
–70
–100
RL = 1k, 3RD
–100
1
AV = 2
VOUT = 2VP-P
VS = p5V
–60
RL = 100Ω, 3RD
–70
RL = 1k, 2ND
–100
–110
0.3
–50
1
10
30
FREQUENCY (MHz)
18067 G37
OUTPUT VOLTAGE SWING (VP-P)
–80
Distortion vs Frequency
–40
AV = 1
VOUT = 2VP-P
VS = 5V, 0V
–60
DISTORTION (dBc)
–60
DISTORTION (dBc)
DISTORTION (dBc)
–50
18067 G33
18067 G32
DISTORTION (dBc)
10
–40
VS = p5V
20ns/DIV
VOUT = p4V
RL = 500Ω
tS = 120ns (SETTLING TIME)
ROS = RL = 50Ω
5
0
OUTPUT
SETTLING
RESOLUTION
(2mV/DIV)
ROS = 10Ω
30
10
ROS = RL = 50Ω
5
INPUT SIGNAL
GENERATION
(2V/DIV)
40
ROS = 10Ω
OVERSHOOT (%)
OVERSHOOT (%)
40
35
0.01% Settling Time
50
VS = 5V, 0V
45 AV = 1
VS = 5V, 0V
4.5
AV = –1
4.4
4.3
AV = 2
4.2
4.1
4.0
3.9
0.1
1
10
FREQUENCY (MHz)
100
18067 G38
18067fc
15
LT1806/LT1807
TYPICAL PERFORMANCE CHARACTERISTICS
±5V Large-Signal Response
±5V Small-Signal Response
0V
0V
VS = p5V
40ns/DIV
FREQ = 1.92MHz
AV = 1
RL = 1k
VS = p5V
20ns/DIV
FREQ = 4.48MHz
AV = 1
RL = 1k
18067 G39
5V Large-Signal Response
18067 G40
5V Small-Signal Response
0V
0.5V
VS = 5V, 0V
20ns/DIV
FREQ = 5.29MHz
AV = 1
RL = 1k
VS = 5V, 0V
AV = 1
RL = 1k
18067 G41
Output Overdriven Recovery
10ns/DIV
18067 G42
Shutdown Response
VIN
1V/DIV
VSHDN
2V/DIV
0V
VOUT
2V/DIV
0V
0V
VOUT
2V/DIV
0V
VS = 5V, 0V
AV = 2
RL = 1k
100ns/DIV
18067 G43
VS = 5V, 0V
AV = 2
RL = 100Ω
20ns/DIV
18067 G44
18067fc
16
LT1806/LT1807
APPLICATIONS INFORMATION
Rail-to-Rail Characteristics
The LT1806/LT1807 have input and output signal range that
covers from negative power supply to positive power supply. Figure 1 depicts a simplified schematic of the amplifier.
The input stage is comprised of two differential amplifiers,
a PNP stage Q1/Q2 and a NPN stage Q3/Q4 that are active
over different ranges of common mode input voltage. The
PNP differential pair is active between the negative supply
to approximately 1.5V below the positive supply. As the
input voltage moves closer toward the positive supply, the
transistor Q5 will steer the tail current I1 to the current
mirror Q6/Q7, activating the NPN differential pair. The PNP
pair becomes inactive for the rest of the input common
mode range up to the positive supply.
A pair of complementary common emitter stages Q14/Q15
that enable the output to swing from rail to rail constructs
the output stage. The capacitors C1 and C2 form the
local feedback loops that lower the output impedance at
high frequency. These devices are fabricated on Linear
Technology’s proprietary high speed complementary
bipolar process.
Power Dissipation
The LT1806/LT1807 amplifiers combine high speed with
large output current in a small package, so there is a need
to ensure that the die’s junction temperature does not
exceed 150°C. The LT1806 is housed in an SO-8 package
or a 6-lead SOT-23 package and the LT1807 is in an SO-8
V+
R6
40k
R3
Q16
V+
Q17
V+
ESDD5
D9
SHDN
R7
100k
R4
R5
V–
ESDD1
+
D1
ESDD2
Q12
Q11
I1
Q13
+IN
D6
D8
D5
D7
ESDD6
V–
–IN
Q5
I2
CC
V–
OUT
Q1 Q2
D3
ESDD3
V–
+
VBIAS
Q4 Q3
ESDD4
BIAS
GENERATION
D2
Q15
C2
BUFFER
AND
OUTPUT BIAS
Q10
V+
D4
Q9
Q8
C1
Q7
Q14
Q6
R1
V–
R2
18067 F01
Figure 1. LT1806 Simplified Schematic Diagram
18067fc
17
LT1806/LT1807
APPLICATIONS INFORMATION
or 8-lead MSOP package. All packages have the V – supply pin fused to the lead frame to enhance the thermal
conductance when connecting to a ground plane or a
large metal trace. Metal trace and plated through-holes
can be used to spread the heat generated by the device
to the backside of the PC board. For example, on a 3/32"
FR-4 board with 2oz copper, a total of 660 square millimeters connects to Pin 4 of LT1807 in an SO-8 package
(330 square millimeters on each side of the PC board) will
bring the thermal resistance, θJA , to about 85°C/W. Without
extra metal trace beside the power line connecting to the
V – pin to provide a heat sink, the thermal resistance will be
around 105°C/W. More information on thermal resistance
for all packages with various metal areas connecting to
the V – pin is provided in Tables 1, 2 and 3.
Table 1. LT1806 6-Lead SOT-23 Package
COPPER AREA
TOPSIDE (mm2)
BOARD AREA
(mm2)
THERMAL RESISTANCE
(JUNCTION-TO-AMBIENT)
270
2500
135°C/W
100
2500
145°C/W
20
2500
160°C/W
0
2500
200°C/W
Device is mounted on topside.
Table 2. LT1806/LT1807 SO-8 Package
COPPER AREA
TOPSIDE
(mm2)
BACKSIDE
(mm2)
BOARD AREA
(mm2)
THERMAL RESISTANCE
(JUNCTION-TO-AMBIENT)
1100
1100
2500
65°C/W
330
330
2500
85°C/W
35
35
2500
95°C/W
35
0
2500
100°C/W
0
0
2500
105°C/W
Table 3. LT1807 8-Lead MSOP Package
COPPER AREA
TOPSIDE
(mm2)
BACKSIDE
(mm2)
BOARD AREA
(mm2)
THERMAL RESISTANCE
(JUNCTION-TO-AMBIENT)
540
540
2500
110°C/W
100
100
2500
120°C/W
100
0
2500
130°C/W
30
0
2500
135°C/W
0
0
2500
140°C/W
Device is mounted on topside.
Junction temperature TJ is calculated from the ambient
temperature TA and power dissipation PD as follows:
TJ = TA + (PD • θJA)
The power dissipation in the IC is the function of the supply
voltage, output voltage and the load resistance. For a given
supply voltage, the worst-case power dissipation PD(MAX)
occurs at the maximum quiescent supply current and at
the output voltage which is half of either supply voltage
(or the maximum swing if it is less than 1/2 the supply
voltage). PD(MAX) is given by:
PD(MAX) = (VS • IS(MAX)) + (VS/2)2/RL
Example: An LT1807 in SO-8 mounted on a 2500mm2
area of PC board without any extra heat spreading plane
connected to its V – pin has a thermal resistance of
105°C/W, θJA. Operating on ±5V supplies with both amplifiers simultaneously driving 50Ω loads, the worst-case
power dissipation is given by:
PD(MAX) = 2 • (10 • 14mA) + 2 • (2.5)2/50
= 0.28 + 0.25 = 0.53W
Device is mounted on topside.
18067fc
18
LT1806/LT1807
APPLICATIONS INFORMATION
The maximum ambient temperature that the part is
allowed to operate is:
TA = TJ – (PD(MAX) • 105°C/W)
= 150°C – (0.53W • 105°C/W) = 94°C
To operate the device at higher ambient temperature,
connect more metal area to the V – pin to reduce the thermal
resistance of the package as indicated in Table 2.
Input Offset Voltage
The offset voltage will change depending upon which
input stage is active and the maximum offset voltage is
guaranteed to less than 550μV. To maintain the precision
characteristics of the amplifier, the change of VOS over the
entire input common mode range (CMRR) is limited to be
less than 550μV on a single 5V and 3V supply.
Input Bias Current
The input bias current polarity depends on a given input
common voltage at which the input stage is operating.
When the PNP input stage is active, the input bias currents
flow out of the input pins. When the NPN input stage is
activated, the input bias current flows into the input pins.
Because the input offset current is less than the input bias
current, matching the source resistances at the input pins
will reduce total offset error.
Output
The LT1806/LT1807 can deliver a large output current, so
the short-circuit current limit is set around 85mA to prevent
damage to the device. Attention must be paid to keep the
junction temperature of the IC below the absolute maximum
rating of 150°C (refer to the Power Dissipation section)
when the output is continuously short circuited. The output
of the amplifier has reverse-biased diodes connected to
each supply. If the output is forced beyond either supply,
unlimited current will flow through these diodes. If the
current is transient and limited to one hundred milliamps
or less, no damage to the device will occur.
Overdrive Protection
When the input voltage exceeds the power supplies, two
pairs of crossing diodes D1 to D4 will prevent the output
from reversing polarity. If the input voltage exceeds either
power supply by 700mV, diode D1/D2 or D3/D4 will turn
on to keep the output at the proper polarity. For the phase
reversal protection to perform properly, the input current
must be limited to less than 5mA. If the amplifier is severely
overdriven, an external resistor should be used to limit
the overdrive current.
18067fc
19
LT1806/LT1807
APPLICATIONS INFORMATION
The LT1806/LT1807’s input stages are also protected
against large differential input voltages of 1.4V or higher
by a pair of back-to-back diodes, D5/D8, that prevent
the emitter-base breakdown of the input transistors. The
current in these diodes should be limited to less than 10mA
when they are active. The worst-case differential input
voltage usually occurs when the input is driven while the
output is shorted to ground in a unity gain configuration.
In addition, the amplifier is protected against ESD strikes
up to 3kV on all pins by a pair of protection diodes, ESDD1
to ESDD6, on each pin that are connected to the power
supplies as shown in Figure 1.
Feedback Components
Capacitive Load
SHDN Pin
The LT1806/LT1807 are optimized for high bandwidth and
low distortion applications. They can drive a capacitive
load of about 20pF in a unity-gain configuration, and more
for higher gain. When driving a larger capacitive load, a
resistor of 10Ω to 50Ω should be connected between the
output and the capacitive load to avoid ringing or oscillation. The feedback should still be taken from the output so
that the resistor will isolate the capacitive load to ensure
stability. Graphs on capacitive loads indicate the transient
response of the amplifier when driving the capacitive load
with a specified series resistor.
The LT1806 has a SHDN pin to reduce the supply current
to less than 0.9mA. When the SHDN pin is pulled low, it
will generate a signal to power down the device. If the pin
is left unconnected, an internal pull-up resistor of 40k will
keep the part fully operating as shown in Figure 1. The
output will be high impedance during shutdown, and the
turn-on and turn-off time is less than 100ns. Because
the input is protected by a pair of back-to-back diodes,
the input signal will feed through to the output during
shutdown mode if the amplitude of signal between the
inputs is larger than 1.4V.
When feedback resistors are used to set up gain, care must
be taken to ensure that the pole formed by the feedback
resistors and the total capacitance at the inverting input
does not degrade stability. For instance, the LT1806/LT1807
in a noninverting gain of 2, set up with two 1k resistors
and a capacitance of 3pF (part plus PC board) will probably
ring in transient response. The pole is formed at 106MHz
that will reduce phase margin by 34 degrees when the
crossover frequency of the amplifier is around 70MHz. A
capacitor of 3pF or higher connected across the feedback
resistor will eliminate any ringing or oscillation.
18067fc
20
LT1806/LT1807
TYPICAL APPLICATIONS
Driving A/D Converter
The LT1806/LT1807 have 60ns settling time to 0.01% on
a 2V step signal, and 20Ω output impedance at 100MHz,
that makes them ideal for driving high speed A/D converters. With the rail-to-rail input and output, and low supply
voltage operation, the LT1806/LT1807 are also desirable
for single supply applications. As shown in the application
on the front page of this data sheet, the LT1807 drives a
10Msps, 12-bit, LTC1420 ADC in a gain of 20. Driving the
LTC1420 differentially will optimize the signal-to-noise
ratio, SNR, and the total harmonic distortion, THD, of the
A/D converter. The lowpass filter, R5, R6 and C3 reduce
noise or distortion products that might come from the input
signal. High quality capacitors and resistors, NPO chip
capacitor and metal film surface mount resistors, should
be used since these components can add to distortion.
The voltage glitch of the converter, due to its sampling
nature is buffered by the LT1807, and the ability of the
amplifier to settle it quickly will affect the spurious free
dynamic range of the system. Figure 2 depicts the LT1806
driving LTC1420 at noninverting gain of 2 configuration.
The FFT responses show a better than 92dB of spurious
free dynamic range, SFDR.
0
VS = p5V
AV = 2
fSAMPLE = 10Msps
fIN = 1.4086MHz
SFDR = 92.5dB
5V
5V
VIN
1.5VP-P
+
R3
49.9Ω
LT1806
+AIN
C1
470pF
–
–5V
–AIN
LTC1420
PGA GAIN = 1
REF = 2.048V
R2
1k
•
•
•
18067 F02
–5V
R1
1k
12 BITS
10Msps
AMPLITUDE (dB)
–20
–40
–60
–80
–100
–120
0
1
2
3
FREQUENCY (MHz)
5
4
18067 F03
Figure 2. Noninverting A/D Driver
Figure 3. 4096 Point FFT Response
18067fc
21
LT1806/LT1807
TYPICAL APPLICATIONS
Single Supply Video Line Driver
The LT1806/LT1807 are wideband rail-to-rail op amps with
large output current that allows them to drive video signals
in low supply applications. Figure 4 depicts a single supply
video line driver with AC coupling to minimize the quiescent power dissipation. Resistors R1 and R2 are used to
level-shift the input and output to provide the largest signal
swing. The gain of 2 is set up with R3 and R4 to restore
the signal at VOUT, which is attenuated by 6dB due to the
matching of the 75Ω line with the back-terminated resistor,
R5. The back termination will eliminate any reflection of
the signal that comes from the load. The input termination
resistor, RT, is optional—it is used only if matching of
the incoming line is necessary. The values of C1, C2 and
C3 are selected to minimize the droop of the luminance
signal. In some less stringent requirements, the value of
capacitors could be reduced. The –3dB bandwidth of the
driver is about 90MHz on 5V supply, and the amount of
peaking will vary upon the value of capacitor C4.
5V
+
R1
5k
3
VIN
RT
75Ω
R2
5k
C3
1000μF
7
+
6
LT1806
2
–
4
75W
COAX CABLE
VOUT
RLOAD
75Ω
R4
1k
18067 F04
C4
3pF
R3
1k
+
R5
75Ω
+
C1
33μF
C2
150μF
Figure 4. 5V Single Supply Video Line Driver
5
4
VS = 5V, 0V
VOLTAGE GAIN (dB)
3
2
1
0
–1
–2
–3
–4
–5
0.2
1
10
FREQUENCY (MHz)
100
18067 F05
Figure 5. Video Line Driver Frequency Response
18067fc
22
LT1806/LT1807
TYPICAL APPLICATIONS
Single 3V Supply, 4MHz, 4th Order Butterworth Filter
Benefiting from a low voltage supply operation, low
distortion and rail-to-rail output of LT1806/LT1807, a low
distortion filter that is suitable for antialiasing can be built
as shown in Figure 6.
On a 3V supply, the filter built with LT1807 has a passband
of 4MHz with 2.5VP-P signal and stopband that is greater
than 70dB to frequency of 100MHz. As an option to minimize
the DC offset voltage at the output, connect a series resistor
of 365Ω and a bypass capacitor at the noninverting inputs
of the amplifiers as shown in Figure 6.
232Ω
274Ω
47pF
22pF
232Ω
665Ω
–
VIN
220pF
VS
274Ω
562Ω
–
1/2 LT1807
470pF
+
365Ω
(OPTIONAL)
1/2 LT1807
VOUT
+
2
18067 F06
4.7μF
(OPTIONAL)
Figure 6. Single 3V Supply, 4MHz, 4th Order Butterworth Filter
10
0
–10
GAIN (dB)
–20
–30
–40
–50
–60
–70
–80
VS = 3V, 0V
VIN = 2.5VP-P
–90
10k
100k
1M
10M
FREQUENCY (Hz)
100M
18067 F07
Figure 7. Filter Frequency Response
18067fc
23
LT1806/LT1807
TYPICAL APPLICATIONS
1MHz Series Resonant Crystal Oscillator with Square
and Sinusoid Outputs
edge and the crystal capacitance (middle trace of Figure 9).
Sinusoid amplitude stability is maintained by the fact that
the sine wave is basically a filtered version of the square
wave; the usual amplitude control loops associated with
sinusoidal oscillators are not immediately necessary.1
One can make use of this sine wave by buffering and
filtering it, and this is the combined task of the LT1806. It
is configured as a bandpass filter with a Q of 5 and does
a good job of cleaning up and buffering the sine wave.
Distortion was measured at –70dBc and –60dBc on the
second and third harmonics.
Figure 8 shows a classic 1MHz series resonant crystal
oscillator. At series resonance, the crystal is a low impedance and the positive feedback connection is what brings
about oscillation at the series resonance frequency. The
RC feedback around the other path ensures that the circuit
does not find a stable DC operating point and refuse to
oscillate. The comparator output is a 1MHz square wave
with a measured jitter of 28psRMS with a 5V supply and
40psRMS with a 3V supply. On the other side of the crystal,
however, is an excellent looking sine wave except for the
fact of the small high frequency glitch caused by the fast
therefore controllable. The important difference here is that any added amplitude stabilization loop
will not be faced with the classical task of avoiding regions of nonoscillation versus clipping.
C4
100pF
R5
6.49k
1k
1MHZ
AT-CUT
1Amplitude will be a linear function of comparator output swing, which is supply dependent and
C3
100pF
VS
R1
1k
R2
1k
R7
15.8k
R6
162Ω
100pF
R4
210Ω
VS
2
1
+
R9
2k
7
3
–
LE
5
8
4
7
–
LT1806
C2
0.1μF
SQUARE WAVE
2
3
VS
LT1713
VS
+
R8
2k
6
SINE WAVE
1 (NC)
4
18067 F08
6
R3
1k
VS = 2.7V TO 6V
C1
0.1μF
Figure 8. LT1713 Comparator is Configured as a Series Resonant Crystal Oscillator.
The LT1806 Op Amp is Configured in a Q = 5 Bandpass Filter with fC = 1MHz
3V/DIV
1V/DIV
1V/DIV
200ns/DIV
18067 F09
Figure 9. Oscillator Waveforms with VS = 3V. Top Trace is Comparator Output.
Middle Trace is Crystal Feedback to Pin 2 at LT1713. Bottom Trace is Buffered,
Inverted and Bandpass Filtered with a Q of 5 by the LT1806
18067fc
24
LT1806/LT1807
PACKAGE DESCRIPTION
S6 Package
6-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1636)
0.62
MAX
2.90 BSC
(NOTE 4)
0.95
REF
1.22 REF
3.85 MAX 2.62 REF
1.4 MIN
2.80 BSC
1.50 – 1.75
(NOTE 4)
PIN ONE ID
RECOMMENDED SOLDER PAD LAYOUT
PER IPC CALCULATOR
0.30 – 0.45
6 PLCS (NOTE 3)
0.95 BSC
0.80 – 0.90
0.20 BSC
0.01 – 0.10
1.00 MAX
DATUM ‘A’
0.30 – 0.50 REF
0.09 – 0.20
(NOTE 3)
1.90 BSC
S6 TSOT-23 0302 REV B
NOTE:
1. DIMENSIONS ARE IN MILLIMETERS
2. DRAWING NOT TO SCALE
3. DIMENSIONS ARE INCLUSIVE OF PLATING
4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR
5. MOLD FLASH SHALL NOT EXCEED 0.254mm
6. JEDEC PACKAGE REFERENCE IS MO-193
18067fc
25
LT1806/LT1807
PACKAGE DESCRIPTION
MS8 Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1660 Rev F)
0.889 p 0.127
(.035 p .005)
5.23
(.206)
MIN
3.20 – 3.45
(.126 – .136)
0.42 p 0.038
(.0165 p .0015)
TYP
3.00 p 0.102
(.118 p .004)
(NOTE 3)
0.65
(.0256)
BSC
8
7 6 5
0.52
(.0205)
REF
RECOMMENDED SOLDER PAD LAYOUT
0.254
(.010)
3.00 p 0.102
(.118 p .004)
(NOTE 4)
4.90 p 0.152
(.193 p .006)
DETAIL “A”
0o – 6o TYP
GAUGE PLANE
1
0.53 p 0.152
(.021 p .006)
DETAIL “A”
2 3
4
1.10
(.043)
MAX
0.86
(.034)
REF
0.18
(.007)
SEATING
PLANE
0.22 – 0.38
(.009 – .015)
TYP
0.65
(.0256)
BSC
0.1016 p 0.0508
(.004 p .002)
MSOP (MS8) 0307 REV F
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
18067fc
26
LT1806/LT1807
PACKAGE DESCRIPTION
S8 Package
8-Lead Plastic Small Outline (Narrow .150 Inch)
(Reference LTC DWG # 05-08-1610)
.189 – .197
(4.801 – 5.004)
NOTE 3
.045 p .005
.050 BSC
8
.245
MIN
7
6
5
.160 p .005
.150 – .157
(3.810 – 3.988)
NOTE 3
.228 – .244
(5.791 – 6.197)
.030 p .005
TYP
1
RECOMMENDED SOLDER PAD LAYOUT
.010 – .020
s 45o
(0.254 – 0.508)
.008 – .010
(0.203 – 0.254)
3
4
.053 – .069
(1.346 – 1.752)
.004 – .010
(0.101 – 0.254)
0o– 8o TYP
.016 – .050
(0.406 – 1.270)
NOTE:
1. DIMENSIONS IN
2
.014 – .019
(0.355 – 0.483)
TYP
INCHES
(MILLIMETERS)
2. DRAWING NOT TO SCALE
3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm)
.050
(1.270)
BSC
SO8 0303
18067fc
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
27
LT1806/LT1807
TYPICAL APPLICATION
FET Input, Fast, High Gain Photodiode Amplifier
total output noise was below 1mVRMS measured over a
10MHz bandwidth. Table 4 shows results achieved with
various values of RF and Figure 11 shows the time domain
response with RF = 499k.
Figure 10 shows a fast, high gain transimpedance
amplifier applied to a photodiode. A JFET buffer is used
for its extremely low input bias current and high speed.
The LT1097 and 2N3904 keep the JFET biased at IDSS
for zero offset and lowest voltage noise. The JFET then
drives the LT1806, with RF closing the high speed loop
back to the JFET input and setting the transimpedance
gain. C4 helps improve the phase margin of the fast loop.
Output voltage noise density was measured as 9nV/√Hz
with RF short circuited. With RF varied from 100k to 1M,
VS+
R1
10M
3
+
–
4
VS–
200k
94ns
4.6MHz
499k
154ns
3MHz
1M
263ns
1.8MHz
C4
3pF
*
–
7
LT1806
3
7
6
LT1097
2
2
C1
100pF
VS+
–3dB
BANDWIDTH
6.8MHz
VS+
R2
1M
VS–
100k
10% to 90%
RISE TIME
64ns
RF
RF
2N5486
SIEMENS/
INFINEON
SFH213FA
PHOTODIODE
Table 4. Results Achieved for Various RF, 1.2V Output Step
+
6
49.9Ω
VOUT
100mV/DIV
50W
4
VS–
18067 F10
R3
10k
C2
2200pF
2N3904
C3
0.1μF
R4
2.4k
R5
33Ω
20ns/DIV
*ADJUST PARASITIC CAPACITANCE AT
RF FOR DESIRED RESPONSE
CHARACTERISTICS
VS = p5V
18067 F11
Figure 11. Step Response
with RF = 499k
VS–
Figure 10. Fast, High Gain Photodiode Amplifier
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
LT1395
400MHz Current Feedback Amplifier
800V/μs Slew Rate, Shutdown
LT1399
Triple 300MHz Current Feedback Amplifier
0.1dB Gain Flatness to 150MHz, Shutdown
LT1632/LT1633
Dual/Quad 45MHz, 45V/μs Rail-to-Rail Input and Output Amplifiers
High DC Accuracy 1.35mV VOS(MAX), 70mA Output Current,
Max Supply Current 5.2mA/Amp
LT1809/LT1810
Single/Dual 180MHz Input and Output Rail-to-Rail Amplifiers
350V/μs Slew Rate, Shutdown, Low Distortion –90dBc at 5MHz
LT1812/LT1813
3mA, 100MHz, 750V/μs Op Amp
High Slew Rate
LT1818/LT1819
9mA, 400MHz, 2500V/μs Op Amp
Ultrahigh Slew Rate
LT6200/LT6201
165MHz Rail-to-Rail Input and Output, 0.95nV/√Hz Low Noise
Op Amp
Lowest Noise
LT6202/LT6203
100MHz Rail-to-Rail Input and Output, 1.9nV/√Hz Op Amp
ICC = 2.5mA
18067fc
28 Linear Technology Corporation
LT 0809 REV C • PRINTED IN USA
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 ● FAX: (408) 434-0507
●
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© LINEAR TECHNOLOGY CORPORATION 2000