LMV710,LMV711,LMV715 LMV710/LMV711/LMV715 Low Power, RRIO Operational Amplifiers with High Output Current Drive and Shutdown Option Literature Number: SNOS519I LMV710/LMV711/LMV715 Low Power, RRIO Operational Amplifiers with High Output Current Drive and Shutdown Option General Description Features The LMV710/LMV711/LMV715 are BiCMOS operational amplifiers with a CMOS input stage. These devices have greater than RR input common mode voltage range, rail-to-rail output and high output current drive. They offer a bandwidth of 5 MHz and a slew rate of 5 V/µs. On the LMV711/LMV715, a separate shutdown pin can be used to disable the device and reduces the supply current to 0.2 µA (typical). They also feature a turn on time of less than 10 µs. It is an ideal solution for power sensitive applications, such as cellular phone, pager, palm computer, etc. In addition, once the LMV715 is in shutdown the output will be “Tristated”. The LMV710 is offered in the space saving 5-Pin SOT23 Tiny package. The LMV711/LMV715 are offered in the space saving 6-Pin SOT23 Tiny package. The LMV710/LMV711/LMV715 are designed to meet the demands of low power, low cost, and small size required by cellular phones and similar battery powered portable electronics. (For 5V supply, typical unless otherwise noted). 3 mV, max ■ Low offset voltage 5 MHz, typ ■ Gain-bandwidth product 5 V/µs, typ ■ Slew rate 5-Pin and 6-Pin SOT23 ■ Space saving packages <10 µs ■ Turn on time from shutdown −40°C to +85°C ■ Industrial temperature range 0.2 µA, typ ■ Supply current in shutdown mode ■ Guaranteed 2.7V and 5V performance ■ Unity gain stable ■ Rail-to-rail input and output ■ Capable of driving 600Ω load Applications ■ ■ ■ ■ ■ ■ ■ Wireless phones GSM/TDMA/CDMA power amp control AGC, RF power detector Temperature compensation Wireless LAN Bluetooth HomeRF Typical Application High Side Current Sensing 10132513 © 2009 National Semiconductor Corporation 101325 www.national.com LMV710/LMV711/LMV715 Low Power, RRIO Operational Amplifiers with High Output Current Drive and Shutdown Option January 9, 2009 LMV710/LMV711/LMV715 Current at Input Pin Mounting Temp. Infrared or Convection (20 sec) Storage Temperature Range Junction Temperature (TJMAX) (Note 5) Absolute Maximum Ratings (Note 1) If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. ESD Tolerance (Note 2) Machine Model Human Body Model Differential Input Voltage Voltage at Input/Output Pin 100V 2000V ± Supply Voltage (V+) + 0.4V (V−) − 0.4V Supply Voltage (V+ - V −) Output Short Circuit to V+ Output Short Circuit to V− Operating Ratings ± 10 mA 235°C −65°C to 150°C 150°C (Note 1) Supply Voltage Temperature Range 2.7V to 5.0V −40°C to 85°C Thermal Resistance (θJA) MF05A Package, 5-Pin SOT23 MF06A package, 6-Pin SOT23 5.5V (Note 3) (Note 4) 265 °C/W 265 °C/W 2.7V Electrical Characteristics Unless otherwise specified, all limits guaranteed for TJ = 25°C. V+ = 2.7V, V − = 0V, VCM = 1.35V and RL > 1 MΩ. Boldface limits apply at the temperature extremes. Symbol Parameter Condition Limits (Note 7) Units 0.4 3 3.2 mV max VOS Input Offset Voltage IB Input Bias Current CMRR Common Mode Rejection Ratio 0 ≤ VCM ≤ 2.7V 75 50 45 dB min PSRR Power Supply Rejection Ratio 2.7V ≤ V+ ≤ 5V, VCM = 0.85V 110 70 68 dB min 2.7V ≤ V+ ≤ 5V, VCM = 1.85V 95 70 68 dB min -0.3 -0.2 3 2.9 Sourcing VO = 0V 28 15 12 mA min Sinking VO = 2.7V 40 25 22 mA min 2.68 2.62 2.60 V min 0.01 0.12 0.15 V max 2.55 2.52 2.50 V min 0.05 0.23 0.30 V max 200 mV VCM ISC VO Input Common-Mode Voltage Range Output Short Circuit Current Output Swing VCM = 0.85V and VCM = 1.85V Typ (Note 6) 4 For CMRR ≥ 50 dB RL = 10 kΩ to 1.35V RL = 600Ω to 1.35V pA V VO (SD) Output Voltage Level in Shutdown Mode (LMV711 only) 50 IO (SD) Output Leakage Current in Shutdown Mode (LMV715 Only) 1 pA CO (SD) Output Capacitance in Shutdown Mode (LMV715 Only) 32 pF IS Supply Current www.national.com On Mode 1.22 1.7 1.9 mA max Shutdown Mode, VSD = 0V 0.002 10 µA 2 AV Parameter Large Signal Voltage SR Slew Rate GBWP φm TON Turn-on Time from Shutdown VSD Shutdown Pin Voltage Range Condition Typ (Note 6) Limits (Note 7) Units Sourcing RL = 10 kΩ VO = 1.35V to 2.3V 115 80 76 dB min Sinking RL = 10 kΩ VO = 0.4V to 1.35V 113 80 76 dB min Sourcing RL = 600Ω VO = 1.35V to 2.2V 110 80 76 dB min Sinking RL = 600Ω VO = 0.5V to 1.35V 100 80 76 dB min (Note 8) 5 V/µs Gain-Bandwidth Product 5 MHz Phase Margin 60 Deg <10 On Mode Shutdown Mode en Input-Referred Voltage Noise f = 1 kHz µs 1.5 to 2.7 2.4 to 2.7 V 0 to 1 0 to 0.8 V 20 3.2V Electrical Characteristics Unless otherwise specified, all limits guaranteed for TJ = 25°C. V+ = 3.2V, V− = 0V, VCM = 1.6V. Boldface limits apply at the temperature extremes. Symbol VO Parameter Output Swing Conditions IO = 6.5 mA Typ (Note 6) Limit (Note 7) Units 3.0 2.95 2.92 V min 0.01 0.18 0.25 V max 5V Electrical Characteristics Unless otherwise specified, all limits guaranteed for TJ = 25°C. V+ = 5V, V − = 0V, VCM = 2.5V, and RL > 1 MΩ. Boldface limits apply at the temperature extremes. Symbol Parameter Condition Typ (Note 6) Limits (Note 7) Units VCM = 0.85V and VCM = 1.85V 0.4 3 3.2 mV max VOS Input Offset Voltage IB Input Bias Current CMRR Common Mode Rejection Ratio 0V ≤ VCM ≤ 5V 70 50 48 dB min PSRR Power Supply Rejection Ratio 2.7V ≤ V+ ≤ 5V, VCM = 0.85V 110 70 68 dB min 2.7V ≤ V+ ≤ 5V, VCM = 1.85V 95 70 68 dB min -0.3 −0.2 5.3 5.2 VCM Input Common-Mode Voltage Range 4 For CMRR ≥ 50 dB 3 pA V www.national.com LMV710/LMV711/LMV715 Symbol LMV710/LMV711/LMV715 Symbol ISC VO Parameter Output Short Circuit Current Output Swing Condition Typ (Note 6) Limits (Note 7) Units Sourcing VO = 0V 35 25 21 mA min Sinking VO = 5V 40 25 21 mA min 4.98 4.92 4.90 V min 0.01 0.12 0.15 V max 4.85 4.82 4.80 V min 0.05 0.23 0.3 V max 200 mV RL = 10 kΩ to 2.5V RL = 600Ω to 2.5V VO (SD) Output Voltage Level in Shutdown Mode (LMV711 only) 50 IO (SD) Output Leakage Current in Shutdown Mode (LMV715 Only) 1 pA CO (SD) Output Capacitance in shutdown Mode (LMV715 Only) 32 pF IS Supply Current AV Large Signal Voltage Gain On Mode 1.17 1.7 1.9 mA max Shutdown Mode 0.2 10 µA Sourcing RL = 10 kΩ VO = 2.5V to 4.6V 123 80 76 dB min Sinking RL = 10 kΩ VO = 0.4V to 2.5V 120 80 76 dB min Sourcing RL = 600Ω VO = 2.5V to 4.5V 110 80 76 dB min Sinking RL = 600Ω VO = 0.5V to 2.5V 118 80 76 dB min SR Slew Rate 5 V/µs GBWP Gain-Bandwidth Product (Note 8) 5 MHz φm Phase Margin 60 Deg TON Turn-on Time from Shutdown <10 µs VSD Shutdown Pin Voltage Range On Mode Shutdown Mode en Input-Referred Voltage Noise f = 1 kHz 2 to 5 2.4 to 5 0 to 1.5 0 to 0.8 V 20 Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics. Note 2: Human body model, 1.5 kΩ in series with 100 pF. Machine model, 0Ω in series with 100 pF. Note 3: Shorting circuit output to V+ will adversely affect reliability. Note 4: Shorting circuit output to V− will adversely affect reliability. Note 5: The maximum power dissipation is a function of TJ(MAX), θJA, and TA. The maximum allowable power dissipation at any ambient temperature is PD = (TJ(MAX) - T A)/θJA. All numbers apply for packages soldered directly into a PC board. Note 6: Typical values represent the most likely parametric norm. Note 7: All limits are guaranteed by testing or statistical analysis. Note 8: Number specified is the slower of the positive and negative slew rates. www.national.com 4 Unless otherwise specified, VS = +5V, single supply, TA = 25°C. Supply Current vs. Supply Voltage (On Mode) LMV711/LMV715 Supply Current vs. Supply Voltage (Shutdown Mode) 10132527 10132528 Output Positive Swing vs. Supply Voltage Output Negative Swing vs. Supply Voltage 10132529 10132530 Output Positive Swing vs. Supply Voltage Output Negative Swing vs. Supply Voltage 10132531 10132532 5 www.national.com LMV710/LMV711/LMV715 Typical Performance Characteristics LMV710/LMV711/LMV715 Output Positive Swing vs. Supply Voltage Output Negative Swing vs. Supply Voltage 10132533 10132534 Input Voltage Noise vs. Frequency PSRR vs. Frequency 10132535 10132536 CMRR vs. Frequency LMV711/LMV715 Turn On Characteristics 10132538 10132537 www.national.com 6 LMV710/LMV711/LMV715 Sourcing Current vs. Output Voltage Sinking Current vs. Output Voltage 10132539 10132540 THD+N vs. Frequency (VS = 5V) THD+N vs. Frequency (VS = 2.7V) 10132541 10132542 THD+N vs. VOUT THD+N vs. VOUT 10132543 10132544 7 www.national.com LMV710/LMV711/LMV715 CCM vs. VCM CCM vs. VCM 10132545 10132546 CDIFF vs. VCM (VS = 2.7V) CDIFF vs. VCM (VS = 5V) 10132547 10132548 Open Loop Frequency Response Open Loop Frequency Response 10132512 www.national.com 10132510 8 LMV710/LMV711/LMV715 Open Loop Frequency Response Open Loop Frequency Response 10132511 10132507 Open Loop Frequency Response Open Loop Frequency Response 10132509 10132508 Non-Inverting Large Signal Pulse Response Non-Inverting Small Signal Pulse Response 10132503 10132502 9 www.national.com LMV710/LMV711/LMV715 Inverting Large Signal Pulse Response Inverting Small Signal Pulse Response 10132504 10132505 VOS vs. VCM VOS vs. VCM 10132549 www.national.com 10132550 10 1.0 SUPPLY BYPASSING The application circuits in this datasheet do not show the power supply connections and the associated bypass capacitors for simplification. When the circuits are built, it is always required to have bypass capacitors. Ceramic disc capacitors (0.1 µF) or solid tantalum (1 µF) with short leads, and located close to the IC are usually necessary to prevent interstage coupling through the power supply internal impedance. Inadequate bypassing will manifest itself by a low frequency oscillation or by high frequency instabilities. Sometimes, a 10 µF (or larger) capacitor is used to absorb low frequency variations and a smaller 0.1 µF disc is paralleled across it to prevent any high frequency feedback through the power supply lines. 10132552 FIGURE 1. When the input is a small signal and this small signal falls inside the VOS transition range, the gain, CMRR and some other parameters will be degraded. To resolve this problem, the small signal should be placed such that it avoids the VOS crossover point. To achieve maximum output swing, the output should be biased at mid-supply. This is normally done by biasing the input at mid-supply. But with supply voltage range from 2V to 3.4V, the input of the op amp should not be biased at mid-supply because of the transition of the VOS. Figure 2 shows an example of how to get away from the VOS crossover point and maintain a maximum swing with a 2.7V supply. Figure 3 shows the waveforms of VIN and VOUT. 2.0 SHUTDOWN MODE The LMV711/LMV715 have a shutdown pin. To conserve battery life in portable applications, they can be disabled when the shutdown pin voltage is pulled low. For LMV711 during shutdown mode, the output stays at about 50 mV from the lower rail, and the current drawn from the power supply is 0.2 µA (typical). This makes the LMV711 an ideal solution for power sensitive applications. For the LMV715 during shutdown mode, the output will be “Tri-stated”. The shutdown pin should never be left unconnected. In applications where shutdown operation is not needed and the LMV711 or LMV715 is used, the shutdown pin should be connected to V+. Leaving the shutdown pin floating will result in an undefined operation mode and the device may oscillate between shutdown and active modes. 3.0 RAIL-TO-RAIL INPUT The rail-to-rail input is achieved by using paralleled PMOS and NMOS differential input stages. (See Simplified Schematics in this datasheet). When the common mode input voltage changes from ground to the positive rail, the input stage goes through three modes. First, the NMOS pair is cutoff and the PMOS pair is active. At around 1.4V, both PMOS and NMOS pairs operate, and finally the PMOS pair is cutoff and NMOS pair is active. Since both input stages have their own offset voltage (V OS), the offset of the amplifier becomes a function of the common-mode input voltage. See curves for VOS vs. VCM in curve section. As shown in the curve, the VOS has a crossover point at 1.4V above V−. Proper design must be done in both DC and AC coupled applications to avoid problems. For large input signals that include the VOS crossover point in their dynamic range, it will cause distortion in the output signal. One way to avoid such distortion is to keep the signal away from the crossover point. For example, in a unity gain buffer configuration and with VS = 5V, a 3V peak-to-peak signal center at 2.5V will contain input-crossover distortion. To avoid this, the input signal should be centered at 3.5V instead. Another way to avoid large signal distortion is to use a gain of −1 circuit which avoids any voltage excursions at the input terminals of the amplifier. See Figure 1. In this circuit, the common mode DC voltage (VCM) can be set at a level away from the VOS crossover point. 10132517 FIGURE 2. 10132551 FIGURE 3. The inputs can be driven 300 mV beyond the supply rails without causing phase reversal at the output. However, the inputs should not be allowed to exceed the maximum ratings. 11 www.national.com LMV710/LMV711/LMV715 Application Information LMV710/LMV711/LMV715 In Figure 5, the isolation resistor RISO and the load capacitor CL form a pole to increase stability by adding more phase margin to the overall system. The desired performance depends on the value of RISO. The bigger the RISO resistor value, the more stable VOUT will be. But the DC accuracy is not great when the RISO gets bigger. If there were a load resistor in Figure 5, the output would be voltage divided by RISO and the load resistor. The circuit in Figure 6 is an improvement to the one in Figure 5 because it provides DC accuracy as well as AC stability. In this circuit, RF provides the DC accuracy by using feed-forward techniques to connect VIN to RL. CF and RISO serve to counteract the loss of phase margin by feeding the high frequency component of the output signal back to the amplifier's inverting input, thereby preserving phase margin in the overall feedback loop. Increased capacitive drive is possible by increasing the value of CF . This in turn will slow down the pulse response. 4.0 COMPENSATION OF INPUT CAPACITANCE In the application (Figure 4) where a large feedback resistor is used, the feedback resistor can react with the input capacitance of the op amp and introduce an additional pole to the close loop frequency response. 10132518 FIGURE 4. Cancelling the Effect of Input Capacitance This pole occurs at frequency fp , where Any stray capacitance due to external circuit board layout, any source capacitance from transducer or photodiode connected to the summing node will also be added to the input capacitance. If fp is less than or close to the unity-gain bandwidth (5 MHz) of the op amp, the phase margin of the loop is reduced and can cause the system to be unstable. To avoid this problem, make sure that fp occurs at least 2 octaves beyond the expected −3 dB frequency corner of the close loop frequency response. If not, a feedback capacitor CF can be placed in parallel with RF such that 10132522 FIGURE 6. Indirectly Driving A Capacitive A Load with DC Accuracy 6.0 APPLICATION CIRCUITS PEAK DETECTOR Peak detectors are used in many applications, such as test equipment, measurement instrumentation, ultrasonic alarm systems, etc. Figure 7 shows the schematic diagram of a peak detector using LMV710 or LMV711 or LMV715. This peak detector basically consists of a clipper, a parallel RC network, and a voltage follower. The paralleled RF and CF introduce a zero, which cancels the effect from the pole. 5.0 CAPACITIVE LOAD TOLERANCE The LMV710/LMV711/ LMV715 can directly drive 200 pF in unity-gain without oscillation. The unity-gain follower is the most sensitive configuration to capacitive loading. Direct capacitive loading reduces the phase margin of amplifiers. The combination of the amplifier's output impedance and the capacitive load induces phase lag. This results in either an underdamped pulse response or oscillation. To drive a heavier capacitive load, circuit in Figure 5 can be used. 10132523 FIGURE 7. Peak Detector The capacitor C1 is first discharged by applying a positive pulse to the reset transistor. When a positive voltage VIN is applied to the input, the input voltage is higher than the voltage across C1. The output of the op amp goes high and forward biases the diode D1. The capacitor C1 is charged to VIN. When the input becomes less than the current capacitor voltage, the output of the op amp A1 goes low and the diode 10132521 FIGURE 5. Indirectly Driving A Capacitive Load using Resistive Isolation www.national.com 12 vent over-charging. A sense resistor RSENSE is connected to the battery directly. This system requires an op amp with railto-rail input. The LMV710/LMV711/LMV715 are ideal for this application because its common mode input range can go beyond the positive rail. HIGH SIDE CURRENT SENSING The high side current sensing circuit (Figure 8) is commonly used in a battery charger to monitor charging current to pre- FIGURE 8. High Side Current Sensing 10132513 10132506 FIGURE 9. Typical of GSM P.A. Control Loop equal. Power control is accomplished by changing the ramping voltage. The LMV710/LMV711/LMV715 are well suited as an error amplifier in this application. The LMV711/LMV715 have an extra shutdown pin to switch the op amp to shutdown mode. In shutdown mode, the LMV711/LMV715 consume very low current. The LMV711 provides a ground voltage to the power amplifier control pin VPC. Therefore, the power amplifier can be turned off to save battery life. The LMV715 output will be “tri-stated” when in shutdown. GSM POWER AMPLIFIER CONTROL LOOP There are four critical sections in the GSM Power Amplifier Control Loop. The class-C RF power amplifier provides amplification of the RF signal. A directional coupler couples small amount of RF energy from the output of the RF P. A. to an envelope detector diode. The detector diode senses the signal level and rectifies it to a DC level to indicate the signal strength at the antenna. An op amp is used as an error amplifier to process the diode voltage and ramping voltage. This loop control the power amplifier gain via the op amp and forces the detector diode voltage and ramping voltage to be 13 www.national.com LMV710/LMV711/LMV715 D1 is reverse biased. This isolates the C1 and leaves it with the charge equivalent to the peak of the input voltage. The follower prevents unintentional discharging of C1 by loading from the following circuit. R5 and C1 are properly selected so that the capacitor is charged rapidly to VIN. During the holding period, the capacitor slowly discharge through C1, via leakage of the capacitor and the reverse-biased diode, or op amp bias currents. In any cases the discharging time constant is much larger than the charge time constant. And the capacitor can hold its voltage long enough to minimize the output ripple. Resistors R2 and R3 limit the current into the inverting input of A1 and the non-inverting input of A2 when power is disconnected from the circuit. The discharging current from C1 during power off may damage the input circuitry of the op amps. The peak detector can be reset by applying a positive pulse to the reset transistor. The charge on the capacitor is dumped into ground, and the detector is ready for another cycle. The maximum input voltage to this detector should be less than (V+ - VD), where VD is the forward voltage drop of the diode. Otherwise, the input voltage should be scaled down before applying to the circuit. LMV710/LMV711/LMV715 Simplified Schematic LMV711 10132516 Connection Diagrams 5-Pin SOT23 LMV710 6-Pin SOT23 LMV711 and LMV715 10132514 10132515 Top View Top View Ordering Information Package 5-Pin SOT23 Temperature Range Industrial −40°C to +85°C LMV710M5 LMV710M5X LMV711M6 6-Pin SOT23 LMV711M6X *LMV715MF *LMV715MFX Packaging Marking A48A A47A A75A Transport Media 1k Units Tape and Reel 3k Units Tape and Reel 14 MF05A 1k Units Tape and Reel 3k Units Tape and Reel 1k Units Tape and Reel 3k Units Tape and Reel *LMV715MF/LMV715MFX are not recommended for new designs with a last time buy date of 12/1/2009. www.national.com NSC Drawing MF06A LMV710/LMV711/LMV715 SOT-23 Tape and Reel Specification Tape Format Tape Section # Cavities Cavity Status Cover Tape Status Leader (Start End) 0 (min) Empty Sealed 75 (min) Empty Sealed Carrier 3000 Filled Sealed 1000 Filled Sealed 125 (min) Empty Sealed 0 (min) Empty Sealed Trailer (Hub End) Tape Dimensions 10132555 TAPE SIZE DIM A DIM Ao DIM B DIM Bo DIM F DIM Ko DIM P1 DIM T DIM W 8 mm .130 (3.3) .124 (3.15) .130 (3.3) .126 (3.2) .138 ± .002 (3.5 ± 0.05) .055 ± .004 (1.4 ± 0.1) .157 (4) .008 ± .004 (0.2 ± 0.1) .315 ± .012 (8 ± 0.3) Note: UNLESS OTHERWISE SPECIFIED 1. CUMULATIVE PITCH TOLERANCE FOR FEEDING HOLES AND CAVITIES (CHIP POCKETS) NOT TO EXCEED .008 IN / 0.2mm OVER 10 PITCH SPAN. 2. THRU HOLE INSIDE CAVITY IS CENTERED WITHIN CAVITY. 3. SMALLEST ALLOWABLE TAPE BENDING RADIUS: 1.181 IN/ 30mm. 4. DIMENSIONS WITH Δ ARE CRITICAL. DIMENSIONS TO BE ABSOLUTELY INSPECTED. 15 www.national.com LMV710/LMV711/LMV715 Reel Dimensions 10132554 TAPE SIZE DIM A DIM B DIM C DIM D DIM N DIM W1 DIM W2 DIM W3 (LSL-USL) 8 mm 7.00 (177.8) .059 (1.5) .512 + .020/−.008 (13 +0.5/−0.2) .795 (20.2) 2.165 (55) .331 + .059/−.000 (8.4 + 1.5/0) .567 (14.4) .311 - .429 (7.9 - 10.9) Note: UNLESS OTHERWISE SPECIFIED 1. MATERIAL: POLYSTYRENE/PVC (WITH ANTISTATIC COATING). OR POLYSTYRENE/PVC, ANTISTATIC OR POLYSTYRENE/PVC, CONDUCTIVE. 2. CONTROLLING DIMENSION IS MILLIMETER, DIMENSIONS IN INCHES ROUNDED. 3. SURFACE RESISTIVITY: 1010 OHM/SQ MAXIMUM. 4. ALL OUTPUT REELS SHALL BE UNIFORM IN SHADE. 5. PACKING OF REELS IN CONTAINERS MUST ENSURE NO DAMAGE TO THE REEL. 6. SURFACE FINISH OF THE FLANGES SHALL BE SMOOTH, MATTE FINISH PREFERRED. 7. ALL EDGES, ESPECIALLY THE TAPE ENTRY EDGES, MUST BE FREE OF BURRS. 8. THE REEL SHOULD NOT WARP IN THE STORAGE TEMPERATURE OF 67°C MAXIMUM. 9. GLASS TRANSITION TEMPERATURE (Tg) OF THE PLASTIC REEL SHALL BE LOWER THAN −20°C. www.national.com 10. ALL GATING FROM THE MOLD MUST BE PROPERLY REMOVED. 11. NO FLASHES ARE TO BE PRESENT ALONG THE PARTING LINES. 12. ALLOWABLE RADIUS FOR CORNERS AND EDGES IS .012 INCHES/0.3 MILLIMETERS MINIMUM. 13. SINK MARKS THAT WILL CAUSE A CHANGE TO THE SPECIFIED DIMENSIONS OR SHAPE OF THE REELS ARE NOT ALLOWED. 14. MOLDED REELS SHALL BE FREE OF COSMETIC DEFECTS SUCH AS VOIDS. FLASHING, EXCESSIVE FLOW MARKS, ETC. 15. THERE MUST BE NO MISMATCH BETWEEN MATING PARTS. 16. MOLDED REELS SHALL BE ANTISTATIC COATED OR BLENDED. 17. THE SOT23-5L AND SOT23-6L PACKAGE USE THE 7-INCH REEL. 16 LMV710/LMV711/LMV715 Physical Dimensions inches (millimeters) unless otherwise noted SOT23-5 NS Package Number MF05A SOT23-6 NS Package Number MF06A 17 www.national.com LMV710/LMV711/LMV715 Low Power, RRIO Operational Amplifiers with High Output Current Drive and Shutdown Option Notes For more National Semiconductor product information and proven design tools, visit the following Web sites at: Products Design Support Amplifiers www.national.com/amplifiers WEBENCH® Tools www.national.com/webench Audio www.national.com/audio App Notes www.national.com/appnotes Clock and Timing www.national.com/timing Reference Designs www.national.com/refdesigns Data Converters www.national.com/adc Samples www.national.com/samples Interface www.national.com/interface Eval Boards www.national.com/evalboards LVDS www.national.com/lvds Packaging www.national.com/packaging Power Management www.national.com/power Green Compliance www.national.com/quality/green Switching Regulators www.national.com/switchers Distributors www.national.com/contacts LDOs www.national.com/ldo Quality and Reliability www.national.com/quality LED Lighting www.national.com/led Feedback/Support www.national.com/feedback Voltage Reference www.national.com/vref Design Made Easy www.national.com/easy PowerWise® Solutions www.national.com/powerwise Solutions www.national.com/solutions Serial Digital Interface (SDI) www.national.com/sdi Mil/Aero www.national.com/milaero Temperature Sensors www.national.com/tempsensors Solar Magic® www.national.com/solarmagic Wireless (PLL/VCO) www.national.com/wireless Analog University® www.national.com/AU THE CONTENTS OF THIS DOCUMENT ARE PROVIDED IN CONNECTION WITH NATIONAL SEMICONDUCTOR CORPORATION (“NATIONAL”) PRODUCTS. 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