MP2305S 2A, 23V Synchronous Rectified Step-Down Converter The Future of Analog IC Technology DESCRIPTION FEATURES The MP2305S is a monolithic synchronous buck regulator. The device integrates a 175mΩ high-side MOSFET and a 115mΩ low-side MOSFET that provide 2A continuous load current over a wide operating input voltage of 4.75V to 23V. Current mode control provides fast transient response and cycle-by-cycle current limit. • • • • • • • • • • An adjustable soft-start prevents inrush current at turn-on. Shutdown mode drops the supply current to 1μA. This device, available in an 8-pin SOIC package, provides a very compact system solution with minimal reliance on external components. EVALUATION BOARD REFERENCE Board Number Dimensions EV2305SDS-00A 2.0”X x 1.5”Y x 0.5”Z 2A Output Current Wide 4.75V to 23V Operating Input Range Integrated Power MOSFET Switches Output Adjustable from 0.923V to 20V Up to 95% Efficiency Programmable Soft-Start Stable with Low ESR Ceramic Output Capacitors Fixed 340KHz Frequency Cycle-by-Cycle Over Current Protection Input Under Voltage Lockout APPLICATIONS • • • • • Distributed Power Systems Networking Systems FPGA, DSP, ASIC Power Supplies Green Electronics/ Appliances Notebook Computers “MPS” and “The Future of Analog IC Technology” are Registered Trademarks of Monolithic Power Systems, Inc. TYPICAL APPLICATION Efficiency vs.Load Current VOUT=3.3V 100 INPUT 4.75V to 23V 90 VIN=4.75V 7 80 1 BS 3 SW EN MP2305S 8 SS GND FB COMP 4 6 5 OUTPUT 3.3V 2A EFFICIENCY (%) 2 IN 70 60 50 40 30 C6 20 (optional) 10 0 0.01 VIN=12V VIN=23V 0.1 1 10 LOAD CURRENT(A) MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 1 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER ORDERING INFORMATION Part Number* Package Top Marking Free Air Temperature (TA) MP2305SDS SOIC8 M2305SDS -40°C to +85°C * For Tape & Reel, add suffix –Z (e.g. MP2305SDS–Z); For RoHS compliant packaging, add suffix –LF (e.g. MP2305SDS–LF–Z) PACKAGE REFERENCE TOP VIEW BS 1 8 SS IN 2 7 EN SW 3 6 COMP GND 4 5 FB ABSOLUTE MAXIMUM RATINGS (1) Thermal Resistance Supply Voltage VIN ........................-0.3V to +26V Switch Voltage VSW ...................-1V to VIN +0.3V Boost Voltage VBS ..........VSW – 0.3V to VSW + 6V All Other Pins ..................................-0.3V to +6V Continuous Power Dissipation (TA = +25°C) (2) ……………………………………………….1.39W Junction Temperature ...............................150°C Lead Temperature ....................................260°C Storage Temperature .............. -65°C to +150°C SOIC8..................................... 90 ...... 45... °C/W Recommended Operating Conditions (3) Supply Voltage VIN .........................4.75V to 23V Output Voltage VOUT .....................0.923V to 20V Operating Junct. Temp. (TJ) ..........-40°C to +125°C (4) θJA θJC Notes: 1) Exceeding these ratings may damage the device. 2) The maximum allowable power dissipation is a function of the maximum junction temperature TJ (MAX), the junction-toambient thermal resistance θJA, and the ambient temperature TA. The maximum allowable continuous power dissipation at any ambient temperature is calculated by PD (MAX) = (TJ (MAX)-TA)/θJA. Exceeding the maximum allowable power dissipation will cause excessive die temperature, and the regulator will go into thermal shutdown. Internal thermal shutdown circuitry protects the device from permanent damage. 3) The device is not guaranteed to function outside of its operating conditions. 4) Measured on JESD51-7 4-layer PCB. MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 2 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER ELECTRICAL CHARACTERISTICS VIN = 12V, TA = +25°C, unless otherwise noted. Parameter Symbol Condition Shutdown Supply Current Supply Current Min VEN = 0V VEN = 5.0V; VFB = 1.0V Feedback Voltage VFB Feedback Overvoltage Threshold Error Amplifier Voltage Gain (5) AEA Error Amplifier Transconductance GEA (5) High-Side Switch On Resistance Low-Side Switch On Resistance (5) High-Side Switch Leakage Current Upper Switch Current Limit Lower Switch Current Limit COMP to Current Sense Transconductance Oscillation Frequency Short Circuit Oscillation Frequency Maximum Duty Cycle Minimum On Time (5) EN Shutdown Threshold Voltage EN Shutdown Threshold Voltage Hysteresis EN Lockout Threshold Voltage EN Lockout Hysterisis Input Under Voltage Lockout Threshold Input Under Voltage Lockout Threshold Hysteresis Soft-Start Current Soft-Start Period Thermal Shutdown (5) 4.75V ≤ VIN ≤ 23V 0.900 ΔIC = ±10μA RDS(ON)1 RDS(ON)2 VEN = 0V, VSW = 0V Minimum Duty Cycle From Drain to Source 3 Max Units 1 1.3 3.0 1.5 μA mA 0.923 0.946 V 1.1 400 V V/V 800 μA/V 175 115 mΩ mΩ μA A A 4.1 1.1 10 5.3 3.5 GCS Fosc1 Fosc2 DMAX Typ 305 VFB = 0V VFB = 0.8V VEN Rising 1.1 340 100 90 220 1.5 A/V 375 2.0 210 VIN Rising VSS = 0V CSS = 0.1μF kHz kHz % ns V mV 2.2 2.5 210 2.7 V mV 3.40 3.80 4.20 V 210 mV 6 15 160 μA ms °C Note: 5) Guaranteed by design, not tested. MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 3 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER PIN FUNCTIONS Pin # Name 1 BS 2 IN 3 SW 4 GND 5 FB 6 COMP 7 EN 8 SS Description High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET switch. Connect a 0.01μF or greater capacitor from SW to BS to power the high side switch. Power Input. IN supplies the power to the IC, as well as the step-down converter switches. Drive IN with a 4.75V to 23V power source. Bypass IN to GND with a suitably large capacitor to eliminate noise on the input to the IC. See Input Capacitor. Power Switching Output. SW is the switching node that supplies power to the output. Connect the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch. Ground. Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a resistive voltage divider from the output voltage. The feedback threshold is 0.923V. See Setting the Output Voltage. Compensation Node. COMP is used to compensate the regulation control loop. Connect a series RC network from COMP to GND to compensate the regulation control loop. In some cases, an additional capacitor from COMP to GND is required. See Compensation Components. Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on the regulator, drive it low to turn it off. Pull up with 100kΩ resistor for automatic startup. Soft-Start Control Input. SS controls the soft start period. Connect a capacitor from SS to GND to set the soft-start period. A 0.1μF capacitor sets the soft-start period to 15ms. To disable the soft-start feature, leave SS unconnected. MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 4 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER TYPICAL PERFORMANCE CHARACTERISTICS VIN = 12V, VO = 3.3V, L = 10µH, C1 = 10µF, C2 = 22µF, TA = +25°C, unless otherwise noted. Efficiency vs.Load Current 70 70 60 50 VIN=12V VIN=23V 10 VIN=8V 4.5 IPEAK_LIMIT (A) 80 EFFICIENCY (%) 90 20 5 100 80 VIN=4.75V 30 VOUT=3.3V VOUT=5V 90 40 Current Limit vs. Duty Cycle Efficiency vs.Load Current VOUT=1.8V 100 60 50 VIN=12V 40 VIN=23V 30 4 3.5 3 20 10 0 0.01 0.1 1 10 0 0.01 LOAD CURRENT(A) 1 10 0 20 40 60 80 100 LOAD CURRENT(A) Output Ripple Voltage Output Ripple Voltage Enable Startup IO=2A IO=0A VO/AC 20mV/div. VO/AC 20mV/div. SW 10V/div. SW 10V/div. IINDUCTOR 1A/div. 2.5 0.1 IO=0A VO 2V/div. EN 5V/div. SW 10V/div. IINDUCTOR 2A/div. IINDUCTOR 1A/div. 4ms/div. Enable Shutdown Enable Startup Enable Shutdown IO=0A IO=2A IO=2A VO 2V/div. EN 5V/div. VO 2V/div. EN 5V/div. VO 2V/div. EN 5V/div. SW 10V/div. SW 10V/div. SW 10V/div. IINDUCTOR 2A/div. IINDUCTOR 2A/div. IINDUCTOR 2A/div. 4ms/div. 1s/div. MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 5 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER OPERATION The converter uses internal N-Channel MOSFET switches to step-down the input voltage to the regulated output voltage. Since the high side MOSFET requires a gate voltage greater than the input voltage, a boost capacitor connected between SW and BS is needed to drive the high side gate. The boost capacitor is charged from the internal 5V rail when SW is low. FUNCTIONAL DESCRIPTION The MP2305S is a synchronous rectified, current-mode, step-down regulator. It regulates input voltages from 4.75V to 23V down to an output voltage as low as 0.923V, and supplies up to 2A of load current. The MP2305S uses current-mode control to regulate the output voltage. The output voltage is measured at FB through a resistive voltage divider and amplified through the internal transconductance error amplifier. The voltage at the COMP pin is compared to the switch current measured internally to control the output voltage. When the MP2305S FB pin exceeds 20% of the nominal regulation voltage of 0.923V, the over voltage comparator is tripped and the COMP pin and the SS pin are discharged to GND, forcing the high-side switch off. + VOUT CURRENT SENSE AMPLIFIER OVP 1.1V -OSCILLATOR FB + 340kHz 0.3V RAMP 5V BS -+ -- + 0.923V + VIN -- CLK -SS IN + ERROR AMPLIFIER S Q R Q 0.175 SW CURRENT COMPARATOR 0.115 VOUT COMP -- EN 2.5V + GND EN OK 1.2V LOCKOUT COMPARATOR OVP IN < 3.8V IN + INTERNAL REGULATORS 1.5V -- SHUTDOWN COMPARATOR Figure 1—Functional Block Diagram MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 6 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER APPLICATIONS INFORMATION COMPONENT SELECTION Setting the Output Voltage The output voltage is set using a resistive voltage divider from the output voltage to FB pin. The voltage divider divides the output voltage down to the feedback voltage by the ratio: VFB = VOUT R2 R1 + R2 Where VFB is the feedback voltage and VOUT is the output voltage. larger value inductor will have a larger physical size, higher series resistance, and/or lower saturation current. A good rule for determining the inductance to use is to allow the peak-to-peak ripple current in the inductor to be approximately 30% of the maximum switch current limit. Also, make sure that the peak inductor current is below the maximum switch current limit. The inductance value can be calculated by: L= Thus the output voltage is: VOUT = 0.923 × R1 + R2 R2 R2 can be as high as 100kΩ, but a typical value is 10kΩ. Using the typical value for R2, R1 is determined by: R1 = 10.83 × ( VOUT − 0.923 ) (kΩ) ⎛ VOUT V × ⎜⎜1 − OUT f S × ΔI L ⎝ VIN ⎞ ⎟⎟ ⎠ Where VOUT is the output voltage, VIN is the input voltage, fS is the switching frequency, and ΔIL is the peak-to-peak inductor ripple current. Choose an inductor that will not saturate under the maximum inductor peak current. The peak inductor current can be calculated by: For example, for a 3.3V output voltage, R2 is 10kΩ, and R1 is 26.1kΩ. ILP = ILOAD + ⎛ VOUT V × ⎜1 − OUT 2 × f S × L ⎜⎝ VIN ⎞ ⎟⎟ ⎠ Inductor where ILOAD is the load current. The inductor is required to supply constant Table 1 lists a number of suitable inductors from current to the output load while being driven by various manufacturers. The choice of which style the switched input voltage. A larger value inductor to use mainly depends on the price vs. inductor will result in less ripple current that will size requirements and any EMI requirement. result in lower output ripple voltage. However, the Table 1—Inductor Selection Guide Inductance (µH) Max DCR (Ω) Current Rating (A) Dimensions L x W x H (mm3) 7440650068 6.8 0.033 3.6 10x10x2.8 744066100 10 0.035 3.6 10x10x3.8 744066150 15 0.050 3.2 10x10x3.8 SLF10165T-6R8N4R33PF 6.8 0.014 4.3 SLF10165T-100M3R83PF 10 0.0185 3.8 SLF10165T-150M3R13PF 15 0.027 3.1 10x10x4.5 10x10x4.5 10x10x4.5 #B952AS-6R8N 6.8 0.035 3.1 10.4x10.4x4.8 #B892NAS-100M 10 0.0225 4.2 12.3x12.3x4.5 #B892NAS-150M 15 0.0355 3.2 12.3x12.3x4.5 Part Number Wurth Electronics TDK Toko MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 7 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER Optional Schottky Diode During the transition between high-side switch and low-side switch, the body diode of the lowside power MOSFET conducts the inductor current. The forward voltage of this body diode is high. An optional Schottky diode may be paralleled between the SW pin and GND pin to improve overall efficiency. Table 2 lists example Schottky diodes and their Manufacturers. Table 2—Diode Selection Guide Part Number Voltage/Current Rating B230 SL23 30V, 2A 30V, 2A MBRS230 30V, 2A Vendor Diodes, Inc. Vishay, Inc. International Rectifier Input Capacitor The input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the AC current to the step-down converter while maintaining the DC input voltage. Use low ESR capacitors for the best performance. Ceramic capacitors are preferred, but tantalum or low-ESR electrolytic capacitors may also suffice. Choose X5R or X7R dielectrics when using ceramic capacitors. Since the input capacitor (C1) absorbs the input switching current it requires an adequate ripple current rating. The RMS current in the input capacitor can be estimated by: I C1 = ILOAD × VOUT ⎛⎜ VOUT ⎞⎟ × 1− VIN ⎜⎝ VIN ⎟⎠ The worst-case condition occurs at VIN = 2VOUT, where IC1 = ILOAD/2. For simplification, choose the input capacitor whose RMS current rating greater than half of the maximum load current. The input capacitor can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor, i.e. 0.1μF, should be placed as close to the IC as possible. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at input. The input voltage ripple for low ESR capacitors can be estimated by: ΔVIN = ⎛ ILOAD V V × OUT × ⎜⎜1 − OUT C1 × fS VIN ⎝ VIN ⎞ ⎟⎟ ⎠ Where C1 is the input capacitance value. Output Capacitor The output capacitor is required to maintain the DC output voltage. Ceramic, tantalum, or low ESR electrolytic capacitors are recommended. Low ESR capacitors are preferred to keep the output voltage ripple low. The output voltage ripple can be estimated by: ΔVOUT = VOUT ⎛ V × ⎜1 − OUT f S × L ⎜⎝ VIN ⎞ ⎞ ⎛ 1 ⎟ ⎟⎟ × ⎜ R ESR + ⎜ ⎟ 8 f C 2 × × S ⎠ ⎝ ⎠ Where C2 is the output capacitance value and RESR is the equivalent series resistance (ESR) value of the output capacitor. In the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance. The output voltage ripple is mainly caused by the capacitance. For simplification, the output voltage ripple can be estimated by: ΔVOUT = ⎛ V × ⎜⎜1 − OUT VIN × L × C2 ⎝ VOUT 8 × fS 2 ⎞ ⎟⎟ ⎠ In the case of tantalum or electrolytic capacitors, the ESR dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated to: ΔVOUT = VOUT ⎛ V × ⎜⎜1 − OUT fS × L ⎝ VIN ⎞ ⎟⎟ × R ESR ⎠ The characteristics of the output capacitor also affect the stability of the regulation system. The MP2305S can be optimized for a wide range of capacitance and ESR values. Compensation Components MP2305S employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the COMP pin. COMP pin is the output of the internal transconductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the control system. MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 8 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER The DC gain of the voltage feedback loop is given by: A VDC = R LOAD × G CS × A EA × VFB VOUT Where AVEA is the error amplifier voltage gain; GCS is the current sense transconductance and RLOAD is the load resistor value. The system has two poles of importance. One is due to the compensation capacitor (C3) and the output resistor of the error amplifier, and the other is due to the output capacitor and the load resistor. These poles are located at: fP1 GEA = 2π × C3 × A VEA fP2 = 1 2π × C2 × R LOAD Where GEA is the error amplifier transconductance. The system has one zero of importance, due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at: f Z1 1 = 2π × C3 × R3 The system may have another zero of importance, if the output capacitor has a large capacitance and/or a high ESR value. The zero, due to the ESR and capacitance of the output capacitor, is located at: fESR = 1 2π × C2 × R ESR In this case, a third pole set by the compensation capacitor (C6) and the compensation resistor (R3) is used to compensate the effect of the ESR zero on the loop gain. This pole is located at: fP 3 = 1 2π × C6 × R3 The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency where the feedback loop has the unity gain is important. Lower crossover frequencies result in slower line and load transient responses, while higher 3. Determine if the second compensation capacitor (C6) is required. It is required if the crossover frequencies could cause system instability. A good rule of thumb is to set the crossover frequency below one-tenth of the switching frequency. Table 3 lists the typical values of compensation components for some standard output voltages with various output capacitors and inductors. The values of the compensation components have been optimized for fast transient responses and good stability at given conditions. Table 3—Compensation Values for Output Voltage/Capacitor Combinations Typical VOUT L1 C2 R3 C3 C6 1.8V 6.8uH 22μF/6.3V Ceramic 3.3kΩ 5.6nF None 3.3V 10μH 22μF/6.3V Ceramic 5.6kΩ 3.3nF None 5.0V 15μH 22μF/6.3V Ceramic 10kΩ 2.2nF None 12.0V 22μH 22μF/16V Ceramic 15kΩ 1.0nF None To optimize the compensation components, the following procedure can be used. 1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine the R3 value by the following equation: R3 = 2π × C2 × fC VOUT 2π × C2 × 0.1 × fS VOUT × < × GEA × GCS VFB GEA × GCS VFB Where fC is the desired crossover frequency which is typically below one tenth of the switching frequency. 2. Choose the compensation capacitor (C3) to achieve the desired phase margin. For applications with typical inductor values, setting the compensation zero, fZ1, below one-forth of the crossover frequency provides sufficient phase margin. Determine the C3 value by the following equation: C3 > 4 2π × R3 × f C where R3 is the compensation resistor. ESR zero of the output capacitor is located at MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 9 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER less than half of the switching frequency, or the following relationship is valid: f 1 < S 2π × C 2 × R ESR 2 In these cases, an external BST diode is recommended from the output of the voltage regulator to BST pin, as shown in Figure 2 External BST Diode IN4148 BST If this is the case, then add the second compensation capacitor (C6) to set the pole fP3 at the location of the ESR zero. Determine the C6 value by the equation: C2 × R ESR C6 = R3 External Bootstrap Diode An external bootstrap diode may enhance the efficiency of the regulator, and it will be a must if the applicable condition is: z VOUT=5V or 3.3V; and z duty cycle is high: D= MP2305 S SW CBST 0.01 L + COUT 5V or 3.3V Figure 2—Add Optional External Bootstrap Diode to Enhance Efficiency The recommended external BST diode is IN4148, and the BST cap is 0.01µF. VOUT >65% VIN MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 10 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER TYPICAL APPLICATION CIRCUIT INPUT 4.75V to 23V 2 1 IN 7 OUTPUT 1.8V 2A BS 3 SW EN MP2305S 8 SS GND 5 FB COMP 4 6 C6 (optional) Figure 3—MP2305S with 1.8V Output, 22µF/6.3V Ceramic Output Capacitor C5 10nF INPUT 8V to 23V 2 7 1 IN BS 3 SW EN MP2305S 8 SS GND FB COMP 4 OUTPUT 5.0V 2A 5 6 C6 (optional) C3 2.2nF Figure 4—MP2305S with 5.0V Output, 22µF/6.3V Ceramic Output Capacitor MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 11 MP2305S – 2A, 23V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER PACKAGE INFORMATION SOIC8 0.189(4.80) 0.197(5.00) 8 0.050(1.27) 0.024(0.61) 5 0.063(1.60) 0.150(3.80) 0.157(4.00) PIN 1 ID 1 0.228(5.80) 0.244(6.20) 0.213(5.40) 4 TOP VIEW RECOMMENDED LAND PATTERN 0.053(1.35) 0.069(1.75) SEATING PLANE 0.004(0.10) 0.010(0.25) 0.013(0.33) 0.020(0.51) 0.0075(0.19) 0.0098(0.25) SEE DETAIL "A" 0.050(1.27) BSC SIDE VIEW FRONT VIEW 0.010(0.25) x 45o 0.020(0.50) GAUGE PLANE 0.010(0.25) BSC 0o-8o 0.016(0.41) 0.050(1.27) DETAIL "A" NOTE: 1) CONTROL DIMENSION IS IN INCHES. DIMENSION IN BRACKET IS IN MILLIMETERS. 2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. 3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. 4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.004" INCHES MAX. 5) DRAWING CONFORMS TO JEDEC MS-012, VARIATION AA. 6) DRAWING IS NOT TO SCALE. NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications. Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications. MP2305S Rev. 1.02 www.MonolithicPower.com 10/22/2013 MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited. © 2013 MPS. All Rights Reserved. 12