Renesas HIP2103-4DEMO1Z 60v, 1a/2a peak, half bridge driver with 4v uvlo Datasheet

DATASHEET
HIP2103, HIP2104
FN8276
Rev 0.00
November 27, 2013
60V, 1A/2A Peak, Half Bridge Driver with 4V UVLO
The HIP2103 and HIP2104 are half bridge drivers designed for
applications using DC motors, three-phase brushless DC
motors, or other similar loads.
Features
Two inputs (HI and LI) are provided to independently control
the high side driver (HO) and the low side driver (LO).
Furthermore, the two inputs can be configured to
enable/disable the device, thus lowering the number of
connections to a microcontroller and lowering costs.
• 3.3V and 12V LDOs with dedicated enable pins (HIP2104)
• 60V maximum bootstrap supply voltage
• 5µA sleep mode quiescent current
• 4V undervoltage lockout
• 3.3V or 5V CMOS compatible inputs with hysteresis
• Integrated bootstrap FET (replaces traditional boot strap diode)
The very low IDD bias current in the Sleep Mode prevents
battery drain when the device is not in use, thus eliminating
the need for an external switch to disconnect the driver from
the battery.
Applications
• Half bridge, full bridge and BLDC motor drives
(see Figures 21, 22, 23)
A fail-safe mechanism is included to improve system reliability
and to minimize the possibility of catastrophic bridge failures
due to controller malfunction. Internal logic prevents both
outputs from turning on simultaneously when HI and LI are
both high simultaneously. Dead-time is still required on the
rising edge of the HI (or LI) input when the LI (or HI) input
transitions low.
• UPS and inverters
• Class-D amplifiers
• Any switch mode power circuit requiring a half bridge driver
Related Literature
• AN1896 “HIP2103, HIP2104 Evaluation Board User’s Guide”
Integrated pull-down resistors on all of the inputs (LI, HI, VDen
and VCen) reduces the need for external resistors. An active
low resistance pull-down on the LO output ensures that the low
side bridge FET remains off during the Sleep Mode or when
VDD is below the undervoltage lockout (UVLO) threshold.
• AN1899 “HIP2103, HIP2104 3-phase, Full or Half Bridge
Motor Drive User’s Guide”
The HIP2104 has a 12V linear regulator and a 3.3V linear
regulator with separate enable pins. The 12V regulator
provides internal bias for VDD and the 3.3V regulator provides
bias for an external microcontroller (and/or other low voltage
ICs), thus eliminating the need for discrete LDOs or DC/DC
converters.
The HIP2103 is available in a 3x3mm, 8 Ld TDFN package and
the HIP2104 is available in a 4x4mm, 12 Ld DFN package.
VBAT
5.5
VBAT
VBAT
5.0
VDen
VCen
VCC
4.5
HB
VDD
HO
HI
HO
HI
HIP2104
HS
LI
LO
µController
VSS
DC
MOTOR
HS
HIP2103
LO
LI
VDD
IBAT (µA)
HB
VDD
4.0
3.5
3.0
VSS
2.5
EPAD
EPAD
2.0
10
20
30
40
VBAT (VDC)
FIGURE 1. TYPICAL FULL BRIDGE APPLICATION
FN8276 Rev 0.00
November 27, 2013
FIGURE 2. HIP2104 SHUTDOWN CURRENT vs VBAT
Page 1 of 21
50
HIP2103, HIP2104
Block Diagram
VBAT
VDD
VCC
155C
OT
3.3V LDO
12V LDO
1 MSEC
DELAY
VCen
1 MSEC
DELAY
VDen
100k
100K
2104
2103
VDD
SEE FIGURES 3 AND 4 FOR
SLEEP MODE TIMING DETAILS
1
HB
4V
UNDER
VOLTAGE
2104
2103
VBAT
Boot FET
20 US
DELAY
R
20 US
DELAY
LOGIC
BIAS
Q
S
SLEEP
MODE
LEVEL
SHIFT
HI
100k
HO
4V
UNDER
VOLTAGE
Logic prevents
shoot-through
when LI and HI
are both high
E
P
A
D
2M
HS
VDD
LO
LI
Active pull-down 100
keeps bridge FET
off during UV, OT,
or sleep
100k
VSS
Symbol Glossary
10 US
DELAY
Time delay functional block with
rising edge prop delay (as indicated
by the rising arrow on the input) and
minimal falling edge delay.
HIP2103
FN8276 Rev 0.00
November 27, 2013
2104
2103
Optional connections as indicated by
part numbers
HIP2104
Page 2 of 21
HIP2103, HIP2104
Pin Configurations
HIP2104
(12 LD 4x4 DFN)
TOP VIEW
HIP2103
(8 LD 3x3 TDFN)
TOP VIEW
VDD
1
HI
2
LI
3
VSS
4
EPAD
(VSS)
8
HB
VDen
1
12
VBAT
7
HO
VCen
2
11
HB
6
HS
VCC
3
10
HO
5
LO
VDD
4
9
HS
HI
5
8
LO
LI
6
7
VSS
EPAD
(VSS)
Pin Descriptions
HIP2103
HIP2104
8 LD
TDFN
12 LD
DFN
SYMBOL
DESCRIPTION
-
1
VDen
(HIP2104 only) VDD enable input, 3.3V or 5V logic compatible, VBAT tolerant. VDD output is turned on after
1ms debouncing period.
-
2
VCen
(HIP2104 only) VCC enable input, 3.3V or 5V logic compatible. VBAT tolerant. VCC output is turned on after
1ms debouncing period.
-
3
VCC
(HIP2104 only) 3.3V output voltage of linear regulator, 75mA. Enabled by VCen.
1
4
VDD
(HIP2103) Input voltage 14V max.
(HIP2104) 0utput voltage of linear regulator, 12V nominal, 75mA. Enabled by VDen.
2
5
HI
High side input, 3.3V or 5V logic compatible. (HI -> HO).
3
6
LI
Low side Input, 3.3V or 5V logic compatible. (LI -> LO).
4
7
VSS
Signal ground.
5
8
LO
Low side driver Output. (LI ->LO).
6
9
HS
High side FET Source connection (low side boot capacitor connection).
7
10
HO
High side driver Output. (HI -> HO)
8
11
HB
High side Boot capacitor.
-
12
VBAT
(HIP2104 only) Positive battery (bridge voltage) connection.
EP
EP
EPAD
Exposed Pad, must be connected to signal ground.
FN8276 Rev 0.00
November 27, 2013
Page 3 of 21
HIP2103, HIP2104
Ordering Information
PART NUMBER
(Notes 1, 2, 3, 4)
PART
MARKING
UVLO
(V)
VCC
REGULATOR
(V)
VDD
REGULATOR
(V)
PACKAGE
(Pb-Free)
PKG.
DWG. #
HIP2103FRTAAZ
DZBF
4.0
N/A
N/A
8 Ld 3x3 TDFN
L8.3x3A
HIP2104FRAANZ
2104AN
4.0
3.3
12
12 Ld 4x4 DFN
L12.4x4A
HIP2103-4DEMO1Z
HIP2103, HIP2104 3-phase, Full, or Half Bridge Motor Drive Demonstration Board
HIP2103_4MBEVAL1Z
HIP2103, HIP2104 Evaluation Board
NOTES:
1. Add “-T*”, suffix for tape and reel. Please refer to TB347 for details on reel specifications.
2. These Intersil Pb-free plastic packaged products employ special Pb-free material sets, molding compounds/die attach materials, and 100% matte
tin plate plus anneal (e3 termination finish, which is RoHS compliant and compatible with both SnPb and Pb-free soldering operations). Intersil
Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
3. For Moisture Sensitivity Level (MSL), please see device information page for HIP2103, HIP2104. For more information on MSL, please see Technical
Brief TB363.
4. All part numbers are rated -40°C to +125°C for the recommended operating junction temperature range.
FN8276 Rev 0.00
November 27, 2013
Page 4 of 21
HIP2103, HIP2104
Absolute Maximum Ratings
Thermal Information
(Note 5)
Supply Voltage VDD (HIP2103 only) . . . . . . . . . . . . . . . . . . . . . . -0.3V to 16V
Bridge Supply Voltage VBAT (HIP2104 Only) . . . . . . . . . . . . . . . -0.3V to 60V
High side Bias Voltage (VHB - VHS) (Note 10). . . . . . . . . . . . . . . -0.3V to 16V
Logic Inputs VCen, VDen (HIP2104 Only) . . . . . . . . . . - 0.3v to VBAT+ 0.3V
Logic Inputs LI, HI . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . - 0.3v to VDD+ 0.3V
Output Voltage LO. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . - 0.3V to VDD + 0.3V
Output Voltage HO . . . . . . . . . . . . . . . . . . . . . . . . . . VHS - 0.3V to VHB+ 0.3V
Voltage on HS (Note 9, 10) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -10V to 60V
Voltage on HB . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .VHS - 0.3V to 66V
Average Current in Boot Diode (Note 6). . . . . . . . . . . . . . . . . . . . . . . 100mA
Maximum Boot Cap Value . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10µF
Average Output Current in HO and LO (Note 6) . . . . . . . . . . . . . . . . 200mA
ESD Ratings
Human Body Model Class 2 (Tested per JESD22-A114E) . . . . . . 2000V
Charged Device Model Class IV . . . . . . . . . . . . . . . . . . . . . . . . . . . 1000V
Latch-Up (Tested per JESD-78B; Class 2, Level A) all pins. . . . . . . . 100mA
Thermal Resistance (Typical)
JA (°C/W) JC (°C/W)
8 Ld DFN Package (Notes 7, 8). . . . . . . . . .
46
7
12 Ld TDFN Package (Notes 7, 8) . . . . . . .
44
7
Max Power Dissipation at +25°C in free air
8 Ld DFN Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2.3W
12 Ld TDFN Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2.2W
Max Power Dissipation at +25°C on copper plane
8 Ld DFN Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14.3W
12 Ld TDFN Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14.3W
Storage Temperature Range. . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Maximum Operating Junction Temperature Range. . . . . . -40°C to +150°C
Nominal Over Temperature Shut-down . . . . . . . . . . . . . . . . . . . . . . .+155°C
Over Temperature Shut-down Range . . . . . . . . . . . . . . . +145°C to +165°C
Pb-Free Reflow Profile . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . see TB493
Recommended Operating Conditions (Note 5)
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . .-40°C to +125°C
Supply Voltage, VBAT(HIP2104 only) (Note 11). . . . . . . . . . . . . 5.0V to 50V
Supply Voltage, VDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4.5V to 14V
High Side Bias Voltage (VHB - VHS) (Note 10) . . . . . . . . . . . . . . -0.3V to 14V
Voltage on HS, Continuous, VHS (Notes 9, 10) . . . . . . . . . . . . . .-10V to 50V
Voltage on HB . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . VHS - 0.3V to 60V
Logic Inputs VCen, VDen (HIP2104 only). . . . . . . . . . . . . . . . . . . .0V to VBAT
Output Voltage (LO) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . GND to VDD
Output Voltage (HO) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . VHS to VHB
Average Output Current in HO and LO (Note 6) . . . . . . . . . . . . 0 to 150mA
CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product
reliability and result in failures not covered by warranty.
NOTES:
5. All voltages are referenced toVSS unless otherwise specified.
6. The average output current, when driving a power MOSFET or similar capacitive load, is the average of the rectified output current. The peak output
currents of this driver are self limiting by trans conductance or rDS(ON) and do not required any external components to minimize the peaks. If the
output is driving a non-capacitive load, such as an LED, the maximum output current must be limited by external means to less than the specified
recommended rectified average output current.
7. JA is measured in free air with the component mounted on a high effective thermal conductivity test board with “direct attach” features. See Tech
Brief TB379.
8. For JC, the “case temp” location is the center of the exposed metal pad on the package underside.
9. The the maximum value of VHS must be limited so that VHB does not exceed 60V.
10. The -10V limit for VHS has no time duration restrictions as far as the HS pin is concerned however, be aware that if the duration of the negative voltage
is significant with respect to the time constant to charge the boot capacitor (across HB and HS) the voltage on the boot capacitor can charge as high
as VDD - (-VHS) = (VDD +VHS) potentially violating the Voltage Rating for (VHB - VHS).
11. When VBAT < ~13V, the output of VDD will sag. The 5V minimum specified for VBAT is the minimum level for which the UVLO will not activate.
DC Electrical Specifications
VDD = VHB = 12V (for HIP2103), VSS = VHS = 0V, VBAT = 18V (for HIP2104), LI = HI = 0V. No load on HO
and LO unless otherwise specified. Boldface limits apply over the operating junction temperature range, -40°C to +125°C.
TJ = +25°C
PARAMETERS
SYMBOL
TEST CONDITIONS
TJ = -40°C to +125°C
MIN
TYP
MAX
MIN
(Note 12)
MAX
(Note 12)
UNITS
-2.5
+2.1
+4.8
- 5%
+ 5%
%
LINEAR BIAS SUPPLIES (HIP2104 only)
VDD Output Voltage Over Rated
Line, Load, and Temperature
VDD12
VDD Rated Output Current
IDDR
VDD Output Current Limit
(brick wall)
IDD12
VDD Drop Output Voltage
(Figure 7)
FN8276 Rev 0.00
November 27, 2013
VDdout
Nominal VDD = 12V
75
83
Load = 75mA
151
237
mA
80
245
mA
0.06
0.7
V
Page 5 of 21
HIP2103, HIP2104
DC Electrical Specifications
VDD = VHB = 12V (for HIP2103), VSS = VHS = 0V, VBAT = 18V (for HIP2104), LI = HI = 0V. No load on HO
and LO unless otherwise specified. Boldface limits apply over the operating junction temperature range, -40°C to +125°C. (Continued)
TJ = +25°C
PARAMETERS
VCC Output Voltage Over Rated
Line, Load, and Temperature
SYMBOL
VCC3.3
VCC Rated Output Current
ICDR
VCC Output Current Limit
(brick wall)
ICC
VCC Drop Output Voltage
(Figure 8)
VCdout
TEST CONDITIONS
Nominal VCC = 3.3V
TJ = -40°C to +125°C
MIN
TYP
MAX
MIN
(Note 12)
MAX
(Note 12)
UNITS
-3.9
+1.8
+4.3
- 5%
+ 5%
%
75
83
149
Load = 75mA
237
mA
80
245
mA
0.5
0.9
V
BIAS CURRENTS
VDD Sleep Mode Current
(HIP2103)
IDDS
HI = LI = 1, after 10 to 30µs delay
9.4
20
µA
VBAT Shutdown Current
(HIP2104)
IDDSbatt
VCen = VDen = 0, after 10 to 30µs
delay, VBAT = 50V
4.8
15
µA
VBAT (HIP2104) or VDD
(HIP2103) Operating Current
IDDO20
f = 20kHz, HI = LI = 50% square wave
VDD = 12V for HIP2103
832
1040
µA
IDDO10
f = 10kHz, HI = LI = 50% square wave
VDD = 12V for HIP2103
661
825
µA
HI = 1, LO = 0, VHS = 0V, VHB = 12V
135
160
µA
HB to HS Quiescent Current
IHBQ
HB to HS Operating Current
IHBS20K
LI = 0, HI = 50% square wave
20kHz, VHS = 0V, VHB = 12V
206
245
µA
IHBS10K
LI = 0, HI = 50% square wave
10kHz, VHS = 0V, VHB = 12V
167
193
µA
IHB20K
LI = 0, HI = 50% square wave
20kHz, VHB = 60V, VHS = 50V
201
240
µA
IHB10K
LI = 0, HI = 50% square wave
10kHz, VHB = 60V, VHS = 50V
164
190
µA
HB to VSS Operating Current
HB to VSS Quiescent Current
IHBQ
LI = HI = 0V; VHB = 60V, VHS = 50V
120
145
µA
HS to VSS Current, Sleep Mode
IHBS
LI = HI = 1; HB open, VHS = 50V
0.03
+1
µA
INPUT PINS
Low Level Input Voltage
Threshold
VIL
High Level Input Voltage
Threshold
VIH
Input Voltage Hysteresis
VHys
Low Level Input Voltage
Threshold
VIL
High Level Input Voltage
Threshold
VIH
Input Voltage Hysteresis
Input Pull-Down
1.44
1.18
1.63
V
2.06
1.73
2.4
V
0.62
0.48
0.85
V
1.13
0.9
1.25
V
1.63
1.38
1.84
V
VHys
0.50
0.36
0.63
V
RI
100
80
130
kΩ
4.2
3.98
4.36
V
0.34
0.267
0.37
V
VDD = 12V
VDD = 5V
UNDERVOLTAGE LOCKOUT (Note 13)
VDD Falling Threshold
VUVF4
VDD Threshold Hysteresis
VUVH
4V option
BOOT FET
FN8276 Rev 0.00
November 27, 2013
Page 6 of 21
HIP2103, HIP2104
DC Electrical Specifications
VDD = VHB = 12V (for HIP2103), VSS = VHS = 0V, VBAT = 18V (for HIP2104), LI = HI = 0V. No load on HO
and LO unless otherwise specified. Boldface limits apply over the operating junction temperature range, -40°C to +125°C. (Continued)
TJ = +25°C
PARAMETERS
On Resistance
SYMBOL
RDon
TEST CONDITIONS
MIN
TYP
TJ = -40°C to +125°C
MAX
MIN
(Note 12)
MAX
(Note 12)
UNITS
IVDD-HB = 75mA, HI = 0, LI = 1
8.2
2.42
15
Ω
LO GATE DRIVER
Sinking rDS(ON)
RDSLOL
ILO = 100mA, LI = 0
2.68
0.61
11
Ω
Sourcing rDS(ON)
RDSLOH
ILO = -75mA, HI = 1
6.47
2.3
15
Ω
ILOH12
HI = 1
VDD = 12V, Cload = 1000pF
ILOH5
HI = 1
VDD = 5V, Cload = 1000pF
(HIP2103 only)
ILOL12
HI = 0
VDD = 12V, Cload = 1000pF
ILOL5
HI = 0
VDD = 5V, Cload = 1000pF
(HIP2103 only)
Peak Pull-Up Current
Peak Pull-Down Current
1
A
A
2
A
A
HO GATE DRIVER
Sinking rDS(ON)
RDSHOL
IHO = 100mA, HI = 0
6.1
4.4
11
Ω
Sourcing rDS(ON)
RDSHOH
IHO = -100mA, HI = 1
11.9
9.7
15
Ω
IHOH12
HI = 1
VDD = 12V, Cload = 1000pF
1
A
IHOH5
HI = 1
VDD = 5V, Cload = 1000pF
(HIP2103 only)
1
A
IHOL12
HI = 0
VDD = 12V, Cload = 1000pF
2
A
IHOL5
HI = 0
VDD = 5V, Cload = 1000pF
(HIP2103 only)
Peak Pull-Up Current
Peak Pull-Down Current
A
NOTES:
12. Parameters with MIN and/or MAX limits are 100% tested at +25°C, unless otherwise specified. Temperature limits established by characterization
and are not production tested.
13. The UV lockout does not disable the VDD and VCC outputs.
FN8276 Rev 0.00
November 27, 2013
Page 7 of 21
HIP2103, HIP2104
AC Electrical Specifications VDD = 12V, GND = 0V, No Load on OUTA or OUTB, Unless Otherwise Specified. VDD load = 1µF and VCC
load = 1µF (HIP2104 only) Boldface limits apply over the operating junction temperature range, -40°C to +125°C.
TJ = +25°C
PARAMETERS
SYMBOL
TEST CONDITIONS
MIN
TYP
MAX
TJ = -40°C to +125°C
MIN
MAX
UNITS
VDen and VCen Turn-On Delay
(Figure 5) (HIP2104 only)
tDen
tCen
VDen = VCen = 1,
VCC = VDD = 10%,
VBAT = 50V
1.69
1.0
2.5
ms
VDen and VCen Turn-on Delay
(Figure 5) (HIP2104 only)
tDen
tCen
VDen = VCen = 1,
VCC = VDD = 10%,
VBAT = 18V
1.68
1.1
2.54
ms
VDen and VCen Turn-on Delay Matching
(Figure 5) (VDen - VCen) (HIP2104 only)
tVenM
VDen = VCen = 1,
VCC = 10%, VDD = 10%
VBAT = 50V
40
-290
340
ns
VDen and VCen Turn-on Delay Matching
(Figure 5) (VDen - VCen) (HIP2104 only)
tVenM
VDen = VCen = 1,
VCC = 10%, VDD = 10%
VBAT = 18V
40
-290
350
ns
LO Turn-Off Propagation Delay
(LI to LO falling) (Figure 6)
tFL12
HI = 0, LI = 1 to 0
VDD = 12V
27
13
39
ns
tFL5
HI = 0, LI = 1 to 0
VDD = 5V (HIP2103 only)
30
23
46
ns
tFH12
LI = 0, HI = 1 to 0
VDD = 12V
23
10
35
ns
tFH5
LI = 0, HI = 1 to 0
Vv = 5V (HIP2103 only)
27
19
38
ns
tRL12
HI = 0, LI = 0 to 1
VDD = 12V
21
7
32
ns
tRL5
HI = 0, LI = 0 to 1
VDD = 5V (HIP2103 only)
25
12
37
ns
tRH12
LI = 0, HI = 0 to 1
VDD = 12V
23
9
35
ns
tRH5
LI = 0, HI = 0 to 1
VDD = 5V (HIP2103 only)
28
15
40
ns
HO Turn-Off Propagation Delay
(HI to HO falling) (Figure 6)
LO Turn-On Propagation Delay
(LI to LO rising) (Figure 6)
HO Turn-On Propagation Delay
(HI to HO rising) (Figure 6)
Turn-On/Off Propagation Mismatch
(HO rising to LO falling) (Figure 6)
tMONHL
LI = 1 -> 0
HI = 0 -> 1
-2.5
-8
+3
ns
Turn-On/Off Propagation Mismatch
(LO rising to HO falling) (Figure 6)
tMONLH
HI = 1 -> 0
LI = 0 -> 1
-4.2
-9.0
+5.4
ns
tR12
CL = 1nF
VDD = 12V
20.5
7
35
ns
tR5
CL = 1nF
VDD = 5V (HIP2103 only)
19.5
6
32
ns
tR12
CL = 1nF
VDD = 12V
21
8
35
ns
tR5
CL = 1nF
VDD = 5V (HIP2103 only)
21
8
34
ns
tF12
CL = 1nF
VDD = 12V
17
3
30
ns
tF5
CL = 1nF
VDD = 5V (HIP2103 only)
17
3
30
ns
tF12
CL = 1nF
VDD = 12V
16
2
30
ns
tF5
CL = 1nF
VDD = 5V (HIP2103 only)
16
1.5
29
ns
LO Output Rise Time
(10% to 90% )
HO Output Rise Time
(10% to 90%)
LO Output Fall Time
(90% to 10%)
HO Output Fall Time
(90% to 10%)
FN8276 Rev 0.00
November 27, 2013
Page 8 of 21
HIP2103, HIP2104
AC Electrical Specifications VDD = 12V, GND = 0V, No Load on OUTA or OUTB, Unless Otherwise Specified. VDD load = 1µF and VCC
load = 1µF (HIP2104 only) Boldface limits apply over the operating junction temperature range, -40°C to +125°C. (Continued)
TJ = +25°C
PARAMETERS
SYMBOL
TEST CONDITIONS
MIN
TYP
TJ = -40°C to +125°C
MAX
MIN
MAX
UNITS
Time Delay to Set Sleep Mode
(Note 14, Figure 4)
tSlpS
HI = LI = 0 -> 1
17
9
27
µs
Time Delay to Reset Sleep Mode
(Note 14, Figure 4)
tSlpR
HI = 0, LI = 0 -> 1
17
9
27
µs
NOTE:
14. When HI and LI are on simultaneously, HO and LO are never on simultaneously. This feature is intended to initiate sleep. This feature cannot be used
to prevent shoot-through for normal alternating switching between LI and HI. Dead time must be provided when HI = 0 -> LI = 1, or LI = 0 -> HI = 1.
See Timing Diagrams (Figure 4).
Timing Diagrams
(Vden and VCen apply to HIP2104 only)
2M to HS
HO = Logic inputs
2M to HS
HO
LO
100 to LS
LO = Logic inputs
100 to LS
LO
*SLEEP
tSlpS
tSlpR
~
~
~
~
UVLO
~
~
HO
VDD
UVLO
VDD
~
~
UV threshold
*SLEEP
VDen
tVDen
~
~
VDen
VCC
~
~
VCC
VCen
VCen
tVCen
*Sleep is an internal state. Minimal IDD or IBAT current results when active (high).
FIGURE 3. VDD POWER-ON/OFF TIMING FOR SLEEP MODE
FN8276 Rev 0.00
November 27, 2013
Page 9 of 21
HIP2103, HIP2104
Timing Diagrams
(Continued)
2M to HS
HO
100 to LS
LO
~
~
LO
HO
dead time
provided by
controller
SLEEP*
~
~~
~
SLEEP*
HI
~
~
HI
LI
LI
20µs
20µs
* Sleep mode is enabled when HI=LI=1 for 20usecs.
Sleep mode is cleared when HI=0 and LI = 1 for 20usecs.
FIGURE 4. SLEEP MODE ENABLED OR CLEARED BY HI AND LI INPUTS
10% VDD
VDD
VDD
10% VCC
VCC
VCC
tVDen
VDen
VDen
VCen
VCen
tVCen
tVenM
FIGURE 5. VCEN AND VDEN DELAY MATCHING
tFH
tRH
tMONHL
tMONLH
HO
HO
HI
HI
LO
LO
LI
LI
tRL
tFL
FIGURE 6. PROPAGATION DELAYS
FN8276 Rev 0.00
November 27, 2013
Page 10 of 21
HIP2103, HIP2104
Typical Performance Curves
4
14
12
NO LOAD
3
160Ω (75mA @ 12V)
VCC (OUTPUT)
VDD (output)
10
8
6
NO LOAD
44Ω (75mA @ 3.3V)
2
1
4
2
0
0
20
18
16
14
12
10
8
6
4
2
6
2
1
FIGURE 8. VCC DROPOUT vs VBAT (HIP2104 ONLY)
5.5
275
5.0
270
265
IBAT (µA)
4.5
IBAT (µA)
3
VBAT (INPUT)
FIGURE 7. VDD DROPOUT vs VBAT (HIP2104 ONLY)
4.0
3.5
3.0
260
255
250
245
2.5
2.0
4
5
0
240
10
20
30
235
50
40
10
20
30
VBAT (VDC)
50
40
VBAT (VDC)
FIGURE 9. HIP2104 SHUTDOWN CURRENT
(VCEN = VDEN = 0, HS = VBAT)
FIGURE 10. HIP2104 QUIESCENT IBAT (VCEN = VDEN = LI = HI = 1)
900
4
IBAT, 20k
800
700
3
IBAT, 10kHz
VCC (VDC)
IBAT (µA)
600
500
400
2
300
1
0kHz, +25°C
200
100
0
0
10
20
30
40
50
VBAT (VDC)
FIGURE 11. HIP2104 VDD OPERATING CURRENT LIMIT
FN8276 Rev 0.00
November 27, 2013
60
0
0
25
50
75
100
125
ICC (mA)
FIGURE 12. HIP2104 VCC CURRENT LIMIT
Page 11 of 21
150
HIP2103, HIP2104
Typical Performance Curves (Continued)
10
14
9
12
8
7
IBAT (µA)
VDD (VDC)
10
8
6
6
5
4
4
3
2
0
2
0
50
100
1
150
5
6
7
8
FIGURE 13. HIP2104 VDD CURRENT LIMIT, 0kHz
IBAT, 20kHz
UVLO (HO AND LO) (V)
600
IDD (µA)
12
13
14
4.3
700
IBAT, 10kHz
500
400
300
200
5
7
9
3.9
3.5
-40
15
13
11
4.1
3.7
IBAT, 0kHz
100
-20
0
VDD (VDC)
20
40
60
80
100
120
140
TEMPERATURE (°C)
FIGURE 15. HIP2103 OPERATING CURRENT
FIGURE 16. HIP2103, HIP2104 UNDERVOLTAGE LOCKOUT
20
9
18
8
16
7
SOURCING
14
6
Ohms
12
Ohms
11
4.5
800
10
8
5
4
SINKING
3
6
2
4
1
2
0
10
FIGURE 14. HIP2103 SLEEP CURRENT (HI = LI = 1)
900
0
9
VBAT (VDC)
IDD (mA)
-40
-20
0
20
40
60
80
TEMPERATURE (°C)
FIGURE 17. BOOT FET RESISTANCE
FN8276 Rev 0.00
November 27, 2013
100
120
140
0
-40
-20
0
20
40
60
80
100
120
TEMPERATURE (°C)
FIGURE 18. HO OUTPUT RESISTANCE
Page 12 of 21
140
HIP2103, HIP2104
Typical Performance Curves (Continued)
9
8
SOURCING
7
Ohms
6
5
4
3
SINKING
2
1
0
-40
-20
0
20
40
60
80
100
120
140
TEMPERATURE (°C)
FIGURE 19. LO OUTPUT RESISTANCE
Functional Description
The following functional description references the “Block
Diagram” on page 2.
Overview
The HIP2103 has independent control inputs, LI and HI, for each
output, LO and HO. There is no logic inversion for these
input/output pairs. To minimize the possibility of shoot-through
failures of the bridge FETs caused by improper LI and HI signals
from an external controller, internal logic in the driver prevents
both outputs being high simultaneously. When either input is
high, the high input must go low before a high on the other input
propagates to its respective drive output. If both inputs are high
simultaneously, both output are low. If one input is high, followed
by the other input going high, the internal logic prevents any
shoot through. Note that the internal logic does not prevent
shoot-through if the dead-time provided by the external controller
is not sufficiently long as required by the turn-on/off times of the
bridge FETS.
If both inputs are high simultaneously for longer than 30µs, the
driver initiates a Sleep Mode to reduce the bias current to
minimize the battery drain. When in Sleep Mode, the HO output
is in a high-impedance state (2MΩ between HO and HS) and the
LO output is held low with an active 100Ω pull-down resistor. The
100Ω pull-down prevents inadvertent shoot-through resulting
from transients on the bridge voltage while both drivers are in the
Sleep Mode.
The undervoltage lockout (UVLO) on VDD drives HO and LO low
when VDD is less that the UV threshold. Sleep Mode is initiated if
UVLO is asserted for longer than 30µs.
The high-side driver bias is established by the boot capacitor
connected between HB and HS. The charge on the boot capacitor
is provided by the internal boot FET that is connected between
VDD and HB. The current path to charge the boot cap is enabled
(boot FET is on) when the drain voltage on the low-side bridge FET
(VHO) is <1V and when HO = 0. When the boot FET is on, the boot
cap is charged to approximately VDD.
FN8276 Rev 0.00
November 27, 2013
The boot FET turns off when H0 = 1. The boot capacitor provides
the charge necessary to turn on the FET and maintains the bias
voltage on the high side driver for the duration of the period while
the FET is on. See the following for details on selecting the boot
capacitor value.
The peak charge current is limited in amplitude by the inherent
resistance of the boot FET and by the delta voltage between VDD
and the drain-source voltage of the low-side bridge FET (VHS) less
the boot cap voltage. Assuming that the on time of the low-side
FET is sufficiently long to fully charge the boot capacitor, the boot
voltage charges very close to VDD (less the voltage across the
drain-source of the low-side bridge FET).
When the HI input transitions high, the high-side bridge FET is
driven on. Because the HS node is connected to the source of the
high-side FET, the HS node rises almost to the level of the bridge
voltage, VBAT (less the conduction voltage across the bridge FET).
Because the boot capacitor voltage is referenced to the source
voltage of the high-side FET, the HB node is VDD volts above the
HS node. Simultaneously with HI = 1, the boot FET is turned off
preventing the boot capacitor from discharging back to VDD.
Because the high-side driver circuit is referenced to the HS node,
the HO output is now approximately VHB + VBAT above ground.
During the low to high transition of the phase node (HS), the boot
capacitor sources the necessary gate charge to fully enhance the
high-side bridge FET gate. After the gate of the bridge FET is fully
charged, the boot capacitor no longer sources charge to the gate
but continues to provide bias current to the high-side driver
through out the period while the high-side bride FET is on.
To prevent the voltage on the boot capacitor from drooping
excessively, the boot capacitor value must be sized appropriately.
If the boot voltage droops to the UVLO threshold, the high-side
FET is turned off to prevent damage due to insufficient gate
voltage.
Page 13 of 21
HIP2103, HIP2104
The boot capacitor value is chosen not only to supply the internal
bias current of the high-side driver but also, and more
significantly, to provide the gate charge of the driven FET without
causing the boot voltage to sag excessively. In practice, the boot
capacitor should have a total charge that is about 20 times the
gate charge of the driven power FET for approximately a 5% drop
in voltage after charge has been transferred from the boot
capacitor to the gate capacitance.
The following parameters are required to calculate the value of
the boot capacitor for a specific amount of voltage droop when
using the HIP2103, HIP2104. In the following example, some
values used are specific to the HIP2103, HIP2104 and others are
arbitrary. The values should be changed to comply with the
actual application.
VDD = 12V
VHB = VDD = VHO
Period = 100µs
This is the nominal value of VDD for
the HIP2104
High side driver bias voltage
referenced to VHS
This is the longest expected switching
period
IHB = IHBS20K + IHB20K = 295µA High side driver bias current at 20kHz
RGS = 10kΩ
Gate-source resistor
Ripple = 5%
Desired ripple voltage on the boot cap
Igate_leak = 100nA
Gate leakage current (from vendor
datasheet)
Qg40_12V = 45nC
From Figure 20
The following equations calculates the total charge required for
the Period:
Qc = Qg40_12V + Period x (IHB + VHO/RGS + Igate_leak)
Cboot = Qc/(Ripple * VDD)
Cboot = 0.324µF
If the gate to source resistor is removed (RGS is usually not
needed or recommended), then:
Cboot = 0.124µF
16
14
Vds = 80V
Vgs, GATE VOLTAGE
Selecting the Boot Capacitor Value
12
10
Vds = 40V
8
6
4
2
0
0
5
10
15
20
25
30
35
45
50
60
Qg, GATE CHARGE (nC)
FIGURE 20. TYPICAL MOSFET GATE CHARGE vs GATE VOLTAGE
Typical Applications
Vbatt
VBAT
VDen
VCen
Vbatt
VCC
HB
VDD
HIP2104
HI
uController
HO
DC
MOTOR
HS
50Vmax
E
P
A
D
LO
LI
VSS
FIGURE 21. HALF BRIDGE MOTOR DRIVE TOPOLOGY
FN8276 Rev 0.00
November 27, 2013
Page 14 of 21
HIP2103, HIP2104
Typical Applications
Vbatt
Vbatt
VBAT
VDen
VCen
VCC
HB
VDD
HB
VDD
VDD
VDD
HIP2104
HO
HO
HI
HS
LI
uController
DC
MOTOR
LO
VSS
HS
HIP2103
HI
LI
LO
VSS
EPAD
EPAD
FIGURE 22. FULL BRIDGE MOTOR DRIVER TOPOLOGY
FN8276 Rev 0.00
November 27, 2013
Page 15 of 21
HIP2103, HIP2104
Typical Applications
VBATT
VBATT
HB
VDD
VDD
VBAT
VDen
HO
VCen
HIP2103
HS
VCC
LI
HB
VDD
HIP2104
BLDC
Motor
HO
LO
VSS
HI
EPAD
HS
LI
µController
HI
LO
HB
VSS
VDD
HO
HIP2103
EPAD
HS
HI
LI
LO
VSS
EPAD
FIGURE 23. BLDC (3-PHASE) MOTOR DRIVE TOPOLOGY
Application Examples
Above are examples (Figures 21, 22, and 23) of how the HIP2103,
HIP2104 can be configured for various motor drive application
with the HIP2104 supplying the 12V bias for the other HIP2103s
and the VCC (3.3V) bias for the controller. VCen and VDen are used
to turn on and off the internal linear regulators of the HIP2104.
Because of entire switching of the bias supplies is implemented
with logic, a signal switch, instead of a power switch, can be used
to turn on and off the driver and controller. A switch debouncing
delay of 1ms is provided on VDen and VCen.
The external diode on VBATT is used to hold up the voltage on the
VBAT input in the presence of severe ripple as usually seen on
LI-ON batteries.
In the case of the HIP2104, when VDen is low, the driver sections
enters the Sleep Mode. When VCen is low, the bias to the
controller is removed resulting with the lowest possible idle
current in both the controller and the driver minimizing the drain
on the battery when the motor drive is off. Sleep mode can also
FN8276 Rev 0.00
November 27, 2013
be initiated on the HIP2104 by driving HI and LI high
simultaneously. In this case, the sleep mode current is
substantially higher (~250µA) because the VDD and VCC outputs
are still active.
In the case of the HIP2103, Sleep Mode in the driver is initiated
when HI and LI are both high simultaneously as previously
described. If VDD is provided by an accompanying HIP2104,
turning off the VDD output of the HIP2104 will also result with
virtually no sleep current in the HIP2103 because there is no
bias. For example, in the BLDC configuration, the sleep mode
current will be ~5µA (in the HIP2104) and no current in both of
the HIP2103s.
Transients on the HS node
An important operating condition that is frequently overlooked is
the transient on the HS pin that occurs when the bridge FETs turn
on or off. The Absolute Maximum negative transient (see page 5)
allowed on the HS pin is -10V without any time restrictions on the
duration of the transient. In most well designed PCBs, all that will
be required is that the transient be less negative than -10V.
Page 16 of 21
HIP2103, HIP2104
The negative transient on the HS pin is the result of the parasitic
inductance of the low-side drain-source conductor path on the
PCB. Even the parasitic inductance of the low-side FET body
contributes to this transient. When the high-side bridge FET turns
off (see Figure 24), as a consequence of the inductive
characteristics of a motor load, the current that was flowing in
the high-side FET (blue) must rapidly commutate through the low
side FET (red). The amplitude of the negative transient impressed
on the HS node is (L x di/dt) where L is the total parasitic
inductance of the low-side FET drain-source path and di/dt is the
rate at which the high-side FET is turned off. With the increasing
current levels of new generation motor drives, appropriately
clamping of this transient becomes more significant for the
proper operation of bridge drivers. Fortunately, the HIP2103,
HIP2104 can withstand greater amplitudes of negative
transients than what is available in many other bridge drivers.
The maximum negative voltage on the HS pin is rated for -10V
with no time during limit.
Another component of negative voltage is from the body diode of
the low side FET during the dead time. When current is flowing
from source to drain, the conduction voltage is approximately
1 to 1.5V negative impressed on the HS pin (possibly greater
during fault load conditions). Because the HIP2103, HIP2104 is
rated for -10V without any time constraints, this negative voltage
component is of no consequence.
HB
HO
Inductive
Load
CBOOT
HS
LO
1V
+
VSS
FIGURE 25. TWO CLAMPING DIODES TO SUPPRESS NEGATIVE
TRANSIENTS
An alternative to the two series connected diodes is one diode
and a resistor (Figure 26). In this case, it is necessary to limit the
current in the diode with a small value resistor, RHS, connected
between the phase node of the 1/2 bridge and the HS pin.
Observe that RHS is effectively in series with the HO output and
serves as a peak current limiting gate resistor on HO.
HB
HO
Inductive
Load
CBOOT
HB
RHS
HS
HO
+
Inductive
Load
CBOOT
LO
HS
+
LO
VSS
+
FIGURE 24. PARASITIC INDUCTANCE ON HS NODE
In the unlikely event that the negative transient exceeds -10V,
there are several ways of reducing the negative amplitude of this
transient if necessary. If the bridge FETs are turned off more
slowly to reduce di/dt, the amplitude will be reduced but at the
expense of more switching losses in the FETs. Careful PCB design
will also reduce the value of the parasitic inductance. However, in
extreme cases, these two solutions by themselves may not be
sufficient. Figure 25 illustrates a simple method for clamping the
negative transient. Two series connected, fast 1 amp PN junction
diodes are connected between HS and VSS as shown. It is
important that these diodes be placed as close as possible to the
HS and VSS pins to minimize the parasitic inductance of this
current path between the two pins. Two diodes in series are
required because they are in parallel with the body diode of the
low side FET. If only one diode is used for the clamp, it will
conduct some of the negative load current that is flowing in the
body diode of the low side FET.
FN8276 Rev 0.00
November 27, 2013
VSS
+
FIGURE 26. RESISTOR AND DIODE NEGATIVE TRANSIENT CLAMP
The value of RHS is determined by how much average current in
the clamping diode is acceptable. Current in the low side FET
flows through the body diode during the dead time resulting with
a negative voltage on HS that is typically about -1.5V. When the
low-side FET is turned on, the current through the body diode is
shunted away into the channel and the conduction voltage from
source to drain is typically much less than the conduction voltage
through the body diode. Consequently, significant current will
flow in the clamping diode only during the dead time. Because
the dead time is much less than the on time of the low side FET,
the resulting average current in the clamping diode is very low.
The value of RHS is then chosen to limit the peak current in the
clamping diode and usually just a few ohms is necessary.
The methods to clamp the negative transients with diodes can
still result with high frequency oscillations on the HS node
depending on the parasitics of the PCB design. An alternative to
the clamping diode in Figure 26 is a small value capacitor
instead of the diode. This capacitor and RHS is very effective for
minimizing the negative spike amplitude and oscillations.
Page 17 of 21
HIP2103, HIP2104
impedance, the boot capacitor can charge to a voltage greater
than VDD (for example VDD + 1.5V). It may be necessary to either
clamp the voltage as described in Figures 25 through 27 and/or
keep the dead time as short as possible.
HB
CBOOT
HO
Inductive
Load
HS
+
RHS _
IBAT, 0kHz
LO
Cfilter
VSS
FIGURE 27. RESISTOR AND CAPACITOR NEGATIVE TRANSIENT FILTER
But this solution also has its limitations. Depending on the value
of the filter capacitor and the PWM switching frequency, RHS
may dissipate significant power because the voltage on the
capacitor is switching between the bridge voltage and ground.
Usually, the power dissipated by RHS is small because the
switching frequency for most motor drives is <20kHz and the
value used for Cfilter is typically about 1000pF.
Another issue is that the charge on Cfilter will be partially
transferred to the gate of the high-side FET when the low-side FET
turns on. When the phase node goes low, a voltage is impressed
across RHS as shown in Figure 27. Because HO is low, the voltage
across RHS is also across the gate of the high side FET. If the filter
cap is very large, the voltage on the gate will approach the bridge
voltage turning on the high-side FET resulting with shoot-through.
Fortunately, the voltage across RHS is much less than the bridge
voltage for two reasons. First, the voltage across RHS is
determined by the turn-on time of the low side FET. As the
low-side FET is turning on, the charge on the filter cap is
depleting lessening the voltage across RHS. Also, because the
relatively large gate capacitance of the high-side FET is in parallel
with RHS, the voltage impressed on the gate is further reduced. In
a practical application using value of Cfilter = 4700pF and
RHS = 1Ω, the voltage impressed on the bridge FET is less
than 1V.
The emphasis of suppressing transients on the HS pin has been
with negative transients. Please note that a similar transients
with a positive polarity occurs when the low-side FET turns off.
This is usually not a problem unless the bridge voltage is close to
the maximum rated operating voltage of 50V. Note that the
maximum voltage ratings for the HS and HB nodes also must be
observed when the positive transient occurs.
The maximum rating for (VHB - VHS) must also not be
overlooked. When a negative transient, Vneg, is present on the
HS pin, the voltage differential across HB and HS will approach
VDD + Vneg. If the transient duration is short compared to the
charging time constant of the boot diode and boot capacitor, the
voltage across HB and HS is not significantly affected. However,
another source of negative voltage on the HS pin will more likely
increase the boot capacitor voltage. While current is flowing from
the source to drain of the low-side FET during the dead time, the
current flows through body diode of the FET. Depending on the
size of the FET and the amplitude of the reverse current, the
voltage across the diode can be as high as -1.5V and much
higher during a load fault. Because this negative voltage has little
FN8276 Rev 0.00
November 27, 2013
General PCB Layout Guidelines
The AC performance of the HIP2103, HIP2104 depends
significantly on the design of the PC board. The following layout
design guidelines are recommended to achieve optimum
performance:
• Place the driver as close as possible to the driven power FET.
• Understand where the switching power currents flow. The high
amplitude di/dt currents of the driven power FET will induce
significant voltage transients on the associated traces.
• Keep power loops as short as possible by paralleling the
source and return traces.
• Use planes where practical; they are usually more effective
than parallel traces.
• Avoid paralleling high amplitude di/dt traces with low level
signal lines. High di/dt will induce currents and consequently,
noise voltages in the low level signal lines.
• When practical, minimize impedances in low level signal
circuits. Noise, magnetically induced on a 10kΩ resistor, is 10x
larger than the noise on a 1kΩ resistor.
• Be aware of magnetic fields emanating from motors and
inductors. Gaps in the magnetic cores of these structures are
especially bad for emitting flux.
• If you must have traces close to magnetic devices, align the
traces so that they are parallel to the flux lines to minimize
coupling.
• The use of low inductance components such as chip resistors
and chip capacitors is highly recommended.
• Use decoupling capacitors to reduce the influence of parasitic
inductance in the VBAT, VDD and GND leads. To be effective,
these caps must also have the shortest possible conduction
paths. If vias are used, connect several paralleled vias to
reduce the inductance of the vias.
• It may be necessary to add resistance to dampen resonating
parasitic circuits especially on LO and LO. If an external gate
resistor is unacceptable, then the layout must be improved to
minimize lead inductance.
• Keep high dv/dt nodes away from low level circuits. Guard
banding can be used to shunt away dv/dt injected currents
from sensitive circuits.
• Avoid having a signal ground plane under a high amplitude
dv/dt circuit. The parasitic capacitance of a ground plane, Cp,
relative to the high amplitude dv/dt circuit will result in
injected (Cp x dv/dt) currents into the signal ground paths
where C is the parasitic capacitance of the ground plane.
• Do power dissipation and voltage drop calculations of the
power traces. Many PCB/CAD programs have built in tools for
calculation of trace resistance. The internet is also a good
source for resistance calculators for PCB trace resistance.
Page 18 of 21
HIP2103, HIP2104
• Large power components (Power FETs, Electrolytic caps, power
resistors, etc.) have internal parasitic inductance which cannot
be eliminated. This must be accounted for in the PCB layout
and circuit design.
vias and the size of the GND planes required for adequate
heatsinking is determined by the power dissipated by the
HIP2103, HIP2104, the air flow, and the maximum temperature
of the air around the IC.
• If you simulate your circuits, consider including parasitic
components especially parasitic inductance.
Note that a separate plane is added under the high side drive
circuits and is connected to HS. In a manner similar to the ground
plane, the HS plane provides the lowest possible parasitic
inductance for the HO/HS gate drive current loop.
General EPAD Heatsinking
Considerations
The EPAD of the HIP2103, HIP2104 is electrically connected to
VSS through the IC substrate. The epad has two main functions:
to provide a quiet signal ground and to provide heat sinking for
the IC. The EPAD must be connected to a ground plane and
switching currents from the driven FETs should not pass through
the ground plane under the IC.
Figure 28 is a PCB layout example of how to use vias to remove
heat from the IC through the EPAD.
For maximum heatsinking, it is recommended that a ground
plane, connected to the EPAD, be added to both sides of the PCB.
A via array, within the area of the EPAD, will conduct heat from
the EPAD to the GND plane on the bottom layer. The number of
See AN1899 “HIP2103, HIP2104 3-phase, Full, or Half Bridge
Motor Driver” for an example of PCB layout of a real application.
VDD
EPAD GND
PLANE
EPAD GND
PLANE
HB
VDD
HI
HO
HI
HO
LI
HS
LI
HS
LO
LS
LS
COMPONENT
LAYER
HB
This plane is
connected to
HS and is under
all high side
driver circuits
LO
BOTTOM
LAYER
FIGURE 28. TYPICAL PCB PATTERN FOR THERMAL VIAS
Revision History
The revision history provided is for informational purposes only and is believed to be accurate, but not warranted. Please go to the web to make sure that
you have the latest revision.
DATE
REVISION
November 27, 2013
FN8276.0
CHANGE
Initial Release
About Intersil
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For the most updated datasheet, application notes, related documentation and related parts, please see the respective product
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Intersil products are sold by description only. Intersil may modify the circuit design and/or specifications of products at any time without notice, provided that such
modification does not, in Intersil's sole judgment, affect the form, fit or function of the product. Accordingly, the reader is cautioned to verify that datasheets are
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For information regarding Intersil Corporation and its products, see www.intersil.com
FN8276 Rev 0.00
November 27, 2013
Page 19 of 21
HIP2103, HIP2104
Package Outline Drawing
L8.3x3A
8 LEAD THIN DUAL FLAT NO-LEAD PLASTIC PACKAGE
Rev 4, 2/10
( 2.30)
3.00
( 1.95)
A
B
3.00
( 8X 0.50)
6
PIN 1
INDEX AREA
(4X)
(1.50)
( 2.90 )
0.15
PIN 1
TOP VIEW
(6x 0.65)
( 8 X 0.30)
TYPICAL RECOMMENDED LAND PATTERN
SEE DETAIL "X"
2X 1.950
PIN #1
INDEX AREA
0.10 C
0.75 ±0.05
6X 0.65
C
0.08 C
1
SIDE VIEW
6
1.50 ±0.10
8
8X 0.30 ±0.05
8X 0.30 ± 0.10
2.30 ±0.10
C
4
0.10 M C A B
0 . 2 REF
5
0 . 02 NOM.
0 . 05 MAX.
DETAIL "X"
BOTTOM VIEW
NOTES:
1.
Dimensions are in millimeters.
Dimensions in ( ) for Reference Only.
2.
Dimensioning and tolerancing conform to ASME Y14.5m-1994.
3.
Unless otherwise specified, tolerance : Decimal ± 0.05
4.
Dimension applies to the metallized terminal and is measured
between 0.15mm and 0.20mm from the terminal tip.
5.
Tiebar shown (if present) is a non-functional feature.
6.
The configuration of the pin #1 identifier is optional, but must be
located within the zone indicated. The pin #1 identifier may be
either a mold or mark feature.
7.
FN8276 Rev 0.00
November 27, 2013
Compliant to JEDEC MO-229 WEEC-2 except for the foot length.
Page 20 of 21
HIP2103, HIP2104
Package Outline Drawing
L12.4x4A
12 LEAD DUAL FLAT NO-LEAD PLASTIC PACKAGE
Rev 2, 6/12
2.5 REF
4.00
A
PIN #1 INDEX AREA
10X 0.50 BSC
6
B
6
1
12X 0 . 45
6
PIN 1
INDEX AREA
4.00
1.58
0.15
(4X)
12
7
TOP VIEW
0.10 M C A B
0.05 M C
4 12 X 0.25
2.80
BOTTOM VIEW
( 2.80 )
SEE DETAIL "X"
1.00 MAX
( 12 X 0.65 )
0.10 C
BASE PLANE C
SEATING PLANE
0.08 C
SIDE VIEW
( 3.75)
( 1.58)
0 . 2 REF
C
( 10X 0 . 5 )
0 . 00 MIN.
0 . 05 MAX.
( 12X 0 . 25)
DETAIL "X"
TYPICAL RECOMMENDED LAND PATTERN
NOTES:
1.
Dimensions are in millimeters.
Dimensions in ( ) for Reference Only.
2.
Dimensioning and tolerancing conform to AMSE Y14.5m-1994.
3.
Unless otherwise specified, tolerance : Decimal ± 0.05
4.
Lead width applies to the metallized terminal and is measured
between 0.15mm and 0.30mm from the terminal tip.
5.
Tiebar shown (if present) is a non-functional feature.
6.
The configuration of the pin #1 identifier is optional, but must be
located within the zone indicated. The pin #1 identifier may be
either a mold or mark feature.
FN8276 Rev 0.00
November 27, 2013
Page 21 of 21