TI ADS1013 Ultra-small, low-power, 16-bit analog-to-digital converter with internal reference Datasheet

AD
S111
5
ADS
1115
ADS1113
ADS1114
ADS1115
www.ti.com ......................................................................................................................................................... SBAS444A – MAY 2009 – REVISED AUGUST 2009
Ultra-Small, Low-Power, 16-Bit
Analog-to-Digital Converter with Internal Reference
Check for Samples: ADS1113 ADS1114 ADS1115
FEATURES
DESCRIPTION
•
The ADS1113, ADS1114, and ADS1115 are
precision analog-to-digital converters (ADCs) with 16
bits of resolution offered in an ultra-small, leadless
QFN-10 package or an MSOP-10 package. The
ADS1113/4/5 are designed with precision, power, and
ease of implementation in mind. The ADS1113/4/5
feature an onboard reference and oscillator. Data are
transferred via an I2C-compatible serial interface; four
I2C slave addresses can be selected. The
ADS1113/4/5 operate from a single power supply
ranging from 2.0V to 5.5V.
1
23
•
•
•
•
•
•
•
•
•
•
ULTRA-SMALL QFN PACKAGE:
2mm × 1,5mm × 0,4mm
WIDE SUPPLY RANGE: 2.0V to 5.5V
LOW CURRENT CONSUMPTION:
Continuous Mode: Only 150μA
Single-Shot Mode: Auto Shut-Down
PROGRAMMABLE DATA RATE:
8SPS to 860SPS
INTERNAL LOW-DRIFT
VOLTAGE REFERENCE
INTERNAL OSCILLATOR
INTERNAL PGA
I2C ™ INTERFACE: Pin-Selectable Addresses
FOUR SINGLE-ENDED OR TWO
DIFFERENTIAL INPUTS (ADS1115)
PROGRAMMABLE COMPARATOR
(ADS1114 and ADS1115)
OPERATING TEMPERATURE: –40°C to +140°C
APPLICATIONS
•
•
•
•
•
PORTABLE INSTRUMENTATION
CONSUMER GOODS
BATTERY MONITORING
TEMPERATURE MEASUREMENT
FACTORY AUTOMATION AND PROCESS
CONTROLS
The ADS1113/4/5 can perform conversions at rates
up to 860 samples per second (SPS). An onboard
PGA is available on the ADS1114 and ADS1115 that
offers input ranges from the supply to as low as
±256mV, allowing both large and small signals to be
measured with high resolution. The ADS1115 also
features an input multiplexer (MUX) that provides two
differential or four single-ended inputs.
The ADS1113/4/5 operate either in continuous
conversion mode or a single-shot mode that
automatically powers down after a conversion and
greatly reduces current consumption during idle
periods. The ADS1113/4/5 are specified from –40°C
to +125°C.
VDD
VDD
Voltage
Reference
ADS1115
ADS1114
ADS1113
Comparator
Voltage
Reference
ALERT/RDY
AIN0
AIN0
AIN1
ADDR
16-Bit DS
ADC
2
IC
Interface
SCL
AIN1
AIN3
SDA
ADDR
AIN2
MUX
PGA
16-Bit DS
ADC
ADS1115
Only
2
IC
Interface
SCL
SDA
Oscillator
Oscillator
GND
GND
1
2
3
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
I2C is a trademark of NXP Semiconductors.
All other trademarks are the property of their respective owners.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2009, Texas Instruments Incorporated
ADS1113
ADS1114
ADS1115
SBAS444A – MAY 2009 – REVISED AUGUST 2009 ......................................................................................................................................................... www.ti.com
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with
appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more
susceptible to damage because very small parametric changes could cause the device not to meet its published specifications.
ORDERING INFORMATION
For the most current package and ordering information, see the Package Option Addendum at the end of this
document, or see the TI web site at www.ti.com.
ABSOLUTE MAXIMUM RATINGS
(1)
ADS1113, ADS1114, ADS1115
VDD to GND
Analog input current
Analog input current
Analog input voltage to GND
SDA, SCL, ADDR, ALERT/RDY voltage to GND
Maximum junction temperature
UNIT
–0.3 to +5.5
V
100, momentary
mA
10, continuous
mA
–0.3 to VDD + 0.3
V
–0.5 to +5.5
V
+150
°C
Operating temperature range
–40 to +140
°C
Storage temperature range
–60 to +150
°C
(1)
Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to absolute
maximum conditions for extended periods may affect device reliability.
PRODUCT FAMILY
2
DEVICE
PACKAGE
DESIGNATOR
MSOP/QFN
RESOLUTION
(Bits)
MAXIMUM SAMPLE
RATE (SPS)
COMPARATOR
PGA
INPUT CHANNELS
(Differential/
Single-Ended)
ADS1113
BROI/N6J
16
860
No
No
1/1
ADS1114
BRNI/N5J
16
860
Yes
Yes
1/1
ADS1115
BOGI/N4J
16
860
Yes
Yes
2/4
ADS1013
BRMI/N9J
12
3300
No
No
1/1
ADS1014
BRQI/N8J
12
3300
Yes
Yes
1/1
ADS1015
BRPI/N7J
12
3300
Yes
Yes
2/4
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Copyright © 2009, Texas Instruments Incorporated
Product Folder Link(s): ADS1113 ADS1114 ADS1115
ADS1113
ADS1114
ADS1115
www.ti.com ......................................................................................................................................................... SBAS444A – MAY 2009 – REVISED AUGUST 2009
ELECTRICAL CHARACTERISTICS
All specifications at –40°C to +125°C, VDD = 3.3V, and Full-Scale (FS) = ±2.048V, unless otherwise noted.
Typical values are at +25°C.
ADS1113, ADS1114, ADS1115
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
ANALOG INPUT
Full-scale input voltage
(1)
VIN = (AINP) – (AINN)
Analog input voltage
±4.096/PGA
AINP or AINN to GND
GND
Differential input impedance
V
VDD
V
See Table 2
FS = ±6.144V
FS = ±4.096V
Common-mode input impedance
(1)
(1)
, ±2.048V
10
MΩ
6
MΩ
FS = ±1.024V
3
MΩ
FS = ±0.512V, ±0.256V
100
MΩ
SYSTEM PERFORMANCE
Resolution
No missing codes
16
Data rate (DR)
Data rate variation
All data rates
–10
Output noise
DR = 8SPS, FS = ±2.048V, best fit
Offset drift
Offset power-supply rejection
(3)
(3)
%
±1
1
LSB
±3
LSB
FS = ±2.048V, single-ended inputs
±3
LSB
FS = ±2.048V
0.005
LSB/°C
FS = ±2.048V
1
FS = ±2.048V at 25°C
0.01
FS = ±0.256V
7
FS = ±2.048V
5
FS = ±6.144V
(1)
LSB/V
0.15
ppm/°C
ppm/°C
80
(3)
%
ppm/°C
40
5
Gain power-supply rejection
PGA gain match
10
(2)
FS = ±2.048V, differential inputs
Offset error
Gain drift
SPS
See Typical Characteristics
Integral nonlinearity
Gain error
Bits
8, 16, 32,
64, 128,
250, 475,
860
ppm/V
Match between any two PGA gains
0.02
0.1
%
Gain match
Match between any two inputs
0.05
0.1
%
Offset match
Match between any two inputs
3
LSB
At dc and FS = ±0.256V
105
dB
At dc and FS = ±2.048V
100
dB
90
dB
fCM = 60Hz, DR = 8SPS
105
dB
fCM = 50Hz, DR = 8SPS
105
dB
Common-mode rejection
At dc and FS = ±6.144V
(1)
DIGITAL INPUT/OUTPUT
Logic level
VIH
0.7VDD
5.5
V
VIL
GND – 0.5
0.3VDD
V
0.4
V
10
μA
VOL
IOL = 3mA
GND
0.15
Input leakage
(1)
(2)
(3)
IH
VIH = 5.5V
IL
VIL = GND
10
μA
This parameter expresses the full-scale range of the ADC scaling. In no event should more than VDD + 0.3V be applied to this device.
99% of full-scale.
Includes all errors from onboard PGA and reference.
Copyright © 2009, Texas Instruments Incorporated
Product Folder Link(s): ADS1113 ADS1114 ADS1115
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3
ADS1113
ADS1114
ADS1115
SBAS444A – MAY 2009 – REVISED AUGUST 2009 ......................................................................................................................................................... www.ti.com
ELECTRICAL CHARACTERISTICS (continued)
All specifications at –40°C to +125°C, VDD = 3.3V, and Full-Scale (FS) = ±2.048V, unless otherwise noted.
Typical values are at +25°C.
ADS1113, ADS1114, ADS1115
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
5.5
V
2
μA
5
μA
200
μA
POWER-SUPPLY REQUIREMENTS
Power-supply voltage
2
Power-down current at 25°C
0.5
Power-down current up to 125°C
Supply current
Operating current at 25°C
150
Operating current up to 125°C
Power dissipation
μA
300
VDD = 5.0V
0.9
mW
VDD = 3.3V
0.5
mW
VDD = 2.0V
0.3
mW
TEMPERATURE
Storage temperature
–60
+150
°C
Operating temperature
–40
+140
°C
Specified temperature
–40
+125
°C
PIN CONFIGURATIONS
RUG PACKAGE
QFN-10
(TOP VIEW)
DGS PACKAGE
MSOP-10
(TOP VIEW)
SCL
10
ADDR
1
ALERT/RDY (ADS1114/5 Only)
2
GND
3
AIN0
9
ADS1113
ADS1114
ADS1115
4
8
VDD
7
AIN3 (ADS1115 Only)
6
ADDR
1
ALERT/RDY (ADS1114/5 Only)
2
10 SCL
SDA
ADS1113
ADS1114
ADS1115
9
SDA
GND
3
8
VDD
AIN0
4
7
AIN3 (ADS1115 Only)
AIN1
5
6
AIN2 (ADS1115 Only)
AIN2 (ADS1115 Only)
5
AIN1
PIN DESCRIPTIONS
DEVICE
PIN #
ADS1113
ADS1114
ADS1115
ANALOG/
DIGITAL
INPUT/
OUTPUT
1
ADDR
ADDR
ADDR
Digital Input
2
NC
3
GND
GND
GND
Analog
4
AIN0
AIN0
AIN0
Analog Input
Differential channel 1: Positive input or single-ended channel 1 input
5
AIN1
AIN1
AIN1
Analog Input
Differential channel 1: Negative input or single-ended channel 2 input
6
NC
NC
AIN2
Analog Input
Differential channel 2: Positive input or single-ended channel 3 input (NC for ADS1113/4)
7
NC
NC
AIN3
Analog Input
Differential channel 2: Negative input or single-ended channel 4 input
(NC for ADS1113/4)
8
VDD
VDD
VDD
Analog
9
SDA
SDA
SDA
Digital I/O
10
SCL
SCL
SCL
Digital Input
(1)
4
(1)
ALERT/RDY ALERT/RDY
Digital Output
DESCRIPTION
I2C slave address select
Digital comparator output or conversion ready (NC for ADS1113)
Ground
Power supply: 2.0V to 5.5V
Serial data: Transmits and receives data
Serial clock input: Clocks data on SDA
NC pins may be left floating or tied to ground.
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Copyright © 2009, Texas Instruments Incorporated
Product Folder Link(s): ADS1113 ADS1114 ADS1115
ADS1113
ADS1114
ADS1115
www.ti.com ......................................................................................................................................................... SBAS444A – MAY 2009 – REVISED AUGUST 2009
TIMING REQUIREMENTS
tLOW
tF
tR
tHDSTA
SCL
tHDSTA
tHIGH
tHDDAT
tSUSTO
tSUSTA
tSUDAT
SDA
tBUF
P
S
S
P
Figure 1. I2C Timing Diagram
Table 1. I2C Timing Definitions
FAST MODE
PARAMETER
HIGH-SPEED MODE
MIN
MAX
MIN
MAX
UNIT
0.4
0.01
3.4
MHz
SCL operating frequency
fSCL
0.01
Bus free time between START and STOP
condition
tBUF
600
160
ns
tHDSTA
600
160
ns
Repeated START condition setup time
tSUSTA
600
160
ns
Stop condition setup time
tSUSTO
600
160
ns
Data hold time
tHDDAT
0
0
ns
Data setup time
tSUDAT
100
10
ns
SCL clock low period
tLOW
1300
160
ns
SCL clock high period
tHIGH
600
Hold time after repeated START condition.
After this period, the first clock is generated.
60
ns
Clock/data fall time
tF
300
160
ns
Clock/data rise time
tR
300
160
ns
Copyright © 2009, Texas Instruments Incorporated
Product Folder Link(s): ADS1113 ADS1114 ADS1115
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5
ADS1113
ADS1114
ADS1115
SBAS444A – MAY 2009 – REVISED AUGUST 2009 ......................................................................................................................................................... www.ti.com
TYPICAL CHARACTERISTICS
At TA = +25°C and VDD = 3.3V, unless otherwise noted.
OPERATING CURRENT vs TEMPERATURE
SHUTDOWN CURRENT vs TEMPERATURE
300
5.0
4.5
Shutdown Current (mA)
Operating Current (mA)
250
VDD = 5V
200
150
VDD = 3.3V
VDD = 2V
100
50
4.0
3.5
3.0
2.5
2.0
VDD = 5V
1.5
VDD = 3.3V
1.0
0.5
0
VDD = 2V
0
-40
-20
0
20
40
60
80
100
120
140
-40
0
-20
20
Temperature (°C)
Figure 2.
60
80
100
120
140
Figure 3.
SINGLE-ENDED OFFSET ERROR vs TEMPERATURE (1)
DIFFERENTIAL OFFSET vs TEMPERATURE
150
60
FS = ±4.096V
FS = ±2.048V
100
(1)
FS = ±1.024V
FS = ±0.512V
50
VDD = 2V
40
VDD = 5V
Offset Voltage (mV)
50
Offset Error (mV)
40
Temperature (°C)
0
-50
-100
-150
-200
VDD = 5V
30
VDD = 4V
20
VDD = 3V
10
0
VDD = 2V
-10
-250
-20
-300
-40
-20
0
20
40
60
80
100
120
140
-40
0
-20
20
40
60
80
100
120
140
Temperature (°C)
Temperature (°C)
Figure 4.
Figure 5.
GAIN ERROR vs TEMPERATURE
GAIN ERROR vs SUPPLY
0.15
0.05
FS = ±0.256V
0.04
0.10
FS = ±0.512V
0.02
Gain Error (%)
Gain Error (%)
0.03
0.01
FS = ±1.024V, ±2.048V,
(1)
(1)
±4.096V , and ±6.144V
0
-0.01
-0.02
0.05
FS = ±256mV
0
FS = ±2.048V
-0.05
-0.10
-0.03
-0.15
-0.04
-40
-20
0
20
40
60
80
100
120
140
2.0
2.5
3.0
Figure 6.
(1)
6
3.5
4.0
4.5
5.0
5.5
Supply Voltage (V)
Temperature (°C)
Figure 7.
This parameter expresses the full-scale range of the ADC scaling. In no event should more than VDD + 0.3V be applied to this device.
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Copyright © 2009, Texas Instruments Incorporated
Product Folder Link(s): ADS1113 ADS1114 ADS1115
ADS1113
ADS1114
ADS1115
www.ti.com ......................................................................................................................................................... SBAS444A – MAY 2009 – REVISED AUGUST 2009
TYPICAL CHARACTERISTICS (continued)
At TA = +25°C and VDD = 3.3V, unless otherwise noted.
INL vs SUPPLY VOLTAGE (2)
INL vs INPUT SIGNAL
60
50
40
FS = ±6.144V
(1)
30
FS = ±0.512, ±0.256V
FS = ±2.048V
20
Integral Nonlinearity (mV)
Integral Nonlinearity (mV)
60
10
40
FS = ±2.048V
VDD = 3.3V
DR = 8SPS
Best Fit
+140°C
20
-40°C
0
-20
+25°C
-40
0
2.0
2.5
3.0
3.5
4.0
4.5
5.0
-60
-2.0
5.5
-1.5
-1.0
Supply Voltage (V)
Integral Nonlinearity (mV)
Integral Nonlinearity (mV)
FS = ±0.512V
VDD = 3.3V
DR = 8SPS
Best Fit
+140°C
0
+25°C
-20
-40
40
20
2.0
TA = -40°C
0
-20
TA = +140°C
TA = +25°C
0
0.125 0.250 0.375
-60
-2.0
0.5
-1.5
-1.0
-0.5
0
0.5
1.0
Input Voltage (V)
Figure 10.
Figure 11.
INL vs INPUT SIGNAL
INL vs TEMPERATURE
140
FS = ±0.512V
VDD = 5V
DR = 8SPS
Best Fit
DR = 8SPS
120
Integral Nonlinearity (mV)
Integral Nonlinearity (mV)
1.5
FS = ±2.048V
VDD = 5V
DR = 8SPS
Best Fit
Input Signal (V)
TA = +25°C
TA = -40°C
0
-20
2.0
-40
-60
-0.5 -0.375 -0.250 -0.125
20
1.5
INL vs INPUT SIGNAL
-40°C
40
1.0
60
20
60
0.5
Figure 9.
INL vs INPUT SIGNAL
40
0
Input Signal (V)
Figure 8.
60
-0.5
TA = +140°C
-40
100
80
VDD = 2V
60
VDD = 5V
40
20
VDD = 3.3V
-60
-0.5 -0.4 -0.3 -0.2 -0.1
0
0
0.1
0.2
0.3
0.4
0.5
-60
-40
-20
Input Voltage (V)
Figure 12.
(2)
0
20
40
60
80
100 120
140
Temperature (°C)
Figure 13.
This parameter expresses the full-scale range of the ADC scaling. In no event should more than VDD + 0.3V be applied to this device.
Copyright © 2009, Texas Instruments Incorporated
Product Folder Link(s): ADS1113 ADS1114 ADS1115
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ADS1113
ADS1114
ADS1115
SBAS444A – MAY 2009 – REVISED AUGUST 2009 ......................................................................................................................................................... www.ti.com
TYPICAL CHARACTERISTICS (continued)
At TA = +25°C and VDD = 3.3V, unless otherwise noted.
NOISE vs INPUT SIGNAL
12
NOISE vs SUPPLY VOLTAGE
35
FS = ±0.512V
FS = ±2.048V
30
8
RMS Noise (mV)
RMS Noise (mV)
10
DR = 860SPS
6
DR = 128SPS
4
DR = 8SPS
20
15
128SPS
10
2
5
0
-0.5 -0.4 -0.3 -0.2 -0.1
0
0
0.1
0.2
0.3
0.4
860SPS
25
0.5
8SPS
2.0
2.5
3.0
Input Voltage (V)
Figure 14.
9
5.0
5.5
185 Units From a Production Lot
FS = ±2.048V
Number of Occurrences
25
8
RMS Noise (mV)
4.5
GAIN ERROR HISTOGRAM
30
10
7
6
5
4
3
20
15
10
5
2
FS = ±2.048V
Data Rate = 8SPS
1
0
-40
-20
0
20
40
60
80
100
120
-0.010
-0.005
0
0.005
0.010
0.015
0.020
0.025
0.030
0.035
0.040
0.045
0.050
0.055
0.060
0.065
0.070
0.075
0.080
0.085
0.090
0
140
Temperature (°C)
Gain Error (%)
Figure 16.
Figure 17.
OFFSET HISTOGRAM
160
140
TOTAL ERROR vs INPUT SIGNAL
4
185 Units From a
Production Lot
FS = ±2.048V
Includes noise, offset, and gain error.
3
2
120
Total Error (mV)
Number of Occurrences
4.0
Figure 15.
NOISE vs TEMPERATURE
100
80
60
1
0
-1
40
-2
20
-3
0
-3
-2
-1
0
1
2
3
-4
-2.048
FS = ±2.048V
Data Rate = 860SPS
Differential Inputs
-1.024
Offset (LSBs)
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0
1.024
2.048
Input Signal (V)
Figure 18.
8
3.5
Supply Voltage (V)
Figure 19.
Copyright © 2009, Texas Instruments Incorporated
Product Folder Link(s): ADS1113 ADS1114 ADS1115
ADS1113
ADS1114
ADS1115
www.ti.com ......................................................................................................................................................... SBAS444A – MAY 2009 – REVISED AUGUST 2009
TYPICAL CHARACTERISTICS (continued)
At TA = +25°C and VDD = 3.3V, unless otherwise noted.
FREQUENCY RESPONSE
0
3
-10
Data Rate = 8SPS
VDD = 5V
2
-20
1
Gain (dB)
Data Rate Error (%)
DATA RATE vs TEMPERATURE
4
VDD = 3.3V
0
-1
-2
-40
-50
-60
VDD = 2V
-3
-4
-40
-30
-70
-80
-20
0
20
40
60
80
100
120
140
1
10
Temperature (°C)
Figure 20.
100
1k
10k
Input Frequency (Hz)
Figure 21.
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ADS1114
ADS1115
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OVERVIEW
The ADS1113/4/5 are very small, low-power, 16-bit,
delta-sigma (ΔΣ) analog-to-digital converters (ADCs).
The ADS1113/4/5 are extremely easy to configure
and design into a wide variety of applications, and
allow precise measurements to be obtained with very
little effort. Both experienced and novice users of
data converters find designing with the ADS1113/4/5
family to be intuitive and problem-free.
The ADS1113/4/5 consist of a ΔΣ analog-to-digital
(A/D) core with adjustable gain (excludes the
ADS1113), an internal voltage reference, a clock
oscillator, and an I2C interface. An additional feature
available on the ADS1114/5 is a programmable digital
comparator that provides an alert on a dedicated pin.
All of these features are intended to reduce required
external circuitry and improve performance. Figure 22
shows the ADS1115 functional block diagram.
The ADS1113/4/5 A/D core measures a differential
signal, VIN, that is the difference of AINP and AINN. A
MUX is available on the ADS1115. This architecture
results in a very strong attenuation in any
common-mode signals. The converter core consists
of a differential, switched-capacitor ΔΣ modulator
followed by a digital filter. Input signals are compared
to the internal voltage reference. The digital filter
receives a high-speed bitstream from the modulator
and outputs a code proportional to the input voltage.
The ADS1113/4/5 have two available conversion
modes: single-shot mode and continuous conversion
mode. In single-shot mode, the ADC performs one
conversion of the input signal upon request and
stores the value to an internal result register. The
device then enters a low-power shutdown mode. This
mode is intended to provide significant power savings
in systems that only require periodic conversions or
when there are long idle periods between
conversions. In continuous conversion mode, the
ADC automatically begins a conversion of the input
signal as soon as the previous conversion is
completed. The rate of continuous conversion is
equal to the programmed data rate. Data can be read
at any time and always reflect the most recent
completed conversion.
VDD
ADS1115
Comparator
Voltage
Reference
MUX
ALERT/RDY
Gain = 2/3, 1,
2, 4, 8, or 16
AIN0
ADDR
PGA
AIN1
16-Bit DS
ADC
2
IC
Interface
SCL
SDA
AIN2
Oscillator
AIN3
GND
Figure 22. ADS1115 Functional Block Diagram
10
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QUICKSTART GUIDE
For example, to write to the configuration register to
set the ADS1113/4/5 to continuous conversion mode
and then read the conversion result, send the
following bytes in this order:
This section provides a brief example of ADS1113/4/5
communications. Refer to subsequent sections of this
data sheet for more detailed explanations. Hardware
for this design includes: one ADS1113/4/5 configured
with an I2C address of 1001000; a microcontroller
with an I2C interface (TI recommends the
MSP430F2002); discrete components such as
resistors, capacitors, and serial connectors; and a 2V
to 5V power supply. Figure 23 shows the basic
hardware configuration.
Write to Config register:
First byte: 0b10010000 (first 7-bit I2C address
followed by a low read/write bit)
Second byte: 0b00000001 (points to Config register)
Third byte: 0b10000100 (MSB of the Config register
to be written)
The ADS1113/4/5 communicate with the master
(microcontroller) through an I2C interface. The master
provides a clock signal on the SCL pin and data are
transferred via the SDA pin. The ADS1113/4/5 never
drive the SCL pin. For information on programming
and debugging the microcontroller being used, refer
to the device-specific product data sheet.
Fourth byte: 0b10000011 (LSB of the Config register
to be written)
Write to Pointer register:
First byte: 0b10010000 (first 7-bit I2C address
followed by a low read/write bit)
Second byte: 0b00000000 (points to Conversion
register)
The first byte sent by the master should be the
ADS1113/4/5 address followed by a bit that instructs
the ADS1113/4/5 to listen for a subsequent byte. The
second byte is the register pointer. Refer to Table 9
for a register map. The third and fourth bytes sent
from the master are written to the register indicated in
the second byte. Refer to Figure 30 and Figure 31 for
read and write operation timing diagrams,
respectively. All read and write transactions with the
ADS1113/4/5 must be preceded by a start condition
and followed by a stop condition.
Read Conversion register:
First byte: 0b10010001 (first 7-bit I2C address
followed by a high read/write bit)
Second byte: the ADS1113/4/5 response with the
MSB of the Conversion register
Third byte: the ADS1113/4/5 response with the LSB
of the Conversion register
+3.3V
VDD
GND
100nF +3.3V
2
I C-Capable Master
(MSP430F2002)
AIN0
AIN1
ADDR
AIN2 (ADS1115 Only)
10kW
+3.3V
10kW
SCL (P1.6)
SDA (P1.7)
SCL
SDA
ALERT
(ADS1114/5 Only)
AIN3 (ADS1115 Only)
ADS1113/4/5
JTAG
VDD
100nF
GND
Serial/UART
Figure 23. Basic Hardware Configuration
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MULTIPLEXER
The ADS1115 contains an input multiplexer, as
shown in Figure 24 . Either four single-ended or two
differential signals can be measured. Additionally,
AIN0 and AIN1 may be measured differentially to
AIN3. The multiplexer is configured by three bits in
the Config register. When single-ended signals are
measured, the negative input of the ADC is internally
connected to GND by a switch within the multiplexer.
VDD
ADS1115
AIN0
VDD
GND
AINP
VDD
AINN
AIN1
GND
AIN2
VDD
GND
AIN3
GND
GND
Figure 24. ADS1115 MUX
The ADS1113 and ADS1114 do not have a
multiplexer. Either one differential or one
single-ended signal may be measured with these
devices. For single-ended measurements, connect
the AIN1 pin to GND. Note that in subsequent
sections of this data sheet, AINP refers to AIN0 and
AINN refers to AIN1 for the ADS1113 and ADS1114.
When measuring single-ended inputs it is important to
note that the negative range of the output codes are
not used. These codes are for measuring negative
differential signals such as (AINP – AINN) < 0. ESD
diodes to VDD and GND protect the inputs on all
three devices (ADS1113, ADS1114, and ADS1115).
To prevent the ESD diodes from turning on, the
absolute voltage on any input must stay within the
following range:
If it is possible that the voltages on the input pins may
violate these conditions, external Schottky clamp
diodes and/or series resistors may be required to limit
the input current to safe values (see the Absolute
Maximum Ratings table).
Also, overdriving one unused input on the ADS1115
may affect conversions taking place on other input
pins. If overdrive on unused inputs is possible, again
it is recommended to clamp the signal with external
Schottky diodes.
ANALOG INPUTS
The ADS1113/4/5 use a switched-capacitor input
stage where capacitors are continuously charged and
then discharged to measure the voltage between
AINP and AINN. The capacitors used are small, and to
external circuitry the average loading appears
resistive. This structure is shown in Figure 26 . The
resistance is set by the capacitor values and the rate
at which they are switched. Figure 25 shows the
on/off setting of the switches illustrated in Figure 26 .
During the sampling phase, S1 switches are closed.
This event charges CA1 to AINP, CA2 to AINN, and CB
to (AINP – AINN). During the discharge phase, S1 is
first opened and then S2 is closed. Both CA1 and CA2
then discharge to approximately 0.7V and CB
discharges to 0V. This charging draws a very small
transient current from the source driving the
ADS1113/4/5 analog inputs. The average value of
this current can be used to calculate the effective
impedance (Reff) where Reff = VIN/IAVERAGE.
tSAMPLE
ON
S1
OFF
ON
S2
OFF
Figure 25. S1 and S2 Switch Timing for Figure 26
GND – 0.3V < AINx < VDD + 0.3V
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0.7V
CA1
AINP
S1
ZCM
S2
0.7V
Equivalent
Circuit
AINP
CB
S1
ZDIFF
S2
AINN
AINN
0.7V
CA2
ZCM
fCLK = 250kHz
0.7V
Figure 26. Simplified Analog Input Circuit
The common-mode input impedance is measured by
applying a common-mode signal to shorted AINP and
AINN inputs and measuring the average current
consumed by each pin. The common-mode input
impedance changes depending on the PGA gain
setting, but is approximately 6MΩ for the default PGA
gain setting. In Figure 26 , the common-mode input
impedance is ZCM.
The typical value of the input impedance cannot be
neglected. Unless the input source has a low
impedance, the ADS1113/4/5 input impedance may
affect the measurement accuracy. For sources with
high output impedance, buffering may be necessary.
Active buffers introduce noise, and also introduce
offset and gain errors. All of these factors should be
considered in high-accuracy applications.
The differential input impedance is measured by
applying a differential signal to AINP and AINN inputs
where one input is held at 0.7V. The current that
flows through the pin connected to 0.7V is the
differential current and scales with the PGA gain
setting. In Figure 26
, the differential input
impedance is ZDIFF. Table 2 describes the typical
differential input impedance.
Because the clock oscillator frequency drifts slightly
with temperature, the input impedances also drift. For
many applications, this input impedance drift can be
ignored, and the values given in Table 2 for typical
input impedance are valid.
Table 2. Differential Input Impedance
FS (V)
(1)
±6.144V
DIFFERENTIAL INPUT IMPEDANCE
22MΩ
±4.096V(1)
15MΩ
±2.048V
4.9MΩ
±1.024V
2.4MΩ
±0.512V
710kΩ
±0.256V
710kΩ
1. This parameter expresses the full-scale range of
the ADC scaling. In no event should more than
VDD + 0.3V be applied to this device.
FULL-SCALE INPUT
A programmable gain amplifier (PGA) is implemented
before the ΔΣ core of the ADS1114/5. The PGA can
be set to gains of 2/3, 1, 2, 4, 8, and 16. Table 3
shows the corresponding full-scale (FS) ranges. The
PGA is configured by three bits in the Config register.
The ADS1113 has a fixed full-scale input range of
±2.048V. The PGA = 2/3 setting allows input
measurement to extend up to the supply voltage
when VDD is larger than 4V. Note though that in this
case (as well as for PGA = 1 and VDD < 4V), it is not
possible to reach a full-scale output code on the
ADC. Analog input voltages may never exceed the
analog input voltage limits given in the Electrical
Characteristics table.
Table 3. PGA Gain Full-Scale Range
PGA SETTING
FS (V)
2/3
±6.144V(1)
1
±4.096V(1)
2
±2.048V
4
±1.024V
8
±0.512V
16
±0.256V
1. This parameter expresses the full-scale range of
the ADC scaling. In no event should more than
VDD + 0.3V be applied to this device.
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DATA FORMAT
The ADS1113/4/5 provide 16 bits of data in binary
twos complement format. The positive full-scale input
produces an output code of 7FFFh and the negative
full-scale input produces an output code of 8000h.
The output clips at these codes for signals that
exceed full-scale. Table 4 summarizes the ideal
output codes for different input signals. Figure 27
shows code transitions versus input voltage.
Table 4. Input Signal versus Ideal Output Code
INPUT SIGNAL, VIN
(AINP – AINN)
IDEAL OUTPUT CODE(1)
≥ FS (215 – 1)/215
7FFFh
+FS/215
0001h
0
0
15
–FS/2
FFFFh
≤ –FS
8000h
1. Excludes the effects of noise, INL, offset, and
gain errors.
0x7FFF
OPERATING MODES
The ADS1113/4/5 operate in one of two modes:
continuous conversion or single-shot. In continuous
conversion mode, the ADS1113/4/5 continuously
perform conversions. Once a conversion has been
completed, the ADS1113/4/5 place the result in the
Conversion register and immediately begins another
conversion. In single-shot mode, the ADS1113/4/5
wait until the OS bit is set high. Once asserted, the bit
is set to '0', indicating that a conversion is currently in
progress. Once conversion data are ready, the OS bit
reasserts and the device powers down. Writing a '1'
to the OS bit during a conversion has no effect.
¼
When the ADS1113/4/5 powers up, a reset is
performed. As part of the reset process, the
ADS1113/4/5 set all of the bits in the Config register
to the respective default settings.
0x0001
0x0000
0xFFFF
¼
Output Code
When designing an input filter circuit, be sure to take
into account the interaction between the filter network
and the input impedance of the ADS1113/4/5.
RESET AND POWER-UP
0x7FFE
The ADS1113/4/5 respond to the I2C general call
reset command. When the ADS1113/4/5 receive a
general call reset, an internal reset is performed as if
the device had been powered on.
0x8001
0x8000
¼
-FS
2
15
-FS
2
0
¼
FS
DUTY CYCLING FOR LOW POWER
Input Voltage (AINP - AINN)
-1
15
2
15
FS
2
-1
15
Figure 27. ADS1113/4/5 Code Transition Diagram
ALIASING
As with any data converter, if the input signal
contains frequencies greater than half the data rate,
aliasing occurs. To prevent aliasing, the input signal
must be bandlimited. Some signals are inherently
bandlimited. For example, the output of a
thermocouple, which has a limited rate of change.
Nevertheless, they can contain noise and interference
components. These components can fold back into
the sampling band in the same way as with any other
signal.
14
The ADS1113/4/5 digital filter provides some
attenuation of high-frequency noise, but the digital
Sinc filter frequency response cannot completely
replace an anti-aliasing filter. For a few applications,
some external filtering may be needed; in such
instances, a simple RC filter is adequate.
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For many applications, the improved performance at
low data rates may not be required. For these
applications, the ADS1113/4/5 support duty cycling
that can yield significant power savings by
periodically requesting high data rate readings at an
effectively lower data rate. For example, an
ADS1113/4/5 in power-down mode with a data rate
set to 860SPS could be operated by a microcontroller
that instructs a single-shot conversion every 125ms
(8SPS). Because a conversion at 860SPS only
requires about 1.2ms, the ADS1113/4/5 enter
power-down mode for the remaining 123.8ms. In this
configuration, the ADS1113/4/5 consume about
1/100th the power of the ADS1113/4/5 operated in
continuous conversion mode. The rate of duty cycling
is completely arbitrary and is defined by the master
controller. The ADS1113/4/5 offer lower data rates
that do not implement duty cycling and offer improved
noise performance if it is needed.
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COMPARATOR (ADS1114/15 ONLY)
The ADS1114/5 are each equipped with a
customizable comparator that can issue an alert on
the ALERT/RDY pin. This feature can significantly
reduce external circuitry for many applications. The
comparator can be implemented as either a
traditional comparator or a window comparator via the
COMP_MODE bit in the Config register. When
implemented as a traditional comparator, the
ALERT/RDY pin asserts (active low by default) when
conversion data exceed the limit set in the high
threshold register. The comparator then deasserts
when the input signal falls below the low threshold
register value. In window comparator mode, the
ALERT/RDY pin asserts if conversion data exceed
the high threshold register or fall below the low
threshold register.
In either window or traditional comparator mode, the
comparator can be configured to latch once asserted
by the COMP_LAT bit in the Config register. This
setting causes the assertion to remain even if the
input signal is not beyond the bounds of the threshold
registers. This latched assertion can be cleared by
issuing an SMBus alert response or by reading the
Conversion register. The COMP_POL bit in the
Config register configures the ALERT/RDY pin as
active high or active low. Operational diagrams for
the comparator modes are shown in Figure 28 and
Figure 29 .
The comparator can be configured to activate the
ALERT/RDY pin after a set number of successive
readings exceed the threshold. The comparator can
be configured to wait for one, two, or four readings
beyond the threshold before activating the
ALERT/RDY pin by changing the COMP_QUE bits in
the Config register. The COMP_QUE bits can also
disable the comparator function.
TH_H
Input Signal
TH_L
Time
Successful
SMBus Alert
Response
Latching
Comparator
Output
Time
Non-Latching
Comparator
Output
Time
Figure 28. Alert Pin Timing Diagram When
Configured as a Traditional Comparator
TH_H
Input Signal
TH_L
Time
CONVERSION READY PIN (ADS1114/5 ONLY)
The ALERT/RDY pin can also be configured as a
conversion ready pin. This mode of operation can be
realized if the MSB of the high threshold register is
set to '1' and the MSB of the low threshold register is
set to '0'. The COMP_POL bit continues to function
and the COMP_QUE bits can disable the pin;
however, the COMP_MODE and COMP_LAT bits no
longer control any function. When configured as a
conversion ready pin, ALERT/RDY continues to
require a pull-up resistor. When in continuous
conversion mode, the ADS1113/4/5 provide a brief
(~8µs) pulse on the ALERT/RDY pin at the end of
each conversion. When in single-shot shutdown
mode, the ALERT/RDY pin asserts low at the end of
a conversion if the COMP_POL bit is set to '0'.
Latching
Comparator
Output
Successful
SMBus Alert
Response
Successful
SMBus Alert
Response
Time
Non-Latching
Comparator
Output
Time
Figure 29. Alert Pin Timing Diagram When
Configured as a Window Comparator
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SMBus ALERT RESPONSE
When configured in latching mode (COMP_LAT = '1'
in the Config register), the ALERT/RDY pin can be
implemented with an SMBus alert. The pin asserts if
the comparator detects a conversion that exceeds an
upper or lower threshold. This interrupt is latched and
can be cleared only by reading conversion data, or by
issuing a successful SMBus alert response and
reading the asserting device I2C address. If
conversion data exceed the upper or lower thresholds
after being cleared, the pin reasserts. This assertion
does not affect conversions that are already in
progress. The ALERT/RDY pin, as with the SDA pin,
is an open-drain pin. This architecture allows several
devices to share the same interface bus. When
disabled, the pin holds a high state so that it does not
interfere with other devices on the same bus line.
When the master senses that the ALERT/RDY pin
has latched, it issues an SMBus alert command
(00011001) to the I2C bus. Any ADS1114/5 data
converters on the I2C bus with the ALERT/RDY pins
asserted respond to the command with the slave
address. In the event that two or more ADS1114/5
data converters present on the bus assert the latched
ALERT/RDY pin, arbitration during the address
response portion of the SMBus alert decides which
device clears its assertion. The device with the lowest
I2C address always wins arbitration. If a device loses
arbitration, it does not clear the comparator output pin
assertion. The master then repeats the SMBus alert
response until all devices have had the respective
assertions cleared. In window comparator mode, the
SMBus alert status bit indicates a '1' if signals exceed
the high threshold and a '0' if signals exceed the low
threshold.
I2C INTERFACE
The ADS1113/4/5 communicate through an I2C
interface. I2C is a two-wire open-drain interface that
supports multiple devices and masters on a single
bus. Devices on the I2C bus only drive the bus lines
low by connecting them to ground; they never drive
the bus lines high. Instead, the bus wires are pulled
high by pull-up resistors, so the bus wires are high
when no device is driving them low. This way, two
devices cannot conflict; if two devices drive the bus
simultaneously, there is no driver contention.
Communication on the I2C bus always takes place
between two devices, one acting as the master and
the other as the slave. Both masters and slaves can
read and write, but slaves can only do so under the
direction of the master. Some I2C devices can act as
masters or slaves, but the ADS1113/4/5 can only act
as slave devices.
16
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An I2C bus consists of two lines, SDA and SCL. SDA
carries data; SCL provides the clock. All data are
transmitted across the I2C bus in groups of eight bits.
To send a bit on the I2C bus, the SDA line is driven to
the appropriate level while SCL is low (a low on SDA
indicates the bit is zero; a high indicates the bit is
one). Once the SDA line settles, the SCL line is
brought high, then low. This pulse on SCL clocks the
SDA bit into the receiver shift register. If the I2C bus
is held idle for more than 25ms, the bus times out.
The I2C bus is bidirectional: the SDA line is used for
both transmitting and receiving data. When the
master reads from a slave, the slave drives the data
line; when the master sends to a slave, the master
drives the data line. The master always drives the
clock line. The ADS1113/4/5 never drive SCL,
because they cannot act as a master. On the
ADS1113/4/5, SCL is an input only.
Most of the time the bus is idle; no communication
occurs, and both lines are high. When communication
is taking place, the bus is active. Only master devices
can start a communication and initiate a START
condition on the bus. Normally, the data line is only
allowed to change state while the clock line is low. If
the data line changes state while the clock line is
high, it is either a START condition or a STOP
condition. A START condition occurs when the clock
line is high and the data line goes from high to low. A
STOP condition occurs when the clock line is high
and the data line goes from low to high.
After the master issues a START condition, it sends a
byte that indicates which slave device it wants to
communicate with. This byte is called the address
byte. Each device on an I2C bus has a unique 7-bit
address to which it responds. The master sends an
address in the address byte, together with a bit that
indicates whether it wishes to read from or write to
the slave device.
Every byte transmitted on the I2C bus, whether it is
address or data, is acknowledged with an
acknowledge bit. When the master has finished
sending a byte (eight data bits) to a slave, it stops
driving SDA and waits for the slave to acknowledge
the byte. The slave acknowledges the byte by pulling
SDA low. The master then sends a clock pulse to
clock the acknowledge bit. Similarly, when the master
has finished reading a byte, it pulls SDA low to
acknowledge this to the slave. It then sends a clock
pulse to clock the bit. (The master always drives the
clock line.)
A not-acknowledge is performed by simply leaving
SDA high during an acknowledge cycle. If a device is
not present on the bus, and the master attempts to
address it, it receives a not-acknowledge because no
device is present at that address to pull the line low.
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When the master has finished communicating with a
slave, it may issue a STOP condition. When a STOP
condition is issued, the bus becomes idle again. The
master may also issue another START condition.
When a START condition is issued while the bus is
active, it is called a repeated START condition.
See the Timing Requirements section for a timing
diagram showing the ADS1113/4/5 I2C transaction.
byte; the I2C specification prohibits acknowledgment
of the Hs master code. Upon receiving a master
code, the ADS1113/4/5 switch on Hs mode filters,
and communicate at up to 3.4MHz. The ADS1113/4/5
switch out of Hs mode with the next STOP condition.
For more information on high-speed mode, consult
the I2C specification.
SLAVE MODE OPERATIONS
I2C ADDRESS SELECTION
The ADS1113/4/5 have one address pin, ADDR, that
sets the I2C address. This pin can be connected to
ground, VDD, SDA, or SCL, allowing four addresses
to be selected with one pin as shown in Table 5 .
The state of the address pin ADDR is sampled
continuously.
Table 5. ADDR Pin Connection and
Corresponding Slave Address
ADDR PIN
SLAVE ADDRESS
Ground
1001000
VDD
1001001
SDA
1001010
SCL
1001011
I2C GENERAL CALL
The ADS1113/4/5 can act as either slave receivers or
slave transmitters. As a slave device, the
ADS1113/4/5 cannot drive the SCL line.
Receive Mode:
In slave receive mode the first byte transmitted from
the master to the slave is the address with the R/W
bit low. This byte allows the slave to be written to.
The next byte transmitted by the master is the
register pointer byte. The ADS1113/4/5 then
acknowledge receipt of the register pointer byte. The
next two bytes are written to the address given by the
register pointer. The ADS1113/4/5 acknowledge each
byte sent. Register bytes are sent with the most
significant byte first, followed by the least significant
byte.
Transmit Mode:
2
The ADS1113/4/5 respond to the I C general call
address (0000000) if the eighth bit is '0'. The devices
acknowledge the general call address and respond to
commands in the second byte. If the second byte is
00000110 (06h), the ADS1113/4/5 reset the internal
registers and enter power-down mode.
I2C SPEED MODES
The I2C bus operates at one of three speeds.
Standard mode allows a clock frequency of up to
100kHz; fast mode permits a clock frequency of up to
400kHz; and high-speed mode (also called Hs mode)
allows a clock frequency of up to 3.4MHz. The
ADS1113/4/5 are fully compatible with all three
modes.
No special action is required to use the ADS1113/4/5
in standard or fast mode, but high-speed mode must
be activated. To activate high-speed mode, send a
special address byte of 00001xxx following the
START condition, where xxx are bits unique to the
Hs-capable master. This byte is called the Hs master
code. (Note that this is different from normal address
bytes; the eighth bit does not indicate read/write
status.) The ADS1113/4/5 do not acknowledge this
In slave transmit mode, the first byte transmitted by
the master is the 7-bit slave address followed by the
high R/W bit. This byte places the slave into transmit
mode and indicates that the ADS1113/4/5 are being
read from. The next byte transmitted by the slave is
the most significant byte of the register that is
indicated by the register pointer. This byte is followed
by an acknowledgment from the master. The
remaining least significant byte is then sent by the
slave and is followed by an acknowledgment from the
master. The master may terminate transmission after
any byte by not acknowledging or issuing a START or
STOP condition.
WRITING/READING THE REGISTERS
To access a specific register from the ADS1113/4/5,
the master must first write an appropriate value to the
Pointer register. The Pointer register is written directly
after the slave address byte, low R/W bit, and a
successful slave acknowledgment. After the Pointer
register is written, the slave acknowledges and the
master issues a STOP or a repeated START
condition.
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POINTER REGISTER
When reading from the ADS1113/4/5, the previous
value written to the Pointer register determines the
register that is read from. To change which register is
read, a new value must be written to the Pointer
register. To write a new value to the Pointer register,
the master issues a slave address byte with the R/W
bit low, followed by the Pointer register byte. No
additional data need to be transmitted, and a STOP
condition can be issued by the master. The master
may now issue a START condition and send the
slave address byte with the R/W bit high to begin the
read. Table 10 details this sequence. If repeated
reads from the same register are desired, there is no
need to continually send Pointer register bytes,
because the ADS1113/4/5 store the value of the
Pointer register until it is modified by a write
operation. However, every write operation requires
the Pointer register to be written.
The four registers are accessed by writing to the
Pointer register byte; see Figure 30 . Table 6 and
Table 7 indicate the Pointer register byte map.
Table 6. Register Address
BIT 1
BIT 0
REGISTER
0
0
Conversion register
0
1
Config register
1
0
Lo_thresh register
1
1
Hi_thresh register
CONVERSION REGISTER
The 16-bit register contains the result of the last
conversion in binary twos complement format.
Following reset or power-up, the Conversion register
is cleared to '0', and remains '0' until the first
conversion is completed.
REGISTERS
The ADS1113/4/5 have four registers that are
accessible via the I2C port. The Conversion register
contains the result of the last conversion. The Config
register allows the user to change the ADS1113/4/5
operating modes and query the status of the devices.
Two registers, Lo_thresh and Hi_thresh, set the
threshold values used for the comparator function.
The register format is shown in Table 8 .
CONFIG REGISTER
The 16-bit register can be used to control the
ADS1113/4/5 operating mode, input selection, data
rate, PGA settings, and comparator modes. The
register format is shown in Table 9 .
Table 7. Pointer Register Byte (Write-Only)
BIT 7
BIT 6
BIT 5
BIT 4
BIT 3
BIT 2
0
0
0
0
0
0
BIT 1
BIT 0
Register address
Table 8. Conversion Register (Read-Only)
BIT
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
NAME
D15
D14
D13
D12
D11
D10
D9
D8
D7
D6
D5
D4
D3
D2
D1
D0
Table 9. Config Register (Read/Write)
BIT
15
14
13
12
11
10
9
8
NAME
OS
MUX2
MUX1
MUX0
PGA2
PGA1
PGA0
MODE
3
2
blank
BIT
7
6
5
4
NAME
DR2
DR1
DR0
COMP_MODE
COMP_POL COMP_LAT
1
0
COMP_QUE1
COMP_QUE0
Default = 8583h.
Bit [15]
OS: Operational status/single-shot conversion start
This bit determines the operational status of the device.
This bit can only be written when in power-down mode.
For a write status:
0 : No effect
1 : Begin a single conversion (when in power-down mode)
For a read status:
0 : Device is currently performing a conversion
1 : Device is not currently performing a conversion
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Bits [14:12]
MUX[2:0]: Input multiplexer configuration (ADS1115 only)
These bits configure the input multiplexer. They serve no function on the ADS1113/4.
000 : AINP = AIN0 and AINN = AIN1 (default)
001 : AINP = AIN0 and AINN = AIN3
010 : AINP = AIN1 and AINN = AIN3
011 : AINP = AIN2 and AINN = AIN3
Bits [11:9]
100 : AINP = AIN0 and AINN = GND
101 : AINP = AIN1 and AINN = GND
110 : AINP = AIN2 and AINN = GND
111 : AINP = AIN3 and AINN = GND
PGA[2:0]: Programmable gain amplifier configuration (ADS1114 and ADS1115 only)
These bits configure the programmable gain amplifier. They serve no function on the ADS1113.
000 : FS = ±6.144V (1)
001 : FS = ±4.096V (1)
010 : FS = ±2.048V (default)
011 : FS = ±1.024V
Bit [8]
100 : FS = ±0.512V
101 : FS = ±0.256V
110 : FS = ±0.256V
111 : FS = ±0.256V
MODE: Device operating mode
This bit controls the current operational mode of the ADS1113/4/5.
0 : Continuous conversion mode
1 : Power-down single-shot mode (default)
Bits [7:5]
DR[2:0]: Data rate
These bits control the data rate setting.
000 : 8SPS
001 : 16SPS
010 : 32SPS
011 : 64SPS
Bit [4]
100 : 128SPS (default)
101 : 250SPS
110 : 475SPS
111 : 860SPS
COMP_MODE: Comparator mode (ADS1114 and ADS1115 only)
This bit controls the comparator mode of operation. It changes whether the comparator is implemented as a
traditional comparator (COMP_MODE = '0') or as a window comparator (COMP_MODE = '1'). It serves no
function on the ADS1113.
0 : Traditional comparator with hysteresis (default)
1 : Window comparator
Bit [3]
COMP_POL: Comparator polarity (ADS1114 and ADS1115 only)
This bit controls the polarity of the ALERT/RDY pin. When COMP_POL = '0' the comparator output is active
low. When COMP_POL='1' the ALERT/RDY pin is active high. It serves no function on the ADS1113.
0 : Active low (default)
1 : Active high
Bit [2]
COMP_LAT: Latching comparator (ADS1114 and ADS1115 only)
This bit controls whether the ALERT/RDY pin latches once asserted or clears once conversions are within the
margin of the upper and lower threshold values. When COMP_LAT = '0', the ALERT/RDY pin does not latch
when asserted. When COMP_LAT = '1', the asserted ALERT/RDY pin remains latched until conversion data
are read by the master or an appropriate SMBus alert response is sent by the master, the device responds with
its address, and it is the lowest address currently asserting the ALERT/RDY bus line. This bit serves no
function on the ADS1113.
0 : Non-latching comparator (default)
1 : Latching comparator
Bits [1:0]
COMP_QUE: Comparator queue and disable (ADS1114 and ADS1115 only)
These bits perform two functions. When set to '11', they disable the comparator function and put the
ALERT/RDY pin into a high state. When set to any other value, they control the number of successive
conversions exceeding the upper or lower thresholds required before asserting the ALERT/RDY pin. They
serve no function on the ADS1113.
00 : Assert after one conversion
01 : Assert after two conversions
10 : Assert after four conversions
11 : Disable comparator (default)
(1)
This parameter expresses the full-scale range of the ADC scaling. In no event should more than VDD + 0.3V be applied to this device.
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Lo_thresh AND Hi_thresh REGISTERS
A secondary conversion ready function of the
comparator output pin can be realized by setting the
Hi_thresh register MSB to '1' and the Lo_thresh
register MSB to ‘0’. However, in all other cases, the
Hi_thresh register must be larger than the Lo_thresh
register. The threshold register formats are shown in
Table 10 . When set to RDY mode, the ALERT/RDY
pin outputs the OS bit when in single-shot mode and
pulses when in continuous conversion mode.
The upper and lower threshold values used by the
comparator are stored in two 16-bit registers. These
registers store values in the same format that the
output register displays values; that is, they are
stored in twos complement format. Because it is
implemented as a digital comparator, special
attention should be taken to readjust values
whenever PGA settings are changed.
Table 10. Lo_thresh and Hi_thresh Registers
REGISTER
Lo_thresh (Read/Write)
BIT
15
14
13
12
11
10
9
8
NAME
Lo_thresh15
Lo_thresh14
Lo_thresh13
Lo_thresh12
Lo_thresh11
Lo_thresh10
Lo_thresh9
Lo_thresh8
BIT
7
6
5
4
3
2
1
0
NAME
Lo_thresh7
Lo_thresh6
Lo_thresh5
Lo_thresh4
Lo_thresh3
Lo_thresh2
Lo_thresh1
Lo_thresh0
BIT
15
14
13
12
11
10
9
8
NAME
Hi_thresh15
Hi_thresh14
Hi_thresh13
Hi_thresh12
Hi_thresh11
Hi_thresh10
Hi_thresh9
Hi_thresh8
BIT
7
6
5
4
3
2
1
0
NAME
Hi_thresh7
Hi_thresh6
Hi_thresh5
Hi_thresh4
Hi_thresh3
Hi_thresh2
Hi_thresh1
Hi_thresh0
blank
REGISTER
Hi_thresh (Read/Write)
blank
Lo_thresh default = 8000h.
Hi_thresh default = 7FFFh.
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1
9
1
9
SCL
¼
SDA
1
0
0
1
0
A1
(1)
A0
(1)
R/W
Start By
Master
0
0
0
0
0
0
P1
P0
ACK By
ADS1113/4/5
ACK By
ADS1113/4/5
Frame 1 Two-Wire Slave Address Byte
Stop By
Master
Frame 2 Pointer Register Byte
1
9
1
9
SCL
(Continued)
¼
SDA
(Continued)
1
0
0
0
1
A1
(1)
A0
(1)
R/W
Start By
Master
D15
D14
D13
D12 D11
1
D9
D8
From
ADS1113/4/5
ACK By
ADS1113/4/5
Frame 3 Two-Wire Slave Address Byte
D10
¼
ACK By
Master
(2)
Frame 4 Data Byte 1 Read Register
9
SCL
(Continued)
SDA
(Continued)
D7
D6
D5
D4
D3
D2
D1
D0
From
ADS1113/4/5
ACK By
Master
(3)
Stop By
Master
Frame 5 Data Byte 2 Read Register
(1)
The values of A0 and A1 are determined by the ADDR pin.
(2)
Master can leave SDA high to terminate a single-byte read operation.
(3)
Master can leave SDA high to terminate a two-byte read operation.
Figure 30. Two-Wire Timing Diagram for Read Word Format
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1
9
1
9
SCL
¼
1
SDA
0
0
1
A1(1)
0
A0(1)
R/W
Start By
Master
0
0
0
0
0
0
P1
P0
ACK By
ADS1113/4/5
¼
ACK By
ADS1113/4/5
Frame 2 Pointer Register Byte
Frame 1 Two-Wire Slave Address Byte
1
9
1
9
SCL
(Continued)
SDA
(Continued)
D15 D14
D13
D12 D11 D10
D9
D7
D8
D6
D5
D4
D3
D2
D1
D0
ACK By
ADS1113/4/5
ACK By
ADS1113/4/5
Frame 4 Data Byte 2
Frame 3 Data Byte 1
(1)
Stop By
Master
The values of A0 and A1 are determined by the ADDR pin.
Figure 31. Two-Wire Timing Diagram for Write Word Format
ALERT
1
9
1
9
SCL
SDA
0
0
0
1
Start By
Master
1
0
0
R/W
0
0
1
A1
ACK By
ADS1113/4/5
Frame 1 SMBus ALERT Response Address Byte
(1)
1
A0
From
ADS1113/4/5
Status
NACK By
Master
Stop By
Master
Frame 2 Slave Address From ADS1115
The values of A0 and A1 are determined by the ADDR pin.
Figure 32. Timing Diagram for SMBus ALERT Response
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APPLICATION INFORMATION
The following sections give example circuits and
suggestions for using the ADS1113/4/5 in various
situations.
The ADS1113/4/5 interface directly to standard mode,
fast mode, and high-speed mode I2C controllers. Any
microcontroller I2C peripheral, including master-only
and non-multiple-master I2C peripherals, can operate
with the ADS1113/4/5. The ADS1113/4/5 do not
perform clock-stretching (that is, they never pull the
clock line low), so it is not necessary to provide for
this function unless other clock-stretching devices are
on the same I2C bus.
BASIC CONNECTIONS
For many applications, connecting the ADS1113/4/5
is simple. A basic connection diagram for the
ADS1115 is shown in Figure 33 .
The fully differential voltage input of the ADS1113/4/5
is ideal for connection to differential sources with
moderately low source impedance, such as
thermocouples and thermistors. Although the
ADS1113/4/5 can read bipolar differential signals,
they cannot accept negative voltages on either input.
It may be helpful to think of the ADS1113/4/5 positive
voltage input as noninverting, and of the negative
input as inverting.
Pull-up resistors are required on both the SDA and
SCL lines because I2C bus drivers are open-drain.
The size of these resistors depends on the bus
operating speed and capacitance of the bus lines.
Higher-value resistors consume less power, but
increase the transition times on the bus, limiting the
bus speed. Lower-value resistors allow higher speed
at the expense of higher power consumption. Long
bus lines have higher capacitance and require
smaller pull-up resistors to compensate. The resistors
should not be too small; if they are, the bus drivers
may not be able to pull the bus lines low.
When the ADS1113/4/5 are converting data, they
draw current in short spikes. The 0.1μF bypass
capacitor supplies the momentary bursts of extra
current needed from the supply.
ADS1115
10
VDD
SCL
1
ADDR
SDA
9
2
ALERT/RDY
VDD
8
3
GND
AIN3
7
4
AIN0
AIN2
6
VDD
Pull-Up Resistors
1kW to 10kW (typ)
Microcontroller or
Microprocessor
0.1mF (typ)
AIN1
2
with I C Port
5
SCL
SDA
GPIO
Inputs Selected
from Configuration
Register
Figure 33. Typical Connections of the ADS1115
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CONNECTING MULTIPLE DEVICES
Connecting multiple ADS1113/4/5s to a single bus is
simple. Using the address pin, the ADS1113/4/5 can
be set to one of four different I2C addresses. An
example showing three ADS1113/4/5 devices is given
in Figure 35 . Up to four ADS1113/4/5s (using
different address pin configurations) can be
connected to a single bus.
Note that only one set of pull-up resistors is needed
per bus. The pull-up resistor values may need to be
lowered slightly to compensate for the additional bus
capacitance presented by multiple devices and
increased line length.
The TMP421 and DAC8574 devices detect the
respective I2C bus addresses based on the states of
pins. In the example, the TMP421 has the address
0101010, and the DAC8574 has the address
1001100. Consult the DAC8574 and TMP421 data
sheets, available at www.ti.com, for further details.
USING GPIO PORTS FOR COMMUNICATION
Most
microcontrollers
have
programmable
input/output (I/O) pins that can be set in software to
act as inputs or outputs. If an I2C controller is not
available, the ADS1113/4/5 can be connected to
GPIO pins and the I2C bus protocol simulated, or
bit-banged, in software. An example of this
configuration for a single ADS1113/4/5 is shown in
Figure 34 .
states. To drive the line low, the pin is set to output
'0'; to let the line go high, the pin is set to input. When
the pin is set to input, the state of the pin can be
read; if another device is pulling the line low, this
configuration reads as a '0' in the port input register.
Note that no pull-up resistor is shown on the SCL
line. In this simple case, the resistor is not needed;
the microcontroller can simply leave the line on
output, and set it to '1' or '0' as appropriate. This
action is possible because the ADS1113/4/5 never
drive the clock line low. This technique can also be
used with multiple devices, and has the advantage of
lower current consumption as a result of the absence
of a resistive pull-up.
If there are any devices on the bus that may drive the
clock lines low, this method should not be used; the
SCL line should be high-Z or '0' and a pull-up resistor
provided as usual.
Some microcontrollers have selectable strong pull-up
circuits built in to the GPIO ports. In some cases,
these circuits can be switched on and used in place
of an external pull-up resistor. Weak pull-ups are also
provided on some microcontrollers, but usually these
are too weak for I2C communication. If there is any
doubt about the matter, test the circuit before
committing it to production.
Bit-banging I2C with GPIO pins can be done by
setting the GPIO line to '0' and toggling it between
input and output modes to apply the proper bus
ADS1115
VDD
Microcontroller or
Microprocessor
with GPIO Ports
GPIO_1
GPIO_0
10
SCL
1
ADDR
SDA
9
2
ALERT/RDY
VDD
8
3
GND
AIN3
7
4
AIN0
AIN2
6
AIN1
5
NOTE: ADS1113/4/5 power and input connections omitted for clarity.
Figure 34. Using GPIO with a Single ADS1115
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GND
VDD
GND
ADS1115
10
SCL
2
I C Pull-Up Resistors
1kW to 10kW (typ.)
VDD
1
ADDR
2
3
4
9
ALERT/RDY
VDD
8
GND
AIN3
7
AIN2
AIN0
6
AIN1
2
SCL
1
ADDR
SDA
9
2
ALERT/RDY
VDD
8
3
GND
AIN3
7
4
AIN0
AIN2
6
2
I C Pull-Up Resistors
1kW to 10kW (typ.)
VDD
AIN1
5
with I C Port
10
ADS1115
SDA
Microcontroller or
Microprocessor
VDD
5
Microcontroller or
Microprocessor
SCL
2
with I C Port
SDA
SCL
SDA
ADS1115
10
10
ADS1115
SCL
1
ADDR
2
ALERT/RDY
3
4
SCL
SDA
9
1
ADDR
SDA
9
VDD
8
2
ALERT/RDY
VDD
8
GND
AIN3
7
3
GND
AIN3
7
AIN0
AIN2
6
4
AIN0
AIN2
6
AIN1
AIN1
5
5
TMP421
ADS1115
10
SCL
1
2
ADDR
SDA
ALERT/RDY
3
GND
4
AIN0
VDD
9
Leave
Floating
1
DXP
V+
8
2
DXN
SCL
7
3
A1
SDA
6
4
A0
GND
5
1
VOUTA
A3
16
2
VOUTB
A2
15
3
VREFH
A1
14
4
VDD
A0
13
5
VREFL
IOVDD
12
6
GND
SDA
11
7
VOUTC
SCL
10
8
VOUTD
LDAC
9
8
AIN3
7
AIN2
6
DAC8574
AIN1
5
ADS1115
10
SCL
1
2
3
4
ADDR
SDA
ALERT/RDY
GND
VDD
AIN3
AIN0
AIN2
9
8
7
6
AIN1
5
NOTE: ADS1113/4/5 power and input connections omitted for
clarity. ADDR, A3, A2, A1, and A0 select the I2C addresses.
NOTE: ADS1113/4/5 power and input connections omitted for
clarity. The ADDR pin selects the I2C address.
Figure 36. Connecting Multiple Device Types
Figure 35. Connecting Multiple ADS1113/4/5s
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SINGLE-ENDED INPUTS
The ADS1115 input range is bipolar differential with
respect to the reference. The single-ended circuit
shown in Figure 37 covers only half the ADS1115
input scale because it does not produce differentially
negative inputs; therefore, one bit of resolution is lost.
Although the ADS1115 has two differential inputs, the
device can easily measure four single-ended signals.
Figure 37 shows a single-ended connection scheme.
The ADS1115 is configured for single-ended
measurement by configuring the MUX to measure
each channel with respect to ground. Data are then
read out of one input based on the selection on the
configuration register. The single-ended signal can
range from 0V to supply. The ADS1115 loses no
linearity anywhere within the input range. Negative
voltages cannot be applied to this circuit because the
ADS1115 can only accept positive voltages.
VDD
ADS1115
Output Codes
0-32767
10
SCL
1
ADDR
SDA
9
2
ALERT/RDY
VDD
8
3
GND
AIN3
7
4
AIN0
AIN2
6
0.1mF (typ)
AIN1
5
Inputs Selected
from Configuration
Register
NOTE: Digital and address pin connections omitted for clarity.
Figure 37. Measuring Single-Ended Inputs
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LOW-SIDE CURRENT MONITOR
Figure 38 shows a circuit for a low-side shunt-type
current monitor. The circuit monitors the voltage
across a shunt resistor, which is sized as small as
possible while giving a measurable output voltage.
This voltage is amplified by an OPA335 low-drift op
amp, and the result is read by the ADS1114/5.
It is suggested that the ADS1114/5 be operated at a
gain of 8. The gain of the OPA335 can then be set
lower. For a gain of 16, the op amp should be set up
to give a maximum output voltage no greater than
0.256V. If the shunt resistor is sized to provide a
maximum voltage drop of 50mV at full-scale current,
the full-scale input to the ADS1114/5 is 0.2V.
2.0V to 5V
3kW
V
0.1mF Typ
5V
FS = 0.2V
Load
OPA335
(1)
RS
(2)
R3
49.9kW
2
ADS1114
IC
1kW
G=4
-5V
The ADS1113/4/5 are fabricated in a small-geometry,
low-voltage process. The analog inputs feature
protection diodes to the supply rails. However, the
current-handling ability of these diodes is limited, and
the ADS1113/4/5 can be permanently damaged by
analog input voltages that remain more than
approximately 300mV beyond the rails for extended
periods. One way to protect against overvoltage is to
place current-limiting resistors on the input lines. The
ADS1113/4/5 analog inputs can withstand momentary
currents as large as 100mA.
If the ADS1113/4/5 are driven by an op amp with
high-voltage supplies, such as ±12V, protection
should be provided, even if the op amp is configured
so that it does not output out-of-range voltages. Many
op amps drift to one of the supply rails immediately
when power is applied, usually before the input has
stabilized; this momentary spike can damage the
ADS1113/4/5. This incremental damage results in
slow, long-term failure, which can be disastrous for
permanently installed, low-maintenance systems.
If an op amp or other front-end circuitry is used with
an ADS1113/4/5, performance characteristics must
be taken into account when designing the application.
(PGA Gain = 16)
256mV FS
(1)
Pull-down resistor to allow accurate swing
to 0V.
(2)
RS is sized for a 50mV drop at full-scale
current.
Figure 38. Low-Side Current Measurement
Copyright © 2009, Texas Instruments Incorporated
Product Folder Link(s): ADS1113 ADS1114 ADS1115
Submit Documentation Feedback
27
PACKAGE OPTION ADDENDUM
www.ti.com
8-Aug-2009
PACKAGING INFORMATION
Orderable Device
Status (1)
Package
Type
Package
Drawing
Pins Package Eco Plan (2)
Qty
ADS1113IDGSR
PREVIEW
MSOP
DGS
10
2500
TBD
Call TI
Call TI
ADS1113IDGST
PREVIEW
MSOP
DGS
10
250
TBD
Call TI
Call TI
ADS1113IRUGR
PREVIEW
QFN
RUG
10
3000
TBD
Call TI
Call TI
ADS1113IRUGT
PREVIEW
QFN
RUG
10
250
TBD
Call TI
Call TI
ADS1114IDGSR
PREVIEW
MSOP
DGS
10
2500
TBD
Call TI
Call TI
Lead/Ball Finish
MSL Peak Temp (3)
ADS1114IDGST
PREVIEW
MSOP
DGS
10
250
TBD
Call TI
Call TI
ADS1114IRUGR
PREVIEW
QFN
RUG
10
3000
TBD
Call TI
Call TI
ADS1114IRUGT
PREVIEW
QFN
RUG
10
250
TBD
Call TI
Call TI
ADS1115IDGSR
PREVIEW
MSOP
DGS
10
2500
TBD
Call TI
Call TI
ADS1115IDGST
PREVIEW
MSOP
DGS
10
250
TBD
Call TI
Call TI
ADS1115IRUGR
PREVIEW
QFN
RUG
10
3000
TBD
Call TI
Call TI
ADS1115IRUGT
PREVIEW
QFN
RUG
10
250
TBD
Call TI
Call TI
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and
package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS
compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is
provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the
accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take
reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on
incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited
information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI
to Customer on an annual basis.
Addendum-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
8-Aug-2009
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
ADS1113IDGSR
MSOP
DGS
10
SPQ
Reel
Reel
A0
Diameter Width (mm)
(mm) W1 (mm)
B0
(mm)
K0
(mm)
P1
(mm)
W
Pin1
(mm) Quadrant
2500
330.0
12.4
5.3
3.3
1.3
8.0
12.0
Q1
ADS1113IDGST
MSOP
DGS
10
250
180.0
12.4
5.3
3.3
1.3
8.0
12.0
Q1
ADS1114IDGSR
MSOP
DGS
10
2500
330.0
12.4
5.3
3.3
1.3
8.0
12.0
Q1
ADS1114IDGST
MSOP
DGS
10
250
180.0
12.4
5.3
3.3
1.3
8.0
12.0
Q1
ADS1115IDGSR
MSOP
DGS
10
2500
330.0
12.4
5.3
3.3
1.3
8.0
12.0
Q1
ADS1115IDGST
MSOP
DGS
10
250
180.0
12.4
5.3
3.3
1.3
8.0
12.0
Q1
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
8-Aug-2009
*All dimensions are nominal
Device
Package Type
Package Drawing
Pins
SPQ
Length (mm)
Width (mm)
Height (mm)
ADS1113IDGSR
MSOP
DGS
10
2500
370.0
355.0
55.0
ADS1113IDGST
MSOP
DGS
10
250
195.0
200.0
45.0
ADS1114IDGSR
MSOP
DGS
10
2500
370.0
355.0
55.0
ADS1114IDGST
MSOP
DGS
10
250
195.0
200.0
45.0
ADS1115IDGSR
MSOP
DGS
10
2500
370.0
355.0
55.0
ADS1115IDGST
MSOP
DGS
10
250
195.0
200.0
45.0
Pack Materials-Page 2
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