AD AD704JR-REEL Quad picoampere input current bipolar op amp Datasheet

a
Quad Picoampere Input Current
Bipolar Op Amp
AD704
FEATURES
High DC Precision
75 mV max Offset Voltage
1 mV/8C max Offset Voltage Drift
150 pA max Input Bias Current
0.2 pA/8C typical IB Drift
Low Noise
0.5 mV p-p typical Noise, 0.1 Hz to 10 Hz
Low Power
600 mA max Supply Current per Amplifier
Chips & MIL-STD-883B Processing Available
Available in Tape and Reel in Accordance
with EIA-481A Standard
Single Version: AD705, Dual Version: AD706
CONNECTION DIAGRAMS
14-Pin Plastic DIP (N)
14-Pin Cerdip (Q) Packages
OUTPUT
1
–IN
2
+ IN
3
+VS
4
14
1
4
AD704
16-Pin SOIC
(R) Package
OUTPUT
OUTPUT
1
13
–IN
–IN
2
12
+ IN
+ IN
3
11
–V S
+V S
4
5
–IN
6
OUTPUT
7
2
4
AD704
15
–IN
14
+ IN
13
–V S
12
+ IN
11
–IN
10
+ IN
+ IN
5
9
–IN
–IN
6
8
OUTPUT
OUTPUT
7
10
NC
8
9
3
PRIMARY APPLICATIONS
Industrial/Process Controls
Weigh Scales
ECG/EKG Instrumentation
Low Frequency Active Filters
1
OUTPUT
(TOP VIEW)
(TOP VIEW)
+ IN
16
2
3
OUTPUT
NC
NC = NO CONNECT
–IN1
OUT1
NC
OUT4
–IN4
(E) Package 20-Terminal LCC
3
2
1
20
19
PRODUCT DESCRIPTION
100
TYPICAL I B – nA
TYPICAL JFET AMP
1
0.1
AD704T
+25
18 +IN4
NC 5
AMP 1
+VS 6
NC 7
17 NC
AMP 4
16 –VS
AD704
AMP 2
AMP 3
15 NC
+IN2 8
9
10
11
12
13
OUT2
NC
OUT3
–IN3
14 +IN3
NC = NO CONNECT
Since it has only 1/20 the input bias current of an AD OP07, the
AD704 does not require the commonly used “balancing”
resistor. Furthermore, the current noise is 1/5 that of the
AD OP07 which makes the AD704 usable with much higher
source impedances. At 1/6 the supply current (per amplifier) of
the AD OP07, the AD704 is better suited for today’s higher
density circuit boards and battery powered applications.
10
0.01
–55
+IN1 4
–IN2
The AD704 is a quad, low power bipolar op amp that has the
low input bias current of a BiFET amplifier but which offers a
significantly lower IB drift over temperature. It utilizes Superbeta bipolar input transistors to achieve picoampere input bias
current levels (similar to FET input amplifiers at room temperature), while its IB typically only increases by 5× at +125°C
(unlike a BiFET amp, for which IB doubles every 10°C resulting
in a 1000× increase at +125°C). Furthermore the AD704
achieves 75 µV offset voltage and low noise characteristics of a
precision bipolar input op amp.
+125
TEMPERATURE – °C
Figure 1. Input Bias Current Over Temperature
The AD704 is an excellent choice for use in low frequency
active filters in 12- and 14-bit data acquisition systems, in
precision instrumentation, and as a high quality integrator. The
AD704 is internally compensated for unity gain and is available
in five performance grades. The AD704J and AD704K are rated
over the commercial temperature range of 0°C to +70°C. The
AD704A and AD704B are rated over the industrial temperature
of –40°C to +85°C. The AD704T is rated over the military
temperature range of –55°C to +125°C and is available
processed to MIL-STD-883B, Rev. C.
REV. A
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700
Fax: 617/326-8703
AD704–SPECIFICATIONS (@ T = +258C, V
A
Model
Conditions
INPUT OFFSET VOLTAGE
Initial Offset
Offset
vs. Temp, Average TC
vs. Supply (PSRR)
TMIN –TMAX
Long Term Stability
INPUT BIAS CURRENT 1
vs. Temp, Average TC
TMIN –TMAX
TMIN –TMAX
INPUT OFFSET CURRENT
vs. Temp, Average TC
TMIN –TMAX
TMIN –TMAX
CM
= 0 V, and 615 V dc, unless otherwise noted)
AD704J/A
Min Typ Max
AD704K/B
Min Typ Max
50
100
0.2
132
126
0.3
150
250
1.5
30
50
0.2
132
126
0.3
75
150
1.0
100
270
300
80
150
200
TMIN –TMAX
100
VS = ± 2 to ± 18 V
VS = ± 2.5 to ± 18 V 100
VCM = 0 V
VCM = ± 13.5 V
0.3
VCM = 0 V
VCM = ± 13.5 V
VCM = 0 V
VCM = ± 13.5 V
80
0.6
100
100
VCM = 0 V
VCM = ± 13.5 V
Input Bias Current2
TMIN –TMAX
Common-Mode Rejection 3
TMIN –TMAX
Power Supply Rejection 4
FREQUENCY RESPONSE
UNITY GAIN
Crossover Frequency
Slew Rate, Unity Gain
Slew Rate
TMIN –TMAX
f = 10 Hz
RLOAD = 2 kΩ
INPUT IMPEDANCE
Differential
Common-Mode
INPUT VOLTAGE RANGE
Common-Mode Voltage
Common-Mode Rejection Ratio
VCM = ± 13.5 V
TMIN –TMAX
250
300
30
0.4
80
80
300
400
94
94
94
94
G = –1
TMIN –TMAX
µV
µV
µV/°C
dB
dB
µV/month
200
250
pA
pA
pA/°C
pA
pA
1.0
600
700
100
150
50
0.4
80
100
200
300
110
104
110
106
150
200
400
500
150
250
400
600
104
104
110
106
pA
pA
pA/°C
pA
pA
µV
µV
pA
pA
dB
dB
dB
dB
150
150
150
dB
0.8
0.15
0.1
0.8
0.15
0.1
0.8
0.15
0.1
MHz
V/µs
V/µs
40i2
300i2
40i2
300i2
40i2
300i2
MΩipF
GΩipF
± 13.5 ± 14
100 132
98
128
± 13.5 ± 14
114 132
108 128
0.1 to 10 Hz
f = 10 Hz
3
50
3
50
INPUT VOLTAGE NOISE
0.1 to 10 Hz
f = 10 Hz
f = 1 kHz
0.5
17
15
0.5
17
15
VO = ± 12 V
RLOAD = 10 kΩ
TMIN –TMAX
VO = ± 10 V
RLOAD = 2 kΩ
TMIN –TMAX
80
Units
100
150
1.0
132
126
0.3
130
200
300
400
INPUT CURRENT NOISE
OPEN-LOOP GAIN
112
108
200
300
250
400
500
600
TMIN –TMAX
AD704T
Typ Max
30
80
0.2
300
400
MATCHING CHARACTERISTICS
Offset Voltage
Crosstalk5
112
108
Min
22
± 13.5 ± 14
110 132
108 128
V
dB
dB
3
50
2.0
0.5
17
15
22
pA p-p
fA/√Hz
2.0
22
µV p-p
nV/√Hz
nV/√Hz
200
150
2000
1500
400
300
2000
1500
400
300
2000
1500
V/mV
V/mV
200
150
1000
1000
300
200
1000
1000
200
100
1000
1000
V/mV
V/mV
–2–
REV. A
AD704
Model
Conditions
OUTPUT CHARACTERISTICS
Voltage Swing
RLOAD = 10 kΩ
TMIN –TMAX
Short Circuit
Current
CAPACITIVE LOAD
Drive Capability
AD704J/A
Min Typ Max
AD704K/B
Min Typ Max
Min
± 13
± 13
± 13
Gain = + 1
10,000
POWER SUPPLY
Rated Performance
Operating Range
Quiescent Current
± 2.0
TRANSISTOR COUNT
± 14
± 15
± 15
TMIN –TMAX
1.5
1.6
# of Transistors
180
± 14
± 15
AD704T
Typ Max
10,000
± 18
2.4
2.6
± 2.0
± 15
1.5
1.6
± 18
2.4
2.6
± 2.0
± 14
± 15
V
mA
10,000
pF
± 15
1.5
1.6
180
± 18
2.4
2.6
180
NOTES
1
Bias current specifications are guaranteed maximum at either input.
2
Input bias current match is the maximum difference between corresponding inputs of all four amplifiers.
3
CMRR match is the difference of ∆VOS/∆VCM between any two amplifiers, expressed in dB.
4
PSRR match is the difference between ∆VOS/∆VSUPPLY for any two amplifiers, expressed in dB.
5
See Figure 2a for test circuit.
All min and max specifications are guaranteed.
Specifications subject to change without notice.
ABSOLUTE MAXIMUM RATINGS 1
METALIZATION PHOTOGRAPH
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± 18 V
Internal Power Dissipation (+25°C) . . . . . . . . . . . See Note 2
Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± VS
Differential Input Voltage3 . . . . . . . . . . . . . . . . . . . . . . . ± 0.7 V
Output Short Circuit Duration (Single Input) . . . . . Indefinite
Storage Temperature Range
(Q) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to +150°C
(N, R) . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to +125°C
Operating Temperature Range
AD704J/K . . . . . . . . . . . . . . . . . . . . . . . . . . . 0°C to +70°C
AD704A/B . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C
AD704T . . . . . . . . . . . . . . . . . . . . . . . . . . –55°C to +125°C
Lead Temperature Range (Soldering 10 seconds) . . . . +300°C
Dimensions shown in inches and (mm).
Contact factory for latest dimensions.
NOTES
1
Stresses above those listed under “Absolute Maximum Ratings” may cause
permanent damage to the device. This is a stress rating only and functional
operation of the device at these or any other conditions above those indicated in
the operational section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect device reliability.
2
Specification is for device in free air:
14-Pin Plastic Package: θJA = 150°C/Watt
14-Pin Cerdip Package: θJA = 110°C/Watt
16-Pin SOIC Package: θJA = 100°C/Watt
20-Terminal LCC Package: θJA = 150°C/Watt
3
The input pins of this amplifier are protected by back-to-back diodes. If the
differential voltage exceeds ± 0.7 volts, external series protection resistors should
be added to limit the input current to less than 25 mA.
–80
AMP4
CROSSTALK – dB
–100
9k Ω
1k Ω
1/4
AD704
INPUT *
SIGNAL
OUTPUT
AD704
PIN 4
+V S
2.5k Ω
1k Ω
0.1 µF
COM
0.1 µF
AMP3
–120
–140
1µF
–160
AD704
PIN 11
10
100
1k
10k
100k
FREQUENCY – Hz
ALL 4 AMPLIFIERS ARE CONNECTED AS SHOWN
SIGNAL INPUT (SUCH THAT THE AMPLIFIER'S OUTPUT IS AT MAX
*THE
AMPLITUDE WITHOUT CLIPPING OR SLEW LIMITING) IS APPLIED TO ONE
Figure 2b. Crosstalk vs. Frequency
AMPLIFIER AT A TIME. THE OUTPUTS OF THE OTHER THREE AMPLIFIERS ARE
THEN MEASURED FOR CROSSTALK.
Figure 2a. Crosstalk Test Circuit
REV. A
AMP2
1µF
–V S
–3–
Units
V
V
mA
mA
AD704–Typical Characteristics (@ +258C, V = 615 V, unless otherwise noted)
S
ORDERING GUIDE
Model
Temperature Range
Package Option*
AD704JN
AD704JR
AD704JR-/REEL
AD704KN
AD704AN
AD704AQ
AD704AR
AD704AR-REEL
AD704BQ
AD704SE/883B
AD704TQ
AD704TQ/883B
0°C to +70°C
0°C to +70°C
0°C to +70°C
0°C to +70°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–55°C to +125°C
–55°C to +125°C
–55°C to +125°C
N-14
R-16
Tape and Reel
N-14
N-14
Q-14
R-16
Tape and Reel
Q-14
E-20A
Q-14
Q-14
50
50
40
40
40
30
20
10
30
20
10
0
30
20
10
0
–80
–40
0
+80
+40
0
–160
INPUT OFFSET VOLTAGE – µV
–80
0
+80
+160
–120
Figure 4. Typical Distribution of
Input Bias Current
–1.0
–1.5
+1.5
+1.0
+0.5
30
25
20
15
10
5
0
–VS
0
5
10
15
20
SUPPLY VOLTAGE – Volts
Figure 6. Input Common-Mode
Voltage Range vs. Supply Voltage
+60
+120
100
OFFSET VOLTAGE DRIFT – µV/°C
OUTPUT VOLTAGE – Volts p-p
–0.5
0
Figure 5. Typical Distribution of
Input Offset Current
35
+V S
–60
INPUT OFFSET CURRENT – pA
INPUT BIAS CURRENT – pA
Figure 3. Typical Distribution of
Input Offset Voltage
INPUT COMMON-MODE VOLTAGE LIMIT – Volts
(REFERRED TO SUPPLY VOLTAGES)
PERCENTAGE OF UNITS
50
PERCENTAGE OF UNITS
PERCENTAGE OF UNITS
Chips are also available.
*E = Leadless Ceramic Chip Carrier; N = Plastic DIP; Q = Cerdip;
R = Small Outline (SOIC).
SOURCE RESISTANCE
MAY BE EITHER BALANCED
OR UNBALANCED
10
1.0
0.1
1k
10k
100k
FREQUENCY – Hz
1M
Figure 7. Large Signal Frequency
Response
–4–
1k
10k
100k
1M
10M
100M
SOURCE RESISTANCE – Ω
Figure 8. Offset Voltage Drift vs.
Source Resistance
REV. A
AD704
120
4
40
30
20
10
0
100
3
2
1
0
2
3
4
POSITIVE I B
60
40
NEGATIVE I B
20
5
–10
–5
0
10
5
15
COMMON MODE VOLTAGE – Volts
WARM-UP TIME – Minutes
Figure 9. Typical Distribution of
Offset Voltage Drift
Figure 11. Input Bias Current vs.
Common-Mode Voltage
Figure 10. Change in Input Offset Voltage vs. Warm-Up Time
1000
Hz
1000
100
CURRENT NOISE – fA/
10
100
100Ω
10
10kΩ
20MΩ
VOUT
1
1
1
10
100
FREQUENCY – Hz
1
1000
Figure 12. Input Noise Voltage
Spectral Density
1000
FIGURE 15
+160
180
+140
160
+120
140
CMR – dB
VS = ± 15V
400
+125°C
+100
+80
+60
–55°C
5
10
15
20
SUPPLY VOLTAGE – ±Volts
Figure 15. Quiescent Supply
Current vs. Supply Voltage (per
Amplifier)
REV. A
T A = +25°C
120
100
–PSR
+PSR
350
0
V S = ±15V
80
+25°C
300
Figure 14. 0.1 Hz to 10 Hz Noise
Voltage
Figure 13. Input Noise Current
Spectral Density
500
450
100
10
FREQUENCY – Hz
PSR – dB
VOLTAGE NOISE – nV/ Hz
1
80
0
–15
0
–0.8
–0.4
0
+0.4
+0.8
INPUT OFFSET VOLTAGE DRIFT – µV/°C
QUIESCENT CURRENT – µA
INPUT BIAS CURRENT – pA
CHANGE IN OFFSET VOLTAGE – µV
PERCENTAGE OF UNITS
50
+40
60
+20
40
0
0.1
1
10
100
1k
10k
FREQUENCY – Hz
100k 1M
Figure 16. Common-Mode
Rejection vs. Frequency
–5–
20
0.1
1
10
100
1k
10k
FREQUENCY – Hz
100k 1M
Figure 17. Power Supply Rejection
vs. Frequency
AD704
+25 C
1M
+125 C
120
30
+VS
60
100
PHASE
80
90
60
120
150
40
GAIN
180
20
0
1
2
4 6 8 10
LOAD RESISTANCE – kΩ
0.01 0.1
100
Figure 18. Open-Loop Gain vs.
Load Resistance Over Temperature
1
R L= 10kΩ
–0.5
–1.0
–1.5
+1.5
+1.0
+0.5
–VS
–20
100k
CLOSED-LOOP OUTPUT IMPEDANCE – Ohms
0
OUTPUT VOLTAGE SWING – Volts
(REFERRED TO SUPPLY VOLTAGES)
–55 C
140
PHASE SHIFT – Degrees
OPEN-LOOP VOLTAGE GAIN – dB
OPEN-LOOP VOLTAGE GAIN
10M
10 100 1k 10k 100k 1M 10M
FREQUENCY – Hz
0
Figure 19. Open-Loop Gain and Phase
vs. Frequency
5
15
10
SUPPLY VOLTAGE – ±Volts
20
Figure 20. Output Voltage Swing vs.
Supply Voltage
RF
1000
+VS
100
0.1 µF
100
90
10
A V = –1000
1/4
AD704
1
V OUT
RL
2kΩ
V IN
A V = +1
CL
0.1
0.1 µF
10
0%
SQUARE
WAVE INPUT
0.01
I OUT = +1mA
2V
–VS
50µs
0.001
1
10
100
1k
FREQUENCY – Hz
10k
100k
Figure 21. Closed-Loop Output
Impedance vs. Frequency
Figure 22a. Unity Gain Follower
(For Large Signal Applications,
Resistor RF Limits the Current
Through the Input Protection
Diodes)
Figure 22b. Unity Gain Follower
Large Signal Pulse Response
RF = 10 kΩ, CL = 1,000 pF
10kΩ
5µs
5µs
+V S
100
90
100
90
0.1 µF
10kΩ
V IN
1/4
AD704
VOUT
RL
2.5kΩ
10
10
0%
0%
20mV
SQUARE
WAVE INPUT
CL
0.1 µF
20mV
–VS
Figure 22c. Unity Gain Follower
Small Signal Pulse Response
RF = 0 Ω, CL = 100 pF
Figure 22d. Unity Gain Follower
Small Signal Pulse Response
RF = 0 Ω, CL = 1,000 pF
–6–
Figure 23a. Unity Gain Inverter
Connection
REV. A
AD704
5µS
50µs
5µS
100
90
100
90
100
90
10
10
10
0%
0%
0%
20mV
Figure 23c. Unity Gain Inverter
Small Signal Pulse Response,
CL = 100 pF
47.5k
R4
Ct
DC
CMRR
TRIM
(5k POT)
Q1 =
GAIN TRIM
(500k POT)
OPTIONAL
AC CMRR TRIM
6.34k
R3
+VS
RG
6.34k
R1
ω
49.9k
R2
=
Figure 23d. Unity Gain Inverter Small
Signal Pulse Response, CL = 1,000 pF
C1
4C2
1
_________
__
Figure 23b. Unity Gain Inverter
Large Signal Pulse Response,
CL = 1,000 pF
2.4k
R5
20mV
R6
Q2 =
ω
C1C2
R6 = R7
1
= _________
R8 C3C4
R8 = R9
0.1 µF
1MΩ
R6
1/4
AD704
1MΩ
R7
C2
1/4
AD704
C1
1MΩ
R8
1/4
AD704
C3
1MΩ
R9
–VS
R10
R2
__ 2R2
INSTRUMENTATION AMPLIFIER GAIN = 1 +
+ ___ (FOR R1 = R3, R2 = R4 + R5)
R1 RG
2MΩ
0.01µF
C5
OUTPUT
1/4
AD704
C4
0.1 µF
–V IN
+VIN
C3
4C4
__
2V
R11
C6
2MΩ
0.01µF
ALL RESISTORS METAL FILM, 1%
OPTIONAL BALANCE RESISTOR
NETWORKS CAN BE REPLACED
WITH A SHORT
CAPACITORS C2 AND C4 ARE
SOUTHERN ELECTRONICS MPCC,
POLYCARBONATE, ±5%, 50 VOLT
Figure 24. Gain of 10 Instrumentation Amplifier with Post Filtering
The instrumentation amplifier circuit offers many performance
benefits including BiFET level input bias currents, low input
offset voltage drift and only 1.2 mA quiescent current. It will
operate for gains G ≥ 2, and at lower gains it will benefit from
the fact that there is no output amplifier offset and noise
contribution as encountered in a 3 op amp design. Good low
frequency CMRR is achieved even without the optional AC
CMRR trim (Figure 25). Table I provides resistance values for
3 common circuit gains. For other gains, use the following
equations:
Table I. Resistance Values for Various Gains
Circuit Gain
(G)
R1 & R3
RG (Max Value
of Trim Potentiometer)
Bandwidth
(–3 dB), Hz
10
100
1,000
6.34 kΩ
526 Ω
56.2 Ω
166 kΩ
16.6 kΩ
1.66 kΩ
50k
5k
0.5k
160
GAIN = 10, 0.2V p-p COMMON-MODE INPUT
COMMON MODE REJECTION – dB
The instrumentation amplifier with post filtering (Figure 24)
combines two applications which benefit greatly from the
AD704. This circuit achieves low power and dc precision over
temperature with a minimum of components.
R2 = R4 + R5 = 49.9 kΩ
49.9 kΩ
R1 = R3 =
0.9 G − 1
Max Value of RG =
Ct ≈
REV. A
99.8 k
0.06 G
140
CIRCUIT TRIMMED
USING CAPACITOR C t
120
100
80
TYPICAL MONOLITHIC IN AMP
60
40
WITHOUT CAPACITOR C t
20
0
1
10
100
FREQUENCY – Hz
1k
10k
Figure 25. Common-Mode Rejection vs. Frequency with
and without Capacitor Ct
1
2 π (R3) 5 × 105
–7–
AD704
The 1 Hz, 4-pole active filter offers dc precision with a minimum of components and cost. The low current noise, IOS, and
IB allow the use of 1 MΩ resistors without sacrificing the
1 µV/°C drift of the AD704. This means lower capacitor values
may be used, reducing cost and space. Furthermore, since the
AD704’s IB is as low as its IOS, over most of the MIL temperature range, most applications do not require the use of the
normal balancing resistor (with its stability capacitor). Adding the
optional balancing resistor enhances performance at high
temperatures, as shown in Figure 26. Table II gives capacitor
values for several common low pass responses.
120
WITHOUT OPTIONAL
BALANCE RESISTOR, R3
60
0
WITH OPTIONAL
BALANCE RESISTOR, R3
C1476–24–10/90
OFFSET VOLTAGE
OF FILTER CIRCUIT (RTI) – µV
180
–60
–120
–180
–40
0
+120
+40
+80
o
TEMPERATURE – C
Figure 26. VOS vs. Temperature Performance of the 1 Hz
Filter Circuit
Table II. 1 Hz, 4-Pole Low-Pass Filter Recommended Component Values
Desired Low
Pass Response
Section 1
Frequency
(Hz)
Bessel
Butterworth
0.1 dB Chebychev
0.2 dB Chebychev
0.5 dB Chebychev
1.0 dB Chebychev
1.43
1.00
0.648
0.603
0.540
0.492
Q
Section 2
Frequency
(Hz)
Q
C1
(mF)
C2
(mF)
C3
(mF)
C4
(mF)
0.522
0.541
0.619
0.646
0.705
0.785
1.60
1.00
0.948
0.941
0.932
0.925
0.806
1.31
2.18
2.44
2.94
3.56
0.116
0.172
0.304
0.341
0.416
0.508
0.107
0.147
0.198
0.204
0.209
0.206
0.160
0.416
0.733
0.823
1.00
1.23
0.0616
0.0609
0.0385
0.0347
0.0290
0.0242
Specified Values are for a –3 dB point of 1.0 Hz. For other frequencies simply scale capacitors C1 through C4 directly; i.e., for 3 Hz Bessel response, C1 = 0.0387 µF,
C2 = 0.0357 µF, C3 = 0.0533 µF, C4 = 0.0205 µF.
OUTLINE DIMENSIONS
14-Pin Cerdip (Q) Package
14-Pin Plastic DIP (N) Package
16-Pin Plastic SO (R) Package
20-Terminal LCCC (E) Package
0.100 (2.54)
0.064 (1.63)
0.358 (9.09)
0.342 (8.69)
NO. 1 PIN
INDEX
PRINTED IN U.S.A.
Dimensions shown in inches and (mm).
0.040 (1.02)
x 45° REF
3 PLCS
0.028 (0.71)
0.022 (0.56)
0.050
(1.27)
BSC
0.020 (0.51)
x 45° REF
–8–
REV. A