NSC DAC121S101CIMM 12-bit micro power, rro digital-to-analog converter Datasheet

DAC121S101/DAC121S101Q
12-Bit Micro Power, RRO Digital-to-Analog Converter
General Description
Features
The DAC121S101 is a full-featured, general purpose 12-bit
voltage-output digital-to-analog converter (DAC) that can operate from a single +2.7V to 5.5V supply and consumes just
177 µA of current at 3.6 Volts. The on-chip output amplifier
allows rail-to-rail output swing and the three wire serial interface operates at clock rates up to 30 MHz over the specified
supply voltage range and is compatible with standard SPI™,
QSPI, MICROWIRE and DSP interfaces. Competitive devices are limited to 20 MHz clock rates at supply voltages in
the 2.7V to 3.6V range.
The supply voltage for the DAC121S101 serves as its voltage
reference, providing the widest possible output dynamic
range. A power-on reset circuit ensures that the DAC output
powers up to zero volts and remains there until there is a valid
write to the device. A power-down feature reduces power
consumption to less than a microWatt.
The low power consumption and small packages of the
DAC121S101 make it an excellent choice for use in battery
operated equipment.
The DAC121S101 is a direct replacement for the AD5320 and
the DAC7512 and is one of a family of pin compatible DACs,
including the 8-bit DAC081S101 and the 10-bit DAC101S101.
The DAC121S101 operates over the extended industrial temperature range of −40°C to +105°C while the DAC121S101Q
operates over the Grade 1 automotive temperature range of
−40°C to +125°C. The DAC121S101 is available in a 6-lead
TSOT and an 8-lead MSOP and the DAC121S101Q is available in the 6-lead TSOT only.
■ DAC121S101Q is AEC-Q100 Grade 1 qualified and is
■
■
■
■
■
■
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manufactured on an Automotive Grade Flow.
Guaranteed Monotonicity
Low Power Operation
Rail-to-Rail Voltage Output
Power-on Reset to Zero Volts Output
Wide Temperature Range of −40°C to +125°C
Wide Power Supply Range of +2.7V to +5.5V
Small Packages
Power Down Feature
Key Specifications
■
■
■
■
■
■
■
Resolution
12 bits
DNL
+0.25, -0.15 LSB (typ)
Output Settling Time
8 µs (typ)
Zero Code Error
4 mV (typ)
Full-Scale Error
−0.06 %FS (typ)
Power Consumption
0.64mW (3.6V) / 1.43mW (5.5V) typ
— Normal Mode
— Pwr Down Mode 0.14µW (3.6V) / 0.39µW (5.5V) typ
Applications
■
■
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■
■
Battery-Powered Instruments
Digital Gain and Offset Adjustment
Programmable Voltage & Current Sources
Programmable Attenuators
Automotive
Pin Configuration
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20114902
SPI™ is a trademark of Motorola, Inc.
© 2010 National Semiconductor Corporation
201149
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DAC121S101/DAC121S101Q 12-Bit Micro Power, RRO Digital-to-Analog Converter
February 19, 2010
DAC121S101/DAC121S101Q
Ordering Information
Order Numbers
Temperature Range
Package
DAC121S101CIMM
−40°C ≤ TA ≤ +105°C
MSOP
DAC121S101CIMMX
−40°C ≤ TA ≤ +105°C
MSOP T/R
DAC121S101CIMK
−40°C ≤ TA ≤ +105°C
TSOT
DAC121S101CIMKX
−40°C ≤ TA ≤ +105°C
TSOT T/R
DAC121S101QCMK
−40°C ≤ TA ≤ +125°C
TSOT
−40°C ≤ TA ≤ +125°C
TSOT T/R
Evaluation Board
TSOT
DAC121S101QCMKX
DAC121S101EVAL
Top Mark
Feature
X60C
X61C
X61Q
AEC-Q100 Grade 1
Qualified; Automotive
Grade Production Flow
Block Diagram
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Pin Descriptions
TSOT
(SOT-23)
Pin No.
MSOP
Pin No.
1
4
VOUT
DAC Analog Output Voltage.
2
8
GND
Ground reference for all on-chip circuitry.
3
1
VA
Power supply and Reference input. Should be decoupled to GND.
4
7
DIN
Serial Data Input. Data is clocked into the 16-bit shift register on the falling edges of SCLK
after the fall of SYNC.
5
6
SCLK
Serial Clock Input. Data is clocked into the input shift register on the falling edges of this pin.
5
SYNC
Frame synchronization input for the data input. When this pin goes low, it enables the input
shift register and data is transferred on the falling edges of SCLK. The DAC is updated on
the 16th clock cycle unless SYNC is brought high before the 16th clock, in which case the
rising edge of SYNC acts as an interrupt and the write sequence is ignored by the DAC.
2, 3
NC
6
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Symbol
Description
No Connect. There is no internal connection to these pins.
2
Operating Ratings (Note 1, Note 2)
Operating Temperature Range
DAC121S101
2)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Supply Voltage, VA
Voltage on any Input Pin
Input Current at Any Pin (Note 3)
Package Input Current (Note 3)
Power Consumption at TA = 25°C
ESD Susceptibility (Note 5)
Human Body Model
Machine Model
Soldering Temperature, Infrared,
10 Seconds (Note 6)
Storage Temperature
DAC121S101Q
Supply Voltage, VA
Any Input Voltage (Note 7)
Output Load
SCLK Frequency
6.5V
−0.3V to (VA + 0.3V)
10 mA
20 mA
See (Note 4)
−40°C ≤ TA ≤ +105°C
−40°C ≤ TA ≤ +125°C
+2.7V to 5.5V
−0.1 V to (VA + 0.1 V)
0 to 1500 pF
Up to 30 MHz
Package Thermal Resistances
2500V
250V
Package
θJA
8-Lead MSOP
6-Lead TSOT
240°C/W
250°C/W
235°C
−65°C to +150°C
Electrical Characteristics
The following specifications apply for VA = +2.7V to +5.5V, RL = 2kΩ to GND, CL = 200 pF to GND, fSCLK = 30 MHz, input code
range 48 to 4047. Boldface limits apply for TMIN ≤ TA ≤ TMAX: all other limits TA = 25°C, unless otherwise specified.
Limits
(Note 9)
Units
(Limits)
Resolution
12
Bits (min)
Monotonicity
12
Bits (min)
±2.6
±8
LSB (max)
+0.25
+1.0
LSB (max)
−0.15
−0.7
LSB (min)
±0.11
±0.5
LSB (max)
Symbol
Parameter
Conditions
Typical
(Note 9)
STATIC PERFORMANCE
INL
Integral Non-Linearity
DNL
Differential Non-Linearity
Over Decimal codes 48 to 4047
VA = 2.7V to 5.5V
VA = 4.5V to 5.5V (Note 10)
ZE
Zero Code Error
IOUT = 0
+4
+15
mV (max)
FSE
Full-Scale Error
IOUT = 0
−0.06
−1.0
%FSR (max)
GE
Gain Error
All ones Loaded to DAC register
−0.10
±1.0
%FSR
ZCED
TC GE
Zero Code Error Drift
Gain Error Tempco
−20
µV/°C
VA = 3V
−0.7
ppm/°C
VA = 5V
−1.0
ppm/°C
OUTPUT CHARACTERISTICS
Output Voltage Range
ZCO
FSO
Zero Code Output
Full Scale Output
Maximum Load Capacitance
0
VA
(Note 10)
V (min)
V (max)
VA = 3V, IOUT = 10 µA
1.8
mV
VA = 3V, IOUT = 100 µA
5.0
mV
VA = 5V, IOUT = 10 µA
3.7
mV
VA = 5V, IOUT = 100 µA
5.4
mV
VA = 3V, IOUT = 10 µA
2.997
V
VA = 3V, IOUT = 100 µA
2.990
V
VA = 5V, IOUT = 10 µA
4.995
V
VA = 5V, IOUT = 100 µA
4.992
V
RL = ∞
1500
pF
RL = 2kΩ
1500
pF
1.3
Ohm
DC Output Impedance
3
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DAC121S101/DAC121S101Q
Absolute Maximum Ratings (Note 1, Note
DAC121S101/DAC121S101Q
Symbol
IOS
Parameter
Output Short Circuit Current
Conditions
Typical
(Note 9)
Limits
(Note 9)
Units
(Limits)
VA = 5V, VOUT = 0V,
Input code = FFFh
−63
mA
VA = 3V, VOUT = 0V,
Input code = FFFh
−50
mA
VA = 5V, VOUT = 5V,
Input code = 000h
74
mA
VA = 3V, VOUT = 3V,
Input code = 000h
53
mA
LOGIC INPUT
IIN
Input Current (Note 10)
VIL
Input Low Voltage (Note 10)
VIH
Input High Voltage (Note 10)
CIN
Input Capacitance (Note 10)
±1
µA (max)
VA = 5V
0.8
V (max)
VA = 3V
0.5
V (max)
VA = 5V
2.4
V (min)
VA = 3V
2.1
V (min)
3
pF (max)
POWER REQUIREMENTS
IA
PC
IOUT / IA
Supply Current (output unloaded)
Power Consumption (output
unloaded)
Power Efficiency
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Normal Mode
fSCLK = 30 MHz
VA = 5.5V
260
312
µA (max)
VA = 3.6V
177
217
µA (max)
Normal Mode
fSCLK = 20 MHz
VA = 5.5V
224
279
µA (max)
VA = 3.6V
158
197
µA (max)
Normal Mode
fSCLK = 0
VA = 5.5V
153
µA (max)
VA = 3.6V
118
µA (max)
All PD Modes,
fSCLK = 30 MHz
VA = 5.0V
84
µA (max)
VA = 3.0V
42
µA (max)
All PD Modes,
fSCLK = 20 MHz
VA = 5.0V
56
µA (max)
VA = 3.0V
28
µA (max)
All PD Modes,
fSCLK = 0 (Note 10)
VA = 5.5V
0.07
1.0
µA (max)
VA = 3.6V
0.04
1.0
µA (max)
Normal Mode
fSCLK = 30 MHz
VA = 5.5V
1.43
1.72
mW (max)
VA = 3.6V
0.64
0.78
mW (max)
Normal Mode
fSCLK = 20 MHz
VA = 5.5V
1.23
1.53
mW (max)
VA = 3.6V
0.57
0.71
mW (max)
Normal Mode
fSCLK = 0
VA = 5.5V
0.84
µW (max)
VA = 3.6V
0.42
µW (max)
All PD Modes,
fSCLK = 30 MHz
VA = 5.0V
0.42
µW (max)
VA = 3.0V
0.13
µW (max)
All PD Modes,
fSCLK = 20 MHz
VA = 5.0V
0.28
µW (max)
VA = 3.0V
0.08
All PD Modes,
fSCLK = 0 (Note 10)
VA = 5.5V
0.39
5.5
µW (max)
VA = 3.6V
0.14
3.6
µW (max)
ILOAD = 2mA
4
µW (max)
VA = 5V
91
%
VA = 3V
94
%
The following specifications apply for VA = +2.7V to +5.5V, RL = 2kΩ to GND, CL = 200 pF to GND, fSCLK = 30 MHz, input code
range 48 to 4047. Boldface limits apply for TMIN ≤ TA ≤ TMAX: all other limits TA = 25°C, unless otherwise specified.
Symbol
fSCLK
ts
SR
Parameter
Conductions
Typical
SCLK Frequency
Output Voltage Settling Time
(Note 10)
Units
(Limits)
30
MHz (max)
10
µs (max)
400h to C00h code
change, RL = 2kΩ
CL ≤ 200 pF
8
CL = 500 pF
12
µs
00Fh to FF0h code
change, RL = 2kΩ
CL ≤ 200 pF
8
µs
CL = 500 pF
12
µs
Output Slew Rate
Glitch Impulse
Limits
1
V/µs
12
nV-sec
0.5
nV-sec
VA = 5V
6
µs
VA = 3V
39
µs
Code change from 800h to 7FFh
Digital Feedthrough
tWU
Wake-Up Time
1/fSCLK
SCLK Cycle Time
33
ns (min)
tH
SCLK High time
5
13
ns (min)
tL
SCLK Low Time
5
13
ns (min)
tSUCL
Set-up Time SYNC to SCLK Rising
Edge
−15
0
ns (min)
tSUD
Data Set-Up Time
2.5
5
ns (min)
tDHD
Data Hold Time
tCS
SCLK fall to rise of SYNC
tSYNC
SYNC High Time
2.5
4.5
ns (min)
VA = 5V
0
3
ns (min)
VA = 3V
−2
1
ns (min)
2.7 ≤ VA ≤ 3.6
9
20
ns (min)
3.6 ≤ VA ≤ 5.5
5
10
ns (min)
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DAC121S101/DAC121S101Q
A.C. and Timing Characteristics
DAC121S101/DAC121S101Q
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrical Characteristics. The guaranteed
specifications apply only for the test conditions listed. Some performance characteristics may degrade when the device is not operated under the listed test
conditions.
Note 2: All voltages are measured with respect to GND = 0V, unless otherwise specified
Note 3: When the input voltage at any pin exceeds the power supplies (that is, less than GND, or greater than VA), the current at that pin should be limited to 10
mA. The 20 mA maximum package input current rating limits the number of pins that can safely exceed the power supplies with an input current of 10 mA to two.
Note 4: The absolute maximum junction temperature (TJMAX) for this device is 150°C. The maximum allowable power dissipation is dictated by TJMAX, the junctionto-ambient thermal resistance (θJA), and the ambient temperature (TA), and can be calculated using the formula PDMAX = (TJMAX − TA) / θJA. The values for maximum
power dissipation will be reached only when the device is operated in a severe fault condition (e.g., when input or output pins are driven beyond the power supply
voltages, or the power supply polarity is reversed). Obviously, such conditions should always be avoided.
Note 5: Human body model is 100 pF capacitor discharged through a 1.5 kΩ resistor. Machine model is 220 pF discharged through ZERO Ohms.
Note 6: See the section entitled "Surface Mount" found in any post 1986 National Semiconductor Linear Data Book for methods of soldering surface mount
devices.
Note 7: The analog inputs are protected as shown below. Input voltage magnitudes up to VA + 300 mV or to 300 mV below GND will not damage this device.
However, errors in the conversion result can occur if any input goes above VA or below GND by more than 100 mV. For example, if VA is 2.7VDC, ensure that
−100mV ≤ input voltages ≤2.8VDC to ensure accurate conversions.
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Note 8: To guarantee accuracy, it is required that VA be well bypassed.
Note 9: Typical figures are at TJ = 25°C, and represent most likely parametric norms. Test limits are guaranteed to National's AOQL (Average Outgoing Quality
Level).
Note 10: This parameter is guaranteed by design and/or characterization and is not tested in production.
Specification Definitions
DIFFERENTIAL NON-LINEARITY (DNL) is the measure of
the maximum deviation from the ideal step size of 1 LSB,
which is VREF / 4096 = VA / 4096.
DIGITAL FEEDTHROUGH is a measure of the energy injected into the analog output of the DAC from the digital inputs
when the DAC outputs are not updated. It is measured with a
full-scale code change on the data bus.
FULL-SCALE ERROR is the difference between the actual
output voltage with a full scale code (FFFh) loaded into the
DAC and the value of VA x 4095 / 4096.
GAIN ERROR is the deviation from the ideal slope of the
transfer function. It can be calculated from Zero and FullScale Errors as GE = FSE - ZE, where GE is Gain error, FSE
is Full-Scale Error and ZE is Zero Error.
GLITCH IMPULSE is the energy injected into the analog output when the input code to the DAC register changes. It is
specified as the area of the glitch in nanovolt-seconds.
INTEGRAL NON-LINEARITY (INL) is a measure of the deviation of each individual code from a straight line through the
input to output transfer function. The deviation of any given
code from this straight line is measured from the center of that
code value. The end point method is used. INL for this product
is specified over a limited range, per the Electrical Tables.
LEAST SIGNIFICANT BIT (LSB) is the bit that has the smallest value or weight of all bits in a word. This value is
MAXIMUM LOAD CAPACITANCE is the maximum capacitance that can be driven by the DAC with output stability
maintained.
MONOTONICITY is the condition of being monotonic, where
the DAC has an output that never decreases when the input
code increases.
MOST SIGNIFICANT BIT (MSB) is the bit that has the largest
value or weight of all bits in a word. Its value is 1/2 of VA.
POWER EFFICIENCY is the ratio of the output current to the
total supply current. The output current comes from the power
supply. The difference between the supply and output currents is the power consumed by the device without a load.
SETTLING TIME is the time for the output to settle to within
1/2 LSB of the final value after the input code is updated.
WAKE-UP TIME is the time for the output to settle to within
1/2 LSB of the final value after the device is commanded to
the active mode from any of the power down modes.
ZERO CODE ERROR is the output error, or voltage, present
at the DAC output after a code of 000h has been entered.
LSB = VREF / 2n
where VREF is the supply voltage for this product, and "n" is
the DAC resolution in bits, which is 12 for the DAC121S101.
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DAC121S101/DAC121S101Q
Transfer Characteristic
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FIGURE 1. Input / Output Transfer Characteristic
Timing Diagram
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FIGURE 2. DAC121S101 Timing
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DAC121S101/DAC121S101Q
Typical Performance Characteristics
fSCLK = 30 MHz, TA = 25C, Input Code Range 48 to 4047, unless
otherwise stated
DNL at VA = 3.0V
DNL at VA = 5.0V
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INL at VA = 3.0V
INL at VA = 5.0V
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TUE at VA = 3.0V
TUE at VA = 5.0V
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8
DAC121S101/DAC121S101Q
DNL vs. VA
INL vs. VA
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3V DNL vs. fSCLK
5V DNL vs. fSCLK
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3V DNL vs. Clock Duty Cycle
5V DNL vs. Clock Duty Cycle
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DAC121S101/DAC121S101Q
3V DNL vs. Temperature
5V DNL vs. Temperature
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3V INL vs. fSCLK
5V INL vs. fSCLK
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3V INL vs. Clock Duty Cycle
5V INL vs. Clock Duty Cycle
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10
DAC121S101/DAC121S101Q
3V INL vs. Temperature
5V INL vs. Temperature
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Zero Code Error vs. fSCLK
Zero Code Error vs. Clock Duty Cycle
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Zero Code Error vs. Temperature
Full-Scale Error vs. fSCLK
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DAC121S101/DAC121S101Q
Full-Scale Error vs. Clock Duty Cycle
Full-Scale Error vs. Temperature
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Supply Current vs. VA
Supply Current vs. Temperature
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5V Glitch Response
Power-On Reset
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12
DAC121S101/DAC121S101Q
3V Wake-Up Time
5V Wake-Up Time
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DAC121S101/DAC121S101Q
1.3 OUTPUT AMPLIFIER
The output buffer amplifier is a rail-to-rail type, providing an
output voltage range of 0V to VA. All amplifiers, even rail-torail types, exhibit a loss of linearity as the output approaches
the supply rails (0V and VA, in this case). For this reason,
linearity is specified over less than the full output range of the
DAC. The output capabilities of the amplifier are described in
the Electrical Tables.
1.0 Functional Description
1.1 DAC SECTION
The DAC121S101 is fabricated on a CMOS process with an
architecture that consists of switches and a resistor string that
are followed by an output buffer. The power supply serves as
the reference voltage. The input coding is straight binary with
an ideal output voltage of:
1.4 SERIAL INTERFACE
The three-wire interface is compatible with SPI, QSPI and
MICROWIRE, as well as most DSPs. See the Timing Diagram
for information on a write sequence.
A write sequence begins by bringing the SYNC line low. Once
SYNC is low, the data on the DIN line is clocked into the 16bit serial input register on the falling edges of SCLK. On the
16th falling clock edge, the last data bit is clocked in and the
programmed function (a change in the mode of operation and/
or a change in the DAC register contents) is executed. At this
point the SYNC line may be kept low or brought high. In either
case, it must be brought high for the minimum specified time
before the next write sequence as a falling edge of SYNC can
initiate the next write cycle.
Since the SYNC and DIN buffers draw more current when they
are high, they should be idled low between write sequences
to minimize power consumption.
VOUT = VA x (D / 4096)
where D is the decimal equivalent of the binary code that is
loaded into the DAC register and can take on any value between 0 and 4095.
1.2 RESISTOR STRING
The resistor string is shown in Figure 3. This string consists
of 4096 equal valued resistors with a switch at each junction
of two resistors, plus a switch to ground. The code loaded into
the DAC register determines which switch is closed, connecting the proper node to the amplifier. This configuration guarantees that the DAC is monotonic.
1.5 INPUT SHIFT REGISTER
The input shift register, Figure 4, has sixteen bits. The first
two bits are "don't cares" and are followed by two bits that
determine the mode of operation (normal mode or one of
three power-down modes). The contents of the serial input
register are transferred to the DAC register on the sixteenth
falling edge of SCLK. See Timing Diagram, Figure 2.
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FIGURE 3. DAC Resistor String
20114908
FIGURE 4. Input Register Contents
Normally, the SYNC line is kept low for at least 16 falling
edges of SCLK and the DAC is updated on the 16th SCLK
falling edge. However, if SYNC is brought high before the 16th
falling edge, the shift register is reset and the write sequence
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is invalid. The DAC register is not updated and there is no
change in the mode of operation or in the output voltage.
14
1.7 POWER-DOWN MODES
The DAC121S101 has four modes of operation. These
modes are set with two bits (DB13 and DB12) in the control
register.
20114909
FIGURE 5. ADSP-2101/2103 Interface
TABLE 1. Modes of Operation
DB13
DB12
0
0
Normal Operation
0
1
Power-Down with 1kΩ to GND
1
0
Power-Down with 100kΩ to GND
1
1
Power-Down with Hi-Z
2.1.2 80C51/80L51 Interface
A serial interface between the DAC121S101 and the
80C51/80L51 microcontroller is shown in Figure 6. The
SYNC signal comes from a bit-programmable pin on the microcontroller. The example shown here uses port line P3.3.
This line is taken low when data is to transmitted to the
DAC121S101. Since the 80C51/80L51 transmits 8-bit bytes,
only eight falling clock edges occur in the transmit cycle. To
load data into the DAC, the P3.3 line must be left low after the
first eight bits are transmitted. A second write cycle is initiated
to transmit the second byte of data, after which port line P3.3
is brought high. The 80C51/80L51 transmit routine must recognize that the 80C51/80L51 transmits data with the LSB first
while the DAC121S101 requires data with the MSB first.
Operating Mode
When both DB13 and DB12 are 0, the device operates normally. For the other three possible combinations of these bits
the supply current drops to its power-down level and the output is pulled down with either a 1kΩ or a 100KΩ resistor, or
is in a high impedance state, as described in Table 1.
The bias generator, output amplifier, the resistor string and
other linear circuitry are all shut down in any of the powerdown modes. However, the contents of the DAC register are
unaffected when in power-down, so when coming out of power down the output voltage returns to the same voltage it was
before entering power down. Minimum power consumption is
achieved in the power-down mode with SCLK disabled and
SYNC and DIN idled low. The time to exit power-down (WakeUp Time) is typically tWU µsec as stated in the A.C. and Timing
Characteristics Table.
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FIGURE 6. 80C51/80L51 Interface
2.0 Applications Information
2.1.3 68HC11 Interface
A serial interface between the DAC121S101 and the 68HC11
microcontroller is shown in Figure 7. The SYNC line of the
DAC121S101 is driven from a port line (PC7 in the figure),
similar to the 80C51/80L51.
The 68HC11 should be configured with its CPOL bit as a zero
and its CPHA bit as a one. This configuration causes data on
the MOSI output to be valid on the falling edge of SCLK. PC7
is taken low to transmit data to the DAC. The 68HC11 transmits data in 8-bit bytes with eight falling clock edges. Data is
transmitted with the MSB first. PC7 must remain low after the
first eight bits are transferred. A second write cycle is initiated
to transmit the second byte of data to the DAC, after which
PC7 should be raised to end the write sequence.
The simplicity of the DAC121S101 implies ease of use. However, it is important to recognize that any data converter that
utilizes its supply voltage as its reference voltage will have
essentially zero PSRR (Power Supply Rejection Ratio).
Therefore, it is necessary to provide a noise-free supply voltage to the device.
2.1 DSP/MICROPROCESSOR INTERFACING
Interfacing the DAC121S101 to microprocessors and DSPs
is quite simple. The following guidelines are offered to hasten
the design process.
2.1.1 ADSP-2101/ADSP2103 Interfacing
Figure 5 shows a serial interface between the DAC121S101
and the ADSP-2101/ADSP2103. The DSP should be set to
operate in the SPORT Transmit Alternate Framing Mode. It is
programmed through the SPORT control register and should
be configured for Internal Clock Operation, Active Low Framing and 16-bit Word Length. Transmission is started by writing
a word to the Tx register after the SPORT mode has been
enabled.
20114911
FIGURE 7. 68HC11 Interface
15
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DAC121S101/DAC121S101Q
1.6 POWER-ON RESET
The power-on reset circuit controls the output voltage during
power-up. Upon application of power the DAC register is filled
with zeros and the output voltage is 0 Volts and remains there
until a valid write sequence is made to the DAC.
DAC121S101/DAC121S101Q
Since the DAC121S101 consumes very little power, a reference source may be used as the supply voltage. The advantages of using a reference source over a voltage regulator are
accuracy and stability. Some low noise regulators can also be
used for the power supply of the DAC121S101. Listed below
are a few power supply options for the DAC121S101.
2.1.4 Microwire Interface
Figure 8 shows an interface between a Microwire compatible
device and the DAC121S101. Data is clocked out on the rising
edges of the SCLK signal.
2.2.1 LM4130
The LM4130 reference, with its 0.05% accuracy over temperature, is a good choice as a power source for the
DAC121S101. Its primary disadvantage is the lack of 3V and
5V versions. However, the 4.096V version is useful if a 0 to
4.095V output range is desirable or acceptable. Bypassing
the LM4130 VIN pin with a 0.1µF capacitor and the VOUT pin
with a 2.2µF capacitor will improve stability and reduce output
noise. The LM4130 comes in a space-saving 5-pin SOT23.
20114912
FIGURE 8. Microwire Interface
2.2 USING REFERENCES AS POWER SUPPLIES
Recall the need for a quiet supply source for devices that use
their power supply voltage as a reference voltage.
20114913
FIGURE 9. The LM4130 as a power supply
minimum due to tolerance, and the DAC121S101 draws zero
current. The maximum resistor value must allow the LM4050
to draw more than its minimum current for regulation plus the
maximum DAC121S101 current in full operation. The conditions for minimum current include the input voltage at its
minimum, the LM4050 voltage at its maximum, the resistor
value at its maximum due to tolerance, and the DAC121S101
draws its maximum current. These conditions can be summarized as
2.2.2 LM4050
Available with accuracy of 0.44%, the LM4050 shunt reference is also a good choice as a power regulator for the
DAC121S101. It does not come in a 3 Volt version, but 4.096V
and 5V versions are available. It comes in a space-saving 3pin SOT23.
R(min) = ( VIN(max) − VZ(min) / (IA(min) + IZ(max))
and
R(max) = ( VIN(min) − VZ(max) / (IA(max) + IZ(min) )
where V Z(min) and VZ(max) are the nominal LM4050 output
voltages ± the LM4050 output tolerance over temperature, IZ
(max) is the maximum allowable current through the LM4050,
IZ(min) is the minimum current required by the LM4050 for
proper regulation, IA(max) is the maximum DAC121S101 supply current, and IA(min) is the minimum DAC121S101 supply
current.
2.2.3 LP3985
The LP3985 is a low noise, ultra low dropout voltage regulator
with a 3% accuracy over temperature. It is a good choice for
applications that do not require a precision reference for the
DAC121S101. It comes in 3.0V, 3.3V and 5V versions, among
others, and sports a low 30 µV noise specification at low frequencies. Since low frequency noise is relatively difficult to
filter, this specification could be important for some applications. The LP3985 comes in a space-saving 5-pin SOT23 and
5-bump micro SMD packages.
20114914
FIGURE 10. The LM4050 as a power supply
The minimum resistor value in the circuit of Figure 10 should
be chosen such that the maximum current through the
LM4050 does not exceed its 15 mA rating. The conditions for
maximum current include the input voltage at its maximum,
the LM4050 voltage at its minimum, the resistor value at its
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16
2.2.4 LP2980
The LP2980 is an ultra low dropout regulator with a 0.5% or
1.0% accuracy over temperature, depending upon grade. It is
available in 3.0V, 3.3V and 5V versions, among others.
20114915
FIGURE 11. Using the LP3985 regulator
20114916
FIGURE 12. Using the LP2980 regulator
Like any low dropout regulator, the LP2980 requires an output
capacitor for loop stability. This output capacitor must be at
least 1.0µF over temperature, but values of 2.2µF or more will
provide even better performance. The ESR of this capacitor
should be within the range specified in the LP2980 data sheet.
Surface-mount solid tantalum capacitors offer a good combination of small size and ESR. Ceramic capacitors are attractive due to their small size but generally have ESR values that
are too low for use with the LP2980. Aluminum electrolytic
capacitors are typically not a good choice due to their large
size and have ESR values that may be too high at low temperatures.
2.3 BIPOLAR OPERATION
The DAC121S101 is designed for single supply operation and
thus has a unipolar output. However, a bipolar output may be
obtained with the circuit in Figure 13. This circuit will provide
an output voltage range of ±5 Volts. A rail-to-rail amplifier
should be used if the amplifier supplies are limited to ±5V.
20114917
FIGURE 13. Bipolar Operation
17
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DAC121S101/DAC121S101Q
An input capacitance of 1.0µF without any ESR requirement
is required at the LP3985 input, while a 1.0µF ceramic capacitor with an ESR requirement of 5mΩ to 500mΩ is required
at the output. Careful interpretation and understanding of the
capacitor specification is required to ensure correct device
operation.
DAC121S101/DAC121S101Q
tions of the analog and digital power planes. Both of these
planes should be located in the same board layer. There
should be a single ground plane. A single ground plane is
preferred if digital return current does not flow through the
analog ground area. Frequently a single ground plane design
will utilize a "fencing" technique to prevent the mixing of analog and digital ground current. Separate ground planes should
only be utilized when the fencing technique is inadequate.
The separate ground planes must be connected in one place,
preferably near the DAC121S101. Special care is required to
guarantee that digital signals with fast edge rates do not pass
over split ground planes. They must always have a continuous return path below their traces.
The DAC121S101 power supply should be bypassed with a
10µF and a 0.1µF capacitor as close as possible to the device
with the 0.1µF right at the device supply pin. The 10µF capacitor should be a tantalum type and the 0.1µF capacitor
should be a low ESL, low ESR type. The power supply for the
DAC121S101 should only be used for analog circuits.
Avoid crossover of analog and digital signals and keep the
clock and data lines on the component side of the board. The
clock and data lines should have controlled impedances.
The output voltage of this circuit for any code is found to be
VO = (VA x (D / 4096) x ((R1 + R2) / R1) - VA x R2 / R1)
where D is the input code in decimal form. With VA = 5V and
R1 = R2,
VO = (10 x D / 4096) - 5V
A list of rail-to-rail amplifiers suitable for this application are
indicated in Table 2.
TABLE 2. Some Rail-to-Rail Amplifiers
Typ ISUPPLY
AMP
PKGS
LMC7111
DIP-8
SOT23-5
0.9 mV
25 µA
LM7301
SO-8
SOT23-5
0.03 mV
620 µA
LM8261
SOT23-5
0.7 mV
1 mA
Typ VOS
2.4 LAYOUT, GROUNDING, AND BYPASSING
For best accuracy and minimum noise, the printed circuit
board containing the DAC121S101 should have separate
analog and digital areas. The areas are defined by the loca-
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18
DAC121S101/DAC121S101Q
Physical Dimensions inches (millimeters) unless otherwise noted
8-Lead MSOP
Order Number DAC121S101CIMM
NS Package Number MUA08A
6-Lead TSOT
Order Numbers DAC121S101CIMK and DAC121S101QCMK
NS Package Number MK06A
19
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DAC121S101/DAC121S101Q 12-Bit Micro Power, RRO Digital-to-Analog Converter
Notes
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