LTC2452 Ultra-Tiny, Differential, 16-Bit ΔΣ ADC with SPI Interface DESCRIPTION FEATURES n n n n n n n n n n n n ±VCC Differential Input Range 16-Bit Resolution (Including Sign), No Missing Codes 2LSB Offset Error 4LSB Full-Scale Error 60 Conversions Per Second Single Conversion Settling Time for Multiplexed Applications Single-Cycle Operation with Auto Shutdown 800µA Supply Current 0.2µA Sleep Current Internal Oscillator—No External Components Required SPI Interface Ultra-Tiny 3mm × 2mm DFN and TSOT-23 Packages APPLICATIONS n n n n n n n System Monitoring Environmental Monitoring Direct Temperature Measurements Instrumentation Industrial Process Control Data Acquisition Embedded ADC Upgrades L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks and No Latency ∆Σ is a trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. Protected by U.S. Patents, including 6208279, 6411242, 7088280, 7164378. The LTC®2452 is an ultra-tiny, fully differential, 16-bit, analog-to-digital converter. The LTC2452 uses a single 2.7V to 5.5V supply and communicates through an SPI interface. The ADC is available in an 8-pin, 3mm × 2mm DFN package or TSOT-23 package. It includes an integrated oscillator that does not require any external components. It uses a delta-sigma modulator as a converter core and has no latency for multiplexed applications. The LTC2452 includes a proprietary input sampling scheme that reduces the average input sampling current several orders of magnitude when compared to conventional delta-sigma converters. Additionally, due to its architecture, there is negligible current leakage between the input pins. The LTC2452 can sample at 60 conversions per second, and due to the very large oversampling ratio, has extremely relaxed antialiasing requirements. The LTC2452 includes continuous internal offset and full-scale calibration algorithms which are transparent to the user, ensuring accuracy over time and over the operating temperature range. The converter has an external REF pin and the differential input voltage range can extend up to ±VREF . Following a single conversion, the LTC2452 can automatically enter a sleep mode and reduce its supply current to less than 0.2µA. If the user reads the ADC once a second, the LTC2452 consumes an average of less than 50µW from a 2.7V supply. TYPICAL APPLICATION Integral Nonlinearity, VCC = 3V 3 2.7V TO 5.5V 0.1µF 10k IN+ 10k IN– 10k R 0.1µF REF VCC 1 CS LTC2452 SCK SDO 3-WIRE SPI INTERFACE INL (LSB) 0.1µF 2 10µF TA = –45°C, 25°C, 90°C 0 –1 GND –2 2452 TA01a –3 –3 1 2 –2 –1 0 DIFFERENTIAL INPUT VOLTAGE (V) 3 2452 TA01b 2452fc 1 LTC2452 ABSOLUTE MAXIMUM RATINGS (Notes 1, 2) Supply Voltage (VCC).................................... –0.3V to 6V Analog Input Voltage (VIN+, VIN–)... –0.3V to (VCC + 0.3V) Reference Voltage (VREF)............... –0.3V to (VCC + 0.3V) Digital Voltage (VSDO, VSCK, VCS)... –0.3V to (VCC + 0.3V) Storage Temperature Range.................... –65°C to 150°C Operating Temperature Range LTC2452C................................................. 0°C to 70°C LTC2452I.............................................. –40°C to 85°C PIN CONFIGURATION TOP VIEW SCK 1 GND 2 REF 3 VCC 4 9 8 SDO 7 CS 6 IN + 5 IN– TOP VIEW SCK 1 GND 2 REF 3 VCC 4 DD8 PACKAGE 8-LEAD (3mm × 2mm) PLASTIC DFN C/I GRADE TJMAX = 125°C, θJA = 76°C/W EXPOSED PAD (PIN 9) IS GND, MUST BE SOLDERED TO PCB 8 SDO 7 CS 6 IN+ 5 IN– TS8 PACKAGE 8-LEAD PLASTIC TSOT-23 C/I GRADE TJMAX = 125°C, θJA = 140°C/W ORDER INFORMATION Lead Free Finish TAPE AND REEL (MINI) TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LTC2452CDDB#TRMPBF LTC2452CDDB#TRPBF LDNJ 8-Lead Plastic (3mm × 2mm) DFN LTC2452IDDB#TRMPBF LTC2452IDDB#TRPBF LDNJ 8-Lead Plastic (3mm × 2mm) DFN LTC2452CTS8#TRMPBF LTC2452CTS8#TRPBF LTDPK 8-Lead Plastic TSOT-23 LTC2452ITS8#TRMPBF LTC2452ITS8#TRPBF LTDPK 8-Lead Plastic TSOT-23 TRM = 500 pieces. *Temperature grades are identified by a label on the shipping container. Consult LTC Marketing for parts specified with wider operating temperature ranges. Consult LTC Marketing for information on lead based finish parts. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ 0°C to 70°C –40°C to 85°C 0°C to 70°C –40°C to 85°C ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. (Note 2) PARAMETER CONDITIONS MIN TYP MAX 16 UNITS Bits Resolution (No Missing Codes) (Note 3) l Integral Nonlinearity (Note 4) l 1 10 LSB l 2 10 LSB Offset Error Offset Error Drift Gain Error 0.02 l 0.01 LSB/°C 0.02 % of FS Gain Error Drift 0.02 LSB/°C Transition Noise 2.2 µVRMS Power Supply Rejection DC 80 dB 2452fc 2 LTC2452 ANALOG INPUTS AND REFERENCES The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS 0 VCC V l 0 VCC V l 2.5 + Positive Input Voltage Range l VIN – Negative Input Voltage Range VREF Reference Voltage Range VOR+ + VUR+ Overrange + Underrange Voltage, IN+ VREF = 5V, VIN– = 2.5V (See Figure 3) 31 LSB VOR– + VUR– Overrange + Underrange Voltage, IN– VREF = 5V, VIN+ = 2.5V (See Figure 3) 31 LSB CIN IN+, IN– Sampling Capacitance IDC_LEAK(IN+) IN+ DC Leakage Current VIN = GND (Note 10) VIN = VCC (Note 10) l l –10 –10 1 1 10 10 nA nA IDC_LEAK(IN–) IN– DC Leakage Current VIN = GND (Note 10) VIN = VCC (Note 10) l l –10 –10 1 1 10 10 nA nA IDC_LEAK(REF) REF DC Leakage Current VREF = 3V (Note 10) l –10 1 10 nA ICONV Input Sampling Current (Note 5) VIN VCC V 0.35 pF 50 nA POWER REQUIREMENTS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. SYMBOL PARAMETER VCC Supply Voltage ICC Supply Current Conversion Sleep CONDITIONS MIN l CS = GND (Note 6) CS = VCC (Note 6) TYP 2.7 800 0.2 l l MAX UNITS 5.5 V 1200 0.6 µA µA DIGITAL INPUTS AND DIGITAL OUTPUTS The l denotes the specifications which apply over the full operating temperature range,otherwise specifications are at TA = 25°C. (Note 2) SYMBOL PARAMETER CONDITIONS MIN VIH High Level Input Voltage l VIL Low Level Input Voltage l IIN Digital Input Current l –10 VCC – 0.5 CIN Digital Input Capacitance VOH High Level Output Voltage IO = –800µA l VOL Low Level Output Voltage IO = 1.6mA l IOZ Hi-Z Output Leakage Current TYP MAX VCC – 0.3 V 0.3 V 10 µA 10 l –10 UNITS pF V 0.4 V 10 µA 2452fc 3 LTC2452 TIMING CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range,otherwise specifications are at TA = 25°C. SYMBOL PARAMETER tCONV Conversion Time CONDITIONS l fSCK SCK Frequency Range l tlSCK SCK Low Period l 250 ns thSCK SCK High Period l 250 ns t1 CS Falling Edge to SDO Low Z (Notes 7, 8) l 0 100 ns t2 CS Rising Edge to SDO High Z (Notes 7, 8) l 0 100 ns t3 CS Falling Edge to SCK Falling Edge l 100 tKQ SCK Falling Edge to SDO Valid l 0 (Note 7) Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2. All voltage values are with respect to GND. VCC = 2.7V to 5.5V unless otherwise specified. VREFCM = VREF/2, FS = VREF VIN = VIN+ – VIN–, –VREF ≤ VIN ≤ VREF; VINCM = (VIN+ + VIN–)/2. Note 3. Guaranteed by design, not subject to test. Note 4. Integral nonlinearity is defined as the deviation of a code from a straight line passing through the actual endpoints of the transfer curve. Guaranteed by design and test correlation. Integral Nonlinearity, VCC = 5V 3 2 2 TA = 90°C Integral Nonlinearity, VCC = 3V TA = –45°C, 25°C 0 –2 –2 2452 G01 MHz ns 100 ns –3 1 2 –2 –1 0 DIFFERENTIAL INPUT VOLTAGE (V) 3 2452 G02 VCC = VREF = 5V, 4.1V, 3V 0 –2 –3 2 1 TA = –45°C, 25°C, 90°C –1 5 ms 2 –1 –5 –4 –3 –2 –1 0 1 2 3 4 DIFFERENTIAL INPUT VOLTAGE (V) UNITS Maximum INL vs Temperature –1 –3 23 3 INL (LSB) 0 MAX 16.6 (TA = 25°C, unless otherwise noted) 1 INL (LSB) INL (LSB) 1 TYP 13 Note 5: CS = VCC. A positive current is flowing into the DUT pin. Note 6: SCK = VCC or GND. SDO is high impedance. Note 7: See Figure 4. Note 8: See Figure 5. Note 9: Input sampling current is the average input current drawn from the input sampling network while the LTC2452 is actively sampling the input. Note 10: A positive current is flowing into the DUT pin. TYPICAL PERFORMANCE CHARACTERISTICS 3 MIN –3 –50 –25 25 50 0 TEMPERATURE (°C) 75 100 2452 G03 2452fc 4 LTC2452 TYPICAL PERFORMANCE CHARACTERISTICS Gain Error vs Temperature 5 4 4 3 3 2 2 1 VCC = VREF = 5V 0 –1 –2 VCC = VREF = 3V –3 VCC = VREF = 4.1V Transition Noise vs Temperature 10 9 VCC = VREF = 3V TRANSITION NOISE RMS (µV) 5 GAIN ERROR (LSB) OFFSET ERROR (LSB) Offset Error vs Temperature (TA = 25°C, unless otherwise noted) VCC = VREF = 4.1V 1 0 VCC = VREF = 5V –1 –2 –3 –4 –4 –5 –50 –25 25 50 0 TEMPERATURE (°C) 75 –25 25 50 0 TEMPERATURE (°C) 75 2452 G04 VCC = 4.1V 100 50 75 VCC = 3V 100 0 –50 –25 25 50 0 TEMPERATURE (°C) 2452 G07 25 50 0 TEMPERATURE (°C) 75 100 75 100 25Hz OUTPUT SAMPLE RATE 10Hz OUTPUT SAMPLE RATE 100 1Hz OUTPUT SAMPLE RATE 10 0 –50 –25 25 50 0 TEMPERATURE (°C) 75 100 2452 G09 2452 G08 Power Supply Rejection vs Frequency at VCC Conversion Time vs Temperature 21 0 20 CONVERSION TIME (ms) –20 –40 –60 –80 –100 –120 –25 2452 G06 AVERAGE POWER DISSIPATION (µW) SLEEP CURRENT (nA) 150 100 25 50 0 TEMPERATURE (°C) VCC = 3V 1000 VCC = 5V 200 REJECTION (dB) CONVERSION CURRENT (µA) VCC = 4.1V 300 –25 2 10000 200 VCC = 5V 400 0 –50 3 Average Power Dissipation vs Temperature, VCC = 3V 250 VCC = 3V VCC = 5V 4 0 –50 100 800 500 5 Sleep Mode Power Supply Current vs Temperature 900 600 6 2452 G05 Conversion Mode Power Supply Current vs Temperature 700 7 1 –5 –50 100 8 19 VCC = 5V, 4.1V, 3V 18 17 16 15 1 10 100 1k 10k 100k FREQUENCY AT VCC (Hz) 1M 10M 2452 G10 14 –50 –25 25 50 0 TEMPERATURE (°C) 75 100 2452 G11 2452fc 5 LTC2452 PIN FUNCTIONS SCK (Pin 1): Serial Clock Input. SCK synchronizes the serial data output. While digital data is available (the ADC is not in CONVERT state) and CS is LOW (ADC is not in SLEEP state) a new data bit is produced at the SDO output pin following every falling edge applied to the SCK pin. GND (Pin 2): Ground. Connect to a ground plane through a low impedance connection. REF (Pin 3): Reference Input. The voltage on REF can have any value between 2.5V and VCC. The reference voltage sets the full-scale range. VCC (Pin 4): Positive Supply Voltage. Bypass to GND (Pin 2) with a 10µF capacitor in parallel with a low-series-inductance 0.1µF capacitor located as close to the LTC2452 as possible. IN– (Pin 5), IN+ (Pin 6): Differential Analog Input. CS (Pin 7): Chip Select (Active LOW) Digital Input. A LOW on this pin enables the SDO digital output. A HIGH on this pin places the SDO output pin in a high impedance state. SDO (Pin 8): Three-State Serial Data Output. SDO is used for serial data output during the DATA OUTPUT state and can be used to monitor the conversion status. Exposed Pad (Pin 9): Ground. Must be soldered to PCB ground. For prototyping purposes, this pad may remain floating. BLOCK DIAGRAM 3 4 REF VCC CS 6 IN + SPI INTERFACE 16-BIT ΔΣ A/D CONVERTER – 5 IN– 16-BIT ΔΣ A/D CONVERTER 2, 9 SDO SCK 7 8 1 DECIMATING SINC FILTER INTERNAL OSCILLATOR GND 2452 BD Figure 1. Functional Block Diagram APPLICATIONS INFORMATION CONVERTER OPERATION Converter Operation Cycle The LTC2452 is a low power, fully differential, delta-sigma analog-to-digital converter with a simple 3-wire SPI interface (see Figure 1). Its operation is composed of three successive states: CONVERT, SLEEP and DATA OUTPUT. The operating cycle begins with the CONVERT state, is followed by the SLEEP state, and ends with the DATA OUTPUT state (see Figure 2). The 3-wire interface consists of serial data output (SDO), serial clock input (SCK), and the active low chip select input (CS). The CONVERT state duration is determined by the LTC2452 conversion time (nominally 16.6 milliseconds). Once 2452fc 6 LTC2452 APPLICATIONS INFORMATION corresponds to the last completed conversion. A new bit of data appears at the SDO pin following each falling edge detected at the SCK input pin and appears from MSB to LSB. The user can reliably latch this data on every rising edge of the external serial clock signal driving the SCK pin (see Figure 3). POWER-ON RESET CONVERT SLEEP NO The DATA OUTPUT state concludes in one of two different ways. First, the DATA OUTPUT state operation is completed once all 16 data bits have been shifted out and the clock then goes low. This corresponds to the 16th falling edge of SCK. Second, the DATA OUTPUT state can be aborted at any time by a LOW-to-HIGH transition on the CS input. Following either one of these two actions, the LTC2452 will enter the CONVERT state and initiate a new conversion cycle. SCK = LOW AND CS = LOW? YES DATA OUTPUT NO 16TH FALLING EDGE OF SCK OR CS = HIGH? YES 2452 F02 Figure 2. LTC2452 State Transition Diagram started, this operation can not be aborted except by a low power supply condition (VCC < 2.1V) which generates an internal power-on reset signal. After the completion of a conversion, the LTC2452 enters the SLEEP state and remains there until both the chip select and serial clock inputs are low (CS = SCK = LOW). Following this condition, the ADC transitions into the DATA OUTPUT state. While in the SLEEP state, whenever the chip select input is pulled high (CS = HIGH), the LTC2452’s power supply current is reduced to less than 200nA. When the chip select input is pulled low (CS = LOW), and SCK is maintained at a HIGH logic level, the LTC2452 will return to a normal power consumption level. During the SLEEP state, the result of the last conversion is held indefinitely in a static register. Upon entering the DATA OUTPUT state, SDO outputs the sign (D15) of the conversion result. During this state, the ADC shifts the conversion result serially through the SDO output pin under the control of the SCK input pin. There is no latency in generating this data and the result Power-Up Sequence When the power supply voltage (VCC) applied to the converter is below approximately 2.1V, the ADC performs a power-on reset. This feature guarantees the integrity of the conversion result. When VCC rises above this critical threshold, the converter generates an internal power-on reset (POR) signal for approximately 0.5ms. The POR signal clears all internal registers. Following the POR signal, the LTC2452 starts a conversion cycle and follows the succession of states shown in Figure 2. The first conversion result following POR is accurate within the specifications of the device if the power supply voltage VCC is restored within the operating range (2.7V to 5.5V) before the end of the POR time interval. Ease of Use The LTC2452 data output has no latency, filter settling delay or redundant results associated with the conversion cycle. There is a one-to-one correspondence between the conversion and the output data. Therefore, multiplexing multiple analog input voltages requires no special actions. The LTC2452 performs offset calibrations every conversion. This calibration is transparent to the user and has no effect upon the cyclic operation described previously. The advantage of continuous calibration is stability of the ADC performance with respect to time and temperature. 2452fc 7 LTC2452 APPLICATIONS INFORMATION The LTC2452 includes a proprietary input sampling scheme that reduces the average input current by several orders of magnitude when compared to traditional delta-sigma architectures. This allows external filter networks to interface directly to the LTC2452. Since the average input sampling current is 50nA, an external RC lowpass filter using 1kΩ and 0.1µF results in <1LSB additional error. Additionally, there is negligible leakage current between IN+ and IN–. 20 16 12 OUTPUT CODE 8 4 0 –4 SIGNALS BELOW GND –8 –12 –16 –20 –0.001 –0.005 Reference Voltage Range 0.005 0 VIN+/VREF+ 0.001 0.0015 2452 F03 The LTC2453 reference input range is 2.5V to VCC. For the simplest operation, REF can be shorted to VCC. Input Voltage Range As mentioned in the Output Data Format section, the output code is given as 32768•VIN/VREF + 32768. For VIN ≥ VREF, the output code is clamped at 65535 (all ones). For VIN ≤ –VREF, the output code is clamped at 0 (all zeroes). The LTC2452 includes a proprietary system that can, typically, digitize each input 8LSB above VREF and below GND, if the differential input is within ±VREF. As an example (Figure 3), if the user desires to measure a signal slightly below ground, the user could set VIN– = GND, and VREF = 5V. If VIN+ = GND, the output code would be approximately 32768. If VIN+ = GND – 8LSB = –1.22 mV, the output code would be approximately 32760. Figure 3. Output Code vs VIN+ with VIN– = 0 The total amount of overrange and underrange capability is typically 31LSB for a given device. The 31LSB total is distributed between the overrange and underrange capability. For example, if the underrange capability is 8LSB, the overrange capability is typically 31 – 8 = 23LSB. Output Data Format The LTC2452 generates a 16-bit direct binary encoded result. It is provided as a 16-bit serial stream through the SDO output pin under the control of the SCK input pin (see Figure 4). Letting VIN = (VIN+ – VIN–), the output code is given as 32768•VIN/VREF + 32768. The first bit output by the LTC2452, D15, is the MSB, which is 1 for VIN+ ≥ VIN– and 0 for VIN+ < VIN–. This bit is followed by successively less significant bits (D14, D13...) until the LSB is output by the LTC2452. Table 1 shows some example output codes. Table 1. LTC2452 Output Data Format DIFFERENTIAL INPUT VOLTAGE VIN+ – VIN– ≥VREF D15 (MSB) D14 D13 D12...D2 D1 1 1 1 1 1 D0 CORRESPONDING (LSB) DECIMAL VALUE 1 65535 VREF – 1LSB 1 1 1 1 1 0 65534 0.5•VREF 1 1 0 0 0 0 49152 0.5•VREF – 1LSB 1 0 1 1 1 1 49151 0 1 0 0 0 0 0 32768 –1LSB 0 1 1 1 1 1 32767 –0.5•VREF 0 1 0 0 0 0 16384 –0.5•VREF – 1LSB 0 0 1 1 1 1 16383 ≤ –VREF 0 0 0 0 0 0 0 2452fc 8 LTC2452 APPLICATIONS INFORMATION t1 t3 t2 CS D14 D15 SDO D13 D12 D11 D10 D9 D8 D7 D6 D5 D4 MSB D3 D2 D1 D0 LSB SCK 2452 F04 tKQ tlSCK thSCK Figure 4. Data Output Timing t2 t1 CS SDO SCK = HIGH CONVERT SLEEP 2452 F05 Figure 5. Conversion Status Monitoring Mode During the data output operation the CS input pin must be pulled low (CS = LOW). The data output process starts with the most significant bit of the result being present at the SDO output pin (SDO = D15) once CS goes low. A new data bit appears at the SDO output pin after each falling edge detected at the SCK input pin. The output data can be reliably latched by the user using the rising edge of SCK. indication of a completed conversion cycle. An example of such a sequence is shown in Figure 5. Conversion status monitoring, while possible, is not required for LTC2452 as its conversion time is fixed and equal at approximately 16.6ms (23ms maximum). Therefore, external timing can be used to determine the completion of a conversion cycle. Conversion Status Monitor SERIAL INTERFACE For certain applications, the user may wish to monitor the LTC2452 conversion status. This can be achieved by holding SCK HIGH during the conversion cycle. In this condition, whenever the CS input pin is pulled low (CS = LOW), the SDO output pin will provide an indication of the conversion status. SDO = HIGH is an indication of a conversion cycle in progress while SDO = LOW is an The LTC2452 transmits the conversion result and receives the start of conversion command through a synchronous 3-wire interface. This interface can be used during the CONVERT and SLEEP states to assess the conversion status and during the DATA OUTPUT state to read the conversion result, and to trigger a new conversion. 2452fc 9 LTC2452 APPLICATIONS INFORMATION Serial Interface Operation Modes Serial Clock Idle-High (CPOL = 1) Examples The modes of operation can be summarized as follows: In Figure 6, following a conversion cycle the LTC2452 automatically enters the low power sleep mode. The user can monitor the conversion status at convenient intervals using CS and SDO. 1) The LTC2452 functions with SCK idle high (commonly known as CPOL = 1) or idle low (commonly known as CPOL = 0). Pulling CS LOW while SCK is HIGH tests whether or not the chip is in the CONVERT state. While in the CONVERT state, SDO is HIGH while CS is LOW. In the SLEEP state, SDO is LOW while CS is LOW. These tests are not required operational steps but may be useful for some applications. 2) After the 16th bit is read, the user can choose one of two ways to begin a new conversion. First, one can pull CS high (CS = ↑). Second, one can use a high-low transition on SCK (SCK = ↓). 3) At any time during the Data Output state, pulling CS high (CS = ↑) causes the part to leave the I/O state, abort the output and begin a new conversion. When the data is available, the user applies 16 clock cycles to transfer the result. The CS rising edge is then used to initiate a new conversion. 4) When SCK = HIGH, it is possible to monitor the conversion status by pulling CS low and watching for SDO to go low. This feature is available only in the idle-high (CPOL = 1) mode. The operation example of Figure 7 is identical to that of Figure 6, except the new conversion cycle is triggered by the falling edge of the serial clock (SCK). A 17th clock pulse is used to trigger a new conversion cycle. CS SD0 D15 D14 D13 D12 D2 D1 D0 SCK clk1 CONVERT clk2 clk3 SLEEP clk4 clk15 clk16 DATA OUTPUT CONVERT 2452 F06 Figure 6. Idle-High (CPOL = 1) Serial Clock Operation Example. The Rising Edge of CS Starts a New Conversion CS SD0 D15 D14 D13 D12 D2 D1 D0 SCK clk1 CONVERT SLEEP clk2 clk3 clk4 clk15 clk16 DATA OUTPUT clk17 CONVERT 2452 F07 Figure 7. Idle-High (CPOL = 1) Clock Operation Example. A 17th Clock Pulse is Used to Trigger a New Conversion Cycle 2452fc 10 LTC2452 APPLICATIONS INFORMATION CS SD0 D15 D14 D13 clk1 clk2 clk3 D12 D2 D1 D0 clk15 clk16 SCK CONVERT SLEEP clk4 clk14 DATA OUTPUT CONVERT 2452 F08 Figure 8. Idle-Low (CPOL = 0) Clock. CS Triggers a New Conversion CS SD0 D15 D14 clk1 clk2 D13 D12 D2 D1 clk14 clk15 D0 SCK CONVERT SLEEP clk3 clk4 DATA OUTPUT clk16 CONVERT 2452 F09 Figure 9. Idle-Low (CPOL = 0) Clock. The 16th SCK Falling Edge Triggers a New Conversion Serial Clock Idle-Low (CPOL = 0) Examples Examples of Aborting Cycle using CS In Figure 8, following a conversion cycle the LTC2452 automatically enters the low-power sleep state. The user determines data availability (and the end of conversion) based upon external timing. The user then pulls CS low (CS = ↓) and uses 16 clock cycles to transfer the result. Following the 16th rising edge of the clock, CS is pulled high (CS = ↑), which triggers a new conversion. For some applications, the user may wish to abort the I/O cycle and begin a new conversion. If the LTC2452 is in the data output state, a CS rising edge clears the remaining data bits from the output registers, aborts the output cycle and triggers a new conversion. Figure 10 shows an example of aborting an I/O with idle-high (CPOL = 1) and Figure 11 shows an example of aborting an I/O with idle-low (CPOL = 0). The timing diagram in Figure 9 is identical to that of Figure 8, except in this case a new conversion is triggered by SCK. The 16th SCK falling edge triggers a new conversion cycle and the CS signal is subsequently pulled high. A new conversion cycle can be triggered using the CS signal without having to generate any serial clock pulses as shown in Figure 12. If SCK is maintained at a low logic level, after the end of a conversion cycle, a new conver2452fc 11 LTC2452 APPLICATIONS INFORMATION CS SD0 D15 D14 D13 SCK clk1 CONVERT SLEEP clk2 clk3 clk4 DATA OUTPUT CONVERT 2452 F10 Figure 10. Idle-High (CPOL = 1) Clock and Aborted I/O Example CS SD0 D15 D14 clk1 clk2 D13 SCK CONVERT SLEEP DATA OUTPUT clk3 CONVERT 2452 F11 Figure 11. Idle-Low (CPOL = 0) Clock and Aborted I/O Example CS SD0 D15 SCK = LOW CONVERT SLEEP DATA OUTPUT CONVERT 2452 F12 Figure 12. Idle-Low (CPOL = 0) Clock and Minimum Data Output Length Example 2452fc 12 LTC2452 APPLICATIONS INFORMATION Figure 13 shows a 2-wire operation sequence which uses an idle-high (CPOL = 1) serial clock signal. The conversion status can be monitored at the SDO output. Following a conversion cycle, the ADC enters SLEEP state and the SDO output transitions from HIGH to LOW. Subsequently 16 clock pulses are applied to the SCK input in order to serially shift the 16 bit result. Finally, the 17th clock pulse is applied to the SCK input in order to trigger a new conversion cycle. sion operation can be triggered by pulling CS low and then high. When CS is pulled low (CS = LOW), SDO will output the sign (D15) of the result of the just completed conversion. While a low logic level is maintained at SCK pin and CS is subsequently pulled high (CS = HIGH) the remaining 15 bits of the result (D14:D0) are discarded and a new conversion cycle starts. Following the aborted I/O, additional clock pulses in the CONVERT state are acceptable, but excessive signal transitions on SCK can potentially create noise on the ADC during the conversion, and thus may negatively influence the conversion accuracy. Figure 14 shows a 2-wire operation sequence which uses an idle-low (CPOL = 0) serial clock signal. The conversion status cannot be monitored at the SDO output. Following a conversion cycle, the LTC2452 bypasses the SLEEP state and immediately enters the DATA OUTPUT state. At this moment the SDO pin outputs the sign (D15) of the conversion result. The user must use external timing in order to determine the end of conversion and result availability. Subsequently 16 clock pulses are applied to SCK in order to serially shift the 16-bit result. The 16th clock falling edge triggers a new conversion cycle. 2-Wire Operation The 2-wire operation modes, while reducing the number of required control signals, should be used only if the LTC2452 low power sleep capability is not required. In addition the option to abort serial data transfers is no longer available. Hardwire CS to GND for 2-wire operation. CS = LOW D15 SD0 D14 D13 D12 D2 D1 D0 SCK clk1 CONVERT clk2 clk3 SLEEP clk4 clk15 clk16 clk17 DATA OUTPUT CONVERT 2452 F13 Figure 13. 2-Wire, Idle-High (CPOL = 1) Serial Clock, Operation Example CS = LOW SD0 D15 D14 D13 D12 D2 D1 D0 clk1 clk2 clk3 clk4 clk14 clk15 clk16 SCK CONVERT DATA OUTPUT CONVERT 2452 F14 Figure 14. 2-Wire, Idle-Low (CPOL = 0) Serial Clock Operation Example 2452fc 13 LTC2452 APPLICATIONS INFORMATION PRESERVING THE CONVERTER ACCURACY The LTC2452 is designed to minimize the conversion result’s sensitivity to device decoupling, PCB layout, antialiasing circuits, line and frequency perturbations. Nevertheless, in order to preserve the high accuracy capability of this part, some simple precautions are desirable. Digital Signal Levels Due to the nature of CMOS logic, it is advisable to keep input digital signals near GND or VCC. Voltages in the range of 0.5V to VCC – 0.5V may result in additional current leakage from the part. Undershoot and overshoot should also be minimized, particularly while the chip is converting. It is thus beneficial to keep edge rates of about 10ns and limit overshoot and undershoot to less than 0.3V. Noisy external circuitry can potentially impact the output under 2-wire operation. In particular, it is possible to get the LTC2452 into an unknown state if an SCK pulse is missed or noise triggers an extra SCK pulse. In this situation, it is impossible to distinguish SDO = 1 (indicating conversion in progress) from valid “1” data bits. As such, CPOL = 1 is recommended for the 2-wire mode. The user should look for SDO = 0 before reading data, and look for SDO = 1 after reading data. If SDO does not return a “0” within the maximum conversion time (or return a “1” after a full data read), generate 16 SCK pulses to force a new conversion. Driving VCC and GND In relation to the VCC and GND pins, the LTC2452 combines internal high frequency decoupling with damping elements, which reduce the ADC performance sensitivity to PCB layout and external components. Nevertheless, the very high accuracy of this converter is best preserved by careful low and high frequency power supply decoupling. A 0.1µF, high quality, ceramic capacitor in parallel with a 10µF ceramic capacitor should be connected between the VCC and GND pins, as close as possible to the package. The 0.1µF capacitor should be placed closest to the ADC package. It is also desirable to avoid any via in the circuit path, starting from the converter VCC pin, passing through these two decoupling capacitors, and returning to the converter GND pin. The area encompassed by this circuit path, as well as the path length, should be minimized. Furthermore, as shown in Figure 15, GND is used as the negative reference voltage. It is thus important to keep the GND line quiet and connect GND through a low-impedance trace. Very low impedance ground and power planes, and star connections at both VCC and GND pins, are preferable. The VCC pin should have two distinct connections: the first to the decoupling capacitors described above, and the second to the ground return for the power supply voltage source. Driving REF A simplified equivalent circuit for REF is shown in Figure 15. Like all other A/D converters, the LTC2452 is only as accurate as the reference it is using. Therefore, it is important to keep the reference line quiet by careful low and high frequency decoupling. VCC ILEAK RSW 15k (TYP) REF ILEAK VCC ILEAK IN+ RSW 15k (TYP) ILEAK VCC ILEAK IN– CEQ 0.35pF (TYP) RSW 15k (TYP) ILEAK VCC ILEAK GND RSW 15k (TYP) 2452 F15 ILEAK Figure 15. LTC2452 Analog Input/Reference Equivalent Circuit 2452fc 14 LTC2452 APPLICATIONS INFORMATION The LT6660 reference is an ideal match for driving the LTC2452’s REF pin. The LTC6660 is available in a 2mm × 2mm DFN package with 2.5V, 3V, 3.3V and 5V options. There are some immediate trade-offs in RS and CIN without needing a full circuit analysis. Increasing RS and CIN can give the following benefits: A 0.1µF, high quality, ceramic capacitor in parallel with a 10µF ceramic capacitor should be connected between the REF and GND pins, as close as possible to the package. The 0.1µF capacitor should be placed closest to the ADC. 1) Due to the LTC2452’s input sampling algorithm, the input current drawn by either VIN+ or VIN– over a conversion cycle is typically 50nA. A high RS • CIN attenuates the high frequency components of the input current, and RS values up to 1k result in <1LSB error. Driving VIN+ and VIN– The input drive requirements can best be analyzed using the equivalent circuit of Figure 16. The input signal VSIG is connected to the ADC input pins (IN+ and IN–) through an equivalent source resistance RS. This resistor includes both the actual generator source resistance and any additional optional resistors connected to the input pins. Optional input capacitors CIN are also connected to the ADC input pins. This capacitor is placed in parallel with the ADC input parasitic capacitance CPAR. Depending on the PCB layout, CPAR has typical values between 2pF and 15pF. In addition, the equivalent circuit of Figure 16 includes the converter equivalent internal resistor RSW and sampling capacitor CEQ. VCC ILEAK RS SIG+ + – IN+ ILEAK CIN CEQ 0.35pF (TYP) CPAR VCC ILEAK RS SIG– + – IN– ILEAK CIN CPAR RSW 15k (TYP) ICONV RSW 15k (TYP) CEQ 0.35pF (TYP) ICONV 2452 F16 Figure 16. LTC2452 Input Drive Equivalent Circuit 2) The bandwidth from VSIG is reduced at the input pins (IN+, IN–). This bandwidth reduction isolates the ADC from high frequency signals, and as such provides simple antialiasing and input noise reduction. 3) Switching transients generated by the ADC are attenuated before they go back to the signal source. 4) A large CIN gives a better AC ground at the input pins, helping reduce reflections back to the signal source. 5) Increasing RS protects the ADC by limiting the current during an outside-the-rails fault condition. There is a limit to how large RS • CIN should be for a given application. Increasing RS beyond a given point increases the voltage drop across RS due to the input current, to the point that significant measurement errors exist. Additionally, for some applications, increasing the RS • CIN product too much may unacceptably attenuate the signal at frequencies of interest. For most applications, it is desirable to implement CIN as a high-quality 0.1µF ceramic capacitor and RS ≤ 1k. This capacitor should be located as close as possible to the actual VIN package pin. Furthermore, the area encompassed by this circuit path, as well as the path length, should be minimized. In the case of a 2-wire sensor that is not remotely grounded, it is desirable to split RS and place series resistors in the ADC input line as well as in the sensor ground return line, which should be tied to the ADC GND pin using a star connection topology. 2452fc 15 LTC2452 APPLICATIONS INFORMATION Figure 17 shows the measured LTC2452 INL vs Input Voltage as a function of RS value with an input capacitor CIN = 0.1µF. In some cases, RS can be increased above these guidelines. The input current is zero when the ADC is either in sleep or I/O modes. Thus, if the time constant of the input RC circuit t = RS • CIN, is of the same order of magnitude or longer than the time periods between actual conversions, then one can consider the input current to be reduced correspondingly. These considerations need to be balanced out by the input signal bandwidth. The 3dB bandwidth ≈ 1/(2pRSCIN). 8 6 10 CIN = 0.1µF VCC = 5V TA = 25°C CIN = 0 8 V = 5V CC 6 TA = 25°C RS = 10k INL (LSB) 4 2 0 –2 4 RS = 2k RS = 1k INL (LSB) 10 Finally, if the recommended choice for CIN is unacceptable for the user’s specific application, an alternate strategy is to eliminate CIN and minimize CPAR and RS. In practical terms, this configuration corresponds to a low impedance sensor directly connected to the ADC through minimum length traces. Actual applications include current measurements through low value sense resistors, temperature measurements, low impedance voltage source monitoring, and so on. The resultant INL vs VIN is shown in Figure 18. The measurements of Figure 18 include a capacitor CPAR corresponding to a minimum sized layout pad and a minimum width input trace of about 1 inch length. RS = 0 2 0 –2 –4 –4 –6 –6 –8 –8 –10 –10 –5 –4 –3 –2 –1 0 1 2 3 4 DIFFERENTIAL INPUT VOLTAGE (V) 5 2452 F17 Figure 17. Measured INL vs Input Voltage, CIN = 0.1µF, VCC = 5V, TA = 25°C RS = 10k RS = 0 RS = 1k, 2k –5 –4 –3 –2 –1 0 1 2 3 4 DIFFERENTIAL INPUT VOLTAGE (V) 5 2452 F18 Figure 18. Measured INL vs Input Voltage, CIN = 0, VCC = 5V, TA = 25°C 2452fc 16 LTC2452 APPLICATIONS INFORMATION Signal Bandwidth, Transition Noise and Noise Equivalent Input Bandwidth The LTC2452 includes a sinc1 type digital filter with the first notch located at f0 = 60Hz. As such, the 3dB input signal bandwidth is 26.54Hz. The calculated LTC2452 input signal attenuation vs frequency over a wide frequency range is shown in Figure 19. The calculated LTC2452 input signal attenuation vs frequency at low frequencies is shown in Figure 20. The converter noise level is about 2.2µVRMS and can be modeled by a white noise source connected at the input of a noise-free converter. On a related note, the LTC2452 uses two separate A/D converters to digitize the positive and negative inputs. Each of these A/D converters has 2.2µVRMS transition noise. If one of the input voltages is within this small transition noise band, then the output will fluctuate one bit, regardless of the value of the other input voltage. If both of the input voltages are within their transition noise bands, the output can fluctuate 2 bits. For a simple system noise analysis, the VIN drive circuit can be modeled as a single-pole equivalent circuit characterized by a pole location fi and a noise spectral density ni. If the converter has an unlimited bandwidth, or at least a bandwidth substantially larger than fi, then the total noise contribution of the external drive circuit would be: Vn = ni p / 2 • fi Then, the total system noise level can be estimated as the square root of the sum of (Vn2) and the square of the LTC2452 noise floor (~2.2µV2). 0 INPUT SIGNAL ATTENUATIOIN (dB) INPUT SIGNAL ATTENUATION (dB) 0 –20 –40 –60 –80 –100 0 2.5 5.0 7.5 1.00 1.25 1.50 INPUT SIGNAL FREQUENCY (MHz) 2452 F19 Figure 19. LTC2452 Input Signal Attentuation vs Frequency –5 –10 –15 –20 –25 –30 –35 –40 –45 –50 0 60 120 180 240 300 360 420 480 540 600 INPUT SIGNAL FREQUENCY (Hz) 2452 F20 Figure 20. LTC2452 Input Signal Attenuation vs Frequency (Low Frequencies) 2452fc 17 LTC2452 TYPICAL APPLICATION JP1 VCC VCC U2 3 LT6660HCDC-5 1 IN OUT V+ 1µF GND GND 2 +5V EXT 1 2 3 1µF GND 4 1k REF+ VCC 0.1µF 0.1µF 3 IN+ IN– 1k 1k 0.1µF 0.1µF 6 IN+ 5 IN– 0.1µF CS SCK SDO 4 REF+ VCC LTC2452 REF– GND 2 1µF 9 CS SCK SDO 7 1 8 U1* VCC V+ 1 10V 2 5V TO CONTROLLER 6 CS 4 SCK/SCL 7 MOSI/SDA 5 MISO/SDO GND GND GND 3 8 13 2452 TA02 2452fc 18 LTC2452 PACKAGE DESCRIPTION DDB Package 8-Lead Plastic DFN (3mm × 2mm) (Reference LTC DWG # 05-08-1702 Rev B) 0.61 ±0.05 (2 SIDES) 0.70 ±0.05 2.55 ±0.05 1.15 ±0.05 PACKAGE OUTLINE 0.25 ± 0.05 0.50 BSC 2.20 ±0.05 (2 SIDES) RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS 3.00 ±0.10 (2 SIDES) R = 0.115 TYP 5 R = 0.05 TYP 0.40 ± 0.10 8 2.00 ±0.10 (2 SIDES) PIN 1 BAR TOP MARK (SEE NOTE 6) 0.56 ± 0.05 (2 SIDES) 0.200 REF 0.75 ±0.05 0 – 0.05 4 0.25 ± 0.05 1 PIN 1 R = 0.20 OR 0.25 × 45° CHAMFER (DDB8) DFN 0905 REV B 0.50 BSC 2.15 ±0.05 (2 SIDES) BOTTOM VIEW—EXPOSED PAD NOTE: 1. DRAWING CONFORMS TO VERSION (WECD-1) IN JEDEC PACKAGE OUTLINE M0-229 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 2452fc 19 LTC2452 PACKAGE DESCRIPTION TS8 Package 8-Lead Plastic TSOT-23 (Reference LTC DWG # 05-08-1637 Rev A) 0.40 MAX 2.90 BSC (NOTE 4) 0.65 REF 1.22 REF 1.4 MIN 3.85 MAX 2.62 REF 2.80 BSC 1.50 – 1.75 (NOTE 4) PIN ONE ID RECOMMENDED SOLDER PAD LAYOUT PER IPC CALCULATOR 0.22 – 0.36 8 PLCS (NOTE 3) 0.65 BSC 0.80 – 0.90 0.20 BSC 0.01 – 0.10 1.00 MAX DATUM ‘A’ 0.30 – 0.50 REF 0.09 – 0.20 (NOTE 3) 1.95 BSC TS8 TSOT-23 0710 REV A NOTE: 1. DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLUSIVE OF PLATING 4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 5. MOLD FLASH SHALL NOT EXCEED 0.254mm 6. JEDEC PACKAGE REFERENCE IS MO-193 2452fc 20 LTC2452 REVISION HISTORY (Revision history begins at Rev C) REV DATE DESCRIPTION PAGE NUMBER C 03/10 Updated Analog Inputs and References section 3 Added text to Input Voltage Range section 8 2452fc Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 21 LTC2452 RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LT1236A-5 Precision Bandgap Reference, 5V 0.05% Max, 5ppm/°C Drift LT1461 Micropower Series Reference, 2.5V 0.04% Max, 3ppm/°C Drift LT1790 Micropower Precision Reference in TSOT-23-6 Package 60µA Max Supply Current, 10ppm/°C Max Drift, 1.25V, 2.048V, 2.5V, 3V, 3.3V, 4.096V and 5V Options LTC1860/LTC1861 12-Bit, 5V, 1-/2-Channel 250ksps SAR ADC in MSOP 850µA at 250ksps, 2µA at 1ksps, SO-8 and MSOP Packages LTC1860L/LTC1861L 12-Bit, 3V, 1-/2-Channel 150ksps SAR ADC 450µA at 150ksps, 10µA at 1ksps, SO-8 and MSOP Packages LTC1864/LTC1865 16-Bit, 5V, 1-/2-Channel 250ksps SAR ADC in MSOP 850µA at 250ksps, 2µA at 1ksps, SO-8 and MSOP Packages LTC1864L/LTC1865L 16-bit, 3V, 1-/2-Channel 150ksps SAR ADC 450µA at 150ksps, 10µA at 1ksps, SO-8 and MSOP Packages LTC2440 24-Bit No Latency DS™ ADC 200nVRMS Noise, 4kHz Output Rate, 15ppm INL LTC2480 16-Bit, Differential Input, No Latency DS ADC, with PGA, Temp. Sensor, SPI Easy-Drive Input Current Cancellation, 600nVRMS Noise, Tiny 10-Lead DFN Package LTC2481 16-Bit, Differential Input, No Latency DS ADC, with PGA, Temp. Sensor, I2C Easy-Drive Input Current Cancellation, 600nVRMS Noise, Tiny 10-Lead DFN Package LTC2482 16-Bit, Differential Input, No Latency DS ADC, SPI Easy-Drive Input Current Cancellation, 600nVRMS Noise, Tiny 10-Lead DFN Package LTC2483 16-Bit, Differential Input, No Latency DS ADC, I2C Easy-Drive Input Current Cancellation, 600nVRMS Noise, Tiny 10-Lead DFN Package LTC2484 24-Bit, Differential Input, No Latency DS ADC, SPI with Temp. Sensor Easy-Drive Input Current Cancellation, 600nVRMS Noise, Tiny 10-Lead DFN Package LTC2485 24-Bit, Differential Input, No Latency DS ADC, I2C with Temp. Sensor Easy-Drive Input Current Cancellation, 600nVRMS Noise, Tiny 10-Lead DFN Package LTC6241 Dual, 18MHz, Low Noise, Rail-to-Rail Op Amp 550nVP-P Noise, 125µV Offset Max LT6660 Micropower References in 2mm × 2mm DFN Package, 2.5V, 3V, 3.3V, 5V 20ppm/°C max drift, 0.2% Max LTC2450 Easy-to-Use, Ultra-Tiny 16-Bit ADC, SPI 2 LSB INL, 50nA Sleep current, Tiny 2mm × 2mm DFN-6 Package, 30Hz Output Rate LTC2450-1 Easy-to-Use, Ultra-Tiny 16-Bit ADC, SPI 2 LSB INL, 50nA Sleep Current, Tiny 2mm × 2mm DFN-6 Package, 60Hz Output Rate LTC2451 Easy-to-Use, Ultra-Tiny 16-Bit ADC, I2C 2 LSB INL, 50nA Sleep Current, Tiny 3mm × 2mm DFN-8 or TSOT Package, Programmable 30Hz/60Hz Output Rates LTC2453 Easy-to-Use, Ultra-Tiny 16-Bit Differential ADC, I2C 2 LSB INL, 50nA Sleep Current, Tiny 3mm × 2mm DFN-8 or TSOT Package 2452fc 22 Linear Technology Corporation LT 0311 REV C • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 l FAX: (408) 434-0507 l www.linear.com LINEAR TECHNOLOGY CORPORATION 2008