LT3480 36V, 2A, 2.4MHz Step-Down Switching Regulator with 70µA Quiescent Current DESCRIPTION FEATURES n n n n n n n n n n n n n Wide Input Range: Operation from 3.6V to 36V Over-Voltage Lockout Protects Circuits through 60V Transients 2A Maximum Output Current Low Ripple Burst Mode® Operation 70μA IQ at 12VIN to 3.3VOUT Output Ripple < 15mV Adjustable Switching Frequency: 200kHz to 2.4MHz Low Shutdown Current: IQ < 1μA Integrated Boost Diode Synchronizable Between 250kHz to 2MHz Power Good Flag Saturating Switch Design: 0.25 On-Resistance 0.790V Feedback Reference Voltage Output Voltage: 0.79V to 20V Soft-Start Capability Small 10-Pin Thermally Enhanced MSOP and (3mm × 3mm) DFN Packages The LT®3480 is an adjustable frequency (200kHz to 2.4MHz) monolithic buck switching regulator that accepts input voltages up to 36V (60V maximum). A high efficiency 0.25 switch is included on the die along with a boost Schottky diode and the necessary oscillator, control, and logic circuitry. Current mode topology is used for fast transient response and good loop stability. Low ripple Burst Mode operation maintains high efficiency at low output currents while keeping output ripple below 15mV in a typical application. In addition, the LT3480 can further enhance low output current efficiency by drawing bias current from the output when VOUT is above 3V. Shutdown reduces input supply current to less than 1μA while a resistor and capacitor on the RUN/SS pin provide a controlled output voltage ramp (soft-start). A power good flag signals when VOUT reaches 86% of the programmed output voltage. The LT3480 is available in 10-Pin MSOP and 3mm × 3mm DFN packages with exposed pads for low thermal resistance. APPLICATIONS n n n n , LT, LTC and LTM are registered trademarks of Linear Technology Corporation. Burst Mode is a registered trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. Automotive Battery Regulation Power for Portable Products Distributed Supply Regulation Industrial Supplies TYPICAL APPLICATION 3.3V Step-Down Converter VIN OFF ON VOUT 3.3V 2A BD RUN/SS BOOST 0.47μF VC LT3480 4.7μH SW RT 470pF VOUT = 5V 90 14k 4.7μF 100 EFFICIENCY (%) VIN 4.5V TO 36V TRANSIENT TO 60V Efficiency VOUT = 3.3V 80 70 PG 40.2k SYNC 60 316k GND VIN = 12V L = 5.6μH F = 800 kHz FB 22μF 100k 50 0 3480 TA01 0.5 1.0 1.5 LOAD CURRENT (A) 2 3480 TA01b 3480fb 1 LT3480 ABSOLUTE MAXIMUM RATINGS (Note 1) VIN, RUN/SS Voltage (Note 5) ...................................60V BOOST Pin Voltage ...................................................56V BOOST Pin Above SW Pin.........................................30V FB, RT, VC Voltage .......................................................5V PG, BD, SYNC Voltage ..............................................30V Maximum Junction Temperature........................... 125°C Operating Temperature Range (Note 2) LT3480E ............................................... –40°C to 85°C LT3480I .............................................. –40°C to 125°C Storage Temperature Range................... –65°C to 150°C Lead Temperature (Soldering, 10 sec) (MSE Only) ....................................................... 300°C PIN CONFIGURATION TOP VIEW TOP VIEW BD 1 10 RT BOOST 2 9 VC SW 3 VIN 4 7 PG RUN/SS 5 6 SYNC 11 BD BOOST SW VIN RUN/SS 8 FB 1 2 3 4 5 10 9 8 7 6 11 RT VC FB PG SYNC MSE PACKAGE 10-LEAD PLASTIC MSOP DD PACKAGE 10-LEAD (3mm s 3mm) PLASTIC DFN JA = 45°C/W, JC = 10°C/W EXPOSED PAD (PIN 11) IS GND, MUST BE SOLDERED TO PCB JA = 45°C/W, JC = 10°C/W EXPOSED PAD (PIN 11) IS GND, MUST BE SOLDERED TO PCB ORDER INFORMATION LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LT3480EDD#PBF LT3480EDD#TRPBF LCTP 10-Lead (3mm × 3mm) Plastic DFN –40°C to 85°C LT3480IDD#PBF LT3480IDD#TRPBF LCTP 10-Lead (3mm × 3mm) Plastic DFN –40°C to 125°C LT3480EMSE#PBF LT3480EMSE#TRPBF LTCTM 10-Lead Plastic MSOP –40°C to 85°C LT3480IMSE#PBF LT3480IMSE#TRPBF LTCTM 10-Lead Plastic MSOP –40°C to 125°C LEAD BASED FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LT3480EDD LT3480EDD#TR LCTP 10-Lead (3mm × 3mm) Plastic DFN –40°C to 85°C LT3480IDD LT3480IDD#TR LCTP 10-Lead (3mm × 3mm) Plastic DFN –40°C to 125°C LT3480EMSE LT3480EMSE#TR LTCTM 10-Lead Plastic MSOP –40°C to 85°C LT3480IMSE LT3480IMSE#TR LTCTM 10-Lead Plastic MSOP –40°C to 125°C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 10V, VRUN/SS = 10V, VBOOST = 15V, VBD = 3.3V unless otherwise noted. (Note 2) PARAMETER CONDITIONS MIN Minimum Input Voltage l VIN Overvoltage Lockout l 36 TYP MAX UNITS 3 3.6 V 38 40 V 3480fb 2 LT3480 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 10V, VRUN/SS = 10V, VBOOST = 15V, VBD = 3.3V unless otherwise noted. (Note 2) PARAMETER CONDITIONS Quiescent Current from VIN VRUN/SS = 0.2V VBD = 3V, Not Switching VBD = 0, Not Switching Quiescent Current from BD VRUN/SS = 0.2V VBD = 3V, Not Switching VBD = 0, Not Switching MIN TYP MAX UNITS l 0.01 30 105 0.5 100 160 μA μA μA l 0.01 80 1 0.5 120 5 μA μA μA Minimum Bias Voltage (BD Pin) Feedback Voltage l FB Pin Bias Current (Note 3) VFB = 0.8V, VC = 0.4V FB Voltage Line Regulation 4V < VIN < 36V 780 775 l 2.7 3 790 790 800 805 7 30 nA 0.002 0.01 %/V Error Amp gm 400 Error Amp Gain 1000 VC Source Current V mV mV μMho 45 μA VC Sink Current 45 μA VC Pin to Switch Current Gain 3.5 A/V VC Clamp Voltage Switching Frequency 2 RT = 8.66k RT = 29.4k RT = 187k 2.1 0.9 160 2.4 1 200 2.7 1.15 240 MHz MHz kHz 60 150 nS 3 3.5 4 A l Minimum Switch Off-Time V Switch Current Limit Duty Cycle = 5% Switch VCESAT ISW = 2A 500 Boost Schottky Reverse Leakage VSW = 10V, VBD = 0V 0.02 2 μA 1.5 2.1 V l Minimum Boost Voltage (Note 4) mV BOOST Pin Current ISW = 1A 22 35 mA RUN/SS Pin Current VRUN/SS = 2.5V 5 10 μA 2.5 V RUN/SS Input Voltage High RUN/SS Input Voltage Low PG Threshold Offset from Feedback Voltage 0.2 V VFB Rising 100 PG Leakage VPG = 5V 0.1 PG Sink Current VPG = 0.4V PG Hysteresis 12 SYNC Low Threshold l 100 mV 1 600 V 0.7 VSYNC = 0V Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The LT3480E is guaranteed to meet performance specifications from 0°C to 85°C. Specifications over the –40°C to 85°C operating temperature range are assured by design, characterization and correlation with statistical process controls. The LT3480I specifications are guaranteed over the –40°C to 125°C temperature range. μA μA 0.5 SYNC High Threshold SYNC Pin Bias Current mV 0.1 V μA Note 3: Bias current flows out of the FB pin. Note 4: This is the minimum voltage across the boost capacitor needed to guarantee full saturation of the switch. Note 5: Absolute Maximum Voltage at VIN and RUN/SS pins is 60V for nonrepetitive 1 second transients, and 40V for continious operation. 3480fb 3 LT3480 TYPICAL PERFORMANCE CHARACTERISTICS Efficiency Efficiency 90 VIN = 7V 85 VIN = 12V 90 VIN = 12V 10 80 80 VIN = 24V 70 VIN = 34V 75 EFFICIENCY (%) EFFICIENCY (%) VIN = 34V 80 VIN = 24V 70 65 70 1 60 50 0.1 60 60 L: NEC PLC-0745-5R6 f: 800kHz VOUT = 5V 50 0 40 55 L: NEC PLC-0745-5R6 f: 800kHz VOUT = 3.3V 50 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 LOAD CURRENT (A) VIN = 12V VOUT = 3.3V L = 5.6μH F = 800 kHz 0 30 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 LOAD CURRENT (A) 0.5 1.0 1.5 LOAD CURRENT (A) POWER LOSS (W) EFFICIENCY (%) Efficiency 90 100 0.01 2 3480 G27 3480 G02 3480 G01 No Load Supply Current No Load Supply Current CATCH DIODE: DIODES, INC. PDS360 350 SUPPLY CURRENT (μA) SUPPLY CURRENT (μA) 100 80 60 40 Maximum Load Current 4.0 400 VOUT = 3.3V 20 3.5 VIN = 12V VOUT = 3.3V 300 LOAD CURRENT (A) 120 INCREASED SUPPLY CURRENT DUE TO CATCH DIODE LEAKAGE AT HIGH TEMPERATURE 250 200 150 0 15 10 20 25 INPUT VOLTAGE (V) 5 30 Maximum Load Current 5 25 50 75 100 125 150 TEMPERATURE (°C) Switch Current Limit MINIMUM 2.0 VOUT = 5V TA = 25 °C L = 4.7μH f = 800kHz 3.5 SWITCH CURRENT LIMIT (A) 2.5 3.0 2.5 2.0 1.5 25 30 3480 G07 30 DUTY CYCLE = 10 % 3.5 3.0 DUTY CYCLE = 90 % 2.5 2.0 1.5 1.0 0.5 1.0 1.0 25 Switch Current Limit 4.0 SWITCH CURRENT LIMIT(A) LOAD CURRENT (A) 20 15 INPUT VOLTAGE (V) 4.5 TYPICAL 3.0 20 15 INPUT VOLTAGE (V) 10 3480 G06 4.0 10 VOUT = 3.3V TA = 25 °C L = 4.7μH f = 800 kHz 3480 G05 3.5 5 MINIMUM 2.0 1.0 0 3480 G04 1.5 2.5 1.5 0 –50 –25 35 3.0 100 50 0 TYPICAL 0 20 60 40 DUTY CYCLE (%) 80 100 3480 G08 0 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3480 G09 3480fb 4 LT3480 TYPICAL PERFORMANCE CHARACTERISTICS Boost Pin Current 80 600 70 500 400 300 200 100 840 60 50 40 30 20 0 0 500 1000 2000 1500 SWITCH CURRENT (mA) 2500 0 500 1000 1500 2000 SWITCH CURRENT (mA) 800 780 Switching Frequency 1.05 1.00 0.95 0.90 0.85 140 1000 120 800 600 400 200 0 0 25 50 75 100 125 150 TEMPERATURE (°C) 0 Soft-Start 2.0 1.5 1.0 20 0.5 0 3 3.5 3480 G16 0 25 50 75 100 125 150 TEMPERATURE (˚C) Boost Diode 12 1.4 10 1.2 8 6 4 2 2.5 2 1.5 RUN/SS PIN VOLTAGE (V) 40 3480 G15 BOOST DIODE Vf (V) RUN/SS PIN CURRENT (μA) 2.5 1 60 RUN/SS Pin Current 3.5 0.5 80 3480 G14 4.0 0 100 0 –50 –25 100 200 300 400 500 600 700 800 900 FB PIN VOLTAGE (mV) 4380 G13 3.0 25 50 75 100 125 150 TEMPERATURE (°C) Minimum Switch On-Time 1200 MINIMUM SWITCH ON TIME (ns) SWITCHING FREQUENCY (kHz) 1.15 1.10 0 4380 G12 Frequency Foldback 1.20 0.80 –50 –25 760 –50 –25 2500 3480 G11 3480 G10 FREQUENCY (MHz) 820 10 0 SWITCH CURRENT LIMIT (A) Feedback Voltage FEEDBACK VOLTAGE (mV) 700 BOOST PIN CURRENT (mA) VOLTAGE DROP (mV) Switch Voltage Drop 1.0 0.8 0.6 0.4 0.2 0 0 5 20 30 15 25 10 RUN/SS PIN VOLTAGE (V) 35 3480 G17 0 0 0.5 1.0 1.5 BOOST DIODE CURRENT (A) 2.0 3480 G18 3480fb 5 LT3480 TYPICAL PERFORMANCE CHARACTERISTICS Error Amp Output Current Minimum Input Voltage Minimum Input Voltage 5.0 50 6.5 40 4.5 20 10 0 –10 –20 –30 4.0 3.5 3.0 2.5 –40 –50 –200 2.0 –100 100 0 FB PIN ERROR VOLTAGE (V) 6.0 INPUT VOLTAGE (V) INPUT VOLTAGE (V) VC PIN CURRENT (μA) 30 VOUT = 3.3V TA = 25°C L = 4.7μH f = 800kHz 10 1 200 VC Voltages 4.0 100 1000 LOAD CURRENT (A) 1 10000 10 100 1000 LOAD CURRENT (A) 10000 3480 G21 Power Good Threshold Switching Waveforms; Burst Mode 95 THRESHOLD VOLTAGE (%) 2.00 CURRENT LIMIT CLAMP VC VOLTAGE (V) VOUT = 5V TA = 25 °C L = 4.7μH f = 800kHz 3480 G20 2.50 1.50 SWITCHING THRESHOLD VSW 5V/DIV 90 85 IL 0.2A/DIV 80 VOUT 10mV/DIV 0.50 0 –50 –25 5.0 4.5 3480 G19 1.00 5.5 0 25 50 75 100 125 150 TEMPERATURE (°C) 75 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3480 G22 3480 G23 Switching Waveforms; Transition from Burst Mode to Full Frequency 5μs/DIV VIN = 12V; FRONT PAGE APPLICATION ILOAD = 10mA 3480 G24 Switching Waveforms; Full Frequency Continuous Operation VSW 5V/DIV VSW 5V/DIV IL 0.2A/DIV IL 0.5A/DIV VOUT 10mV/DIV VOUT 10mV/DIV 1μs/DIV VIN = 12V; FRONT PAGE APPLICATION ILOAD = 110mA 3480 G25 1μs/DIV VIN = 12V; FRONT PAGE APPLICATION ILOAD = 1A 3480 G26 3480fb 6 LT3480 PIN FUNCTIONS BD (Pin 1): This pin connects to the anode of the boost Schottky diode. BD also supplies current to the internal regulator. BOOST (Pin 2): This pin is used to provide a drive voltage, higher than the input voltage, to the internal bipolar NPN power switch. SW (Pin 3): The SW pin is the output of the internal power switch. Connect this pin to the inductor, catch diode and boost capacitor. VIN (Pin 4): The VIN pin supplies current to the LT3480’s internal regulator and to the internal power switch. This pin must be locally bypassed. RUN/SS (Pin 5): The RUN/SS pin is used to put the LT3480 in shutdown mode. Tie to ground to shut down the LT3480. Tie to 2.5V or more for normal operation. If the shutdown feature is not used, tie this pin to the VIN pin. RUN/SS also provides a soft-start function; see the Applications Information section. SYNC (Pin 6): This is the external clock synchronization input. Ground this pin for low ripple Burst Mode operation at low output loads. Tie to a clock source for synchronization. Clock edges should have rise and fall times faster than 1μs. See synchronizing section in Applications Information. PG (Pin 7): The PG pin is the open collector output of an internal comparator. PG remains low until the FB pin is within 14% of the final regulation voltage. PG output is valid when VIN is above 3.6V and RUN/SS is high. FB (Pin 8): The LT3480 regulates the FB pin to 0.790V. Connect the feedback resistor divider tap to this pin. VC (Pin 9): The VC pin is the output of the internal error amplifier. The voltage on this pin controls the peak switch current. Tie an RC network from this pin to ground to compensate the control loop. RT (Pin 10): Oscillator Resistor Input. Connecting a resistor to ground from this pin sets the switching frequency. Exposed Pad (Pin 11): Ground. The Exposed Pad must be soldered to PCB. BLOCK DIAGRAM VIN 4 VIN C1 – + INTERNAL 0.79V REF 5 10 RUN/SS 3 SLOPE COMP BD SWITCH LATCH BOOST 6 RT OSCILLATOR 200kHz–2.4MHz C3 Q S DISABLE SYNC L1 VOUT 3 C2 D1 BurstMode DETECT SOFT-START 7 2 R SW RT 1 PG ERROR AMP + – + – 0.7V VC CLAMP VC 9 CC GND 11 FB RC CF 8 R2 R1 3480 BD 3480fb 7 LT3480 OPERATION The LT3480 is a constant frequency, current mode stepdown regulator. An oscillator, with frequency set by RT, enables an RS flip-flop, turning on the internal power switch. An amplifier and comparator monitor the current flowing between the VIN and SW pins, turning the switch off when this current reaches a level determined by the voltage at VC. An error amplifier measures the output voltage through an external resistor divider tied to the FB pin and servos the VC pin. If the error amplifier’s output increases, more current is delivered to the output; if it decreases, less current is delivered. An active clamp on the VC pin provides current limit. The VC pin is also clamped to the voltage on the RUN/SS pin; soft-start is implemented by generating a voltage ramp at the RUN/SS pin using an external resistor and capacitor. An internal regulator provides power to the control circuitry. The bias regulator normally draws power from the VIN pin, but if the BD pin is connected to an external voltage higher than 3V bias power will be drawn from the external source (typically the regulated output voltage). This improves efficiency. The RUN/SS pin is used to place the LT3480 in shutdown, disconnecting the output and reducing the input current to less than 1μA. The switch driver operates from either the input or from the BOOST pin. An external capacitor and diode are used to generate a voltage at the BOOST pin that is higher than the input supply. This allows the driver to fully saturate the internal bipolar NPN power switch for efficient operation. To further optimize efficiency, the LT3480 automatically switches to Burst Mode operation in light load situations. Between bursts, all circuitry associated with controlling the output switch is shut down, reducing the input supply current to 70μA in a typical application. The oscillator reduces the LT3480’s operating frequency when the voltage at the FB pin is low. This frequency foldback helps to control the output current during startup and overload. The LT3480 contains a power good comparator which trips when the FB pin is at 86% of its regulated value. The PG output is an open-collector transistor that is off when the output is in regulation, allowing an external resistor to pull the PG pin high. Power good is valid when the LT3480 is enabled and VIN is above 3.6V. The LT3480 has an overvoltage protection feature which disables switching action when the VIN goes above 38V typical (36V minimum). When switching is disabled, the LT3480 can safely sustain input voltages up to 60V. 3480fb 8 LT3480 APPLICATIONS INFORMATION FB Resistor Network The output voltage is programmed with a resistor divider between the output and the FB pin. Choose the 1% resistors according to: ⎛ V ⎞ R1= R2 ⎜ OUT − 1⎟ ⎝ 0.79 V ⎠ Reference designators refer to the Block Diagram. Setting the Switching Frequency The LT3480 uses a constant frequency PWM architecture that can be programmed to switch from 200kHz to 2.4MHz by using a resistor tied from the RT pin to ground. A table showing the necessary RT value for a desired switching frequency is in Figure 1. SWITCHING FREQUENCY (MHz) RT VALUE (kΩ) 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 187 121 88.7 68.1 56.2 46.4 40.2 34 29.4 23.7 19.1 16.2 13.3 11.5 9.76 8.66 Figure 1. Switching Frequency vs. RT Value Operating Frequency Tradeoffs Selection of the operating frequency is a tradeoff between efficiency, component size, minimum dropout voltage, and maximum input voltage. The advantage of high frequency operation is that smaller inductor and capacitor values may be used. The disadvantages are lower efficiency, lower maximum input voltage, and higher dropout voltage. The highest acceptable switching frequency (fSW(MAX)) for a given application can be calculated as follows: fSW(MAX ) = VD + VOUT tON(MIN) ( VD + VIN – VSW ) where VIN is the typical input voltage, VOUT is the output voltage, VD is the catch diode drop (~0.5V) and VSW is the internal switch drop (~0.5V at max load). This equation shows that slower switching frequency is necessary to safely accommodate high VIN/VOUT ratio. Also, as shown in the next section, lower frequency allows a lower dropout voltage. The reason input voltage range depends on the switching frequency is because the LT3480 switch has finite minimum on and off times. The switch can turn on for a minimum of ~150ns and turn off for a minimum of ~150ns. Typical minimum on time at 25°C is 80ns. This means that the minimum and maximum duty cycles are: DCMIN = fSW tON(MIN) DCMAX = 1– fSW tOFF(MIN) where fSW is the switching frequency, the tON(MIN) is the minimum switch on time (~150ns), and the tOFF(MIN) is the minimum switch off time (~150ns). These equations show that duty cycle range increases when switching frequency is decreased. A good choice of switching frequency should allow adequate input voltage range (see next section) and keep the inductor and capacitor values small. Input Voltage Range The maximum input voltage for LT3480 applications depends on switching frequency, the Absolute Maximum Ratings of the VIN and BOOST pins, and the operating mode. The LT3480 can operate from input voltages up to 38V, and safely withstand input voltages up 60V. Note that while VIN>38V (typical), the LT3480 will stop switching, allowing the output to fall out of regulation. While the output is in start-up, short-circuit, or other overload conditions, the switching frequency should be chosen according to the following discussion. For safe operation at inputs up to 60V the switching frequency must be set low enough to satisfy VIN(MAX) ≥ 40V according to the following equation. If lower VIN(MAX) is desired, this equation can be used directly. 3480fb 9 LT3480 APPLICATIONS INFORMATION VIN(MAX ) = VOUT + VD –V +V fSW tON(MIN) D SW where VIN(MAX) is the maximum operating input voltage, VOUT is the output voltage, VD is the catch diode drop (~0.5V), VSW is the internal switch drop (~0.5V at max load), fSW is the switching frequency (set by RT), and tON(MIN) is the minimum switch on time (~150ns). Note that a higher switching frequency will depress the maximum operating input voltage. Conversely, a lower switching frequency will be necessary to achieve safe operation at high input voltages. If the output is in regulation and no short-circuit, startup, or overload events are expected, then input voltage transients of up to 60V are acceptable regardless of the switching frequency. In this mode, the LT3480 may enter pulse skipping operation where some switching pulses are skipped to maintain output regulation. In this mode the output voltage ripple and inductor current ripple will be higher than in normal operation. Above 38V switching will stop. The minimum input voltage is determined by either the LT3480’s minimum operating voltage of ~3.6V or by its maximum duty cycle (see equation in previous section). The minimum input voltage due to duty cycle is: VIN(MIN) = VOUT + VD –V +V 1– fSW tOFF(MIN) D SW where VIN(MIN) is the minimum input voltage, and tOFF(MIN) is the minimum switch off time (150ns). Note that higher switching frequency will increase the minimum input voltage. If a lower dropout voltage is desired, a lower switching frequency should be used. Inductor Selection For a given input and output voltage, the inductor value and switching frequency will determine the ripple current. The ripple current ΔIL increases with higher VIN or VOUT and decreases with higher inductance and faster switching frequency. A reasonable starting point for selecting the ripple current is: ΔIL = 0.4(IOUT(MAX)) where IOUT(MAX) is the maximum output load current. To guarantee sufficient output current, peak inductor current must be lower than the LT3480’s switch current limit (ILIM). The peak inductor current is: IL(PEAK) = IOUT(MAX) + ΔIL/2 where IL(PEAK) is the peak inductor current, IOUT(MAX) is the maximum output load current, and ΔIL is the inductor ripple current. The LT3480’s switch current limit (ILIM) is at least 3.5A at low duty cycles and decreases linearly to 2.5A at DC = 0.8. The maximum output current is a function of the inductor ripple current: IOUT(MAX) = ILIM – ΔIL/2 Be sure to pick an inductor ripple current that provides sufficient maximum output current (IOUT(MAX)). The largest inductor ripple current occurs at the highest VIN. To guarantee that the ripple current stays below the specified maximum, the inductor value should be chosen according to the following equation: ⎛ V +V ⎞⎛ V +V ⎞ L = ⎜ OUT D ⎟ ⎜ 1– OUT D ⎟ VIN(MAX ) ⎠ ⎝ fSW ΔIL ⎠ ⎝ where VD is the voltage drop of the catch diode (~0.4V), VIN(MAX) is the maximum input voltage, VOUT is the output voltage, fSW is the switching frequency (set by RT), and L is in the inductor value. The inductor’s RMS current rating must be greater than the maximum load current and its saturation current should be about 30% higher. For robust operation in fault conditions (start-up or short circuit) and high input voltage (>30V), the saturation current should be above 3.5A. To keep the efficiency high, the series resistance (DCR) should be less than 0.1 , and the core material should be intended for high frequency applications. Table 1 lists several vendors and suitable types. 3480fb 10 LT3480 APPLICATIONS INFORMATION Table 1. Inductor Vendors VENDOR URL PART SERIES Murata www.murata.com LQH55D Open TDK www.componenttdk.com SLF7045 SLF10145 Shielded Shielded Toko www.toko.com Sumida www.sumida.com TYPE D62CB Shielded D63CB Shielded D75C Shielded D75F Open CR54 Open CDRH74 Shielded CDRH6D38 Shielded CR75 Open Of course, such a simple design guide will not always result in the optimum inductor for your application. A larger value inductor provides a slightly higher maximum load current and will reduce the output voltage ripple. If your load is lower than 2A, then you can decrease the value of the inductor and operate with higher ripple current. This allows you to use a physically smaller inductor, or one with a lower DCR resulting in higher efficiency. There are several graphs in the Typical Performance Characteristics section of this data sheet that show the maximum load current as a function of input voltage and inductor value for several popular output voltages. Low inductance may result in discontinuous mode operation, which is okay but further reduces maximum load current. For details of maximum output current and discontinuous mode operation, see Linear Technology Application Note 44. Finally, for duty cycles greater than 50% (VOUT/VIN > 0.5), there is a minimum inductance required to avoid subharmonic oscillations. See AN19. Input Capacitor Bypass the input of the LT3480 circuit with a ceramic capacitor of X7R or X5R type. Y5V types have poor performance over temperature and applied voltage, and should not be used. A 4.7μF to 10μF ceramic capacitor is adequate to bypass the LT3480 and will easily handle the ripple current. Note that larger input capacitance is required when a lower switching frequency is used. If the input power source has high impedance, or there is significant inductance due to long wires or cables, additional bulk capacitance may be necessary. This can be provided with a lower performance electrolytic capacitor. Step-down regulators draw current from the input supply in pulses with very fast rise and fall times. The input capacitor is required to reduce the resulting voltage ripple at the LT3480 and to force this very high frequency switching current into a tight local loop, minimizing EMI. A 4.7μF capacitor is capable of this task, but only if it is placed close to the LT3480 and the catch diode (see the PCB Layout section). A second precaution regarding the ceramic input capacitor concerns the maximum input voltage rating of the LT3480. A ceramic input capacitor combined with trace or cable inductance forms a high quality (under damped) tank circuit. If the LT3480 circuit is plugged into a live supply, the input voltage can ring to twice its nominal value, possibly exceeding the LT3480’s voltage rating. This situation is easily avoided (see the Hot Plugging Safety section). For space sensitive applications, a 2.2μF ceramic capacitor can be used for local bypassing of the LT3480 input. However, the lower input capacitance will result in increased input current ripple and input voltage ripple, and may couple noise into other circuitry. Also, the increased voltage ripple will raise the minimum operating voltage of the LT3480 to ~3.7V. Output Capacitor and Output Ripple The output capacitor has two essential functions. Along with the inductor, it filters the square wave generated by the LT3480 to produce the DC output. In this role it determines the output ripple, and low impedance at the switching frequency is important. The second function is to store energy in order to satisfy transient loads and stabilize the LT3480’s control loop. Ceramic capacitors have very low equivalent series resistance (ESR) and provide the best ripple performance. A good starting value is: COUT = 100 VOUT fSW where fSW is in MHz, and COUT is the recommended output capacitance in μF. Use X5R or X7R types. This choice will provide low output ripple and good transient response. Transient performance can be improved with a higher value 3480fb 11 LT3480 APPLICATIONS INFORMATION Table 2. Capacitor Vendors VENDOR PHONE URL Panasonic (714) 373-7366 www.panasonic.com PART SERIES COMMANDS Ceramic, Polymer, EEF Series Tantalum Kemet (864) 963-6300 www.kemet.com Sanyo (408) 749-9714 www.sanyovideo.com Ceramic, Tantalum T494, T495 Ceramic, Polymer, POSCAP Tantalum Murata (408) 436-1300 AVX www.murata.com Ceramic www.avxcorp.com Ceramic, Tantalum Taiyo Yuden (864) 963-6300 www.taiyo-yuden.com capacitor if the compensation network is also adjusted to maintain the loop bandwidth. A lower value of output capacitor can be used to save space and cost but transient performance will suffer. See the Frequency Compensation section to choose an appropriate compensation network. When choosing a capacitor, look carefully through the data sheet to find out what the actual capacitance is under operating conditions (applied voltage and temperature). A physically larger capacitor, or one with a higher voltage rating, may be required. High performance tantalum or electrolytic capacitors can be used for the output capacitor. Low ESR is important, so choose one that is intended for use in switching regulators. The ESR should be specified by the supplier, and should be 0.05 or less. Such a capacitor will be larger than a ceramic capacitor and will have a larger capacitance, because the capacitor must be large to achieve low ESR. Table 2 lists several capacitor vendors. Catch Diode The catch diode conducts current only during switch off time. Average forward current in normal operation can be calculated from: ID(AVG) = IOUT (VIN – VOUT)/VIN where IOUT is the output load current. The only reason to consider a diode with a larger current rating than necessary for nominal operation is for the worst-case condition of shorted output. The diode current will then increase to the typical peak switch current. Peak reverse voltage is equal TPS Series Ceramic to the regulator input voltage. Use a Schottky diode with a reverse voltage rating greater than the input voltage. The overvoltage protection feature in the LT3480 will keep the switch off when VIN > 38V which allows the use of 40V rated Schottky even when VIN ranges up to 60V. Table 3 lists several Schottky diodes and their manufacturers. Table 3. Diode Vendors PART NUMBER VR (V) IAVE (A) VF AT 1A (mV) VF AT 2A (mV) On Semicnductor MBRM120E MBRM140 20 40 1 1 530 550 595 Diodes Inc. B120 B130 B220 B230 DFLS240L 20 30 20 30 40 1 1 2 2 2 500 500 International Rectifier 10BQ030 20BQ030 30 30 1 2 420 500 500 500 470 470 Ceramic Capacitors Ceramic capacitors are small, robust and have very low ESR. However, ceramic capacitors can cause problems when used with the LT3480 due to their piezoelectric nature. When in Burst Mode operation, the LT3480’s switching frequency depends on the load current, and at very light loads the LT3480 can excite the ceramic capacitor at audio frequencies, generating audible noise. Since the LT3480 operates at a lower current limit during Burst Mode 3480fb 12 LT3480 APPLICATIONS INFORMATION Frequency Compensation The LT3480 uses current mode control to regulate the output. This simplifies loop compensation. In particular, the LT3480 does not require the ESR of the output capacitor for stability, so you are free to use ceramic capacitors to achieve low output ripple and small circuit size. Frequency compensation is provided by the components tied to the VC pin, as shown in Figure 2. Generally a capacitor (CC) and a resistor (RC) in series to ground are used. In addition, there may be lower value capacitor in parallel. This capacitor (CF) is not part of the loop compensation but is used to filter noise at the switching frequency, and is required only if a phase-lead capacitor is used or if the output capacitor has high ESR. Loop compensation determines the stability and transient performance. Designing the compensation network is a bit complicated and the best values depend on the application and in particular the type of output capacitor. A practical approach is to start with one of the circuits in this data sheet that is similar to your application and tune the compensation network to optimize the performance. Stability should then be checked across all operating conditions, including load current, input voltage and temperature. The LT1375 data sheet contains a more thorough discussion of loop compensation and describes how to test the stability using a transient load. Figure 2 shows an equivalent circuit for the LT3480 control loop. The error amplifier is a transconductance amplifier with finite output impedance. The power section, consisting of the modulator, power switch and inductor, is modeled as a transconductance amplifier generating an output LT3480 CURRENT MODE POWER STAGE gm = 3.5mho SW ERROR AMPLIFIER OUTPUT R1 CPL FB gm = 420μmho + A final precaution regarding ceramic capacitors concerns the maximum input voltage rating of the LT3480. A ceramic input capacitor combined with trace or cable inductance forms a high quality (under damped) tank circuit. If the LT3480 circuit is plugged into a live supply, the input voltage can ring to twice its nominal value, possibly exceeding the LT3480’s rating. This situation is easily avoided (see the Hot Plugging Safely section). current proportional to the voltage at the VC pin. Note that the output capacitor integrates this current, and that the capacitor on the VC pin (CC) integrates the error amplifier output current, resulting in two poles in the loop. In most cases a zero is required and comes from either the output capacitor ESR or from a resistor RC in series with CC. This simple model works well as long as the value of the inductor is not too high and the loop crossover frequency is much lower than the switching frequency. A phase lead capacitor (CPL) across the feedback divider may improve the transient response. Figure 3 shows the transient response when the load current is stepped from 500mA to 1500mA and back to 500mA. – operation, the noise is typically very quiet to a casual ear. If this is unacceptable, use a high performance tantalum or electrolytic capacitor at the output. ESR 0.8V C1 + 3M C1 VC CF POLYMER OR TANTALUM GND RC CERAMIC R2 CC 3480 F02 Figure 2. Model for Loop Response VOUT 100mV/DIV IL 0.5A/DIV VIN = 12V; FRONT PAGE APPLICATION 10μs/DIV 3480 F03 Figure 3. Transient Load Response of the LT3480 Front Page Application as the Load Current is Stepped from 500mA to 1500mA. VOUT = 3.3V 3480fb 13 LT3480 APPLICATIONS INFORMATION operation at a lower output load current than when in Burst Mode. The front page application circuit will switch at full frequency at output loads higher than about 60mA. VSW 5V/DIV BOOST and BIAS Pin Considerations IL 0.2A/DIV VOUT 10mV/DIV 5μs/DIV VIN = 12V; FRONT PAGE APPLICATION ILOAD = 10mA 3480 F04 Figure 4. Burst Mode Operation Low-Ripple Burst Mode and Pulse-Skip Mode The LT3480 is capable of operating in either Low-Ripple Burst Mode or Pulse-Skip Mode which are selected using the SYNC pin. See the Synchronization section for details. To enhance efficiency at light loads, the LT3480 can be operated in Low-Ripple Burst Mode operation which keeps the output capacitor charged to the proper voltage while minimizing the input quiescent current. During Burst Mode operation, the LT3480 delivers single cycle bursts of current to the output capacitor followed by sleep periods where the output power is delivered to the load by the output capacitor. Because the LT3480 delivers power to the output with single, low current pulses, the output ripple is kept below 15mV for a typical application. In addition, VIN and BD quiescent currents are reduced to typically 30μA and 80μA respectively during the sleep time. As the load current decreases towards a no load condition, the percentage of time that the LT3480 operates in sleep mode increases and the average input current is greatly reduced resulting in high efficiency even at very low loads. See Figure 4. At higher output loads (above 140mA for the front page application) the LT3480 will be running at the frequency programmed by the RT resistor, and will be operating in standard PWM mode. The transition between PWM and Low-Ripple Burst Mode is seamless, and will not disturb the output voltage. If low quiescent current is not required the LT3480 can operate in Pulse-Skip mode. The benefit of this mode is that the LT3480 will enter full frequency standard PWM Capacitor C3 and the internal boost Schottky diode (see the Block Diagram) are used to generate a boost voltage that is higher than the input voltage. In most cases a 0.22μF capacitor will work well. Figure 2 shows three ways to arrange the boost circuit. The BOOST pin must be more than 2.3V above the SW pin for best efficiency. For outputs of 3V and above, the standard circuit (Figure 5a) is best. For outputs between 2.8V and 3V, use a 1μF boost capacitor. A 2.5V output presents a special case because it is marginally adequate to support the boosted drive stage while using the internal boost diode. For reliable BOOST pin operation with 2.5V outputs use a good external Schottky diode (such as the ON Semi MBR0540), and a 1μF boost capacitor (see Figure 5b). For lower output voltages the boost diode can be tied to the input (Figure 5c), or to another supply greater than 2.8V. Tying BD to VIN reduces the maximum input voltage to 30V. The circuit in Figure 5a is more efficient because the BOOST pin current and BD pin quiescent current comes from a lower voltage source. You must also be sure that the maximum voltage ratings of the BOOST and BD pins are not exceeded. The minimum operating voltage of an LT3480 application is limited by the minimum input voltage (3.6V) and by the maximum duty cycle as outlined in a previous section. For proper startup, the minimum input voltage is also limited by the boost circuit. If the input voltage is ramped slowly, or the LT3480 is turned on with its RUN/SS pin when the output is already in regulation, then the boost capacitor may not be fully charged. Because the boost capacitor is charged with the energy stored in the inductor, the circuit will rely on some minimum load current to get the boost circuit running properly. This minimum load will depend on input and output voltages, and on the arrangement of the boost circuit. The minimum load generally goes to zero once the circuit has started. Figure 6 shows a plot of minimum load to start and to run as a function of input voltage. In many cases the discharged output capacitor will present a load to the switcher, which will allow it to start. The plots show 3480fb 14 LT3480 APPLICATIONS INFORMATION 6.0 VOUT BD 5.5 TO START (WORST CASE) VIN VIN LT3480 GND 4.7μF INPUT VOLTAGE (V) BOOST C3 SW 5.0 4.5 4.0 TO RUN 3.5 3.0 (5a) For VOUT > 2.8V VOUT = 3.3V TA = 25°C L = 8.2μH f = 700kHz 2.5 2.0 VOUT BD BOOST VIN VIN LT3480 TO START (WORST CASE) SW (5b) For 2.5V < VOUT < 2.8V VOUT LT3480 5.0 TO RUN 4.0 VOUT = 5V TA = 25°C L = 8.2μH f = 700kHz 2.0 BOOST VIN 6.0 3.0 BD VIN 10000 8.0 INPUT VOLTAGE (V) GND 100 1000 LOAD CURRENT (A) C3 7.0 4.7μF 10 1 D2 1 C3 10 100 1000 LOAD CURRENT (A) 10000 3480 F06 4.7μF GND SW Figure 6. The Minimum Input Voltage Depends on Output Voltage, Load Current and Boost Circuit 3480 FO5 (5c) For VOUT < 2.5V; VIN(MAX) = 30V Figure 5. Three Circuits For Generating The Boost Voltage the worst-case situation where VIN is ramping very slowly. For lower start-up voltage, the boost diode can be tied to VIN; however, this restricts the input range to one-half of the absolute maximum rating of the BOOST pin. At light loads, the inductor current becomes discontinuous and the effective duty cycle can be very high. This reduces the minimum input voltage to approximately 300mV above VOUT. At higher load currents, the inductor current is continuous and the duty cycle is limited by the maximum duty cycle of the LT3480, requiring a higher input voltage to maintain regulation. Soft-Start The RUN/SS pin can be used to soft-start the LT3480, reducing the maximum input current during start-up. The RUN/SS pin is driven through an external RC filter to create a voltage ramp at this pin. Figure 7 shows the start-up and shut-down waveforms with the soft-start circuit. By choosing a large RC time constant, the peak start-up current can be reduced to the current that is required to regulate the output, with no overshoot. Choose the value of the resistor so that it can supply 20μA when the RUN/SS pin reaches 2.5V. Synchronization To select Low-Ripple Burst Mode operation, tie the SYNC pin below 0.3V (this can be ground or a logic output). 3480fb 15 LT3480 APPLICATIONS INFORMATION D4 MBRS140 IL 1A/DI RUN VIN VIN 15k RUN/SS RUN/SS 0.22μF BOOST LT3480 VRUN/ 2V/DI GND VOUT SW VC GND FB VOUT 2V/DI BACKUP 2ms/DIV 3480 F07 Figure 7. To Soft-Start the LT3480, Add a Resisitor and Capacitor to the RUN/SS Pin Synchronizing the LT3480 oscillator to an external frequency can be done by connecting a square wave (with 20% to 80% duty cycle) to the SYNC pin. The square wave amplitude should have valleys that are below 0.3V and peaks that are above 0.8V (up to 6V). The LT3480 will not enter Burst Mode at low output loads while synchronized to an external clock, but instead will skip pulses to maintain regulation. The LT3480 may be synchronized over a 250kHz to 2MHz range. The RT resistor should be chosen to set the LT3480 switching frequency 20% below the lowest synchronization input. For example, if the synchronization signal will be 250kHz and higher, the RT should be chosen for 200kHz. To assure reliable and safe operation the LT3480 will only synchronize when the output voltage is near regulation as indicated by the PG flag. It is therefore necessary to choose a large enough inductor value to supply the required output current at the frequency set by the RT resistor. See Inductor Selection section. It is also important to note that slope compensation is set by the RT value: When the sync frequency is much higher than the one set by RT, the slope compensation will be significantly reduced which may require a larger inductor value to prevent subharmonic oscillation. Shorted and Reversed Input Protection If the inductor is chosen so that it won’t saturate excessively, an LT3480 buck regulator will tolerate a shorted output. There is another situation to consider in systems where the output will be held high when the input to the LT3480 is absent. This may occur in battery charging applications 3480 F08 Figure 8. Diode D4 Prevents a Shorted Input from Discharging a Backup Battery Tied to the Output. It Also Protects the Circuit from a Reversed Input. The LT3480 Runs Only When the Input is Present or in battery backup systems where a battery or some other supply is diode OR-ed with the LT3480’s output. If the VIN pin is allowed to float and the RUN/SS pin is held high (either by a logic signal or because it is tied to VIN), then the LT3480’s internal circuitry will pull its quiescent current through its SW pin. This is fine if your system can tolerate a few mA in this state. If you ground the RUN/SS pin, the SW pin current will drop to essentially zero. However, if the VIN pin is grounded while the output is held high, then parasitic diodes inside the LT3480 can pull large currents from the output through the SW pin and the VIN pin. Figure 8 shows a circuit that will run only when the input voltage is present and that protects against a shorted or reversed input. PCB Layout For proper operation and minimum EMI, care must be taken during printed circuit board layout. Figure 9 shows the recommended component placement with trace, ground plane and via locations. Note that large, switched currents flow in the LT3480’s VIN and SW pins, the catch diode (D1) and the input capacitor (C1). The loop formed by these components should be as small as possible. These components, along with the inductor and output capacitor, should be placed on the same side of the circuit board, and their connections should be made on that layer. Place a local, unbroken ground plane below these components. The SW and BOOST nodes should be as small as possible. 3480fb 16 LT3480 APPLICATIONS INFORMATION L1 Finally, keep the FB and VC nodes small so that the ground traces will shield them from the SW and BOOST nodes. The Exposed Pad on the bottom of the package must be soldered to ground so that the pad acts as a heat sink. To keep thermal resistance low, extend the ground plane as much as possible, and add thermal vias under and near the LT3480 to additional ground planes within the circuit board and on the bottom side. C2 VOUT CC RRT RC R2 Hot Plugging Safely R1 D1 C1 RPG GND 3480 F09 VIAS TO LOCAL GROUND PLANE VIAS TO VOUT VIAS TO RUN/SS VIAS TO SYNC VIAS TO VIN OUTLINE OF LOCAL GROUND PLANE VIAS TO PG Figure 9. A Good PCB Layout Ensures Proper, Low EMI Operation CLOSING SWITCH SIMULATES HOT PLUG IIN VIN The small size, robustness and low impedance of ceramic capacitors make them an attractive option for the input bypass capacitor of LT3480 circuits. However, these capacitors can cause problems if the LT3480 is plugged into a live supply (see Linear Technology Application Note 88 for a complete discussion). The low loss ceramic capacitor, combined with stray inductance in series with the power DANGER VIN 20V/DIV RINGING VIN MAY EXCEED ABSOLUTE MAXIMUM RATING LT3480 + 4.7μF LOW IMPEDANCE ENERGIZED 24V SUPPLY IIN 10A/DIV STRAY INDUCTANCE DUE TO 6 FEET (2 METERS) OF TWISTED PAIR 20μs/DIV (10a) 0.7Ω LT3480 VIN 20V/DIV + 0.1μF 4.7μF IIN 10A/DIV (10b) LT3480 + 22μF 35V AI.EI. 20μs/DIV VIN 20V/DIV + 4.7μF IIN 10A/DIV (10c) 20μs/DIV 3480 F10 Figure 10. A Well Chosen Input Network Prevents Input Voltage Overshoot and Ensures Reliable Operation when the LT3480 is Connected to a Live Supply 3480fb 17 LT3480 APPLICATIONS INFORMATION source, forms an under damped tank circuit, and the voltage at the VIN pin of the LT3480 can ring to twice the nominal input voltage, possibly exceeding the LT3480’s rating and damaging the part. If the input supply is poorly controlled or the user will be plugging the LT3480 into an energized supply, the input network should be designed to prevent this overshoot. Figure 10 shows the waveforms that result when an LT3480 circuit is connected to a 24V supply through six feet of 24-gauge twisted pair. The first plot is the response with a 4.7μF ceramic capacitor at the input. The input voltage rings as high as 50V and the input current peaks at 26A. A good solution is shown in Figure 10b. A 0.7 resistor is added in series with the input to eliminate the voltage overshoot (it also reduces the peak input current). A 0.1μF capacitor improves high frequency filtering. For high input voltages its impact on efficiency is minor, reducing efficiency by 1.5 percent for a 5V output at full load operating from 24V. the thermal resistance from die (or junction) to ambient can be reduced to JA = 35°C/W or less. With 100 LFPM airflow, this resistance can fall by another 25%. Further increases in airflow will lead to lower thermal resistance. Because of the large output current capability of the LT3480, it is possible to dissipate enough heat to raise the junction temperature beyond the absolute maximum of 125°C. When operating at high ambient temperatures, the maximum load current should be derated as the ambient temperature approaches 125°C. Power dissipation within the LT3480 can be estimated by calculating the total power loss from an efficiency measurement and subtracting the catch diode loss and inductor loss. The die temperature is calculated by multiplying the LT3480 power dissipation by the thermal resistance from junction to ambient. Other Linear Technology Publications Application Notes 19, 35 and 44 contain more detailed descriptions and design information for buck regulators and other switching regulators. The LT1376 data sheet has a more extensive discussion of output ripple, loop compensation and stability testing. Design Note 100 shows how to generate a bipolar output supply using a buck regulator. High Temperature Considerations The PCB must provide heat sinking to keep the LT3480 cool. The Exposed Pad on the bottom of the package must be soldered to a ground plane. This ground should be tied to large copper layers below with thermal vias; these layers will spread the heat dissipated by the LT3480. Place additional vias can reduce thermal resistance further. With these steps, TYPICAL APPLICATIONS 5V Step-Down Converter VIN 6.8V TO 36V TRANSIENT TO 60V* VIN ON OFF VOUT 5V 2A BD RUN/SS BOOST 0.47μF VC 4.7μF LT3480 SW D RT 16.2k L 6.8μH PG 40.2k SYNC 470pF f = 800kHz 536k GND FB 22μF 100k 3480 TA02 D: DIODES INC. DFLS240L L: TAIYO YUDEN NP06DZB6R8M 3480fb 18 LT3480 TYPICAL APPLICATIONS 3.3V Step-Down Converter VIN 4.4V TO 36V TRANSIENT TO 60V* VIN BD RUN/SS ON OFF VOUT 3.3V 2A BOOST L 4.7μH 0.47μF VC 4.7μF SW LT3480 D RT 14k PG SYNC 40.2k 316k FB GND 470pF 22μF 100k f = 800kHz 3480 TA03 D: DIODES INC. DFLS240L L: TAIYO YUDEN NP06DZB4R7M 2.5V Step-Down Converter VIN 4V TO 36V TRANSIENT TO 60V* VIN ON OFF BD RUN/SS D2 BOOST 1μF VC 4.7μF LT3480 L 4.7μH SW D1 RT 20k VOUT 2.5V 2A PG 215k 56.2k SYNC 330pF f = 600kHz GND FB 47μF 100k 3480 TA04 D1: DIODES INC. DFLS240L D2: MBR0540 L: TAIYO YUDEN NP06DZB4R7M 3480fb Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 19 LT3480 TYPICAL APPLICATIONS 5V, 2MHz Step-Down Converter VIN 8.6V TO 22V TRANSIENT TO 38V VIN BD RUN/SS ON OFF VOUT 5V 2A BOOST L 2.2μH 0.47μF VC 2.2μF SW LT3480 D RT 14k PG SYNC 11.5k 536k FB GND 470pF 22μF 100k f = 2MHz 3480 TA05 D: DIODES INC. DFLS240L L: SUMIDA CDRH4D22/HP-2R2 12V Step-Down Converter VIN 15V TO 36V TRANSIENT TO 60V* VIN ON OFF VOUT 12V 2A BD RUN/SS BOOST 0.47μF VC 10μF LT3480 SW D RT 26.1k L 10μH PG 40.2k 715k SYNC GND 330pF f = 800kHz FB 22μF 50k 3480 TA06 D: DIODES INC. DFLS240L L: NEC/TOKIN PLC-0755-100 3480fb 20 LT3480 TYPICAL APPLICATIONS 1.8V Step-Down Converter VOUT 1.8V 2A VIN 3.5V TO 27V VIN ON OFF BD RUN/SS BOOST 0.47μF VC 4.7μF LT3480 SW D RT 18.2k L 3.3μH PG 68.1k SYNC 330pF f = 500kHz 127k GND FB 47μF 100k 3480 TA08 D: DIODES INC. DFLS240L L: TAIYO YUDEN NP06DZB3R3M 3480fb 21 LT3480 PACKAGE DESCRIPTION DD Package 10-Lead Plastic DFN (3mm × 3mm) (Reference LTC DWG # 05-08-1660) R = 0.115 TYP 6 0.38 p 0.10 10 0.675 p 0.05 3.50 p 0.05 1.65 p 0.05 2.15 p 0.05 (2 SIDES) 3.00 p 0.10 (4 SIDES) PACKAGE OUTLINE 1.65 p 0.10 (2 SIDES) PIN 1 TOP MARK (SEE NOTE 6) (DD) DFN 1103 5 0.200 REF 0.25 p 0.05 0.50 BSC 2.38 p 0.05 (2 SIDES) 1 0.25 p 0.05 0.50 BSC 0.75 p 0.05 0.00 – 0.05 2.38 p 0.10 (2 SIDES) BOTTOM VIEW—EXPOSED PAD RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS NOTE: 1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-2). CHECK THE LTC WEBSITE DATA SHEET FOR CURRENT STATUS OF VARIATION ASSIGNMENT 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 3480fb 22 LT3480 PACKAGE DESCRIPTION MSE Package 10-Lead Plastic MSOP (Reference LTC DWG # 05-08-1660) BOTTOM VIEW OF EXPOSED PAD OPTION 2.794 p 0.102 (.110 p .004) 5.23 (.206) MIN 0.889 p 0.127 (.035 p .005) 1 2.06 p 0.102 (.081 p .004) 1.83 p 0.102 (.072 p .004) 2.083 p 0.102 3.20 – 3.45 (.082 p .004) (.126 – .136) 10 0.50 0.305 p 0.038 (.0197) (.0120 p .0015) BSC TYP RECOMMENDED SOLDER PAD LAYOUT 3.00 p 0.102 (.118 p .004) (NOTE 3) 10 9 8 7 6 3.00 p 0.102 (.118 p .004) (NOTE 4) 4.90 p 0.152 (.193 p .006) 0.254 (.010) DETAIL “A” 0o – 6o TYP 1 2 3 4 5 GAUGE PLANE 0.53 p 0.152 (.021 p .006) DETAIL “A” 0.18 (.007) 0.497 p 0.076 (.0196 p .003) REF SEATING PLANE 0.86 (.034) REF 1.10 (.043) MAX 0.17 – 0.27 (.007 – .011) TYP 0.50 (.0197) BSC 0.1016 p 0.0508 (.004 p .002) MSOP (MSE) 0307 REV B NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 3480fb 23 LT3480 TYPICAL APPLICATION 1.2V Step-Down Converter VOUT 1.2V 2A VIN 3.6V TO 27V BD VIN RUN/SS ON OFF BOOST 0.47μF VC 4.7μF LT3480 SW D RT 16.2k L 3.3μH PG 52.3k SYNC 68.1k GND 330pF FB 100k 47μF f = 500kHz 3480 TA09 D: DIODES INC. DFLS240L L: TAIYO YUDEN NP06DZB3R3M RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LT1933 500mA (IOUT), 500kHz Step-Down Switching Regulator in SOT-23 VIN: 3.6V to 36V, VOUT(MIN) = 1.2V, IQ = 1.6mA, ISD <1μA, ThinSOT Package LT3437 60V, 400mA (IOUT), MicroPower Step-Down DC/DC Converter with Burst Mode VIN: 3.3V to 80V, VOUT(MIN) = 1.25V, IQ = 100μA, ISD <1μA, 10-Pin 3mm x 3mm DFN and 16-Pin TSSOP Packages LT1936 36V, 1.4A (IOUT), 500kHz High Efficiency Step-Down DC/DC Converter VIN: 3.6V to 36V, VOUT(MIN) = 1.2V, IQ = 1.9mA, ISD <1μA, MS8E Package LT3493 36V, 1.2A (IOUT), 750kHz High Efficiency Step-Down DC/DC Converter VIN: 3.6V to 40V, VOUT(MIN) = 0.8V, IQ = 1.9mA, ISD <1μA, 6-Pin 2mm x 3mm DFN Package LT1976/LT1977 60V, 1.2A (IOUT), 200kHz/500kHz, High Efficiency Step-Down DC/DC Converter with Burst Mode VIN: 3.3V to 60V, VOUT(MIN) = 1.2V, IQ = 100μA, ISD <1μA, 16-Pin TSSOP Package LT1767 25V, 1.2A (IOUT), 1.1MHz, High Efficiency Step-Down DC/DC Converter VIN: 3V to 25V, VOUT(MIN) = 1.2V, IQ = 1mA, ISD <6μA, MS8E Package LT1940 Dual 25V, 1.4A (IOUT), 1.1MHz, High Efficiency Step-Down DC/DC Converter VIN: 3.6V to 25V, VOUT(MIN) = 1.2V, IQ = 3.8mA, ISD <30μA, 16-Pin TSSOP Package LT1766 60V, 1.2A (IOUT), 200kHz, High Efficiency Step-Down DC/DC Converter VIN: 5.5V to 60V, VOUT(MIN) = 1.2V, IQ = 2.5mA, ISD = 25μA, 16-Pin TSSOP Package LT3434/LT3435 60V, 2.4A (IOUT), 200/500kHz, High Efficiency Step-Down DC/DC Converter with Burst Mode VIN: 3.3V to 60V, VOUT(MIN) = 1.2V, IQ = 100μA, ISD <1μA, 16-Pin TSSOP Package LT3481 36V, 2A (IOUT), 2.8MHz, High Efficiency Step-Down DC/DC Converter with Burst Mode VIN: 3.6V to 34V, VOUT(MIN) = 1.26V, IQ = 50μA, ISD <1μA, 10-Pin 3mm x 3mm DFN and 10-Pin MSOP Packages LT3684 36V, 2A (IOUT), 2.8MHz, High Efficiency Step-Down DC/DC Converter VIN: 3.6V to 34V, VOUT(MIN) = 1.26V, IQ = 1.5mA, ISD <1μA, 10-Pin 3mm x 3mm DFN and 10-Pin MSOP Packages 3480fb 24 Linear Technology Corporation LT 0308 REV B • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com © LINEAR TECHNOLOGY CORPORATION 2008