1.25 Gbps Clock and Data Recovery IC ADN2805 FEATURES GENERAL DESCRIPTION Locks to 1.25 Gbps NRZ serial data input Patented clock recovery architecture No reference clock required Loss-of-lock indicator I2C interface to access optional features Single-supply operation: 3.3 V Low power: 390 mW typical 5 mm × 5 mm 32-lead LFCSP, Pb free The ADN2805 provides the receiver functions of quantization and clock and data recovery for 1.25 Gbps. The ADN2805 automatically locks to all data rates without the need for an external reference clock or programming. All SONET jitter requirements are met, including jitter transfer, jitter generation, and jitter tolerance. All specifications are specified for −40°C to +85°C ambient temperature, unless otherwise noted. The ADN2805 is available in a compact 5 mm × 5 mm 32-lead LFCSP. APPLICATIONS GbE line card FUNCTIONAL BLOCK DIAGRAM REFCLKP/REFCLKN (OPTIONAL) LOL CF1 CF2 FREQUENCY DETECT LOOP FILTER PHASE DETECT LOOP FILTER VCC VEE PIN NIN BUFFER PHASE SHIFTER VCO VREF DATA RE-TIMING DATAOUTP/ DATAOUTN CLKOUTP/ CLKOUTN ADN2805 07121-001 2 2 Figure 1. Rev. 0 Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©2008 Analog Devices, Inc. All rights reserved. ADN2805 TABLE OF CONTENTS Features .............................................................................................. 1 Theory of Operation ...................................................................... 10 Applications ....................................................................................... 1 Functional Description .................................................................. 12 General Description ......................................................................... 1 Frequency Acquisition ............................................................... 12 Functional Block Diagram .............................................................. 1 Input Buffer ................................................................................. 12 Revision History ............................................................................... 2 Lock Detector Operation .......................................................... 12 Specifications..................................................................................... 3 SQUELCH Mode........................................................................ 13 Jitter Specifications ....................................................................... 3 System Reset ................................................................................ 13 Output and Timing Specifications ............................................. 4 I2C Interface ................................................................................ 13 Absolute Maximum Ratings............................................................ 6 Applications Information .............................................................. 14 Thermal Characteristics .............................................................. 6 PCB Design Guidelines ............................................................. 14 ESD Caution .................................................................................. 6 Outline Dimensions ....................................................................... 16 Pin Configuration and Function Descriptions ............................. 7 Ordering Guide .......................................................................... 16 2 I C Interface Timing and Internal Register Description ............. 8 REVISION HISTORY 1/08—Revision 0: Initial Version Rev. 0 | Page 2 of 16 ADN2805 SPECIFICATIONS TA = TMIN to TMAX, VCC = VMIN to VMAX, VEE = 0 V, CF = 0.47 μF, SLICEP = SLICEN = VEE, input data pattern: PRBS 223 − 1, unless otherwise noted. Table 1. Parameter QUANTIZER—DC CHARACTERISTICS Input Voltage Range Peak-to-Peak Differential Input Input Common-Mode Level QUANTIZER—AC CHARACTERISTICS Data Rate S11 Input Resistance Input Capacitance LOSS-OF-LOCK (LOL) DETECT VCO Frequency Error for LOL Assert VCO Frequency Error for LOL Deassert LOL Response Time ACQUISITION TIME Lock-to-Data Mode Optional Lock to REFCLK Mode DATA RATE READBACK ACCURACY Fine Readback POWER SUPPLY Power Supply Voltage Power Supply Current OPERATING TEMPERATURE RANGE Conditions Min @ PIN or NIN, dc-coupled PIN − NIN DC-coupled 1.8 0.2 2.3 Typ Max Unit 2.5 2.8 2.0 2.8 V V V 1250 @ 2.5 GHz Differential −15 100 0.65 Mbps dB Ω pF With respect to nominal With respect to nominal 1000 250 200 ppm ppm μs GbE 1.5 20.0 ms ms In addition to REFCLK accuracy 3.0 3.3 118 Locked to 1.25 Gbps −40 100 ppm 3.6 131 +85 V mA °C JITTER SPECIFICATIONS TA = TMIN to TMAX, VCC = VMIN to VMAX, VEE = 0 V, CF = 0.47 μF, SLICEP = SLICEN = VEE, input data pattern: PRBS 223 − 1, unless otherwise noted. Table 2. Parameter PHASE-LOCKED LOOP CHARACTERISTICS Jitter Peaking Jitter Generation Jitter Tolerance Conditions GbE, IEEE 802.3, 637 kHz Rev. 0 | Page 3 of 16 Min 0.749 Typ Max Unit 0 0.001 0.02 0.03 0.003 0.04 dB UI rms UI p-p UI p-p ADN2805 OUTPUT AND TIMING SPECIFICATIONS Table 3. Parameter LVDS OUTPUT CHARACTERISTICS CLKOUTP/CLKOUTN, DATAOUTP/DATAOUTN Differential Output Swing Output Offset Voltage Output Impedance LVDS Outputs Timing Rise Time Fall Time Setup Time Hold Time 2 I C® INTERFACE DC CHARACTERISTICS Input High Voltage Input Low Voltage Input Current Output Low Voltage I2C INTERFACE TIMING SCK Clock Frequency SCK Pulse Width High SCK Pulse Width Low Start Condition Hold Time Start Condition Setup Time Data Setup Time Data Hold Time SCK/SDA Rise/Fall Time Stop Condition Setup Time Bus Free Time Between a Stop and a Start REFCLK CHARACTERISTICS Input Voltage Range Input Low Voltage Input High Voltage Minimum Differential Input Drive Reference Frequency Required Accuracy LVTTL DC INPUT CHARACTERISTICS Input High Voltage Input Low Voltage Input High Current Input Low Current LVTTL DC OUTPUT CHARACTERISTICS Output High Voltage Output Low Voltage 1 Conditions Min Typ Max Unit VOD (see Figure 3) VOS (see Figure 3) Differential 240 1125 300 1200 100 400 1275 mV mV Ω 115 115 400 400 220 220 440 440 ps ps ps ps 0.3 VCC +10.0 0.4 V V μA V 20% to 80% 80% to 20% TS (see Figure 2), GbE TH (see Figure 2), GbE LVCMOS VIH VIL VIN = 0.1 VCC or VIN = 0.9 VCC VOL, IOL = 3.0 mA See Figure 10 360 360 0.7 VCC −10.0 400 tHIGH tLOW tHD;STA tSU;STA tSU;DAT tHD;DAT tR/tF tSU;STO tBUF Optional lock-to-REFCLK mode @ REFCLKP or REFCLKN VIL VIH 600 1300 600 600 100 300 20 + 0.1 Cb 1 600 1300 300 0 VCC 100 10 160 100 VIH VIL IIH, VIN = 2.4 V IIL, VIN = 0.4 V 2.0 VOH, IOH = −2.0 mA VOL, IOL = 2.0 mA 2.4 0.8 5 −5 Cb = total capacitance of one bus line in pF. If mixed with high speed mode devices, faster fall times are allowed. Rev. 0 | Page 4 of 16 0.4 kHz ns ns ns ns ns ns ns ns ns V V mV p-p MHz ppm V V μA μA V V ADN2805 Timing Characteristics CLKOUTP TH 07121-002 TS DATAOUTP/ DATAOUTN Figure 2. Output Timing DIFFERENTIAL CLKOUTP/N, DATAOUTP/N VOH VOS 07121-003 |VOD| VOL Figure 3. Differential Output Specifications 5mA RLOAD 100Ω 100Ω VDIFF SIMPLIFIED LVDS OUTPUT STAGE Figure 4. Differential Output Stage Rev. 0 | Page 5 of 16 07121-004 5mA ADN2805 ABSOLUTE MAXIMUM RATINGS THERMAL CHARACTERISTICS TA = TMIN to TMAX, VCC = VMIN to VMAX, VEE = 0 V, CF = 0.47 μF, SLICEP = SLICEN = VEE, unless otherwise noted. Thermal Resistance 4-layer board with exposed paddle soldered to VEE. Table 4. Parameter Supply Voltage (VCC) Minimum Input Voltage (All Inputs) Maximum Input Voltage (All Inputs) Maximum Junction Temperature Storage Temperature Range Rating 4.2 V VEE − 0.4 V VCC + 0.4 V 125°C −65°C to +150°C Table 5. Thermal Resistance Package Type 32-Lead LFCSP ESD CAUTION Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Rev. 0 | Page 6 of 16 θJA 28 Unit °C/W ADN2805 32 TEST2 31 VCC 30 VEE 29 DATAOUTP 28 DATAOUTN 27 SQUELCH 26 CLKOUTP 25 CLKOUTN PIN CONFIGURATION AND FUNCTION DESCRIPTIONS PIN 1 INDIC ATOR ADN2805* TOP VIEW (Not to Scale) 24 VCC 23 VEE 22 NC 21 SDA 20 SCK 19 SADDR5 18 VCC 17 VEE * THERE IS AN EXPOSED PAD ON THE BOTTOM OF THE PACKAGE THAT MUST BE CONNECTED TO GND. 07121-005 NC 9 REFCLKP 10 REFCLKN 11 VCC 12 VEE 13 CF2 14 CF1 15 LOL 16 TEST1 1 VCC 2 VREF 3 NIN 4 PIN 5 NC 6 NC 7 VEE 8 Figure 5. Pin Configuration Table 6. Pin Function Descriptions Pin No. 1 2 3 4 5 6, 7, 9, 22 8 10 11 12 13 14 15 16 17 18 19 20 21 23 24 25 26 27 28 29 30 31 32 Exposed Pad 1 Mnemonic TEST1 VCC VREF NIN PIN NC VEE REFCLKP REFCLKN VCC VEE CF2 CF1 LOL VEE VCC SADDR5 SCK SDA VEE VCC CLKOUTN CLKOUTP SQUELCH DATAOUTN DATAOUTP VEE VCC TEST2 Pad Type 1 P AO AI AI P DI DI P P AO AO DO P P DI DI DI P P DO DO DI DO DO P P P Description Connect to VCC. Power for Limiting Amplifier, LOS. Internal VREF Voltage. Decouple to GND with a 0.1 μF capacitor. Differential Data Input. CML. Differential Data Input. CML. No Connect. GND for Limiting Amplifier, LOS. Differential REFCLK Input. 10 MHz to 160 MHz. Differential REFCLK Input. 10 MHz to 160 MHz. VCO Power. VCO GND. Frequency Loop Capacitor. Frequency Loop Capacitor. Loss-of-Lock Indicator. LVTTL active high. FLL Detector GND. FLL Detector Power. Slave Address Bit 5. I2C Clock Input. I2C Data Input. Output Buffer, I2C GND. Output Buffer, I2C Power. Differential Recovered Clock Output. LVDS. Differential Recovered Clock Output. LVDS. Disable Clock and Data Outputs. Active high. LVTTL. Differential Recovered Data Output. LVDS. Differential Recovered Data Output. LVDS. Phase Detector, Phase Shifter GND. Phase Detector, Phase Shifter Power. Connect to VCC. Connect to GND. Type: P = power, AI = analog input, AO = analog output, DI = digital input, DO = digital output. Rev. 0 | Page 7 of 16 ADN2805 I2C INTERFACE TIMING AND INTERNAL REGISTER DESCRIPTION R/W CTRL. SLAVE ADDRESS [6...0] A5 SET BY PIN 19 0 0 0 0 0 X 07121-006 1 MSB = 1 0 = WR 1 = RD S SLAVE ADDR, LSB = 0 (WR) A(S) SUB ADDR A(S) DATA A(S) DATA A(S) P 07121-007 Figure 6. Slave Address Configuration Figure 7. I2C Write Data Transfer SLAVE ADDR, LSB = 0 (WR) A(S) SUB ADDR S = START BIT A(S) = ACKNOWLEDGE BY SLAVE A(S) S SLAVE ADDR, LSB = 1 (RD) A(S) DATA A(M) DATA A(M) P P = STOP BIT A(M) = LACK OF ACKNOWLEDGE BY MASTER A(M) = ACKNOWLEDGE BY MASTER 07121-008 S Figure 8. I2C Read Data Transfer SDA SLAVE ADDRESS A6 SUB ADDRESS A5 A7 STOP BIT DATA A0 D7 D0 SCK S WR ACK ACK SLADDR[4...0] ACK SUB ADDR[6...1] DATA[6...1] Figure 9. I2C Data Transfer Timing tF tSU;DAT tHD;STA tBUF SDA tR tR tSU;STO tF tLOW tHIGH tHD;STA S tSU;STA tHD;DAT S Figure 10. I2C Port Timing Diagram Rev. 0 | Page 8 of 16 P S 07121-010 SCK P 07121-009 START BIT ADN2805 Table 7. Internal Register Map 1, 2 Reg. Name FREQ0 FREQ1 FREQ2 RATE MISC R/W R R R R R Address 0x0 0x1 0x2 0x3 0x4 D7 D6 D5 MSB MSB 0 MSB COARSE_RD[8] MSB X X X CTRLA CTRLB W W 0x8 0x9 CTRLC W 0x11 fREF Range Config Reset LOL MISC[4] 0 0 1 2 D4 D3 D2 D1 Coarse Data Rate Readback Static LOL Data Rate LOL Status Measure Complete Data Rate/DIV_fREF Ratio 0 System 0 Reset Reset MISC[2] 0 0 0 0 D0 LSB LSB LSB COARSE_RD[1] COARSE_RD[0] (LSB) X Measure Data Rate 0 Lock to Reference 0 Squelch Mode Output Boost All writeable registers default to 0x00. X = don’t care. Table 8. Miscellaneous Register, MISC1 D7 X 1 D6 X D5 X Static LOL D4 0 = waiting for next LOL 1 = static LOL until reset LOL Status D3 0 = locked 1 = acquiring Data Rate Measurement Complete D2 0 = measuring data rate 1 = measurement complete D1 X Coarse Rate Readback LSB D0 COARSE_RD[0] X = don’t care. Table 9. Control Register, CTRLA 1 fREF Range D7 0 0 1 1 1 D6 0 1 0 1 Data Rate/DIV_fREF Ratio D5 D4 D3 D2 0 0 0 0 1 0 0 0 1 2 0 0 1 0 4 n 2n 1 0 0 0 256 10 MHz to 20 MHz 20 MHz to 40 MHz 40 MHz to 80 MHz 80 MHz to 160 MHz Measure Data Rate D1 Set to 1 to measure data rate Lock to Reference D0 0 = lock to input data 1 = lock to reference clock Where DIV_fREF is the divided down reference referred to the 10 MHz to 20 MHz band. Table 10. Control Register, CTRLB Configure LOL D7 0 = LOL pin normal operation 1 = LOL pin is static LOL Reset MISC[4] D6 Write a 1 followed by 0 to reset MISC[4] System Reset D5 Write a 1 followed by 0 to reset ADN2805 D4 Set to 0 Reset MISC[2] D3 Write a 1 followed by 0 to reset MISC[2] D2 Set to 0 D1 Set to 0 D0 Set to 0 Table 11. Control Register, CTRLC D7 Set to 0 D6 Set to 0 D5 Set to 0 D4 Set to 0 D3 Set to 0 D2 Set to 0 Squelch Mode D1 0 = SQUELCH DATAOUT and CLKOUT 1 = SQUELCH DATAOUT or CLKOUT Rev. 0 | Page 9 of 16 Output Boost D0 0 = default output swing 1 = boost output swing ADN2805 THEORY OF OPERATION Another view of the circuit is that the phase shifter implements the zero required for frequency compensation of a second-order phase-locked loop, and this zero is placed in the feedback path and, thus, does not appear in the closed-loop transfer function. Jitter peaking in a conventional second-order phase-locked loop is caused by the presence of this zero in the closed-loop transfer function. Because this circuit has no zero in the closed-loop transfer, jitter peaking is minimized. The delay and phase loops together simultaneously provide wideband jitter accommodation and narrow-band jitter filtering. The linearized block diagram in Figure 11 shows that the jitter transfer function, Z(s)/X(s), is second-order low-pass, providing excellent filtering. Note that the jitter transfer has no zero, unlike an ordinary second-order phase-locked loop. This means that the main PLL has virtually zero jitter peaking (see Figure 12). This makes this circuit ideal for signal regenerator applications where jitter peaking in a cascade of regenerators can contribute to hazardous jitter accumulation. The error transfer, e(s)/X(s), has the same high-pass form as an ordinary phase-locked loop. This transfer function is free to be optimized to give excellent wideband jitter accommodation because the jitter transfer function, Z(s)/X(s), provides the narrow-band jitter filtering. INPUT DATA e(s) X(s) d/sc o/s 1/n Z(s) RECOVERED CLOCK d = PHASE DETECTOR GAIN o = VCO GAIN c = LOOP INTEGRATOR psh = PHASE SHIFTER GAIN n = DIVIDE RATIO JITTER TRANSFER FUNCTION Z(s) 1 = cn n psh X(s) s2 +s +1 do o TRACKING ERROR TRANSFER FUNCTION 07121-011 e(s) s2 = d psh do X(s) s2 + s + c cn Figure 11. ADN2805 PLL/DLL Architecture JITTER PEAKING IN ORDINARY PLL ADN2805 Z(s) X(s) o n psh d psh c FREQUENCY (kHz) 07121-012 The delay and phase loops together track the phase of the input data signal. For example, when the clock lags input data, the phase detector drives the VCO to a higher frequency and increases the delay through the phase shifter; both of these actions serve to reduce the phase error between the clock and data. The faster clock picks up phase, while simultaneously, the delayed data loses phase. Because the loop filter is an integrator, the static phase error is driven to zero. psh JITTER GAIN (dB) The ADN2805 is a delay- and phase-locked loop circuit for clock recovery and data retiming from an NRZ encoded data stream. The phase of the input data signal is tracked by two separate feedback loops that share a common control voltage. A high speed delay-locked loop path uses a voltage controlled phase shifter to track the high frequency components of input jitter. A separate phase control loop, comprised of the VCO, tracks the low frequency components of input jitter. The initial frequency of the VCO is set by yet a third loop, which compares the VCO frequency with the input data frequency and sets the coarse tuning voltage. The jitter tracking phase-locked loop (PLL) controls the VCO by the fine-tuning control. Figure 12. ADN2805 Jitter Response vs. Conventional PLL The delay and phase loops contribute to overall jitter accommodation. At low frequencies of input jitter on the data signal, the integrator in the loop filter provides high gain to track large jitter amplitudes with small phase error. In this case, the VCO is frequency modulated and jitter is tracked as in an ordinary phase-locked loop. The amount of low frequency jitter that can be tracked is a function of the VCO tuning range. A wider tuning range gives larger accommodation of low frequency jitter. The internal loop control voltage remains small for small phase errors; therefore, the phase shifter remains close to the center of its range and thus contributes little to the low frequency jitter accommodation. At medium jitter frequencies, the gain and tuning range of the VCO are not large enough to track input jitter. In this case, the VCO control voltage becomes large and saturates, and the VCO frequency dwells at either one extreme of its tuning range or at the other. The size of the VCO tuning range, therefore, has only a small effect on the jitter accommodation. As such, the delaylocked loop control voltage is larger, and, consequently, the phase shifter takes on the burden of tracking the input jitter. The phase shifter range, in UI, can be seen as a broad plateau on the jitter tolerance curve. The phase shifter has a minimum range of 2 UI at all data rates. Rev. 0 | Page 10 of 16 ADN2805 The gain of the loop integrator is small for high jitter frequencies; therefore, larger phase differences are needed to make the loop control voltage large enough to tune the range of the phase shifter. Large phase errors at high jitter frequencies cannot be tolerated. In this region, the gain of the integrator determines the jitter accommodation. Because the gain of the loop integrator declines linearly with frequency, jitter accommodation is lower with higher jitter frequency. At the highest frequencies, the loop gain is very small, and little tuning of the phase shifter can be expected. In this case, jitter accommodation is determined by the eye opening of the input data, the static phase error, and the residual loop jitter generation. The jitter accommodation is roughly 0.5 UI in this region. The corner frequency between the declining slope and the flat region is the closed loop bandwidth of the delay-locked loop, which is roughly 1.5 MHz at 1.25 Gbps. Rev. 0 | Page 11 of 16 ADN2805 FUNCTIONAL DESCRIPTION FREQUENCY ACQUISITION When LOL deasserts, the FLL turns off. The PLL/DLL pulls in the VCO frequency until the VCO frequency equals the data frequency. The frequency loop requires a single external capacitor between CF1 and CF2, Pin 15 and Pin 14. A 0.47 μF ± 20%, X7R ceramic chip capacitor with <10 nA leakage current is recommended. Calculate the leakage current of the capacitor by dividing the maximum voltage across the 0.47 μF capacitor, ~3 V, by the insulation resistance of the capacitor. The insulation resistance of the 0.47 μF capacitor should be greater than 300 MΩ. INPUT BUFFER The input buffer has differential inputs (PIN/NIN), which are internally terminated with 50 Ω to an on-chip voltage reference (VREF = 2.5 V typically). The minimum differential input level required to achieve a BER of 10−10 is 200 mV p-p. LOCK DETECTOR OPERATION The lock detector on the ADN2805 has three modes of operation: normal mode, REFCLK mode, and static LOL mode. Normal Mode In normal mode, the ADN2805 locks onto 1.25 Gbps NRZ data without the use of a reference clock as an acquisition aid. In this mode, the lock detector monitors the frequency difference between the VCO and the input data frequency, and deasserts the loss-of-lock signal, which appears on Pin 16 (LOL) when the VCO is within 250 ppm of the data frequency. This enables the DLL/PLL, which pulls the VCO frequency in the remaining amount and acquires phase lock. When locked, if the input frequency error exceeds 1000 ppm (0.1%), the loss-of-lock signal reasserts and control returns to the frequency loop, which begins a new frequency acquisition. The LOL pin remains asserted until the VCO locks onto a valid input data stream to within 250 ppm frequency error. This hysteresis is shown in Figure 13. LOL 1 –250 –1000 0 250 1000 fVCO ERROR (ppm) 07121-013 The ADN2805 acquires frequency from the data at 1.25 Gbps. The lock detector circuit compares the frequency of the VCO and the frequency of the incoming data. When these frequencies differ by more than 1000 ppm, LOL asserts. This initiates a frequency acquisition cycle. An on-chip frequency-locked loop (FLL) forces the frequency of the VCO to be approximately equal to the frequency of the incoming data. LOL is deasserted once the VCO frequency is within 250 ppm of the data frequency. Figure 13. Transfer Function of LOL LOL Detector Operation Using a Reference Clock In REFCLK mode, a reference clock is used as an acquisition aid to lock the ADN2805 VCO. Lock-to-reference mode is enabled by setting CTRLA[0] to 1. The user also needs to write to the CTRLA[7:6] and CTRLA[5:2] bits to set the reference frequency range and the divide ratio of the data rate with respect to the reference frequency. In this mode, the lock detector monitors the difference in frequency between the divided down VCO and the divided down reference clock. The loss-of-lock signal, which appears on Pin 16 (LOL), deasserts when the VCO is within 250 ppm of the desired frequency. This enables the DLL/ PLL, which pulls the VCO frequency in the remaining amount with respect to the input data and acquires phase lock. When locked, if the input frequency error exceeds 1000 ppm (0.1%), the loss-of-lock signal reasserts and control returns to the frequency loop, which reacquires with respect to the reference clock. The LOL pin remains asserted until the VCO frequency is within 250 ppm of the desired frequency. This hysteresis is shown in Figure 13. Static LOL Mode The ADN2805 implements a static LOL feature to indicate whether a loss-of-lock condition has ever occurred and remains asserted, even if the ADN2805 regains lock, until the static LOL bit is manually reset. The I2C register bit, MISC[4], is the static LOL bit. If there is ever an occurrence of a loss-of-lock condition, this bit internally asserts to Logic high. The MISC[4] bit remains high even after the ADN2805 has reacquired lock to a new data rate. This bit can be reset by writing a 1 followed by 0 to I2C Register Bit CTRLB[6]. When reset, the MISC[4] bit remains deasserted until another loss-of-lock condition occurs. Writing a 1 to I2C Register Bit CTRLB[7] causes the LOL pin, Pin 16, to become a static LOL indicator. In this mode, the LOL pin mirrors the contents of the MISC[4] bit and has the functionality described in the previous paragraph. The CTRLB[7] bit defaults to 0. In this mode, the LOL pin operates in the normal operating mode, that is, it asserts only when the ADN2805 is in acquisition mode and deasserts when the ADN2805 reacquires lock. Rev. 0 | Page 12 of 16 ADN2805 SQUELCH MODE Two squelch modes are available with the ADN2805. The SQUELCH DATAOUT and CLKOUT mode is selected when CTRLC[1] = 0 (default mode). In this mode, when the SQUELCH input, Pin 27, is driven to a TTL high state, both the clock and data outputs are set to the zero state to suppress downstream processing. If the squelch function is not required, tie Pin 27 to VEE. SQUELCH DATAOUT or CLKOUT mode is selected when CTRLC[1] is 1. In this mode, when the SQUELCH input is driven to a high state, the DATAOUTN/DATAOUTP pins are squelched. When the SQUELCH input is driven to a low state, the CLKOUT pins are squelched. This feature is especially useful in repeater applications, where the recovered clock may not be needed. SYSTEM RESET A frequency acquisition can be initiated by writing a 1 followed by a 0 to the I2C Register Bit CTRLB[5]. This initiates a new frequency acquisition while keeping the ADN2805 in the operating mode that it was previously programmed to in Register CTRL[A], Register CTRL[B], and Register CTRL[C]. I2C INTERFACE The ADN2805 supports a 2-wire, I2C-compatible, serial bus driving multiple peripherals. Two inputs, serial data (SDA) and serial clock (SCK), carry information between any devices connected to the bus. Each slave device is recognized by a unique address. The ADN2805 has two possible 7-bit slave addresses for both read and write operations. The MSB of the 7-bit slave address is factory programmed to 1. Bit 5 of the slave address is set by Pin 19, SADDR5. Slave Address Bits[4:0] are defaulted to all 0s. The slave address consists of the 7 MSBs of an 8-bit word. The LSB of the word either sets a read or write operation (see Figure 6). Logic 1 corresponds to a read operation whereas Logic 0 corresponds to a write operation. To control the device on the bus, the following protocol must be followed. First, the master initiates a data transfer by establishing a start condition, defined by a high-to-low transition on SDA while SCK remains high. This indicates that an address/data stream follows. All peripherals respond to the start condition and shift the next eight bits (the 7-bit address and the R/W bit). The bits are transferred from MSB to LSB. The peripheral that recognizes the transmitted address responds by pulling the data line low during the ninth clock pulse. This is known as an acknowledge bit. All other devices withdraw from the bus at this point and maintain an idle condition. The idle condition is where the device monitors the SDA and SCK lines waiting for the start condition and correct transmitted address. The R/W bit determines the direction of the data. Logic 0 on the LSB of the first byte means that the master writes information to the peripheral. Logic 1 on the LSB of the first byte means that the master reads information from the peripheral. The ADN2805 acts as a standard slave device on the bus. The data on the SDA pin is eight bits long, supporting the 7-bit addresses, plus the R/W bit. The ADN2805 has eight subaddresses to enable the user-accessible internal registers (see Table 7 through Table 11). It, therefore, interprets the first byte as the device address and the second byte as the starting subaddress. Auto-increment mode is supported, allowing data to be read from or written to the starting subaddress and each subsequent address without manually addressing the subsequent subaddress. A data transfer is always terminated by a stop condition. The user can also access any unique subaddress register on a one-by-one basis without updating all registers. Stop and start conditions can be detected at any stage of the data transfer. If these conditions assert out of sequence with normal read and write operations, they cause an immediate jump to the idle condition. During a given SCK high period, the user should issue one start condition, one stop condition, or a single stop condition followed by a single start condition. If an invalid subaddress is issued by the user, the ADN2805 does not issue an acknowledge and returns to the idle condition. If the user exceeds the highest subaddress while reading back in auto-increment mode, the highest subaddress register contents continue to be output until the master device issues a no-acknowledge. This indicates the end of a read. In a no-acknowledge condition, the SDATA line is not pulled low on the ninth pulse. See Figure 7 and Figure 8 for sample read and write data transfers and Figure 9 for a more detailed timing diagram. Rev. 0 | Page 13 of 16 ADN2805 APPLICATIONS INFORMATION PCB DESIGN GUIDELINES If connections to the supply and ground are made through vias, the use of multiple vias in parallel helps to reduce series inductance, especially on Pin 24, which supplies power to the high speed CLKOUTP/CLKOUTN and DATAOUTP/ DATAOUTN output buffers. Refer to Figure 14 for the recommended connections. Proper RF PCB design techniques must be used for optimal performance. Power Supply Connections and Ground Planes Use of one low impedance ground plane is recommended. To reduce series inductance, solder the VEE pins directly to the ground plane. If the ground plane is an internal plane and connections to the ground plane are made through vias, multiple vias can be used in parallel to reduce the series inductance, especially on Pin 23, which is the ground return for the output buffers. Connect the exposed pad to the ground plane using plugged vias to prevent solder from leaking through the vias during reflow. By using adjacent power supply and ground planes, excellent high frequency decoupling can be realized by using close spacing between the planes. This capacitance is given by CPLANE = 0.88ε r A/d (pF ) where: εr is the dielectric constant of the PCB material. A is the area of the overlap of power and ground planes (cm2). d is the separation between planes (mm). Use of a 22 μF electrolytic capacitor between VCC and VEE is recommended at the location where the 3.3 V supply enters the PCB. When using 0.1 μF and 1 nF ceramic chip capacitors, place them between the IC power supply VCC and VEE, as close as possible to the ADN2805 VCC pins. For FR-4, εr = 4.4 mm and 0.25 mm spacing, C ~15 pF/cm2. 50Ω TRANSMISSION LINES VCC DATAOUTP + 22µF 0.1µF DATAOUTN 1nF CLKOUTP TEST2 VCC VEE DATAOUTP DATAOUTN SQUELCH CLKOUTP CLKOUTN CLKOUTN 0.1µF 50Ω 32 31 30 29 28 27 26 25 REFCLKP REFCLKN NC VCC VEE CF2 CF1 LOL OPTICAL TRANSCEIVER MODULE 24 EXPOSED PAD 23 TIED OFF TO 22 VEE PLANE 21 20 WITH VIAS 19 18 17 0.1µF I2C CONTROLLER I2C CONTROLLER VCC 0.1µF µC NC 50Ω 1nF VCC VEE NC SDA SCK SADDR5 VCC VEE 1nF VCC 0.1µF 1nF 0.47µF ±20% >300MΩ INSULATION RESISTANCE Figure 14. Typical Applications Circuit Rev. 0 | Page 14 of 16 07121-014 1nF 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 0.1µF TEST1 VCC VREF NIN PIN NC NC VEE VCC ADN2805 VCC Use of 50 Ω transmission lines is required for all high frequency input and output signals to minimize reflections: PIN, NIN, CLKOUTP, CLKOUTN, DATAOUTP, and DATAOUTN (also REFCLKP and REFCLKN, if a high frequency reference clock is used, such as 155 MHz). It is also necessary for the PIN/NIN input traces to be matched in length, and the CLKOUTP/ CLKOUTN and DATAOUTP/DATAOUTN output traces to be matched in length to avoid skew between the differential traces. ADN2805 50Ω CIN PIN 50Ω CIN NIN TIA 50Ω 0.1µF VREF 50Ω 3kΩ 2.5V 07121-015 Transmission Lines Figure 15. AC-Coupled Input Configuration The high speed inputs, PIN and NIN, are internally terminated with 50 Ω to an internal reference voltage (see Figure 15). A 0.1 μF is recommended between VREF, Pin 3, and GND to provide an ac ground for the inputs. Soldering Guidelines for Lead Frame Chip Scale Package The lands on the 32-lead LFCSP are rectangular. The printed circuit board (PCB) pad for these should be 0.1 mm longer than the package land length and 0.05 mm wider than the package land width. The land should be centered on the pad. This ensures that the solder joint size is maximized. The bottom of the chip scale package has a central exposed pad. The pad on the PCB should be at least as large as this exposed pad. The user must connect the exposed pad to VEE using plugged vias so that solder does not leak through the vias during reflow. This ensures a solid connection from the exposed pad to VEE. As with any high speed mixed-signal design, take care to keep all high speed digital traces away from sensitive analog nodes. VCC V1 CIN V2 ADN2805 PIN TIA V1b CIN V2b 50Ω NIN V1 1 2 COUT + 50Ω VREF DATAOUTP CDR BUFFER DATAOUTN COUT – 3 4 V1b V2 VREF V2b VTH VDIFF NOTES: 1. DURING DATA PATTERNS WITH HIGH TRANSITION DENSITY, DIFFERENTIAL DC VOLTAGE AT V1 AND V2 IS ZERO. 2. WHEN THE OUTPUT OF THE TIA GOES TO CID, V1 AND V1b ARE DRIVEN TO DIFFERENT DC LEVELS. V2 AND V2b DISCHARGE TO THE VREF LEVEL, WHICH EFFECTIVELY INTRODUCES A DIFFERENTIAL DC OFFSET ACROSS THE AC COUPLING CAPACITORS. 3. WHEN THE BURST OF DATA STARTS AGAIN, THE DIFFERENTIAL DC OFFSET ACROSS THE AC COUPLING CAPACITORS IS APPLIED TO THE INPUT LEVELS CAUSING A DC SHIFT IN THE DIFFERENTIAL INPUT. THIS SHIFT IS LARGE ENOUGH SUCH THAT ONE OF THE STATES, EITHER HIGH OR LOW DEPENDING ON THE LEVELS OF V1AND V1b WHEN THE TIA WENT TO CID, IS CANCELED OUT. THE QUANTIZER DOES NOT RECOGNIZE THIS AS A VALID STATE. 4. THE DC OFFSET SLOWLY DISCHARGES UNTIL THE DIFFERENTIAL INPUT VOLTAGE EXCEEDS THE SENSITIVITY OF THE ADN2805. THE QUANTIZER CAN RECOGNIZE BOTH HIGH AND LOW STATES AT THIS POINT. Figure 16. Example of Baseline Wander Rev. 0 | Page 15 of 16 07121-016 VDIFF = V2 – V2b VTH = ADN2805 QUANTIZER THRESHOLD ADN2805 OUTLINE DIMENSIONS 0.60 MAX 5.00 BSC SQ 0.60 MAX PIN 1 INDICATOR TOP VIEW 0.50 BSC 4.75 BSC SQ 0.50 0.40 0.30 32 1 3.25 3.10 SQ 2.95 EXPOSED PAD (BOTTOM VIEW) 17 16 9 8 0.25 MIN 3.50 REF 0.80 MAX 0.65 TYP 12° MAX 1.00 0.85 0.80 PIN 1 INDICATOR 25 24 0.05 MAX 0.02 NOM SEATING PLANE 0.30 0.23 0.18 0.20 REF COPLANARITY 0.08 COMPLIANT TO JEDEC STANDARDS MO-220-VHHD-2 Figure 17. 32-Lead Lead Frame Chip Scale Package [LFCSP_VQ] 5 mm × 5 mm Body, Very Thin Quad (CP-32-2) Dimensions shown in millimeters ORDERING GUIDE Model ADN2805ACPZ 1 ADN2805ACPZ-500RL71 ADN2805ACPZ-RL71 EVAL-ADN2805EBZ1 1 Temperature Range −40°C to +85°C −40°C to +85°C −40°C to +85°C Package Description 32-Lead LFCSP_VQ 32-Lead LFCSP_VQ, Tape-Reel, 500 pieces 32-Lead LFCSP_VQ, Tape-Reel, 1,500 pieces Evaluation Board Package Option CP-32-2 CP-32-2 CP-32-2 Z = RoHS Compliant Part. Purchase of licensed I2C components of Analog Devices or one of its sublicensed Associated Companies conveys a license for the purchaser under the Philips I2C Patent Rights to use these components in an I2C system, provided that the system conforms to the I2C Standard Specification as defined by Philips. ©2008 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D07121-0-1/08(0) Rev. 0 | Page 16 of 16