Dual, 16-Bit, 1600 MSPS, TxDAC+ Digital-to-Analog Converter AD9142 Data Sheet FEATURES GENERAL DESCRIPTION Very small inherent latency variation: <2 DAC clock cycles Proprietary low spurious and distortion design 6-carrier GSM ACLR = 79 dBc at 200 MHz IF SFDR > 85 dBc (bandwidth = 300 MHz) at ZIF Flexible 16-bit LVDS interface Supports word and byte load Multiple chip synchronization Fixed latency and data generator latency compensation Selectable 2×, 4×, 8× interpolation filter Low power architecture fS/4 power saving coarse mixer Input signal power detection Emergency stop for downstream analog circuitry protection FIFO error detection On-chip numeric control oscillator allows carrier placement anywhere in the DAC Nyquist bandwidth Transmit enable function for extra power saving High performance, low noise PLL clock multiplier Digital gain and phase adjustment for sideband suppression Digital inverse sinc filter Supports single DAC mode Low power: 2.0 W at 1.6 GSPS, 1.7 W at 1.25 GSPS, full operating conditions 72-lead LFCSP The AD9142 is a dual, 16-bit, high dynamic range digital-toanalog converter (DAC) that provides a sample rate of 1600 MSPS, permitting a multicarrier generation up to the Nyquist frequency. The AD9142 TxDAC+® includes features optimized for direct conversion transmit applications, including complex digital modulation, input signal power detection, and gain, phase, and offset compensation. The DAC outputs are optimized to interface seamlessly with analog quadrature modulators, such as the ADL537x F-MOD series and the ADRF670x series from Analog Devices, Inc. A 3-wire serial port interface provides for the programming/readback of many internal parameters. Full-scale output current can be programmed over a range of 9 mA to 33 mA. The AD9142 is available in a 72-lead LFCSP. 1. 2. 3. 4. 5. APPLICATIONS Wireless communications: 3G/4G and MC-GSM base stations, wideband repeaters, software defined radios Wideband communications: point-to-point, LMDS/MMDS Transmit diversity/MIMO Instrumentation Automated test equipment Rev. 0 PRODUCT HIGHLIGHTS Advanced low spurious and distortion design techniques provide high quality synthesis of wideband signals from baseband to high intermediate frequencies. Very small inherent latency variation simplifies both software and hardware design in the system. It allows easy multichip synchronization for most applications. New low power architecture improves power efficiency (mW/MHz/channel) by 30%. Input signal power and FIFO error detection simplify designs for downstream analog circuitry protection. Programmable transmit enable function allows easy design balance between power consumption and wakeup time. Document Feedback Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 ©2012 Analog Devices, Inc. All rights reserved. Technical Support www.analog.com AD9142 Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 Input Signal Power Detection and Protection ........................ 30 Applications ....................................................................................... 1 Transmit Enable Function ......................................................... 31 General Description ......................................................................... 1 Digital Function Configuration ............................................... 31 Product Highlights ........................................................................... 1 Multidevice Synchronization and Fixed Latency ....................... 32 Revision History ............................................................................... 3 Very Small Inherent Latency Variation ................................... 32 Functional Block Diagram .............................................................. 4 Further Reducing the Latency Variation ................................. 32 Specifications..................................................................................... 5 Synchronization Implementation ............................................ 33 DC Specifications ......................................................................... 5 Synchronization Procedures ..................................................... 33 Digital Specifications ................................................................... 6 Interrupt Request Operation ........................................................ 34 DAC Latency Specifications ........................................................ 7 Interrupt Working Mechanism ................................................ 34 Latency Variation Specifications ................................................ 7 Interrupt Service Routine .......................................................... 34 AC Specifications.......................................................................... 7 Temperature Sensor ....................................................................... 35 Operating Speed Specifications .................................................. 8 DAC Input Clock Configurations ................................................ 36 Absolute Maximum Ratings ....................................................... 9 Driving the DACCLK and REFCLK Inputs ........................... 36 Thermal Resistance ...................................................................... 9 Direct Clocking .......................................................................... 36 ESD Caution .................................................................................. 9 Clock Multiplication .................................................................. 36 Pin Configuration and Function Descriptions ........................... 10 PLL Settings ................................................................................ 37 Typical Performance Characteristics ........................................... 12 Configuring the VCO Tuning Band ........................................ 37 Terminology .................................................................................... 17 Automatic VCO Band Select .................................................... 37 Serial Port Operation ..................................................................... 18 Manual VCO Band Select ......................................................... 37 Data Format ................................................................................ 18 Analog Outputs............................................................................... 38 Serial Port Pin Descriptions ...................................................... 18 Transmit DAC Operation.......................................................... 38 Serial Port Options ..................................................................... 18 Interfacing to Modulators ......................................................... 39 Data Interface .................................................................................. 20 Reducing LO Leakage and Unwanted Sidebands .................. 40 LVDS Input Data Ports .............................................................. 20 Example Start-Up Routine ............................................................ 41 Word Interface Mode ................................................................. 20 Device Configuration Register Map and Description ............... 42 Byte Interface Mode ................................................................... 20 SPI Configure Register .............................................................. 44 Data Interface Configuration Options .................................... 20 Power-Down Control Register ................................................. 44 Interface Delay Line ................................................................... 22 Interrupt Enable0 Register ........................................................ 44 FIFO Operation .............................................................................. 23 Interrupt Enable1 Register ........................................................ 44 Resetting the FIFO ..................................................................... 24 Interrupt Flag0 Register............................................................. 45 Serial Port Initiated FIFO Reset ............................................... 24 Interrupt Flag1 Register............................................................. 45 Frame Initiated FIFO Reset....................................................... 24 Interrupt Select0 Register .......................................................... 45 Digital Datapath.............................................................................. 26 Interrupt Select1 Register .......................................................... 46 Interpolation Filters ................................................................... 26 DAC Clock Receiver Control Register .................................... 46 Digital Modulation ..................................................................... 28 Ref Clock Receiver Control Register ....................................... 46 Datapath Configuration ............................................................ 29 PLL Control Register ................................................................. 47 Digital Quadrature Gain and Phase Adjustment ................... 29 PLL Control Register ................................................................. 47 DC Offset Adjustment ............................................................... 29 PLL Control Register ................................................................. 47 Inverse Sinc Filter ....................................................................... 30 PLL Status Register..................................................................... 48 Rev. 0 | Page 2 of 64 Data Sheet AD9142 PLL Status Register .....................................................................48 NCO_PHASE_OFFSET1 Register............................................ 55 IDAC FS Adjust LSB Register ....................................................48 IQ_PHASE_ADJ0 Register ........................................................ 55 IDAC FS Adjust MSB Register ..................................................48 IQ_PHASE_ADJ1 Register ........................................................ 55 QDAC FS Adjust LSB Register ..................................................48 IDAC_DC_OFFSET0 Register.................................................. 55 QDAC FS Adjust MSB Register ................................................49 IDAC_DC_OFFSET1 Register.................................................. 55 Die Temperature Sensor Control Register ...............................49 QDAC_DC_OFFSET0 Register ................................................ 55 Die Temperature LSB Register ..................................................49 QDAC_DC_OFFSET1 Register ................................................ 56 Die Temperature MSB Register .................................................49 IDAC_GAIN_ADJ Register....................................................... 56 Chip ID Register..........................................................................49 QDAC_GAIN_ADJ Register ..................................................... 56 Interrupt Configuation Register ...............................................50 Gain Step Control0 Register ...................................................... 56 Sync CTRL Register ....................................................................50 Gain Step Control1 Register ...................................................... 56 Frame Reset CTRL Register.......................................................50 TX Enable Control Register ...................................................... 57 FIFO Level Configuration Register ..........................................51 DAC Output Control Register .................................................. 57 FIFO Level Readback Register ..................................................51 Data Receiver Test Control Register......................................... 57 FIFO CTRL Register ...................................................................51 Data Receiver Test Control Register......................................... 57 Data Format Select Register.......................................................52 Device Configuration0 Register................................................ 58 Datapath Control Register .........................................................52 Version Register .......................................................................... 58 Interpolation Control Register ..................................................52 Device Configuration1 Register................................................ 58 Over Threshold CTRL0 Register ..............................................53 Device Configuration2 Register................................................ 58 Over Threshold CTRL1 Register ..............................................53 DAC Latency and System Skews ................................................... 59 Over Threshold CTRL2 Register ..............................................53 DAC Latency Variations............................................................. 59 Input Power Readback LSB Register ........................................53 FIFO Latency Variation.............................................................. 59 Input Power Readback MSB Register .......................................53 Clock Generation Latency Variation ........................................ 60 NCO Control Register ................................................................54 Correcting System Skews ........................................................... 60 NCO_FREQ_TUNING_WORD0 Register.............................54 Packaging and Ordering Information .......................................... 61 NCO_FREQ_TUNING_WORD1 Register.............................54 Outline Dimensions.................................................................... 61 NCO_FREQ_TUNING_WORD2 Register.............................54 Ordering Guide ........................................................................... 61 NCO_FREQ_TUNING_WORD3 Register.............................54 NCO_PHASE_OFFSET0 Register ............................................54 REVISION HISTORY 11/12—Revision 0: Initial Version Rev. 0 | Page 3 of 64 AD9142 Data Sheet FUNCTIONAL BLOCK DIAGRAM INPUT POWER DETECTION fDAC /4 MOD DAC 1 16-BIT IOUT1P IOUT1N DAC CLK 16 DAC 2 16-BIT IOUT2P GAIN 1 10 GAIN 2 IOUT2N DAC_CLK INTERP MODE CTRL3 INTERP MODE CTRL2 INTERP MODE CTRL1 FIFO CTRL INTERFACE CTRL FRAMEP/ FRAMEN 16 OVER-THRESHOLD PROTECTION FIFO 8-SAMPLE LVDS DATA RECEIVER D0P/D0N NCO HB3 2× HB2 2× HB1 2× DC OFFSET CONTROL COMPLEX MODULATION D15P/D15N GAIN AND PHSE CONTROL AD9142 INV SINC DCIP/DCIN 10 REF AND BIAS REFIO FSADJ INTERNAL CLOCK TIMING AND CONTROL LOGIC SERIAL INPUT/OUTPUT PORT POWER-ON RESET MULTICHIP SYNCHRONIZATION DAC_CLK CLOCK MULTIPLIER CLK RCVR DACCLKP DACCLKN REF RCVR REFP/SYNCP REFN/SYNCN 10930-001 RESET TXEN IRQ2 IRQ1 CS SCLK SYNC SDIO PROGRAMMING REGISTERS Figure 1. Rev. 0 | Page 4 of 64 Data Sheet AD9142 SPECIFICATIONS DC SPECIFICATIONS TMIN to TMAX, AVDD33 = 3.3 V, DVDD18 = 1.8 V, CVDD18 = 1.8 V, IOUTFS = 20 mA, maximum sample rate, unless otherwise noted. Table 1. Parameter RESOLUTION ACCURACY Differential Nonlinearity (DNL) Integral Nonlinearity (INL) MAIN DAC OUTPUTS Offset Error Gain Error Full-Scale Output Current Output Compliance Range Output Resistance Gain DAC Monotonicity Settling Time to Within ±0.5 LSB MAIN DAC TEMPERATURE DRIFT Offset Gain Reference Voltage REFERENCE Internal Reference Voltage Output Resistance ANALOG SUPPLY VOLTAGES AVDD33 CVDD18 DIGITAL SUPPLY VOLTAGES DVDD18 POWER CONSUMPTION 2× Mode NCO OFF NCO ON 4× Mode NCO OFF NCO ON 4× Mode NCO OFF NCO ON 8× Mode NCO OFF NCO ON Phase-Lock Loop Inverse Sinc Reduced Power Mode (Power Down) AVDD33 CVDD18 DVDD18 OPERATING RANGE Test Conditions/Comments Min Typ 16 Max ±2.1 ±3.7 With internal reference Based on a 10 kΩ external resistor between FSADJ and AVSS −0.001 −3.2 19.06 −1.0 0 2 19.8 Unit Bits LSB LSB +0.001 4.7 +20.6 +1.0 % FSR % FSR mA V MΩ 10 Guaranteed 20 ns 0.04 100 30 ppm/°C ppm/°C ppm/°C 1.17 1.19 V kΩ 5 3.13 1.71 3.3 1.8 3.47 1.89 V V 1.71 1.8 1.89 V fDAC = 491.52 MSPS 700 870 mW mW 836 1085 mW mW 1030 1365 mW mW 1315 1815 70 113 mW mW mW mW mW mA mA mA °C fDAC = 737.28 MSPS fDAC = 983.04 MSPS fDAC = 1600 MSPS fDAC = 1474.56 MSPS −40 Rev. 0 | Page 5 of 64 +25 96.6 1.5 42.3 8.6 +85 AD9142 Data Sheet DIGITAL SPECIFICATIONS TMIN to TMAX, AVDD33 = 3.3 V, DVDD18 = 1.8 V, CVDD18 = 1.8 V, IOUTFS = 20 mA, maximum sample rate, unless otherwise noted. Table 2. Parameter CMOS INPUT LOGIC LEVEL Input Logic High Logic Low CMOS OUTPUT LOGIC LEVEL Output Logic High Logic Low LVDS RECEIVER INPUTS Input Voltage Range Input Differential Threshold Symbol Input Differential Hysteresis Receiver Differential Input Impedance DAC UPDATE RATE DAC Adjusted Update Rate DAC CLOCK INPUT (DACCLKP, DACCLKN) Differential Peak-to-Peak Voltage Common-Mode Voltage REFCLK/SYNCCLK INPUT (REFP/SYNCP, REFN/SYNCN) Differential Peak-to-Peak Voltage Common-Mode Voltage Input Clock Frequency SERIAL PORT INTERFACE Maximum Clock Rate Minimum Pulse Width High Low Setup Time Hold Time Setup Time VIDTHH to VIDTHL RIN VIA or VIB VIDTH Test Conditions/Comments Min DVDD18 = 1.8 V DVDD18 = 1.8 V 1.2 DVDD18 = 1.8 V DVDD18 = 1.8 V 1.4 Data and FRAME inputs DCI input Typ 825 −100 −225 Unit 0.6 V V 0.4 V V 1675 +100 +225 20 120 1600 250 2× interpolation 500 1.25 2000 mV V 100 500 1.25 2000 mV V MHz 1 GHz ≤ fVCO ≤ 2.1 GHz SCLK 450 40 MHz 12.5 12.5 SDIO to SCLK SDIO to SCLK CS to SCLK Rev. 0 | Page 6 of 64 mV mV mV mV Ω MSPS MSPS 100 Self biased input, ac-coupled tPWH tPWL tDS tDH tDCSB Max 1.5 0.68 2.38 1.4 ns ns ns ns ns Data Sheet AD9142 DAC LATENCY SPECIFICATIONS TMIN to TMAX, AVDD33 = 3.3 V, DVDD18 = 1.8 V, CVDD18 = 1.8 V, IOUTFS = 20 mA, FIFO level is set to 4 (half of the FIFO depth), unless otherwise noted. Table 3. Parameter WORD INTERFACE MODE 2× Interpolation 4× Interpolation 8× Interpolation BYTE INTERFACE MODE 2× Interpolation 4× Interpolation 8× Interpolation INDIVIDUAL FUNCTION BLOCKS Modulation Fine Coarse Inverse Sinc Phase Compensation Gain Compensation Test Conditions/Comments Fine/coarse modulation, inverse sinc, gain/phase compensation off Min Typ Max Unit 134 244 481 DACCLK cycles DACCLK cycles DACCLK cycles 145 271 506 DACCLK cycles DACCLK cycles DACCLK cycles 17 10 20 12 16 DACCLK cycles DACCLK cycles DACCLK cycles DACCLK cycles DACCLK cycles Fine/coarse modulation, inverse sinc, gain/phase compensation off LATENCY VARIATION SPECIFICATIONS 1 Table 4. Parameter DAC LATENCY VARIATION SYNC Off SYNC On 1 Min Typ Max Unit 2 1 DACCLK cycles DACCLK cycles DAC latency is defined as the elapsed time from a data sample clocked at the input to the AD9142 until the analog output begins to change. AC SPECIFICATIONS TMIN to TMAX, AVDD33 = 3.3 V, DVDD18 = 1.8 V, CVDD18 = 1.8 V, IOUTFS = 20 mA, maximum sample rate, unless otherwise noted. Table 5. Parameter SPURIOUS-FREE DYNAMIC RANGE (SFDR) fDAC = 737.28 MSPS BW = 125 MHz BW = 270 MHz fDAC = 983.04 MSPS BW = 360MHz fDAC = 1228.8 MSPS BW = 200MHz BW = 500MHz fDAC = 1474.56 MSPS BW = 737MHz BW = 400MHz TWO-TONE INTERMODULATION DISTORTION (IMD) fDAC = 737.28 MSPS fDAC = 983.04 MSPS fDAC = 1228.8 MSPS fDAC = 1474.56 MSPS Test Conditions/Comments −14 dBFS single tone fOUT = 200 MHz Min Typ Max Unit 85 80 dBc dBc 85 dBc 85 75 dBc dBc 85 80 dBc dBc 80 82 80 85 79 dBc dBc dBc dBc dBc fOUT = 200 MHz fOUT = 280 MHz fOUT = 10 MHz fOUT = 280 MHz −6 dBFS each tone fOUT = 200 MHz fOUT = 200 MHz fOUT = 280 MHz fOUT = 10 MHz fOUT = 280 MHz Rev. 0 | Page 7 of 64 AD9142 Data Sheet Parameter NOISE SPECTRAL DENSITY (NSD) fDAC = 737.28 MSPS fDAC = 983.04 MSPS fDAC = 1228.8 MSPS fDAC = 1474.56 MSPS W-CDMA ADJACENT CHANNEL LEAKAGE RATIO (ACLR) fDAC = 983.04 MSPS fDAC = 1228.8 MSPS fDAC = 1474.56 MSPS W-CDMA SECOND (ACLR) fDAC = 983.04 MSPS fDAC = 1228.8 MSPS fDAC = 1474.56 MSPS Test Conditions/Comments Eight-tone, 500 kHz tone spacing fOUT = 200 MHz fOUT = 200 MHz fOUT = 280 MHz fOUT = 10 MHz fOUT = 280 MHz Single carrier fOUT = 200 MHz fOUT = 20 MHz fOUT = 280 MHz fOUT = 20 MHz fOUT = 280 MHz Single carrier fOUT = 200 MHz fOUT = 20 MHz fOUT = 280 MHz fOUT = 20 MHz fOUT = 280 MHz Min Typ Max −160 −161.5 −164.5 −166 −162.5 dBm/Hz dBm/Hz dBm/Hz dBm/Hz dBm/Hz 81 83 80 81 80 dBc dBc dBc dBc dBc 85 86 86 86 85 dBc dBc dBc dBc dBc OPERATING SPEED SPECIFICATIONS Table 6. Interpolation Factor 2× 4× 8× DVDD18, CVDD18 = 1.8 V ± 5% fINTERFACE (Mbps) Max fDAC (Mbps) Max 250 500 250 1000 187.5 1500 DVDD18, CVDD18 = 1.8 V ± 2% or 1.9 V ± 5% fINTERFACE (Mbps) Max fDAC (Mbps) Max 250 500 250 1000 200 1600 Rev. 0 | Page 8 of 64 Unit Data Sheet AD9142 ABSOLUTE MAXIMUM RATINGS THERMAL RESISTANCE Table 7. Parameter AVDD33 to AVSS, EPAD, CVSS, DVSS DVDD18, CVDD18 to AVSS, EPAD, CVSS, DVSS AVSS to EPAD, CVSS, DVSS EPAD to AVSS, CVSS, DVSS CVSS to AVSS, EPAD, DVSS DVSS to AVSS, EPAD, CVSS FSADJ, REFIO, IOUT1P/IOUT1N, IOUT2P/IOUT2N to AVSS D[15:0]P/D[15:0]N, FRAMEP/FRAMEN, DCIP/DCIN to EPAD, DVSS DACCLKP/DACCLKN, REFP/SYNCP/REFN/SYNCN to CVSS RESET, IRQ1, IRQ2, CS, SCLK, SDIO to EPAD, DVSS Junction Temperature Storage Temperature Range The exposed pad (EPAD) must be soldered to the ground plane (AVSS) for the 72-lead LFCSP. The EPAD provides an electrical, thermal, and mechanical connection to the board. Rating −0.3 V to +3.6 V −0.3 V to +2.1 V −0.3 V to +0.3 V −0.3 V to +0.3 V −0.3 V to +0.3 V −0.3 V to +0.3 V −0.3 V to AVDD33 + 0.3 V −0.3 V to DVDD18 + 0.3 V Typical θJA, θJB, and θJC values are specified for a 4-layer board in still air. Airflow increases heat dissipation, effectively reducing θJA and θJB. Table 8. Thermal Resistance Package 72-Lead LFCSP −0.3 V to CVDD18 + 0.3 V −0.3 V to DVDD18 + 0.3 V ESD CAUTION 125°C −65°C to +150°C Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Rev. 0 | Page 9 of 64 θJA 20.7 θJB 10.9 θJC 1.1 Unit °C/W Conditions EPAD soldered to ground plane AD9142 Data Sheet 72 71 70 69 68 67 66 65 64 63 62 61 60 59 58 57 56 55 CVDD18 CVDD18 REFIO FSADJ AVDD33 IOUT1P IOUT1N AVDD33 CVDD18 CVDD18 DACCLKN DACCLKP CVDD18 CVDD18 AVDD33 IOUT2N IOUT2P AVDD33 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 AD9142 TOP VIEW (Not to Scale) 54 53 52 51 50 49 48 47 46 45 44 43 42 41 40 39 38 37 CS SCLK SDIO IRQ1 IRQ2 DVDD18 DVDD18 D0N D0P D1N D1P DVDD18 D2N D2P D3N D3P D4N D4P NOTES 1. EXPOSED PAD (EPAD) MUST BE SOLDERED TO THE GROUND PLANE (AVSS). THE EPAD PROVIDES AN ELECTRICAL, THERMAL, AND MECHANICAL CONNECTION TO THE BOARD. 2. EPAD IS THE GROUND CONNECTION FOR CVSS AND DVSS. 10930-002 DVDD18 D11P D11N D10P D10N D9P D9N D8P D8N DCIP DCIN D7P D7N D6P D6N D5P D5N DVDD18 19 20 21 22 23 24 25 26 27 28 29 30 31 32 33 34 35 36 CVDD18 REFP/SYNCP REFN/SYNCN CVDD18 RESET TXEN DVDD18 FRAMEP FRAMEN D15P D15N DVDD18 D14P D14N D13P D13N D12P D12N Figure 2. Pin Configuration Table 9. Pin Function Descriptions Pin No. 1 2 3 4 5 6 Mnemonic CVDD18 REFP/SYNCP REFN/SYNCN CVDD18 RESET TXEN 7 DVDD18 8 9 10 11 12 13 14 15 16 17 18 19 FRAMEP FRAMEN D15P D15N DVDD18 D14P D14N D13P D13N D12P D12N DVDD18 20 21 22 23 24 D11P D11N D10P D10N D9P Description 1.8 V PLL Supply. CVDD18 supplies the clock receivers, clock multiplier, and clock distribution. PLL Reference Clock Input, Positive. PLL Reference Clock Input, Negative. 1.8 V PLL Supply. CVDD18 supplies the clock receivers, clock multiplier, and clock distribution. Reset, Active Low. CMOS levels with respect to DVDD18. Recommended reset pulse length is 1 μs. Active High Transmit Path Enable. CMOS levels with respect to DVDD18. A low level on this pin triggers three selectable actions in the DAC. See Register 0x43 in Table 77 for details. 1.8 V Digital Supply. Pin 7 supplies power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Frame Input, Positive. Frame Input, Negative. Data Bit 15 (MSB), Positive. Data Bit 15 (MSB), Negative. 1.8 V Digital Supply. Pin 12 supplies the power to the digital core and digital data ports. Data Bit 14, Positive. Data Bit 14, Negative. Data Bit 13, Positive. Data Bit 13, Negative. Data Bit 12, Positive. Data Bit 12, Negative. 1.8 V Digital Supply. Pin 19 supplies power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Data Bit 11, Positive. Data Bit 11, Negative. Data Bit 10, Positive. Data Bit 10, Negative. Data Bit 9, Positive. Rev. 0 | Page 10 of 64 Data Sheet Pin No. 25 26 27 28 29 30 31 32 33 34 35 36 Mnemonic D9N D8P D8N DCIP DCIN D7P D7N D6P D6N D5P D5N DVDD18 37 38 39 40 41 42 43 D4P D4N D3P D3N D2P D2N DVDD18 44 45 46 47 48 D1P D1N D0P D0N DVDD18 49 DVDD18 50 51 52 53 54 55 56 57 58 59 60 61 62 63 64 65 66 67 68 69 70 71 72 IRQ2 IRQ1 SDIO SCLK CS AVDD33 IOUT2P IOUT2N AVDD33 CVDD18 CVDD18 DACCLKN DACCLKP CVDD18 CVDD18 AVDD33 IOUT1N IOUT1P AVDD33 FSADJ REFIO CVDD18 CVDD18 EPAD AD9142 Description Data Bit 9, Negative. Data Bit 8, Positive. Data Bit 8, Negative. Data Clock Input, Positive. Data Clock Input, Negative. Data Bit 7, Positive. Data Bit 7, Negative. Data Bit 6, Positive. Data Bit 6, Negative. Data Bit 5, Positive. Data Bit 5, Negative. 1.8 V Digital Supply. Pin 36 supplies power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Data Bit 4, Positive. Data Bit 4, Negative. Data Bit 3, Positive. Data Bit 3, Negative. Data Bit 2, Positive. Data Bit 2, Negative. 1.8 V Digital Supply. Pin 43 supplies power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Data Bit 1, Positive. Data Bit 1, Negative. Data Bit 0 (LSB), Positive. Data Bit 0 (LSB), Negative. 1.8 V Digital Supply. Pin 48 supplies power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. 1.8 V Digital Supply. Pin 49 supplies power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Second Interrupt Request. Open-drain, active low output. Connect an external pull-up to DVDD18 through a 10 kΩ resistor. First Interrupt Request. Open-drain, active low output. Connect an external pull-up to DVDD18 through a 10 kΩ resistor. Serial Port Data Input/Output. CMOS levels with respect to DVDD18. Serial Port Clock Input. CMOS levels with respect to DVDD18. Serial Port Chip Select. Active low (CMOS levels with respect to DVDD18). 3.3 V Analog Supply. QDAC Positive Current Output. QDAC Negative Current Output. 3.3 V Analog Supply. 1.8 V Clock Supply. Supplies clock receivers and clock distribution. 1.8 V Clock Supply. Supplies clock receivers and clock distribution. DAC Clock Input, Negative. DAC Clock Input, Positive. 1.8 V Clock Supply. Supplies clock receivers and clock distribution. 1.8 V Clock Supply. Supplies clock receivers and clock distribution. 3.3 V Analog Supply. IDAC Negative Current Output. IDAC Positive Current Output. 3.3 V Analog Supply. Full-Scale Current Output Adjust. Place a 10 kΩ resistor from this pin to AVSS. Voltage Reference. Nominally 1.2 V output. Decouple REFIO to AVSS. 1.8 V Clock Supply. Pin 71 supplies the clock receivers, clock multiplier, and clock distribution. 1.8 V Clock Supply. Pin 72 supplies the clock receivers, clock multiplier, and clock distribution. Exposed Pad. The exposed pad (EPAD) must be soldered to the ground plane (AVSS). The EPAD provides an electrical, thermal, and mechanical connection to the board. Rev. 0 | Page 11 of 64 AD9142 Data Sheet TYPICAL PERFORMANCE CHARACTERISTICS 0 –60 fDAC = 737.28MHz fDAC = 983.04MHz fDAC = 1228.8MHz fDAC = 1474.56MHz –10 –65 IN-BAND SFDR (dBc) –20 –30 SFDR (dBc) BW BW BW BW –40 –50 –60 = 80MHz, –6dBFS = 80MHz, –12dBFS = 300MHz, –6dBFS = 300MHz, –12dBFS –70 –75 –80 –70 –85 –80 100 200 300 400 500 600 700 800 fOUT (MHz) 10930-003 0 < –85 Figure 3. Single-Tone (0 dBFS) SFDR vs. fOUT in the First Nyquist Zone over fDAC 0 –60 IN-BAND SFDR (dBc) –40 –50 –60 –70 –80 100 120 140 160 180 200 = 80MHz, –6dBFS = 80MHz, –12dBFS = 300MHz, –6dBFS = 300MHz, –12dBFS –70 –75 –80 –85 0 100 200 300 400 500 600 700 800 fOUT (MHz) < –85 10930-005 –100 Figure 4. Single-Tone Second Harmonic vs. fOUT in the First Nyquist Zone over Digital Back Off, fDAC = 1474.56 MHz 0 –60 BW BW BW BW –65 IN-BAND SFDR (dBc) –30 –40 –50 –60 –70 150 200 250 300 Figure 7. Single-Tone SFDR (Excluding 2nd Harmonic) vs. fOUT in 80 MHz and 300 MHz BW, fDAC = 983.04 MHz 0dBFS –6dBFS –12dBFS –16dBFS –20 100 fOUT (MHz) 0 –10 50 10930-006 –85 MEANS ≤ –85 –90 THIRD HARMONIC (dBc) 80 –80 = 80MHz, –6dBFS = 80MHz, –12dBFS = 300MHz, –6dBFS = 300MHz, –12dBFS –70 –75 –80 –85 –85 MEANS ≤ –85 –90 0 100 200 300 400 fOUT (MHz) 500 600 700 800 < –85 10930-007 –100 Figure 5. Single-Tone Third Harmonic vs. fOUT in the First Nyquist Zone over Digital Back Off, fDAC = 1474.56 MHz 0 50 100 150 200 fOUT (MHz) 250 300 350 10930-008 SECOND HARMONIC (dBc) BW BW BW BW –65 –30 60 Figure 6. Single-Tone SFDR (Excluding 2nd Harmonic) vs. fOUT in 80 MHz and 300 MHz Bandwidths, fDAC = 737.28 MHz 0dBFS –6dBFS –12dBFS –16dBFS –20 40 fOUT (MHz) 0 –10 20 10930-004 –85 MEANS ≤ –85 –90 Figure 8. Single-Tone SFDR (Excluding 2nd Harmonic) vs. fOUT in 80 MHz and 300 MHz Bandwidths, fDAC = 1228.8 MHz Rev. 0 | Page 12 of 64 Data Sheet –60 BW BW BW BW 0 = 80MHz, –6dBFS = 80MHz, –12dBFS = 300MHz, –6dBFS = 300MHz, –12dBFS 0.6MHz TONE SPACING 16MHz TONE SPACING 35MHz TONE SPACING –20 –70 –40 IMD (dBc) IN-BAND SFDR (dBc) –65 AD9142 –75 –80 –60 –80 –85 –100 0 50 100 150 200 250 300 350 fOUT (MHz) –120 10930-009 < –85 0 –20 300 400 500 600 700 800 Figure 12. Two-Tone Third IMD vs. fOUT over Tone Spacing, fDAC = 1474.56 MHz –152 fDAC = 737.28MHz fDAC = 983.04MHz fDAC = 1228.8MHz fDAC = 1474.56MHz –10 200 fOUT (MHz) Figure 9. Single-Tone SFDR (Excluding 2nd Harmonic) vs. fOUT in 80 MHz and 300 MHz Bandwidths, fDAC = 1474.56 MHz 0 100 10930-010 –85 MEANS ≤ –85 fDAC = 737.28MHz fDAC = 983.04MHz fDAC = 1228.8MHz fDAC = 1474.56MHz –154 –156 NSD (dBm/Hz) IMD (dBc) –30 –40 –50 –158 –160 –162 –60 –164 –70 –166 –80 200 300 400 500 600 700 800 fOUT (MHz) –168 0 300 400 500 600 700 800 800 Figure 13. Single-Tone (0 dBFS) NSD vs. fOUT over fDAC –152 0dBFS –6dBFS –9dBFS –20 200 fOUT (MHz) Figure 10. Two-Tone Third IMD vs. fOUT over fDAC 0 100 10930-012 100 10930-014 0 10930-011 –90 0dBFS –6dBFS –12dBFS –16dBFS –154 –156 NSD (dBm/Hz) –60 –158 –160 –162 –80 –164 –100 –166 –120 0 100 200 300 400 500 600 700 800 fOUT (MHz) 10930-013 IMD (dBc) –40 –168 0 100 200 300 400 500 600 700 fOUT (MHz) Figure 14. Single-Tone NSD vs. fOUT over Digital Back Off, fDAC = 1474.56 MHz Figure 11. Two-Tone Third IMD vs. fOUT over Digital Back Off, fDAC = 1474.56 MHz Rev. 0 | Page 13 of 64 AD9142 –150 Data Sheet –60 737.2MHz 983.04MHz 1228.8MHz 1474.56MHz –152 –154 –65 –156 –70 –158 ACLR (dBc) NSD (dBm/Hz) fDAC = 1474.56MHz, PLL OFF, 0dBFS fDAC = 1474.56MHz, PLL ON, 0dBFS fDAC = 1228.8MHz, PLL OFF, 0dBFS fDAC = 1228.8MHz, PLL ON, 0dBFS –160 –162 –75 –80 –164 –166 –85 0 100 200 300 400 500 600 700 800 fOUT (MHz) –90 10930-200 –170 0 200 300 400 500 600 700 800 fOUT (MHz) Figure 18. 1C WCDMA 2nd Adjacent ACLR vs. fOUT, PLL On and Off Figure 15. 1C WCDMA NSD vs. fOUT, over fDAC –150 100 10930-101 –168 PLL OFF PLL ON –152 –154 NSD (dBm/Hz) –156 –158 –160 –162 –164 0 100 200 300 400 500 600 700 800 fOUT (MHz) 10930-016 –168 10930-015 –166 Figure 16. Single-Tone NSD vs. fOUT, fDAC = 1474.28 MHz, PLL On and Off –60 fDAC = 1474.56MHz, PLL OFF, 0dBFS fDAC = 1474.56MHz, PLL ON, 0dBFS fDAC = 1228.8MHz, PLL OFF, 0dBFS fDAC = 1228.8MHz, PLL ON, 0dBFS –65 –70 –75 –80 0 100 200 300 400 500 600 700 800 fOUT (MHz) Figure 17. 1C WCDMA 1st Adjacent ACLR vs. fOUT, PLL On and Off 10930-017 –85 10930-100 ACLR (dBc) Figure 19. Two-Tone Third IMD Performance, IF = 280 MHz, fDAC = 1474.28 MHz Figure 20. 1C WCDMA ACLR Performance, IF = 280 MHz, fDAC = 1474.28 MHz Rev. 0 | Page 14 of 64 Data Sheet AD9142 1.4 2× INTERPOLATION 4× INTERPOLATION 8× INTERPOLATION 1.2 POWER (W) 1.0 0.8 0.6 0.4 10930-018 0 0 200 400 600 800 1000 1200 1400 1600 1800 fDAC (MHz) Figure 21. Single-Tone fDAC = 1474.56 MHz, fOUT = 280 MHz, −14 dBFS 10930-021 0.2 Figure 24. Total Power Consumption vs. fDAC over Interpolation 450 2× INTERPOLATION 4× INTERPOLATION 8× INTERPOLATION 400 350 DVDD18 (mA) 300 250 200 150 100 50 200 400 600 800 1000 1200 1400 1600 1800 10930-024 0 1600 10930-022 10930-019 0 fDAC (MHz) Figure 22. 4C WCDMA ACLR Performance, IF = 280 MHz, fDAC = 1474.28 MHz Figure 25. DVDD18 Current vs. fDAC over Interpolation 0.30 NCO INV SINC DIG GAIN, PHASE, AND OFFSET 0.25 DVDD18 (mA) 0.20 0.15 0.10 0.05 10930-020 0 Figure 23. Single-Tone SFDR fDAC = 1474.56 MHz, 4× Interpolation, fOUT = 10 MHz, −14 dBFS 0 200 400 600 800 1000 1200 1400 fDAC (MHz) Figure 26. DVDD18 Current vs. fDAC over Digital Functions Rev. 0 | Page 15 of 64 AD9142 250 Data Sheet CVDD18 PLL OFF AVDD33 CVDD18 PLL ON 150 100 50 0 0 200 400 600 800 1000 1200 1400 fDAC (MHz) 1600 10930-023 SUPPLY CURRENT (mA) 200 Figure 27. CVDD18, AVDD33 Current vs. fDAC Rev. 0 | Page 16 of 64 Data Sheet AD9142 TERMINOLOGY Integral Nonlinearity (INL) INL is the maximum deviation of the actual analog output from the ideal output, determined by a straight line drawn from zero scale to full scale. Settling Time Settling time is the time required for the output to reach and remain within a specified error band around its final value, measured from the start of the output transition. Differential Nonlinearity (DNL) DNL is the measure of the variation in analog value, normalized to full scale, associated with a 1 LSB change in digital input code. Spurious Free Dynamic Range (SFDR) SFDR is the difference, in decibels, between the peak amplitude of the output signal and the peak spurious signal within the dc to Nyquist frequency of the DAC. Typically, the interpoloation filters reject energy in this band. This specification, therefore, defines how well the interpolation filters work and the effect of other parasitic coupling paths on the DAC output. Offset Error Offset error is the deviation of the output current from the ideal of 0 mA. For IOUT1P, 0 mA output is expected when all inputs are set to 0. For IOUT1N, 0 mA output is expected when all inputs are set to 1. Gain Error Gain error is the difference between the actual and ideal output span. The actual span is determined by the difference between the output when all inputs are set to 1 and the output when all inputs are set to 0. Output Compliance Range The output compliance range is the range of allowable voltage at the output of a current output DAC. Operation beyond the maximum compliance limits can cause either output stage saturation or breakdown, resulting in nonlinear performance. Temperature Drift Temperature drift is specified as the maximum change from the ambient (25°C) value to the value at either TMIN or TMAX. For offset and gain drift, the drift is reported in ppm of fullscale range (FSR) per degree Celsius. For reference drift, the drift is reported in ppm per degree Celsius. Power Supply Rejection (PSR) PSR is the maximum change in the full-scale output as the supplies are varied from minimum to maximum specified voltages. Signal-to-Noise Ratio (SNR) SNR is the ratio of the rms value of the measured output signal to the rms sum of all other spectral components below the Nyquist frequency, excluding the first six harmonics and dc. The value for SNR is expressed in decibels. Interpolation Filter If the digital inputs to the DAC are sampled at a multiple rate of fDATA (interpolation rate), a digital filter can be constructed that has a sharp transition band near fDATA/2. Images that typically appear around fDAC (output data rate) can be greatly suppressed. Adjacent Channel Leakage Ratio (ACLR) ACLR is the ratio in decibels relative to the carrier (dBc) between the measured power within a channel relative to its adjacent channel. Complex Image Rejection In a traditional two-part upconversion, two images are created around the second IF frequency. These images have the effect of wasting transmitter power and system bandwidth. By placing the real part of a second complex modulator in series with the first complex modulator, either the upper or lower frequency image near the second IF can be rejected. Rev. 0 | Page 17 of 64 AD9142 Data Sheet SERIAL PORT OPERATION 54 CS SPI PORT 53 SCLK 52 SDIO 10930-025 The serial port is a flexible, synchronous serial communications port that allows easy interfacing to many industry standard microcontrollers and microprocessors. The serial I/O is compatible with most synchronous transfer formats, including both the Motorola SPI and Intel® SSR protocols. The interface allows read/write access to all registers that configure the AD9142. MSB-first or LSB-first transfer formats are supported. The serial port interface is a 3-wire only interface. The input and output share a single pin input/output (SDIO). SERIAL PORT PIN DESCRIPTIONS Serial Clock (SCLK) The serial clock pin synchronizes data to and from the device and runs the internal state machines. The maximum frequency of SCLK is 40 MHz. All data input is registered on the rising edge of SCLK. All data is driven out on the falling edge of SCLK. Chip Select (CS) Figure 28. Serial Port Interface Pins There are two phases to a communication cycle with the AD9142. Phase 1 is the instruction cycle (the writing of an instruction byte into the device), coincident with the first 16 SCLK rising edges. The instruction word provides the serial port controller with information regarding the data transfer cycle, Phase 2, of the communication cycle. The Phase 1 instruction word defines whether the upcoming data transfer is a read or write, along with the starting register address for the following data transfer. A logic high on the CS pin, followed by a logic low, resets the serial port timing to the initial state of the instruction cycle. From this state, the next 16 rising SCLK edges represent the instruction bits of the current I/O operation. The remaining SCLK edges are for Phase 2 of the communication cycle. Phase 2 is the actual data transfer between the device and the system controller. Phase 2 of the communication cycle is a transfer of one data byte. Registers change immediately upon writing to the last bit of each transfer byte, except for the frequency tuning word and NCO phase offsets, which change only when the frequency tuning word (FTW) update bit is set. DATA FORMAT The instruction byte contains the information shown in Table 10. Table 10. Serial Port Instruction Word I15 (MSB) R/W A14 to A0 (Bit 14 to Bit 0 of the instruction word) determine the register that is accessed during the data transfer portion of the communication cycle. For multibyte transfers, A14 is the starting address; the device generates the remaining register addresses based on the SPI_LSB_FIRST bit. I[14:0] A[14:0] R/W (Bit 15 of the instruction word) determines whether a read or a write data transfer occurs after the instruction word write. Logic 1 indicates a read operation and Logic 0 indicates a write operation. CS is an active low input that starts and gates a communication cycle. It allows more than one device to be used on the same serial communications line. The SDIO pins enter a high impedance state when the CS input is high. During the communication cycle, CS should stay low. Serial Data I/O (SDIO) The SDIO pin is a bidirectional data line. SERIAL PORT OPTIONS The serial port can support both MSB-first and LSB-first data formats. This functionality is controlled by the SPI_LSB_FIRST bit (Register 0x00, Bit 6). The default is MSB first (LSB_FIRST = 0). When SPI_LSB_FIRST = 0 (MSB first), the instruction and data bits must be written from MSB to LSB. Multibyte data transfers in MSB-first format start with an instruction word that includes the register address of the most significant data byte. Subsequent data bytes must follow from high address to low address. In MSB-first mode, the serial port internal word address generator decrements for each data byte of the multibyte communication cycle. When SPI_LSB_FIRST = 1 (LSB first), the instruction and data bits must be written from LSB to MSB. Multibyte data transfers in LSB-first format start with an instruction word that includes the register address of the least significant data byte. Subsequent data bytes must follow from low address to high address. In LSB-first mode, the serial port internal word address generator increments for each data byte of the multibyte communication cycle. If the MSB-first mode is active, the serial port controller data address decrements from the data address written toward 0x00 for multibyte I/O operations. If the LSB-first mode is active, the serial port controller data address increments from the data address written toward 0xFF for multibyte I/O operations. Rev. 0 | Page 18 of 64 Data Sheet AD9142 tDCSB INSTRUCTION CYCLE tSCLK DATA TRANSFER CYCLE CS CS tPWH SCLK R/W A14 A13 A3 A2 A1 A0 D7N D6N D5N D30 D20 D10 D00 tDS SDIO Figure 29. Serial Register Interface Timing, MSB First INSTRUCTION CYCLE tDH INSTRUCTION BIT 15 INSTRUCTION BIT 14 10930-028 SCLK 10930-026 SDIO tPWL Figure 31. Timing Diagram for Serial Port Register Write CS DATA TRANSFER CYCLE CS A0 A1 A2 A12 A13 A14 R/W D00 D10 D20 D4N D5N D6N D7N 10930-027 SDIO tDV SDIO DATA BIT n DATA BIT n – 1 Figure 32. Timing Diagram for Serial Port Register Read Figure 30. Serial Register Interface Timing, LSB First Rev. 0 | Page 19 of 64 10930-029 SCLK SCLK AD9142 Data Sheet DATA INTERFACE LVDS INPUT DATA PORTS BYTE INTERFACE MODE The AD9142 has a 16-bit LVDS bus that accepts 16-bit I and Q data either in word wide (16-bit) or byte wide (8-bit) formats. In the word wide interface mode, the data is sent over the entire 16-bit data bus. In the byte wide interface mode, the data is sent over the lower 8-bit (D7 to D0) LVDS bus. Table 11 lists the pin assignment of the bus and the SPI register configuration for each mode. In byte mode, the required sequence of the input data stream is I[15:8], I[7:0], Q[15:8], Q[7:0]. A frame signal is required to align the order of input data bytes properly. Time align both the DCI signal and frame signal with the data. The rising edge of the frame indicates the start of the sequence. The frame can be either a one shot or periodical signal as long as its first rising edge is correctly captured by the device. For a one shot frame, the frame pulse needs to hold at high for at least one DCI cycle. For a periodical frame, the frequency needs to be Table 11. LVDS Data Input Modes Pin Assignment D15 to D0 D7 to D0 SPI Register Configuration Register 0x26, Bit 0 = 0 Register 0x26, Bit 0 = 1 fDCI/(2 × n) where n is a positive integer, that is, 1, 2, 3, … Figure 34 is an example of signal timing in byte mode. WORD INTERFACE MODE In word mode, the digital clock input (DCI) signal is a reference bit that generates a double data rate (DDR) data sampling clock. Time align the DCI signal with the data. The IDAC data follows the rising edge of the DCI, and the QDAC data follows the falling edge of the DCI, as shown in Figure 33. BYTE MODE INPUT DATA[7:0] Q0 I1 DCI Figure 33. Timing Diagram for Word Mode Q0[15:8] Q0[7:0] FRAME Figure 34. Timing Diagram for Byte Mode Q1 10930-030 I0 I0[7:0] DCI WORD MODE INPUT DATA[15:0] I0[15:8] 10930-031 Interface Mode Word Byte DATA INTERFACE CONFIGURATION OPTIONS To provide more flexibility for the data interface, some additional options are listed in Table 12. Table 12. Data Interface Configuration Options Register 0x26 Data Format (Bit 7) Data Pairing (Bit 6) Data Bus Invert (Bit 5) Rev. 0 | Page 20 of 64 Function Select between binary and twos complement formats. Indicate I/Q data pairing on data input. This allows the I and Q data that is received to be paired in various ways. Swaps the bit order of the data input port. Remaps the input data from D[15:0] to D[0:15]. Data Sheet AD9142 LVDS Input Level Requirements receiver requires a minimum of ±225 mV swing at its input. Figure 35 shows the LVDS input configuration and the required swing levels. Because the DCI is typically generated from the same bank as the data in the data source, it is recommended that the output swing of the LVDS driver be larger than the required DCI input level, thus meeting both input data and DCI requirements. There are two types of LVDS receivers in the AD9142. The 16-bit data bus and the frame input share the same LVDS receiver design. The DCI uses a different LVDS design. The main difference between the two LVDS receivers is the required input differential swing level. The data bus and frame receiver require a minimum of ±100 mV swing at the input. The DCI AD9142 + Dn 100Ω DATA RECEIVER TO INTERNAL DIGITAL – DnP DnN GND VCM = (VINP + VINN)/2 = 1.2V + DCI 100Ω DCI RECEIVER TO INTERNAL DIGITAL – DCIP DCIN AD9142 LVDS INPUT CONFIGURATION DCIP 1.32V DCIN 1.1V 1.25V 1.15V DnP DnN +225mV 0V DCI +100mV 0V –100mV Dn –225mV AD9142 DCI INPUT LVDS LEVEL AD9142 DATA AND FRAME INPUT LVDS LEVEL Figure 35. Data Interface Voltage Swing Requirements Rev. 0 | Page 21 of 64 10930-038 GND AD9142 Data Sheet INTERFACE DELAY LINE Interface Timing Requirements A four-tap delay line is provided for the user to adjust the timing between the data bus and the DCI. Table 13 specifies the setup and hold times for each delay tap. The following example illustrates how to calculate the optimal delay at the data source to achieve the best sampling timing in the delay line-based mode: There is a fixed 1.9 ns delay on the DCI when the delay line is enabled. Each tap adds a nominal delay of 300 ps to the fixed delay. To achieve the best timing margin, that is, to center the setup and hold window in the middle of the data eye, the user may need to add a delay on the data bus with respect to the DCI in the data source. Figure 36 is an example of calculating the optimal external delay. • • Table 13. Setup and Hold Times 1 0 0x00 0x0 −1.25 2.51 1.26 1 0x07 0x0 −1.50 2.82 1.32 2 0x7F 0x0 −1.70 3.23 1.53 3 0xFF 0x5 −1.93 3.64 1.71 The negative sign indicates the direction of the setup time. The setup time is defined as positive when it is on the left side of the clock edge and negative when it is on the right side of the clock edge. The shadow area in Figure 36 is the interface setup and hold time window set to 0. To optimize the interface timing, this window must be placed in the middle of the data transitions. Because the input is double data rate, the available data period is 2.5 ns. Therefore, the optimal data bus delay, with respect to the DCI at the data source, can be calculated as t DELAY = (| t S | + | t H |) 2 − t DATA PERIOD = 1.88 − 1.25 = 0.63 ns 2 SPI Sequence to Enable Delay Line-Based Mode It is recommended that the following SPI sequence be used to enable the delay line-based mode: 1. 2. 0x79 → 0x18 /* Configure Data Interface */ 0x5E → 0x00 /* Delay setting 0 */ 0x5F → 0x00 0x5F[3] → 1b /* Enable the delay line */ 3. tDELAY = 0.63ns tDATA PERIOD = 2.5ns INPUT DATA [15:0] WITH OPTIMIZED DELAY DATA EYE |tS| = 1.25ns |tH| = 2.51ns DCI = 200MHz NO DATA TRANSITION Figure 36. Example of Interfacing Timing in the Delay Line-Based Mode Rev. 0 | Page 22 of 64 10930-039 Delay Setting Register 0x5E[7:0] Register 0x5F[2:0] tS (ns)1 tH (ns) |tS + tH| (ns) fDCI = 200 MHz Delay setting = 0 Data Sheet AD9142 FIFO OPERATION As is shown in the Data Interface section, the AD9142 adopts source synchronous clocking in the data receiver. The nature of source synchronous clocking is the creation of a separate clock domain at the receiving device. In the DAC, it is the DAC clock domain, that is, the DACCLK. Therefore, there are two clock domains inside of the DAC: the DCI and the DACCLK. Often, these two clock domains are not synchronous, requiring an additional stage to adjust the timing for proper data transfer. In the AD9142, a FIFO stage is inserted between the DCI and DACCLK domains to transfer the received data into the core clock domain (DACCLK) of the DAC. is read from the FIFO register, which is determined by the read pointer, and fed into the digital datapath. The value of the read pointer is incremented every time data is read into the datapath from the FIFO. The FIFO pointers are incremented at the data rate, which is the DACCLK rate divided by the interpolation rate. The AD9142 contains a 2-channel, 16-bit wide, 8-word deep FIFO. The FIFO acts as a buffer that absorbs timing variations between the two clock domains. The timing budget between the two clock domains in the system is significantly relaxed due to the depth of the FIFO. Normally, data is written to and read from the FIFO at the same rate to maintain a constant FIFO depth. If data is written to the FIFO faster than data is read, the FIFO depth increases. If data is read from the FIFO faster than data is written to it, the FIFO depth decreases. For optimal timing margin, maintain the FIFO depth near half full (a difference of four between the write pointer and read pointer values). The FIFO depth represents the FIFO pipeline delay and is part of the overall latency of the AD9142. Figure 37 shows the block diagram of the datapath through the FIFO. The input data is latched into the device, formatted, and then written into the FIFO register, which is determined by the FIFO write pointer. The value of the write pointer is incremented every time a new word is loaded into the FIFO. Meanwhile, data Valid data is transmitted through the FIFO as long as the FIFO does not overflow (full) or underflow (empty). An overflow or underflow condition occurs when the write pointer and read pointer point to the same FIFO slot. This simultaneous access of data leads to unreliable data transfer through the FIFO and must be avoided. FIFO WRITE CLOCK FIFO READ CLOCK DACCLK ÷INT FIFO FIFO SLOT 0 FIFO SLOT 2 DATA RECEIVER INPUT DATA [15:0] FIFO SLOT 3 DATA FORMAT LATCHED DATA [15:0] I[15:0] I DATA PATH FIFO SLOT 1 RETIMED DCI DCI I[15:0] I DAC READ POINTER FIFO SLOT 4 I/Q[31:0] WRITE POINTER FIFO SLOT 5 FIFO SLOT 6 Q[15:0] Q[15:0] Q DATA PATH Q DAC FIFO SLOT 7 FRAME RESET LOGIC FIFO LEVEL FIFO LEVEL REQUEST REG 0x23 Figure 37. Block Diagram of FIFO Rev. 0 | Page 23 of 64 10930-040 SPI FIFO RESET REG 0x25[0] AD9142 Data Sheet RESETTING THE FIFO SERIAL PORT INITIATED FIFO RESET Upon power-on of the device, the read and write pointers start to roll around the FIFO from an arbitrary slot; consequently, the FIFO depth is unknown. To avoid a concurrent read and write to the same FIFO address and to assure a fixed pipeline delay from power-on to power-on, it is important to reset the FIFO pointers to a known state each time the device powers on or wakes up. This state is specified in the requested FIFO level (FIFO depth and FIFO level are used interchangeably in this document), which consists of two parts: the integral FIFO level and the fractional FIFO level. A SPI initiated FIFO reset is the most common method to reset the FIFO. To initialize the FIFO level through the serial port, toggle FIFO_SPI_RESET_REQUEST (Register 0x25[0]) from 0 to 1 and back to 0. When the write to this register is complete, the FIFO level is initialized to the requested FIFO level and the readback of FIFO_SPI_RESET_ACK (Register 0x25[1]) is set to 1. The FIFO level readback, in the same format as the FIFO level request, should be within ±1 DACCLK cycle of the requested level. For example, if the requested value is 0x40 in 4× interpolation, the readback value should be one of the following: 0x33, 0x40, or 0x41. The range of ±1 DACCLK cycle indicates the default DAC latency uncertainty from power-on to power-on without turning on synchronization. The integer FIFO level represents the difference of the states between the read and write point in the unit of input data period (1/fDATA). The fractional FIFO level represents the difference of the FIFO pointers smaller than the input data period. The resolution of the fractional FIFO level is the input data period divided by the interpolation ratio and, thus, it is equal to one DACCLK cycle. The exact FIFO level, that is, the FIFO latency, can be calculated by FIFO Latency = Integral Level + Fractional Level Because the FIFO has eight data slots, there are eight possible FIFO integral levels. The maximum supported interpolation rate in the AD9142 is 8× interpolation. Therefore, there are eight possible FIFO fractional levels. Two 3-bit registers in Register 0x23 are assigned to represent each level separately; Bits[6:4] represent the FIFO integral level and Bits[2:0] represent the FIFO fractional level. For example, if the interpolation rate is 4× and the desired total FIFO depth is 4.5 input data periods, set the FIFO_LEVEL_CONFIG (Register 0x23) to 0x42 (4 here means four data cycles and 2 means two DAC cycles, which is half of a data cycle). Note that there are only four possible fractional levels in the case of 4× interpolation. Table 14 shows additional examples of configuring the desired FIFO level in various interpolation rate modes. Table 14. Examples of FIFO Level Configuration Interpolation Rate 2× 4× 8× Example FIFO Level (1/fDATA) 3 + 1/2 4 + 1/4 4 + 3/8 Integer Level (Register 0x23[6:4]) 3 4 4 Fractional Level (Register 0x23[2:0]) 1 1 3 By default, the FIFO level is 4.0. It can be programmed to any allowed value from 0.0 to 7.x. The maximum allowed number for x is the interpolation rate minus 1. For example, in 8× interpolation, the maximum allowed for x is 7. The following two ways are used to reset the FIFO and initialize the FIFO level: • • Serial port (SPI) initiated FIFO reset. Frame initiated FIFO reset. The recommended procedure for a serial port FIFO reset is as follows: 1. 2. 3. 4. 5. 6. 7. 8. Configure the DAC in the desired interpolation mode (Register 0x28[1:0]). Ensure that the DACCLK and DCI are running and stable at the clock inputs. Program Register 0x23 to the customized value, if the desired value is not 0x40. Request the FIFO level reset by setting Register 0x25[0] to 1. Verify that the part acknowledges the request by setting Register 0x25[1] to 1. Remove the request by setting Register 0x25[0] to 0. Verify that the part drops the acknowledge signal by setting Register 0x25[1] to 0. Read back Register 0x24 multiple times to verify that the actual FIFO level is set to the requested level and that the readback values are stable. By design, the readback should be within ±1 DACCLK around the requested level. FRAME INITIATED FIFO RESET The frame input has two functions. One function is to indicate the beginning of a byte stream in the byte interface mode, as discussed in the Data Interface section. The other function is to initialize the FIFO level by asserting the frame signal high for at least the time interval required to load complete data to the I and QDACs. This corresponds to one DCI period in word mode and two DCI periods in byte mode. Note that this requirement of the frame pulse length is longer than that of the frame signal when it serves only to assemble the byte stream. The device accepts either a continuous frame or a one shot frame signal. In the continuous reset mode, the FIFO responds to every valid frame pulse and resets itself. In the one shot reset mode, the FIFO responds only to the first valid frame pulse after the FRAME_RESET_MODE bits (Register 0x22[1:0]) are set. Therefore, even with a continuous frame input, the FIFO resets one time only; this prevents the FIFO from toggling between the two states from periodic resets. The one shot frame reset mode is the default and the recommended mode. Rev. 0 | Page 24 of 64 Data Sheet AD9142 The recommended procedure for a frame initiated FIFO reset is as follows: 1. 2. 3. 4. 5. 6. 7. 8. Configure the DAC in the desired interpolation mode (Register 0x28[1:0]). Ensure that the DACCLK and DCI are running and stable at the clock inputs. Program Register 0x23 to the customized value, if the desired value is not 0x40. Configure the FRAME_RESET_MODE bits (Register 0x22[1:0])to 00b. Choose whether continuous or one shot mode is desired by writing 0 or 1 to EN_CON_FRAME_RESET (Register 0x22[2]). Toggle the frame input from 0 to 1 and back to 0. The pulse width needs to be longer than the minimum requirement. a. If the frame input is a continuous clock, turn on the signal. Read back FRAME_RESET_ACK, Register 0x22[3], to verify that the reset is complete. Read back Register 0x24 multiple times to verify that the actual FIFO level is set to the requested level and the readback values are stable. By design, the readback should be within ±1 DACCLK around the requested level. Monitoring the FIFO Status The real-time FIFO status can be monitored from the SPI Register 0x24 and reflects the real-time FIFO depth after a FIFO reset. Without timing drifts in the system, this readback should not change from that which resulted from the FIFO reset. When there is a timing drift or other abnormal clocking situation, the FIFO level readback can change. However, as long as the FIFO does not overflow or underflow, there is no error in data transmission. Three status bits in Register 0x06, Bits[2:0], indicate if there are FIFO underflows, overflows, or similar situations. The status of the three bits can be latched and used to trigger hardware interrupts, IRQ1 and IRQ2. To enable latching and interrupts, configure the corresponding bits in Register 0x03 and Register 0x04. Rev. 0 | Page 25 of 64 AD9142 Data Sheet DIGITAL DATAPATH HB1 HB3 HB2 COARSE AND FINE MODULATION DIGITAL GAIN AND PHASE AND OFFSET ADJUSTMENT INV SINC 10930-041 INPUT POWER DETECTION AND PROTECTION Figure 38. Block Diagram of Digital Datapath The block diagram in Figure 38 shows the functionality of the digital datapath. The digital processing includes The interpolation filters accept I and Q data streams and process them as two independent data streams, whereas the quadrature modulator and phase adjustment block accepts I and Q data streams as a quadrature data stream. Therefore, quadrature input data is required when digital modulation and phase adjustment functions are used. –0.02 –0.04 –0.06 –0.10 0 0.05 0.10 0.15 0.20 0.25 0.30 0.35 0.40 0.45 FREQUENCY (Hz) 10930-042 –0.08 Figure 39. Pass-Band Detail of 2× Mode 10 INTERPOLATION FILTERS The AD9142 provides three interpolation modes (see Table 6). Each mode offers a different usable signal bandwidth in an operating mode. Which mode to select depends on the required signal bandwidth and the DAC update rate. Refer to Table 6 for the maximum speed and signal bandwidth of each interpolation mode. 0 –10 –20 MAGNITUDE (dB) The transmit path contains three interpolation filters. Each of the three interpolation filters provides a 2× increase in output data rate and a low-pass function. The half-band (HB) filters are cascaded to provide 4× or 8× interpolation ratios. The usable bandwidth is defined as the frequency band over which the filters have a pass-band ripple of less than ±0.001 dB and a stop band rejection of greater than 85 dB. 2× Interpolation Mode Figure 39 and Figure 40 show the pass-band and all-band filter response for 2× mode. Note that the transition from the transition band to the stop band is much sharper than the transition from the pass band to the transition band. Therefore, when the desired output signal moves out of the defined pass band, the signal image, which is supposed to be suppressed by the stop band, grows faster than the droop of the signal itself due to the degraded pass-band flatness. In cases where the degraded image rejection is acceptable or can be compensated by the analog low-pass filter at the DAC output, it is possible to let the output signal extend beyond the specified usable signal bandwidth. Rev. 0 | Page 26 of 64 –30 –40 –50 –60 –70 –80 –90 –100 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 FREQUENCY (Hz) Figure 40. All-Band Response of 2× Mode 1.8 2.0 10930-043 • • 0 An input power detection block Three half-band interpolation filters A quadrature modulator consisting of a fine resolution NCO and an fS/4 coarse modulation block An inverse sinc filter A gain and phase and offset adjustment block MAGNITUDE (dB) • • • 0.02 Data Sheet AD9142 4× Interpolation Mode 10 0 Figure 41 and Figure 42 show the pass-band and all-band filter responses for 4× mode. –10 –20 MAGNITUDE (dB) 0.02 –0.02 –30 –40 –50 –60 –70 –0.04 –80 –90 –0.06 –100 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 FREQUENCY (Hz) –0.08 1.8 2.0 10930-049 MAGNITUDE (dB) 0 0 0.05 0.10 0.15 0.20 0.25 0.30 0.35 0.40 0.45 FREQUENCY (Hz) 10930-046 Figure 44. All-Band Response of 8× Mode –0.10 Figure 41. Pass-Band Detail of 4× Mode 10 0 –10 MAGNITUDE (dB) –20 –30 –40 –50 –60 –70 –80 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 FREQUENCY (Hz) 10930-047 –90 –100 Figure 42. All-Band Response of 4× Mode 8× Interpolation Mode Figure 43 and Figure 44 show the pass-band and all-band filter responses for 8× mode. The maximum DAC update rate is 1.6 GHz, and the maximum input data rate that is supported in this mode is 200 MHz (1.6 GHz/8). 0.02 –0.02 –0.04 Lower Coefficient H(1) H(2) H(3) H(4) H(5) H(6) H(7) H(8) H(9) H(10) H(11) H(12) H(13) H(14) H(15) H(16) H(17) H(18) H(19) H(20) H(21) H(22) H(23) H(24) H(25) H(26) H(27) H(28) –0.06 –0.08 –0.10 0 0.05 0.10 0.15 0.20 0.25 0.30 0.35 0.40 FREQUENCY (Hz) 0.45 10930-048 MAGNITUDE (dB) 0 Table 15. Half-Band Filter 1 Coefficient Figure 43. Pass-Band Detail of 8× Mode Rev. 0 | Page 27 of 64 Upper Coefficient H(55) H(54) H(53) H(52) H(51) H(50) H(49) H(48) H(47) H(46) H(45) H(44) H(43) H(42) H(41) H(40) H(39) H(38) H(37) H(36) H(35) H(34) H(33) H(32) H(31) H(30) H(29) Integer Value −4 0 +13 0 −32 0 +69 0 −134 0 +239 0 −401 0 +642 0 −994 0 +1512 0 −2307 0 +3665 0 −6638 0 +20,754 +32,768 AD9142 Data Sheet Upper Coefficient H(23) H(22) H(21) H(20) H(19) H(18) H(17) H(16) H(15) H(14) H(13) Integer Value −2 0 +17 0 −75 0 +238 0 −660 0 +2530 +4096 Table 17. Half-Band Filter 3 Coefficient Lower Coefficient H(1) H(2) H(3) H(4) H(5) H(6) Upper Coefficient H(11) H(10) H(9) H(8) H(7) Integer Value +29 0 −214 0 +1209 +2048 FTW[31:0] ~ NCO PHASE[15:0] SINE Q DATA IN The NCO modulator mixes the carrier signal generated by the NCO with the I and Q signals. The NCO produces a quadrature carrier signal to translate the input signal to a new center frequency. A complex carrier signal is a pair of sinusoidal waveforms of the same frequency, offset 90 degrees from each other. The frequency of the complex carrier signal is set via NCO_FREQ_ TUNING_WORD[31:0] in Register 0x31 through Register 0x34. The NCO operating frequency, fNCO, is always equal to fDAC, the DACCLK frequency. The frequency of the complex carrier signal can be set from dc up to ±0.5 × fNCO. The frequency tuning word (FTW) is in twos complement format. It can be calculated as f DAC f ≤ f CARRIER ≤ DAC 2 2 − The AD9142 provides two modes to modulate the baseband quadrature signal to the desired DAC output frequency. FTW = Coarse (fS/4) modulation Fine (NCO) modulation f CARRIER f DAC FTW = (1 − fS/4 Modulation The fS/4 modulation is a convenient and low power modulation mode to translate the input baseband frequency to a fixed fS/4 IF frequency, fS being the DAC sampling rate. When modulation frequencies other than this frequency are required, the NCO modulation mode must be used. NCO Modulation The NCO modulation mode makes use of a numerically controlled oscillator (NCO), a phase shifter, and a complex modulator to provide a means for modulating the signal by a programmable carrier signal. A block diagram of the digital modulator is shown in Figure 45. The NCO modulation allows the DAC output signal to be placed anywhere in the output spectrum with very fine frequency resolution. Q DATA OUT Figure 45. NCO Modulator Block Diagram DIGITAL MODULATION • • COSINE 10930-050 Lower Coefficient H(1) H(2) H(3) H(4) H(5) H(6) H(7) H(8) H(9) H(10) H(11) H(12) I DATA OUT I DATA IN Table 16. Half-Band Filter 2 Coefficient ( )( f × 232 f CARRIER f DAC CARRIER ≥ 0) ) × (232 ) ( f CARRIER < 0 ) The generated quadrature carrier signal is mixed with the I and Q data. The quadrature products are then summed into the I and Q data paths, as shown in Figure 45. Updating the Frequency Tuning Word The frequency tuning word registers are not updated immediately upon writing, as are other configuration registers. Similar to FIFO reset, the NCO update can be triggered in two ways. • • Rev. 0 | Page 28 of 64 SPI initiated update Frame initiated update Data Sheet AD9142 SPI Initiated Update quadrature gain and phase adjust values optimizes image rejection in single sideband radios. In the SPI initiated update method, the user simply toggles Register 0x30[0] (NCO_SPI_UPDATE_REQ) after configuring the NCO settings. The NCO is updated on the rising edge (from 0 to 1) in this bit. Register 0x30[1] (NCO_SPI_UPDATE_ACK) goes high when the NCO is updated. A falling edge (from 1 to 0) in Register 0x30[0] clears Bit 1 of Register 0x30 and prepares the NCO for the next update operation. This update method is recommended when there is no requirement to align the DAC output from multiple devices because SPI writes to multiple devices are asynchronous. Ordinarily, the I and Q channels have the same gain or signal magnitude. The quadrature gain adjustment is used to balance the gain between the I and Q channels. The digital gain of the I and Q channels can be adjusted independently through two 6-bit registers, IDAC_GAIN_ADJ (Register 0x3F[5:0]) and QDAC_GAIN_ADJ (Register 0x40[5:0]). The range of the adjustment is [0, 2] or [−∞, 6 dB] with a step size of 2−5 (−30 dB). The default setting is 0x20, corresponding to a gain equal to 1 or 0 dB. Frame Initiated Update Quadrature Phase Adjustment When the DAC output from multiple devices needs to be well aligned with NCO turned on, the frame initiated update is recommended. In this method, the NCOs from multiple devices are updated at the same time upon the rising edge of the frame signal. To use this update method, the FRAME_RESET_MODE (Register 0x22[1:0]) needs to be set in NCO only or FIFO and NCO, depending on whether FIFO reset is needed at the same time. The second step is to ensure that the reset mode is in one shot mode (EN_CON_FRAME_RESET, Register 0x22[2] = 0). When this second step is completed, the NCO waits for a valid frame pulse and updates the FTW accordingly. The user can verify if the frame pulse is correctly received by reading Register 0x30[6] (NCO_FRAME_ UPDATE_ACK) wherein a 1 indicates a complete update operation. See the FIFO Operation section for information to generate a valid frame pulse. Under normal circumstances, I and Q channels have an angle of precisely 90 degrees between them. The quadrature phase adjustment is used to change the angle between the I and Q channels. IQ_PHASE_ADJ[12:0] (Register 0x37 and Register 0x38) provide an adjustment range of ±14 degrees with a resolution of 0.0035 degrees. If the original angle is precisely 90 degrees, setting IQ_PHASE_ADJ[12:0] to 0x0FFF adds approximately 14 degrees between I and QDAC outputs, creating an angle of 104 degrees between the channels. Likewise, if the original angle is precisely 90 degrees, setting IQ_PHASE_ADJ[12:0] to 0x1000 adds approximately −14 degrees between the I and QDAC outputs, creating an angle of 76 degrees between the channels. The application requirements of the input data rate The interpolation ratio The output signal center frequency The output signal bandwidth Given these four parameters, the first step in configuring the datapath is to verify that the device supports the desired input data rate, the DAC sampling rate, and the bandwidth requirements. After this verification, the modes of the interpolation filters can be chosen. If the output signal center frequency is different from the baseband input center frequency, additional frequency offset requirements are determined and applied with on-chip digital modulation. DIGITAL QUADRATURE GAIN AND PHASE ADJUSTMENT The digital quadrature gain and phase adjustment function enables compensation of the gain and phase imbalance of the I and Q paths caused by analog mismatches between DAC I/Q outputs, quadrature modulator I/Q baseband inputs, and DAC/modulator interface I/Q paths. The undesired imbalances cause unwanted sideband signal to appear at the quadrature modulator output with significant energy. Tuning the As shown in Figure 46, the DAC offset current varies as a function of the I/QDAC_DC_OFFSET values. Figure 46 shows the nominal current of the positive node of the DAC output, IOUTP, when the digital inputs are fixed at midscale (0x0000, twos complement data format) and the DAC offset value is swept from 0x0000 to 0xFFFF. Because IOUTP and IOUTN are complementary current outputs, the sum of IOUTP and IOUTN is always 20 mA. Rev. 0 | Page 29 of 64 20 0 15 5 10 10 5 15 0 0x0000 0x4000 0x8000 0xC000 20 0xFFFF DAC OFFSET VALUE Figure 46. DAC Output Currents vs. DAC Offset Value IOUTxN (mA) • • • • The dc value of the I datapath and the Q datapath can be controlled independently by adjusting the values in the two 16-bit registers, IDAC_DC_OFFSET, Bits[15:0] and QDAC_DC_OFFSET, Bits[15:0] (Register 0x3B through Register 0x3E). These values are added directly to the datapath values. Care should be taken not to overrange the transmitted values. 10930-051 Configuring the AD9142 datapath starts with the following four parameters: DC OFFSET ADJUSTMENT IOUTxP (mA) DATAPATH CONFIGURATION Quadrature Gain Adjustment AD9142 Data Sheet INVERSE SINC FILTER INPUT SIGNAL POWER DETECTION AND PROTECTION The AD9142 provides a digital inverse sinc filter to compensate for the DAC rolloff over frequency. The inverse sinc (sinc−1) filter is a seven tap FIR filter. Figure 47 shows the frequency response of sin(x)/x rolloff, the inverse sinc filter, and their composite response. The composite response has less than ±0.05 dB passband ripple up to a frequency of 0.4 × fDAC. The input signal power detection and protection function detects the average power of the DAC input signal and prevents overrange signals from being passed to the next stage. An overrange DAC output signal can cause destructive breakdown on power sensitive devices, such as power amplifiers. The power detection and protection feature of the AD9142 detects overrange signals in the DAC. When an overrange signal is detected, the protection function either attenuates or mutes the signal to protect the downstream devices from abnormal power surges in the signal. To provide the necessary peaking at the upper end of the pass band, the inverse sinc filter has an intrinsic insertion loss of about 3.8 dB. The loss of the digital gain can be offset by increasing the quadrature gain adjustment setting on both the I and Q data paths to minimize the impact on the output signal-to-noise ratio. However, care is needed to ensure that the additional digital gain does not cause signal saturation, especially at high output frequencies. The sinc−1 filter is disabled by default; it can be enabled by setting the INVSINC_ENABLE bit to 1 in Register 0x27[7]). Figure 48 shows the block diagram of the power detection and protection function. The protection block is at the very last stage of the data path and the detection block uses a separate path from the data path. The design of the detection block guarantees that the worst-case latency of power detecting is shorter than that of the data path. This ensures that the protection circuit initiates before the overrange signal reaches the analog DAC core. The sum of I2 and Q2 is calculated as a representation of the input signal power. Only the upper six MSBs, D[15:10], of data samples are used in the calculation; consequently, samples whose power is 36 dB below the fullscale peak power are not detected. The calculated sample power numbers accumulate through a moving average filter. Its output is the average of the input signal power in a certain number of data clock cycles. The length of the filter is configurable through the SAMPLE_WINDOW_LENGTH (Register 0x2B[3:0]). To determine whether the input average power is over range, the device averages the power of the samples in the filter and compares the average power with a user defined threshold, OVER_THRESHOLD_LEVEL[11:0] (Register 0x29 and Register 0x2A). When the output of the averaging filter is larger than the threshold, the DAC output is either attenuated or muted. 1 –1 –2 –3 –5 0 0.05 0.10 0.15 0.20 0.25 0.30 0.35 0.40 FREQUENCY (Hz) 0.45 0.50 10930-052 –4 Figure 47. Responses of sin(x)/x Roll Off (Blue), the Sinc−1 Filter (Red), and the Composite of Both (Black) Table 18. Inverse Sinc Filter Lower Coefficient H(1) H(2) H(3) H(4) Upper Coefficient H(7) H(6) H(5) The appropriate filter length and average power threshold for effective protection are application dependent. It is recommended that experiments be performed with real-world vectors to determine the values of these parameters. Integer Value −1 +4 −16 +192 POWER PROTECTION (ATTENUATE OR MUTE) SIGNAL PROCESSING ENGINE FIFO DAC CORE POWER DETECTION I2 + Q2 AVERAGING FILTER FILTER LENGTH SETTINGS REG 0x2B[3:0] AVE POWER REG 0x2C AND 0x2D[4:0] USER-DEFINED THRESHOLD REG 0x29 AND 0x2A[4:0] Figure 48. Block Diagram of Input Signal Power Detection and Protection Function Rev. 0 | Page 30 of 64 10930-053 MAGNITUDE (dB) 0 Data Sheet AD9142 TRANSMIT ENABLE FUNCTION DIGITAL FUNCTION CONFIGURATION The transmit enable (TXEN) function provides the user a hardware switch of the DAC output. The function accepts a CMOS signal via Pin 6 (TXEN). When this signal is detected high, the transmit path is enabled and the DAC transmits the data normally. When this signal is detected low, one of the three actions related to the DAC output is triggered. Each of the digital gain and phase adjust functions and the inverse sinc filter can be enabled and adjusted independently. The pipeline latencies these blocks add into the data path are different between enabled and disabled. If fixed DAC pipeline latency is desired during operation, leave these functions always on or always off after initial configuration. 1. The digital dc adjust function is always on. The default value is 0; that is, there is no additional dc offset. The pipeline latency that this block adds is a constant, no matter the value of the dc offset. 2. 3. The DAC output is gradually attenuated from full scale gain to 0. The attenuation step size is set in Register 0x42[5:0]. The DAC is put in sleep mode and the output current is turned off. Other parts of the DAC are still running in this mode. The DAC is put in power-down mode. In this mode, not only the DAC output current is turned off but the rest of the DAC is powered down. This minimizes the power consumption of the DAC when the data is not transmitting but it takes a bit longer than the first two modes to start to re-transmit data due to the device power-up time. There is also a latency difference between using and not using the input signal power detection and protection function. Therefore, to keep the overall latency fixed, leave this function always on or always off after the initial configuration. The TXEN function also provides a gain ramp-up function that lets the user turn on the DAC output gradually when the TXEN signal switches from low to high. The ramp-up gain step can be configured using Register 0x41[5:0]. Although all of these actions can be taken through SPI writes, TXEN provides a much faster way to turn on and off the DAC output. The response time of a SPI write command is dominated by the SPI port communication time. This feature is useful when the user must turn off the DAC very quickly. Rev. 0 | Page 31 of 64 AD9142 Data Sheet MULTIDEVICE SYNCHRONIZATION AND FIXED LATENCY A DAC introduces a variation of pipeline latency to a system. The latency variation causes the phase of a DAC output to vary from power-on to power-on. Therefore, the output from different DAC devices may not be perfectly aligned even with well aligned clocks and digital inputs. The skew between multiple DAC outputs varies from power-on to power-on. In applications such as transmit diversity or digital predistortion, where deterministic latency is desired, the variation of the pipeline latency must be minimized. Deterministic latency in this document is defined as a fixed time delay from the digital input to the analog output in a DAC from power-on to power-on. Multiple DAC devices are considered synchronized to each other when each DAC in this group has the same constant latency from power-on to power-on. Three conditions must be identical in all of the ready-to-sync devices before these devices are considered synchronized: • • • The phase of DAC internal clocks The FIFO level The alignment of the input data VERY SMALL INHERENT LATENCY VARIATION The innovative architecture of the AD9142 minimizes the inherent latency variation. The worst-case variation in the AD9142 is two DAC clock cycles. For example, in the case of a 1.5 GHz sample rate, the variation is less than 1.4 ns under any scenario. Therefore, without turning on the synchronization engine, the DAC outputs from multiple AD9142 devices are guaranteed to be aligned within two DAC clock cycles, regardless of the timing between the DCI and the DACCLK. No additional clocks are required to achieve this accuracy. The user must reset the FIFO in each DAC device through the SPI at start-up. Therefore, the AD9142 can decrease the complexity of system design in multi transmit channel applications. Note the alignment of the DCI signals in the design. The DCI is used as a reference in the AD9142 design to align the FIFO and the phase of internal clocks in multiple parts. The achieved DAC output alignment depends on how well the DCIs are aligned at the input of each device. The equation below is the expression of the worst-case DAC output alignment accuracy in the case of DCI mismatches. FURTHER REDUCING THE LATENCY VARIATION For applications that require finer synchronization accuracy (DAC latency variation < 2 DAC clock cycles), the AD9142 has a provision for enabling multiple devices to be synchronized to each other within a single DAC clock cycle. To further reduce the latency variation in the DAC, the synchronization machine needs to be turned on and two external clocks (frame and sync) need to be generated in the system and fed to all the DAC devices. Set Up and Hold Timing Requirement The sync clock (fSYNC) serves as a reference clock in the system to reset the clock generation circuitry in multiple AD9142 devices simultaneously. Inside the DAC, the sync clock is sampled by the DACCLK to generate a reference point for aligning the internal clocks, so there is a setup and hold timing requirement between the sync clock and the DAC clock. If the user adopts the continuous frame reset mode, that is, the FIFO and sync engine periodically reset, the timing requirements between the sync clock and the DAC clock must be met. Otherwise, the device can lose lock and corrupt the output. In the one shot frame reset mode, it is still recommended that this timing be met at the time when the sync routine is run because not meeting the timing can degrade the sync alignment accuracy by one DAC cycle, as shown in Table 19. For users who want to synchronize the device in a one-shot manner and continue to monitor the synchronization status, the AD9142 provides a sync monitoring mode. It provides a continuous sync and frame clock to synchronize the part once and ignore the clock cycles after the first valid frame pulse is detected. In this way, the user can monitor the sync status without periodically resynchronizing the device; to engage the sync monitoring mode, set Register 0x22[1:0] (FRAME_RESET_ MODE) to 11b. Table 19. Sync Clock and DAC Clock Setup and Hold Times Falling Edge Sync Timing (default) tS (ns) tH (ns) |tS + tH| (ns) tSK (OUT) = tSK (DCI) + 2/fDAC where: tSK (OUT) is the worst case skew between the DAC output from two AD9142 devices. tSK (DCI) is the skew between two DCIs at the DCI input of the two AD9142 devices. fDAC is the DACCLK frequency. The better the alignment of the DCIs, the smaller is the overall skew between two DAC outputs. Rev. 0 | Page 32 of 64 Max 246 −11 235 Unit ps ps ps Data Sheet AD9142 SYNCHRONIZATION IMPLEMENTATION Synchronization Procedure for PLL Off The AD9142 lets the user choose either the rising or falling edge of the DAC clock to sample the sync clock, which makes it easier to meet the timing requirements. The sync clock, fSYNC, should be 1/8 × fDATA or slower by a factor of 2n, n being an integer (1, 2, 3…). Note that there is a limit on how slow the sync clock can be because of the ac coupling nature of the sync clock receiver. Choose an appropriate value of the ac coupling capacitors to ensure that the signal swing meets the data sheet specification, as listed in Table 2. 1. The frame clock resets the FIFO in multiple AD9142 devices. The frame can be either a one shot or continuous clock. In either case, the pulse width of the frame must be longer than one DCI cycle in the word mode and two DCI cycles in the byte mode. When the frame is a continuous clock, fFRAME should be at 1/8 × fDATA or slower by a factor of 2n, n being an integer (1, 2, 3…). Table 20 lists the requirements of the frame clock in various conditions. Table 20. Frame Clock Speed and Pulse Width Requirement Sync Clock One Shot Continuous 1 Maximum Speed N/A1 fDATA/8 Minimum Pulse Width For both one shot and continuous sync clocks, word mode = one DCI cycle and byte mode = two DCI cycles. N/A means not applicable. 2. 3. 4. 5. 6. 7. 8. Synchronization Procedure for PLL On Note that, because the sync clock and PLL reference clock share the same clock and the maximum sync clock rate is fDATA/8, the same limit also applies to the reference clock. Therefore, only 2× interpolation is supported for synchronization with PLL on. 1. SYNCHRONIZATION PROCEDURES When the sync accuracy of an application is looser than two DAC clock cycles, it is recommended to turn off the synchronization machine because there are no additional steps required, other than the regular start-up procedure sequence. For applications that require finer than two-DAC clock cycle sync accuracy, it is recommended that the procedure in the Synchronization Procedure for PLL Off or Synchronization Procedure for PLL On sections be followed to set up the system and configure the device. For more information about the details of the synchronization scheme in the AD9142 and using the synchronization function to correct system skews and drifts, see the DAC Latency and System Skews section. Configure the DAC interpolation mode and, if NCO is used, configure the NCO FTW. Set up the DAC data interface according to the procedure outlined in the Data Interface section and verify that the DLL is locked. Choose the appropriate mode in FRAME_RESET_MODE. a. If NCO is not used, choose FIFO only mode. b. If NCO is used, it must be synchronized. FIFO and NCO mode can then be used. Configure Bit 2 in Register 0x22 for continuous or one shot reset mode. One shot reset mode is recommended. Ensure that the DACCLK, DCI, and sync clock to all of the AD9142 devices are running and stable. Enable the sync engine by writing 1 to Register 0x21[0]. Send a valid frame pulse(s) to all of the AD9142 devices. Verify that the frame pulse is received by each device by reading back Register 0x22[3]. All the readback values are 1. At this point, the devices should be synchronized. 2. 3. 4. 5. 6. 7. 8. 9. Rev. 0 | Page 33 of 64 Set up the PLL according to the procedure in the Clock Multiplication section and ensure that the PLL is locked. Configure the DAC interpolation mode and, if NCO is used, configure the NCO FTW. Set up the DAC data interface according to the procedure in the Data Interface section and verify that the DLL is locked. Choose the appropriate mode in FRAME_RESET_MODE. a. If NCO is not used, choose the FIFO only mode. b. If NCO is used, it must be synchronized. FIFO and NCO mode can then be used. Configure Bit 2 in Register 0x22 for continuous or one shot reset mode. One shot reset mode is recommended. Ensure that DACCLK, DCI, and sync clock to all of the AD9142 devices are running. Enable the sync engine by writing 1 to Register 0x21[0]. Send a valid frame pulse(s) to all of the AD9142 devices. Verify that the frame pulse is received by each device by reading back Register 0x22[3]. All the readback values are 1. At this point, the devices should be synchronized. AD9142 Data Sheet INTERRUPT REQUEST OPERATION method is by writing 1 to the corresponding event flag bit. The second method is to use a hardware or software reset to clear the INTERRUPT_SOURCE signal. The AD9142 provides an interrupt request output signal on Pin 50 and Pin 51 (IRQ2 and IRQ1, respectively) that can be used to notify an external host processor of significant device events. Upon assertion of the interrupt, query the device to determine the precise event that occurred. The IRQ1 pin is an open-drain, active low output. Pull the IRQ1 pin high external to the device. This pin can be tied to the interrupt pins of other devices with open-drain outputs to wire-OR these pins together. The IRQ2 circuitry works in the same way as the IRQ1 circuitry. Any one or multiple event flags can be enabled to trigger the IRQ1 and IRQ2 pins. The user can select one or both hardware interrupt pins for the enabled event flags. Register 0x07 and Register 0x08 determine the pin to which each event flag is routed. Set Register 0x07 and Register 0x08 to 0 for IRQ1 and set these registers to 1 for IRQ2. Ten event flags provide visibility into the device. These flags are located in the two event flag registers, Register 0x05 and Register 0x06. The behavior of each event flag is independently selected in the interrupt enable registers, Register 0x03 and Register 0x04. When the flag interrupt enable is active, the event flag latches and triggers an external interrupt. When the flag interrupt is disabled, the event flag monitors the source signal, but the IRQ1 and IRQ2 pin remain inactive. INTERRUPT SERVICE ROUTINE Interrupt request management starts by selecting the set of event flags that require host intervention or monitoring. Enable the events that require host action so that the host is notified when they occur. For events requiring host intervention upon IRQx activation, run the following routine to clear an interrupt request: INTERRUPT WORKING MECHANISM Figure 49 shows the interrupt related circuitry and how the event flag signals propagate to the IRQx output. The INTERRUPT_ ENABLE signal represents one bit from the interrupt enable register. The EVENT_FLAG_SOURCE signal represents one bit from the event flag register. The EVENT_FLAG_SOURCE signal represents one of the device signals that can be monitored, such as the PLL_LOCK signal from the PLL phase detector or the FIFO_WARNING_1 signal from the FIFO controller. 1. 2. 3. 4. When an interrupt enable bit is set high, the corresponding event flag bit reflects a positively tripped version of the EVENT_FLAG_ SOURCE signal; that is, the event flag bit is latched on the rising edge of the EVENT_FLAG_SOURCE signal. This signal also asserts the external IRQ pins. 5. 6. Read the status of the event flag bits that are being monitored. Set the interrupt enable bit low so that the unlatched EVENT_FLAG_SOURCE can be monitored directly. Perform any actions that may be required to clear the EVENT_FLAG_SOURCE. In many cases, no specific actions may be required. Read the event flag to verify that the actions taken have cleared the EVENT_FLAG_SOURCE. Clear the interrupt by writing 1 to the event flag bit. Set the interrupt enable bits of the events to be monitored. Note that some EVENT_FLAG_SOURCE signals are latched signals. These signals are cleared by writing to the corresponding event flag bit. For more information about each of the event flags, see the Device Configuration Register Map and Description section. When an interrupt enable bit is set low, the event flag bit reflects the present status of the EVENT_FLAG_SOURCE signal, and the event flag has no effect on the external IRQ pins. Clear the latched version of an event flag (the INTERRUPT_ SOURCE signal) in one of two ways. The recommended 0 1 EVENT_FLAG IRQ EVENT_FLAG_SOURCE OTHER INTERRUPT SOURCES 10930-054 INTERRUPT_ENABLE INTERRUPT_ SOURCE WRITE_1_TO_EVENT_FLAG DEVICE_RESET Figure 49. Simplified Schematic of IRQ Circuitry Rev. 0 | Page 34 of 64 Data Sheet AD9142 TEMPERATURE SENSOR The AD9142 has a diode-based temperature sensor for measuring the temperature of the die. The temperature reading is accessed using Register 0x1D and Register 0x1E. The temperature of the die can be calculated as T DIE = Estimates of the ambient temperature can be made if the power dissipation of the device is known. For example, if the device power dissipation is 800 mW and the measured die temperature is 50°C, then the ambient temperature can be calculated as TA = TDIE – PD × θJA = 50 – 0.8 × 20.7 = 33.4°C ( DieTemp [ 15 : 0 ] − 41, 237 ) 106 where TDIE is the die temperature in degrees Celsius. The temperature accuracy is ±7°C typical over the +85°C to −40°C range with one point temperature calibration against a known temperature. A typical plot of the die temperature vs. die temperature code readback is shown in Figure 50. 51000 where: TA is the ambient temperature in degrees Celsius. θJA is the thermal resistance from junction to ambient of the AD9142 as shown in Table 8. To use the temperature sensor, it must be enabled by setting Bit 0, Register 0x1C to 1. In addition, to get accurate readings, the die temperature control register (Register 0x1C) should be set to 0x03. 47000 45000 43000 41000 39000 37000 35000 –40 –30 –20 –10 0 10 20 30 40 50 60 70 80 90 TEMPERATURE (°C) 10930-201 DIE CODE READBACK 49000 Figure 50. Die Temperature vs. Die Temperature Code Readback Rev. 0 | Page 35 of 64 AD9142 Data Sheet DAC INPUT CLOCK CONFIGURATIONS The AD9142 DAC sample clock (DACCLK) can be sourced directly or by clock multiplying. Clock multiplying employs the on-chip phase-locked loop (PLL) that accepts a reference clock operating at a submultiple of the desired DACCLK rate. The PLL then multiplies the reference clock up to the desired DACCLK frequency, which can then be used to generate all of the internal clocks required by the DAC. The clock multiplier provides a high quality clock that meets the performance requirements of most applications. Using the on-chip clock multiplier removes the burden of generating and distributing the high speed DACCLK. The second mode bypasses the clock multiplier circuitry and lets DACCLK be sourced directly to the DAC core. This mode lets the user source a very high quality clock directly to the DAC core. DRIVING THE DACCLK AND REFCLK INPUTS The DACCLK and REFCLK differential inputs share similar clock receiver input circuitry. Figure 51 shows a simplified circuit diagram of the input. The on-chip clock receiver has a differential input impedance of about 10 kΩ. It is self biased to a commonmode voltage of about 1.25 V. The inputs can be driven by differential PECL or LVDS drivers with ac coupling between the clock source and the receiver. 1~100nF AD9142 DACCLKP/ REFP/SYNCP Direct clocking with a low noise clock produces the lowest noise spectral density at the DAC outputs. To select the differential CLK inputs as the source for the DAC sampling clock, set the PLL enable bit (Register 0x12[7]) to 0. This powers down the internal PLL clock multiplier and selects the input from the DACCLKP and DACCLKN pins as the source for the internal DAC sampling clock. The REFCLK input can remain floating. The device also has clock duty cycle correction circuitry and differential input level correction circuitry. Enabling these circuits can provide improved performance in some cases. The control bits for these functions are in Register 0x10 and Register 0x11. CLOCK MULTIPLICATION The on-chip PLL clock multiplier circuit generates the DAC sample rate clock from a lower frequency reference clock. When the PLL enable bit (Register 0x12[7]) is set to 1, the clock multiplication circuit generates the DAC sampling clock from the lower rate REFCLK input and the DACCLK input is left floating. The functional diagram of the clock multiplier is shown in Figure 52. The clock multiplication circuit operates such that the VCO outputs a frequency, fVCO, equal to the REFCLK input signal frequency multiplied by N1 × N0. N1 is the divide ratio of the loop divider; N0 is the divide ratio of the VCO divider. fVCO = fREFCLK × (N1 × N0) 5kΩ 1~100nF 5kΩ DACCLKN/ REFN/SYNCN The DAC sample clock frequency, fDACCLK, is equal to 1.25V fDACCLK = fREFCLK × N1 10930-055 100Ω Figure 51. Clock Receiver Input Simplified Equivalent Circuit The minimum input drive level to the differential clock input is 100 mV p-p differential. The optimal performance is achieved when the clock input signal is between 800 mV p-p differential and 1.6 V p-p differential. Whether using the on-chip clock multiplier or sourcing the DACCLK directly, the input clock signal to the device must have low jitter and fast edge rates to optimize the DAC noise performance. REFP/SYNCP (PIN 2) REFN/SYNCN (PIN 3) PHASE FREQUENCY DETECTION The output frequency of the VCO must be chosen to keep fVCO in the optimal operating range of 1.0 GHz to 2.1 GHz. It is important to select a frequency of the reference clock and values of N1 and N0 so that the desired DACCLK frequency can be synthesized and the VCO output frequency is in the correct range. ADC PLL CHARGE PUMP CURRENT REG 0x14[4:0] PLL LOOP BW REG 0x14[7:5] CHARGE PUMP ON-CHIP LOOP FILTER VCO (1GHz~2.1GHz) LOOP DIVIDER REG 0x15[1:0] VCO DIVIDER REG 0x15[3:2] DIVIDE BY 2, 4, 8, OR 16 DIVIDE BY 1, 2, OR 4 DACCLKN (PIN 62) VCO CONTROL VOLTAGE REG 0x16[3:0] DACCLK DACCLKP (PIN 61) PLL ENABLE REG 0x12[7] Figure 52. PLL Clock Multiplication Circuit Rev. 0 | Page 36 of 64 10930-056 RECOMMENDED EXTERNAL CIRCUITRY DIRECT CLOCKING Data Sheet AD9142 PLL SETTINGS 61 The PLL circuitry requires three settings to be programmed to their nominal values. The PLL values shown in Table 21 are the recommended settings for these parameters. 53 57 49 45 PLL BAND 41 Table 21. PLL Settings Register Address 0x14[7:5] 0x14[4:0] 0x15[4] Optimal Setting (Binary) 111 00111 0 33 29 25 21 17 13 9 5 1 950 CONFIGURING THE VCO TUNING BAND The PLL VCO has a valid operating range from approximately 1.0 GHz to 2.1 GHz covered in 64 overlapping frequency bands. For any desired VCO output frequency, there may be several valid PLL band select values. The frequency bands of a typical device are shown in Figure 53. Device-to-device variations and operating temperature affect the actual band frequency range. Therefore, it is required that the optimal PLL band select value be determined for each individual device. 1150 1350 1550 1750 1950 VCO FREQUENCY (MHz) 2150 10930-057 PLL SPI Control Register PLL Loop Bandwidth PLL Charge Pump Current PLL Cross Control Enable 37 Figure 53. PLL Lock Range for a Typical Device MANUAL VCO BAND SELECT The device includes a manual band select mode (PLL auto manual enable, Register 0x12[6] = 1) that lets the user select the VCO tuning band. In manual mode, the VCO band is set directly with the value written to the manual VCO band bits (Register 0x12[5:0]). AUTOMATIC VCO BAND SELECT PLL ENABLE SEQUENCE The device has an automatic VCO band select feature on chip. Using the automatic VCO band select feature is a simple and reliable method of configuring the VCO frequency band. This feature is enabled by starting the PLL in manual mode, and then placing the PLL in autoband select mode by setting Register 0x12 to a value of 0xC0 and then to a value of 0x80. When these values are written, the device executes an automated routine that determines the optimal VCO band setting for the device. To enable the PLL in automatic or manual mode properly, the following sequence must be followed: The setting selected by the device ensures that the PLL remains locked over the full −40°C to +85°C operating temperature range of the device without further adjustment. The PLL remains locked over the full temperature range even if the temperature during initialization is at one of the temperature extremes. Automatic Mode Sequence 1. 2. 3. 4. 5. 6. Configure the loop divider and the VCO divider registers for the desired divide ratios. Set 00111b to PLL charge pump current and 111b to PLL loop bandwidth for the best performance. Set the PLL mode to manual using Register 0x12[6] = 1b. Enable the PLL using Register 0x12[7] = 1b. Set the PLL mode to automatic using Register 0x12[6] = 0b. Enable the PLL using Register 0x12[7] = 1b. Manual Mode 1. 2. 3. 4. 5. 6. Rev. 0 | Page 37 of 64 Configure the loop divider and the VCO divider registers for the desired divide ratios. Set 00111b to PLL charge pump current and 111b to PLL loop bandwidth for the best performance. Select the desired band. Set the PLL mode to manual using Register 0x12[6] = 1b. Enable the PLL using Register 0x12[7] = 1b. Enable the PLL one more time using Register 0x12[7] = 1b. AD9142 Data Sheet ANALOG OUTPUTS Figure 54 shows a simplified block diagram of the transmit path DACs. The DAC core consists of a current source array, a switch core, digital control logic, and full-scale output current control. The DAC full-scale output current (IOUTFS) is nominally 20 mA. The output currents from the IOUT1P/IOUT2P and IOUT1N/ IOUT2N pins are complementary, meaning that the sum of the two currents always equals the full-scale current of the DAC. The digital input code to the DAC determines the effective differential current delivered to the load. I DAC FS ADJUST REG 0x18, 0x19 CURRENT SCALING 15 IOUT2N IOUT2P 0 Q DAC FS ADJUST REG 0x1A, 0x1B Figure 54. Simplified Block Diagram of DAC Core The DAC has a 1.2 V band gap reference with an output impedance of 5 kΩ. The reference output voltage appears on the REFIO pin. When using the internal reference, decouple the REFIO pin to AVSS with a 0.1 µF capacitor. Use the internal reference only for external circuits that draw dc currents of 2 µA or less. For dynamic loads or static loads greater than 2 µA, buffer the REFIO pin. If desired, the internal reference can be overdriven by applying an external reference (from 1.10 V to 1.30 V) to the REFIO pin. A 10 kΩ external resistor, RSET, must be connected from the FSADJ pin to AVSS. This resistor, together with the reference control amplifier, sets up the correct internal bias currents for the DAC. Because the full-scale current is inversely proportional to this resistor, the tolerance of RSET is reflected in the full-scale output amplitude. The full-scale current equation, where the DAC gain is set individually for the Q and IDACs in Register 0x40 and Register 0x44, respectively, is as follows: 0 200 400 600 800 DAC GAIN CODE 1000 10930-059 5 Q DAC VREF 3 × 72 + × DAC gain RSET 16 20 10 IOUT1N 10kΩ RSET I FS = 25 I DAC 5kΩ FSADJ 30 IOUT1P REFIO 0.1µF 35 10930-058 1.2V For nominal values of VREF (1.2 V), RSET (10 kΩ), and DAC gain (512), the full-scale current of the DAC is typically 20.16 mA. The DAC full-scale current can be adjusted from 8.64 mA to 31.68 mA by setting the DAC gain parameter, as shown in Figure 55. IFS (mA) TRANSMIT DAC OPERATION Figure 55. DAC Full-Scale Current vs. DAC Gain Code Transmit DAC Transfer Function The output currents from the IOUT1P/IOUT2P and IOUT1N/ IOUT2N pins are complementary, meaning that the sum of the two currents always equals the full-scale current of the DAC. The digital input code to the DAC determines the effective differential current delivered to the load. IOUT1P/IOUT2P provide maximum output current when all bits are high. The output currents vs. DACCODE for the DAC outputs is expressed as DACCODE I OUTP = × I OUTFS 2N IOUTN = IOUTFS – IOUTP (1) (2) where DACCODE = 0 to 2N − 1. Transmit DAC Output Configurations The optimum noise and distortion performance of the AD9142 is realized when it is configured for differential operation. The common-mode rejection of a transformer or differential amplifier significantly reduces the common-mode error sources of the DAC outputs. These common-mode error sources include even-order distortion products and noise. The enhancement in distortion performance becomes more significant as the frequency content of the reconstructed waveform increases and/or its amplitude increases. This is due to the first-order cancellation of various dynamic common-mode distortion mechanisms, digital feedthrough, and noise. Rev. 0 | Page 38 of 64 Data Sheet AD9142 Figure 56 shows the most basic DAC output circuitry. A pair of resistors, RO, convert each of the complementary output currents to a differential voltage output, VOUT. Because the current outputs of the DAC are high impedance, the differential driving point impedance of the DAC outputs, ROUT, is equal to 2 × RO. See Figure 57 for the output voltage waveforms. ADL537x 67 IOUT1P IBBP RBIP 50Ω 66 RBIN 50Ω IBBN IOUT1N 59 + IOUT2N QBBN RBQN 50Ω RO VOUTI RO RLI 100Ω RBQP 50Ω 58 VIN – RLQ 100Ω QBBP IOUT2P IOUT1N 10930-062 VIP IOUT1P AD9142 Figure 58. Typical Interface Circuitry Between the AD9142 and the ADL537x Family of Modulators VQP + IOUT2P The baseband inputs of the ADL537x family require a dc bias of 500 mV. The nominal midscale output current on each output of the DAC is 10 mA (one-half the full-scale current). Therefore, a single 50 Ω resistor to ground from each of the DAC outputs results in the desired 500 mV dc common-mode bias for the inputs to the ADL537x. The addition of the load resistor in parallel with the modulator inputs reduces the signal level. The peak-to-peak voltage swing of the transmitted signal is RO 10930-060 VOUTQ RO VQN – IOUT2N Figure 56. Basic Transmit DAC Output Circuit +VPEAK VSIGNAL = I FS × VCM VN VP (2 × R B × R L ) (2 × R B + R L ) Baseband Filter Implementation 0 Most applications require a baseband anti-imaging filter between the DAC and the modulator to filter out Nyquist images and broadband DAC noise. The filter can be inserted between the I-V resistors at the DAC output and the signal level setting resistor across the modulator input. This configuration establishes the input and output impedances for the filter. 10930-061 VOUT Figure 59 shows a fifth-order, low-pass filter. A common-mode choke is placed between the I-V resistors and the remainder of the filter to remove the common-mode signal produced by the DAC and to prevent the common-mode signal from being converted to a differential signal, which can appear as unwanted spurious signals in the output spectrum. Splitting the first filter capacitor into two and grounding the center point creates a common-mode low-pass filter, which provides additional common-mode rejection of high frequency signals. A purely differential filter can pass common-mode signals. Figure 57. Output Voltage Waveforms The common-mode signal voltage, VCM, is calculated as VCM = I FS × RO 2 The peak output voltage, VPEAK, is calculated as VPEAK = IFS × RO In this circuit configuration, the single-ended peak voltage is the same as the peak differential output voltage. INTERFACING TO MODULATORS For more details about interfacing the AD9142 DAC to an IQ modulator, refer to the Circuits from the Lab CN-0205, Interfacing the ADL5375 I/Q Modulator to the AD9122 Dual Channel, 1.2 GSPS High Speed DAC on the Analog Devices website. The AD9142 interfaces to the ADL537x family of modulators with a minimal number of components. An example of the recommended interface circuitry is shown in Figure 58. 50Ω AD9142 22pF 33nH 33nH 33nH 33nH 3.6pF 50Ω 3pF 6pF 22pF 140Ω ADL537x 3pF Figure 59. DAC Modulator Interface with Fifth-Order, Low-Pass Filter Rev. 0 | Page 39 of 64 10930-063 –VPEAK AD9142 Data Sheet REDUCING LO LEAKAGE AND UNWANTED SIDEBANDS Analog quadrature modulators can introduce unwanted signals at the local oscillator (LO) frequency due to dc offset voltages in the I and Q baseband inputs, as well as feedthrough paths from the LO input to the output. The LO feedthrough can be nulled by applying the correct dc offset voltages at the DAC output using the digital dc offset adjustments (Register 0x3B through Register 0x3E). (Register 0x37 and Register 0x38) and the DAC FS adjust registers (Register 0x18 through Register 0x1B) can be used to calibrate the I and Q transmit paths to optimize sideband suppression. For more information about suppressing LO leakage and sideband image, refer to Application Note AN-1039, Correcting Imperfections in IQ Modulators to Improve RF Signal Fidelity and Application Note AN-1100, Wireless Transmitter IQ Balance and Sideband Suppression from the Analog Devices website. Effective sideband suppression requires both gain and phase matching of the I and Q signals. The I/Q phase adjust registers Rev. 0 | Page 40 of 64 Data Sheet AD9142 EXAMPLE START-UP ROUTINE To ensure reliable start-up of the AD9142, certain sequences must be followed. This section shows an example start-up routine. /* Configure PLL */ 0x14 → 0xE3 /* Configure PLL loop BW and charge pump current */ 0x15 → 0xC2 /* Configure VCO divider and Loop divider */ Device Configuration and Start-Up Sequence • • • • • • 0x12 → 0xC0 /*Enable the PLL */ fDATA = 200 MHz, interpolation is 8×. Input data is baseband data. fOUT = 350 MHz. PLL is enabled, fREF = 200 MHz. Fine NCO is enabled, inverse sinc filter is enabled. A delay line-based mode is used with an interface delay setting of 0. 0x12 → 0x80 /* Configure Data Interface */ 0x5E → 0x00 /* Delay setting 0 */ 0x5F → 0x08 /* Enable the delay line */ /* Configure Interpolation filter */ Derived PLL Settings 0x28 → 0x03 /* 8× interpolation */ The following PLL settings can be derived from the device configuration: • • • • /* Reset FIFO */ fDAC = 200 × 8 = 1600 MHz. fVCO= fDAC = 1600 MHz (1 GHz < fVCO < 2 GHz). VCO divider = fVCO/fDAC = 1. Loop divider = fDAC/fREF = 8. 0x25 → 0x01 Read 0x25[1] /* Expect 1b if the FIFO reset is complete */ Read 0x24 /* The readback should be one of the three values: 0x37, 0x40, or 0x41 */ Derived NCO Settings The following NCO settings can be derived from the device configuration: • • • /* Configure NCO */ 0x27→ 0x40 /* Enable NCO */ fDAC = 200 × 8 = 1600 MHz. fCARRIER = fOUT = 350 MHz. FTW = fCARRIER/fDAC × 232 = 0x38000000. 0x31 → 0x00 0x32 → 0x00 0x33 → 0x00 Start-Up Sequence 1. 2. 3. 4. 5. Power up the device (no specific power supply sequence is required). Apply stable DAC clock. Apply stable DCI clock. Feed stable input data. Issue H/W reset (optional). /* Device configuration register write sequence. Must be written in sequence for every device after reset*/ 0x00 → 0x20 /* Issue software reset */ 0x34 → 0x38 0x30 → 0x01 Read 0x30[1] /* Expect 1b if the NCO update is complete */ /* Enable Inverse SINC filter */ 0x27 → 0xC0 /* Power up DAC outputs */ 0x01 → 0x00 0x20 → 0x01 /* Device Startup Configuration */ 0x79 → 0x18 /* Device Startup Configuration */ 0x80 → 0xAD /* Device Startup Configuration */ 0xE1 → 0x1A /* Device Startup Configuration */ Rev. 0 | Page 41 of 64 AD9142 Data Sheet DEVICE CONFIGURATION REGISTER MAP AND DESCRIPTION Table 22. Device Configuration Register Map Reg 0x00 0x01 0x03 Name Common PD_CONTROL INTERRUPT_ ENABLE0 Bits [7:0] [7:0] [7:0] Bit 7 Reserved PD_IDAC Reserved Bit 6 SPI_LSB_FIRST PD_QDAC ENABLE_ SYNC_LOST 0x04 INTERRUPT_ ENABLE1 0x05 INTERRUPT_ FLAG0 0x06 INTERRUPT_ FLAG1 0x07 IRQ_SEL0 [7:0] 0x08 IRQ_SEL1 [7:0] 0x10 DACCLK_ RECEIVER_ CTRL 0x11 REFCLK_ RECEIVER_CTRL [7:0] DACCLK_ DUTYCYCLE_ CORRECTION [7:0] DUTYCYCLE_ CORRECTION 0x12 PLL_CTRL0 [7:0] PLL_ENABLE 0x14 PLL_CTRL2 0x15 PLL_CTRL3 [7:0] [7:0] 0x16 0x17 0x18 0x19 [7:0] PLL_LOCK [7:0] Reserved [7:0] [7:0] PLL_STATUS0 PLL_STATUS1 IDAC_FS_ADJ0 IDAC_FS_ADJ1 Reserved [7:0] Reserved SYNC_LOST SYNC_LOCKED SYNC_DONE [7:0] Reserved [7:0] Reserved SEL_SYNC_ LOST SEL_SYNC_ LOCKED Reserved Reserved Reserved AUTO_ MANUAL_SEL PLL_LOOP_BW DIGLOGIC_DIVIDER Reserved [7:0] 0x26 DATA_ FORMAT_SEL 0x27 DATAPATH_ CTRL [7:0] DATA_ FORMAT [7:0] INVSINC_ ENABLE Bit 1 Bit 0 PD_DACCLK PD_FRAME ENABLE_OVER_ ENABLE_ DACOUT_ THRESHOLD MUTED ENABLE_FIFO_ ENABLE_FIFO_ ENABLE_FIFO_ UNDERFLOW OVERFLOW WARNING PLL_LOST PLL_LOCKED OVER_ DACOUT_ THRESHOLD MUTED FIFO_ FIFO_OVERFIFO_ UNDERFLOW FLOW WARNING SEL_PLL_LOST SEL_PLL_ SEL_OVER_ SEL_DACOUT LOCKED THRESHOLD _MUTED SEL_FIFO_ SEL_FIFO_ SEL_FIFO_ UNDERFLOW OVERFLOW WARNING DACCLK_CROSSPOINT_LEVEL REFCLK_CROSSPOINT_LEVEL PLL_MANUAL_BAND PLL_CP_CURRENT VCO_DIVIDER CROSSPOINT_ CTRL_EN LOOP_DIVIDER VCO_CTRL_VOLTAGE_READBACK PLL_BAND_READBACK IDAC_FULLSCALE_ADJUST_LSB Reserved IDAC_FULLSCALE_ADJUST_ MSB QDAC_FULLSCALE_ADJUST_LSB Reserved QDAC_FULLSCALE_ADJUST_ MSB FS_CURRENT REF_CURRENT DIE_TEMP_ SENSOR_EN DIE_TEMP_LSB DIE_TEMP_MSB CHIP_ID INTERRUPT_CONFIGURATION [7:0] [7:0] [7:0] [7:0] [7:0] Bit 2 Reserved PD_DEVICE ENABLE_PLL_ LOCKED Reserved [7:0] Reserved 0x22 FRAME_RST_ CTRL 0x23 FIFO_LEVEL_ CONFIG 0x24 FIFO_LEVEL_ READBACK 0x25 FIFO_CTRL SEL_SYNC_ DONE DACCLK_ CROSSPOINT_ CTRL_ENABLE REFCLK_ CROSSPOINT_ CTRL_ENABLE 0x1A QDAC_FS_ADJ0 [7:0] 0x1B QDAC_FS_ADJ1 [7:0] 0x1C DIE_TEMP_ SENSOR_CTRL 0x1D DIE_TEMP_LSB 0x1E DIE_TEMP_MSB 0x1F CHIP_ID 0x20 INTERRUPT_ CONFIG 0x21 SYNC_CTRL Bit 5 Bit 4 Bit 3 DEVICE_RESET PD_DATARCV Reserved ENABLE_ ENABLE_ ENABLE_PLL_ SYNC_LOCKED SYNC_DONE LOST Reserved Reserved [7:0] Reserved INTEGRAL_FIFO_LEVEL_REQUEST [7:0] Reserved INTEGRAL_FIFO_LEVEL_READBACK [7:0] FRAME_ RESET_ACK Reserved SYNC_CLK_ SYNC_ EDGE_SEL ENABLE FRAME_RESET_MODE EN_CON_ FRAME_RESET FRACTIONAL_FIFO_LEVEL_REQUEST Reserved FRACTIONAL_FIFO_LEVEL_READBACK Reserved DATA_PAIRIN G NCO_ENABLE DATA_BUS_ INVERT IQ_GAIN_ADJ_ IQ_PHASE_ DCOFFSET_ ADJ_ENABLE ENABLE FIFO_SPI_ RESET_ACK Reserved Reserved Rev. 0 | Page 42 of 64 FS4_ NCO_SIDEMODULATION_ BAND_SEL ENABLE Reset 0x00 0xC0 0x00 RW RW RW RW 0x00 RW 0x00 R 0x00 R 0x00 RW 0x00 RW 0xFF RW 0xBF RW 0x00 RW 0xE7 RW 0xC9 RW 0x00 0x00 0xF9 0xE1 R R RW RW 0xF9 0x01 RW RW 0x02 RW 0x00 0x00 0x0A 0x00 R R R RW 0x00 RW 0x12 RW 0x40 RW 0x00 R FIFO_SPI_ 0x00 RESET_ REQUEST DATA_BUS_ 0x00 WIDTH SEND_IDATA_ 0x00 TO_QDAC RW RW RW Data Sheet 0x28 INTERPOLATION_ CTRL 0x29 OVER_ THRESHOLD_ CTRL0 0x2A OVER_ THRESHOLD_ CTRL1 0x2B OVER_ THRESHOLD_ CTRL2 0x2C INPUT_POWER_ READBACK_LSB 0x2D INPUT_POWER_ READBACK_MSB 0x30 NCO_CTRL AD9142 [7:0] Reserved [7:0] INTERPOLATION_MODE THRESHOLD_LEVEL_REQUEST_LSB [7:0] Reserved [7:0] ENABLE_ PROTECTION THRESHOLD_LEVEL_REQUEST_MSB IQ_DATA_ SWAP Reserved [7:0] SAMPLE_WINDOW_LENGTH INPUT_POWER_READBACK_LSB [7:0] Reserved [7:0] Reserved NCO_FRAME_ UPDATE_ACK INPUT_POWER_READBACK_MSB SPI_NCO_ PHASE_RST_ ACK SPI_NCO_ PHASE_ RST_REQ Reserved NCO_SPI_ UPDATE_ACK 0x00 RW 0x00 RW 0x00 RW 0x00 RW 0x00 R 0x00 R NCO_SPI_ 0x00 UPDATE_REQ RW 0x31 NCO_FREQ_ TUNING_ WORD0 0x32 NCO_FREQ_ TUNING_ WORD1 0x33 NCO_FREQ_ TUNING_ WORD2 0x34 NCO_FREQ_ TUNING_ WORD3 0x35 NCO_PHASE_ OFFSET0 0x36 NCO_PHASE_ OFFSET1 0x37 IQ_PHASE_ ADJ0 0x38 IQ_PHASE_ ADJ1 0x3B IDAC_DC_ OFFSET0 0x3C IDAC_DC_ OFFSET1 0x3D QDAC_DC_ OFFSET0 0x3E QDAC_DC_ OFFSET1 0x3F IDAC_GAIN_ADJ 0x40 QDAC_GAIN_ ADJ 0x41 GAIN_STEP_ CTRL0 0x42 GAIN_STEP_ CTRL1 0x43 TX_ENABLE_ CTRL [7:0] NCO_FTW0 0x00 RW [7:0] NCO_FTW1 0x00 RW [7:0] NCO_FTW2 0x00 RW [7:0] NCO_FTW3 0x10 RW [7:0] NCO_PHASE_OFFSET_LSB 0x00 RW [7:0] NCO_PHASE_OFFSET_MSB 0x00 RW [7:0] IQ_PHASE_ADJ_LSB 0x00 RW RW 0x44 DAC_OUTPUT_ CTRL [7:0] DAC_OUTPUT_ CTRL_EN [7:0] Reserved IQ_PHASE_ADJ_MSB [7:0] IDAC_DC_OFFSET_LSB 0x00 0 0x00 [7:0] IDAC_DC_OFFSET_MSB 0x00 RW [7:0] QDAC_DC_OFFSET_LSB 0x00 RW [7:0] QDAC_DC_OFFSET_MSB 0x00 RW RW [7:0] [7:0] Reserved Reserved IDAC_GAIN_ADJ QDAC_GAIN_ADJ 0x20 0x20 RW RW [7:0] Reserved RAMP_UP_STEP 0x01 RW RAMP_DOWN_STEP 0x01 RW TXENABLE_ 0x07 POWER_ DOWN_EN FIFO_ERROR_ 0x8F SHUTDOWN_ EN RW [7:0] DAC_OUTPUT_ DAC_OUTPUT_ STATUS ON [7:0] 0x5E DATA_RX_CTRL0 [7:0] 0x5F DATA_RX_CTRL1 [7:0] 0x79 DEVICE_ [7:0] CONFIG0 0x7F Version [7:0] 0x80 DEVICE_ [7:0] CONFIG1 0xE1 DEVICE_ [7:0] CONFIG2 Reserved Reserved Reserved TXENABLE_ GAINSTEP_EN FIFO_WARNING_ OVERSHUTDOWN_EN THRESHOLD_ SHUTDOWN_ EN DLY_TAP_LSB DLYLINE_EN DEVICE_CONFIGURATION0 TXENABLE_ SLEEP_EN Reserved RW 0xFF 0x07 0x00 RW RW RW Version DEVICE_CONFIGURATION1 0x05 0x00 R RW DEVICE_CONFIGURATION2 0x00 RW Rev. 0 | Page 43 of 64 DLY_TAP_MSB AD9142 Data Sheet SPI CONFIGURE REGISTER Address: 0x00, Reset: 0x00, Name: Common Table 23. Bit Descriptions for Common Bits 6 Bit Name SPI_LSB_FIRST Settings 0 1 5 DEVICE_RESET Description Serial port communication, MSB-first or LSB-first selection. MSB first. LSB first. The device resets when 1 is written to this bit. DEVICE_RESET is a self clear bit. After the reset, the bit returns to 0 automatically. The readback is always 0. Reset 0x0 Access RW 0x0 RW Reset 0x1 Access RW 0x1 RW 0x0 RW 0x0 RW 0x0 RW 0x0 RW Reset 0x0 0x0 0x0 0x0 0x0 0x0 0x0 Access RW RW RW RW RW RW RW Reset 0x0 0x0 0x0 Access RW RW RW POWER-DOWN CONTROL REGISTER Address: 0x01, Reset: 0xC0, Name: PD_CONTROL Table 24. Bit Descriptions for PD_CONTROL Bits 7 Bit Name PD_IDAC 6 PD_QDAC 5 PD_DATARCV 2 PD_DEVICE 1 PD_DACCLK 0 PD_FRAME Settings Description The IDAC is powered down when PD_IDAC is set to 1. This bit powers down only the analog portion of the IDAC. The IDAC digital data path is not affected. The QDAC is powered down when PD_QDAC is set to 1. This bit powers down only the analog portion of the QDAC. The QDAC digital data path is not affected. The data interface circuitry is powered down when PD_DATARCV is set to 1. This bit powers down the data interface and the write side of the FIFO. The bandgap circuitry is powered down when set to 1. This bit powers down the entire chip. The DAC clocking powers down when PD_DEVICE is set to 1. This bit powers down the DAC clocking path and, thus, the majority of the digital functions. The frame receiver powers down when PD_FRAME is set to 1. The frame signal is internally pulled low. Set to 1 when frame is not used. INTERRUPT ENABLE0 REGISTER Address: 0x03, Reset: 0x00, Name: INTERRUPT_ENABLE0 Table 25. Bit Descriptions for INTERRUPT_ENABLE0 Bits 6 5 4 3 2 1 0 Bit Name ENABLE_SYNC_LOST ENABLE_SYNC_LOCKED ENABLE_SYNC_DONE ENABLE_PLL_LOST ENABLE_PLL_LOCKED ENABLE_OVER_THRESHOLD ENABLE_DACOUT_MUTED Settings Description Enable interrupt for sync lost. Enable interrupt for sync lock. Enable interrupt for sync done. Enable interrupt for PLL lost. Enable interrupt for PLL locked. Enable interrupt for overthreshold. Enable interrupt for DACOUT muted. INTERRUPT ENABLE1 REGISTER Address: 0x04, Reset: 0x00, Name: INTERRUPT_ENABLE1 Table 26. Bit Descriptions for INTERRUPT_ENABLE1 Bits 2 1 0 Bit Name ENABLE_FIFO_UNDERFLOW ENABLE_FIFO_OVERFLOW ENABLE_FIFO_WARNING Settings Description Enable interrupt for FIFO underflow. Enable interrupt for FIFO overflow. Enable interrupt for FIFO warning. Rev. 0 | Page 44 of 64 Data Sheet AD9142 INTERRUPT FLAG0 REGISTER Address: 0x05, Reset: 0x00, Name: INTERRUPT_FLAG0 Table 27. Bit Descriptions for INTERRUPT_FLAG0 Bits 6 5 4 3 2 1 Bit Name SYNC_LOST SYNC_LOCKED SYNC_DONE PLL_LOST PLL_LOCKED OVER_THRESHOLD 0 DACOUT_MUTED Settings Description SYNC_LOST is set to 1 when sync is lost. SYNC_LOCKED is set to 1 when sync is locked. SYNC_DONE is set to 1 when sync is done. PLL_LOST is set to 1 when PLL loses lock. PLL_LOCKED is set to 1 when PLL is locked. OVER_THRESHOLD is set to 1 when input power is overthreshold. DACOUT_MUTED is set to 1 when the DAC output is muted (midscale dc). Reset 0x0 0x0 0x0 0x0 0x0 0x0 Access R R R R R R 0x0 R Description FIFO_UNDERFLOW is set to 1 when the FIFO read pointer catches the FIFO write pointer. FIFO_OVERFLOW is set to 1 when the FIFO write pointer catches the FIFO read pointer. FIFO_WARNING is set to 1 when the FIFO is one slot from empty (≤1) or full (≥6). Reset 0x0 Access R 0x0 R 0x0 R 0 1 Description Selects the IRQ1 pin. Selects the IRQ2 pin. Reset 0x0 Access RW INTERRUPT FLAG1 REGISTER Address: 0x06, Reset: 0x00, Name: INTERRUPT_FLAG1 Table 28. Bit Descriptions for INTERRUPT_FLAG1 Bits 2 Bit Name FIFO_UNDERFLOW 1 FIFO_OVERFLOW 0 FIFO_WARNING Settings INTERRUPT SELECT0 REGISTER Address: 0x07, Reset: 0x00, Name: IRQ_SEL0 Table 29. Bit Descriptions for IRQ_SEL0 Bits 6 Bit Name SEL_SYNC_LOST Settings 5 SEL_SYNC_LOCKED 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0x0 RW 4 SEL_SYNC_DONE 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0x0 RW 3 SEL_PLL_LOST 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0x0 RW 2 SEL_PLL_LOCKED 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0x0 RW 1 SEL_OVER_THRESHOLD 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0x0 RW 0 SEL_DACOUT_MUTED 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0x0 RW Rev. 0 | Page 45 of 64 AD9142 Data Sheet INTERRUPT SELECT1 REGISTER Address: 0x08, Reset: 0x00, Name: IRQ_SEL1 Table 30. Bit Descriptions for IRQ_SEL1 Bits 2 Bit Name SEL_FIFO_UNDERFLOW 1 0 Settings 0 1 Description Selects the IRQ1 pin. Selects the IRQ2 pin. Reset 0x0 Access RW SEL_FIFO_OVERFLOW 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0x0 RW SEL_FIFO_WARNING 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0x0 RW Reset 0x1 Access RW 0x1 RW 0x1F RW Reset 0x0 Access RW 0x0 RW 0x1F RW DAC CLOCK RECEIVER CONTROL REGISTER Address: 0x10, Reset: 0xFF, Name: DACCLK_RECEIVER_CTRL Table 31. Bit Descriptions for DACCLK_RECEIVER_CTRL Bits 7 Bit Name DACCLK_DUTYCYCLE_CORRECTION 5 DACCLK_CROSSPOINT_CTRL_ENABLE [4:0] DACCLK_CROSSPOINT_LEVEL Settings Description Enables duty cycle correction at the DACCLK input. For best performance, the default and recommended status is turned on. Enables crosspoint control at the DACCLK input. For best performance, the default and recommended status is turned on. A twos complement value. For best performance, it is recommended to set DACCLK_CROSSPOINT_LEVEL to the default value. Highest crosspoint. Lowest crosspoint. 01111 11111 REF CLOCK RECEIVER CONTROL REGISTER Address: 0x11, Reset: 0xBF, Name: REFCLK_RECEIVER_CTRL Table 32. Bit Descriptions for REFCLK_RECEIVER_CTRL Bits 7 Bit Name DUTYCYCLE_CORRECTION 5 REFCLK_CROSSPOINT_CTRL_ENABLE [4:0] REFCLK_CROSSPOINT_LEVEL Settings 01111 11111 Description Enables duty cycle correction at the REFCLK input. For best performance, the default and recommended status is turned off. Enables crosspoint control at the REFCLK input. For best performance, the default and recommended status is turned off. A twos complement value. For best performance, it is recommended to set REFCLK_CROSSPOINT_LEVEL to the default value. Highest crosspoint. Lowest crosspoint. Rev. 0 | Page 46 of 64 Data Sheet AD9142 PLL CONTROL REGISTER Address: 0x12, Reset: 0x00, Name: PLL_CTRL0 Table 33. Bit Descriptions for PLL_CTRL0 Bits 7 6 Bit Name PLL_ENABLE AUTO_MANUAL_SEL Settings 0 1 [5:0] PLL_MANUAL_BAND 000000 111111 Description Enables PLL clock multiplier. PLL band selection mode. Automatic mode. Manual mode. PLL band setting in manual mode. 64 bands in total, covering a 1 GHz to 2.1 GHz VCO range. Lowest band (1 GHz). Highest band (2.1 GHz). Reset 0x0 0x0 Access RW RW 0x00 RW Reset 0x7 Access RW 0x07 RW Reset 0x3 Access RW 0x0 RW 0x2 RW 0x1 RW PLL CONTROL REGISTER Address: 0x14, Reset: 0xE7, Name: PLL_CTRL2 Table 34. Bit Descriptions for PLL_CTRL2 Bits [7:5] Bit Name PLL_LOOP_BW Settings 0x00 0x1F [4:0] PLL_CP_CURRENT 0x00 0x1F Description Selects the PLL loop filter bandwidth. The default and recommended setting is 111 for optimal PLL performance. Lowest setting. Highest setting. Sets nominal PLL charge pump current. The default and recommended setting is 00111 for optimal PLL performance. Lowest setting. Highest setting. PLL CONTROL REGISTER Address: 0x15, Reset: 0xC9, Name: PLL_CTRL3 Table 35. Bit Descriptions for PLL_CTRL3 Bits [7:6] Bit Name DIGLOGIC_DIVIDER Settings 00 01 10 11 4 CROSSPOINT_CTRL_EN [3:2] VCO_DIVIDER 00 01 10 11 [1:0] LOOP_DIVIDER 00 01 10 11 Description REFCLK to PLL digital clock divide ratio. The PLL digital clock drives the internal PLL logics. The divide ratio must be set to ensure that the PLL digital clock is below 75 MHz. fREFCLK/fDIG = 2. fREFCLK/fDIG = 4. fREFCLK/fDIG = 8. fREFCLK/fDIG = 16. Enable loop divider crosspoint control. The default and recommended setting is turned off (0) for optimal PLL performance. PLL VCO divider. This divider determines the ratio of the VCO frequency to the DACCLK frequency. fVCO/fDACCLK = 1. fVCO/fDACCLK = 2. fVCO/fDACCLK = 4. fVCO/fDACCLK = 4. PLL loop divider. This divider determines the ratio of the DACCLK frequency to the REFCLK frequency. fDACCLK/fREFCLK = 2. fDACCLK/fREFCLK = 4. fDACCLK/fREFCLK = 8. fDACCLK/fREFCLK = 16. Rev. 0 | Page 47 of 64 AD9142 Data Sheet PLL STATUS REGISTER Address: 0x16, Reset: 0x00, Name: PLL_STATUS0 Table 36. Bit Descriptions for PLL_STATUS0 Bits 7 [3:0] Bit Name PLL_LOCK VCO_CTRL_VOLTAGE_READBACK Settings 1111 0111 0000 Description PLL clock multiplier output is stable. VCO control voltage readback. A binary value. The highest VCO control voltage. The mid value when a proper VCO band is selected. When the PLL is locked, selecting a higher VCO band decreases this value and selecting a lower VCO band increases this value. The lowest VCO control voltage. Reset 0x0 0x0 Access R R Description Indicates the VCO band currently selected. Reset 0x00 Access R Description See Register 0x19. Reset 0xF9 Access RW Description IDAC full-scale adjust, Bits[9:0] sets the full-scale current of the IDAC. The full-scale current can be adjusted from 8.64 mA to 31.68 mA. The default value (0x1F9) sets the full-scale current to 20 mA. Reset 0x1 Access RW Description See Register 0x1B. Reset 0xF9 Access RW PLL STATUS REGISTER Address: 0x17, Reset: 0x00, Name: PLL_STATUS1 Table 37. Bit Descriptions for PLL_STATUS1 Bits [5:0] Bit Name PLL_BAND_READBACK Settings IDAC FS ADJUST LSB REGISTER Address: 0x18, Reset: 0xF9, Name: IDAC_FS_ADJ0 Table 38. Bit Descriptions for IDAC_FS_ADJ0 Bits [7:0] Bit Name IDAC_FULLSCALE_ADJUST_LSB Settings IDAC FS ADJUST MSB REGISTER Address: 0x19, Reset: 0xE1, Name: IDAC_FS_ADJ1 Table 39. Bit Descriptions for IDAC_FS_ADJ1 Bits [1:0] Bit Name IDAC_FULLSCALE_ADJUST_MSB Settings QDAC FS ADJUST LSB REGISTER Address: 0x1A, Reset: 0xF9, Name: QDAC_FS_ADJ0 Table 40. Bit Descriptions for QDAC_FS_ADJ0 Bits [7:0] Bit Name QDAC_FULLSCALE_ADJUST_LSB Settings Rev. 0 | Page 48 of 64 Data Sheet AD9142 QDAC FS ADJUST MSB REGISTER Address: 0x1B, Reset: 0x01, Name: QDAC_FS_ADJ1 Table 41. Bit Descriptions for QDAC_FS_ADJ1 Bits [1:0] Bit Name QDAC_FULLSCALE_ADJUST_MSB Settings Description QDAC full-scale adjust, Bits[9:0] sets the full-scale current of the QDAC. The full-scale current can be adjusted from 8.64 mA to 31.68 mA. The default value (0x1F9) sets the full-scale current to 20 mA. Reset 0x1 Access RW Reset 0x0 Access RW 0x1 RW 0x0 RW Reset 0x00 Access R DIE TEMPERATURE SENSOR CONTROL REGISTER Address: 0x1C, Reset: 0x02, Name: DIE_TEMP_SENSOR_CTRL Table 42. Bit Descriptions for DIE_TEMP_SENSOR_CTRL Bits [6:4] Bit Name FS_CURRENT Settings 000 001 … 110 111 [3:1] REF_CURRENT 000 001 … 110 111 0 DIE_TEMP_SENSOR_EN Description Temperature sensor ADC full-scale current. Using the default setting is recommended. 50 μA. 62.5 μA. 125 μA. 137.5 μA. Temperature sensor ADC reference current. Using the default setting is recommended. 12.5 μA. 19 μA. 50 μA. 56.5 μA. Enable the on-chip temperature sensor. DIE TEMPERATURE LSB REGISTER Address: 0x1D, Reset: 0x00, Name: DIE_TEMP_LSB Table 43. Bit Descriptions for DIE_TEMP_LSB Bits [7:0] Bit Name DIE_TEMP_LSB Settings Description See Register 0x1E. DIE TEMPERATURE MSB REGISTER Address: 0x1E, Reset: 0x00, Name: DIE_TEMP_MSB Table 44. Bit Descriptions for DIE_TEMP_MSB Bits [7:0] Bit Name DIE_TEMP_MSB Settings Description Die temperature, Bits[15:0] indicate the approximate die temperature. For more information, see the Temperature Sensor section. Reset 0x00 Access R CHIP ID REGISTER Address: 0x1F, Reset: 0x0A, Name: CHIP_ID Table 45. Bit Descriptions for CHIP_ID Bits [7:0] Bit Name CHIP_ID Settings Description The AD9142 chip ID is 0x0A. Rev. 0 | Page 49 of 64 Reset 0x0A Access R AD9142 Data Sheet INTERRUPT CONFIGUATION REGISTER Address: 0x20, Reset: 0x00, Name: INTERRUPT_CONFIG Table 46. Bit Descriptions for INTERRUPT_CONFIG Bits [7:0] Bit Name INTERRUPT_CONFIGURATION Settings 0x00 0x01 Description Test mode. Recommended mode (described in Interrupt Request Operation section). Reset 0x00 Access RW SYNC CTRL REGISTER Address: 0x21, Reset: 0x00, Name: SYNC_CTRL Table 47. Bit Descriptions for SYNC_CTRL Bits 1 Bit Name SYNC_CLK_EDGE_SEL Settings 0 1 0 SYNC_ENABLE Description Selects the sampling edge of the DACCLK on the SYNC CLK. SYNC CLK is sampled by rising edges of DACCLK. SYNC CLK is sampled by falling edges of DACCLK. Enables multichip synchronization. Reset 0x0 Access RW 0x0 RW Reset 0x0 Access R 0x0 RW 0x2 RW FRAME RESET CTRL REGISTER Address: 0x22, Reset: 0x12, Name: FRAME_RST_CTRL Table 48. Bit Descriptions for FRAME_RST_CTRL Bits 3 Bit Name FRAME_RESET_ACK 2 EN_CON_FRAME_RESET Settings 0 1 [1:0] FRAME_RESET_MODE 00 01 10 11 Description Frame reset acknowledge. This bit is set to 1 when a valid frame pulse is received. Reset mode selection. Responds to only the first valid frame pulse and resets the FIFO and/or NCO one time only. This is the default and recommended mode. Responds to every valid frame pulse and resets the FIFO and/or NCO accordingly. These bits determine what is to be reset when the device receives a valid frame signal. FIFO only. NCO only. FIFO and NCO. None. Rev. 0 | Page 50 of 64 Data Sheet AD9142 FIFO LEVEL CONFIGURATION REGISTER Address: 0x23, Reset: 0x40, Name: FIFO_LEVEL_CONFIG Table 49. Bit Descriptions for FIFO_LEVEL_CONFIG Bits [6:4] Bit Name INTEGRAL_FIFO_LEVEL_REQUEST Settings Description Sets the integral FIFO level. This is the difference between the read pointer and the write pointer values in the unit of input data rate (fDATA). The default and recommended FIFO level is integral level = 4 and fractional level = 0. See the FIFO Operation section for details. 0. 1. 000 001 … 111 [2:0] 7. Sets the fractional FIFO level. This is the difference between the read pointer and the write pointer values in the unit of DACCLK rate (FDAC). The maximum allowed setting value = interpolation rate − 1. See the FIFO Operation section for details. 0. 1. FRACTIONAL_FIFO_LEVEL_REQUEST 000 001 … Max allowed setting. Reset 0x4 Access RW 0x0 RW Reset 0x0 Access R 0x0 R Reset 0x0 0x0 Access R RW 001 in 2×. 003 in 4×. 007 in 8×. FIFO LEVEL READBACK REGISTER Address: 0x24, Reset: 0x00, Name: FIFO_LEVEL_READBACK Table 50. Bit Descriptions for FIFO_LEVEL_READBACK Bits [6:4] Bit Name INTEGRAL_FIFO_LEVEL_READBACK [2:0] FRACTIONAL_FIFO_LEVEL_READBACK Settings Description The integral FIFO level read back. The difference between the overall FIFO level request and readback should be within two DACCLK cycles. See the FIFO Operation section for details. The fractional FIFO level read back. This value should be used in combination with the readback in Bit[6:4]. FIFO CTRL REGISTER Address: 0x25, Reset: 0x00, Name: FIFO_CTRL Table 51. Bit Descriptions for FIFO_CTRL Bits 1 0 Bit Name FIFO_SPI_RESET_ACK FIFO_SPI_RESET_REQUEST Settings Description Acknowledge a serial port initialized FIFO reset. Initialize a FIFO reset via the serial port. Rev. 0 | Page 51 of 64 AD9142 Data Sheet DATA FORMAT SELECT REGISTER Address: 0x26, Reset: 0x00, Name: DATA_FORMAT_SEL Table 52. Bit Descriptions for DATA_FORMAT_SEL Bits 7 Bit Name DATA_FORMAT Settings 0 1 6 DATA_PAIRING 0 1 5 DATA_BUS_INVERT 0 1 0 DATA_BUS_WIDTH 0 1 Description Select binary or twos complement data format. Input data in twos complement format. Input data in binary format. Indicate I/Q data pairing on data input. I samples are paired with the next Q samples. I samples are paired with the prior Q samples. Swap the bit order of the data input port. MSBs become the LSBs: D[15:0] changes to D[0:15]. The order of the data bits corresponds to the pin descriptions in Table 9. The order of the data bits is inverted. Data interface mode. See the LVDS Input Data Ports section for information about the operation of the different interface modes. Word mode; 16-bit interface bus width. Byte mode; 8-bit interface bus width. Reset 0x0 Access RW 0x0 RW 0x0 RW 0x0 RW Reset 0x0 0x0 0x0 0x0 0x0 0x0 Access RW RW RW RW RW RW 0x0 RW Reset 0x0 Access RW DATAPATH CONTROL REGISTER Address: 0x27, Reset: 0x00, Name: DATAPATH_CTRL Table 53. Bit Descriptions for DATAPATH_CTRL Bits 7 6 5 4 2 1 Bit Name INVSINC_ENABLE NCO_ENABLE IQ_GAIN_ADJ_DCOFFSET_ENABLE IQ_PHASE_ADJ_ENABLE FS4_MODULATION_ENABLE NCO_SIDEBAND_SEL Settings 0 1 0 SEND_IDATA_TO_QDAC Description Enable the inverse sinc filter. Enable the NCO. Enable digital IQ gain adjustment and dc offset. Enable digital IQ phase adjustment. Enable fS/4 modulation function. Selects the single-side NCO modulation image. The NCO outputs the high-side image. The NCO outputs the low-side image. Send the IDATA to the QDAC. When enabled, I data is sent to both the IDAC and the QDAC. The Q data path still runs, and the Q data is ignored. INTERPOLATION CONTROL REGISTER Address: 0x28, Reset: 0x00, Name: INTERPOLATION_CTRL Table 54. Bit Descriptions for INTERPOLATION_CTRL Bits [1:0] Bit Name INTERPOLATION_MODE Settings 00 10 11 Description Interpolation rate and mode selection. 2× Mode 1; use HB1 filter. 4× mode; use HB1 and HB2 filters. 8× mode; use all three filters (HB1, HB2, and HB3). Rev. 0 | Page 52 of 64 Data Sheet AD9142 OVER THRESHOLD CTRL0 REGISTER Address: 0x29, Reset: 0x00, Name: OVER_THRESHOLD_CTRL0 Table 55. Bit Descriptions for OVER_THRESHOLD_CTRL0 Bits [7:0] Bit Name THRESHOLD_LEVEL_REQUEST_LSB Settings Description See Register 0x2A. Reset 0x0 Access RW Reset 0x00 Access RW Reset 0x0 0x0 0x0 Access RW RW RW Reset 0x0 Access R Reset 0x00 Access R OVER THRESHOLD CTRL1 REGISTER Address: 0x2A, Reset: 0x00, Name: OVER_THRESHOLD_CTRL1 Table 56. Bit Descriptions for OVER_THRESHOLD_CTRL1 Bits [4:0] Bit Name THRESHOLD_LEVEL_REQUEST_MSB Settings Description Minimum average input power (I2 + Q2) to trigger the input power protection function. OVER THRESHOLD CTRL2 REGISTER Address: 0x2B, Reset: 0x00, Name: OVER_THRESHOLD_CTRL2 Table 57. Bit Descriptions for OVER_THRESHOLD_CTRL2 Bits 7 6 [3:0] Bit Name ENABLE_PROTECTION IQ_DATA_SWAP SAMPLE_WINDOW_LENGTH Settings 0000 0001 … 1010 1011 to 1111 Description Enable input power protection. Swap I and Q data in average power calculation. Number of data input samples for power averaging. 512 IQ data sample pairs. 1024 IQ data sample pairs. 219 IQ data sample pairs. invalid. INPUT POWER READBACK LSB REGISTER Address: 0x2C, Reset: 0x00, Name: INPUT_POWER_READBACK_LSB Table 58. Bit Descriptions for INPUT_POWER_READBACK_LSB Bits [7:0] Bit Name INPUT_POWER_READBACK_LSB Settings Description See Register 0x2D. INPUT POWER READBACK MSB REGISTER Address: 0x2D, Reset: 0x00, Name: INPUT_POWER_READBACK_MSB Table 59. Bit Descriptions for INPUT_POWER_READBACK_MSB Bits [4:0] Bit Name INPUT_POWER_READBACK_MSB Settings Description Input signal average power readback. Rev. 0 | Page 53 of 64 AD9142 Data Sheet NCO CONTROL REGISTER Address: 0x30, Reset: 0x00, Name: NCO_CTRL Table 60. Bit Descriptions for NCO_CTRL Bits 6 5 4 1 0 Bit Name NCO_FRAME_UPDATE_ACK SPI_NCO_PHASE_RST_ACK SPI_NCO_PHASE_RST_REQ NCO_SPI_UPDATE_ACK NCO_SPI_UPDATE_REQ Settings Description Frequency tuning word update request from frame. NCO phase SPI reset acknowledge. NCO phase SPI reset request. Frequency tuning word update acknowledge. Frequency tuning word update request from SPI. Reset 0x0 0x0 0x0 0x0 0x0 Access R R RW R RW Reset 0x00 Access RW Reset 0x00 Access RW Reset 0x00 Access RW Reset 0x10 Access RW Reset 0x00 Access RW NCO_FREQ_TUNING_WORD0 REGISTER Address: 0x31, Reset: 0x00, Name: NCO_FREQ_TUNING_WORD0 Table 61. Bit Descriptions for NCO_FREQ_TUNING_WORD0 Bits [7:0] Bit Name NCO_FTW0 Settings Description See Register 0x34. NCO_FREQ_TUNING_WORD1 REGISTER Address: 0x32, Reset: 0x00, Name: NCO_FREQ_TUNING_WORD1 Table 62. Bit Descriptions for NCO_FREQ_TUNING_WORD1 Bits [7:0] Bit Name NCO_FTW1 Settings Description See Register 0x34. NCO_FREQ_TUNING_WORD2 REGISTER Address: 0x33, Reset: 0x00, Name: NCO_FREQ_TUNING_WORD2 Table 63. Bit Descriptions for NCO_FREQ_TUNING_WORD2 Bits [7:0] Bit Name NCO_FTW2 Settings Description See Register 0x34. NCO_FREQ_TUNING_WORD3 REGISTER Address: 0x34, Reset: 0x10, Name: NCO_FREQ_TUNING_WORD3 Table 64. Bit Descriptions for NCO_FREQ_TUNING_WORD3 Bits [7:0] Bit Name NCO_FTW3 Settings Description FTW[31:0] is the 32-bit frequency tuning word that determines the frequency of the complex carrier generated by the on-chip NCO. The frequency is not updated when the FTW registers are written. The values are only updated when a serial port update or frame update is initialized in Register 0x30. It is in twos complement format. NCO_PHASE_OFFSET0 REGISTER Address: 0x35, Reset: 0x00, Name: NCO_PHASE_OFFSET0 Table 65. Bit Descriptions for NCO_PHASE_OFFSET0 Bits [7:0] Bit Name NCO_PHASE_OFFSET_LSB Settings Description See Register 0x36. Rev. 0 | Page 54 of 64 Data Sheet AD9142 NCO_PHASE_OFFSET1 REGISTER Address: 0x36, Reset: 0x00, Name: NCO_PHASE_OFFSET1 Table 66. Bit Descriptions for NCO_PHASE_OFFSET1 Bits [7:0] Bit Name NCO_PHASE_OFFSET_MSB Settings Description This register sets the initial phase of the complex carrier signal upon reset. The phase offset spans from 0 degrees to 360 degrees. Each bit represents an offset of 0.0055 degrees. This value is in twos complement format. Reset 0x00 Access RW Reset 0x00 Access RW Reset 0x0 Access RW Reset 0x00 Access RW Reset 0x00 Access RW Reset 0x00 Access RW IQ_PHASE_ADJ0 REGISTER Address: 0x37, Reset: 0x00, Name: IQ_PHASE_ADJ0 Table 67. Bit Descriptions for IQ_PHASE_ADJ0 Bits [7:0] Bit Name IQ_PHASE_ADJ_LSB Settings Description See Register 0x38. IQ_PHASE_ADJ1 REGISTER Address: 0x38, Reset: 0x000, Name: IQ_PHASE_ADJ1 Table 68. Bit Descriptions for IQ_PHASE_ADJ1 Bits [4:0] Bit Name IQ_PHASE_ADJ_MSB Settings Description IQ phase adjust, Bits[12:0], is used to insert a phase offset between the I and Q datapaths. It provides an adjustment range of ±14 degrees with a step of 0.0035 degrees. This value is in twos complement. See the Quadrature Phase Adjustment section for more information. IDAC_DC_OFFSET0 REGISTER Address: 0x3B, Reset: 0x00, Name: IDAC_DC_OFFSET0 Table 69. Bit Descriptions for IDAC_DC_OFFSET0 Bits [7:0] Bit Name IDAC_DC_OFFSET_LSB Settings Description See Register 0x3C. IDAC_DC_OFFSET1 REGISTER Address: 0x3C, Reset: 0x00, Name: IDAC_DC_OFFSET1 Table 70. Bit Descriptions for IDAC_DC_OFFSET1 Bits [7:0] Bit Name IDAC_DC_OFFSET_MSB Settings Description IDAC DC offset, Bits[15:0], is a dc value that is added directly to the sample values written to the IDAC. QDAC_DC_OFFSET0 REGISTER Address: 0x3D, Reset: 0x00, Name: QDAC_DC_OFFSET0 Table 71. Bit Descriptions for QDAC_DC_OFFSET0 Bits [7:0] Bit Name QDAC_DC_OFFSET_LSB Settings Description See Register 0x3E. Rev. 0 | Page 55 of 64 AD9142 Data Sheet QDAC_DC_OFFSET1 REGISTER Address: 0x3E, Reset: 0x00, Name: QDAC_DC_OFFSET1 Table 72. Bit Descriptions for QDAC_DC_OFFSET1 Bits [7:0] Bit Name QDAC_DC_OFFSET_MSB Settings Description QDAC DC offset, Bits[15:0], is a dc value that is added directly to the sample values written to the QDAC. Reset 0x00 Access RW Reset 0x20 Access RW Reset 0x20 Access RW Reset 0x01 Access RW Reset 0x0 Access RW 0x0 R 0x01 RW IDAC_GAIN_ADJ REGISTER Address: 0x3F, Reset: 0x20, Name: IDAC_GAIN_ADJ Table 73. Bit Descriptions for IDAC_GAIN_ADJ Bits [5:0] Bit Name IDAC_GAIN_ADJ Settings Description This register is the 6-bit digital gain adjust on the I channel. The bit weighting is MSB = 20, LSB = 2−5, which yields a multiplier range of 0 to 2 or −∞ to 6 dB. The default gain setting is 0x20, which maps to unity gain (0 dB). QDAC_GAIN_ADJ REGISTER Address: 0x40, Reset: 0x20, Name: QDAC_GAIN_ADJ Table 74. Bit Descriptions for QDAC_GAIN_ADJ Bits [5:0] Bit Name QDAC_GAIN_ADJ Settings Description This register is the 6-bit digital gain adjust on the Q channel. The bit weighting is MSB = 20, LSB = 2−5, which yields a multiplier range of 0 to 2 or −∞ to 6 dB. The default gain setting is 0x20, which maps to unity gain (0 dB). GAIN STEP CONTROL0 REGISTER Address: 0x41, Reset: 0x01, Name: GAIN_STEP_CTRL0 Table 75. Bit Descriptions for GAIN_STEP_CTRL0 Bits [5:0] Bit Name RAMP_UP_STEP Settings Description This register sets the step size of the increasing gain. The digital gain increases by the configured amount in every four DAC cycles until the gain reaches the setting in I/QDAC_GAIN_ADJ (Register 0x3F and Register 0x40). The bit weighting is MSB = 21, LSB = 2−4. Note that the value in this register should not be greater than the values in the I/QDAC_GAIN_ADJ (Register 0x3F and Register 0x40). GAIN STEP CONTROL1 REGISTER Address: 0x42, Reset: 0x01, Name: GAIN_STEP_CTRL1 Table 76. Bit Descriptions for GAIN_STEP_CTRL1 Bits 7 Bit Name DAC_OUTPUT_STATUS 6 DAC_OUTPUT_ON [5:0] RAMP_DOWN_STEP Settings Description This bit indicates the DAC output on/off status. When the DAC output is automatically turned off, this bit is 1. In the case where the DAC output is automatically turned off in the input power protection mode or TX enable mode, this register allows for turning on the DAC output manually. It is a self clear bit. This register sets the step size of the decreasing gain. The digital gain decreases by the configured amount in every four DAC cycles until the gain reaches zero. The bit weighting is MSB = 21, LSB = 2−4. Note that the value in this register should not be greater than the values in the I/QDAC_GAIN_ADJ (Register 0x3F and Register 0x40). Rev. 0 | Page 56 of 64 Data Sheet AD9142 TX ENABLE CONTROL REGISTER Address: 0x43, Reset: 0x07, Name: TX_ENABLE_CTRL Table 77. Bit Descriptions for TX_ENABLE_CTRL Bits 2 Bit Name TXENABLE_GAINSTEP_EN 1 TXENABLE_SLEEP_EN 0 TXENABLE_POWER_DOWN_EN Settings Description DAC output gradually turns on/off under the control of the TXENABLE signal from the TXEN pin according to the settings in Register 0x41 and Register 0x42. When set to 1, the device is put in sleep mode when the TXENABLE signal from the TXEN pin is low. When set to 1, the device is put in power down mode when TXENABLE signal from the TXEN pin is low. Reset 0x1 Access RW 0x1 RW 0x1 RW Reset 0x1 Access RW 0x1 RW 0x1 RW 0x1 RW Reset 0xFF Access RW Reset 0x0 0x7 Access RW RW DAC OUTPUT CONTROL REGISTER Address: 0x44, Reset: 0x8F, Name: DAC_OUTPUT_CTRL Table 78. Bit Descriptions for DAC_OUTPUT_CTRL Bits 7 Bit Name DAC_OUTPUT_CTRL_EN Settings 3 FIFO_WARNING_SHUTDOWN_EN 2 OVERTHRESHOLD_SHUTDOWN_EN 0 FIFO_ERROR_SHUTDOWN_EN Description Enable the DAC output control. This bit needs to be set to 1 to enable the rest of the bits in this register. When this bit and Bit 7 are both high, if a FIFO warning occurs, the DAC output shuts down automatically. By default, this function is on. The DAC output is turned off when the input average power is greater than the predefined threshold. The DAC output is turned off when the FIFO reports warnings. DATA RECEIVER TEST CONTROL REGISTER Address: 0x5E, Reset: 0xFF, Name: DATA_RX_CTRL0 Table 79. Bit Descriptions for DATA_RX_CTRL0 Bits [7:0] Bit Name DLY_TAP_LSB Settings Description See Register 0x5F[2:0]. DATA RECEIVER TEST CONTROL REGISTER Address: 0x5F, Reset: 0x07, Name: DATA_RX_CTRL1 Table 80. Bit Descriptions for DATA_RX_CTRL1 Bits 3 [2:0] Bit Name DLYLINE_EN DLY_TAP_MSB Settings 00 01 10 11 Description 1 = Enable the data interface. Four available delay settings. See the Interface Delay Line section for more information. 0x000 0x007 0x07F 0x5FF Rev. 0 | Page 57 of 64 AD9142 Data Sheet DEVICE CONFIGURATION0 REGISTER Address: 0x79, Reset: 0x00, Name: DEVICE_CONFIG0 Table 81. Bit Descriptions for DEVICE_CONFIG0 Bits [7:0] Bit Name DEVICE_ CONFIGURATION0 Settings 0x18 Description Recommended setting for device start-up configuration Reset 0x00 Access RW Description Chip version Reset 0x05 Access R Reset 0x00 Access RW Reset 0x00 Access RW VERSION REGISTER Address: 0x7F, Reset: 0x05, Name: Version Table 82. Bit Descriptions for Version Bits [7:0] Bit Name Version Settings DEVICE CONFIGURATION1 REGISTER Address: 0x80, Reset: 0x00, Name: DEVICE_CONFIG1 Table 83. Bit Descriptions for DEVICE_CONFIG1 Bits [7:0] Bit Name DEVICE_ CONFIGURATION1 Settings 0xAD Description Recommended setting for device start-up configuration DEVICE CONFIGURATION2 REGISTER Address: 0xE1, Reset: 0x00, Name: DEVICE_CONFIG2 Table 84. Bit Descriptions for DEVICE_CONFIG2 Bits [7:0] Bit Name DEVICE_ CONFIGURATION2 Settings 0x1A Description Recommended setting for device start-up configuration Rev. 0 | Page 58 of 64 Data Sheet AD9142 DAC LATENCY AND SYSTEM SKEWS DACCLK/8 DIV 2 DACCLK/4 DACCLK DIV 2 DIV 2 DACCLK/2 FIFO RdPtr DATA INTERFACE FIFO HB2 HB1 OTHER DIGITAL FUNCTIONALITIES HB3 I AND Q DAC FIFO WrPtr DCI VARYING LATENCY FIXED LATENCY VARYING LATENCY 10930-064 FIXED LATENCY Figure 60. Breakdown of Pipeline Latencies Figure 61 is an example of FIFO latency variation. The latency in Case 2 is two data cycles longer than that in Case 1. If other latencies are the same, the skew between the DAC outputs in these two cases is, likewise, two data cycles. Therefore, to keep a constant FIFO latency, the FIFO depth needs to be reset to a predefined value. Theoretically, any value other than 0 is valid but typically it is set to 4 to maximize the capacity of absorbing the rate fluctuation between the read and write side. FIFO WrPtr DATA 1 FIFO WrPtr DATA 1 FIFO RdPtr DATA 2 FIFO LATENCY VARIATION There are eight data slots in the FIFO. The FIFO read and write pointers circulate the FIFO from Slot 0 to Slot 7 and back to Slot 0. The FIFO depth is defined as the number of FIFO slots that are required for the read pointer to catch the write pointer. It is also the time a particular piece of data stays in the FIFO from the point that it is written into the FIFO to the point where it is read out from the FIFO. Therefore, the latency of the FIFO is equivalent to its depth. FIFO DATA 0 DATA 2 DATA 3 DATA 3 DATA 4 DATA 4 DATA 5 DATA 5 DATA 6 DATA 6 DATA 7 DATA 7 CASE 1: LATENCY = 4 DCI CYCLES CASE 2: LATENCY = 6 DCI CYCLES FIFO RdPtr Figure 61. Example of FIFO Latency Difference Figure 62 shows two equivalent cases of FIFO latency of four data cycles. Although neither the read nor the write pointer match each other in these two cases, the FIFO depth is the same in both cases. Also, note that the beginning slots of the data stream in the two cases are not the same, but the read and write pointers point to the same piece of data in both cases. This does not affect the alignment accuracy of the DAC outputs as long as the data and the DCIs are well aligned at multiple devices. FIFO FIFO DATA 0 DATA 5 FIFO WrPtr DATA 1 DATA 2 FIFO RdPtr DATA 3 DATA 4 FIFO WrPtr DATA 6 DATA 7 DATA 0 LATENCY = 4 DCI CYCLES DATA 1 DATA 5 DATA 2 DATA 6 DATA 3 DATA 7 DATA 4 Figure 62. Example of Equal FIFO Latencies Rev. 0 | Page 59 of 64 FIFO RdPtr 10930-066 DACs, like any other devices with internal multiphase clocks, have an inherent pipeline latency variation. Figure 60 shows the breakdown of pipeline latencies in the AD9142. The highlighted section, including the FIFO and the clock generation circuitry, is where the pipeline latencies vary. Upon each power-on, the status of both the FIFO and the clock generation state machine is arbitrary. This leads to varying latency in these two blocks. FIFO DATA 0 10930-065 DAC LATENCY VARIATIONS AD9142 Data Sheet CLOCK GENERATION LATENCY VARIATION CORRECTING SYSTEM SKEWS The state machine of the clock generation circuitry is another source of latency variations; this type of latency variation results from inherent phase uncertainty of the static frequency dividers. The divided down clock can be high or low at the rising edge of the input clock, unless specifically forced to a known state. This means that whenever there is interpolation (when slower clocks need to be internally generated by dividing down the DACCLK), there is an inherent latency variation in the DAC. Figure 63 is an example of this latency variation in 2× interpolation. There are two phase possibilities in the DACCLK/2 clock. The DACCLK/2 clock is used to read data from the FIFO and to drive the interpolation filter. Regardless of which clock edge is used to drive the digital circuit, there is a latency of one DAC clock cycle between Case 1 and Case 2 (see Figure 62). Because the power-on state arbitrarily falls in one of the two cases, the phase uncertainty of the divider appears as a varying skew between two DAC outputs. Generally, it is assumed that the input data and the DCI among multiple devices are well aligned to each other. Depending on the system design, the data and DCI being input into each DAC can originate from various FPGAs or ASICs. Without synchronizing the data sources, the output of one data source can be skewed from that of another. The alignment between multiple data sources can also drift over temperature. HB1 HB2 HB3 Figure 64 shows an example of a 2-channel transmitter with two data sources and two dual DACs. A constant but unknown phase offset appears between the outputs of the DAC devices, even if the DAC does not introduce any latency variations. The multidevice synchronization in the AD9142 can be used to compensate the skew due to misalignment of the data sources by resetting the two sides of the FIFO independently through two external reference clocks: the frame and the sync clock. The offset between the two data sources is then absorbed by the FIFO and clock generation block in the DAC. For more information about using the multidevice synchronization function, refer to the Synchronization Implementation section. DCI FRAME DAC 16-BIT DATA DATA GEN MATCH SYNC LINE FOR ALL DATA GEN DACCLK DACCLK/2 (CASE 1) 10930-067 DACCLK/2 (CASE 2) LATENCY VARIATION = 1 DACCLK CYCLE Figure 63. Latency Variation in 2× Interpolation from Clock Generation DCI FRAME DAC 16-BIT DATA DCI FRAME DAC 16-BIT DATA DATA GEN DCI FRAME DAC 16-BIT DATA 2 SYNC CLOCK DATA SKEW Figure 64. DAC Output Skew from Skewed Input Data and DCI Rev. 0 | Page 60 of 64 10930-068 4 MASTER REF CLOCK Data Sheet AD9142 PACKAGING AND ORDERING INFORMATION OUTLINE DIMENSIONS 10.10 10.00 SQ 9.90 0.60 0.42 0.24 0.60 0.42 0.24 0.30 0.23 0.18 55 54 72 1 PIN 1 INDICATOR PIN 1 INDICATOR 9.85 9.75 SQ 9.65 0.50 BSC 0.50 0.40 0.30 18 37 BOTTOM VIEW 0.80 MAX 0.65 TYP 0.05 MAX 0.02 NOM COPLANARITY 0.08 0.20 REF SEATING PLANE 0.25 MIN 8.50 REF FOR PROPER CONNECTION OF THE EXPOSED PAD, REFER TO THE PIN CONFIGURATION AND FUNCTION DESCRIPTIONS SECTION OF THIS DATA SHEET. COMPLIANT TO JEDEC STANDARDS MO-220-VNND-4 06-25-2012-A 1.00 0.85 0.80 19 36 TOP VIEW 12° MAX 6.15 6.00 SQ 5.85 EXPOSED PAD Figure 65. 72-Lead Lead Frame Chip Scale Package [LFCSP_VQ] 10 mm × 10 mm Body, Very Thin Quad (CP-72-7) Dimensions shown in millimeters ORDERING GUIDE Model 1 AD9142BCPZ AD9142BCPZRL AD9142-M5372-EBZ AD9142-M5375-EBZ 1 Temperature Range −40°C to +85°C −40°C to +85°C Package Description 72-lead LFCSP_VQ 72-lead LFCSP_VQ Evaluation Board Connected to ADL5372 Modulator Evaluation Board Connected to ADL5375 Modulator Z = RoHS Compliant Part. Rev. 0 | Page 61 of 64 Package Option CP-72-7 CP-72-7 AD9142 Data Sheet NOTES Rev. 0 | Page 62 of 64 Data Sheet AD9142 NOTES Rev. 0 | Page 63 of 64 AD9142 Data Sheet NOTES ©2012 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D10930-0-11/12(0) Rev. 0 | Page 64 of 64 Mouser Electronics Authorized Distributor Click to View Pricing, Inventory, Delivery & Lifecycle Information: Analog Devices Inc.: AD9142BCPZ AD9142BCPZRL