LINER LTC4085EDE-1-PBF Usb power manager with ideal diode controller and 4.1v li-ion charger Datasheet

LTC4085-1
USB Power Manager with
Ideal Diode Controller and
4.1V Li-Ion Charger
DESCRIPTIO
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FEATURES
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The LTC®4085-1 is a USB power manager and Li-Ion
battery charger designed for portable battery-powered
applications. The part controls the total current used by
the USB peripheral for operation and battery charging.
The total input current can be limited to 20% or 100%
of a programmed value up to 1.5A (typically 100mA or
500mA). Battery charge current is automatically reduced
such that the sum of the load current and charge current
does not exceed the programmed input current limit.
Seamless Transition Between Input Power Sources:
Li-Ion Battery, USB and 5V Wall Adapter
215mΩ Internal Ideal Diode Plus Optional External
Ideal Diode Controller Provide Low Loss PowerPathTM
When Wall Adapter/USB Input Not Present
Load Dependent Charging Guarantees Accurate USB
Input Current Compliance
4.1V Float Voltage Improves Battery Life Span and
High Temperature Safety Margin
Constant-Current/Constant-Voltage Operation with
Thermal Feedback to Maximize Charging Rate Without
Risk of Overheating*
Selectable 100% or 20% Input Current Limit
(e.g., 500mA/100mA)
Battery Charge Current Independently Programmable
Up to 1.2A
Preset 4.1V Charge Voltage with 0.8% Accuracy
C/10 Charge Current Detection Output
Tiny (4mm × 3mm × 0.75mm) 14-Lead DFN Package
The LTC4085-1 includes a complete constant-current/
constant-voltage linear charger for single cell Li-Ion batteries. This 4.1V version of the standard LTC4085 is intended
for applications which will be operated or stored above
approximately 60°C. Under these conditions, a reduced
float voltage will trade-off initial cell capacity for the benefit
of increased capacity retention over the life of the battery. A
reduced float voltage also minimizes swelling in prismatic
and polymer cells, and avoids open CID (pressure fuse)
in cylindrical cells.
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APPLICATIO S
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The LTC4085-1 also includes a programmable termination timer, automatic recharging, an end-of-charge status
output and an NTC thermistor.
Portable USB Devices: Cameras, MP3 Players, PDAs
, LT, LTC and LTM are registered trademarks of Linear Technology Corporation.
PowerPath is a trademark of Linear Technology Corporation. All other trademarks are the
property of their respective owners. Protected by U.S. Patents, including 6522118, 6700364.
Other patents pending.
The LTC4085-1 is available in a 14-lead low profile 4mm
× 3mm DFN package.
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TYPICAL APPLICATIO
ILOAD
5V WALL
ADAPTER
INPUT
4.7μF
600
4.7μF
1k
IIN
Input and Battery Current vs Load Current
RPROG = 100k, RCLPROG = 2k
510Ω
IN
WALL
500
SUSPEND USB POWER
SUSP
ACPR
400
100mA 500mA SELECT
HPWR
OUT
PROG
LTC4085-1
*
CHRG
NTC
GND
2k
10k
ILOAD
300
IBAT
(CHARGING)
200
0
IBAT
TIMER
+
10k
100k
IIN
100
BAT
CLPROG
VNTC
GATE
CURRENT (mA)
5V (NOM)
FROM USB
CABLE VBUS
TO LDOs,
REGs, ETC
0.1μF
0
* OPTIONAL - TO LOWER
IBAT
(DISCHARGING)
WALL = 0V
–100
100
200
400
300
ILOAD (mA)
500
600
40851 TA01b
IDEAL DIODE IMPEDANCE
40851 TA01
40851f
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LTC4085-1
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AXI U RATI GS
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ABSOLUTE
PI CO FIGURATIO
(Notes 1, 2, 3, 4, 5)
Terminal Voltage
IN, OUT
t < 1ms and Duty Cycle < 1%................... –0.3V to 7V
Steady State ............................................. –0.3V to 6V
BAT, CHRG, HPWR, SUSP, WALL, ACPR....... –0.3V to 6V
NTC, TIMER, PROG, CLPROG .......–0.3V to (VCC + 0.3V)
Pin Current (Steady State)
IN, OUT, BAT (Note 6)...............................................2.5A
Operating Temperature Range.................. –40°C to 85°C
Maximum Operating Junction Temperature .......... 110°C
Storage Temperature Range................... –65°C to 125°C
TOP VIEW
IN
1
14 BAT
OUT
2
13 GATE
CLPROG
3
HPWR
4
SUSP
5
10 ACPR
TIMER
6
9 VNTC
WALL
7
8 NTC
12 PROG
15
11 CHRG
DE PACKAGE
14-LEAD (4mm × 3mm) PLASTIC DFN
TJMAX = 125°C, θJA = 40°C/W
EXPOSED PAD (PIN 15) IS GND, MUST BE CONNECTED TO PCB
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ORDER I FOR ATIO
LEAD FREE FINISH
TAPE AND REEL
PART MARKING
PACKAGE DESCRIPTION
TEMPERATURE RANGE
LTC4085EDE-1#PBF
LTC4085EDE-1#TRPBF
40851
14-Lead (4mm × 3mm) Plastic DFN
–40°C to 85°C
Consult LTC Marketing for parts specified with wider operating temperature ranges.
Consult LTC Marketing for information on non-standard lead based finish parts.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/
ELECTRICAL CHARACTERISTICS
The ● indicates specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VIN = 5V, VBAT = 3.7V, HPWR = 5V, WALL = 0V, RPROG = 100k,
RCLPROG = 2k, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
MIN
VIN
Input Supply Voltage
IN and OUT
4.35
VBAT
Input Voltage
BAT
IIN
Input Supply Current
IBAT = 0 (Note 7)
Suspend Mode; SUSP = 5V
Suspend Mode; SUSP = 5V, WALL = 5V,
VOUT = 4.8V
●
●
●
IOUT
Output Supply Current
VOUT = 5V, VIN = 0V, NTC = VNTC
IBAT
Battery Drain Current
VUVLO
ΔVUVLO
TYP
MAX
UNITS
5.5
V
4.3
V
0.5
50
60
1.2
100
110
mA
μA
μA
●
0.7
1.4
mA
VBAT = 4.3V, Charging Stopped
Suspend Mode; SUSP = 5V
VIN = 0V, BAT Powers OUT, No Load
●
●
●
15
22
60
27
35
100
μA
μA
μA
Input or Output Undervoltage Lockout
VIN Powers Part, Rising Threshold
VOUT Powers Part, Rising Threshold
●
●
3.8
2.95
4
3.15
V
V
Input or Output Undervoltage Lockout
VIN Rising – VIN Falling
or VOUT Rising – VOUT Falling
ILIM
Current Limit
RCLPROG = 2k (0.1%), HPWR = 5V
RCLPROG = 2k (0.1%), HPWR = 0V
IIN(MAX)
Maximum Input Current Limit
(Note 8)
2.4
A
RON
ON Resistance VIN to VOUT
IOUT = 100mA Load
215
mΩ
3.6
2.75
130
mV
Current Limit
●
●
475
90
500
100
525
110
mA
mA
40851f
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LTC4085-1
ELECTRICAL CHARACTERISTICS
The ● indicates specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VIN = 5V, VBAT = 3.7V, HPWR = 5V, WALL = 0V, RPROG = 100k,
RCLPROG = 2k, unless otherwise noted.
SYMBOL
PARAMETER
CONDITIONS
VCLPROG
CLPROG Pin Voltage
RPROG = 2k
RPROG = 1k
ISS
Soft Start Inrush Current
IN or OUT
VCLEN
Input Current Limit Enable Threshold
Voltage
(VIN – VOUT) VIN Rising
(VIN – VOUT) VIN Falling
VFLOAT
Regulated Output Voltage
IBAT = 2mA
IBAT = 2mA, (0°C – 85°C)
IBAT
Current Mode Charge Current
RPROG = 100k (0.1%), No Load
RPROG = 50k (0.1%), No Load
IBAT(MAX)
Maximum Charge Current
(Note 8)
●
●
MIN
TYP
MAX
UNITS
0.98
0.98
1
1
1.02
1.02
V
V
5
mA/μs
20
50
-60
80
mV
mV
4.065
4.058
4.1
4.1
4.135
4.142
V
V
465
900
500
1000
535
1080
mA
mA
Battery Charger
●
●
1.5
A
VPROG
PROG Pin Voltage
RPROG = 100k
RPROG = 50k
●
●
kEOC
Ratio of End-of-Charge Current to
Charge Current
VBAT = VFLOAT (4.1V)
●
ITRIKL
Trickle Charge Current
VBAT = 2V, RPROG = 100k (0.1%)
VTRIKL
Trickle Charge Threshold Voltage
VCEN
Charger Enable Threshold Voltage
(VOUT – VBAT) Falling; VBAT = 4V
(VOUT – VBAT) Rising; VBAT = 4V
VRECHRG
Recharge Battery Threshold Voltage
VFLOAT – VRECHRG
tTIMER
TIMER Accuracy
VBAT = 4.3V
Recharge Time
Percent of Total Charge Time
50
%
Low Battery Trickle Charge Time
Percent of Total Charge Time, VBAT < 2.8V
25
%
105
°C
TLIM
●
0.98
0.98
1
1
1.02
1.02
V
V
0.085
0.1
0.11
mA/mA
35
50
60
mA
2.75
2.9
3
V
55
80
●
65
100
-10
Junction Temperature in Constant
Temperature Mode
mV
mV
135
mV
10
%
Internal Ideal Diode
RFWD
Incremental Resistance, VON Regulation
IBAT = 100mA
125
mΩ
RDIO(ON)
ON Resistance VBAT to VOUT
IBAT = 600mA
215
mΩ
VFWD
Voltage Forward Drop (VBAT – VOUT)
IBAT = 5mA
IBAT = 100mA
IBAT = 600mA
VOFF
Diode Disable Battery Voltage
2.8
V
IFWD
Load Current Limit, for VON Regulation
550
mA
ID(MAX)
Diode Current Limit
2.2
A
20
mV
●
10
30
55
160
50
mV
mV
mV
External Ideal Diode
VFWD,EDA
External Ideal Diode Forward Voltage
VGATE = 1.85V; IGATE = 0
Logic
VOL
Output Low Voltage CHRG, ACPR
ISINK = 5mA
●
VIH
Input High Voltage
SUSP, HPWR Pin
●
VIL
Input Low Voltage
SUSP, HPWR Pin
●
IPULLDN
Logic Input Pull-Down Current
SUSP, HPWR
0.1
0.4
1.2
V
V
0.4
2
V
μA
40851f
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LTC4085-1
ELECTRICAL CHARACTERISTICS
The ● indicates specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VIN = 5V, VBAT = 3.7V, HPWR = 5V, WALL = 0V, RPROG = 100k,
RCLPROG = 2k, unless otherwise noted.
SYMBOL
PARAMETER
VCHG(SD)
Charger Shutdown Threshold Voltage
on TIMER
ICHG(SD)
Charger Shutdown Pull-Up Current
on TIMER
VWAR
CONDITIONS
MIN
TYP
MAX
UNITS
●
0.14
VTIMER = 0V
●
5
14
Absolute Wall Input Threshold Voltage
VWALL Rising Threshold
●
4.15
4.25
VWAF
Absolute Wall Input Threshold Voltage
VWALL Falling Threshold
VWDR
Delta Wall Input Threshold Voltage
VWALL – VBAT Rising Threshold
VWDF
Delta Wall Input Threshold Voltage
VWALL – VBAT Falling Threshold
IWALL
Wall Input Current
VWALL = 5V
VVNTC
VNTC Bias Voltage
IVNTC = 500μA
INTC
NTC Input Leakage Current
VNTC = 1V
VCOLD
Cold Temperature Fault Threshold
Voltage
Rising Threshold
Hysteresis
0.738 • VVNTC
0.018 • VVNTC
V
V
VHOT
Hot Temperature Fault Threshold
Voltage
Falling Threshold
Hysteresis
0.326 • VVNTC
0.015 • VVNTC
V
V
VDIS
NTC Disable Voltage
NTC Input Voltage to GND (Falling)
Hysteresis
0.4
μA
4.35
3.12
0
V
V
75
●
V
mV
25
60
mV
75
150
μA
NTC
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: VCC is the greater of VIN, VOUT or VBAT.
Note 3: All voltage values are with respect to GND.
Note 4: This IC includes overtemperature protection that is intended
to protect the device during momentary overload conditions. Junction
temperatures will exceed 110°C when overtemperature protection is
active. Continuous operation above the specified maximum operating
junction temperature may result in device degradation or failure.
●
4.4
4.85
0
●
75
100
35
V
±1
125
μA
mV
mV
Note 5: The LTC4085E-1 is guaranteed to meet specified performance
from 0° to 85°C. Specifications over the –40°C to 85°C operating
temperature range are assured by design, characterization and correlation
with statistical process controls.
Note 6: Guaranteed by long term current density limitations.
Note 7: Total input current is equal to this specification plus 1.002 • IBAT
where IBAT is the charge current.
Note 8: Accuracy of programmed current may degrade for currents greater
than 1.5A.
40851f
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LTC4085-1
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TYPICAL PERFOR A CE CHARACTERISTICS
Input Supply Current
vs Temperature
800
700
70
VIN = 5V
VBAT = 4.2V
RPROG = 100k
RCLPROG = 2k
100
VIN = 5V
VBAT = 4.2V
60 R
PROG = 100k
RCLPROG = 2k
50 SUSP = 5V
IIN (μA)
600
IIN (μA)
Battery Drain Current
vs Temperature
(BAT Powers OUT, No Load)
Input Supply Current vs
Temperature (Suspend Mode)
500
400
VIN = 0V
90 VBAT = 4.2V
80
70
IBAT (μA)
900
TA = 25°C unless otherwise noted.
40
30
300
50
40
30
20
200
20
10
100
0
–50
–25
0
25
50
TEMPERATURE (°C)
100
75
10
0
–50
25
50
25
0
TEMPERATURE (°C)
75
40851 G01
0
–50
100
525
1.2
VIN = 5V
108 VBAT = 3.7V
RPROG = 100k
106 R
CLPROG = 2k
104
VIN = 5V
RCLPROG = 2k
1.0
VCLPROG (V)
IIN (mA)
100
75
CLPROG Pin Voltage
vs Temperature
110
VIN = 5V
VBAT = 3.7V
RPROG = 100k
515 RCLPROG = 2k
495
25
50
0
TEMPERATURE (°C)
40851 G03
Input Current Limit
vs Temperature, HPWR = 0V
505
–25
40851 G02
Input Current Limit
vs Temperature, HPWR = 5V
IIN (mA)
60
102
100
98
HPWR = 5V
0.8
0.6
0.4
96
485
94
475
–50
90
–50
HPWR = 0V
0.2
92
–25
0
25
50
TEMPERATURE (°C)
75
100
–25
25
50
0
TEMPERATURE (°C)
75
40851 G04
0
25
50
TEMPERATURE (°C)
4.20
VIN = 5V
= 4.2V
V
1.015 BAT
RPROG = 100k
= 2k
R
1.010 CLPROG
75
100
40851 G06
Battery Regulation (Float)
Voltage vs Temperature
VFLOAT Load Regulation
1.020
4.120
RPROG = 34k
4.115
4.15
VIN = 5V
IBAT = 2mA
4.110
1.005
1.000
0.995
VFLOAT (V)
4.10
VFLOAT (V)
VPROG (V)
–25
40851 G05
PROG Pin Voltage
vs Temperature
4.05
4.105
4.100
4.095
4.00
4.090
0.990
3.95
0.985
0.980
–50
0
–50
100
4.085
3.90
–25
0
50
25
TEMPERATURE (°C)
75
100
40851 G07
0
200
400
600
IBAT (mA)
800
1000
40851 G08
4.080
–50
–25
0
50
25
TEMPERATURE (°C)
75
100
40851 G09
40851f
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LTC4085-1
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TYPICAL PERFOR A CE CHARACTERISTICS
Battery Current and Voltage
vs Time
600
ILOAD = 400mA
250
IBAT (mA)
RON (mΩ)
175
300
3
75
2
100
C/10
400
300
200
100 VIN = 5V
VBAT = 3.5V
θJA = 50°C/W
0
50
25
75
–50 –25
0
TEMPERATURE (°C)
TERMINATION 1
100
TIME (min)
0
200
150
40851 G10
600
4085 G112
1000
120
VIN = 5V
VOUT = NO LOAD
500 RPROG = 100k
RCLPROG = 2k
HPWR = 5V
400
VBAT = 3.7V
900 VIN = 0V
800
700
IOUT (mA)
IBAT (mA)
VIN = 5V
VOUT = NO LOAD
100 RPROG = 100k
RCLPROG = 2k
HPWR = 0V
80
60
200
40
100
20
600
500
400
300
–50°C
0°C
50°C
100°C
200
100
0
0
0.5
1
1.5
2 2.5
VBAT (V)
3.5
3
4
0
0
4.5
0
0.5
1
1.5
2 2.5
VBAT (V)
3
3.5
40851 G13
0
4.5
50
700
3500
3500
600
3000
IOUT (mA)
IOUT
300
2500
2000
1500
RDIO
200
1000
100
500
0
0
50
100
VFWD (mV)
150
IOUT (mA)
800
5000
VBAT = 3.7V
4500 VIN = 0V
Si2333 PFET
4000
400
200
40851 G16
0
200
150
Ideal Diode Resistance and
Current vs Forward Voltage with
External Device
5000
VBAT = 3.7V
4500 VIN = 0V
Si2333 PFET
4000
VBAT = 3.7V
900 VIN = 0V
500
100
VFWD (mV)
40851 G15
Ideal Diode Current vs Forward
Voltage and Temperature with
External Device
1000
IOUT (mA), RDIO (mΩ)
4
40851 G14
Ideal Diode Resistance and
Current vs Forward Voltage
(No External Device)
125
Ideal Diode Current vs Forward
Voltage and Temperature
(No External Device)
Charging from USB, Low Power,
IBAT vs VBAT
300
100
40851 G11
Charging from USB, IBAT vs VBAT
IBAT (mA)
500
4
400mAhr CELL
100 VIN = 5V
RPROG = 100k
RCLPROG = 2.1k
0
50
0
150
0
25
50
TEMPERATURE (°C)
5
400
200
–25
600
VBAT AND VCHRG (V)
VIN = 5.5V
125
–50
6
VBAT
VIN = 5V
200
CHRG
IBAT
500
VIN = 4.5V
225
Charge Current vs Temperature
(Thermal Regulation)
IBAT (mA)
Input RON vs Temperature
275
TA = 25°C unless otherwise noted.
3000
2500
2000
1500
–50°C
0°C
50°C
100°C
0
20
60
40
VFWD (mV)
80
100
40851 G17
1000
500
0
0
20
60
40
VFWD (mV)
80
100
40851 G18
40851f
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LTC4085-1
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TYPICAL PERFOR A CE CHARACTERISTICS
Input Connect Waveforms
Input Disconnect Waveforms
VIN
5V/DIV
VOUT
5V/DIV
VIN
5V/DIV
VOUT
5V/DIV
IIN
0.5A/DIV
IBAT
0.5A/DIV
IIN
0.5A/DIV
IBAT
0.5A/DIV
1ms/DIV
VBAT = 3.85V
IOUT = 100mA
TA = 25°C unless otherwise noted.
1ms/DIV
40851 G19
VBAT = 3.85V
IOUT = 100mA
Wall Connect Waveforms,
VIN = 0V
40851 G20
Wall Disconnect Waveforms,
VIN = 0V
HPWR
5V/DIV
WALL
5V/DIV
VOUT
5V/DIV
IIN
0.5A/DIV
IWALL
0.5A/DIV
IBAT
0.5A/DIV
IBAT
0.5A/DIV
100μs/DIV
VBAT = 3.85V
IOUT = 50mA
1ms/DIV
40851 G21
VBAT = 3.85V
IOUT = 100mA
RPROG = 100k
Response to HPWR
40851 G22
Response to Suspend
WALL
5V/DIV
SUSP
5V/DIV
VOUT
5V/DIV
IWALL
0.5A/DIV
IBAT
0.5A/DIV
VOUT
5V/DIV
IIN
0.5A/DIV
IBAT
0.5A/DIV
1ms/DIV
VBAT = 3.85V
IOUT = 100mA
RPROG = 100k
40851 G23
100μs/DIV
VBAT = 3.85V
IOUT = 50mA
40851 G24
40851f
7
LTC4085-1
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PI FU CTIO S
IN (Pin 1): Input Supply. Connect to USB supply, VBUS.
Input current to this pin is limited to either 20% or 100%
of the current programmed by the CLPROG pin as determined by the state of the HPWR pin. Charge current (to
BAT pin) supplied through the input is set to the current
programmed by the PROG pin but will be limited by the
input current limit if charge current is set greater than the
input current limit.
OUT (Pin 2): Voltage Output. This pin is used to provide
controlled power to a USB device from either USB VBUS
(IN) or the battery (BAT) when the USB is not present.
This pin can also be used as an input for battery charging
when the USB is not present and a wall adapter is applied
to this pin. OUT should be bypassed with at least 4.7μF
to GND.
CLPROG (Pin 3): Current Limit Program and Input Current Monitor. Connecting a resistor, RCLPROG, to ground
programs the input to output current limit. The current
limit is programmed as follows:
ICL (A) =
1000V
RCLPROG
In USB applications the resistor RCLPROG should be set
to no less than 2.1k.
The voltage on the CLPROG pin is always proportional to
the current flowing through the IN to OUT power path.
This current can be calculated as follows:
IIN(A) =
VCLPROG
• 1000
RCLPROG
HPWR (Pin 4): High Power Select. This logic input is used
to control the input current limit. A voltage greater than
1.2V on the pin will set the input current limit to 100% of
the current programmed by the CLPROG pin. A voltage
less than 0.4V on the pin will set the input current limit
to 20% of the current programmed by the CLPROG pin.
A 2μA pull-down is internally applied to this pin to ensure
it is low at power up when the pin is not being driven
externally.
SUSP (Pin 5): Suspend Mode Input. Pulling this pin above
1.2V will disable the power path from IN to OUT. The supply current from IN will be reduced to comply with the
USB specification for suspend mode. Both the ability to
charge the battery from OUT and the ideal diode function
(from BAT to OUT) will remain active. Suspend mode will
reset the charge timer if VOUT is less than VBAT while in
suspend mode. If VOUT is kept greater than VBAT, such as
when a wall adapter is present, the charge timer will not
be reset when the part is put in suspend. A 2μA pull-down
is internally applied to this pin to ensure it is low at power
up when the pin is not being driven externally.
TIMER (Pin 6): Timer Capacitor. Placing a capacitor, CTIMER,
to GND sets the timer period. The timer period is:
t TIMER(Hours) =
CTIMER • RPROG • 3Hours
0.1μF • 100k
Charge time is increased if charge current is reduced
due to undervoltage current limit, load current, thermal
regulation and current limit selection (HPWR).
Shorting the TIMER pin to GND disables the battery
charging functions.
40851f
8
LTC4085-1
U
U
U
PI FU CTIO S
WALL (Pin 7): Wall Adapter Present Input. Pulling this
pin above 4.25V will disconnect the power path from IN
to OUT. The ACPR pin will also be pulled low to indicate
that a wall adapter has been detected.
NTC (Pin 8): Input to the NTC Thermistor Monitoring
Circuits. The NTC pin connects to a negative temperature
coeffcient thermistor which is typically co-packaged with
the battery pack to determine if the battery is too hot or
too cold to charge. If the battery’s temperature is out of
range, charging is paused until the battery temperature reenters the valid range. A low drift bias resistor is required
from VNTC to NTC and a thermistor is required from NTC
to ground. If the NTC function is not desired, the NTC pin
should be grounded.
VNTC (Pin 9): Output Bias Voltage for NTC. A resistor from
this pin to the NTC pin will bias the NTC thermistor.
ACPR (Pin 10): Wall Adapter Present Output. Active low
open drain output pin. A low on this pin indicates that the
wall adapter input comparator has had its input pulled
above the input threshold. This feature is disabled if no
power is present on IN or OUT or BAT (i.e., below UVLO
thresholds).
CHRG (Pin 11): Open-Drain Charge Status Output. When
the battery is being charged, the CHRG pin is pulled low by
an internal N-channel MOSFET. When the timer runs out or
the charge current drops below 10% of the programmed
charge current (while in voltage mode) or the input supply
or output supply is removed, the CHRG pin is forced to a
high impedance state.
PROG (Pin 12): Charge Current Program. Connecting a
resistor, RPROG, to ground programs the battery charge
current. The battery charge current is programmed as
follows:
ICHG(A) =
50, 000V
RPROG
GATE (Pin 13): External Ideal Diode Gate Pin. This pin
can be used to drive the gate of an optional external
PFET connected between BAT and OUT. By doing so, the
impedance of the ideal diode between BAT and OUT can be
reduced. When not in use, this pin should be left floating.
It is important to maintain a high impedance on this pin
and minimize all leakage paths.
BAT (Pin 14): Connect to a single cell Li-Ion battery. This
pin is used as an output when charging the battery and
as an input when supplying power to OUT. When the OUT
pin potential drops below the BAT pin potential, an ideal
diode function connects BAT to OUT and prevents VOUT
from dropping significantly below VBAT. A precision internal
resistor divider sets the final float (charging) potential on
this pin. The internal resistor divider is disconnected when
IN and OUT are in undervoltage lockout.
Exposed Pad (Pin 15): Ground. The exposed package pad
is ground and must be soldered to the PC board for proper
functionality and for maximum heat transfer.
40851f
9
LTC4085-1
W
BLOCK DIAGRA
VBUS
1
IN
CURRENT LIMIT
OUT
ILIM_CNTL
IIN
1000 1V
3
2k
4
SOFT_START
+
CL
–
CLPROG
HPWR
ENABLE
CURRENT_CONTROL
CC/CV REGULATOR
CHARGER
IN
500mA/100mA
OUT BAT
25mV
2
25mV
–
+EDA
GATE
13
IDEAL_DIODE
ENABLE
105°C
DIE TEMP
2μA
–
+
ILIM
+
–
+ –
BAT
TA
14
SOFT_START2
CHARGE_CONTROL
PROG
+
CHG
–
12
100k
–
+
7
10
ICHRG
+
–
1V
+–
25mV
WALL
ACPR
VOLTAGE_DETECT
4.25V
+
–
0.25V
+
–
2.9V
BATTERY UVLO
+
–
4.0V
RECHARGE
UVLO
BAT_UV
RECHRG
9
CONTROL_LOGIC
–
+
100k
8
TIMER
OSCILLATOR
6
VNTC
NTC
–
+
100k
0.1V
+
–
CLK
HOLD
TOO C0LD
NTCERR
CHRG
RESET
COUNTER
STOP
11
NTC
TOO HOT
2μA
NTC_ENABLE
GND
SUSP
C/10
EOC
4085 BD
40851f
10
LTC4085-1
U
OPERATIO
The LTC4085-1 is a complete PowerPath controller for
battery powered USB applications. The LTC4085-1 is designed to receive power from a USB source, a wall adapter,
or a battery. It can then deliver power to an application
connected to the OUT pin and a battery connected to the
BAT pin (assuming that an external supply other than the
battery is present). Power supplies that have limited current resources (such as USB VBUS supplies) should be
connected to the IN pin which has a programmable current
limit. Battery charge current will be adjusted to ensure that
the sum of the charge current and load current does not
exceed the programmed input current limit.
An ideal diode function provides power from the battery
when output/load current exceeds the input current limit or
when input power is removed. Powering the load through
the ideal diode instead of connecting the load directly to
the battery allows a fully charged battery to remain fully
charged until external power is removed. Once external
power is removed the output drops until the ideal diode is
forward biased. The forward biased ideal diode will then
provide the output power to the load from the battery.
Furthermore, powering switching regulator loads from the
OUT pin (rather than directly from the battery) results in
shorter battery charge times. This is due to the fact that
switching regulators typically require constant input power.
When this power is drawn from the OUT pin voltage (rather
than the lower BAT pin voltage) the current consumed
by the switching regulator is lower leaving more current
available to charge the battery.
The LTC4085-1 also has the ability to receive power from
a wall adapter. Wall adapter power can be connected to
the output (load side) of the LTC4085-1 through an external device such as a power Schottky or FET, as shown
in Figure 1. The LTC4085-1 has the unique ability to use
the output, which is powered by the wall adapter, as a
path to charge the battery while providing power to the
load. A wall adapter comparator on the LTC4085-1 can
be configured to detect the presence of the wall adapter
and shut off the connection to the USB to prevent reverse
conduction out to the USB bus.
40851f
11
LTC4085-1
U
OPERATIO
WALL
ADAPTER
10
4.25V
(RISING)
3.15V
(FALLING)
ACPR
–
+
WALL
7
+
–
USB VBUS
1
IN
+
–
75mV (RISING)
25mV (FALLING)
ENABLE
CURRENT LIMIT
CONTROL
OUT
2
LOAD
CHRG
CONTROL
IDEAL
DIODE
BAT
14
40851 F01
+
Li-Ion
Figure 1: Simplified Block Diagram—PowerPath
40851f
12
LTC4085-1
U
OPERATIO
Table 1. Operating Modes—PowerPath States
Current Limited Input Power (IN to OUT)
WALL PRESENT
SUSPEND
VIN > 3.8V
VIN > (VOUT + 100mV)
VIN > (VBAT + 100mV)
CURRENT LIMIT ENABLED
Y
X
X
X
X
N
X
Y
X
X
X
N
X
X
N
X
X
N
X
X
X
N
X
N
X
X
X
X
N
N
N
N
Y
Y
Y
Y
Battery Charger (OUT to BAT)
WALL PRESENT
SUSPEND
VOUT > 4.35V
VOUT > (VBAT + 100mV)
CHARGER ENABLED
X
X
X
X
N
X
N
X
N
N
X
X
Y
Y
Y
WALL PRESENT
SUSPEND
VIN
VBAT > VOUT
VBAT > 2.8V
DIODE ENABLED
X
X
X
X
N
N
X
X
X
N
X
N
X
X
X
Y
Y
Y
Ideal Diode (BAT to OUT)
Operating Modes—Pin Currents vs Programmed Currents (Powered from IN)
PROGRAMMING
OUTPUT CURRENT
BATTERY CURRENT
INPUT CURRENT
ICL = ICHG
IOUT < ICL
IOUT = ICL = ICHG
IOUT > ICL
IBAT = ICL – IOUT
IBAT = 0
IBAT = ICL – IOUT
IIN = IQ + ICL
IIN = IQ + ICL
IIN = IQ + ICL
ICL > ICHG
IOUT < (ICL – ICHG)
IOUT > (ICL – ICHG)
IOUT = ICL
IOUT > ICL
IBAT = ICHG
IBAT = ICL – IOUT
IBAT = 0
IBAT = ICL – IOUT
IIN = IQ + ICHG + IOUT
IIN = IQ + ICL
IIN = IQ + ICL
IIN = IQ + ICL
ICL < ICHG
IOUT < ICL
IOUT > ICL
IBAT = ICL – IOUT
IBAT = ICL – IOUT
IIN = IQ + ICL
IIN = IQ + ICL
40851f
13
LTC4085-1
U
OPERATIO
USB Current Limit and Charge Current Control
The current limit and charger control circuits of the
LTC4085-1 are designed to limit input current as well as
control battery charge current as a function of IOUT. The
programmed current limit, ICL, is defined as:
1000
1000V
ICL = • VCLPROG =
RCLPROG
RCLPROG
The programmed battery charge current, ICHG, is defined
as:
50,000
50,000V
ICHG = • VPROG =
R
R
PROG
PROG
Input current, IIN, is equal to the sum of the BAT pin output
current and the OUT pin output current:
The current limiting circuitry in the LTC4085-1 can and
should be configured to limit current to 500mA for USB
applications (selectable using the HPWR pin and programmed using the CLPROG pin).
The LTC4085-1 reduces battery charge current such that
the sum of the battery charge current and the load current
does not exceed the programmed input current limit (onefifth of the programmed input current limit when HPWR
is low, see Figure 2). The battery charge current goes to
zero when load current exceeds the programmed input
current limit (one-fifth of the limit when HPWR is low). If
the load current is greater than the current limit, the output
voltage will drop to just under the battery voltage where
the ideal diode circuit will take over and the excess load
current will be drawn from the battery.
IIN = IOUT + IBAT
120
600
IIN
500
600
IIN
100
500
IIN
80
200
IBAT
CHARGING
400
ILOAD
60
40
IBAT
CHARGING
CURRENT (mA)
ILOAD
300
CURRENT (mA)
CURRENT (mA)
400
ILOAD
300
200
100
20
100
0
0
0
–100
–20
0
100
200
300
400
ILOAD (mA)
500
600
IBAT
(IDEAL DIODE)
40851 F02a
(2a) High Power Mode/Full Charge
RPROG = 100k and RCLPROG = 2k
0
20
40
60
80
ILOAD (mA)
100
120
IBAT
(IDEAL DIODE)
IBAT = ICHG
–100
IBAT
CHARGING
0
100
40851 F02b
(2b) Low Power Mode/Full Charge
RPROG = 100k and RCLPROG = 2k
200
IBAT = ICL – IOUT
300
400
ILOAD (mA)
500
600
IBAT
(IDEAL DIODE)
40851 F02c
(2c) High Power Mode with
ICL = 500mA and ICHG = 250mA
RPROG = 100k and RCLPROG = 2k
Figure 2: Input and Battery Currents as a Function of Load Current
40851f
14
LTC4085-1
U
OPERATIO
Programming Current Limit
The formula for input current limit is:
1000
1000V
ICL = • VCLPROG =
RCLPROG
RCLPROG
where VCLPROG is the CLPROG pin voltage and RCLPROG
is the total resistance from the CLPROG pin to ground.
For example, if typical 500mA current limit is required,
calculate:
RCLPROG =
1V
• 1000 = 2k
500mA
In USB applications, the minimum value for RCLPROG
should be 2.1k. This will prevent the application current
from exceeding 500mA due to LTC4085-1 tolerances
and quiescent currents. A 2.1k CLPROG resistor will
give a typical current limit of 476mA in high power mode
(HPWR = 1) or 95mA in low power mode (HPWR = 0).
VCLPROG will track the input current according to the following equation:
IIN =
VCLPROG
• 1000
RCLPROG
For best stability over temperature and time, 1% metal
film resistors are recommended.
significantly below the BAT pin voltage. A comparison of
the I-V curve of the ideal diode and a Schottky diode can
be seen in Figure 3.
If the input current increases beyond the programmed
input current limit additional current will be drawn from
the battery via the internal ideal diode. Furthermore, if
power to IN (USB VBUS) or OUT (external wall adapter) is
removed, then all of the application power will be provided
by the battery via the ideal diode. A 4.7μF capacitor at
OUT is sufficient to keep a transition from input power
to battery power from causing significant output voltage
droop. The ideal diode consists of a precision amplifier that
enables a large P-Channel MOSFET transistor whenever
the voltage at OUT is approximately 20mV (VFWD) below
the voltage at BAT. The resistance of the internal ideal
diode is approximately 200mΩ. If this is sufficient for the
application then no external components are necessary.
However, if more conductance is needed, an external
PFET can be added from BAT to OUT. The GATE pin of the
LTC4085-1 drives the gate of the PFET for automatic ideal
diode control. The source of the external PFET should be
connected to OUT and the drain should be connected to
BAT. In order to help protect the external PFET in overcurrent situations, it should be placed in close thermal
contact to the LTC4085-1.
IMAX
Ideal Diode from BAT to OUT
SLOPE: 1/RDIO(ON)
CURRENT (A)
The LTC4085-1 has an internal ideal diode as well as a
controller for an optional external ideal diode. If a battery
is the only power supply available or if the load current
exceeds the programmed input current limit, then the
battery will automatically deliver power to the load via an
ideal diode circuit between the BAT and OUT pins. The
ideal diode circuit (along with the recommended 4.7μF
capacitor on the OUT pin) allows the LTC4085-1 to handle
large transient loads and wall adapter or USB VBUS connect/disconnect scenarios without the need for large bulk
capacitors. The ideal diode responds within a few microseconds and prevents the OUT pin voltage from dropping
SCHOTTKY
DIODE
40851 F03
VFWD
FORWARD VOLTAGE (V)
(BAT-OUT)
Figure 3. LTC4085-1 Schottky Diode vs Forward Voltage Drop
40851f
15
LTC4085-1
U
OPERATIO
Battery Charger
The battery charger circuits of the LTC4085-1 are designed
for charging single cell lithium-ion batteries. Featuring
an internal P-channel power MOSFET, the charger uses a
constant-current/constant-voltage charge algorithm with
programmable current and a programmable timer for
charge termination. Charge current can be programmed
up to 1.5A. The final float voltage accuracy is ±0.8% typical. No blocking diode or sense resistor is required when
powering the IN pin. The CHRG open-drain status output
provides information regarding the charging status of the
LTC4085-1 at all times. An NTC input provides the option
of charge qualification using battery temperature.
An internal thermal limit reduces the programmed charge
current if the die temperature attempts to rise above a
preset value of approximately 105°C. This feature protects
the LTC4085-1 from excessive temperature, and allows
the user to push the limits of the power handling capability of a given circuit board without risk of damaging the
LTC4085-1. Another benefit of the LTC4085-1 thermal limit
is that charge current can be set according to typical, not
worst-case, ambient temperatures for a given application
with the assurance that the charger will automatically
reduce the current in worst-case conditions.
The charge cycle begins when the voltage at the OUT pin
rises above the output UVLO level and the battery voltage
is below the recharge threshold. No charge current actually
flows until the OUT voltage is greater than the output UVLO
level and 100mV above the BAT voltage. At the beginning
of the charge cycle, if the battery voltage is below 2.8V,
the charger goes into trickle charge mode to bring the
cell voltage up to a safe level for charging. The charger
goes into the fast charge constant-current mode once
the voltage on the BAT pin rises above 2.8V. In constant-
current mode, the charge current is set by RPROG. When
the battery approaches the final float voltage, the charge
current begins to decrease as the LTC4085-1 switches to
constant-voltage mode. When the charge current drops
below 10% of the programmed charge current while in
constant-voltage mode the CHRG pin assumes a high
impedance state.
An external capacitor on the TIMER pin sets the total
minimum charge time. When this time elapses the
charge cycle terminates and the CHRG pin assumes a
high impedance state, if it has not already done so. While
charging in constant-current mode, if the charge current
is decreased by thermal regulation or in order to maintain
the programmed input current limit the charge time is
automatically increased. In other words, the charge time
is extended inversely proportional to charge current delivered to the battery. For Li-Ion and similar batteries that
require accurate final float potential, the internal bandgap
reference, voltage amplifier and the resistor divider provide
regulation with ±0.8% accuracy.
Trickle Charge and Defective Battery Detection
At the beginning of a charge cycle, if the battery voltage
is low (below 2.8V) the charger goes into trickle charge
reducing the charge current to 10% of the full-scale current. If the low battery voltage persists for one quarter
of the total charge time, the battery is assumed to be
defective, the charge cycle is terminated and the CHRG
pin output assumes a high impedance state. If for any
reason the battery voltage rises above ~2.8V the charge
cycle will be restarted. To restart the charge cycle (i.e. when
the dead battery is replaced with a discharged battery),
simply remove the input voltage and reapply it or cycle
the TIMER pin to 0V.
40851f
16
LTC4085-1
U
OPERATIO
Programming Charge Current
The formula for the battery charge current is:
ICHG = (IPROG ) • 50, 000 =
VPROG
• 50, 000
RPROG
where VPROG is the PROG pin voltage and RPROG is the
total resistance from the PROG pin to ground. Keep in
mind that when the LTC4085-1 is powered from the IN pin,
the programmed input current limit takes precedent over
the charge current. In such a scenario, the charge current
cannot exceed the programmed input current limit.
For example, if typical 500mA charge current is required,
calculate:
1V RPROG = • 50,000 = 100k
500mA For best stability over temperature and time, 1% metal
film resistors are recommended. Under trickle charge
conditions, this current is reduced to 10% of the fullscale value.
The Charge Timer
The programmable charge timer is used to terminate the
charge cycle. The timer duration is programmed by an
external capacitor at the TIMER pin. The charge time is
typically:
tTIMER (Hours) =
The timer starts when an input voltage greater than the
undervoltage lockout threshold level is applied or when
leaving shutdown and the voltage on the battery is less than
the recharge threshold. At power up or exiting shutdown
with the battery voltage less than the recharge threshold
the charge time is a full cycle. If the battery is greater than
the recharge threshold the timer will not start and charging
is prevented. If after power-up the battery voltage drops
below the recharge threshold or if after a charge cycle the
battery voltage is still below the recharge threshold the
charge time is set to one half of a full cycle.
The LTC4085-1 has a feature that extends charge time
automatically. Charge time is extended if the charge
current in constant-current mode is reduced due to load
current or thermal regulation. This change in charge time
is inversely proportional to the change in charge current.
As the LTC4085-1 approaches constant-voltage mode
the charge current begins to drop. This change in charge
current is due to normal charging operation and does not
affect the timer duration.
Once a time-out occurs and the voltage on the battery is
greater than the recharge threshold, the charge current
stops, and the CHRG output assumes a high impedance
state if it has not already done so.
Connecting the TIMER pin to ground disables the battery
charger.
CTIMER • RPROG • 3Hours
0.1μF • 100k
40851f
17
LTC4085-1
U
OPERATIO
CHRG Status Output Pin
When the charge cycle starts, the CHRG pin is pulled to
ground by an internal N-channel MOSFET capable of driving
an LED. When the charge current drops below 10% of the
programmed full charge current while in constant-voltage
mode, the pin assumes a high impedance state (but charge
current continues to flow until the charge time elapses).
If this state is not reached before the end of the programmable charge time, the pin will assume a high impedance
state when a time-out occurs. The CHRG current detection
threshold can be calculated by the following equation:
IDETECT =
0.1V
5000V
• 50, 000 =
RPROG
RPROG
For example, if the full charge current is programmed
to 500mA with a 100k PROG resistor the CHRG pin will
change state at a battery charge current of 50mA.
Note: The end-of-charge (EOC) comparator that monitors the charge current latches its decision. Therefore,
the first time the charge current drops below 10% of the
programmed full charge current while in constant-voltage mode will toggle CHRG to a high impedance state.
If, for some reason, the charge current rises back above
the threshold the CHRG pin will not resume the strong
pull-down state. The EOC latch can be reset by a recharge
cycle (i.e. VBAT drops below the recharge threshold) or
toggling the input power to the part.
Current Limit Undervoltage Lockout
An internal undervoltage lockout circuit monitors the
input voltage and disables the input current limit circuits
until VIN rises above the undervoltage lockout threshold.
The current limit UVLO circuit has a built-in hysteresis of
125mV. Furthermore, to protect against reverse current in
the power MOSFET, the current limit UVLO circuit disables
the current limit (i.e. forces the input power path to a high
impedance state) if VOUT exceeds VIN. If the current limit
UVLO comparator is tripped, the current limit circuits will
not come out of shutdown until VOUT falls 50mV below
the VIN voltage.
Charger Undervoltage Lockout
An internal undervoltage lockout circuit monitors the VOUT
voltage and disables the battery charger circuits until VOUT
18
rises above the undervoltage lockout threshold. The battery
charger UVLO circuit has a built-in hysteresis of 125mV.
Furthermore, to protect against reverse current in the power
MOSFET, the charger UVLO circuit keeps the charger shut
down if VBAT exceeds VOUT. If the charger UVLO comparator
is tripped, the charger circuits will not come out of shut
down until VOUT exceeds VBAT by 50mV.
Suspend
The LTC4085-1 can be put in suspend mode by forcing
the SUSP pin greater than 1.2V. In suspend mode the ideal
diode function from BAT to OUT is kept alive. If power is
applied to the OUT pin externally (i.e., a wall adapter is
present) then charging will be unaffected. Current drawn
from the IN pin is reduced to 50μA. Suspend mode is
intended to comply with the USB power specification
mode of the same name.
NTC Thermistor—Battery Temperature Charge
Qualification
The battery temperature is measured by placing a negative temperature coefficient (NTC) thermistor close to the
battery pack. The NTC circuitry is shown in Figure 4.
To use this feature, connect the NTC thermistor (RNTC)
between the NTC pin and ground and a resistor (RNOM) from
the NTC pin to VNTC. RNOM should be a 1% resistor with
a value equal to the value of the chosen NTC thermistor at
25°C (this value is 10k for a Vishay NTHS0603N02N1002J
thermistor). The LTC4085-1 goes into hold mode when
the resistance (RHOT) of the NTC thermistor drops to 0.48
times the value of RNOM, or approximately 4.8k, which
should be at 45°C. The hold mode freezes the timer and
stops the charge cycle until the thermistor indicates a return to a valid temperature. As the temperature drops, the
resistance of the NTC thermistor rises. The LTC4085-1 is
designed to go into hold mode when the value of the NTC
thermistor increases to 2.82 times the value of RNOM. This
resistance is RCOLD. For a Vishay NTHS0603N02N1002J
thermistor, this value is 28.2k which corresponds to approximately 0°C. The hot and cold comparators each have
approximately 2°C of hysteresis to prevent oscillation
about the trip point. Grounding the NTC pin will disable
the NTC function.
40851f
LTC4085-1
U
U
W
U
APPLICATIO S I FOR ATIO
VNTC
LTC4085-1
VNTC
9
RNOM
10k
NTC
LTC4085-1
9
0.738 • VNTC
–
TOO_COLD
0.738 • VNTC
RNOM
124k
NTC
–
TOO_COLD
8
+
8
+
RNTC
10k
–
R1
24.3k
–
TOO_HOT
0.326 • VNTC
TOO_HOT
0.326 • VNTC
+
+
RNTC
100k
+
+
NTC_ENABLE
NTC_ENABLE
–
0.1V
–
0.1V
40851 F04a
(4a)
40851 F04b
(4b)
Figure 4. NTC Circuits
Alternate NTC Thermistors
The LTC4085-1 NTC trip points were designed to work
with thermistors whose resistance-temperature characteristics follow Vishay Dale’s “R-T Curve 2.” The Vishay
NTHS0603N02N1002J is an example of such a thermistor. However, Vishay Dale has many thermistor products
that follow the “R-T Curve 2” characteristic in a variety of
sizes. Furthermore, any thermistor whose ratio of RCOLD
to RHOT is about 6.0 will also work (Vishay Dale R-T Curve
2 shows a ratio of 2.816/0.4839 = 5.82).
Power conscious designs may want to use thermistors
whose room temperature value is greater than 10k. Vishay
Dale has a number of values of thermistor from 10k to 100k
that follow the “R-T Curve 1.” Using these as indicated
in the NTC Thermistor section will give temperature trip
points of approximately 3°C and 42°C, a delta of 39°C.
This delta in temperature can be moved in either direction by changing the value of RNOM with respect to RNTC.
Increasing RNOM will move both trip points to lower
temperatures. Likewise, a decrease in RNOM with respect
to RNTC will move the trip points to higher temperatures.
To calculate RNOM for a shift to lower temperature, for
example, use the following equation:
RNOM =
R COLD
• RNTC at 25 °C
2 . 816
where RCOLD is the resistance ratio of RNTC at the desired
cold temperature trip point. To shift the trip points to higher
temperatures use the following equation:
RNOM =
RHOT
• RNTC at 25 °C
0 . 484
where RHOT is the resistance ratio of RNTC at the desired
hot temperature trip point.
The following example uses a 100K R-T Curve 1 Thermistor
from Vishay Dale. The difference between the trip points
is 39°C, from before—and the desired cold trip point of
0°C, would put the hot trip point at about 39°C. The RNOM
needed is calculated as follows:
RNOM =
RCOLD
•R
at 25°C =
2.816 NTC
3.266
• 100kΩ = 116kΩ
2.816
40851f
19
LTC4085-1
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APPLICATIO S I FOR ATIO
The nearest 1% value for RNOM is 115k. This is the value
used to bias the NTC thermistor to get cold and hot trip
points of approximately 0°C and 39°C, respectively. To
extend the delta between the cold and hot trip points, a
resistor (R1) can be added in series with RNTC (see Figure 4).
The values of the resistors are calculated as follows:
RNOM
R
− RHOT
= COLD
2.816 − 0.484
0.484
⎡
⎤
R1= ⎢
⎥ • [RCOLD − RHOT ] − RHOT
⎣ 2.816 − 0.484 ⎦
where RNOM is the value of the bias resistor, RHOT and
RCOLD are the values of RNTC at the desired temperature
trip points. Continuing the forementioned example with
a desired hot trip point of 50°C:
RNOM =
=
R COLD R HOT
2.816 0.484
100k • (3.266 0.3602)
2.816 0.484
= 124.6k,124k nearest 1%
0.484
2.816 0.484 •
R1= 100k • ( 3.266 0.3602) 0.3602
= 24.3k
The final solution is shown in Figure 4, where
RNOM = 124k, R1 = 24.3k and RNTC = 100k at 25°C
Using the WALL Pin to Detect the Presence of a Wall
Adapter
The WALL input pin identifies the presence of a wall
adapter (the pin should be tied directly to the adapter
output voltage). This information is used to disconnect the
input pin, IN, from the OUT pin in order to prevent back
conduction to whatever may be connected to the input.
It also forces the ACPR pin low when the voltage at the
WALL pin exceeds the input threshold. In order for the
presence of a wall adapter to be acknowledged, both of
the following conditions must be satisfied:
1. The WALL pin voltage exceeds VWAR (approximately
4.25V); and
2. The WALL pin voltage exceeds VWDR (approximately
75mV above VBAT)
The input power path (between IN and OUT) is re-enabled
and the ACPR pin assumes a high impedance state when
either of the following conditions is met:
1. The WALL pin voltage falls below VWDF (approximately
25mV above VBAT); or
2. The WALL pin voltage falls below VWAF (approximately
3.12V)
Each of these thresholds is suitably filtered in time to
prevent transient glitches on the WALL pin from falsely
triggering an event.
Power Dissipation
The conditions that cause the LTC4085-1 to reduce charge
current due to the thermal protection feedback can be approximated by considering the power dissipated in the part.
For high charge currents and a wall adapter applied to VOUT,
the LTC4085-1 power dissipation is approximately:
PD = (VOUT – VBAT) • IBAT
Where, PD is the power dissipated, VOUT is the supply
voltage, VBAT is the battery voltage, and IBAT is the battery
charge current. It is not necessary to perform any worstcase power dissipation scenarios because the LTC4085-1
will automatically reduce the charge current to maintain
the die temperature at approximately 105°C. However, the
approximate ambient temperature at which the thermal
feedback begins to protect the IC is:
TA = 105°C – PD • θJA
TA = 105°C – (VOUT – VBAT) • IBAT • θJA
40851f
20
LTC4085-1
U
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APPLICATIO S I FOR ATIO
Example: Consider an LTC4085-1 operating from a wall
adapter with 5V at VOUT providing 0.8A to a 3V Li-Ion
battery. The ambient temperature above which the
LTC4085-1 will begin to reduce the 0.8A charge current,
is approximately
TA = 105°C – (5V – 3V) • 0.8A • 37°C/W
TA = 105°C – 1.6W • 37°C/W = 105°C – 59°C = 46°C
The LTC4085-1 can be used above 46°C, but the charge
current will be reduced below 0.8A. The charge current at
a given ambient temperature can be approximated by:
IBAT =
105°C – TA
( VOUT – VBAT ) • θJA
Consider the above example with an ambient temperature
of 55°C. The charge current will be reduced to approximately:
IBAT =
105°C – 55°C
50°C
=
= 0.675A
(5V – 3V) • 37°C/W 74°C/A
Board Layout Considerations
In order to be able to deliver maximum charge current
under all conditions, it is critical that the Exposed Pad on
the backside of the LTC4085-1 package is soldered to the
board. Correctly soldered to a 2500mm2 double-sided 1oz.
copper board the LTC4085-1 has a thermal resistance of
approximately 37°C/W. Failure to make thermal contact
between the Exposed Pad on the backside of the package
and the copper board will result in thermal resistances far
greater than 37°C/W. As an example, a correctly soldered
LTC4085-1 can deliver over 1A to a battery from a 5V supply
at room temperature. Without a backside thermal connection, this number could drop to less than 500mA.
VIN and Wall Adapter Bypass Capacitor
Many types of capacitors can be used for input bypassing.
However, caution must be exercised when using multilayer
ceramic capacitors. Because of the self resonant and high
Q characteristics of some types of ceramic capacitors, high
voltage transients can be generated under some start-up
conditions, such as connecting the charger input to a hot
power source. For more information, refer to Application
Note 88.
Stability
The constant-voltage mode feedback loop is stable without
any compensation when a battery is connected. However,
a 4.7μF capacitor with a 1Ω series resistor to GND is
recommended at the BAT pin to keep ripple voltage low
when the battery is disconnected.
40851f
21
LTC4085-1
U
TYPICAL APPLICATIO
USB Power Control Application with Wall Adapter Input
5V WALL
ADAPTER
INPUT
4.7μF
1k
510Ω
TO LDOs
REGs, ETC
4.7μF
510Ω
1Ω*
5V (NOM)
FROM USB
CABLE VBUS
OUT
IN
4.7μF
CHRG
GATE
ACPR
1Ω*
WALL
BAT
VNTC
LTC4085-1
RNTCBIAS
10k
+
Li-Ion
CELL
NTC
RNTC
10k
SUSPEND USB POWER
SUSP
500mA/100mA SELECT
HPWR
PROG
*SERIES 1Ω RESISTOR ONLY
NEEDED FOR INDUCTIVE
INPUT SUPPLIES
CLPROG
RPROG
71.5k
TIMER
GND
RCLPROG
2.1k
0.15μF
40851 TA02
40851f
22
LTC4085-1
U
PACKAGE DESCRIPTIO
DE Package
14-Lead Plastic DFN (4mm × 3mm)
(Reference LTC DWG # 05-08-1708 Rev B)
0.70 ±0.05
3.30 ±0.05
3.60 ±0.05
2.20 ±0.05
1.70 ± 0.05
PACKAGE
OUTLINE
0.25 ± 0.05
0.50 BSC
3.00 REF
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED
R = 0.115
TYP
4.00 ±0.10
(2 SIDES)
R = 0.05
TYP
3.00 ±0.10
(2 SIDES)
0.40 ± 0.10
8
14
3.30 ±0.10
1.70 ± 0.10
PIN 1 NOTCH
R = 0.20 OR
0.35 × 45°
CHAMFER
PIN 1
TOP MARK
(SEE NOTE 6)
(DE14) DFN 0806 REV B
7
0.200 REF
1
0.25 ± 0.05
0.50 BSC
0.75 ±0.05
3.00 REF
0.00 – 0.05
BOTTOM VIEW—EXPOSED PAD
NOTE:
1. DRAWING PROPOSED TO BE MADE VARIATION OF VERSION (WGED-3) IN JEDEC
PACKAGE OUTLINE MO-229
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE
TOP AND BOTTOM OF PACKAGE
40851f
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
23
LTC4085-1
RELATED PARTS
PART NUMBER
DESCRIPTION
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LTC3406/LTC3406A
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LTC3411
1.25A (IOUT), 4 MHz, Synchronous Step-Down
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MS10 Package
LTC3440
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Charges Single Cell Li-Ion Batteries Directly from a USB Port, Thermal
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Charges Single Cell Li-Ion Batteries Directly from a USB Port, Thermal
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USB Power Manager with Ideal Diode Controller
and Li-Ion Charger
Charges Single Cell Li-Ion Batteries Directly from a USB Port, Thermal
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Package
LTC4089/LTC4089-1/ High Voltage USB Power Manager with Ideal
High Efficiency 1.2A Charger from 6V to 36V (40V max) Input Charges Single
LTC4089-5
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LTC4090
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Adaptive Output Control
Bat-Track and ThinSOT are trademarks of Linear Technology Corporation.
40851f
24 Linear Technology Corporation
LT 1007 • PRINTED IN USA
1630 McCarthy Blvd., Milpitas, CA 95035-7417
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●
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© LINEAR TECHNOLOGY CORPORATION 2006