Linear LT1236 1.5ppm c drift, low noise, buffered reference Datasheet

LT6657
1.5ppm/°C Drift, Low Noise,
Buffered Reference
Features
Description
Low Drift
nn A Grade: 1.5ppm/°C Max
nn B Grade: 3ppm/°C Max
nn Low Noise:
nn 0.5ppm
P-P (0.1Hz to 10Hz)
nn 0.8ppm
RMS (10Hz to 1kHz)
nn Wide Supply Range to 40V
nn Sources and Sinks 10mA Min
nn Line Regulation: 0.2ppm/V
nn Load Regulation: 0.7ppm/mA
nn Reverse Supply Protection
nn Reverse Output Protection
nn Low Power Shutdown: <4µA Max
nn Thermal Protection
nn Can Operate in Shunt Mode
nn Configurable as a Negative Reference
nn Available Output Voltage Options: 2.5V, 3V, 5V
nn MSOP-8 Package
The LT®6657 is a precision voltage reference that combines
robust operating characteristics with extremely low drift
and low noise. With advanced curvature compensation,
this bandgap reference achieves 1.5ppm/°C drift with
predictable temperature behavior, and an initial voltage
accuracy of 0.1%. It also offers 0.5ppmP-P noise and very
low temperature cycling hysteresis.
Applications
The LT6657 is fully specified over the temperature range of
–40°C to 125°C. It is available in the 8-lead MSOP package.
High Temperature Industrial
nn High Resolution Data Acquisition Systems
nn Instrumentation and Process Control
nn Automotive Control and Monitoring
nn Medical Equipment
nn Shunt and Negative Voltage References
L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear
Technology Corporation. All other trademarks are the property of their respective owners.
nn
The LT6657 is a low dropout reference that can be powered
from as little as 50mV above the output voltage, up to 40V.
The buffered output supports ±10mA of output drive with
low output impedance and precise load regulation. The
high sink current capability allows operation as a negative
voltage reference with the same precision as a positive
reference. This part is safe under reverse battery conditions, and includes current protection when the output is
short-circuited and thermal shutdown for overload conditions. A shutdown is included to allow power reduction
while enabling a quick turn-on.
nn
Typical Application
Basic Connection
2
(VOUT + 50mV) < VIN < 40V
CIN
0.1µF
3
IN
LT6657
OUT
6
VOUT
COUT
1µF
SHDN
GND
4
6657 TA01a
OUTPUT VOLTAGE CHANGE (NORMALIZED) (PPM)
Output Voltage Temperature Drift
200
THREE TYPICAL PARTS
100
1ppm/°C BOX
0
–100
–200
–45
–20
30
80
5
55
TEMPERATURE (°C)
105
130
6657 TA01b
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1
LT6657
Absolute Maximum Ratings
Pin Configuration
(Note 1)
Input Voltage VIN (to GND)........................... –40V to 40V
Shutdown Voltage SHDN............................. –20V to 40V
Output Voltage VOUT...................................... –3V to 30V
Input-to-Output Differential Voltage (Note 2)...........±40V
Output Short-Circuit Duration........................... Indefinite
Operating Junction Temperature
Range................................................. –40°C to 150°C
Storage Temperature Range................... –65°C to 150°C
Lead Temperature (Soldering 10 sec)
(Note 3)............................................................. 300°C
TOP VIEW
DNC
VIN
SHDN
GND
8
7
6
5
1
2
3
4
DNC
DNC
VOUT
DNC
MS8 PACKAGE
8-LEAD PLASTIC MSOP
TJMAX = 150°C, θJA = 273°C/W
DNC: CONNECTED INTERNALLY
DO NOT CONNECT EXTERNAL CIRCUITRY TO THESE PINS
Order Information
http://www.linear.com/product/LT6657#orderinfo
TUBE
TAPE AND REEL
PART MARKING* PACKAGE DESCRIPTION
LT6657AHMS8-2.5#PBF
LT6657AHMS8-2.5#TRPBF
LTGKN
8-Lead Plastic MSOP
SPECIFIED TEMPERATURE RANGE
–40°C to 125°C
LT6657BHMS8-2.5#PBF
LT6657BHMS8-2.5#TRPBF
LTGKN
8-Lead Plastic MSOP
–40°C to 125°C
LT6657AHMS8-3#PBF
LT6657AHMS8-3#TRPBF
LTGYG
8-Lead Plastic MSOP
–40°C to 125°C
LT6657BHMS8-3#PBF
LT6657BHMS8-3#TRPBF
LTGYG
8-Lead Plastic MSOP
–40°C to 125°C
LT6657AHMS8-5#PBF
LT6657AHMS8-5#TRPBF
LTGYH
8-Lead Plastic MSOP
–40°C to 125°C
LT6657BHMS8-5#PBF
LT6657BHMS8-5#TRPBF
LTGYH
8-Lead Plastic MSOP
–40°C to 125°C
*Temperature grades are identified by a label on the shipping container.
Consult LTC Marketing for parts specified with wider operating temperature ranges. Parts ending with PBF are RoHS and WEEE compliant.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/. Some packages are available in 500 unit reels through
designated sales channels with #TRMPBF suffix.
† This product is only offered in trays. For more information go to: http://www.linear.com/packaging/
Available Options
OUTPUT VOLTAGE
INITIAL ACCURACY
TEMPERATURE COEFFICIENT
ORDER PART NUMBER**
SPECIFIED TEMPERATURE RANGE
2.5V
0.1%
0.1%
1.5ppm/°C
3ppm/°C
LT6657AHMS8-2.5
LT6657BHMS8-2.5
–40°C to 125°C
–40°C to 125°C
3V
0.1%
0.1%
1.5ppm/°C
3ppm/°C
LT6657AHMS8-3
LT6657BHMS8-3
–40°C to 125°C
–40°C to 125°C
5V
0.1%
0.1%
1.5ppm/°C
3ppm/°C
LT6657AHMS8-5
LT6657BHMS8-5
–40°C to 125°C
–40°C to 125°C
** See the Order Information section for complete part number listing.
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LT6657
Electrical Characteristics
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. The test conditions are VIN = VOUT + 0.5V, VSHDN = 1.6V, IOUT = 0,
COUT = 1µF, unless otherwise noted.
PARAMETER
CONDITIONS
MIN
Output Voltage Accuracy
–0.1
Output Voltage Temperature Coefficient
(Note 4)
LT6657A
LT6657B
Line Regulation (Note 5)
VOUT + 0.5V ≤ VIN ≤ 40V
l
l
TYP
MAX
0
0.1
%
0.5
1
1.5
3
ppm/°C
ppm/°C
0.2
2
4
ppm/V
ppm/V
0.7
2
4
ppm/mA
ppm/mA
0.9
3
6
ppm/mA
ppm/mA
0.9
6
ppm/mA
20
50
70
mV
mV
65
100
140
mV
mV
330
450
500
mV
mV
–230
–150
–50
mV
mV
0.7
2
V
µA
l
Load Regulation (Note 5)
IOUT (Source) = 10mA
l
IOUT (Sink) = 10mA
l
Shunt Configuration
VOUT Is Shorted to VIN
ISHUNT 2.5 to 11mA
Minimum VIN – VOUT
VIN – VOUT,
ΔVOUT = 0.1%
l
IOUT = 0mA
l
IOUT (Source) = 1mA
l
IOUT (Source) = 10mA
l
IOUT (Sink) = 10mA
l
Shutdown Pin (SHDN)
Supply Current in Shutdown
1.6
UNITS
Logic High Input Voltage
Logic High Input Current, SHDN = 1.6V
l
l
Logic Low Input Voltage
Logic Low Input Current, SHDN = 0.8V
l
l
0.2
0.8
1
V
µA
SHDN = 0.4V
l
0.01
4
µA
SHDN = 0.8V
l
2.0
20
µA
1.2
1.8
2.3
mA
mA
Supply Current
No Load
Output Short-Circuit Current
Short VOUT to GND
Short VOUT to VIN
15
16
mA
mA
Output Voltage Noise (Note 6)
0.1Hz ≤ f ≤ 10Hz
10Hz ≤ f ≤ 1kHz
0.5
0.8
ppmP-P
ppmRMS
Turn-On Time
0.1% Settling, CL = 1µF
180
µsec
30
ppm/√kHr
20
24
30
35
40
ppm
ppm
ppm
ppm
ppm
l
Long-Term Drift of Output Voltage (Note 7)
Hysteresis (Note 8)
ΔT = 0°C to 50°C
ΔT = 0°C to 70°C
ΔT = –40°C to 85°C
ΔT = –40°C to 125°C
ΔT = –55°C to 125°C
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: With VIN at 40V, VOUT may not be pulled below 0V. The total VIN to
VOUT differential voltage must not exceed ±40V.
Note 3: The stated temperature is typical for soldering of the leads during
manual rework. For detailed IR reflow recommendations, refer to the
Application information section.
Note 4: Temperature coefficient is measured by dividing the maximum
change in output voltage by the specified temperature range.
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LT6657
Electrical Characteristics
Note 5: Line and load regulation are measured on a pulse basis for
specified input voltage or load current ranges. Output voltage change due
to die temperature change must be taken into account separately.
Note 6: Peak-to-peak noise is measured with a 2-pole highpass filter at
0.1Hz and 3-pole lowpass filter at 10Hz. The unit is enclosed in a still-air
environment to eliminate thermocouple effects on the leads, and the
test time is 10 seconds. Due to the statistical nature of noise, repeating
noise measurements will yield larger and smaller peak values in a given
measurement interval. By repeating the measurement for 1000 intervals,
each 10 seconds long, it is shown that there are time intervals during
which the noise is higher than in a typical single interval, as predicted by
statistical theory. In general, typical values are considered to be those for
which at least 50% of the units may be expected to perform similarly or
better. For the 1000 interval test, a typical unit will exhibit noise that is
less than the typical value listed in the Electrical Characteristics table in
more than 50% of its measurement intervals. See Application Note 124 for
noise testing details. RMS noise is measured with a spectrum analyzer in a
shielded environment.
Note 7: Long term stability typically has a logarithmic characteristic
and therefore change after 1000 hours tend to be much smaller than
before that time. Total drift in the second thousand hours is normally
less than one third of the first thousand hours with a continuing trend
toward reduced drift with time. Long-term stability will also be affected by
differential stresses between the IC and the board material created during
board assembly.
Note 8 : Hysteresis in output voltage is created by mechanical stress that
depends on whether the IC was previously at a different temperature.
Output voltage is always measured at 25°C, but the IC is cycled 25°C to
cold to 25°C, or 25°C to hot to 25°C before successive measurements.
Hysteresis measures the maximum output change for the averages of
three hot or cold temperature cycles, preconditioned by one cold and one
hot cycles. For instruments that are stored at well controlled temperatures
(within 30 degrees of the operational temperature), hysteresis is usually
not a significant error source.
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LT6657
Typical Performance Characteristics
The test conditions are TA = 25°C,
VIN = VOUT + 0.5V, VSHDN = 1.6V, IOUT = 0, COUT = 1µF, unless otherwise noted.
2.5V Output Voltage
Temperature Drift
2.5008
2.5V Low Frequency 0.1Hz to
10Hz Noise
2.5V Output Voltage Noise
Spectrum
110
THREE TYPICAL PARTS
COUT = 1µF Cer
COUT = 5µF Cer
COUT = 47µF Tant
2.5000
2.4996
2.4992
–50 –25
0
NOISE VOLTAGE (nV/√Hz)
OUTPUT NOISE (500nV/DIV)
OUTPUT VOLTAGE (V)
100
2.5004
90
80
70
60
25 50 75 100 125 150
TEMPERATURE (°C)
TIME (1s/DIV)
50
0.01
6657 G02
0.1
1
10
FREQUENCY (kHz)
100
6657 G03
6657 G01
2.5V Integrated Noise
10Hz to 10kHz
2.0
COUT = 1µF
VSHDN = VIN
1
1.0
0.5
125°C
25°C
–40°C
–55°C
0.0
–0.5
–40 –30 –20 –10 0
10 20
INPUT VOLTAGE (V)
10
6657 G04
30
MS8 PACKAGE PART SELF
HEATING IS INCLUDED
10
0
–10
–20
–30
0.1
125°C
25°C
–40°C
–55°C
1
OUTPUT CURRENT (mA)
2.5000
2.4995
2.4990
10
6657 G07
0
10
30
20
INPUT VOLTAGE (V)
40
6657 G06
2.5V Minimum VIN to VOUT
Differential (Sourcing)
2.5V Load Regulation (Sinking)
OUTPUT VOLTAGE CHANGE (ppm)
20
40
125°C
25°C
–40°C
6657 G05
2.5V Load Regulation (Sourcing)
30
30
PART SELF HEATING
IS INCLUDED
2.5005
20
10
MS8 PACKAGE PART SELF
HEATING IS INCLUDED
OUTPUT CURRENT (mA)
0.1
1
FREQUENCY (kHz)
OUTPUT VOLTAGE (V)
10
0.1
0.01
OUTPUT VOLTAGE CHANGE (ppm)
2.5V Line Regulation
2.5010
1.5
INPUT CURRENT (mA)
INTEGRATED NOISE (µVRMS)
100
2.5V Supply Current vs
Input Voltage
10
0
–10
–20
–30
0.1
125°C
25°C
–40°C
–55°C
1
OUTPUT CURRENT (mA)
10
6657 G08
1
0.1
125°C
25°C
–40°C
–55°C
0
100
200
300
400
INPUT-OUTPUT VOLTAGE (mV)
500
6657 G09
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LT6657
Typical Performance Characteristics
VIN = VOUT + 0.5V, VSHDN = 1.6V, IOUT = 0, COUT = 1µF, unless otherwise noted.
2.5V Minimum VIN to VOUT
Differential (Sinking)
2.5V Power Supply Rejection
Ratio vs Frequency
120
1
VIN < VOUT
0.1
0
–300 –250 –200 –150 –100 –50
INPUT-OUTPUT VOLTAGE (mV)
100
80
60
40
1
10
100
FREQUENCY (kHz)
0
GROUND PIN CURRENT
CURRENTS GOING INTO
THE PART ARE POSITIVE
–12
–10
–5
0
5
LOAD CURRENT (mA)
1.35
1.30
1.25
1.15
1.10
1.05
5.0016
OUTPUT VOLTAGE (V)
SUPPLY CURRENT IN SHUTDOWN (µA)
1.0
0.0
0
20
30
INPUT VOLTAGE (V)
40
6657 G16
0
–5
–10
–15
–20
0
50
100
TEMPERATURE (°C)
150
–30
–10
125°C
25°C
–40°C
–55°C
0
40
10
20
30
SHUTDOWN VOLTAGE (V)
6657 G15
5V Output Voltage Temperature
Drift
4.0
2.0
5
6657 G14
2.5V Supply Current in Shutdown
vs Input Voltage
3.0
10
–25
1.00
–50
10
125°C
25°C
–40°C
–55°C
1k
Shutdown Pin Current vs
Shutdown Voltage
VTH(RISING)
VTH(FALLING)
6657 G13
VSHDN = 0.4V
10
100
FREQUENCY (kHz)
5V Low Frequency 0.1Hz to 10Hz
Noise
THREE TYPICAL PARTS
OUTPUT NOISE (500nV/DIV)
–8
1
6657 G12
SHUTDOWN CURRENT (µA)
SHUTDOWN VOLTAGE THRESHOLDS (V)
SUPPLY AND GROUND CURRENTS (mA)
1.40
SUPPLY PIN CURRENT
–4
0.1
1000
Shutdown Voltage Thresholds vs
Temperature
125°C
25°C
–40°C
–55°C
4
1
6657 G11
Supply and Ground Currents vs
Load Current
8
COUT = 1µF
COUT = 10µF
COUT = 100µF
20
6657 G10
12
10
COUT = 1µF
COUT = 10µF
0
0.1
50
2.5V Output Impedance vs
Frequency
OUTPUT IMPEDANCE (Ω)
125°C
25°C
–40°C
–55°C
POWER SUPPLY REJECTION RATIO (dB)
OUTPUT CURRENT (mA)
10
The test conditions are TA = 25°C,
5.0008
5.0000
4.9992
4.9984
–50 –30 –10 10 30 50 70 90 110 130 150
TEMPERATURE (°C)
6657 G17
TIME (1s/DIV)
6657 G18
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LT6657
Typical Performance Characteristics
The test conditions are TA = 25°C,
VIN = VOUT + 0.5V, VSHDN = 1.6V, IOUT = 0, COUT = 1µF, unless otherwise noted.
5V Output Voltage Noise
Spectrum
250
200
150
100
50
0.01
0.1
2.0
1
10
FREQUENCY (kHz)
1.5
10
1
0.1
0.01
100
0.1
1
FREQUENCY (kHz)
5.0000
4.9995
0
10
20
30
INPUT VOLTAGE (V)
10
0
–10
–30
0.1
40
6657 G22
1
OUTPUT CURRENT (mA)
0
–10
125°C
25°C
–40°C
–55°C
100
200
300
400
INPUT–OUTPUT VOLTAGE (mV)
500
6657 G25
OUTPUT CURRENT (mA)
1
125°C
25°C
–40°C
–55°C
–20
–30
0.1
10
1
OUTPUT CURRENT (mA)
10
6657 G24
5V Output Impedance vs
Frequency
10
0
10
5V Minimum VIN to VOUT
Differential (Sinking)
10
OUTPUT CURRENT (mA)
125°C
25°C
–40°C
–55°C
MS8 PACKAGE PART SELF
HEATING IS INCLUDED
20
6657 G23
5V Minimum VIN to VOUT
Differential (Sourcing)
0.1
MS8 PACKAGE PART SELF
HEATING IS INCLUDED
–20
40
5V Load Regulation (Sinking)
100
125°C
25°C
–40°C
–55°C
OUTPUT IMPEDANCE (Ω)
4.9990
20
30
30
OUTPUT VOLTAGE CHANGE (ppm)
125°C
25°C
–40°C
125°C
25°C
–40°C
–55°C
6657 G21
5V Load Regulation (Sourcing)
30
OUTPUT VOLTAGE CHANGE (ppm)
OUTPUT VOLTAGE (V)
5.0005
0.5
–0.5
–40 –30 –20 –10 0
10 20
INPUT VOLTAGE (V)
10
6657 G20
5V Line Regulation
PART SELF HEATING
IS INCLUDED
1.0
0
6657 G19
5.0010
VSHDN = VIN
COUT = 1µF
INTEGRATED NOISE (µVRMS)
300
NOISE VOLTAGE (nV/√Hz)
100
COUT = 1µF Cer
COUT = 5µF Cer
COUT = 47µF Tant
5V Supply Current vs Input
Voltage
INPUT CURRENT (mA)
350
5V Integrated Noise 10Hz to
10kHz
1
VIN < VOUT
0.1
–350 –300 –250 –200 –150 –100 –50 0
INPUT–OUTPUT VOLTAGE (mV)
50
6657 G26
COUT = 1µF
COUT = 10µF
COUT = 100µF
10
1
0.1
1
10
100
FREQUENCY (kHz)
1k
6657 G27
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LT6657
Pin Functions
SHDN (Pin 3): Shutdown Input. This active low input
disables the part to reduce supply current < 2µA. This
pin must be driven externally and should be tied to VIN
if unused. It may be driven to logic high or to VIN during
normal operation.
VOUT (Pin 6): Reference Output Voltage. This pin can
source and sink current to a load. An output capacitor of
1µF or higher is required for stability.
DNC (Pins 1, 5, 7, 8): Internal Functions. Do Not Connect
or electrically stress these pins. These pins must be left
floating and leakage currents from these pins should be
kept to a minimum. Allow additional routing clearance.
VIN (Pin 2): Input Voltage Supply. Bypass VIN with a local
0.1µF or larger capacitor to GND.
GND (Pin 4): Device Ground. This pin must be connected
to a noise-free ground plane. A star-ground with related
circuits will give the best results. Be careful of trace impedance, as the GND pin carries supply return current.
Block Diagram
VIN
3
SHDN
2
BIAS
+
BANDGAP
–
VOUT
ERROR
AMP
6
RF
RG
GND
4
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LT6657
Applications Information
Line and Load Regulation
The line regulation of the LT6657 is typically well below
1ppm/V. A 10V change in input voltage causes a typical
output shift of only 2ppm. Load regulation is also less than
1ppm/mA in an MS8 package. A 5mA change in load current shifts output voltage by only 4ppm. These electrical
effects are measured with low duty cycle pulses.
To realize such excellent load regulation the IR drops on
the VOUT and GND lines need to be minimized. One ounce
copper foil printed circuit board has 0.5mΩ/square. Just
1mΩ of added trace resistance introduces an error of 1µV
for each 1mA passing through it. This will add a 0.4ppm/
mA to the load regulation with a 2.5V reference. These
externally created errors have the same order of magnitude as the typical load regulation values for the LT6657.
Minimizing wire resistance and using a separate ground
return for the load will maintain excellent load regulation.
When sourcing current, the ground connection pin can
be used as kelvin sensing for improved output regulation.
Additional output changes due to die temperature change
must be taken into account separately. These added effects
may be estimated from:
Line_Reg (in ppm) = (IIN + IOUT) • θJA • TC • VIN
Load_Reg (in ppm) = (VIN – VOUT) • θJA • TC • IOUT
Where voltages are in V, currents are in mA, package
thermal resistance θJA is in °C/mW, and temperature
coefficient, TC, is in ppm/°C. For example, with typical
quiescent current IIN = 1.2mA, IOUT = 1mA, VIN – VOUT = 1V,
the added line-regulation is typically 0.66ppm/V and
added load-regulation is typically 0.3ppm/mA for a TC
of 1ppm/°C and MSOP-8 package with θJA = 0.3°C/mW
thermal resistance.
Bypass and Load Capacitors
The LT6657 voltage reference requires a 0.1µF or larger
input capacitor placed close to the part to improve power
supply rejection. A long input wire with large series inductance can create ringing response to large load transients.
The output requires a capacitor of 1µF or higher placed
near the part. Frequency stability, turn-on time and settling
behavior are directly affected by the value and type of the
output capacitor. Equivalent resistance in series with the
output capacitor (ESR) introduces a zero in the output
buffer transfer function and can cause instability. It is
recommended to keep the ESR less than 0.5Ω to maintain
sufficient phase margin. Both capacitance and ESR are
frequency dependent. At higher frequencies, capacitance
drops and ESR increases. To ensure stability above 100kHz,
the output capacitor must also have suitable characteristics above 100kHz. The following paragraphs describe
capacitors with suitable performance.
For applications requiring a large output capacitor, a low
ESR ceramic capacitor in parallel with a bulk tantalum
capacitor provides an optimally damped response. For
example, a 47µF tantalum capacitor with larger ESR in
parallel with a 10µF ceramic capacitor with ESR smaller
than 0.5Ω improves transient response and increases
phase margin.
Give extra consideration to the use of ceramic capacitors
such as X7R types. These capacitors are small, come in
appropriate values and are relatively stable over a wide
temperature range. However, for low noise requirements,
X7R capacitors may not be suitable as they may exhibit a
piezoelectric effect. Mechanical vibrations cause a charge
displacement in the ceramic dielectric and the resulting
perturbations can appear as noise.
For very low noise applications, film capacitors should be
considered for their lack of piezoelectric effects. Film capacitors such as polyester, polycarbonate and polypropylene
have good temperature stability. Additional care must be
taken as polypropylene have an upper limit of 85°C to 105°C.
Above these temperatures the working voltage often needs
to be derated per manufacturer specifications. Another
type of film capacitor is polyphenylene sulfide (PPS).
These capacitors work over a wide temperature range,
are stable and have large capacitance values beyond 1µF.
In voltage reference applications, film capacitor lifetime
is affected by temperature and applied voltage. Capacitor
lifetime is degraded by operating near or exceeding the
rated voltage, at high temperature, with AC ripple or some
combination of these. Most voltage reference applications
present AC ripple only during transient events.
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LT6657
Applications Information
Turn-On and Line Transient Response
The turn-on time is slew-limited and determined by the
short-circuit current, the output capacitor, and the output
voltage value as determined by the equation:
tON = VOUT
Increasing the output load speeds up the response
(Figure 3).
VIN
0.2V/DIV
3V/DC
C
• OUT
ISC
For example, the LT6657-2.5V, with a 1µF output capacitor and a typical current limit of 15mA the turn-on time
would be:
1µF
tON = 2.5V •
= 167µs
15mA
The resulting turn-on time is shown in Figure 1.
VOUT
2mV/DIV
2.5V/DC
COUT = 1µF, IOUT = 1mA SOURCING
6657 F03
50µs/DIV
Figure 3. Line Transient Response with VIN = 0.4VP-P
A larger output capacitor lowers the amplitude response
with a longer time response trade-off (Figure 4).
VIN
1V/DIV
VIN
0.5V/DIV
3V/DC
GND
VOUT
1V/DIV
GND
VOUT
2mV/DIV
2.5V/DC
COUT = 1µF
50µs/DIV
6657 F01
COUT = 10µF, IOUT = 0mA
Figure 1. 2.5V Turn-On Characteristics
Line transient response with a 1µF output capacitor and
no output current is shown in Figure 2. The peak voltage
output response is less than 1mV.
6657 F04
50µs/DIV
Figure 4. Line Transient Response with VIN = 1VP-P
Load Transient Response
The test circuit of Figure 5 is used to measure load transient
response with various currents.
VIN
0.2V/DIV
3V/DC
2
VIN = 3V
3
VOUT
2mV/DIV
2.5V/DC
CIN
0.1µF
COUT = 1µF, IOUT = 0mA
50µs/DIV
LT6657
SHDN
OUT
6
VOUT
1k
VGEN
COUT
1µF
GND
6657 F05
4
6657 F02
Figure 2. Line Transient Response with VIN = 0.4VP-P
IN
Figure 5. Transient Load Test Circuit
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LT6657
Applications Information
Figure 6 and 7 shows the load transient response to a
5mA current step both sourcing and sinking.
IOUT
5mA
4mA
IOUT
0mA
VOUT
2mV/DIV/AC
2.5VDC
5mA
COUT = 1µF
VOUT
10mV/DIV/AC
2.5V/DC
50µs/DIV
6657 F09
Figure 9. Output Response with a 4mA to 5mA Load Step Sinking
COUT = 1µF
50µs/DIV
6657 F06
Figure 6. Output Response with a 5mA Load Step Sourcing
Figures 10 and 11 show the load transient response to an
even smaller 0.5mA current step both sourcing and sinking.
IOUT
0mA
IOUT
5mA
0.5mA
0mA
VOUT
2mV/DIV/AC
2.5V/DC
VOUT
10mV/DIV/AC
2.5VDC
COUT = 1µF
COUT = 1µF
50µs/DIV
50µs/DIV
6657 F07
6657 F10
Figure 10. Output Response with a 0.5mA Load Step Sourcing
Figure 7. Output Response with a 5mA Load Step Sinking
Figure 8 and 9 shows the load transient response to a
smaller 4mA to 5mA current step while sourcing and sinking.
IOUT
0.5mA
0mA
IOUT
4mA
VOUT
2mV/DIV/AC
2.5V/DC
5mA
COUT = 1µF
VOUT
2mV/DIV/AC
2.5V/DC
50µs/DIV
6657 F11
Figure 11. Output Response with a 0.5mA Load Step Sinking
COUT = 1µF
50µs/DIV
6657 F08
Figure 8. Output Response with a 4mA to 5mA Load Step Sourcing
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11
LT6657
Applications Information
LT6657 Sinking Current Dropout Description
The LT6657 output stage can source and sink current
of equal magnitude. When sourcing current it performs
as a conventional low dropout regulating device. When
sinking current, it can maintain a regulated output with
an input voltage equal to, more positive than, or also
slightly less than the output voltage. The specification
for dropout voltage while sinking is expressed in negative
voltage values for VIN – VOUT. A typical unit will maintain
a regulated output voltage while sinking current with an
input voltage 250mV (50mV guaranteed) below the output
voltage. Lower input voltage will cause the output to drop
out of regulation. This allows shunt reference applications
where the output and input can be tied together and sink
current from the output to ground.
Positive or Negative Shunt Mode Operation
In addition to the series mode operation, the LT6657 can
be operated in shunt mode. In this mode the reference is
wired as a two terminal circuit which can be used both
as a positive or a negative voltage reference, as shown in
Figures 12 and 13.
RSHUNT is chosen using the following formula:
RSHUNT =
VDD – VOUT
ISHUNT _ MAX
where: ISHUNT_MAX = 2.5mA + IOUT_MAX
2
3
–VDD
ISHUNT RSHUNT
IN
LT6657
SHDN
OUT
6
IOUT
+VOUT
COUT
1µF
GND
4
IOUT
–VOUT
6657 F13
Figure 13. Negative Shunt Mode Operation
The ISHUNT current has to be operated above 2.5mA to
obtain the same performance as the series mode operation. In shunt mode operation IOUT_MAX is less than or
equal to 8.5mA. A COUT of 1µF or more is required on the
output for stability.
Shutdown Mode
When the SHDN pin is pulled below 0.8V with respect to
ground, the LT6657 enters a low power state and turns the
output off. Quiescent current is typically 2µA. If SHDN is
set less than 0.4V the quiescent current drops to 0.01µA
typical. The SHDN pin turn-on threshold is 1.26V and it has
approximately 150mV hysteresis for the turn-off threshold.
The turn-on logic high voltage is 1.6V. Drive the SHDN
with either logic or an open-collector/drain with a pull-up
resistor. The resistor supplies the pull-up current to the
open-collector/drain logic, normally several microamperes,
plus the SHDN pin current, typically less than 5µA at 6V. If
unused, connect the SHDN input pin to VIN.
Power Dissipation
VDD
RSHUNT
2
3
IN
LT6657
SHDN
OUT
6
IOUT
COUT
1µF
GND
4
6657 F12
+VOUT
Power dissipation for LT6657 depends on VIN, load current
and the package type. The MSOP-8 package has a thermal
resistance of θJA = 273°C/W.
Although the maximum junction temperature is 150°C ,for
best performance it is recommended to limit the change
in junction temperature as much as possible. The plot in
Figure 12. Positive Shunt Mode Operation
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LT6657
Applications Information
Figure 14 shows the maximum ambient temperature limits
for different VIN and load condition using a maximum
junction temperature of 125°C in the MSOP-8 package.
If the load current exceeds 10mA the parts could begin to
current limit. In this case, the output voltage is no longer
regulated and the part could dissipate much more power
and operate hotter than the graph shows.
MAXIMUM AMBIENT
OPERATING TEMPERATURE (°C)
125
VOUT = 2.5V
115
105
95
85
75
65
55
45
10mA SINK MS8
10mA SOURCE MS8
0
5
10
15
20 25
VIN (V)
30
35
40
6657 F14
Figure 14. Maximum Ambient Operating Temperature
With a large input voltage and sourcing current, an internal
thermal shutdown protection circuit limits the maximum
power dissipation. When sinking current, there is no need
for thermal shutdown protection because the power dissipation is much smaller and the sinking current limit will
give some load protection.
Noise Performance and Specification
The LT6657 offers exceptional low noise for a bandgap
reference; only 0.5ppmP-P in the 0.1Hz to 10Hz bandwidth.
As a result system noise performance may be dominated
by system design and physical layout. Care is required to
achieve the best possible noise performance. The use of
dissimilar metals in component leads and PC board traces
creates thermocouples. Variations in thermal resistance,
caused by uneven air flow over the circuit board create differential lead temperature, thereby creating a thermoelectric
voltage noise at the output of the reference. Minimizing the
number of thermocouples, as well as limiting airflow, can
substantially reduce these errors. Additional information
can be found in Linear Technology Application Note 82.
Position the input and load capacitors close to the part.
Although the LT6657 has 130dB DC PSRR, the power supply should be as stable as possible to guarantee optimal
performance. A plot of the 0.1Hz to 10Hz low frequency
noise is shown in the Typical Performance Characteristics
section. Noise performance can be further improved by
wiring several LT6657s in parallel as shown in the Typical
Applications Section. With this technique the noise is
reduced by √N, where N is the number of LT6657s used.
Noise in any frequency band is a random function based
on physical properties such as thermal noise, shot noise,
and flicker noise. The most precise way to specify a random
error such as noise is in terms of its statistics, for example
as an RMS value. This allows for relatively simple maximum
error estimation, generally involving assumptions about
noise bandwidth and crest factor. Unlike wideband noise,
low frequency noise, typically specified in a 0.1Hz to 10Hz
band, has traditionally been specified in terms of expected
error, illustrated as peak-to-peak error. Low frequency
noise is generally measured with an oscilloscope over a
10 second time frame. This is a pragmatic approach, given
that it can be difficult to measure noise accurately at low
frequencies, and that it can also be difficult to agree on the
statistical characteristics of the noise, since flicker noise
dominates the spectral density. While practical, a random
sampling of 10 second intervals is an inadequate method
for representation of low frequency noise, especially for
systems where this noise is a dominant limit of system
performance. Given the random nature of noise, the output
voltage may be observed over many time intervals, each
giving different results. Noise specifications that were
determined using this method are prone to subjectivity,
and will tend toward a mean statistical value, rather than
the maximum noise that is likely to be produced by the
device in question.
Because the majority of voltage reference data sheets
express low frequency noise as a typical number, and as
it tends to be illustrated with a repeatable plot near the
mean of a distribution of peak-to-peak values, the LT6657
data sheet provides a similarly defined typical specification
in order to allow a reasonable direct comparison against
similar products. Data produced with this method generally
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13
LT6657
Applications Information
15V
+
1µF
10k
A1
LT1012
Q3
2N2907
–
T
4
A = 10
LOW NOISE
PRE-AMP
= TANTALUM,WET SLUG
ILEAK < 5nA
SEE TEXT/APPENDIX B
100k
1k*
1µF
200Ω*
450Ω*
900Ω*
LT6657
2.5V
OUT
T
100k
+
SHIELD
Q1
+
1300µF
SHDN
15V
–15V
–15V
–
VIN
IN
1N4697
10V
0.15µF
A2
LT1097
5
Q2
0.022µF
100k*
**1.2k
– INPUT
750Ω*
1µF
REFERENCE
UNDER TEST
10Ω*
–15V
SHIELDED CAN
AC LINE GROUND
0.1µF
6657 F16
A = 100 AND
0.1Hz TO 10Hz FILTER
0.1µF
1µF
+
124k*
A3
LT1012
–
124k*
–
A4
LT1012
ADC/DVM
SYSTEM
+
0.1µF
1M*
330µF
16V
10k*
330Ω*
330µF
16V
100Ω*
OUT
+
+
IN
330µF
16V
330µF
16V
+
+
2k
10k
TO ADC/DVM
SYSTEM
Figure 15. LT6657 Noise Test Circuitry (from AN124)
suggests that in a series of 10 second output voltage
measurements, at least half the observations should
have a peak-to-peak value that is below this number. For
example, the LT6657-2.5 measures less than 0.5ppmP-P
in at least 50% of the 10 second observations.
As mentioned above, the statistical distribution of noise
is such that if observed for long periods of time, the peak
error in output voltage due to noise may be much larger
than that observed in a smaller interval. The likely maximum error due to noise is often estimated using the RMS
value, multiplied by an estimated crest factor, assumed to
be in the range of 6 to 8.4. This maximum possible value
will only be observed if the output voltage is measured
for very long periods of time. Therefore, in addition to the
common method, a more thorough approach to measuring
noise has been used for the LT6657 (described in detail in
Linear Technology’s AN124) that allows more information
to be obtained from the result. In particular, this method
characterizes the noise over a significantly greater length
of time, resulting in a more complete description of low
frequency noise. The reference noise is measured at the
output of the circuit shown in Figure 15 with an ADC/DVM
system. Peak-to-peak voltage is then calculated for 10
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For more information www.linear.com/LT6657
LT6657
Applications Information
1.2
AVERAGE VP-P = 1.24µV
5000
1
4000
0.8
3000
0.6
2000
0.4
1000
0.2
0
0.8
1
1.2
1.6
1.4
PEAK-TO-PEAK NOISE (µVP-P)
CUMULATIVE PROBABILITY
NUMBER OF OBSERVATIONS
6000
0
1.8
6657 F16
Figure 16. LT6657 Low Frequency Noise Histogram
This method of testing low frequency noise is more practical
than common methods. The results yield a comprehensive
statistical description, rather than a single observation. In
addition, the direct measurement of output voltage over
time gives an actual representation of peak noise, rather
than an estimate based on statistical assumptions such
as crest factor.
Hysteresis
Thermal hysteresis is a measure of change of output
voltage as a result of temperature cycling. Figure 17
illustrates the typical hysteresis based on data taken
from the LT6657-2.5. A proprietary design technique
minimizes thermal hysteresis. The LT6657 is capable of
dissipating relatively high power. For example, with a 40V
input voltage and 5mA source load current applied to the
LT6657-2.5, the power dissipation is PD = 40V • 1.4mA +
37.5V • 5mA = 244mW, which causes an increase in the
die temperature of 73°C in MSOP-8 package. This could
increase the junction temperature above 125°C and may
cause the output to shift due to thermal hysteresis each
time the device is powered up.
20
COLD: 25°C TO –40°C TO 25°C
HOT: 25°C TO 125°C TO 25°C
MS8
16
NUMBER OF UNITS
second intervals over hundreds of intervals. The results are
then summarized in terms of the fraction of measurement
intervals for which observed noise is below a specified
level. For example, the LT6657-2.5 measures less than
0.55ppmP-P in 80% of the measurement intervals, and
less than 0.59ppmP-P in 95% of observation intervals.
The preamplifier and filter are shown in Figure 15. This
statistical variation in noise is illustrated in Figure 16.
12
8
4
0
–150
–100 –50
0
100
50
CHANGE IN OUTPUT VOLTAGE (ppm)
150
6657 F17
Figure 17. ∆VOUT Due to Thermal Hysteresis
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15
LT6657
Applications Information
Long-Term Drift
PC Board Layout Stress
The LT6657 drift data was taken on parts that were soldered into PC boards similar to a real world application.
The boards were then placed into a constant temperature
oven with TA = 35°C, their outputs scanned regularly and
measured with an 8.5 digit DVM. Typical long-term drift
is illustrated in Figure 18a and 18b.
The LT6657 is a very stable reference over temperature
with less than 1.5ppm/°C error as shown in the Electrical
Characteristics table. The mechanical stress caused by
soldering parts to a printed circuit board may cause the
output voltage to shift and the die temperature coefficient
to change. The PC Board can affect all aspects of stability, including long term stability, thermal hysteresis and
humidity stability. See Linear’s AN82 for more detailed
information.
LONG TERM DRIFT (ppm)
80
40
IR Reflow Shift
0
–40
–80
0
200
400
600
TIME (HOURS)
800
1000
6657 F18a
Figure 18a. Long-Term Drift MS8
40
300
0
–40
–80
380s
0
500
1000 1500 2000
TIME (HOURS)
2500
3000
150
RAMP
DOWN
tP
30s
T = 150°C
tL
130s
RAMP TO
150°C
75
40s
120s
6657 F18b
0
Figure 18b. Long-Term Drift MS8 Burn-In 150°C/24H
Figure 18.
TP = 260°C
TL = 217°C
TS(MAX) = 200°C
TS = 190°C
225
TEMPERATURE (°C)
LONG TERM DRIFT (ppm)
80
The mechanical stress of soldering a part to a board can
cause the output voltage to shift. Moreover, the heat of
an IR reflow or convection soldering oven can also cause
the output voltage to shift. The materials that make up a
semiconductor device and its package have different rates
of expansion and contraction. After a part undergoes the
extreme heat of a lead-free IR reflow profile, like the one
shown in Figure 19, the output voltage shifts. After the
device expands, due to the heat, and then contracts, the
stresses on the die move. This shift is similar to, but larger
than thermal hysteresis.
0
2
6
4
MINUTES
8
10
6657 F19
Figure 19. Lead-Free Reflow Profile
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LT6657
Applications Information
Experimental results of IR reflow shift are shown in Figure
20 for MS8. These results show only shift due to reflow
and not mechanical stress.
9
8
MS8
1 CYCLE
3 CYCLES
NUMBER OF UNITS
7
6
5
4
3
2
1
0
–300
–200 –100
0
200
100
CHANGE IN OUTPUT VOLTAGE (ppm)
300
6657 F20
Figure 20. ∆VOUT Due to IR Reflow (MS8 Package),
Peak Temperature = 260°C
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17
LT6657
Typical Applications
Extended Supply Range Reference
Boosted Output Current Reference
40V TO 100V
VOUT + 1.5V < VIN < 40V
270k
220Ω
2N3440
4.7µF
2N2905
IN
BZX84C12
LT6657
OUT
SHDN
IN
1µF
LT6657
0.1µF
0.1µF
IOUT
UP TO 300mA
OUT
SHDN
6657 TA02
GND
GND
1µF
6657 TA03
Boosted Output Current with Current Limit
Negative Shunt Mode Reference
VOUT + 2V < VIN < 40V
1
LED1*
4.7µF
220Ω
IN
10Ω
LT6657
OUT
SHDN
2
2N2905
–VDD
RSHUNT
ISHUNT
IOUT
1µF
GND
IOUT
–VOUT
6657 TA05
IN
LT6657
SHDN
0.1µF
V –V
RSHUNT = DD OUT
ISHUNT _MAX
IOUT
UP TO 100mA
OUT
ISHUNT _MAX = 2.5mA + IOUT _MAX
1µF
IOUT _MAX < 8.5mA
GND
6657 TA04
*LED CANNOT BE OMMITTED
THE LED CLAMPS THE VOLTAGE
DROP ACROSS THE 220Ω AND
LIMITS OUTPUT CURRENT
Sinking Current from External Circuitry
VEXT (>VOUT)
RLOAD
(VOUT – 230mV) TO 40V
IN
LT6657
VOUT
OUT
SHDN
0.1µF
1µF
GND
6657 TA06
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18
For more information www.linear.com/LT6657
LT6657
Typical Applications
Low Noise Statistical Averaging Reference
eNOUT = eN/√N Where N is the Number of LT6657s in Parallel
3V TO
40V
IN
LT6657
20Ω
OUT
VOUT = 2.5V
SHDN
0.1µF
1µF
1µF
GND
IN
LT6657
20Ω
OUT
SHDN
0.1µF
1µF
GND
IN
LT6657
20Ω
OUT
SHDN
0.1µF
GND
1µF
IN
6657 TA07a
LT6657
20Ω
OUT
SHDN
0.1µF
1µF
GND
Low Frequency Noise (0.1Hz to 10Hz) with Four LT6657s in Parallel
9000
1
7000
6000
0.8
5000
0.6
4000
3000
0.4
2000
0.2
1000
0
0.4
CUMULATIVE PROBABILITY
NUMBER OF OBSERVATIONS
8000
1.2
AVERAGE VP-P = 0.63µV
0.5
0.6
0.8
0.9
0.7
PEAK-TO-PEAK NOISE (µVP-P)
0
1.0
6657 TA07b
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For more information www.linear.com/LT6657
19
LT6657
Package Description
Please refer to http://www.linear.com/product/LT6657#packaging for the most recent package drawings.
MS8 Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1660 Rev G)
0.889 ±0.127
(.035 ±.005)
5.10
(.201)
MIN
3.20 – 3.45
(.126 – .136)
3.00 ±0.102
(.118 ±.004)
(NOTE 3)
0.65
(.0256)
BSC
0.42 ± 0.038
(.0165 ±.0015)
TYP
8
7 6 5
0.52
(.0205)
REF
RECOMMENDED SOLDER PAD LAYOUT
0.254
(.010)
3.00 ±0.102
(.118 ±.004)
(NOTE 4)
4.90 ±0.152
(.193 ±.006)
DETAIL “A”
0° – 6° TYP
GAUGE PLANE
0.53 ±0.152
(.021 ±.006)
DETAIL “A”
1
2 3
4
1.10
(.043)
MAX
0.86
(.034)
REF
0.18
(.007)
SEATING
PLANE
0.22 – 0.38
(.009 – .015)
TYP
0.65
(.0256)
NOTE:
BSC
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
0.1016 ±0.0508
(.004 ±.002)
MSOP (MS8) 0213 REV G
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20
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LT6657
Revision History
REV
DATE
DESCRIPTION
A
03/16
Conditions Added for Electrical Characteristic, Minimum VIN – VOUT
PAGE NUMBER
B
06/16
3
Added 3V, 5V options
1, 2, 6, 7
Changed CL, CLOAD to COUT
9, 10, 11
Corrected Graphs G03, G12
5, 6
6657fb
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection
of its circuits
as described
herein will not infringe on existing patent rights.
For more
information
www.linear.com/LT6657
21
LT6657
Typical Application
Low Noise Precision 20-Bit Analog-to-Digital Converter Application
SNR = 97dB
SINAD = 97dB
THD = –117dB
SFDR = 120dB
2
VIN = 5V
0.1µF
3
IN
OUT
6
LT6657
47µF
10V
X7R
1µF
SHDN
0.1µF
GND
4
+3.3V
10µF
6.3V
2
+
4
10Ω
V–
6800pF
–3.6V
NPO
0.1µF
4
3300pF
1206 NPO
VIN–
5
+
–
LT6203
10Ω
IN+
LTC2378-20
6800pF
NPO
5
IN–
GND
GND
GND
GND
VIN+
10µF
6.3V
9
CNV
13 SCK
SCK
14 SDO
SDO
11 BUSY
BUSY
RDL/SDI
12 RD
3
6
10
16
1
V+
8V LT6203
3
5
–
1
0.1µF
VDD 2
OVDD 15
REF 7
8
REF/DGC
+2.5V
7
6657 TA08
1k
6
Related Parts
PART NUMBER DESCRIPTION
COMMENTS
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LT1461
Micropower Series Low Dropout
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LT1790
Micropower Precision Series References
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LT6650
Micropower Reference with Buffer Amplifier
0.5% Max, 5.6µA Supply, SOT23 Package
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High Precision, Buffered Voltage Reference Family
0.05% Max Initial Error, 5ppm/°C Max Drift, Shutdown Current <2µA, –40°C to
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LT6654
Low Noise, High Voltage, High Output Drive
Voltage Reference Family
1.6ppm Peak-to-Peak Noise (0.1Hz to 10Hz), Sink/Source ±10mA, 10ppm/°C Max
Drift, –40°C to 125°C Operation
LTC6655
Precision, Very Low Noise and Temperature Drift,
Voltage Reference Family
0.25ppm Peak-to-Peak Noise (0.1Hz to 10Hz), Sink/Source ±5mA, 0.025% Max,
2ppm/°C Max Drift, –40°C to 125°C Operation
LT6656
Ultra Low Current Series Voltage Reference Family
Supply current < 1µA, 0.05% Max, 10ppm/°C, Sink/Source ±5mA
6657fb
22 Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
For more information www.linear.com/LT6657
(408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com/LT6657
LT 0616 REV B • PRINTED IN USA
 LINEAR TECHNOLOGY CORPORATION 2015