AD AD9683BCPZ-170 Analog-to-digital converter Datasheet

FEATURES
FUNCTIONAL BLOCK DIAGRAM
JESD204B Subclass 0 or Subclass 1 coded serial digital outputs
Signal-to-noise ratio (SNR) = 70.6 dBFS at 185 MHz AIN and
250 MSPS
Spurious-free dynamic range (SFDR) = 88 dBc at 185 MHz AIN
and 250 MSPS
Total power consumption: 434 mW at 250 MSPS
1.8 V supply voltages
Integer 1-to-8 input clock divider
Sample rates of up to 250 MSPS
Intermediate frequency (IF) sampling frequencies of up to
400 MHz
Internal analog-to-digital converter (ADC) voltage reference
Flexible analog input range
1.4 V p-p to 2.0 V p-p (1.75 V p-p nominal)
ADC clock duty cycle stabilizer (DCS)
Serial port control
Energy saving power-down modes
AVDD DRVDD
DVDD
AGND
DGND DRGND
AD9683
JESD204B
INTERFACE
VIN+
VIN–
PIPELINE
14-BIT ADC
HIGH
SPEED
SERIALIZERS
CML, TX
OUTPUTS
SERDOUT0±
VCM
CMOS
DIGITAL
INPUT
CONTROL
REGISTERS
SYSREF±
SYNCINB±
CLK±
RFCLK
PDWN
CLOCK
GENERATION
CMOS DIGITAL
INPUT/OUTPUT
RST
FAST
DETECT
SDIO SCLK CS
CMOS
DIGITAL
OUTPUT
FD
11410-001
Data Sheet
14-Bit, 170 MSPS/250 MSPS, JESD204B,
Analog-to-Digital Converter
AD9683
Figure 1.
GENERAL DESCRIPTION
APPLICATIONS
Communications
Diversity radio systems
Multimode digital receivers (3G)
TD-SCDMA, WiMAX, W-CDMA, CDMA2000, GSM, EDGE, LTE
DOCSIS 3.0 CMTS upstream receive paths
HFC digital reverse path receivers
Smart antenna systems
Electronic test and measurement equipment
Radar receivers
COMSEC radio architectures
IED detection/jamming systems
General-purpose software radios
Broadband data applications
Ultrasound equipment
Rev. D
The AD9683 is a 14-bit ADC with sampling speeds of up to
250 MSPS. The AD9683 supports communications applications
where low cost, small size, wide bandwidth, and versatility are
desired.
The ADC core features a multistage, differential pipelined
architecture with integrated output error correction logic. The
ADC core features wide bandwidth inputs supporting a variety
of user-selectable input ranges. An integrated voltage reference
eases design considerations. A duty cycle stabilizer (DCS) is
provided to compensate for variations in the ADC clock duty cycle,
allowing the converter to maintain excellent performance. The
JESD204B high speed serial interface reduces board routing
requirements and lowers pin count requirements for the
receiving device.
The ADC output data is routed directly to the JESD204B serial
output lane. These outputs are at CML voltage levels. Data can be
sent through the lane at the maximum sampling rate of 250 MSPS,
which results in a lane rate of 5 Gbps. Synchronization inputs
(SYNCINB± and SYSREF±) are provided.
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AD9683* PRODUCT PAGE QUICK LINKS
Last Content Update: 03/25/2017
COMPARABLE PARTS
TOOLS AND SIMULATIONS
View a parametric search of comparable parts.
• Visual Analog
• AD9683 IBIS Model
EVALUATION KITS
• AD9683 Evaluation Board
REFERENCE MATERIALS
Informational
DOCUMENTATION
• JESD204 Serial Interface
Application Notes
Press
• AN-1142: Techniques for High Speed ADC PCB Layout
• JESD204B FPGA Debug Software Accelerates High-speed
Design
• AN-282: Fundamentals of Sampled Data Systems
• AN-345: Grounding for Low-and-High-Frequency Circuits
• Xilinx and Analog Devices Achieve JEDEC JESD204B
Interoperability
• AN-501: Aperture Uncertainty and ADC System
Performance
Technical Articles
• AN-737: How ADIsimADC Models an ADC
• MS-2124: Understanding AC Behaviors of High Speed
ADCs
• AN-741: Little Known Characteristics of Phase Noise
• MS-2210: Designing Power Supplies for High Speed ADC
• AN-742: Frequency Domain Response of SwitchedCapacitor ADCs
Tutorials
• AN-807: Multicarrier WCDMA Feasibility
• MT-075: Differential Drivers for High Speed ADCs
Overview
• AN-827: A Resonant Approach to Interfacing Amplifiers to
Switched-Capacitor ADCs
• AN-835: Understanding High Speed ADC Testing and
Evaluation
DESIGN RESOURCES
• AD9683 Material Declaration
• AN-851: A WiMax Double Downconversion IF Sampling
Receiver Design
• PCN-PDN Information
• AN-877: Interfacing to High Speed ADCs via SPI
• Symbols and Footprints
• Quality And Reliability
• AN-878: High Speed ADC SPI Control Software
• AN-905: Visual Analog Converter Evaluation Tool Version
1.0 User Manual
• AN-935: Designing an ADC Transformer-Coupled Front
End
Data Sheet
• AD9683: 14-Bit, 170 MSPS/250 MSPS, JESD204B, Analogto-Digital Converter Data Sheet
SOFTWARE AND SYSTEMS REQUIREMENTS
• ADC-FMC Interposer & Xilinx ZC706 Reference Design
DISCUSSIONS
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SAMPLE AND BUY
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AD9683
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Power Dissipation and Standby Mode .................................... 23
Applications ....................................................................................... 1
Digital Outputs ............................................................................... 24
Functional Block Diagram .............................................................. 1
JESD204B Transmit Top Level Description............................ 24
General Description ......................................................................... 1
ADC Overrange and Gain Control.......................................... 29
Revision History ............................................................................... 2
DC Correction (DCC) ................................................................... 31
Product Highlights ........................................................................... 3
DC Correction Bandwidth........................................................ 31
Specifications..................................................................................... 4
DC Correction Readback .......................................................... 31
ADC DC Specifications ............................................................... 4
DC Correction Freeze ................................................................ 31
ADC AC Specifications ............................................................... 5
DC Correction Enable Bits ....................................................... 31
Digital Specifications ................................................................... 6
Serial Port Interface (SPI) .............................................................. 32
Switching Specifications .............................................................. 8
Configuration Using the SPI ..................................................... 32
Timing Specifications .................................................................. 9
Hardware Interface..................................................................... 32
Absolute Maximum Ratings.......................................................... 10
SPI Accessible Features .............................................................. 33
Thermal Characteristics ............................................................ 10
Memory Map .................................................................................. 34
ESD Caution ................................................................................ 10
Reading the Memory Map Register Table............................... 34
Pin Configuration and Function Descriptions ........................... 11
Memory Map Register Table ..................................................... 35
Typical Performance Characteristics ........................................... 13
Memory Map Register Descriptions ........................................ 39
Equivalent Circuits ......................................................................... 18
Applications Information .............................................................. 43
Theory of Operation ...................................................................... 19
Design Guidelines ...................................................................... 43
ADC Architecture ...................................................................... 19
Outline Dimensions ....................................................................... 44
Analog Input Considerations.................................................... 19
Ordering Guide .......................................................................... 44
Voltage Reference ....................................................................... 20
Clock Input Considerations ...................................................... 21
REVISION HISTORY
6/2016—Rev. C to Rev.D
Changes to Table 17 ........................................................................ 37
Change to JESD204B Link Control 1 (Address 0x5F) Section ....... 40
9/2015—Rev. B to Rev. C
Changes to General Description Section ...................................... 3
Changes to Nyquist Clock Input Options Section ..................... 21
Changes to JESD204B Overview Section .................................... 24
Changes to Figure 60 ...................................................................... 27
Change to Table 17 ......................................................................... 37
5/2014—Rev. A to Rev. B
Changed Minimum RF Clock Rate from 625 MHz to 500 MHz
(Throughout) .................................................................................... 6
Changes to SYNCINB+ Pin Description .................................... 11
Changes to Transfer Register Map Section ................................. 34
Changes to Register 0x3A ............................................................. 36
Changes to Register 0x6F, Register 0x70, Register 0x72,
Register 0x73, Register 0x74, Register 0x75 ................................ 38
Changes to JESD204B Link Control 2 (Address 0x60) Section..... 40
2/2014—Rev. 0 to Rev. A
Changes to Data Output Parameters, Table 4 ................................8
Changes to Figure 3 ...........................................................................9
4/2013—Revision 0: Initial Version
Rev. D | Page 2 of 44
Data Sheet
AD9683
Flexible power-down options allow significant power savings,
when desired. Programmable overrange level detection is
supported via the dedicated fast detect pins.
Programming for setup and control is accomplished using a
3-wire SPI-compatible serial interface.
The AD9683 is available in a 32-lead LFCSP and is specified
over the industrial temperature range of −40°C to +85°C.
PRODUCT HIGHLIGHTS
1. Integrated 14-bit, 170 MSPS/250 MSPS ADC.
2. The configurable JESD204B output block supports lane
rates up to 5 Gbps.
3. An on-chip, phase-locked loop (PLL) allows users to provide a
single ADC sampling clock; the PLL multiplies the ADC
sampling clock to produce the corresponding JESD204B
data rate clock.
4. Support for an optional radio frequency (RF) clock input to
ease system board design.
5. Proprietary differential input maintains excellent SNR
performance for input frequencies of up to 400 MHz.
6. Operation from a single 1.8 V power supply.
7. Standard serial port interface (SPI) that supports various
product features and functions, such as controlling the clock
DCS, power-down, test modes, voltage reference mode,
overrange fast detection, and serial output configuration.
Rev. D | Page 3 of 44
AD9683
Data Sheet
SPECIFICATIONS
ADC DC SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, DVDD = 1.8 V, maximum sample rate for speed grade, VIN = −1.0 dBFS differential input, 1.75 V p-p
full-scale input range, duty cycle stabilizer enabled, default SPI, unless otherwise noted.
Table 1.
Parameter
RESOLUTION
ACCURACY
No Missing Codes
Offset Error
Gain Error
Differential Nonlinearity (DNL)
Integral Nonlinearity (INL)1
TEMPERATURE DRIFT
Offset Error
Gain Error
INPUT REFERRED NOISE
VREF = 1.75 V
ANALOG INPUT
Input Span
Input Capacitance2
Input Resistance3
Input Common-Mode Voltage
POWER SUPPLIES
Supply Voltage
AVDD
DRVDD
DVDD
Supply Current
IAVDD
IDRVDD + IDVDD
POWER CONSUMPTION
Sine Wave Input
Standby Power4
Power-Down Power5
Temperature
Full
Min
14
Full
Full
Full
Full
25°C
Full
25°C
AD9683-170
Typ
Max
Min
14
Guaranteed
AD9683-250
Typ
Max
Unit
Bits
Guaranteed
±0.8
±1.5
mV
%FSR
LSB
LSB
LSB
LSB
Full
Full
±7
±13
±7
±39
ppm/°C
ppm/°C
25°C
1.38
1.42
LSB rms
Full
Full
Full
Full
1.75
2.5
20
0.9
1.75
2.5
20
0.9
V p-p
pF
kΩ
V
Full
Full
Full
±9
−6.6/−0.3
±0.8
±9
−5.3/+1.2
±0.75
±0.5
±0.5
±1.6
1.7
1.7
1.7
1.8
1.8
1.8
1.9
1.9
1.9
Full
Full
135
68
Full
Full
Full
365
221
9
±2.7
1.7
1.7
1.7
1.8
1.8
1.8
1.9
1.9
1.9
V
V
V
151
73
149
92
163
97
mA
mA
403
434
266
9
468
mW
mW
mW
Measured with a low input frequency, full-scale sine wave.
Input capacitance refers to the effective capacitance between one differential input pin and its complement.
3
Input resistance refers to the effective resistance between one differential input pin and its complement.
4
Standby power is measured with a low input frequency, full-scale sine wave, and the CLK± pins active. Address 0x08 is set to 0x20, and the PDWN pin is asserted.
5
Power-down power is measured with a low input frequency, a full-scale sine wave, RFCLK pulled high, and the CLK± pins active. Address 0x08 is set to 0x00, and the
PDWN pin is asserted.
1
2
Rev. D | Page 4 of 44
Data Sheet
AD9683
ADC AC SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, DVDD = 1.8 V, maximum sample rate for speed grade, VIN = −1.0 dBFS differential input, 1.75 V p-p
full-scale input range, default SPI, unless otherwise noted.
Table 2.
Parameter1
SIGNAL-TO-NOISE-RATIO (SNR)
fIN = 30 MHz
fIN = 90 MHz
fIN = 140 MHz
fIN = 185 MHz
fIN = 220 MHz
SIGNAL-TO-NOISE AND DISTORTION (SINAD)
fIN = 30 MHz
fIN = 90 MHz
fIN = 140 MHz
fIN = 185 MHz
fIN = 220 MHz
EFFECTIVE NUMBER OF BITS (ENOB)
fIN = 30 MHz
fIN = 90 MHz
fIN = 140 MHz
fIN = 185 MHz
fIN = 220 MHz
SPURIOUS-FREE DYNAMIC RANGE (SFDR)
fIN = 30 MHz
fIN = 90 MHz
fIN = 140 MHz
fIN = 185 MHz
fIN = 220 MHz
WORST SECOND OR THIRD HARMONIC
fIN = 30 MHz
fIN = 90 MHz
fIN = 140 MHz
fIN = 185 MHz
fIN = 220 MHz
WORST OTHER (HARMONIC OR SPUR)
fIN = 30 MHz
fIN = 90 MHz
fIN = 140 MHz
fIN = 185 MHz
fIN = 220 MHz
Temperature
25°C
25°C
Full
25°C
25°C
Full
25°C
25°C
25°C
Full
25°C
25°C
Full
25°C
Min
AD9683-170
Typ
Max
Min
AD9683-250
Typ
Max
72.3
72.0
72.1
71.7
71.3
70.5
71.3
70.6
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
71
70.0
70.0
70.0
71.3
70.8
70.9
70.6
70.2
69.5
70.1
69.5
Unit
68.8
68.7
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
25°C
25°C
25°C
25°C
25°C
11.5
11.5
11.4
11.3
11.1
11.5
11.4
11.4
11.3
11.1
Bits
Bits
Bits
Bits
Bits
25°C
25°C
Full
25°C
25°C
Full
25°C
94
89
87
86
94
89
87
88
dBc
dBc
dBc
dBc
dBc
dBc
dBc
69.9
68.7
81
80
87
86
25°C
25°C
Full
25°C
25°C
Full
25°C
−94
−89
−87
−86
25°C
25°C
Full
25°C
25°C
Full
25°C
Rev. D | Page 5 of 44
−81
−94
−89
−87
−88
−87
−86
−99
−92
−95
−94
−80
−83
−96
−94
−94
−93
−82
−95
−92
dBc
dBc
dBc
dBc
dBc
dBc
dBc
dBc
dBc
dBc
dBc
dBc
dBc
dBc
AD9683
Parameter1
TWO-TONE SFDR
fIN1 = 184.12 MHz (−7 dBFS), fIN2 = 187.12 MHz (−7 dBFS)
FULL POWER BANDWIDTH2
1
2
Data Sheet
Temperature
25°C
25°C
Min
AD9683-170
Typ
Max
Min
AD9683-250
Typ
Max
87
1000
87
1000
Unit
dBc
MHz
See the AN-835 Application Note, Understanding High Speed ADC Testing and Evaluation for a complete set of definitions.
Full power bandwidth is the bandwidth of operation determined by where the spectral power of the fundamental frequency is reduced by 3 dB.
DIGITAL SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, DVDD = 1.8 V, maximum sample rate for speed grade, VIN = −1.0 dBFS differential input, 1.75 V p-p
full-scale input range, DCS enabled, default SPI, unless otherwise noted.
Table 3.
Parameter
DIFFERENTIAL CLOCK INPUTS (CLK+, CLK−)
Input CLK± Clock Rate
Logic Compliance
Internal Common-Mode Bias
Differential Input Voltage
Input Voltage Range
Input Common-Mode Range
High Level Input Current
Low Level Input Current
Input Capacitance
Input Resistance
RF CLOCK INPUT (RFCLK)
RF Clock Rate
Logic Compliance
Internal Bias
Input Voltage Range
High Input Voltage Level
Low Input Voltage Level
High Level Input Current
Low Level Input Current
Input Capacitance
Input Resistance (AC-Coupled)
SYNCIN INPUTS (SYNCINB+/SYNCINB−)
Logic Compliance
Internal Common-Mode Bias
Differential Input Voltage Range
Input Voltage Range
Input Common-Mode Range
High Level Input Current
Low Level Input Current
Input Capacitance
Input Resistance
Temperature
Min
Full
40
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Rev. D | Page 6 of 44
Typ
Max
Unit
625
MHz
CMOS/LVDS/LVPECL
0.9
0.3
AGND
0.9
0
−60
8
12
V
V p-p
V
V
µA
µA
pF
kΩ
1500
MHz
3.6
AVDD
1.4
+60
0
4
10
500
CMOS/LVDS/LVPECL
0.9
AGND
1.2
AGND
0
−150
8
AVDD
AVDD
0.6
+150
0
1
10
12
CMOS/LVDS
0.9
0.3
DGND
0.9
−5
−10
12
3.6
DVDD
1.4
+5
+10
1
16
20
V
V
V
V
µA
µA
pF
kΩ
V
V p-p
V
V
µA
µA
pF
kΩ
Data Sheet
Parameter
SYSREF INPUTS (SYSREF+/SYSREF−)
Logic Compliance
Internal Common-Mode Bias
Differential Input Voltage Range
Input Voltage Range
Input Common-Mode Range
High Level Input Current
Low Level Input Current
Input Capacitance
Input Resistance
LOGIC INPUT (RST)1
High Level Input Voltage
Low Level Input Voltage
High Level Input Current
Low Level Input Current
Input Resistance
Input Capacitance
LOGIC INPUTS (SCLK, PDWN, CS2)3
High Level Input Voltage
Low Level Input Voltage
High Level Input Current
Low Level Input Current
Input Resistance
Input Capacitance
LOGIC INPUT (SDIO)3
High Level Input Voltage
Low Level Input Voltage
High Level Input Current
Low Level Input Current
Input Resistance
Input Capacitance
DIGITAL OUTPUTS (SERDOUT0+/SERDOUT0−)
Logic Compliance
Differential Output Voltage (VOD)
Output Offset Voltage (VOS)
DIGITAL OUTPUTS (SDIO/FD4)
High Level Output Voltage (VOH)
IOH = 50 µA
IOH = 0.5 mA
IOH = 2.0 mA
Low Level Output Voltage (VOL)
IOL = 2.0 mA
IOL = 1.6 mA
IOL = 50 µA
AD9683
Temperature
Min
Typ
Max
Unit
LVDS
Full
Full
Full
Full
Full
Full
Full
Full
0.9
0.3
AGND
0.9
−5
−10
8
Full
Full
Full
Full
Full
Full
1.22
0
−5
−100
Full
Full
Full
Full
Full
Full
1.22
0
45
−10
Full
Full
Full
Full
Full
Full
1.22
0
45
−10
Full
Full
400
0.75
Full
Full
Full
1.79
1.75
1.6
Full
Full
Full
Pull-up.
Needs an external pull-up.
Pull-down.
4
Compatible with JEDEC standard JESD8-7A.
1
2
3
Rev. D | Page 7 of 44
3.6
AVDD
1.4
+5
+10
4
10
12
2.1
0.6
+5
−45
V
V
µA
µA
kΩ
pF
2.1
0.6
100
+10
V
V
µA
µA
kΩ
pF
2.1
0.6
100
+10
V
V
µA
µA
kΩ
pF
750
1.05
mV
V
26
2
26
2
26
5
CML
600
DRVDD/2
V
V p-p
V
V
µA
µA
pF
kΩ
V
V
V
0.25
0.2
0.05
V
V
V
AD9683
Data Sheet
SWITCHING SPECIFICATIONS
Table 4.
Parameter
CLOCK INPUT PARAMETERS
Conversion Rate1
SYSREF± Setup Time to Rising Edge CLK±2
SYSREF± Hold Time from Rising Edge CLK±2
SYSREF± Setup Time to Rising Edge RFCLK±2
SYSREF± Hold Time from Rising Edge RFCLK±2
CLK± Pulse Width High
Divide-by-1 Mode, DCS Enabled
Divide-by-1 Mode, DCS Disabled
Divide-by-2 Mode Through Divide-by-8 Mode
Aperture Delay
Aperture Uncertainty (Jitter)
DATA OUTPUT PARAMETERS
Data Output Period or Unit Interval (UI)
Data Output Duty Cycle
Data Valid Time
PLL Lock Time
Wake-Up Time
Standby
ADC (Power-Down)3
Output (Power-Down)4
Subclass 0: SYNCINB± Falling Edge to First Valid
K.28 Characters (Delay Required for Rx CGS Start)
Subclass 1: SYSREF± Rising Edge to First Valid K.28
Characters (Delay Required for SYNCINB± Rising
Edge/Rx CGS Start)
CGS Phase K.28 Characters Duration
Pipeline Delay
JESD204B (Latency)
Fast Detect (Latency)
Lane Rate
Uncorrelated Bounded High Probability (UBHP) Jitter
Random Jitter
At 3.4 Gbps
At 5 Gbps
Output Rise/Fall Time
Differential Termination Resistance
Out-of-Range Recovery Time
AD9683-170
Min Typ Max
AD9683-250
Min Typ Max
Full
Full
Full
Full
Full
40
40
2.61
2.76
0.8
tA
tJ
Full
Full
Full
Full
Full
tLOCK
Symbol
Temperature
fS
tREFS
tREFH
tREFSRF
tREFHRF
tCH
170
300
40
400
0
2.9
2.9
250
MSPS
ps
ps
ps
ps
2.2
2.1
300
40
400
0
1.0
0.16
1.0
0.16
ns
ns
ns
ns
ps rms
Full
25°C
25°C
25°C
20 × fS
50
0.82
25
20 × fS
50
0.78
25
Seconds
%
UI
µs
25°C
25°C
25°C
Full
10
250
50
10
250
50
5
5
µs
µs
µs
Multiframes
Full
6
6
Multiframes
Full
1
1
Multiframe
Full
Full
Full
Full
36
7
3.4
10
Full
Full
Full
25°C
Full
2.4
3.19
3.05
1.8
1.9
0.8
36
7
2
Rev. D | Page 8 of 44
12
Cycles5
Cycles5
Gbps
ps
1.7
60
100
3
ps rms
ps rms
ps
Ω
Cycles5
5
60
100
3
Conversion rate is the clock rate after the divider.
Refer to Figure 3 for timing diagram.
3
Wake-up time ADC is defined as the time required for the ADC to return to normal operation from power-down mode.
4
Wake-up time output is defined as the time required for JESD204B output to return to normal operation from power-down mode.
5
Cycles refers to ADC conversion rate cycles.
1
2.0
2.0
Unit
5
Data Sheet
AD9683
TIMING SPECIFICATIONS
Table 5.
Parameter
SPI TIMING REQUIREMENTS
tDS
tDH
tCLK
tS
tH
tHIGH
tLOW
tEN_SDIO
Test Conditions/Comments
See Figure 67
Setup time between the data and the rising edge of SCLK
Hold time between the data and the rising edge of SCLK
Period of the SCLK
Setup time between CS and SCLK
Hold time between CS and SCLK
Minimum period that SCLK must be in a logic high state
Minimum period that SCLK must be in a logic low state
Time required for the SDIO pin to switch from an input to an
output relative to the SCLK falling edge (not shown in figures)
Time required for the SDIO pin to switch from an output to an
input relative to the SCLK rising edge (not shown in figures)
Time required after hard or soft reset until SPI access is available
(not shown in figures)
tDIS_SDIO
tSPI_RST
Min
Typ
Max
Unit
2
2
40
2
2
10
10
10
ns
ns
ns
ns
ns
ns
ns
ns
10
ns
500
µs
Timing Diagrams
SAMPLE N
N – 36
N+1
N – 35
ANALOG
INPUT
SIGNAL
N – 34
N–1
N – 33
CLK–
CLK+
CLK–
CLK+
SAMPLE N – 36
ENCODED INTO 2
8B/10B SYMBOLS
11410-002
SERDOUT0±
SAMPLE N – 34
ENCODED INTO 2
8B/10B SYMBOLS
SAMPLE N – 35
ENCODED INTO 2
8B/10B SYMBOLS
Figure 2. Data Output Timing
RFCLK
CLK–
CLK+
SYSREF–
tREFS
tREFSRF
tREFH
tREFHRF
11410-003
SYSREF+
NOTES
1. CLOCK INPUT IS EITHER RFCLK OR CLK±, NOT BOTH.
Figure 3. SYSREF± Setup and Hold Timing (Clock Input Either RFCLK or CLK±, Not Both)
Rev. D | Page 9 of 44
AD9683
Data Sheet
ABSOLUTE MAXIMUM RATINGS
THERMAL CHARACTERISTICS
Table 6.
Parameter
Electrical
AVDD to AGND
DRVDD to DRGND
DVDD to DGND
VIN+, VIN− to AGND
CLK+, CLK− to AGND
RFCLK to AGND
VCM to AGND
CS, PDWN to DGND
SCLK to DGND
SDIO to DGND
RST to DGND
FD to DGND
SERDOUT0+, SERDOUT0− to AGND
SYNCINB+, SYNCINB− to DGND
SYSREF+, SYSREF− to AGND
Environmental
Operating Temperature Range
(Ambient)
Maximum Junction Temperature
Under Bias
Storage Temperature Range
(Ambient)
Rating
−0.3 V to +2.0 V
−0.3 V to +2.0 V
−0.3 V to +2.0 V
−0.3 V to AVDD + 0.2 V
−0.3 V to AVDD + 0.2 V
−0.3 V to AVDD + 0.2 V
−0.3 V to AVDD + 0.2 V
−0.3 V to DVDD + 0.3 V
−0.3 V to DVDD + 0.3 V
−0.3 V to DVDD + 0.3 V
−0.3 V to DVDD + 0.3 V
−0.3 V to DVDD + 0.3 V
−0.3 V to DRVDD + 0.3 V
−0.3 V to DVDD + 0.3 V
−0.3 V to AVDD + 0.3 V
−40°C to +85°C
The exposed pad must be soldered to the ground plane of the
LFCSP. This increases the reliability of the solder joints,
maximizing the thermal capability of the package.
Table 7. Thermal Resistance
Package Type
32-Lead LFCSP
5 mm × 5 mm
(CP-32-12)
θJA1, 2
37.1
32.4
29.1
θJC1, 3, 4
3.1
N/A
N/A
θJB1, 4, 5
20.7
N/A
N/A
Unit
°C/W
°C/W
°C/W
Per JEDEC 51-7, plus JEDEC 25-5 2S2P test board.
Per JEDEC JESD51-2 (still air) or JEDEC JESD51-6 (moving air).
3
Per MIL-STD-883, Method 1012.1.
4
N/A = not applicable.
5
Per JEDEC JESD51-8 (still air).
1
2
Typical θJA is specified for a 4-layer printed circuit board (PCB)
with a solid ground plane. As shown in Table 7, airflow increases
heat dissipation, which reduces θJA. In addition, metal in direct
contact with the package leads from metal traces, through holes,
ground, and power planes reduces the θJA.
ESD CAUTION
150°C
Airflow
Velocity
(m/sec)
0
1.0
2.5
−65°C to +125°C
Stresses at or above those listed under Absolute Maximum
Ratings may cause permanent damage to the product. This is a
stress rating only; functional operation of the product at these
or any other conditions above those indicated in the operational
section of this specification is not implied. Operation beyond
the maximum operating conditions for extended periods may
affect product reliability.
Rev. D | Page 10 of 44
Data Sheet
AD9683
32
31
30
29
28
27
26
25
AVDD
AVDD
AVDD
VIN+
VIN–
AVDD
AVDD
VCM
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
1
2
3
4
5
6
7
8
AD9683
TOP VIEW
(Not to Scale)
24
23
22
21
20
19
18
17
DNC
PDWN
CS
SCLK
SDIO
FD
DGND
DVDD
NOTES
1. DNC = DO NOT CONNECT. DO NOT CONNECT TO THIS PIN.
2. THE EXPOSED THERMAL PAD ON THE BOTTOM OF THE
PACKAGE PROVIDES THE GROUND REFERENCE FOR
AVDD. THIS EXPOSED PAD MUST BE CONNECTED TO
AGND FOR PROPER OPERATION.
11410-004
DGND
DVDD
SYNCINB+
SYNCINB–
DRGND
DRVDD
SERDOUT0–
SERDOUT0+
9
10
11
12
13
14
15
16
RFCLK
CLK–
CLK+
AVDD
SYSREF+
SYSREF–
AVDD
RST
Figure 4. Pin Configuration (Top View)
Table 8. Pin Function Descriptions
Pin No.
ADC Power Supplies
4, 7, 26, 27, 30, 31, 32
10, 17
9, 18
13
14
24
ADC Analog
1
2
3
25
28
29
ADC Fast Detect Output
19
Digital Inputs
5
6
11
12
Data Outputs
15
16
Mnemonic
Type
Description
AVDD
DVDD
DGND
DRGND
DRVDD
Supply
Supply
Ground
Ground
Supply
DNC
EPAD (AGND)
Ground
Analog Power Supply (1.8 V Nominal).
Digital Power Supply (1.8 V Nominal).
Ground Reference for DVDD.
Ground Reference for DRVDD.
JESD204B PHY Serial Output Driver Supply (1.8 V Nominal). Note that
the DRVDD power is referenced to the AGND plane.
Do Not Connect.
Exposed Pad. The exposed thermal pad on the bottom of the package
provides the ground reference for AVDD. This exposed pad must be
connected to AGND for proper operation.
RFCLK
CLK−
CLK+
VCM
Input
Input
Input
Output
VIN−
VIN+
Input
Input
ADC RF Clock Input.
ADC Nyquist Clock Input—Complement.
ADC Nyquist Clock Input—True.
Common-Mode Level Bias Output for Analog Inputs. Decouple this
pin to ground using a 0.1 µF capacitor.
Differential Analog Input (−).
Differential Analog Input (+).
FD
Output
Fast Detect Indicator (CMOS Levels).
SYSREF+
SYSREF−
SYNCINB+
SYNCINB−
Input
Input
Input
Input
JESD204B LVDS SYSREF Input—True.
JESD204B LVDS SYSREF Input—Complement.
JESD204B LVDS Sync Input—True/JESD204B CMOS Sync Input.
JESD204B LVDS Sync Input—Complement.
SERDOUT0−
SERDOUT0+
Output
Output
CML Output Data—Complement.
CML Output Data—True.
Rev. D | Page 11 of 44
AD9683
Pin No.
Device Under Test (DUT) Controls
8
20
21
22
23
Data Sheet
Mnemonic
Type
Description
RST
SDIO
SCLK
CS
PDWN
Input
Input/output
Input
Input
Input
Digital Reset (Active Low).
SPI Serial Data Input/Output.
SPI Serial Clock.
SPI Chip Select (Active Low). This pin needs an external pull-up.
Power-Down Input (Active High). The operation of this pin depends
on SPI mode and can be configured as power-down or standby (see
Table 17).
Rev. D | Page 12 of 44
Data Sheet
AD9683
TYPICAL PERFORMANCE CHARACTERISTICS
AVDD = 1.8 V, DRVDD = 1.8 V, DVDD = 1.8 V, maximum sample rate for speed grade, VIN = −1.0 dBFS, 1.75 V p-p differential input,
DCS enabled, 16k sample, TA = 25°C, default SPI, unless otherwise noted.
0
0
170MSPS
90.1MHz AT –1.0dBFS
SNR = 70.7dB (71.7dBFS)
SFDR = 89dBc
–20
–20
–40
AMPLITUDE (dBFS)
–60
THIRD HARMONIC
–80
SECOND HARMONIC
–100
20
30
40
50
60
70
80
–100
–140
30
40
0
–20
–40
–40
AMPLITUDE (dBFS)
170MSPS
90.1MHz AT –1.0dBFS
SNR = 71.1dB (72.1dBFS)
–20 SFDR = 88dBc
–60
THIRD HARMONIC
SECOND HARMONIC
–100
–120
50
60
70
80
170MSPS
305.1MHz AT –1.0dBFS
SNR = 67.6dB (68.6dBFS)
SFDR = 85dBc
–60
THIRD
HARMONIC
SECOND
HARMONIC
–80
–100
10
20
30
40
50
60
70
80
–140
11410-006
0
40
50
60
70
80
SFDR (dBFS)
SNR/SFDR (dBc AND dBFS)
100
–60
SECOND
HARMONIC
30
120
–40
–80
20
Figure 9. AD9683-170 Single-Tone FFT with fIN = 305.1 MHz
170MSPS
185.1MHz AT –1.0dBFS
SNR = 69.6dB (70.6 dBFS)
SFDR = 90dBc
–20
10
FREQUENCY (MHz)
Figure 6. AD9683-170 Single-Tone FFT with fIN = 90.1 MHz, RFCLK = 680 MHz
with Divide by 4 (Address 0x09 = 0x21)
0
0
11410-009
–120
FREQUENCY (MHz)
THIRD
HARMONIC
–100
80
SNR (dBFS)
60
SFDR (dBc)
40
SNR (dBc)
20
–120
0
10
20
30
40
50
60
70
80
FREQUENCY (MHz)
Figure 7. AD9683-170 Single-Tone FFT with fIN = 185.1 MHz
0
–100
11410-007
–140
20
10
Figure 8. AD9683-170 Single-Tone FFT with fIN = 185.1 MHz,
RFCLK = 680 MHz with Divide by 4 (Address 0x09 = 0x21)
0
–80
0
FREQUENCY (MHz)
Figure 5. AD9683-170 Single-Tone FFT with fIN = 90.1 MHz
–140
SECOND
HARMONIC
11410-008
10
11410-005
0
FREQUENCY (MHz)
AMPLITUDE (dBFS)
THIRD
HARMONIC
–80
–120
–120
AMPLITUDE (dBFS)
–60
–90
–80
–70
–60
–50
–40
–30
INPUT AMPLITUDE (dBFS)
–20
–10
0
11410-010
AMPLITUDE (dBFS)
–40
–140
170MSPS
185.1MHz AT –1dBFS
SNR = 70.1dB (71.1dBFS)
SFDR = 84dBc
Figure 10. AD9683-170 Single-Tone SNR/SFDR vs. Input Amplitude (AIN)
with fIN = 185.1 MHz
Rev. D | Page 13 of 44
AD9683
Data Sheet
100
0
95
–20
SFDR/IMD3 (dBc AND dBFS)
SNR (dBFS)/SFDR (dBc)
SFDR (dBc)
90
85
80
75
SNR (dBFS)
70
SFDR (dBc)
–40
IMD3 (dBc)
–60
–80
SFDR (dBFS)
–100
65
80 115 150 185 220 255 290 325 360 395 430 465 500
FREQUENCY (MHz)
11410-011
45
–120
–90.0 –81.7 –73.4 –65.1 –56.8 –48.5 –40.2 –31.9 –23.6 –15.3 –7.0
Figure 11. AD9683-170 Single-Tone SNR/SFDR vs. Input Frequency (fIN)
INPUT AMPLITUDE (dBFS)
Figure 14. AD9683-170 Two-Tone SFDR/IMD3 vs. Input Amplitude (AIN)
with fIN1 = 184.12 MHz, fIN2 = 187.12 MHz, fS = 170 MSPS
0
100
170MSPS
89.12MHz AT –7dBFS
92.12MHz AT –7dBFS
SFDR = 90dBc (97dBFS)
–20
90
–40
SFDR (dBc)
AMPLITUDE (dBFS)
85
80
75
SNR (dBFS)
–60
–80
–100
70
–120
65
45
80 115 150 185 220 255 290 325 360 395 430 465 500
FREQUENCY (MHz)
–140
11410-012
60
10
Figure 12. AD9683-170 Single-Tone SNR/SFDR vs. Input Frequency (fIN),
RFCLK = 680 MHz with Divide by 4 (Address 0x09 = 0x21)
0
10
20
30
40
50
60
70
80
FREQUENCY (MHz)
11410-015
SNR (dBFS)/SFDR (dBc)
95
Figure 15. AD9683-170 Two-Tone FFT with fIN1 = 89.12 MHz, fIN2 = 92.12 MHz,
fS = 170 MSPS
0
0
170MSPS
184.12MHz AT –7dBFS
187.12MHz AT –7dBFS
SFDR = 87dBc (94dBFS)
–20
–20
SFDR (dBc)
–40
AMPLITUDE (dBFS)
SFDR/IMD3 (dBc AND dBFS)
11410-014
IMD3 (dBFS)
60
10
–40
IMD3 (dBc)
–60
–80
SFDR (dBFS)
–100
–60
–80
–100
–120
–78.5
–67.0
–55.5
–44.0
–32.5
INPUT AMPLITUDE (dBFS)
–21.0
–9.5
Figure 13. AD9683-170 Two-Tone SFDR/IMD3 vs. Input Amplitude (AIN)
with fIN1 = 89.12 MHz, fIN2 = 92.12 MHz, fS = 170 MSPS
Rev. D | Page 14 of 44
–140
0
10
20
30
40
50
60
70
80
FREQUENCY (MHz)
Figure 16. AD9683-170 Two-Tone FFT with fIN1 = 184.12 MHz,
fIN2 = 187.12 MHz, fS = 170 MSPS
11410-016
–120
–90.0
11410-013
IMD3 (dBFS)
Data Sheet
AD9683
100
0
SFDR (dBc)
95
–40
AMPLITUDE (dBFS)
90
85
80
–60
THIRD HARMONIC
–80
–100
75
–120
SNR (dBFS)
50
60
70
80
90 100 110 120 130 140 150 160 170
SAMPLE RATE (MSPS)
–140
11410-017
70
40
SECOND HARMONIC
0
25
50
75
100
125
FREQUENCY (MHz)
11410-020
SNR (dBFS)/SFDR (dBc)
250MSPS
90.1MHz AT –1dBFS
SNR = 71dB (72dBFS)
SFDR = 89dBc
–20
Figure 20. AD9683-250 Single-Tone FFT with fIN = 90.1 MHz, RFCLK = 1.0 GHz
with Divide by 4 (Address 0x09 = 0x21)
Figure 17. AD9683-170 Single-Tone SNR/SFDR vs. Sample Rate (fS)
with fIN = 90.1 MHz
0
700000
250MSPS
185.1MHz AT –1dBFS
SNR = 69.5dB (70.5dBFS)
–20 SFDR = 88dBc
2,097,152 TOTAL HITS
1.375 LSB rms
598772
600000
521038
–40
400000
AMPLITUDE (dBFS)
NUMBER OF HITS
500000
384443
300000
278480
200000
–60
–80
THIRD HARMONIC
SECOND HARMONIC
–100
138113
100153
100000
–120
41248
638
N–5
24088
7601
2363
N–3
N–1
N+1
N+3
182
N+5
–140
OUTPUT CODE
0
100
125
0
250MSPS
185.1MHz AT –1dBFS
SNR = 70dB (71dBFS)
–20 SFDR = 85dBc
–40
AMPLITUDE (dBFS)
–40
–60
THIRD HARMONIC
–80
SECOND HARMONIC
–100
–60
THIRD HARMONIC
–80
SECOND HARMONIC
–100
–120
–140
0
25
50
75
100
125
FREQUENCY (MHz)
–140
0
25
50
75
100
125
FREQUENCY (MHz)
Figure 22. AD9683-250 Single-Tone FFT with fIN = 185.1 MHz,
RFCLK = 1.0 GHz with Divide by 4 (Address 0x09 = 0x21)
Figure 19. AD9683-250 Single-Tone FFT with fIN = 90.1 MHz
Rev. D | Page 15 of 44
11410-022
–120
11410-019
AMPLITUDE (dBFS)
75
Figure 21. AD9683-250 Single-Tone FFT with fIN = 185.1 MHz
250MSPS
90.1MHz AT –1dBFS
SNR = 71dB (72dBFS)
SFDR = 89dBc
–20
50
FREQUENCY (MHz)
Figure 18. AD9683-170 Grounded Input Histogram
0
25
11410-021
N–7
28
11410-018
0
1
AD9683
Data Sheet
100
0
250MSPS
305.1MHz AT –1dBFS
SNR = 67.5dB (68.5dBFS)
SFDR = 85dBc
95
SFDR (dBc)
SNR (dBFS)/SFDR (dBc)
–20
–60
SECOND HARMONIC
THIRD HARMONIC
–80
–100
–120
85
80
75
SNR (dBFS)
70
65
0
25
50
75
100
125
FREQUENCY (MHz)
60
10
11410-023
–140
Figure 23. AD9683-250 Single-Tone FFT with fIN = 305.1 MHz
45
80 115 150 185 220 255 290 325 360 395 430 465 500
FREQUENCY (MHz)
11410-026
AMPLITUDE (dBFS)
–40
90
Figure 26. AD9683-250 Single-Tone SNR/SFDR vs. Input Frequency (fIN),
RFCLK = 1.0 GHz with Divide by 4 (Address 0x09 = 0x21)
0
120
SFDR (dBFS)
–20
80
SFDR/IMD3 (dBc AND dBFS)
SNR/SFDR (dBc AND dBFS)
100
SNR (dBFS)
60
SFDR (dBc)
40
SNR (dBc)
SFDR (dBc)
–40
IMD3 (dBc)
–60
–80
SFDR (dBFS)
–100
20
–80
–60
–70
–50
–40
–30
–20
–10
0
INPUT AMPLITUDE (dBFS)
11410-024
–90
–120
–90.0
–78.5
–67.0
–55.5
–44.0
–32.5
–21.0
–9.5
INPUT AMPLITUDE (dBFS)
Figure 24. AD9683-250 Single-Tone SNR/SFDR vs. Input Amplitude (AIN)
with fIN = 185.1 MHz
11410-027
IMD3 (dBFS)
0
–100
Figure 27. AD9683-250 Two-Tone SFDR/IMD3 vs. Input Amplitude (AIN)
with fIN1 = 89.12 MHz, fIN2 = 92.12 MHz, fS = 250 MSPS
0
100
95
–20
SFDR/IMD3 (dBc AND dBFS)
SNR (dBFS)/SFDR (dBc)
SFDR (dBc)
90
85
80
75
SNR (dBFS)
70
SFDR (dBc)
–40
IMD3 (dBc)
–60
–80
SFDR (dBFS)
–100
65
80 115 150 185 220 255 290 325 360 395 430 465 500
FREQUENCY (MHz)
11410-025
45
–120
–90.0
Figure 25. AD9683-250 Single-Tone SNR/SFDR vs. Input Frequency (fIN)
–78.5
–67.0
–55.5
–44.0
–32.5
INPUT AMPLITUDE (dBFS)
–21.0
–9.5
11410-028
IMD3 (dBFS)
60
10
Figure 28. AD9683-250 Two-Tone SFDR/IMD3 vs. Input Amplitude (AIN)
with fIN1 = 184.12 MHz, fIN2 = 187.12 MHz, fS = 250 MSPS
Rev. D | Page 16 of 44
Data Sheet
AD9683
100
0
250MSPS
89.12MHz AT –7dBFS
92.12MHz AT –7dBFS
SFDR = 90dBc (97dBFS)
SFDR (dBc)
95
SNR/SFDR (dBFS/dBc)
–20
–60
–80
–100
90
85
80
75
–120
SNR (dBFS)
0
25
50
75
100
125
FREQUENCY (MHz)
70
40
11410-029
–140
80
100
120
140
160
180
200
240
220
SAMPLE RATE (MSPS)
Figure 29. AD9683-250 Two-Tone FFT with fIN1 = 89.12 MHz, fIN2 = 92.12 MHz,
fS = 250 MSPS
Figure 31. AD9683-250 Single-Tone SNR/SFDR vs. Sample Rate (fS)
with fIN = 90.1 MHz
0
700000
250MSPS
184.12MHz AT –7dBFS
187.12MHz AT –7dBFS
SFDR = 87dBc (94dBFS)
–20
60
11410-031
AMPLITUDE (dBFS)
–40
2,097,152 TOTAL HITS
1.419 LSB rms
600000
581334
520772
500000
–60
–80
300000
200000
–120
100000
0
25
50
75
100
FREQUENCY (MHz)
125
11410-030
–100
–140
Figure 30. AD9683-250 Two-Tone FFT with
fIN1 = 184.12 MHz, fIN2 = 187.12 MHz, fS = 250 MSPS
395507
400000
0
261252
181231
70369
4
N–7
161
2316
N–5
59901
15633
7965
N–3
N–1
N+1
N+3
658
N+5
OUTPUT CODE
Figure 32. AD9683-250 Grounded Input Histogram
Rev. D | Page 17 of 44
49
11410-032
NUMBER OF HITS
AMPLITUDE (dBFS)
–40
AD9683
Data Sheet
EQUIVALENT CIRCUITS
DVDD
AVDD
VIN
400Ω
PDWN,
SCLK,
CS
11410-033
11410-038
30kΩ
Figure 33. Equivalent Analog Input Circuit
Figure 38. Equivalent PDWN, SCLK, or CS Input Circuit
AVDD
DVDD
AVDD
AVDD
DVDD
0.9V
15kΩ
DVDD
0.9V
15kΩ
CLK+
17kΩ
CLK–
17kΩ
SYNCINB+
11410-039
11410-034
SYNCINB–
Figure 34. Equivalent Clock lnput Circuit
Figure 39. Equivalent SYNCINB± Input Circuit
0.5pF
AVDD
AVDD
INTERNAL
CLOCK DRIVER
RFCLK
AVDD
AVDD
0.9V
10kΩ
17kΩ
17kΩ
SYSREF–
11410-035
SYSREF+
11410-040
BIAS
CONTROL
Figure 35. Equivalent RF Clock lnput Circuit
Figure 40. Equivalent SYSREF± Input Circuit
DRVDD
DRVDD
DRVDD
DRVDD
3mA
DRVDD
3mA
RTERM
RST
VCM
SERDOUT0±
3mA
11410-036
3mA
11410-041
SERDOUT0±
28kΩ
400Ω
Figure 36. Digital CML Output Circuit
Figure 41. Equivalent RST Input Circuit
DVDD
AVDD
400Ω
400Ω
SDIO
11410-042
11410-037
31kΩ
VCM
Figure 37. Equivalent SDIO Circuit
Figure 42. Equivalent VCM Circuit
Rev. D | Page 18 of 44
Data Sheet
AD9683
THEORY OF OPERATION
The user can sample frequencies from dc to 400 MHz using
appropriate low-pass or band-pass filtering at the ADC inputs
with little loss in ADC performance. Operation above 400 MHz
analog input is permitted but occurs at the expense of increased
ADC noise and distortion.
A synchronization capability is provided to allow synchronized
timing between multiple devices.
Programming and control of the AD9683 are accomplished
using a 3-pin, SPI-compatible serial interface.
ADC ARCHITECTURE
The AD9683 architecture consists of a front-end, sample-andhold circuit, followed by a pipelined switched capacitor ADC. The
quantized outputs from each stage are combined into a final 14-bit
result in the digital correction logic. The pipelined architecture
permits the first stage to operate on a new input sample, and the
remaining stages to operate on the preceding samples. Sampling
occurs on the rising edge of the clock.
Each stage of the pipeline, excluding the last, consists of a low
resolution flash ADC connected to a switched capacitor digitalto-analog converter (DAC) and an interstage residue amplifier
(MDAC). The MDAC magnifies the difference between the
reconstructed DAC output and the flash input for the next stage
in the pipeline. One bit of redundancy is used in each stage to
facilitate digital correction of flash errors. The last stage simply
consists of a flash ADC.
The input stage contains a differential sampling circuit that can
be ac- or dc-coupled in differential or single-ended modes. The
output staging block aligns the data, corrects errors, and passes the
data to the output buffers. The output buffers are powered from a
separate supply, allowing digital output noise to be separated from
the analog core.
ANALOG INPUT CONSIDERATIONS
The analog input to the AD9683 is a differential, switched capacitor
circuit that has been designed for optimum performance while
processing a differential input signal.
The clock signal alternatively switches the input between sample
mode and hold mode (see the configuration shown in Figure 43).
When the input is switched into sample mode, the signal source
must be capable of charging the sampling capacitors and settling
within 1/2 clock cycle.
A small resistor in series with each input can help reduce the
peak transient current required from the output stage of the
driving source. A shunt capacitor can be placed across the
inputs to provide dynamic charging currents. This passive
network creates a low-pass filter at the ADC input; therefore,
the precise values are dependent on the application.
In IF undersampling applications, reduce the shunt capacitors.
In combination with the driving source impedance, the shunt
capacitors limit the input bandwidth. Refer to the AN-742
Application Note, Frequency Domain Response of SwitchedCapacitor ADCs; the AN-827 Application Note, A Resonant
Approach to Interfacing Amplifiers to Switched-Capacitor ADCs;
and the Analog Dialogue article, “Transformer-Coupled FrontEnd for Wideband A/D Converters,” for more information.
BIAS
S
S
CFB
CS
VIN+
CPAR1
CPAR2
S
S
H
CS
VIN–
CPAR1
CPAR2
S
CFB
S
BIAS
11410-043
The AD9683 has one analog input channel and one JESD204B
output lane. The signal passes through several stages before
appearing at the output port.
Figure 43. Switched Capacitor Input
For best dynamic performance, match the source impedances
driving VIN+ and VIN− and differentially balance the inputs.
Input Common Mode
The analog inputs of the AD9683 are not internally dc biased.
In ac-coupled applications, the user must provide this bias
externally. Configuring the input so that VCM = 0.5 × AVDD (or
0.9 V) is recommended for optimum performance. An on-board
common-mode voltage reference is included in the design and is
available from the VCM pin. Using the VCM output to set the
input common mode is recommended. Optimum performance
is achieved when the common-mode voltage of the analog input
is set by the VCM pin voltage (typically 0.5 × AVDD). Decouple
the VCM pin to ground by using a 0.1 µF capacitor, as described
in the Applications Information section. Place this decoupling
capacitor close to the pin to minimize the series resistance and
inductance between the part and this capacitor.
Differential Input Configurations
Optimum performance is achieved while driving the AD9683 in a
differential input configuration. For baseband applications, the
AD8138, ADA4937-1, ADA4938-1, and ADA4930-1 differential
drivers provide excellent performance and a flexible interface to
the ADC.
Rev. D | Page 19 of 44
AD9683
Data Sheet
The output common-mode voltage of the ADA4930-1 is easily
set with the VCM pin of the AD9683 (see Figure 44), and the
driver can be configured in a Sallen-Key filter topology to
provide band limiting of the input signal.
In the double balun and transformer configurations, the value
of the input capacitors and resistors is dependent on the input
frequency and source impedance. Based on these parameters,
the value of the input resistors and capacitors may need to be
adjusted or some components may need to be removed. Table 9
displays recommended values to set the RC network for different
input frequency ranges. However, these values are dependent on
the input signal and bandwidth. Use these values only as a starting
guide. Note that the values given in Table 9 are for the R1, R2, C1,
C2, and R3 components shown in Figure 45 and Figure 46.
15pF
200Ω
15Ω
33Ω
VIN–
AVDD
5pF
ADC
ADA4930-1
0.1µF
33Ω
15Ω
VCM
VIN+
120Ω
Table 9. Example RC Network
15pF
33Ω
11410-044
200Ω
0.1µF
Figure 44. Differential Input Configuration Using the ADA4930-1
For baseband applications where SNR is a key parameter,
differential transformer coupling is the recommended input
configuration. An example is shown in Figure 45. To bias the
analog input, the VCM voltage can be connected to the center
tap of the secondary winding of the transformer.
R2
VIN+
R1
2V p-p
49.9Ω
R1
Series
(Ω)
33
15
15
1000pF
C1
VCM
VIN–
165Ω
VPOS
0.1µF
1µH
11410-045
33Ω
R3
C2
Consider the signal characteristics when selecting a transformer.
Most RF transformers saturate at frequencies below a few
megahertz. Excessive signal power can also cause core saturation,
which leads to distortion.
R2
2V p-p
P
ADC
0.1µF
R1
R2
R3
VIN–
VCM
33Ω
C2
0.1µF
11410-046
33Ω
165Ω
1nF
20kΩ║2.5pF
68nH
A stable and accurate voltage reference is built into the AD9683.
The full-scale input range can be adjusted by varying the reference
voltage via the SPI. The input span of the ADC tracks the reference
voltage changes linearly.
VIN+
C1
0.1µF
301Ω
VCM
VOLTAGE REFERENCE
33Ω
S
1nF
ADC
3.9pF
180nH 220nH
C2
R3
R1
0.1µF
5.1pF
15pF
Figure 47. Differential Input Configuration Using the AD8375
At input frequencies in the second Nyquist zone and above, the
noise performance of most amplifiers is not adequate to achieve
the true SNR performance of the AD9683. For applications where
SNR is a key parameter, differential double balun coupling is
the recommended input configuration (see Figure 46). In this
configuration, the input is ac-coupled and the VCM voltage is
provided to each input through a 33 Ω resistor. These resistors
compensate for losses in the input baluns to provide a 50 Ω
impedance to the driver.
S
R3
Shunt
(Ω)
24.9
24.9
24.9
1000pF
NOTES
1. ALL INDUCTORS ARE COILCRAFT® 0603CS COMPONENTS WITH THE
EXCEPTION OF THE 1µH CHOKE INDUCTORS (COILCRAFT 0603LS).
2. FILTER VALUES SHOWN ARE FOR A 20MHz BANDWIDTH FILTER
CENTERED AT 140MHz.
Figure 45. Differential Transformer-Coupled Configuration
PA
C2
Shunt
(pF)
15
8.2
≤3.9
180nH 220nH
1µH
R2
AD8375
0.1µF
R2
Series
(Ω)
0
0
0
ADC
R1
0.1µF
C1
Differential
(pF)
8.2
8.2
≤3.9
An alternative to using a transformer-coupled input at frequencies
in the second Nyquist zone is to use an amplifier with variable
gain. The AD8375 digital variable gain amplifier (DVGA)
provides good performance for driving the AD9683. Figure 47
shows an example of the AD8375 driving the AD9683 through
a band-pass antialiasing filter.
C2
R3
Frequency
Range
(MHz)
0 to 100
100 to 400
>400
11410-047
90Ω
76.8Ω
VIN
Figure 46. Differential Double Balun Input Configuration
Rev. D | Page 20 of 44
Data Sheet
AD9683
CLOCK INPUT CONSIDERATIONS
Mini-Circuits®
ADT1-1WT, 1:1Z
390pF
XFMR
390pF
CLOCK
INPUT
ADC
CLK+
100Ω
50Ω
390pF
CLK–
11410-049
The AD9683 has two options for deriving the input sampling clock:
a differential Nyquist sampling clock input or an RF clock input
(which is internally divided by 2 or 4). The clock input is selected in
Address 0x09 and by default is configured for the Nyquist clock
input. For optimum performance, clock the AD9683 Nyquist
sample clock input, CLK+ and CLK−, with a differential signal.
The signal is typically ac-coupled into the CLK+ and CLK− pins
via a transformer or via capacitors. These pins are biased internally
(see Figure 48) and require no external bias. If the clock inputs
are floated, CLK− is pulled slightly lower than CLK+ to prevent
spurious clocking.
SCHOTTKY
DIODES:
HSMS2822
Figure 49. Transformer-Coupled Differential Clock (Up to 200 MHz)
25Ω
CLOCK
INPUT
ADC
390pF
390pF
CLK+
Nyquist Clock Input Options
390pF
The Nyquist clock input pins, CLK+ and CLK−, are internally
biased to 0.9 V and have a typical input impedance of 4 pF in
parallel with 10 kΩ (see Figure 48). The input clock is typically
ac-coupled to CLK+ and CLK−. Figure 49 through Figure 52
present some typical clock drive circuits for reference.
1nF
CLK–
11410-050
The AD9683 Nyquist clock input supports a differential clock
between 40 MHz and 625 MHz. The clock input structure supports
differential input voltages from 0.3 V to 3.6 V and is therefore
compatible with various logic family inputs such as CMOS,
LVDS, and LVPECL. A sine wave input is also accepted, but
higher slew rates typically provide optimal performance. Clock
source jitter is a critical parameter that can affect performance, as
described in the Jitter Considerations section. If the inputs are
floated, pull the CLK− pin low to prevent spurious clocking.
SCHOTTKY
DIODES:
HSMS2822
25Ω
Figure 50. Balun-Coupled Differential Clock (Up to 625 MHz)
In some cases, it is desirable to buffer or generate multiple
clocks from a single source. In those cases, Analog Devices, Inc.,
offers clock drivers with excellent jitter performance. Figure 51
shows a typical PECL driver circuit that uses PECL drivers such
as the AD9510, AD9511, AD9512, AD9513, AD9514, AD9515,
AD9516-0 through AD9516-5 device family, AD9517-0 through
AD9517-4 device family, AD9518-0 through AD9518-4 device
family, AD9520-0 through AD9520-5 device family, AD9522-0
through AD9522-5 device family, AD9523, AD9524, and
ADCLK905/ADCLK907/ADCLK925.
AVDD
0.1µF
CLK+
AD95xx
CLK–
0.1µF
11410-048
4pF
100Ω
0.1µF
CLK–
50kΩ
240Ω
50kΩ
11410-051
CLOCK
INPUT
PECL DRIVER
240Ω
Figure 51. Differential PECL Sample Clock (Up to 625 MHz)
Figure 48. Equivalent Nyquist Clock Input Circuit
For applications where a single-ended low jitter clock between
40 MHz and 200 MHz is available, an RF transformer is
recommended. Figure 49 shows an example using an RF
transformer in the clock network. At frequencies above 200 MHz,
an RF balun is recommended, as seen in Figure 50. The back-toback Schottky diodes across the transformer secondary limit
clock excursions into the AD9683 to approximately 0.8 V p-p
differential. This limit helps prevent the large voltage swings of
the clock from feeding through to other portions of the AD9683,
yet preserves the fast rise and fall times of the clock, which are
critical to low jitter performance.
Analog Devices also offers LVDS clock drivers with excellent jitter
performance. A typical circuit is shown in Figure 52. It uses
LVDS drivers such as the AD9510, AD9511, AD9512, AD9513,
AD9514, AD9515, AD9516-0 through AD9516-5 device family,
AD9517-0 through AD9517-4 device family, AD9518-0 through
AD9518-4 device family, AD9520-0 through AD9520-5 device
family, AD9522-0 through AD9522-5 device family, AD9523,
and AD9524.
0.1µF
0.1µF
CLOCK
INPUT
ADC
CLK+
AD95xx
0.1µF
CLOCK
INPUT
LVDS DRIVER
100Ω
0.1µF
CLK–
50kΩ
50kΩ
Figure 52. Differential LVDS Sample Clock (Up to 625 MHz)
Rev. D | Page 21 of 44
11410-052
CLK+
4pF
ADC
0.1µF
CLOCK
INPUT
0.9V
AD9683
Data Sheet
RF Clock Input Options
The AD9683 RF clock input supports a single-ended clock
between 500 MHz to 1.5 GHz. The equivalent RF clock input
circuit is shown in Figure 53. The input is self biased to 0.9 V and is
typically ac-coupled. The input has a typical input impedance of
10 kΩ in parallel with 0.5 pF at the RFCLK pin.
divide ratios can be selected using Address 0x09 and Address 0x0B.
Address 0x09 is used to set the RF clock input, and Address 0x0B
can be used to set the divide ratio of the 1 to 8 divider for both
the RF clock input and the Nyquist clock input. For divide ratios
other than 1, the duty cycle stabilizer (DCS) is automatically
enabled.
0.5pF
RFCLK
NYQUIST
CLOCK
10kΩ
Figure 55. Clock Divider Circuit
11410-053
BIAS
CONTROL
Figure 53. Equivalent RF Clock Input Circuit
It is recommended that the RF clock input of the AD9683 be
driven with a PECL or sine wave signal with a minimum signal
amplitude of 600 mV p-p. Regardless of the type of signal being
used, clock source jitter is of the most concern, as described in the
Jitter Considerations section. Figure 54 shows the preferred method
of clocking when using the RF clock input on the AD9683. It is
recommended that a 50 Ω transmission line be used to route
the clock signal to the RF clock input of the AD9683 due to the
high frequency nature of the signal; terminate the transmission
line close to the RF clock input.
0.1µF
RFCLK
50Ω
11410-054
50Ω Tx LINE
The AD9683 clock divider can be synchronized using the external
SYSREF input. Bit 1 and Bit 2 of Address 0x3A allow the clock
divider to be resynchronized on every SYSREF signal or only on
the first signal after the register is written. A valid SYSREF causes
the clock divider to reset to its initial state. This synchronization
feature allows multiple parts to have their clock dividers aligned to
guarantee simultaneous input sampling.
Clock Duty Cycle
Typical high speed ADCs use both clock edges to generate a
variety of internal timing signals and, as a result, may be sensitive to
clock duty cycle. Commonly, a ±5% tolerance is required on the
clock duty cycle to maintain dynamic performance characteristics.
The AD9683 contains a DCS that retimes the nonsampling (falling)
edge, providing an internal clock signal with a nominal 50% duty
cycle. This allows the user to provide a wide range of clock input
duty cycles without affecting the performance of the AD9683.
ADC
RF CLOCK
INPUT
11410-055
÷1 TO ÷8
DIVIDER
INTERNAL
CLOCK DRIVER
RFCLK
÷2 OR ÷4
Figure 54. Typical RF Clock Input Circuit
Figure 56 shows the RF clock input of the AD9683 being driven
from the LVPECL outputs of the AD9515. The differential LVPECL
output signal from the AD9515 is converted to a single-ended
signal using an RF balun or RF transformer. The RF balun
configuration is recommended for clock frequencies associated
with the RF clock input.
Input Clock Divider
The AD9683 contains an input clock divider with the ability to
divide the Nyquist input clock by integer values between 1 and 8.
The RF clock input uses an on-chip predivider to divide the clock
input by four before it reaches the 1 to 8 divider. This allows
higher input frequencies to be achieved on the RF clock input. The
Jitter on the rising edge of the input clock is still of paramount
concern and is not reduced by the DCS. The duty cycle control
loop does not function for clock rates of less than 40 MHz
nominally. The loop has a time constant associated with it that
must be considered when the clock rate can change dynamically.
A wait time of 1.5 µs to 5 µs is required after a dynamic clock
frequency increase or decrease before the DCS loop is relocked
to the input signal. During the time that the loop is not locked,
the DCS loop is bypassed, and the internal device timing is
dependent on the duty cycle of the input clock signal. In such
applications, it may be appropriate to disable the DCS. In all
other applications, enabling the DCS circuit is recommended
to maximize ac performance.
Rev. D | Page 22 of 44
Data Sheet
AD9683
VDD
127Ω
0.1µF
ADC
127Ω
50Ω Tx LINE
0.1µF
0.1µF
RFCLK
CLOCK INPUT
AD9515
0.1µF
50Ω
LVPECL
DRIVER
0.1µF
CLOCK INPUT
82.5Ω
11410-056
82.5Ω
Figure 56. Differential PECL RF Clock Input Circuit
POWER DISSIPATION AND STANDBY MODE
SNRHF = −10 log[(2π × fIN × tJRMS)2 + 10 ( − SNRLF /10) ]
In the equation, the rms aperture jitter represents the root-meansquare of all jitter sources, which include the clock input, the
analog input signal, and the ADC aperture jitter specification. IF
undersampling applications are particularly sensitive to jitter,
as shown in Figure 57.
80
75
0.5
0.25
0.4
0.20
TOTAL POWER
0.3
IAVDD
0.2
0.15
0.10
IDVDD
0.1
0.05
65
0
40
60
55
70
0
85 100 115 130 145 160 175 190 205 220 235 250
ENCODE FREQUENCY (MSPS)
Figure 58. AD9683-250 Power vs. Encode Rate
50
1
10
100
1000
INPUT FREQUENCY (MHz)
11410-057
0.05ps
0.2ps
0.5ps
1ps
1.5ps
MEASURED
55
11410-058
SNR (dBFS)
70
As shown in Figure 58, the power dissipated by the AD9683 is
proportional to its sample rate. The data in Figure 58 was taken
using the same operating conditions as those used for the Typical
Performance Characteristics section. IDVDD in Figure 58 is a
summation of IDVDD and IDRVDD.
SUPPLY CURRENT (A)
High speed, high resolution ADCs are sensitive to the quality of
the clock input. The degradation in SNR at a given input frequency
(fIN) due to jitter (tJ) can be calculated by
TOTAL POWER (W)
Jitter Considerations
Figure 57. AD9683-250 SNR vs. Input Frequency and Jitter
Treat the clock input as an analog signal in cases where aperture
jitter may affect the dynamic range of the AD9683. Separate the
power supplies for the clock drivers from the ADC output driver
supplies to avoid modulating the clock signal with digital noise.
Low jitter, crystal controlled oscillators make the best clock sources.
If the clock is generated from another type of source (by gating,
dividing, or another method), retime it using the original clock at
the last step.
Refer to the AN-501 Application Note, Aperture Uncertainty and
ADC System Performance, and the AN-756 Application Note,
Sampled Systems and the Effects of Clock Phase Noise and Jitter, for
more information about jitter performance as it relates to ADCs.
By asserting PDWN (either through the SPI port or by asserting
the PDWN pin high), the AD9683 is placed in power-down mode.
In this state, the ADC typically dissipates about 9 mW. Asserting the
PDWN pin low returns the AD9683 to its normal operating mode.
Low power dissipation in power-down mode is achieved by
shutting down the reference, reference buffer, biasing networks,
and clock. Internal capacitors are discharged when entering powerdown mode and then must be recharged when returning to normal
operation. As a result, wake-up time is related to the time spent
in power-down mode, and shorter power-down cycles result in
proportionally shorter wake-up times.
When using the SPI port interface, the user can place the ADC
in power-down mode or standby mode. Standby mode allows
the user to keep the internal reference circuitry powered when
faster wake-up times are required. See the Memory Map Register
Descriptions section and the AN-877 Application Note, Interfacing
to High Speed ADCs via SPI, for additional details.
Rev. D | Page 23 of 44
AD9683
Data Sheet
DIGITAL OUTPUTS
JESD204B TRANSMIT TOP LEVEL DESCRIPTION
The AD9683 digital output uses the JEDEC Standard No.
JESD204B, Serial Interface for Data Converters. JESD204B is a
protocol to link the AD9683 to a digital processing device over a
serial interface of up to 5 Gbps link speeds. The benefits of the
JESD204B interface include a reduction in required board area
for data interface routing and the enabling of smaller packages
for converter and logic devices. The AD9683 supports single
lane interfaces.
JESD204B Overview
The JESD204B data transmit block assembles the parallel data from
the ADC into frames and uses 8B/10B encoding as well as optional
scrambling to form serial output data. Lane synchronization is
supported using special characters during the initial establishment
of the link, and additional synchronization is embedded in the
data stream thereafter. A matching external receiver is required
to lock onto the serial data stream and recover the data and clock.
For additional details on the JESD204B interface, refer to the
JESD204B standard.
The AD9683 JESD204B transmit block maps the output of the
ADC over a single link. The link is configured to use a single
pair of serial differential outputs that is called a lane. The
JESD204B specification refers to a number of parameters to
define the link, and these parameters must match between the
JESD204B transmitter (AD9683 output) and receiver.
The JESD204B link is described according to the following
parameters:
•
•
•
•
•
•
•
•
•
•
•
•
•
•
Figure 59 shows a simplified block diagram of the AD9683
JESD204B link. The AD9683 uses one converter and one lane.
The converter data is output to SERDOUT0+/SERDOUT0−.
In the AD9683, the 14-bit converter word is divided into two octets
(eight bits of data) by default. The first octet contains Bit 13 (MSB)
through Bit 6. The second octet contains Bit 5 through Bit 0 (LSB)
and two added tail bits. The tail bits can be configured as zeros, a
pseudorandom number sequence, or control bits indicating
overrange, underrange, or valid data conditions.
The two resulting octets can be scrambled. Scrambling is
optional; however, it is available to avoid spectral peaks when
transmitting similar digital data patterns. The scrambler uses a
self synchronizing, polynomial-based algorithm defined by the
1 + x14 + x15 equation. The descrambler in the receiver should be
a self-synchronizing version of the scrambler polynomial.
The two octets are then encoded with an 8B/10B encoder. The
8B/10B encoder works by taking eight bits of data (an octet) and
encoding them into a 10-bit symbol. Figure 60 shows how the
14-bit data is taken from the ADC, the tail bits are added, the two
octets are scrambled, and how the octets are encoded into two
10-bit symbols. Figure 60 illustrates the default data format.
At the data link layer, in addition to the 8B/10B encoding, the
character replacement is used to allow the receiver to monitor
frame alignment. The character replacement process occurs on the
frame and multiframe boundaries, and implementation depends
on which boundary is occurring, and if scrambling is enabled.
If scrambling is disabled, the following applies:
S = samples transmitted per single converter per frame
cycle (AD9683 value = 1)
M = number of converters per converter device
(AD9683 value = 1)
L = number of lanes per converter device
(AD9683 value = 1)
N = converter resolution (AD9683 value = 14)
N’ = total number of bits per sample (AD9683 value = 16)
CF = number of control words per frame clock cycle per
converter device (AD9683 value = 0)
CS = number of control bits/conversion sample
(configurable on the AD9683 up to two bits)
K = number of frames per multiframe (configurable on
the AD9683)
HD = high density mode (AD9683 value = 0)
F = octets per frame (AD9683 value = 2)
C = control bit (overrange, overflow, underflow; available
on the AD9683)
T = tail bit (available on the AD9683)
SCR = scrambler enable/disable (configurable on the AD9683)
FCHK = checksum for the JESD204B parameters
(automatically calculated and stored in register map)
•
•
If the last scrambled octet of the last frame of the multiframe
equals the last octet of the previous frame, the transmitter
replaces the last octet with the control character /A/ =
/K28.3/.
On other frames within the multiframe, if the last octet in
the frame equals the last octet of the previous frame, the
transmitter replaces the last octet with the control
character /F/ = /K28.7/.
If scrambling is enabled, the following applies:
•
•
If the last octet of the last frame of the multiframe equals
0x7C, the transmitter replaces the last octet with the
control character /A/ = /K28.3/.
On other frames within the multiframe, if the last octet
equals 0xFC, the transmitter replaces the last octet with the
control character /F/ = /K28.7/.
Refer to JEDEC Standard No. 204B, July 2011 for additional
information about the JESD204B interface. Section 5.1 covers
the transport layer and data format details and Section 5.2
covers scrambling and descrambling.
Rev. D | Page 24 of 44
Data Sheet
AD9683
JESD204B Synchronization Details
•
The AD9683 is a JESD204B Subclass 1 device that establishes
synchronization of the link through two control signals, SYSREF
and SYNC, and typically a common device clock. SYSREF and
SYNC are common to all converter devices for alignment purposes
at the system level.
The synchronization process is accomplished over three phases:
code group synchronization (CGS), initial lane alignment sequence
(ILAS), and data transmission. If scrambling is enabled, the bits are
not actually scrambled until the data transmission phase, and
the CGS phase and ILAS phase do not use scrambling.
CGS Phase
In the CGS phase, the JESD204B transmit block transmits
/K28.5/ characters. The receiver (external logic device) must
locate /K28.5/ characters in its input data stream using clock
and data recovery (CDR) techniques.
When a certain number of consecutive /K28.5/ characters are
detected on the link lane, the receiver initiates a SYSREF edge
so that the AD9683 transmit data establishes a local multiframe
clock (LMFC) internally.
The SYSREF edge also resets any sampling edges within the ADC
to align sampling instances to the LMFC. This is important to
maintain synchronization across multiple devices.
The receiver or logic device deasserts the SYNC signal
(SYNCINB±), and the transmitter block begins the ILAS phase.
ILAS Phase
In the ILAS phase, the transmitter sends out a known pattern,
and the receiver aligns the lanes in the link and verifies the
parameters of the link.
If scrambling is enabled and the last octet of the multiframe is
equal to 0x7C, or the last octet of a frame is equal to 0xFC.
Table 10. Fourteen Configuration Octets of the ILAS Phase
No.
0
1
2
3
4
5
6
7
8
9
10
11
12
13
Bit 7
(MSB)
Bit 6
Bit 5
Bit 4 Bit 3
DID[7:0]
Bit 2
Bit 1
Bit 0
(LSB)
BID[3:0]
LID[4:0]
L[4:0]
SCR
F[7:0]
K[4:0]
M[7:0]
CS[1:0]
SUBCLASS[2:0]
JESDV[2:0]
N[4:0]
N’[4:0]
S[4:0]
CF[4:0]
Reserved, don’t care
Reserved, don’t care
FCHK[7:0]
Link Setup Parameters
The following sections demonstrate how to configure the AD9683
JESD204B interface. The steps to configure the output include
the following:
1.
2.
3.
4.
5.
6.
Disable the lane before changing the configuration.
Select a quick configuration option.
Configure detailed options.
Check FCHK, the checksum of the JESD204B interface
parameters.
Set additional digital output configuration options.
Re-enable the lane.
Disable Lane Before Changing Configuration
The ILAS phase begins after SYNC has been deasserted (goes
high). The transmit block begins to transmit four multiframes.
Dummy samples are inserted between the required characters
so that full multiframes are transmitted. The four multiframes
include the following:
Before modifying the JESD204B link parameters, disable the link
and hold it in reset. This is accomplished by writing Logic 1 to
Address 0x5F, Bit 0.
•
•
•
•
•
Multiframe 1 begins with an /R/ character [K28.0] and
ends with an /A/ character [K28.3].
Multiframe 2 begins with an /R/ character followed by a /Q/
[K28.4] character, followed by link configuration parameters
over 14 configuration octets (see Table 10), and ends with
an /A/ character.
Multiframe 3 is the same as Multiframe 1.
Multiframe 4 is the same as Multiframe 1.
Configure Detailed Options
Configure the tail bits and control bits as follows.
•
With N’ = 16 and N = 14, there are two bits available per
sample for transmitting additional information over the
JESD204B link. The options are tail bits or control bits. By
default, tail bits of 0b00 value are used.
Tail bits are dummy bits sent over the link to complete the
two octets and do not convey any information about the input
signal. Tail bits can be fixed zeros (default) or pseudorandom numbers (Address 0x5F, Bit 6).
One or two control bits can be used instead of the tail bits
through Address 0x72, Bits[7:6]. The tail bits can be set
using Address 0x14, Bits[7:5], and the tail bits can be
enabled using Address 0x5F, Bit 6.
Data Transmission Phase
•
In the data transmission phase, frame alignment is monitored
with control characters. Character replacement is used at the
end of frames. Character replacement in the transmitter occurs
in the following instances:
Set lane identification values.
•
•
If scrambling is disabled and the last octet of the frame or
multiframe equals the octet value of the previous frame.
Rev. D | Page 25 of 44
JESD204B allows parameters to identify the device and lane.
These parameters are transmitted during the ILAS phase, and
they are accessible in the internal registers.
AD9683
•
Data Sheet
There are three identification values: device identification
(DID), bank identification (BID), and lane identification
(LID). DID and BID are device specific; therefore, they can
be used for link identification.
Set the number of frames per multiframe, K.
•
•
Per the JESD204B specification, a multiframe is defined as a
group of K successive frames, where K is between 1 and 32,
and it requires that the number of octets be between 17 and
1024. The K value is set to 32 by default in Address 0x70,
Bits[7:0]. Note that the K value is the register value plus 1.
The K value can be changed; however, it must comply with
a few conditions. The AD9683 uses a fixed value for octets
per frame (F) based on the JESD204B quick configuration
setting. K must also be a multiple of 4 and conform to the
following equation:
32 ≥ K ≥ Ceil (17/F)
•
The JESD204B specification also requires the number of
octets per multiframe (K × F) to be between 17 and 1024.
The F value is fixed through the quick configuration
setting to ensure that this relationship is true.
Verify read only values: lanes per link (L), octets per frame (F),
number of converters (M), and samples per converter per frame
(S). The AD9683 calculates values for some JESD204B parameters
based on other settings, particularly the quick configuration
register selection. The read only values here are available in the
register map for verification.
•
•
•
•
•
L = lanes per link is 1; read the values from Address 0x6E,
Bits[4:0]
F = octets per frame is 1, 2, or 4; read the value from
Address 0x6F, Bits[7:0]
HD = high density mode can be 0 or 1; read the value from
Address 0x75, Bit 7
M = number of converters per link is 1; read the value from
Address 0x71, Bits[7:0]
S = samples per converter per frame can be 1 or 2; read the
value from Address 0x74, Bits[4:0]
Check FCHK, Checksum of JESD204B Interface Parameters
Table 11. JESD204B Configurable Identification Values
The JESD204B parameters can be verified through the checksum
value (FCHK) of the JESD204B interface parameters. Each lane has
a FCHK value associated with it. The FCHK value is transmitted
during the ILAS second multiframe and can be read from the
internal registers.
ID Value
LID
DID
BID
The checksum value is the modulo 256 sum of the parameters
listed in the No. column of Table 12. The checksum is calculated
by adding the parameter fields before they are packed into the
octets shown in Table 12.
Register, Bits
0x67, [4:0]
0x64, [7:0]
0x65, [3:0]
Value Range
0 to 31
0 to 255
0 to 15
Scramble, SCR.
•
Scrambling can be enabled or disabled by setting Address 0x6E,
Bit 7. By default, scrambling is enabled. Per the JESD204B
protocol, scrambling is functional only after the lane
synchronization has completed.
Select lane synchronization options.
Most of the synchronization features of the JESD204B interface
are enabled, by default, for typical applications. In some cases,
these features can be disabled or modified as follows:
•
ILAS enabling is controlled in Address 0x5F, Bits[3:2] and,
by default, is enabled. Optionally, to support some unique
instances of the interfaces (such as NMCDA-SL), the
JESD204B interface can be programmed to either disable the
ILAS sequence or continually repeat the ILAS sequence.
The AD9683 has fixed values of some of the JESD204B interface
parameters, and they are as follows:
•
•
•
N = 14, number of bits per converter is 14 in Address 0x72,
Bits[3:0]
N’ = 16, number of bits per sample is 16 in Address 0x73,
Bits[3:0]
CF = 0, number of control words per frame clock cycle per
converter is 0 in Address 0x75, Bits[4:0]
The FCHK value for the lane configuration for data coming out
of the Lane 0 can be read from Address 0x79.
Table 12. JESD204B Configuration Table Used in ILAS and
CHKSUM Calculation
No.
0
1
2
3
4
5
6
7
8
9
10
Bit 7
(MSB)
Bit 6
Bit 5
Bit 4 Bit 3
DID[7:0]
Bit 2
Bit 1
Bit 0
(LSB)
BID[3:0]
LID[4:0]
L[4:0]
SCR
F[7:0]
K[4:0]
M[7:0]
CS[1:0]
SUBCLASS[2:0]
JESDV[2:0]
N[4:0]
N’[4:0]
S[4:0]
CF[4:0]
Set Additional Digital Output Configuration Options
Other data format controls include the following:
•
•
•
Rev. D | Page 26 of 44
Invert polarity of serial output data, Address 0x60, Bit 1
ADC data format select (offset binary or twos complement),
Address 0x14, Bits[1:0]
Options for interpreting signal on SYSREF± and SYNCINB±,
Address 0x3A, Bits[4:0]
Data Sheet
AD9683
Reenable Lane After Configuration
After modifying the JESD204B link parameters, enable the link so
that the synchronization process can begin. This is accomplished
by writing Logic 0 to Address 0x5F, Bit 0.
AD9683 ADC
CONVERTER
INPUT
CONVERTER
SAMPLE
CONVERTER
JESD204B LANE CONTROL
(M = 1, L = 1)
11410-059
SERDOUT0±
SYSREF±
SYNCINB±
Figure 59. Transmit Link Simplified Block Diagram
A PATH
(LSB)
8B/10B
ENCODER/
CHARACTER
REPLACEMENT
A6
A7
A8
A9
A10
A11
A12
A13
C0
C1
A0
A1
A2
A3
A4
A5
S8
S9
S10
S11
S12
S13
S14
S15
S0
S1
S2
S3
S4
S5
S6
S7
SERIALIZER
E10
E11
E12
E13
E14
E15
E16
E17
E18
E19
E0
E1
E2
E3
E4
E5
E6
E7
E8
E9
SERDOUT±
E19 . . . E9 E8 E7 E6 E5 E4 E3 E2 E1 E0
~SYNC
t
SYSREF
11410-160
ADC
VINA–
JESD204B
TEST PATTERN
10-BIT
OPTIONAL
SCRAMBLER
1 + x14 + x15
OCTET1
VINA+
A13
A12
A11
A10
A9
A8
A7
A6
A5
A4
A3
A2
A1
A0
JESD204B
TEST PATTERN
8-BIT
OCTET0
(MSB)
ADC
TEST PATTERN
16-BIT
Figure 60. Digital Processing of JESD204B Lane
Table 13. JESD204B Typical Configurations
M (No. of Converters),
Address 0x71,
Bits[7:0]
1
DATA
FROM
ADC
L (No. of Lanes),
Address 0x6E,
Bits[4:0]
1
FRAME
ASSEMBLER
(ADD TAIL BITS)
F (Octets/Frame),
Address 0x6F,
Bits[7:0], Read Only
2
OPTIONAL
SCRAMBLER
1 + x14 + x15
S (Samples/ADC/Frame),
Address 0x74, Bits[4:0],
Read Only
1
8B/10B
ENCODER
TO
RECEIVER
HD (High Density Mode),
Address 0x75, Bit 7,
Read Only
0
11410-061
JESD204B
Configure
Setting
0x11 (Default)
Figure 61. ADC Output Data Path
Table 14. JESD204B Frame Alignment Monitoring and Correction Replacement Characters
Scrambling
Off
Off
Off
On
On
On
Lane Synchronization
On
On
Off
On
On
Off
Character to be Replaced
Last octet in frame repeated from previous frame
Last octet in frame repeated from previous frame
Last octet in frame repeated from previous frame
Last octet in frame equals D28.7
Last octet in frame equals D28.3
Last octet in frame equals D28.7
Rev. D | Page 27 of 44
Last Octet in
Multiframe
No
Yes
Not applicable
No
Yes
Not applicable
Replacement Character
K28.7
K28.3
K28.7
K28.7
K28.3
K28.7
AD9683
Data Sheet
Frame alignment monitoring and correction is part of the JESD204B
specification. The 14-bit word requires two octets to transmit all
the data. The two octets (MSB and LSB), where F = 2, make up
a frame. During normal operating conditions, frame alignment
is monitored via alignment characters, which are inserted under
certain conditions at the end of a frame. Table 14 summarizes the
conditions for character insertion along with the expected characters
under the various operation modes. If lane synchronization is
enabled, the replacement character value depends on whether
the octet is at the end of a frame or at the end of a multiframe.
Based on the operating mode, the receiver can ensure that it is
still synchronized to the frame boundary by correctly receiving
the replacement characters.
The AD9683 digital outputs can interface with custom ASICs and
FPGA receivers, providing superior switching performance in
noisy environments. Single point-to-point network topologies are
recommended with a single differential 100 Ω termination resistor
placed as close to the receiver logic as possible. The common mode
of the digital output automatically biases itself to half the supply
of the AD9683 (that is, the common-mode voltage is 0.9 V for a
supply of 1.8 V) if a dc-coupled connection is used (see Figure 63).
For a receiver logic that is not within the bounds of the DRVDD
supply, use an ac-coupled connection. Simply place a 0.1 µF
capacitor on each output pin and derive a 100 Ω differential
termination close to the receiver side.
DRVDD
100Ω
DIFFERENTIAL
TRACE PAIR
SERDOUT0+
100Ω
Digital Outputs and Timing
The AD9683 has differential digital outputs that power up by
default. The driver current is derived on chip and sets the output
current at each output equal to a nominal 3 mA. Each output
presents a 100 Ω dynamic internal termination to reduce
unwanted reflections.
Place a 100 Ω differential termination resistor at each receiver
input to result in a nominal 600 mV p-p swing at the receiver
(see Figure 62). Alternatively, single-ended 50 Ω termination
can be used. When single-ended termination is used, the
termination voltage must be DRVDD/2; otherwise, ac coupling
capacitors can be used to terminate to any single-ended voltage.
VRXCM
DRVDD
SERDOUT0+
OR
RECEIVER
SERDOUT0–
VCM = Rx VCM
Figure 62. AC-Coupled Digital Output Termination Example
11410-062
0.1µF
OUTPUT SWING = 600mV p-p
OUTPUT SWING = 600mV p-p
VCM = DRVDD/2
Figure 63. DC-Coupled Digital Output Termination Example
If there is no far-end receiver termination, or if there is poor
differential trace routing, timing errors may result. To avoid
such timing errors, it is recommended that the trace length be
less than six inches, and that the differential output traces be
close together and at equal lengths.
Figure 64 shows an example of the digital output (default) data eye
and time interval error (TIE) jitter histogram and bathtub curve for
the AD9683 lane running at 5 Gbps.
Additional SPI options allow the user to further increase the output
driver voltage swing or enable preemphasis to drive longer trace
lengths (see Address 0x15 in Table 17). The power dissipation
of the DRVDD supply increases when this option is used. See the
Memory Map section for more details.
100Ω
DIFFERENTIAL
0.1µF TRACE PAIR
100Ω
RECEIVER
SERDOUT0–
11410-063
Frame and Lane Alignment Monitoring and Correction
The format of the output data is twos complement by default.
To change the output data format to offset binary, see the
Memory Map section (Address 0x14 in Table 17).
Rev. D | Page 28 of 44
Data Sheet
AD9683
HEIGHT1: EYE DIAGRAM
400
1
3
–
6000
200
–
1–2
1–4
5000
100
4000
BER
HITS
1–6
0
1–8
3000
–100
1–10
2000
–300
1000
EYE: ALL BITS OFFSET: 0
–400 ULS: 7000; 993329 TOTAL: 7000; 993329
–100
0
TIME (ps)
100
0
200
1–12
1–14
–10
0
TIME (ps)
1–16
–0.5
10
0
ULS
11410-064
–200
–200
TJ AT BER1: BATHTUB
2
–
300
VOLTAGE (mV)
PERIOD1: HISTOGRAM
7000
1
0.5
Figure 64. AD9683 Digital Outputs Data Eye, Histogram and Bathtub, External 100 Ω Terminations at 5 Gbps
HEIGHT1: EYE DIAGRAM
400
1
3
–
6000
200
–
1–2
1–4
5000
100
4000
BER
HITS
1–6
0
1–8
3000
–100
1–10
2000
–300
1000
EYE: ALL BITS OFFSET: 0.0018
–400 ULS: 8000; 673330 TOTAL: 8000; 673330
–150
–50 0 50
TIME (ps)
150
0
250
1–12
1–14
–10
0
TIME (ps)
10
1–16
–0.5
0
ULS
0.5
11410-065
–200
–250
TJ AT BER1: BATHTUB
2
–
300
VOLTAGE (mV)
PERIOD1: HISTOGRAM
7000
1
Figure 65. AD9683 Digital Outputs Data Eye, Histogram and Bathtub, External 100 Ω Terminations at 3.4 Gbps
ADC OVERRANGE AND GAIN CONTROL
ADC Overrange (OR)
In receiver applications, it is desirable to have a mechanism to
reliably determine when the converter is about to be clipped.
The standard overflow indicator provides delayed information on
the state of the analog input that is of limited value in preventing
clipping. Therefore, it is helpful to have a programmable threshold
below full scale that allows time to reduce the gain before the
clip occurs. In addition, because input signals can have significant
slew rates, latency of this function is of concern.
The ADC overrange indicator is asserted when an overrange is
detected on the input of the ADC. The overrange condition is
determined at the output of the ADC pipeline and, therefore, is
subject to a latency of 36 ADC clock cycles. An overrange at the
input is indicated by this bit 36 clock cycles after it occurs.
Using the SPI port, the user can provide a threshold above which
the FD output is active. Bit 0 of Address 0x45 enables the fast
detect feature. Address 0x47 to Address 0x4A allow the user to
set the threshold levels. As long as the signal is below the selected
threshold, the FD output remains low. In this mode, the magnitude
of the data is considered in the calculation of the condition, but
the sign of the data is not considered. The threshold detection
responds identically to positive and negative signals outside the
desired range (magnitude).
Gain Switching
The AD9683 includes circuitry that is useful in applications
either where large dynamic ranges exist or where gain ranging
amplifiers are employed. This circuitry allows digital thresholds
to be set such that an upper threshold and a lower threshold can
be programmed.
One such use is to detect when an ADC is about to reach full
scale with a particular input condition. The result is to provide
an indicator that can be used to quickly insert an attenuator that
prevents ADC overdrive.
Rev. D | Page 29 of 44
AD9683
Data Sheet
Fast Threshold Detection (FD)
comparison is subject to the ADC pipeline latency but is
accurate in terms of converter resolution. The lower threshold
magnitude is defined by
The FD indicator is asserted if the input magnitude exceeds the
value programmed in the fast detect upper threshold registers,
located in Address 0x47 and Address 0x48. The selected threshold
register is compared with the signal magnitude at the output of
the ADC. The fast upper threshold detection has a latency of
seven clock cycles. The approximate upper threshold magnitude
is defined by
Lower Threshold Magnitude (dBFS) = 20 log (Threshold
Magnitude/213)
For example, to set an upper threshold of −6 dBFS, write
0x0FFF to those registers, and to set a lower threshold of
−10 dBFS, write 0x0A1D to those registers.
Upper Threshold Magnitude (dBFS) = 20 log (Threshold
Magnitude/213)
The dwell time can be programmed from 1 to 65,535 sample
clock cycles by placing the desired value in the fast detect dwell
time registers, located in Address 0x4B and Address 0x4C.
The FD indicators are not cleared until the signal drops below
the lower threshold for the programmed dwell time. The lower
threshold is programmed in the fast detect lower threshold
registers, located at Address 0x49 and Address 0x4A. The fast
detect lower threshold register is a 16-bit register that is compared
with the signal magnitude at the output of the ADC. This
The operation of the upper threshold and lower threshold registers,
along with the dwell time registers, is shown in Figure 66.
UPPER THRESHOLD
DWELL TIME
LOWER THRESHOLD
DWELL TIME
FD
Figure 66. Threshold Settings for FD Signals
Rev. D | Page 30 of 44
TIMER COMPLETES BEFORE
SIGNAL RISES ABOVE LT
11410-066
MIDSCALE
TIMER RESET BY
RISE ABOVE
LOWER THRESHOLD
Data Sheet
AD9683
DC CORRECTION (DCC)
Because the dc offset of the ADC may be significantly larger than
the signal being measured, a dc correction circuit is included to
null the dc offset before measuring the power. The dc correction
circuit can also be switched into the main signal path; however,
this may not be appropriate if the ADC is digitizing a time-varying
signal with significant dc content, such as GSM.
DC CORRECTION BANDWIDTH
The dc correction circuit is a high-pass filter with a programmable
bandwidth (ranging between 0.29 Hz and 2.387 kHz at
245.76 MSPS). The bandwidth is controlled by writing to
the four dc correction bandwidth select bits, located at
Address 0x40, Bits[5:2]. The following equation can be used
to compute the bandwidth value for the dc correction circuit:
DC CORRECTION READBACK
The current dc correction value can be read back in Address 0x41
and Address 0x42. The dc correction value is a 16-bit value that
can span the entire input range of the ADC.
DC CORRECTION FREEZE
Setting Bit 6 of Address 0x40 freezes the dc correction at its
current state and continues to use the last updated value as the
dc correction value. Clearing this bit restarts dc correction and
adds the currently calculated value to the data.
DC CORRECTION ENABLE BITS
Setting Bit 1 of Address 0x40 enables dc correction for use in
the output data signal path.
DC_Corr_BW = 2−k−14 × fCLK/(2 × π)
where:
k is the 4-bit value programmed in Bits[5:2] of Address 0x40
(values between 0 and 13 are valid for k).
fCLK is the AD9683 ADC sample rate in hertz.
Rev. D | Page 31 of 44
AD9683
Data Sheet
SERIAL PORT INTERFACE (SPI)
The AD9683 SPI allows the user to configure the converter for
specific functions or operations through a structured register
space provided inside the ADC. The SPI gives the user added
flexibility and customization, depending on the application.
Addresses are accessed via the serial port and can be written to
or read from via the port. Memory is organized into bytes that
can be further divided into fields. These fields are documented
in the Memory Map section. For detailed operational information,
see the AN-877 Application Note, Interfacing to High Speed
ADCs via SPI.
CONFIGURATION USING THE SPI
Three pins define the SPI of this ADC: the SCLK pin, the SDIO
pin, and the CS pin (see Table 15). The SCLK (serial clock) pin is
used to synchronize the read and write data presented from/to the
ADC. The SDIO (serial data input/output) pin is a dual-purpose
pin that allows data to be sent to and read from the internal ADC
memory map registers. The CS (chip select bar) pin is an active low
control that enables or disables the read and write cycles.
Table 15. Serial Port Interface Pins
Pin
SCLK
SDIO
CS
Function
Serial clock. The serial shift clock input, which is used to
synchronize the serial interface reads and writes.
Serial data input/output. A dual-purpose pin that
typically serves as an input or an output, depending on
the instruction being sent and the relative position in the
timing frame.
Chip select bar. An active low control that gates the read
and write cycles.
The falling edge of CS, in conjunction with the rising edge of
SCLK, determines the start of the framing. An example of the
serial timing and its definitions can be found in Figure 67 and
Table 5.
Other modes involving CSare available. CS can be held low
indefinitely, which permanently enables the device; this is called
streaming. CS can stall high between bytes to allow for additional
external timing. When CS is tied high, SPI functions are placed
in a high impedance mode. This mode turns on any SPI pin
secondary functions.
During an instruction phase, a 16-bit instruction is transmitted.
Data follows the instruction phase, and its length is determined
by the W0 and the W1 bits.
All data is composed of 8-bit words. The first bit of each individual
byte of serial data indicates whether a read or write command is
issued. This allows the SDIO pin to change direction from an
input to an output.
In addition to word length, the instruction phase determines
whether the serial frame is a read or write operation, allowing
the serial port to be used both to program the chip and to read
the contents of the on-chip memory. If the instruction is a readback
operation, performing a readback causes the SDIO pin to change
direction from an input to an output at the appropriate point in
the serial frame.
Data can be sent in MSB first mode or in LSB first mode. MSB
first is the default on power-up and can be changed via the SPI
port configuration register. For more information about this and
other features, see the AN-877 Application Note, Interfacing to
High Speed ADCs via SPI.
HARDWARE INTERFACE
The pins described in Table 15 comprise the physical interface
between the user programming device and the serial port of the
AD9683. The SCLK pin and the CS pin function as inputs when
using the SPI interface. The SDIO pin is bidirectional, functioning
as an input during write phases and as an output during readback.
The SPI interface is flexible enough to be controlled by either
FPGAs or microcontrollers. One method for SPI configuration
is described in detail in the AN-812 Application Note,
Microcontroller-Based Serial Port Interface (SPI) Boot Circuit.
Do not activate the SPI port during periods when the full dynamic
performance of the converter is required. Because the SCLK signal,
the CS signal, and the SDIO signal are typically asynchronous to
the ADC clock, noise from these signals can degrade converter
performance. If the on-board SPI bus is used for other devices, it
may be necessary to provide buffers between this bus and the
AD9683 to prevent these signals from transitioning at the
converter inputs during critical sampling periods.
Rev. D | Page 32 of 44
Data Sheet
AD9683
SPI ACCESSIBLE FEATURES
Table 16 provides a brief description of the general features that are accessible via the SPI. These features are described in detail in the
AN-877 Application Note, Interfacing to High Speed ADCs via SPI. The AD9683 part-specific features are described in the Memory Map
Register Descriptions section.
Table 16. Features Accessible Using the SPI
Feature Name
Mode
Clock
Offset
Test Input/Output
Output Mode
Output Phase
Output Delay
VREF
Description
Allows the user to set either power-down mode or standby mode
Allows the user to access the DCS via the SPI
Allows the user to digitally adjust the converter offset
Allows the user to set test modes to have known data on output bits
Allows the user to set up outputs
Allows the user to set the output clock polarity
Allows the user to vary the DCO delay
Allows the user to set the reference voltage
tDS
tS
tHIGH
tCLK
tDH
tH
tLOW
CS
SDIO DON’T CARE
R/W
W1
W0
A12
A11
A10
A9
A8
A7
D5
Figure 67. Serial Port Interface Timing Diagram
Rev. D | Page 33 of 44
D4
D3
D2
D1
D0
DON’T CARE
11410-067
DON’T CARE
SCLK DON’T CARE
AD9683
Data Sheet
MEMORY MAP
READING THE MEMORY MAP REGISTER TABLE
Default Values
Each row in the memory map register table has eight bit locations.
The memory map is roughly divided into three sections: the
chip configuration registers (Address 0x00 to Address 0x02);
the ADC functions registers, including setup, control, and test
(Address 0x08 to Address 0xA8); and the device update register
(Address 0xFF).
After the AD9683 is reset, critical registers are loaded with default
values. The default values for the registers are given in the memory
map register table (see Table 17).
The memory map register table (see Table 17) documents the
default hexadecimal value for each hexadecimal address shown.
The column with the heading Bit 7 (MSB) is the start of the default
hexadecimal value given. For example, Address 0x14, the output
mode register, has a hexadecimal default value of 0x01. This means
that Bit 0 = 1, and the remaining bits are 0s. This setting is the
default output format value, which is twos complement. For
more information on this function and others, see the AN-877
Application Note, Interfacing to High Speed ADCs via SPI. This
application note details the functions controlled by Address 0x00
to Address 0x21 and Address 0xFF, with the exception of
Address 0x08 and Address 0x14. The remaining registers,
Address 0x08, Address 0x14, and Address 0x3A through
Address 0xA8, are documented in the Memory Map Register
Descriptions section.
Logic Levels
An explanation of logic level terminology follows:
•
•
“Bit is set” is synonymous with “bit is set to Logic 1” or
“writing Logic 1 for the bit.”
“Clear a bit” is synonymous with “bit is set to Logic 0” or
“writing Logic 0 for the bit.”
Transfer Register Map
Address 0x09, Address 0x0B, Address 0x0D, Address 0x10,
Address 0x14, Address 0x18, Address 21, and Address 0x3A to
Address 0x4C are shadowed. Writes to these addresses do not
affect part operation until a transfer command is issued by
writing 0x01 to Address 0xFF, setting the transfer bit. This
allows these registers to be updated internally and simultaneously
when the transfer bit is set. The internal update takes place when
the transfer bit is set, and then the bit autoclears.
Open and Reserved Locations
All address and bit locations that are not included in Table 17
are not currently supported for this device. Write unused bits of
a valid address location with 0s. Writing to these locations is
required only when part of an address location is open (for
example, Address 0x18). If the entire address location is open
(for example, Address 0x13), do not write to this address location.
Rev. D | Page 34 of 44
Data Sheet
AD9683
MEMORY MAP REGISTER TABLE
All address and bit locations that are not included in Table 17 are not currently supported for this device.
Table 17. Memory Map Registers
Reg
Addr
(Hex)
0x00
0x01
0x02
Reg Addr
Name
SPI port
configuration
Chip ID
Chip grade
Bit 7
(MSB)
0
0x08
PDWN modes
0x09
Global clock
Reserved
0x0A
PLL status
PLL locked
status
0x0B
Clock divide
0x0D
Test mode
0x10
Customer offset
Bit 6
LSB first
User test mode cycle:
00 = repeat pattern
(user pattern 1, 2, 3, 4, 1,
2, 3, 4, 1, …);
10 = single pattern
(user pattern 1, 2, 3, 4,
then all zeros)
Bit 5
Soft reset
Bit 4
1
Bit 3
1
Bit 2
Soft reset
Bit 1
LSB first
Bit 0 (LSB)
0
AD9683 8-bit chip ID is 0xC3
Speed grade:
Reserved for chip die revision, currently
00 = 250 MSPS,
0x0
11 = 170 MSPS
External
JESD204B
JESD204B power modes:
ADC power modes:
PDWN
standby
00 = normal mode
00 = normal mode
mode:
(power-up);
mode
(power-up),
0=
(when
01 = power-down
01 = power-down mode,
PDWN is
external
mode, PLL off, serializer
10 = standby mode,
full
PDWN is
off, clocks stopped,
does not affect JESD204B
powerused):
digital held in reset;
digital circuitry
down,
0=
10 = standby mode, PLL
1=
JESD204B
on, serializer off, clocks
PDWN
core is
stopped, digital circuitry
puts
unaffected,
held in reset
device in
1=
standby
JESD204B
core is
powered
down
except for
PLL
Clock selection:
Clock duty
00 = Nyquist clock,
cycle
01 = RF clock divide by 2,
stabilizer
10 = RF clock divide by 4,
enable
11 = clock off
JESD204B
link is ready
Clock divide phase relative to
Clock divider ratio relative to
the encode clock:
the encode clock:
0x0 = 0 input clock cycles delayed,
0x00 = divide by 1,
0x1 = 1 input clock cycles delayed,
0x01 = divide by 2,
0x2 = 2 input clock cycles delayed,
0x02 = divide by 3,
…
…
0x7 = 7 input clock cycles delayed
0x07 = divide by 8
Long
Short
Data output test generation mode:
pseudopseudo0000 = off (normal mode),
random
random
0001 = midscale short,
number
number
0010 = positive full scale,
generator generator
0011 = negative full scale,
reset:
reset:
0100 = alternating checkerboard,
0 = long
0 = short
0101 = PN sequence long,
PRN
PRN
0110 = PN sequence short,
enabled,
enabled,
0111 = 1/0 word toggle,
1 = long
1 = short
1000 = user test mode (use with Address 0x0D,
PRN held
PRN held in
Bits[7:6] and user pattern 1, 2, 3, 4),
in reset
reset
1001 to 1110 = unused,
1111 = ramp output
Offset adjust in LSBs from +31 to −32 (twos complement format):
01 1111 = adjust output by +31,
01 1110 = adjust output by +30,
…
00 0001 = adjust output by +1,
00 0000 = adjust output by 0 (default),
…
10 0001 = adjust output by −31,
10 0000 = adjust output by −32
Rev. D | Page 35 of 44
Default
0x18
Notes
0xC3
0x00
or 0x30
Read only
0x00
0x01
DCS enabled
if clock divider
enabled
Read only
0x00
0x00
0x00
Clock divide
values other
than 0x00
automatically
cause the DCS
to become
active
AD9683
Reg
Addr
(Hex)
0x14
Reg Addr
Name
Output mode
0x15
CML output
adjust
0x18
Input span
select
0x19
User Test
Pattern 1 LSB
User Test
Pattern 1 MSB
User Test
Pattern 2 LSB
User Test
Pattern 2 MSB
User Test
Pattern 3 LSB
User Test
Pattern 3 MSB
User Test
Pattern 4 LSB
User Test
Pattern 4 MSB
PLL low encode
0x1A
0x1B
0x1C
0x1D
0x1E
0x1F
0x20
0x21
0x3A
SYNCINB±/
SYSREF±
control
Data Sheet
Bit 7
Bit 6
Bit 5
(MSB)
JESD204B CS bits assignment
(in conjunction with Address 0x72):
000 = {overrange||underrange, valid},
001 = {overrange, underrange},
010 = {overrange||underrange, blank},
011 = {blank, valid},
100 = {blank, blank},
101 = {underrange, overrange},
110 = {valid, overange||underrange},
111 = {valid, blank}
Bit 4
ADC
output
disable
Bit 3
Bit 2
ADC data
invert:
0 = normal
(default),
1=
inverted
Bit 1
Bit 0 (LSB)
Data format select (DFS) :
00 = offset binary,
01 = twos complement
JESD204B CML differential output drive
level adjustment:
000 = 75% of nominal ( 438 mV p-p),
001 = 83% of nominal (488 mV p-p),
010 = 91% of nominal (538 mV p-p),
011 = nominal (default) (588 mV p-p),
100 = 109% of nominal (638 mV p-p),
101 = 117% of nominal (690 mV p-p),
110 = 126% of nominal (740 mV p-p),
111 = 134% of nominal (790 mV p-p)
Main reference full-scale VREF adjustment:
0 1111 = internal 2.087 V p-p,
…
0 0001 = internal 1.772 V p-p,
0 0000 = internal 1.75 V p-p (default),
1 1111 = internal 1.727 V p-p,
…
1 0000 = internal 1.383 V p-p
User Test Pattern 1 LSB; use in conjunction with Address 0x0D and Address 0x61
Default
0x01
0x03
0x00
User Test Pattern 1 MSB
User Test Pattern 2 LSB
User Test Pattern 2 MSB
User Test Pattern 3 LSB
User Test Pattern 3 MSB
User Test Pattern 4 LSB
User Test Pattern 4 MSB
00 = for lane speeds of
>2 Gbps,
01 = for lane speeds of
<2 Gbps
JESD204B
JESD204B
realign
realign
SYNCINB±:
SYSREF±:
0 = normal
0=
mode,
normal
1 = realigns
mode,
lane on
1=
every
realigns
active
lane on
SYNCINB±
every
active
SYSREF±
Rev. D | Page 36 of 44
0x00
SYSREF±
mode:
0=
continuous
reset clock
dividers,
1 = sync
on next
SYSREF±
rising edge
only
SYSREF±
enable:
0=
disabled,
1=
enabled.
Note that
this bit
self-clears
after
SYSREF if
SYSREF±
mode = 1
Enable
internal
SYSREF±
buffer;
0 = buffer
disabled,
external
SYSREF±
pin
ignored;
1 = buffer
enabled,
use
external
SYSREF±
pin
0x00
Notes
Data Sheet
Reg
Addr
(Hex)
0x40
0x41
0x42
0x45
0x47
0x48
0x49
0x4A
0x4B
0x4C
0x5E
0x5F
Reg Addr
Name
DC correction
control
AD9683
Bit 7
(MSB)
Bit 6
Freeze dc
correction:
0=
calculate,
1 = freeze
value
DC Correction
Value 0
DC Correction
Value 1
Fast detect
control
Bit 5
Bit 4
Bit 3
Bit 2
DC correction bandwidth select;
correction bandwidth is 2387.32 Hz/register value;
there are 14 possible values;
0000 = 2387.32 Hz,
0001 = 1193.66 Hz,
0010 = 596.83 Hz,
0011 = 298.42 Hz,
0100 = 149.21 Hz,
0101 = 74.60 Hz,
0110 = 37.30 Hz,
0111 = 18.65 Hz,
1000 = 9.33 Hz,
1001 = 4.66 Hz,
1010 = 2.33 Hz,
1011 = 1.17 Hz,
1100 = 0.58 Hz,
1101 = 0.29 Hz,
1110 = reserved,
1111 = reserved
DC correction value LSB[7:0]
Bit 1
Enable dc
correction
Bit 0 (LSB)
0x00
Forced FD
output
value; if
force FD
pin is true,
this value
is output
on the FD
pin
Fast detect upper threshold[7:0]
Fast detect upper threshold[14:8]
Fast detect
upper
threshold
Fast detect
lower threshold
Fast detect
dwell time
JESD204B quick
config
JESD204B Link
Control 1
0x60
JESD204B Link
Control 2
Reserved;
set to 0
Serial tail
bit
enable:
0 = extra
bits are 0,
1 = extra
bits are
9-bit PN
Reserved;
set to 0
0x61
JESD204B Link
CTRL 3
Reserved;
set to 0
Reserved;
set to 0
0x64
JESD204B DID
config
Force FD
output
enable:
0=
normal
function,
1 = force
to value
Enable fast
detect
output
Fast detect lower threshold[7:0]
Fast detect lower threshold[14:8]
Fast detect dwell time[7:0]
Fast detect dwell time[15:8]
JESD204B quick configuration, always reads back 0x00;
0x11: M = 1, L = 1; one converter, one lane
JESD204B Reserved;
ILAS mode:
Reserved;
test
set to 1
01 = ILAS normal mode
set to 0
sample
enabled,
enable
11 = ILAS always on, test
mode
Reserved;
set to 0
SYNCINB±
logic type:
0 = LVDS
(differential),
1 = CMOS
(singleended)
Test data injection point:
01 = 10-bit data at
8B/10B output,
10 = 8-bit data at
scrambler input
Reserved;
set to 0
Invert
transmit
bits
0x00
0x00
JESD204B
link powerdown; set
high while
configuring
link
parameters
0x14
Reserved;
set to 0
0x00
JESD204B test mode patterns:
0000 = normal operation (test mode disabled),
0001 = alternating checker board,
0010 = 1/0 word toggle,
0011 = PN Sequence PN23,
0100 = PN Sequence PN9,
0101 = continuous/repeat user test mode,
0110 = single user test mode,
0111 = reserved,
1100 = PN Sequence PN7,
1101 = PN Sequence PN15,
other setting are unused
JESD204B DID value
Rev. D | Page 37 of 44
Notes
0x00
DC correction value MSB[15:8]
FD pin
function:
0 = fast
detect,
1=
overrange
Default
0x00
0x00
Always reads
back 0x00
AD9683
Reg
Addr
(Hex)
0x65
0x67
0x6E
0x6F
Reg Addr
Name
JESD204B BID
config
JESD204B LID
config
JESD204B
scrambler (SCR)
and lane (L)
configuration
Data Sheet
Bit 7
(MSB)
Bit 6
Bit 5
Bit 4
Bit 3
Bit 2
Bit 1
JESD204B BID value
Bit 0 (LSB)
Default
JESD204B LID value
JESD204B number of lanes (L); 0 = one lane per link (L = 1)
JESD204B
scrambling
(SCR):
0=
disabled,
1=
enabled
0x80
JESD204B
parameter, F
JESD204B number of octets per frame (F); calculated value; read only
0x01
0x70
JESD204B
parameter, K
JESD204B number of frames per multiframe (K);
set value of K per JESD204B specifications, but must also be a multiple of four octets
0x1F
0x71
JESD204B
parameter, M
JESD204B
parameters,
N/CS
JESD204B number of converters (M); 0 = 1 converter
0x00
0x72
0x73
0x74
0x75
0x76
0x77
0x79
0x80
JESD204B
parameters,
subclass/N’
JESD204B
parameter, S
JESD204B
parameters, HD
and CF
JESD204B
RESV1
JESD204B
RESV2
JESD204B
CHKSUM
JESD204B
output driver
control
0x8B
JESD204B LMFC
offset
0xA8
JESD204B
preemphasis
Device update
(global)
0xFF
Notes
Read only
(Note that this value is in x − 1 format)
(Note that this value is in x − 1 format)
Number of control bits
(CS):
00 = no control bits
(CS = 0),
01 = 1 control bit
(CS = 1),
10 = 2 control bits
(CS = 2)
JESD204B subclass:
00 = Subclass 0,
01 = Subclass 1 (default)
Reserved;
set to 1
JESD204B
HD value;
read only
ADC converter resolution (N),
0xD = 14-bit converter (N = 14)
0x0D
JESD204B N’ value; 0xF = N’ = 16
0x2F
Read only
(Note that this value is in x − 1 format)
(Note that this value is in x − 1 format)
JESD204B samples per converter per frame cycle (S); read only
0x20
JESD204B control words per frame clock cycle per link (CF); read only
0x00
(Note that this value is in x − 1 format)
Read only
(Note that this value is in x − 1 format)
JESD204B Reserved Field 1
JESD204B Reserved Field 2
JESD204B checksum value for the output lane
JESD204B
driver
powerdown:
0=
enabled,
1=
powered
down
Local multiframe clock (LMFC) phase offset value; reset value for
LMFC phase counter when SYSREF± is asserted; used for
deterministic delay applications
JESD204B preemphasis enable option (consult factory for more details);
set value to 0x04 for preemphasis off, and set value to 0x14 for preemphasis on
Transfer
settings
Rev. D | Page 38 of 44
0x00
0x00
0x04
Typically not
required
Data Sheet
AD9683
MEMORY MAP REGISTER DESCRIPTIONS
SYNCINB±/SYSREF± Control (Address 0x3A)
For more information on functions controlled in Address 0x00
to Address 0x21 and Address 0xFF, with the exception of Address
0x08 and Address 0x14, see the AN-877 Application Note,
Interfacing to High Speed ADCs via SPI.
Bits[7:5]—Reserved
Bit 4—JESD204B realign SYNCINB±
PDWN Modes (Address 0x08)
Bits[7:6]—Reserved
Bit 5—External PDWN mode
When this bit is set low, the JESD204B link operates in normal
mode. When this bit is high, the JESD204B link realigns on
every active SYNCINB± assertion.
Bit 3—JESD204B realign SYSREF±
This bit controls the function of the PDWN pin. When this bit is 0,
asserting the PDWN pin results in a full power-down of the device.
When this bit is 1, asserting the PDWN pin places the device in
standby.
Bit 4—JESD204B standby mode
This bit controls the state of the JESD204B digital circuitry when
the external PDWN pin is used to place the device into standby.
If this bit is 0, the JES204B digital circuitry is not placed into
standby. When this bit is 1, the JESD204B circuitry is placed
into standby when the PDWN pin is asserted and Bit 5 is 1.
Bits[3:2]—JESD204B power modes
These bits control the power modes of the JESD204B digital
circuitry. When Bits[3:2] = 00, the JESD204B digital circuitry
is in normal mode. When Bits[3:2] = 01, the JESD204B digital
circuitry is in power-down mode with the PLL off, serializer off,
clocks stopped, and the digital circuitry held in reset. When
Bits[3:2] = 10 the JESD204B digital circuitry is placed into standby
mode with the PLL on, serializer off, clocks stopped, and the
digital circuitry held in reset.
Bits[1:0]—ADC power modes
These bits select power mode for the ADC excluding the
JESD204B digital circuitry. When Bits[1:0] = 00, the ADC is in
normal mode. When Bits[1:0] = 01, the ADC is placed into
power-down mode, and when Bits[1:0] = 10, the ADC is placed
into standby mode.
When this bit is set low, the JESD204B link operates in normal
mode. When this bit is high, the JESD204B link realigns on
every active SYSREF± assertion.
Bit 2—SYSREF± mode
When this bit is set low, the clock dividers are continuously
reset on each SYSREF± assertion. When this bit is high, the
clock dividers are reset on the next rising edge of SYSREF± only.
Bit 1—SYSREF± enable
When this bit is set low, the SYSREF± input is disabled. When
this bit is high, the SYSREF± input is enabled.
Bit 0—Enable SYNCINB± buffer
When this bit is set low, the SYNCINB± input buffer is disabled.
When this bit is high, the SYNCINB± input buffer is enabled.
DC Correction Control (Address 0x40)
Bit 7—Reserved
Bit 6—Freeze dc correction
When Bit 6 is set low, the dc correction is continuously calculated.
When Bit 6 is set high, the dc correction is no longer updated to
the signal monitor block, which holds the last dc value calculated.
Bits[5:2]—DC correction bandwidth select
Bits[5:2] set the averaging time of the signal monitor dc correction
function. This 4-bit word sets the bandwidth of the correction
block, according to the following equation:
DC _ Corr _ BW = 2 −k − 14 ×
Output Mode (Address 0x14)
f CLK
2× π
Bit 4—ADC output disable
where:
k is the 4-bit value programmed in Bits[5:2] of Address 0x40
(values between 0 and 13 are valid for k; programming 14 or 15
provides the same result as programming 13).
fCLK is the AD9683 ADC sample rate in hertz.
If this bit is set, the output data from the ADC is disabled.
Bit 1—Enable dc correction
Bit 3—Open
Bit 2—ADC data invert
Setting this bit high causes the output of the dc measurement
block to be summed with the data in the signal path to remove
the dc offset from the signal path.
Bits[7:5]—JESD204B CS Bits Assignment
These bits control the function of the CS bits in the JESD204B
serial data stream.
If this bit is set, the output data from the ADC is inverted.
Bit 0—Reserved
Bits[1:0]—Data Format Select
These bits select the output data format. When Bits[1:0] = 00,
the output data is in offset binary format, and when Bits[1:0] = 01,
the output data is in twos complement format.
DC Correction Value 0 (Address 0x41)
Bits[7:0]—DC correction value LSB[7:0]
These bits are the LSBs of the dc correction value.
Rev. D | Page 39 of 44
AD9683
Data Sheet
DC Correction Value 1 (Address 0x42)
JESD204B Quick Configuration (Address 0x5E)
Bits[7:0]—DC correction value MSB[15:8]
Bits[7:0]—JESD204B quick configuration
These bits are the MSBs of the dc correction value.
These bits serve to quickly set up the default JESD204B link
parameters for M = 1 and L = 1.
Fast Detect Control (Address 0x45)
JESD204B Link Control 1 (Address 0x5F)
Bits[7:5]—Reserved
Bit 4—FD pin function
When this bit is set low, the FD pin functions as the fast detect
output. When this pin is set high, the FD pin functions as the
overrange indicator.
Bit 3—Force FD output enable
Setting this bit high forces the FD output pin to the value written to
Bit 2 of this register (Address 0x45). This enables the user to
force a known value on the FD pin for debugging.
Bit 7—Open
Bit 6—Serial tail bit enable
If this bit is set and the CS bits are not enabled, unused tail bits are
padded with a pseudorandom number sequence from a 9-bit
LFSR (see JESD204B 5.1.4).
Bit 5—JESD204B test sample enable
Bit 2—Forced FD Output Value
If set, JESD204B test samples are enabled, and the long transport
layer test sample sequence (as specified in JESD204B Section
5.1.6.3) sent on all link lanes.
The value written to Bit 2 is forced on the FD output pin when
Bit 3 is written high.
Bit 4—Reserved; set to 1
Bits[3:2]—ILAS mode
Bit 1—Reserved
Bit 0—Enable fast detect output
01 = initial lane alignment sequence enabled.
Setting this bit high enables the output of the upper threshold
FD comparator to drive the FD output pin.
Fast Detect Upper Threshold (Address 0x47 and
Address 0x48)
Address 0x48, Bit 7—Reserved
Address 0x48, Bits[6:0]—Fast detect upper threshold[14:8]
Address 0x47, Bits[7:0]—Fast detect upper threshold[7:0]
These registers provide an upper limit threshold. The 15-bit
value is compared with the output magnitude from the ADC
block. If the ADC magnitude exceeds this threshold value, the
FD output pin is set when Bit 0 in Address 0x45 is set.
Fast Detect Lower Threshold (Address 0x49 and
Address 0x4A)
11 = initial lane alignment sequence always on in test mode;
JESD204B data link layer test mode where the repeated lane
alignment sequence (as specified in JESD204B 5.3.3.8.2) is sent on
all lanes.
Bit 1—Reserved; set to 0
Bit 0—JESD204B link power-down
If Bit 0 is set high, the serial transmit link is held in reset with its
clock gated off. The JESD204B transmitter must be powered
down when changing any of the link configuration bits.
JESD204B Link Control 2 (Address 0x60)
Bits[7:5]—Reserved; set to 0
Bit 4—SYNCINB± logic type
0 = LVDS differential pair SYNCINB± input (default).
Address 0x4A, Bit 7—Reserved
Address 0x4A, Bits[6:0]—Fast detect lower threshold[14:8]
Address 0x49, Bits[7:0]—Fast detect lower threshold[7:0]
These registers provide a lower limit threshold. The 15-bit value is
compared with the output magnitude from the ADC block. If the
ADC magnitude is less than this threshold value for the number
of cycles programmed in the fast detect dwell time register, the
FD output bit is cleared.
1 = CMOS single-ended SYNCINB± using the SYNCINB+ input.
If operating in this mode, the SYNCINB− input should be left
floating.
Bit 3—Open
Bit 2—Reserved; set to 0
Bit 1—Invert transmit bits
Setting this bit inverts the 10 serial output bits. This effectively
inverts the output signals.
Fast Detect Dwell Time (Address 0x4B and
Address 0x4C)
Bit 0—Reserved; Set to 0
Address 0x4C, Bits[7:0]—Fast Detect Dwell Time[15:8]
Address 0x4B, Bits[7:0]—Fast Detect Dwell Time[7:0]
Bit [7:6]—Reserved; set to 0
Bits[5:4]—Test data injection point
These register values set the minimum time in ADC sample
clock cycles (after clock divider) that a signal needs to stay below
the lower threshold limit before the FD output bits are cleared.
01 = 10-bit test generation data injected at output of 8B/10B
encoder (at input to PHY).
JESD204B Link Control 3 (Address 0x61)
10 = 8-bit test generation data injected at input of scrambler
Rev. D | Page 40 of 44
Data Sheet
AD9683
Bits[3:0]—JESD204B test mode patterns
0000 = normal operation (test mode disabled).
JESD204B Parameter, M (Address 0x71)
0001 = alternating checkerboard.
0 = link connected to one ADC. Only primary input used (M = 1).
0010 = 1/0 word toggle.
JESD204B Parameters, N/CS (Address 0x72)
0011 = PN23 sequence.
Bits[7:6]—Number of control bits (CS)
0100 = PN9 sequence.
00 = no control bits sent per sample (CS = 0).
0101 = continuous/repeat user test mode. The most significant
bits from the user pattern (1, 2, 3, 4) are placed on the output for
one clock cycle and then the output user pattern is repeated (1,
2, 3, 4, 1, 2, 3, 4, 1, 2, 3, 4….).
01 = one control bit sent per sample—overrange bit enabled
(CS = 1).
0110 = single user test mode. The most significant bits from the
user pattern (1, 2, 3, 4) are placed on the output for one clock
cycle, and then all zeros are output (output user pattern 1, 2, 3, 4;
then output all zeros).
Bits[5:4]—Open
Bits [3:0]—ADC converter resolution (N)
Bits[7:0]—JESD204B Number of Converters (M)
0111 = reserved.
10 = two control bits sent per sample—overflow/underflow bits
enabled (CS = 2).
Read only bits showing the converter resolution (reads back 13
(0xD) for 14-bit resolution).
JESD204B Parameter, Subclass/N’ (Address 0x73)
1100 = PN7 sequence.
Bit 7—Reserved
Bits[6:5]—JESD204B subclass
1101 = PN15 sequence.
Others = unused.
When Bits[6:5] are 00, the device operates in Subclass 0 mode, and
when Bits[6:5] are 01, the device operates in Subclass 1 mode.
JESD204B Device Identification (DID) Configuration
(Address 0x64)
Bit 4—Reserved
Bits[3:0]—JESD204B N’ value
Bits[7:0]—JESD204B device identification (DID) value
JESD204B Bank Identification (BID) Configuration
(Address 0x65)
Read only bits showing the total number of bits per sample,
minus 1 (reads back 15 (0xF) for 16 bits per sample).
Bits[7:4]—Open
Bits[3:0]—JESD204B bank identification (BID) value
JESD204B Samples per Converter per Frame Cycle (S)
(Address 0x74)
JESD204B Lane Identification (LID) Configuration
(Address 0x67)
Bits[7:5]—Open
Bits[4:0]—JESD204B lane identification (LID) value
JESD204B Scrambler (SCR) and Lane (L) Configuration
(Address 0x6E)
Bit 7—JESD204B scrambling (SCR)
When this bit is set to low, it disables the scrambler (SCR = 0).
When this bit is set to high, it enables the scrambler (SCR = 1).
Bits[6:5]—Open
Bits[4:0]—JESD204B number of lanes (L)
Bits[7:6]—Open
Bit 5—Reserved; set to 1
Bits[4:0]—JESD204B samples per converter per frame per
cycle (S)
Read only bits showing the number of samples per converter
frame cycle, minus 1 (reads back 0 (0x0) for one sample per
converter frame).
JESD204B Parameters HD and CF (Address 0x75)
Bit 7—JESD204B high density (HD) value (read only)
Read only bit. Always set to 0.
Bits[6:5]—Open
Bits[4:0]—JESD204B control words per frame clock cycle per
link (CF)
0 = one lane per link (L = 1).
JESD204B Parameter, F (Address 0x6F, Read Only)
Bits[7:0]—JESD204B number of octets per frame (F)
The readback from this register is calculated from the following
equation: F = (M × 2)/L.
The valid value for F is F = 2, with M = 1 and L = 1.
Read only bits. Reads back 0x0.
JESD204B Reserved 1 (Address 0x76)
Bits[7:0]—JESD204B Reserved Field 1
This read/write register is available for customer use.
JESD204B Parameter, K (Address 0x70)
Bits[7:0]—JESD204B Number of Frames per Multiframe (K)
This register sets the K value for the JESD204B interface, which
defines the number of frames per multiframe. The value must
be a multiple of 4.
JESD204B Reserved 2 (Address 0x77)
Bits[7:0]—JESD204B Reserved Field 2
This read/write register is available for customer use.
Rev. D | Page 41 of 44
AD9683
Data Sheet
JESD204B Checksum (Address 0x79)
JESD204B LMFC Offset (Address 0x8B)
Bits[7:0]—JESD204B checksum value for the output lane
Bits[7:5]—Reserved
Bits[4:0]—Local multiframe clock phase offset value
This read only register is automatically calculated for the lane.
Checksum equals sum (all link configuration parameters for the
lane) modulus 256.
JESD204B Output Driver Control (Address 0x80)
These bits are the reset value for the local multiframe clock
(LMFC) phase counter when SYSREF± is asserted. These bits
are used in applications requiring deterministic delay.
Bits[7:1]—Reserved
Bit 1—JESD204B driver power-down
JESD204B Preemphasis (Address 0xA8)
When this bit is set low, the JESD204B output drivers are enabled.
When this bit is set high, the JESD204B output drivers are
powered down.
These bits enable the preemphasis feature on the JESD204B
output drivers. Setting Bits[7:0] to 0x04 disables premphasis,
and setting Bits[7:0] to 0x14 enables preemphasis.
Bits[7:0]—JESD204B preemphasis enable option
Rev. D | Page 42 of 44
Data Sheet
AD9683
APPLICATIONS INFORMATION
DESIGN GUIDELINES
Before starting system level design and layout of the AD9683, it
is recommended that the designer become familiar with these
guidelines, which describe the special circuit connections and
layout requirements needed for certain pins.
Power and Ground Recommendations
When connecting power to the AD9683, it is recommended that
two separate 1.8 V power supplies be used. The power supply for
AVDD can be isolated, and the power supply for DVDD and
DRVDD can be tied together, in which case, an isolation inductor
of approximately 1 µH is recommended. Alternatively, the
JESD204B PHY power (DRVDD) and analog (AVDD) supplies
can be tied together, and a separate supply can be used for the
digital outputs (DVDD).
The designer can employ several different decoupling capacitors
to cover both high and low frequencies. Place these capacitors
close to the point of entry at the PCB level and close to the pins
of the part with minimal trace length.
When using the AD9683, a single PCB ground plane is sufficient.
With proper decoupling and smart partitioning of the PCB analog,
digital, and clock sections, optimum performance is easily
achieved.
Exposed Pad Thermal Heat Slug Recommendations
It is mandatory that the exposed pad on the underside of the
ADC be connected to analog ground (AGND) to achieve the
best electrical and thermal performance. Mate a continuous,
exposed (no solder mask) copper plane on the PCB to the
AD9683 exposed pad.
The copper plane should have several vias to achieve the lowest
possible resistive thermal path for heat dissipation to flow through
the bottom of the PCB. Fill or plug these with nonconductive
epoxy.
To maximize the coverage and adhesion between the ADC and
the PCB, overlay a silkscreen to partition the continuous plane
on the PCB into several uniform sections. This provides several tie
points between the ADC and the PCB during the reflow process.
Using one continuous plane with no partitions guarantees only
one tie point between the ADC and the PCB. See the evaluation
board for a PCB layout example. For detailed information about
the packaging and PCB layout of chip scale packages, refer to
the AN-772 Application Note, A Design and Manufacturing
Guide for the Lead Frame Chip Scale Package (LFCSP).
VCM
Decouple the VCM pin to ground with 0.1 µF capacitors, as shown
in Figure 45. It is recommended to place one 0.1 µF capacitor as
close as possible to the VCM pin and another at the VCM
connection to the analog input network.
SPI Port
Do not activate the SPI port during periods when the full dynamic
performance of the converter is required. Because the SCLK, CS,
and SDIO signals are typically asynchronous to the ADC clock,
noise from these signals can degrade converter performance. If the
on-board SPI bus is used for other devices, it may be necessary
to provide buffers between this bus and the AD9683 to keep
these signals from transitioning at the converter input pins during
critical sampling periods.
Rev. D | Page 43 of 44
AD9683
Data Sheet
OUTLINE DIMENSIONS
0.30
0.25
0.18
32
25
1
24
0.50
BSC
3.75
3.60 SQ
3.55
EXPOSED
PAD
17
TOP VIEW
0.80
0.75
0.70
0.50
0.40
0.30
8
16
0.05 MAX
0.02 NOM
COPLANARITY
0.08
0.20 REF
PKG-004570
SEATING
PLANE
PIN 1
INDICATOR
9
BOTTOM VIEW
0.25 MIN
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
SECTION OF THIS DATA SHEET.
COMPLIANT TO JEDEC STANDARDS MO-220-WHHD-5.
01-26-2016-B
PIN 1
INDICATOR
5.10
5.00 SQ
4.90
Figure 68. 32-Lead Lead Frame Chip Scale Package [LFCSP_WQ]
5 mm × 5 mm Body, Very Very Thin Quad
(CP-32-12)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
AD9683BCPZ-170
AD9683BCPZRL7-170
AD9683-170EBZ
AD9683BCPZ-250
AD9683BCPZRL7-250
AD9683-250EBZ
1
Temperature Range
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
Package Description
32-Lead Lead Frame Chip Scale Package [LFCSP_WQ]
32-Lead Lead Frame Chip Scale Package [LFCSP_WQ]
Evaluation Board with AD9683-170
32-Lead Lead Frame Chip Scale Package [LFCSP_WQ]
32-Lead Lead Frame Chip Scale Package [LFCSP_WQ]
Evaluation Board with AD9683-250
Z = RoHS Compliant Part.
©2013–2016 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D11410-0-6/16(D)
Rev. D | Page 44 of 44
Package Option
CP-32-12
CP-32-12
CP-32-12
CP-32-12