TI1 ALM2402-Q1 The alm2402-q1 is a dual high voltage Datasheet

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ALM2402-Q1
SLOS912A – FEBRUARY 2015 – REVISED APRIL 2015
ALM2402-Q1 Dual Op-amp with High Current Output
1 Features
3 Description
•
The ALM2402-Q1 is a dual high voltage, high current
op-amp with protection features that are optimal for
driving low impedances and/or high ESR capacitive
loads. ALM2402-Q1 operates with single or split
power supplies from 5.0 V to 16 V and can output up
to 400 mA DC.
1
•
•
•
•
•
•
•
•
•
•
•
High Output Current Drive: 400 mA Continuous
(Per Channel)
– Op-amp with Discrete Power Boost Buffer
Replacement
Wide Supply Range for Both Supplies (up to 16 V)
Over Temperature Shutdown
Current limit
Shutdown Pin for Low Iq Applications
Stable with Large Capacitive Loads (up to 3 µF)
Zero Crossover Distorion
Qualified for Automotive Applications
AEC-Q100 Qualified With the Following Results:
– Device Temperature Grade 1: –40°C to 125°C
Ambient Operating Temperature Range
– Device HBM Classification Level 2
– Device CDM Classification Level C5
Low Offset Voltage: 1 mV (typ)
Internal RF/EMI Filter
Available in 3 mm x 3 mm 12 pin WSON (DRR)
with Thermal Pad
2 Applications
•
•
•
Each op-amp includes over-temperature flag/shutdown. It also includes separate supply pins for each
output stage that allow the user to apply a lower
voltage on the output to limit the Voh and henceforth
the on-chip power dissipation.
The ALM2402 is packaged in a 12 pin leadless DRR
package and 14 pin leaded HTSSOP (preview). Both
include a thermally conductive power pad that
facilitates heat sinking. The very low thermal
impedance of these packages enable optimal current
drive with minimal die temperature increase.
Providing customers with the ability to drive high
currents in harsh temperature conditions. Maximum
power dissipation can be determined in the figure
below.
Device Information(1)
PART NUMBER
ALM2402-Q1
Large Capacitive Loads
– Cable Shields
– Reference Buffers
– Power-FET/IGBT Gates
– Super Caps
Tracking LDO
Inductive Loads
– Resolvers
– Bipolar DC & Servo Motors
– Solenoids & Valves
PACKAGE
BODY SIZE
DRR (12)
3.00 mm x 3.00 mm
HTSSOP (14)
5.00 mm x 4.40 mm
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
4 Simplified Schematic
V CC_OUT
Maximum Power Dissipation vs Temperature
+
OPAMP
VCC
IN1+
5
VCC_ O1
+ ½
ALM2402
OUT1
IN1OTF1
GND
Allowable Power Dissipation (W)
VCC
4.5
4
3.5
3
2.5
2
1.5
1
0.5
-40
-20
0
20
40
60
TA(qC)
80
100
120
140
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
ALM2402-Q1
SLOS912A – FEBRUARY 2015 – REVISED APRIL 2015
www.ti.com
Table of Contents
1
2
3
4
5
6
7
8
9
Features ..................................................................
Applications ...........................................................
Description .............................................................
Simplified Schematic.............................................
Revision History.....................................................
Pin Configuration and Functions .........................
Specifications.........................................................
1
1
1
1
2
3
4
7.1
7.2
7.3
7.4
7.5
7.6
4
4
4
4
5
5
Absolute Maximum Ratings .....................................
Thermal Information ..................................................
ESD Ratings ............................................................
Recommended Operating Conditions.......................
Electrical Characteristics...........................................
AC Characteristics ....................................................
Typical Characteristics.......................................... 6
Detailed Description ............................................ 10
9.1 Overview ................................................................. 10
9.2 Functional Block Diagram ....................................... 10
9.3 Feature Description................................................. 11
9.4 Device Functional Modes........................................ 13
10 Applications and Implementation...................... 13
10.1 Application Information.......................................... 13
10.2 Typical Application ................................................ 15
11 Power Supply Recommendations ..................... 20
12 Layout................................................................... 21
12.1 Layout Guidelines ................................................. 21
12.2 Layout Example .................................................... 21
13 Device and Documentation Support ................. 22
13.1 Trademarks ........................................................... 22
13.2 Electrostatic Discharge Caution ............................ 22
13.3 Glossary ................................................................ 22
14 Mechanical, Packaging, and Orderable
Information ........................................................... 22
5 Revision History
Changes from Original (February 2015) to Revision A
•
2
Page
Initial release of full version document. ................................................................................................................................. 1
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6 Pin Configuration and Functions
IN1-
1
IN1+
2
3
OTF/SH_DN
HTSSOP
Exposed
Thermal Pad
14
GND
13
OUT1
12
VCC_O1
11
VCC
VCC_O2
IN2+
4
IN2-
5
10
GND
6
9
OUT2
NC
7
8
NC
DRR
IN1-
1
12
GND
IN1+
2
11
OUT1
OTF/SH_DN
3
IN2+
4
Exposed
10
Thermal Pad
9
VCC
IN2-
5
8
VCC_O2
GND
6
7
OUT2
VCC_O1
It is recommended to connect the Exposed Pad to ground for best thermal performance. Must not be connected to
any other pin than ground. However, it can be left floating.
HTSSOP is in preview
Pin Functions
PIN
NAME
DDR
PWP (1)
I/O
DESCRIPTION
NO.
NO.
IN(X)+
2, 4
2, 4
Input
non-inverting opamp input terminal
IN(X)-
1, 5
1, 5
Input
inverting opamp input terminal
OUT(X)
Output
11, 7
13, 9
OTF/SH_D
N
3
3
VCC_O(X)
8, 10
10, 12
Input
Output stage supply pin
VCC
9
11
Input
Gain stage supply pin
GND
6, 12
14
Input
Ground pin (Both ground pins must be used and connected together on board)
NC
N/A
7, 8
N/A
No Internal Connection (do no connect)
(1)
Opamp output
Input/output Over temperature flag and Shutdown (see for truth table)
Preview.
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7 Specifications
7.1 Absolute Maximum Ratings (1)
at 25°C free-air temperature (unless otherwise noted)
VCC
Supply Voltage
(2)
MIN
MAX
-0.3
18
UNIT
V
-0.3
18
V
-0.3
18
V
-0.3
18
V
20
mA
VCC_(OX)
Output supply voltage
VOUT(X)
Opamp voltage (2)
VIN(X)
Positive and negative input to GND voltage
IOTF
Over Temperature Flag pin maximum Current
VOTF
Over Temperature Flag pin maximum Voltage
ISC
Continuous output short current per opamp
TA
Operating free-air temperature range
–40
125
°C
TJ
Operating virtual junction temperature (3)
-40
150
°C
Tstg
Storage temperature range
–65
150
°C
(2)
0
7
Internally
Limited
V
mA
Figure 6
(1)
(2)
(3)
Stresses beyond those listed under "absolute maximum ratings" may cause permanent damage to the device. These are stress ratings
only, and functional operation of the device at these or any other conditions beyond those indicated under "recommended operating
conditions" is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
All voltage values are with respect to the GND/substrate terminal, unless otherwise noted.
Maximum power dissipation is a function of TJ(max), θJA, and TA. The maximum allowable power dissipation at any allowable ambient
temperature is PD = (TJ(max) – TA)/θJA. Operating at the absolute maximum TJ of 150°C can affect reliability.
7.2 Thermal Information
ALM2402Q1
THERMAL METRIC (1)
DRR
UNIT
12 PINS
θJA
Junction-to-ambient thermal resistance
39.2
°C/W
θJCtop
Junction-to-case (top) thermal resistance
34.5
°C/W
θJB
Junction-to-board thermal resistance
15.0
°C/W
ψJT
Junction-to-top characterization parameter
0.3
°C/W
ψJB
Junction-to-board characterization parameter
15.2
°C/W
θJCbot
Junction-to-case (bottom) thermal resistance
4.2
°C/W
(1)
For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
7.3 ESD Ratings
VALUE
V(ESD)
(1)
(2)
Electrostatic discharge
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001 (1)
±2000
Charged-device model (CDM), per JEDEC specification JESD22C101 (2)
±750
UNIT
V
JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process. Manufacturing with
less than 500-V HBM is possible with the necessary precautions.
JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process. Manufacturing with
less than 250-V CDM is possible with the necessary precautions.
7.4 Recommended Operating Conditions
TA= 25°C
MIN
MAX
TJ
Junction Temperature
-40
150
TA
Ambient Temeperature
-40
125
4
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UNIT
°C
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Recommended Operating Conditions (continued)
TA= 25°C
MIN
IOUT (1)
MAX
Continuous output current (sourcing)
400
Continuous output current (sinking)
400
VIH_OTF
OTF input high voltage (Opamp "On" or full operation state)
VIL_OTF
OTF input low voltage (Opamp "Off" or shutdown state)
VIN(X)
Positive and negative input to GND voltage
0
7
VOTF
Over Temperature Flag pin maximum Voltage
2
5
VCC
Input Vcc
4.5
16
VCC_O(X)
Output Vcc
3
16
(1)
UNIT
mA
1.0
0.35
V
Current Limit must taken into consideration when choosing maximum output current
7.5 Electrical Characteristics
VOTF = 5 V, VCC = VCC_O1 = VCC_O2 = 5 V and 12 V; TA = –40°C to 125°C; Typical Values at TA = 25°C, unless otherwise noted
PARAMETER
TEST CONDITIONS
VIO
Input Offset Voltage
IIB
Input Bias Current
IIOS
Input Offset Current
(1)
(1)
VICM
ICC
Vo
VICM = Vcc/2
(1)
Input Common Mode Range
MIN
VICM = Vcc/2, RL = 10 kΩ
TYP
MAX
1
15
mV
1.5
100
nA
30
nA
Vcc-1.2
V
VICM = Vcc/2
(1)
VCC = 5.0
0.2
VCC = 12.0 V
0.2
7
Total Supply Current (both
amplifiers) (1)
IO = 0 A
Positive Output Swing
VCC = VCC_O(X) = 5.0
V; VICM = Vcc/2; VID =
100 mV
ISINK = 200 mA
4.7
4.87
ISINK = 100 mA
4.85
4.94
VCC = VCC_O(X) = 5.0
V; VICM = Vcc/2; VID =
100 mV
ISOURCE = 200
mA
200
425
ISOURCE = 100
mA
100
200
165
175
°C
450
mV
Over Temp. Fault and Shutdown (3)
VOL_OTF
Over Temp. Fault low voltage
5
15
mA
0.5 (2)
VOTF = 0V
Negative Output Swing
OTF
157
Rpullup = 2.5 kΩ, Vpullup = 5.0 V
Short to Supply Limit (low-side limit) (4)
550
ILIMIT
Short to Ground Limit (high-side
limit) (1) (4)
750
PSRR
Power Supply Rejection Ratio (1)
VCC = 5.0 V to 12 V, RL = 10 kΩ, VICM =
Vcc/2, VO = Vcc/2
65
90
CMRR
Common Mode Rejection Ratio (1)
VICM = VICM(min) to VICM(max), RL = 10
kΩ, VO = Vcc/2
45
90
AVD
DC Voltage Gain (1)
RL = 10 kΩ, VICM = Vcc/2, VO = 0.3 V to
Vcc-1.5
70
90
(1)
(2)
(3)
(4)
UNIT
V
mV
mA
dB
dB
dB
Tested and verified in closed loop negative feedback configuration.
Verified by design.
Please see refer to Absolute Maximum Ratings() table for maximum junction temperature recommendations.
This is the static current limit. It can be temporarily higher in applications due to internal propagation delay.
7.6 AC Characteristics
TJ= –40°C to 125°C; Typical Values at TA = TJ = 25°C; VCC = VCC_O1 = VCC_O2 = 5.0 V and 12 V; VICM=VCC/2
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
GBW
Gain Bandwidth
CL=15 pF RL=10 kΩ
600
KHz
PM
Phase Margin
CL=200 nF RL= 50 Ω
50
°
GM
Gain Margin
CL=200 nF RL= 50 Ω
SR
Slew Rate
G = +1; CL=50 pF; 3 V step
THD + N
Total Harmonic Distortion + Noise
AV = 2 V/V, RL = 100 Ω, Vo = 8 Vpp, Vcc
= 12 V, F = 1 kHz, VICM = Vcc/2
17
dB
0.17
V/us
-80
dB
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AC Characteristics (continued)
TJ= –40°C to 125°C; Typical Values at TA = TJ = 25°C; VCC = VCC_O1 = VCC_O2 = 5.0 V and 12 V; VICM=VCC/2
PARAMETER
en
TEST CONDITIONS
Input Voltage Noise Density
MIN
Vcc = 5 V, F = 1kHz, VICM = Vcc/2
TYP
MAX
110
UNIT
nV/√HZ
8 Typical Characteristics
TA= 25°C and VCC = VCC_O(X)
5.01
TA=-40°C
TA=0°C
TA=25°C
TA=85°C
TA=105°C
TA=125°C
4.98
4.95
Vout (V)
Vout (V)
4.92
4.89
4.86
4.83
4.8
4.77
-350
-300
-250
-200
-150
Iout (mA)
-100
-50
0.65
0.6
0.55
0.5
0.45
0.4
0.35
0.3
0.25
0.2
0.15
0.1
0.05
0
TA=-40°C
TA=0°C
TA=25°C
TA=85°C
TA=105°C
TA=125°C
0
0
50
Figure 1. VOH at VCC = 5 V
TA=-40°C
TA=125°C
TA=0°C
TA=85°C
TA=25°C
Vout (V)
Vout (mV)
3.2
3.15
3.1
3.05
3
-0.35
-0.3
-0.25
-0.2
-0.15
Iout (mA)
-0.1
-0.05
0
0.65
0.6
0.55
0.5
0.45
0.4
0.35
0.3
0.25
0.2
0.15
0.1
0.05
0
250
300
350
300
350
TA=-40°C
TA=0°C
TA=25°C
TA=85°C
TA=105°C
TA=125°C
0
Figure 3. VOH at VCC = 3.3 V
6
150
200
Iout (mA)
Figure 2. VOL at VCC = 5V
3.3
3.25
100
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50
100
150
200
Iout (mA)
250
Figure 4. VOL at VCC = 3.3 V
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Typical Characteristics (continued)
TA= 25°C and VCC = VCC_O(X)
0.75
0.95
VCC=5V
VCC=12V
0.7
0.85
Current (mA)
Current (mA)
0.65
0.6
0.55
0.5
0.75
0.7
0.65
0.4
0.6
-20
0
20
40
60
TA(qC)
80
100
120
0.55
-40
140
Figure 5. Short to Supply Current Limit vs. Temperature
-20
0
20
40
60
TA(qC)
80
100
120
140
Figure 6. Short to Groung Current Limit vs. Temperature
400
120
Vcc_o(x) Diode (high side)
GND Diode (low side)
350
Gain
Phase
90
300
Gain (dB) & Phase (q)
Forward Current (mA)
0.8
0.45
0.35
-40
VCC=5V
VCC=12V
0.9
250
200
150
100
60
30
0
-30
50
0
200
-60
300
400
500 600 700 800
Forward Voltage
1000
1
2 3 4 5 7 10 2030 50 100 200
Freq (kHz)
500 1000
10000
VCC = 5.0 V
Figure 8. Gain and Phase (CL = 200 nF and RL = 50 Ω)
Figure 7. PMOS (High Side) and NMOS (Low Side) Output
Diode Forward Voltage
100
150
Gain
Phase
Vcc = 5V
Vcc = 12V
Output Impedance (:)
Gain (dB) & Phase (q)
120
90
60
30
0
10
1
-30
0.1
-60
1
2 3 4 5 7 10 2030 50 100 200
Freq (kHz)
500 1000
10000
0.05
0.01
0.1
1
10
Freq (kHz)
100
1000
10000
VCC = 5.0 V
Figure 9. Gain and Phase (CL = 50 pF and RL = 10 kΩ)
Figure 10. Output Impedance vs. Frequency
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Typical Characteristics (continued)
TA= 25°C and VCC = VCC_O(X)
140
100
VCC=5V
VCC=12V
120
PSRR- Vcc=12V
PSRR+ Vcc=12V
PSRR+ Vcc=5V
PSRR- Vcc=5V
80
PSRR (dB)
CMRR (dB)
100
80
60
60
40
40
20
20
0
0.01
0.1
0.5
2 3 5 10 20
Freq (kHz)
100
1000
0
0.01
10000
0.1
Figure 11. CMRR vs. Frequency
100
1000
10000
5
VCC=5V
VCC=12V
6.9
VCC=5V
VCC=12V
4.5
6.6
4
6.3
3.5
IIB (nA)
6
ICC (mA)
2 3 5 10 20
Freq (kHz)
Figure 12. PSRR vs. Frequency
7.2
5.7
5.4
5.1
3
2.5
2
1.5
4.8
4.5
1
4.2
0.5
3.9
-60
-40
-20
0
20
40
60
TA(qC)
80
100
120
0
-60
140
Figure 13. ICC vs. Temperature
-40
-20
0
20
40 60
TA(qC)
80
100 120 140 160
Figure 14. Input Bias Current vs. Temperature
0.3
4.2
CL=0pF, RL=10k:
CL=0pF, RL=50:
CL=200nF, RL=10k:
CL=200nF, RL=50:
3.9
3.6
3.3
VCC=5V Positive Transition
VCC=12V Positive Transition
VCC=5V Negative Transition
VCC=12V Negative Transition
0.28
0.26
0.24
SR (V/Ps)
3
Volts (V)
0.5
2.7
2.4
2.1
0.22
0.2
0.18
1.8
0.16
1.5
0.14
1.2
0.9
0
10
20
30
40
50
t(Ps)
60
70
VCC = 5.0 V
80
90
100
0.12
-60
-40
0
20
40
60
TA(qC)
80
100
120
140
VCC =5.0 V
Figure 15. Slew Rate
8
-20
Figure 16. Slew Rate vs. Temperature
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Typical Characteristics (continued)
TA= 25°C and VCC = VCC_O(X)
-65
-20
RL=100:
RL=10k:
RL=100:
RL=10k:
-70
THD+N (dB)
THD+N (dB)
-40
-60
-75
-80
-80
-85
-100
20 30 50 70100
200
500 1000 2000
Frequency (Hz)
Av = 2V/V
-90
20 30 50 70100
5000 1000020000
Vo = 8Vpp
500 1000 2000
Frequency (Hz)
Av = 1V/V
Figure 17. THD + Noise (Vcc = 12 V)
5000 1000020000
Vo = 1Vpp
Figure 18. THD + Noise (Vcc = 5 V)
20%
0.4
VCC=5V
VCC=12V
0.2
Percent of Amplifiers (%)
0
-0.2
VIOS (mV)
200
-0.4
-0.6
-0.8
-1
15%
10%
5%
-1.2
6
2
3.
8
3.
2.
2
2.
4
6
2
1.
8
Vcm = Vcc/2
Figure 20. Offset Voltage Production Distribution
Figure 19. Input Offset vs. Temperature
80
1000
75
600MHz
70
65
EMIRRV_PEAK(dB)
Voltage noise (nV/—Hz)
1.
Offset Voltage (mV)
Vcc =12 V and 5 V
Vcm = Vcc/2
0.
140
0
120
4
100
0.
80
.4
-2
-1
.6
-1
.2
-0
.8
-0
.4
40
60
TA(qC)
-2
20
.2
0
-2
-20
.8
0
-40
-3
-1.4
-60
100
1GHz
100MHz
60
55
50
300MHz
33MHz
45
40
35
30
10MHz
25
20
10
100
1000
Frequency (Hz)
10000
100000
20
-30
Figure 21. . Input Voltage Noise Spectral Density vs.
Frequency
-25
-20
-15
-10
-5
RF Input Peak Voltage (dBVp)
0
Figure 22. EMIRR vs. Power
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9 Detailed Description
9.1 Overview
ALM2402Q1 is a dual power opamp with features and performance that make it preferable in many applications.
Its high voltage tolerance, low offset and drift make it optimal in sensing applications. While its current limiting
and over temperature detection make it very robust in applications that drive analog signal off of the PCB on to
wires that are susceptible to faults from the outside world.
This device is optimal for applications that require high amounts of power. Its rail to rail output, enabled by the
low Rdson PMOS and NMOS transistors keep the power dissipation low. The small 3mm x 3mm DRR package
with its thermal pad and low θJA also allows users to deliver high currents to loads.
Other key features this device offers is its separate output driver supply (for external high-side current limit
adjustability), wide stability range (with good phase margin up to 1uF) and shutdown capability (for applications
that need low Icc).
9.2 Functional Block Diagram
Vcc
10
PMOS Current
Limiting and
Biasing
+
1
OTA
EMI
Rejection
11
-
2
NMOS Current
Limiting and
Biasing
EN
EN
12
3
Vcc
Internal
Thermal Detection
Circuitry
Vcc
8
PMOS Current
Limiting and
Biasing
+
4
OTA
EMI
Rejection
5
9
7
NMOS Current
Limiting and
Biasing
-
EN
6
Figure 23. Functional Block Diagram
10
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9.3 Feature Description
9.3.1 OTF/SH_DN
The OTF/SH_DN pin is a bidirectional pin that will allow the user to put both opamps in to a low Iq state
(<500µA) when forced low or below VIL_OTF. Due to this pin being bidirectional and it's Enable/Disable
functionality, it must be pulled high or above VIH_OTF through a pullup resistor in order for the opamp to function
properly or within the specs guaranteed in Electrical Characteristics.
When the junction temperature of ALM2402Q1 crosses the limits specified in Electrical Characteristics, the
OTF/SH_DN pin will go low to alert the application that the both output have turned off due to an over
temperature event. Also, the OTF pin will go low if VCC_O1 and VCC_O2 are 0 V.
When OTF/SH_DN is pulled low and the opamps are shutdown, the opamps will be in open-loop even when
there is negative feedback applied. This is due to the loss of open loop gain in the opamps when the biasing is
disabled. Please see Open Loop and Closed Loop for more detail on open and close loop considerations.
9.3.2 Supply Voltage
ALM2402Q1 uses three power rails. VCC powers the opamp signal path (OTA) and protection circuitry and
VCC_O1 and VCC_O2 power the output high side driver.. Each supply can operate at separate voltages levels
(higher or lower). The min and max values listed in Electrical Characteristics table are voltages that will enable
ALM2402Q1 to properly function at or near the specification listed in Electrical Characteristics table. The
specification listed in this table are guaranteed for 5 V and 12 V.
9.3.3 Current Limit and Short Circuit Protection
Each opamp in ALM2402Q1 has seperate internal current limiting for the PMOS (high-side) and NMOS (lowside) output transistors. If the output is shorted to ground then the PMOS (high-side) current limit is activated and
will limit the current to 750mA nominally (see Electrical Characteristics) or to values shown in Figure 6 over
temperature. If the output is shorted to supply then the NMOS (low-side) current limit is activated and will limit the
current to 550mA nominally (see Electrical Characteristics) or to values shown in Figure 5 over temperature. The
current limit value decreases with increasing temperature due to the temperature coefficient of a base-emitter
junction voltage. Similarly, the current limit value increases at low temperatures.
A programmable current limit for short to ground scenarios can be achieved by adding resistance between
VCC_O(X) and the supply (or battery).
When current is limited, the safe limits for the die temperature (see Recommended Operating Conditions and
Absolute Maximum Ratings) must be taken in to account. With too much power dissipation, the die temperature
can surpass the thermal shutdown limits and the opamp will shutdown and reactivate once the die has fallen
below thermal limits. However, it is not recommended to continuously operate the device in thermal hysteresis for
long periods of time (see Absolute Maximum Ratings).
9.3.4 Input Common Mode Range and Overvoltage Clamps
ALM2402Q1's input common mode range is between 0.2V and VCC-1.2V (see Electrical Characteristics).
Staying withing this range will allow the opamps to perform and operate within the specification listed in Electrical
Characteristics. Operating beyond these limits can cause distortion and non-linearities.
In order for the inputs to tolerate high voltages in the event of a short to supply, zener diodes have been added
(see Figure 24). The current into this zener is limited via internal resistors. When operating near or above the
zener voltage (7 V), the additional voltage gain error caused by the mismatch in internal resistors must be taken
in to account. In unity gain, the opamp will force both gate voltages to be equal to the zener voltage on the
positive input pin and ideally both zeners will sink the same amount of current and force the output voltage to be
equal to Vin. In reality, RN and RP and VZ between both zener diodes do not perfectly match and have some %
difference between their values. This leads to the output being Vo=Vin*(ΔR + ΔVZ) .
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Feature Description (continued)
½
ALM2402
RN
+
RP
VIN
+
–
Figure 24. Schematic Including Input Clamps
9.3.5 Thermal Shutdwon
If the die temperature exceeds safe limits, all outputs will be disabled, and the OTF/SH_DN pin will be driven low.
Once the die temperature has fallen to a safe level, operation will automatically resume. The OTF/SH_DN pin will
be released after operation has resumed.
When operating the die at a high temperature, the opamp will toggle on and off between the thermal shutdown
hysteresis. In this event the safe limits for the die temperature (see Recommended Operating Conditions and
Thermal Information) must be taken in to account. It is not recommended to continuously operate the device in
thermal hysteresis for long periods of time (see Recommended Operating Conditions).
9.3.6 Output Stage
Designed as a high voltage, high current operational amplifier, the ALM2402Q1 device delivers a robust output
drive capability. A class AB output stage with common-source transistors is used to achieve full rail-to-rail output
swing capability. For resistive loads up to 10 kΩ, the output swings typically to within 5 mV of either supply rail
regardless of the power-supply voltage applied. Different load conditions change the ability of the amplifier to
swing close to the rails; refer to the graphs in Typical Characteristics section.
Each output transistor has internal reverse diodes between drain and source that will conduct if the output is
forced higher than the supply or lower than ground (reverse current flow). Users may choose to use these as
flyback protection in inductive load driving applications. Figure 7 show I-V characteristics of both diodes. It is
recommended to limit the use of these diodes to pulsed operation to minimize junction temperature overheating
due to (VF*IF). Internal current limiting circuitry will not operate when current is flown in the reverse direction and
the reverse diodes are active.
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Feature Description (continued)
9.3.7
EMI Susceptibility and Input Filtering
Op-amps vary with regard to the susceptibility of the device to electromagnetic interference (EMI). If conducted
EMI enters the op-amp, the dc offset observed at the amplifier output may shift from the nominal value while EMI
is present. This shift is a result of signal rectification associated with the internal semiconductor junctions. While
all op-amp pin functions can be affected by EMI, the signal input pins are likely to be the most susceptible. The
ALM2402Q1 device incorporates an internal input low-pass filter that reduces the amplifiers response to EMI.
Both common-mode and differential mode filtering are provided by this filter.
Texas Instruments has developed the ability to accurately measure and quantify the immunity of an operational
amplifier over a broad frequency spectrum extending from 10 MHz to 990 MHz. The EMI rejection ratio (EMIRR)
metric allows op-amps to be directly compared by the EMI immunity. Figure 22 shows the results of this testing
on the ALM2402Q1 device. Detailed information can also be found in the application report, EMI Rejection Ratio
of Operational Amplifiers (SBOA128), available for download from www.ti.com
9.4 Device Functional Modes
9.4.1 Open Loop and Closed Loop
Due to its very high open loop DC gain, the ALM2402Q1 will function as a comparator in open loop for most
applications. As noted in Electrical Characteristics table, the majority of electrical characteristics are verified in
negative feedback, closed loop configurations. Certain DC electrical characteristics, like offset, may have a
higher drift across temperature and lifetime when continuously operated in open loop over the lifetime of the
device.
9.4.2 Shutdown
When the OTF/SH_DN pin is left floating or is grounded, the opamp will shutdown to a low Iq state and will not
operate. The opamp outputs will go to a high impedance state. Please see OTF/SH_DN for more detailed
information on OTF/SH_DN pin.
Table 1. Shutdown Truth Table
Logic State
OTF/SH_DN
Opamp State
High ( > VIH_OTF see Recommended Operating Conditions)
Operating
Low ( < VIL_OTF see Recommended Operating Conditions)
Shutdown (low Iq state)
10 Applications and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
10.1 Application Information
ALM2402Q1 is a dual power opamp with performance and protection features that are optimal for many
applications. As it is an opamp, there are many general design consideration that must taken into account. Below
will describe what to consider for most closed loop applications and gives a specific example of ALM2402Q1
being used in a motor drive application.
10.1.1 Capacitive Load and Stability
The ALM2402Q1 device is designed to be used in applications where driving a capacitive load is required. As
with all op-amps, specific instances can occur where the ALM2402Q1 device can become unstable. The
particular op-amp circuit configuration, layout, gain, and output loading are some of the factors to consider when
establishing whether or not an amplifier is stable in operation. An op-amp in the unity-gain (1 V/V) buffer
configuration that drives a capacitive load exhibits a greater tendency to be unstable than an amplifier operated
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Application Information (continued)
at a higher noise gain. The capacitive load, in conjunction with the op-amp output resistance, creates a pole
within the feedback loop that degrades the phase margin. The degradation of the phase margin increases as the
capacitive loading increases. When operating in the unity-gain configuration, the ALM2402Q1 device remains
stable with a pure capacitive load up to approximately 3µF. The equivalent series resistance (ESR) of some very
large capacitors (CL greater than 1 μF) is sufficient to alter the phase characteristics in the feedback loop such
that the amplifier remains stable. Increasing the amplifier closed-loop gain allows the amplifier to drive
increasingly larger capacitance. This increased capability is evident when observing the overshoot response of
the amplifier at higher voltage gains.
One technique for increasing the capacitive load drive capability of the amplifier operating in a unity-gain
configuration is to insert a small resistor, typically 100mΩ to 10Ω, in series with the output (RS), as shown in
Figure 25. This resistor significantly reduces the overshoot and ringing associated with large capacitive loads.
V+
RS
VOUT
+
VIN
RL
+
–
CL
Figure 25. Capacitive Load Drive
3.8
3.8
3.6
3.6
3.4
3.4
3.2
3.2
Vout (V)
Vout (V)
Below are application curves displaying the step response of the above configuration with CL = 2.2 µF, RL = 10
MΩ and RL = 100 Ω. Displaying the ALM2402Q1's good stability performance with big capacitive loads.
3
2.8
2.8
2.6
2.6
2.4
2.4
2.2
2.2
0
10
20
30
40
50
t (Ps)
60
70
80
90
0
10
20
30
40
50
60
70
80
90
t (s)
Figure 26. Output Pulse Response (CL = 2.2 µF and RL =
10 MΩ)
14
3
Figure 27. Output Pulse Response (CL = 2.2 µF and RL =
100 Ω)
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10.2 Typical Application
R2
R1
Resolver
+
Rotor
COSINE
Sensing
Coil
Excitation Coil
Vbias
ALM2402Q1
+
SINE
Sensing
Coil
SIN +
excite -
CBL
V+
V-
excite +
V+
V-
ADC
ADC
DAC
SIN -
COS +
R4
COS -
CBL
R3
PGA410x
Resolver to Digital
Converter
Figure 28. ALM2402Q1 in Resolver Application
High power AC and BLDC motor drive applications need angular and position feedback in order to efficiently and
accurately drive the motor. Position feedback can be achieved by using optical encoders, hall sensors or
resolvers. Resolvers are the go to choice when environmental or longevity requirements are challenging and
extensive.
A resolver acts like a transformer with one primary coil and two secondary coils. The primary coil, or excitation
coil, is located on the rotor of the resolver. As the rotor of the resolver spins, the excitation coil induces a current
into the sine and cosine sensing coils. These coils are oriented 90 degrees from one another and produce a
vector position read by the resolver to digital converter chip.
Resolver excitation coils can have a very low DC resistance (<100 Ω), causing a need of to sink and source up
to 200 mA from the excitation driver. The ALM2402Q1 can source and sink this current while providing current
limiting and thermal shutdown protection. Incorporating these protections in a resolver design can increase the
life of the end product.
The fundamental design steps and ALM2402Q1 benefits shown in this application example can be applied to
other inductive load applications like DC and servo motors. For more information on other applications that
ALM2402Q1 offers a solution to please see (SLVA696), available for download from www.ti.com.
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Typical Application (continued)
10.2.1 Design Requirements
For this design example, use the parameters listed in Table 2 as the input parameters.
Table 2. Design Parameters
DESIGN PARAMETER
EXAMPLE VALUE
Ambient Temperature Range
-40°C to 125°C
Available Supply Voltages
12 V, 5 V, 3.3 V
EMC Capacitance (CL)
100 nF
Excitation Input Voltage Range
2 Vrms - 7 Vrms
Excitation Frequency
10 kHz
10.2.2 Detailed Design Procedure
When using ALM2402Q1 in a resolver application, determine:
• Resolver Excitation Input Impedance or Resistance and Inductance: ZO= 50 + j188; (R = 50 Ω and L = 3 mH)
• Resolver Transformation Ration (VEXC/VSINCOS): 0.5 V/V at 10 kHz
• Package and θJA : DRR, 39.2°C/W
• Opamp Maximum Junction Temperature: 150ºC
• Opamp Bandwidth: 600 kHz
10.2.2.1 Resolver Excitation Input (Opamp Output)
Like a transformer, a resolver needs an alternating current input to function properly. The resolver takes this
alternating current from the primary coil (excitation input) and creates a multiple of it on the secondary sides
(SIN, COS ports). When determining how to generate this alternating current it is important to understand an
opamp's ability or limitations. For the excitation input, the resolver input impedance, stability RMS voltage and
desired frequency must be taken in to account:
10.2.2.1.1 Excitation Voltage
For this example, the resolver impedance is specified between 2Vrms and 7Vrms up 20kHz maximum frequency.
Since, the resolver attenuation is ~0.5V/V and most data acquisition microelectronics run off of 5V supply
voltages. An excitation input of 6Vpp (or 2.12Vrms) will be chosen to give the output readout circuitry enough
headroom to measure the secondary side outputs (~3Vpp).
The excitation coil can be driven by a single-ended opamp output with the other side of the coil grounded or
differentially as shown in Figure 28. Differential drive offers higher peak to peak voltage (double) on to the
excitation coil, while not using up as much output voltage headroom from the opamp. Leading to lower distortion
on the output signal.
Another consideration for excitation is opamp power dissipation. As described in Power Dissipation and Thermal
Reliability, power dissipation from the opamp can be lowered by driving the output peak voltages close to the
supply and ground voltages. With ALM2402Q1's very low VOH/VOL, this can be easily accomplished. Please see
Figure 1 for VOH/VOL values with respect to output current and Output Stage for further description of the rail-rail
output stage.
10.2.2.1.2 Excitation Frequency
The excitation frequency is chosen based on the desired secondary side output signal resolution. As shown in
Figure 34, the excitation signal is similar to a sampling pulse in ADCs, with the real information being in the
envelope created by the rotor. With a GBW of 600kHz, ALM2402Q1 has more than enough open loop gain at
10kHz to create negligible closed loop gain error.
Along with GBW, ALM2402Q1 has optimal THD and SR performance (see Typical Characteristics) to achieve
6Vpp (or 3Vpp from each opamp). The signal integrity can also be observed in the Typical Characteristics
section.
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10.2.2.1.3 Excitation Impedance
Knowledge of the primary side impedance is very important when chosing an opamp for this application. As
shown below in Figure 29, the excitation coil looks like an inductance in series with a resistance. Many time
these values aren't given and must by calculated from the cartesian or polar form, as it is given as a function of
frequency or phase angle. This calculation is a trivial task.
Once the coil resistance is determined, the maximum or peak-peak current needed from ALM2402Q1 can be
determined by below:
IOUT =
VPP
REXC
(1)
In this example the peak-peak output current equates to ~120mA. Each opamp will handle the peak current, with
one sinking max and the other sourcing. Knowledge of the opamp current is very important when determining
ALM2402Q1's power dissipation. Which is discussed in the Power Dissipation and Thermal Reliability section.
R2
LEXC
RL
CEMC
R1
+
Excitation Coil
Model
RCRS
ALM2402Q1
Vbias
CCRS
+
R3
CEMC
R4
Figure 29. Excitation Coil Implementation
The primary side of a resolver is inductive, but that typically is not all the opamps driving the coils see. As shown
in , many times designers will add a resistor in series with a capacitor to illiminate crossover distortion. Which
happens due to the biasing of BJTs in the discrete implementation. With ALM2402Q1's rail-rail output, this is
rarely needed. This can be seen in the waveforms shown in the section.
It is also common practice to add EMC capacitors to the opamp outputs to help shield other devices on the PCB
from the radiation created by the motor and resolver. When choosing CEMC, it ismportant to take the opamp's
stability in to account. With ALM2402Q1 having bery good phase margin at and above 200nF, no stability issues
will be present for many typical CEMC values.
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10.2.2.2 Resolver Output
As mentioned in the Excitation Frequency section, the excitation signal is similar to a sampling pulse in ADCs,
with the real information being in the envelope created by the rotor. The equations below show the behavior of
the sin and cos outputs. Whereby the excitation signal is attenuated and enveloped by the voltage created from
the electromagnetic response of the rotating rotor. The resolver analog output to digital converter will filter out the
excitation signal and process the sine and cosine angles produced by the rotor. Hince, signal intergity or the sine
and cosine envelope is most important in resolver design and some trade-offs in signal integrity of the excitation
signal can be made for cost or convenience. Many times users can use a square wave or sawtooth signal to
accomplish excitation, as opposed to a sine wave.
VEXC = VPP ´ sin (2πft )
(2)
VSIN = TR ´ VPP ´ sin (2πft )´ sin(θ)
(3)
VCOS = TR ´ VPP ´ sin (2πft )´ cos(θ)
(4)
10.2.2.3 Power Dissipation and Thermal Reliability
Very critical aspects to many industrial and automotive applications are operating temperature and power
dissipation. Resolvers are typically chosen over other position feedback techniques due to their sustainability and
accuracy in harsh conditions and very high temperatures.
Along with the resolver, the electronics used in this system must be able to withstand these conditions.
ALM2402Q1 is Q100 qualified and is able to operate at temperatures up to 125°C. In order to insure that this
device can withstand these temperatures, the internal power dissipation must be determined.
The total power dissipation from ALM2402Q1 in this application is the sum of the power from the input supply
and output supplies.
Input
Supply
Power
Output
Supply
Power
Load
Power
PD = PSS + (PSSO - PL )
(5)
As shown in the equation below. PSS is a function of the internal supply and operating current of both opamps
(ICC). With this opamp being CMOS, the ICC will not increase proportionally to the load like a BJT based design.
It will stay close to the average value listed in Electrical Characteristics.
PD = VCC ´ ICC + (VCCO(X) - VOUT (RMS))´ IOUT (RMS)
For more information on this and calculating and measuring power dissipation with complex loads, please refer
to (SBOA022), available for download from www.ti.com
(6)
3 V ö 60 mA
æ
PD = 12 V ´ 5 mA + ç 12 V = 480 mW
÷´
2ø
2
è
(7)
As shown inFigure 30, the load current will flow out of one opamp, through the load and in to the other. Each
opamp shares the same load at 180° phase difference. The PMOS and NMOS output transistors are resistive
when driven near supply and ground. Operating the output voltage at a high percentage of the supply voltage will
greatly limit the chip power dissipation. The Typical Characteristics section gives more information on the
expected voltage drop, that can be used to determine the limits of VOUT.
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Vcco1
Vcc
10
PMOS Current
Limiting and
Biasing
+
1
OTA
EMI
Rejection
VO1
11
NMOS Current
Limiting and
Biasing
-
2
IL*sin(ωt+180° )
EN
EN
12
3
Vcc
Internal
Thermal Detection
Circuitry
8
PMOS Current
Limiting and
Biasing
+
OTA
EMI
Rejection
7
VO2
NMOS Current
Limiting and
Biasing
-
5
Vcco2
IL *sin(ωt)
Vcc
4
9
EN
6
Figure 30. ALM2402Q1 Current Flow
After the total power dissipation is determined, the junction temperature at the worst expected ampient
temperature case must be determined. This can be determined by Equation 9 below or from Figure 31.
TJ (MAX ) = PD ´ θJA + TA( MAX )
TJ(MAX) = 480 mW ´ 39.2
(8)
°C
+ 125°C = 143.8°C
W
Where:
TJ(MAX) is the target maximum junction temperature. → 150°C
TA is the operating ambient temperature. → 125°C
θJA is the package junction to ambient thermal resistance. → 39.2°C/W
(9)
For this example, the maximum junction temperature equates to ~144ºC which is in the safe operating region,
below the maximum junction temperature of 150°C. It is required to limit ALM2402Q1's die junction temperature
to less than 150°C. Please see Absolute Maximum Ratings table for further detail.
Allowable Power Dissipation (W)
5
4.5
4
3.5
3
2.5
2
1.5
1
0.5
-40
-20
0
20
40
60
TA(qC)
80
100
120
140
Maximum power dissipation is a function of TJ(max), θJA, and TA. The maximum allowable power dissipation at any
allowable ambient temperature is PD = (TJ(max) – TA)/θJA. Operating at the absolute maximum TJ of 150°C can affect
reliability.
Figure 31. Maximum Power Dissipation vs Temperature (DRR)
10.2.2.3.1 Improving Package Thermal Performance
θJA value depends on the PC board layout. An external heat sink and/or a cooling mechanism, like a cold air fan,
can help reduce θJA and thus improve device thermal capabilities. Refer to TI’s design support web page at
www.ti.com/thermal for a general guidance on improving device thermal performance.
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10.2.3 Application Curves
Below is test data with ALM2402Q1 exciting TE Connectivity (V23401-D1001-B102) Hollow Shaft Resolver.
Table 3. Waveform Legend
Waveform Color
Description
Green
SINE output
Blue
COSINE output
Red
Excitation positive terminal inputs (referenced to ground)
Purple
Excitation negative terminal inputs (referenced to ground)
The peak-peak excitation voltage is the difference between the
green and blue voltages
Figure 32. Resolver Excitation VEXC ≈ 6 Vpp 10 kHz
The peak-peak excitation voltage is the difference between the
green and blue voltages
Figure 33. Resolver Excitation VEXC≈6Vpp at 10 kHz
(ZOOM)
The peak-peak excitation voltage is the difference between the green and blue voltages
Figure 34. Resolver Excitation VEXC≈4Vpp at 20 kHz
11 Power Supply Recommendations
The ALM2402Q1 device is recommended for continuous operation from 4.5V to 16V (±2.25V to ±8.0V) for Vcc
and 3.0V to 16V (±1.5V to ±8.0V) for Vcc_o(x); many specifications apply from –40°C to 125°C. The Typical
Characteristics presents parameters that can exhibit significant variance with regard to operating voltage or
temperature.
CAUTION
Supply voltages larger than 18V can permanently damage the device (see Absolute
maximum Ratings).
Place 0.1-μF bypass capacitors close to the power-supply pins to reduce errors coupling in from noisy or high
impedance power supplies. For more detailed information on bypass capacitor placement, refer to the Layout
Guidelines section.
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12 Layout
12.1 Layout Guidelines
•
•
•
•
For best operational performance of the device, use good PCB layout practices, including:
Noise can propagate into analog circuitry through the power pins of the circuit as a whole, as well as the
operational amplifier. Bypass capacitors are used to reduce the coupled noise by providing low impedance
power sources local to the analog circuitry.
– Connect low-ESR, 0.1-μF ceramic bypass capacitors between each supply pin and ground, placed as
close to the device as possible. A single bypass capacitor from V+ to ground is applicable for single
supply applications.
Separate grounding for analog and digital portions of circuitry is one of the simplest and most-effective
methods of noise suppression. One or more layers on multilayer PCBs are usually devoted to ground planes.
A ground plane helps distribute heat and reduces EMI noise pickup. Make sure to physically separate digital
and analog grounds, paying attention to the flow of the ground current. For more detailed information, refer to
Circuit Board Layout Techniques, (SLOA089).
To reduce parasitic coupling, run the input traces as far away from the supply or output traces as possible. If
it is not possible to keep them separate, it is much better to cross the sensitive trace perpendicular as
opposed to in parallel with the noisy trace.
Keep the length of input traces as short as possible. Always remember that the input traces are the most
sensitive part of the circuit.
12.2 Layout Example
This layout does not verify optimum thermal impedance performance. Refer to TI’s design support web page at
www.ti.com/thermal for a general guidance on improving device thermal performance.
Figure 35. ALM2402Q1 Layout Example
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13 Device and Documentation Support
13.1 Trademarks
All trademarks are the property of their respective owners.
13.2 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
13.3 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
14 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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Product Folder Links: ALM2402-Q1
PACKAGE OPTION ADDENDUM
www.ti.com
6-Apr-2015
PACKAGING INFORMATION
Orderable Device
Status
(1)
ALM2402QDRRRQ1
ACTIVE
Package Type Package Pins Package
Drawing
Qty
SON
DRR
12
3000
Eco Plan
Lead/Ball Finish
MSL Peak Temp
(2)
(6)
(3)
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
Op Temp (°C)
Device Marking
(4/5)
-40 to 125
ALM24Q
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3)
MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4)
There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5)
Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead/Ball Finish - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead/Ball Finish values may wrap to two lines if the finish
value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
Samples
PACKAGE OPTION ADDENDUM
www.ti.com
6-Apr-2015
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
3-Apr-2015
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
ALM2402QDRRRQ1
Package Package Pins
Type Drawing
SON
DRR
12
SPQ
Reel
Reel
A0
Diameter Width (mm)
(mm) W1 (mm)
3000
330.0
12.4
Pack Materials-Page 1
3.3
B0
(mm)
K0
(mm)
P1
(mm)
3.3
1.1
8.0
W
Pin1
(mm) Quadrant
12.0
Q2
PACKAGE MATERIALS INFORMATION
www.ti.com
3-Apr-2015
*All dimensions are nominal
Device
Package Type
Package Drawing
Pins
SPQ
Length (mm)
Width (mm)
Height (mm)
ALM2402QDRRRQ1
SON
DRR
12
3000
367.0
367.0
35.0
Pack Materials-Page 2
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