Elantec EL4095 Video gain control/fader/multiplexer Datasheet

Video Gain Control/Fader/Multiplexer
Features
General Description
# Full function video fader
# 0.02%/0.02§ differential gain/
phase @ 100% gain
# 25 ns multiplexer included
# Output amplifier included
# Calibrated linear gain control
# g 5V to g 15V operation
# 60 MHz bandwidth
# Low thermal errors
The EL4095C is a versatile variable-gain building block. At its
core is a fader which can variably blend two inputs together and
an output amplifier that can drive heavy loads. Each input appears as the input of a current-feedback amplifier and with external resistors can separately provide any gain desired. The
output is defined as:
Video faders/wipers
Gain control
Graphics overlay
Video text insertion
Level adjust
Modulation
Temp. Range
Package
OutlineÝ
EL4095CN b 40§ C to a 85§ C 14 Pin P-DIP MDP0031
EL4095CS b 40§ C to a 85§ C SO-14
where A and B are the fed-back gains of each channel.
Signal bandwidth is 60 MHz, and gain-control bandwidth
20 MHz. The gain control recovers from overdrive in only
70 ns.
Ordering Information
Part No.
VOUT e A*VINA (0. 5V a VGAIN) a B*VINB (0.5V–VGAIN),
Additionally, two logic inputs are provided which each override
the analog VGAIN control and force 100% gain for one input
and 0% for the other. The logic inputs switch in only 25 ns and
provide high attenuation to the off channel, while generating
very small glitches.
Applications
#
#
#
#
#
#
EL4095C
EL4095C
MDP0027
The EL4095C operates from g 5V to g 15V power supplies, and
is available in both 14-pin DIP and narrow surface mount packages.
Connection Diagram
14-Pin DIP, SO
Manufactured under U.S. Patent No. 5,321,371, 5,374,898
Note: All information contained in this data sheet has been carefully checked and is believed to be accurate as of the date of publication; however, this data sheet cannot be a ‘‘controlled document’’. Current revisions, if any, to these
specifications are maintained at the factory and are available upon your request. We recommend checking the revision level before finalization of your design documentation.
© 1992 Elantec, Inc.
August 1996 Rev D
4095 – 1
Top View
EL4095C
Video Gain Control/Fader/Multiplexer
Supply Voltage
Voltage between VS a and VSb
Input Voltage
a 18V
a 33V
(VSb) b0.3V
to (VS a ) a 0.3V
Current Into bVINA, bVINB
Input Voltage
Input Voltage
b 1V to a 6V
VFORCE Input Voltage
g 35 mA
IOUT
Output Current
b 40§ C to a 85§ C
TA
Operating Temperature Range
TJ
Operating Junction Temperature
0§ C to a 150§ C
b 65§ C to a 150§ C
TST
Storage Temperature Range
Internal Power Dissipation
See Curves
5 mA
VGAIN g 5V
VSb to VS a
TD is 0.7in
Absolute Maximum Ratings (TA e 25§ C)
VS a
VS
a VINA,
a VINB
IIN
VGAIN
VGAIN
Important Note:
All parameters having Min/Max specifications are guaranteed. The Test Level column indicates the specific device testing actually
performed during production and Quality inspection. Elantec performs most electrical tests using modern high-speed automatic test
equipment, specifically the LTX77 Series system. Unless otherwise noted, all tests are pulsed tests, therefore TJ e TC e TA.
Test Level
I
II
III
IV
V
Test Procedure
100% production tested and QA sample tested per QA test plan QCX0002.
100% production tested at TA e 25§ C and QA sample tested at TA e 25§ C ,
TMAX and TMIN per QA test plan QCX0002.
QA sample tested per QA test plan QCX0002.
Parameter is guaranteed (but not tested) by Design and Characterization Data.
Parameter is typical value at TA e 25§ C for information purposes only.
Open Loop DC Electrical Characteristics
Parameter
Limits
Description
Min
Typ
Max
Test
Level
Units
mV
VOS
Input Offset Voltage
1.5
5
I
IB a
a VIN Input Bias Current
5
10
I
mA
IBb
b VIN Input Bias Current
10
50
I
mA
CMRR
Common Mode Rejection
I
dB
b CMRR
b VIN Input Bias Current
I
mA/V
I
dB
I
mA/V
I
MX
65
0.5
Common Mode Rejection
PSRR
Power Supply Rejection Ratio
b IPSR
b VIN Input Current
65
Transimpedance
RINb
b VIN Input Resistance
VIN
a VIN Range
VO
Output Voltage Swing
ISC
Output Short-Circuit Current
VIH
Input High Threshold at
Force A or Force B Inputs
VIL
Input Low Threshold at
Force A or Force B Inputs
IFORCE, High
Input Current of Force A
or Force B, VFORCE e 5V
IFORCE, Low
Input Current of Force A
or Force B, VFORCE e 0V
0.2
1.5
95
0.2
Power Supply Rejection Ratio
ROL
80
2
0.4
V
X
(Vb) a 3.5
(V a ) b3.5
I
V
(Vb) a 2
(V a ) b2
I
V
160
I
mA
2.0
I
V
I
V
b 50
I
mA
b 650
I
mA
80
80
125
0.8
b 440
2
TD is 4.0in
VS e g 15V, TA e 25§ C, VGAIN ground unless otherwise specified
EL4095C
Video Gain Control/Fader/Multiplexer
Open Loop DC Electrical Characteristics Ð Contd.
Parameter
Limits
Description
Min
Typ
60
75
Max
Test
Level
Units
I
dB
Feedthrough,
Forced
Feedthrough of Deselected Input to Output,
Deselected Input at 100% Gain Control
VGAIN, 100%
Minimum Voltage at
VGAIN for 100% Gain
0.45
0.5
0.55
I
V
VGAIN, 0%
Maximum Voltage at
VGAIN for 0% Gain
b 0.55
b 0.5
b 0.45
I
V
NL, Gain
Gain Control Non-linearity,
VIN e g 0.5V
2
4
I
%
RIN, VG
Impedance between VGAIN and VGAIN
5.5
6.5
I
kX
NL, AV e 1
AV e 0.5
AV e 0.25
Signal Non-linearity, VIN e g 1V, VGAIN e 0.55V
Signal Non-linearity, VIN e g 1V, VGAIN e 0V
Signal Non-linearity, VIN e g 1V, VGAIN e b0.25V
0.03
0.07
0.4
V
V
I
%
%
%
IS
Supply Current
17
21
I
mA
4.5
k 0.01
TD is 2.4in
VS e g 15V, TA e 25§ C, unless otherwise specified
Closed Loop AC Electrical Characteristics
Parameter
Limits
Description
Min
SR
Slew Rate; VOUT from b3V to a 3V
Measured at b2V and a 2V
BW
Bandwidth
dG
di
TS
b 3 dB
b 1 dB
b 0.1 dB
Test
Level
Units
330
V
V/ms
60
30
6
V
MHz
MHz
MHz
Typ
Max
Differential Gain; AC Amplitude of 286 mVp-p
at 3.58 MHz on DC Offset of b0.7V, 0V and a 0.7V
AV e 100%
AV e 50%
AV e 25%
0.02
0.07
0.07
V
%
%
%
Differential Phase; AC Amplitude of 286 mVp-p
at 3.58 MHz on DC Offset of b0.7V, 0V and a 0.7V
AV e 100%
AV e 50%
AV e 25%
0.02
0.05
0.15
V
§
§
§
Settling Time to 0.2%; VOUT from b2V to a 2V
AV e 100%
AV e 25%
100
100
V
ns
ns
TFORCE
Propagation Delay from VFORCE e 1.4V to 50%
Output Signal Enabled or Disabled Amplitude
25
V
ns
BW, Gain
b 3 dB Gain Control Bandwidth,
VGAIN Amplitude 0.5 VP-P
20
V
MHz
TREC, Gain
Gain Control Recovery from Overload;
VGAIN from b0.7V to 0V
70
V
ns
3
TD is 3.8in
VS e g 15V, AV e a 1, RF e RIN e 1 kX, RL e 500X, CL e 15 pF, CINb e 2 pF, TA e 25§ C, AV e 100% unless otherwise
noted
EL4095C
Video Gain Control/Fader/Multiplexer
Typical Performance Curves
Large-Signal Pulse
Response Gain e a 1
Large-Signal Pulse
Response Gain e b 1
4095 – 7
4095 – 6
Frequency Response for Different
Gains-AV e a 1
Small-Signal Pulse Response
for Various Gains
4095 – 8
4095 – 9
Frequency Response with Different
Values of RF b Gain e a 1
Frequency Response with Different
Values of RF b Gain e b 1
4095 – 10
4095 – 11
4
EL4095C
Video Gain Control/Fader/Multiplexer
Typical Performance Curves Ð Contd.
Frequency Response with Different Gains
Frequency Response with Various
Load Capacitances and Resistances
Frequency Response with Various
Values of Parasitic CIN b
Input Noise Voltage and
Current vs Frequency
Change in Bandwidth and Slewrate with
Supply Voltage b Gain e a 1
Change in Bandwidth and Slewrate with
Supply Voltage b Gain e b 1
4095 – 12
5
EL4095C
Video Gain Control/Fader/Multiplexer
Typical Performance Curves Ð Contd.
Change in Bandwidth and Slewrate
with Temperature b Gain e a 1
Change in Bandwidth and Slewrate
with Temperature b Gain e b 1
DC Nonlinearity vs Input Voltage
b Gain e a 1
Change in VOS and IB- vs die Temperature
Differential Gain and Phase Errors vs
Gain Control Setting b Gain e a 1
Differential Gain and Phase Errors vs
Gain Control Setting b Gain e b 1
4095 – 13
6
EL4095C
Video Gain Control/Fader/Multiplexer
Typical Performance Curves Ð Contd.
Differential Phase Error vs
DC Offset b Gain e a 1
Differential Phase Error vs
DC Offset b Gain e a 1
Differential Phase Error vs
DC Offset b Gain e b 1
Differential Phase Error vs
DC Offset b Gain e b 1
Attenuation over
Frequency b Gain e a 1
Attenuation over
Frequency b Gain e b 1
4095 – 14
7
EL4095C
Video Gain Control/Fader/Multiplexer
Typical Performance Curves Ð Contd.
Gain Control Gain vs Frequency
Gain vs VG (1 VDC at VINA)
4095 – 15
4095 – 16
Gain Control Response to a Non-Overloading
Step, Constant Sinewave at VINA
VGAIN Overload Recovery Delay
4095 – 18
4095 – 17
VGAIN Overload Recovery
ResponseÐNo AC Input
Cross-Fade Balance b 0V on
AIN and BIN; Gain e a 1
4095 – 19
4095 – 20
8
EL4095C
Video Gain Control/Fader/Multiplexer
Typical Performance Curves Ð Contd.
Change in V100% and
V0% of Gain Control
vs Supply Voltage
Change in V100% and
V0% of Gain Control
vs VGAIN Offset
Change in V100% and
V0% of Gain Control
vs Die Temperature
4095 – 21
Force Response
Force-Induced Output Transient
4095 – 22
4095 – 23
Package Power Dissipation
vs Ambient Temperature
Supply Current vs Supply Voltage
4095 – 25
4095 – 24
9
EL4095C
Video Gain Control/Fader/Multiplexer
Test Circuit, AV e a 1
4095 – 26
10
EL4095C
Video Gain Control/Fader/Multiplexer
Applications Information
Frequency Response
The EL4095 is a general-purpose two-channel
fader whose input channels each act as a currentfeedback amplifier (CFA) input. Each input can
have its own gain factor as established by external resistors. For instance, the Test Circuit shows
two channels each arranged as a 1 gain, with the
traditional single feedback resistor RF connected
from VOUT to the b VIN of each channel.
Like other CFA’s, there is a recommended feedback resistor, which for this circuit is 1 KX. The
value of RF sets the closed-loop b 3 dB bandwidth, and has only a small range of practical
variation. The user should consult the typical
performance curves to find the optional value of
RF for a given circuit gain. In general, the bandwidth will decrease slightly as closed-loop gain is
increased; RF can be reduced to make up for
bandwidth loss. Too small a value of RF will
cause frequency response peaking and ringing
during transients. On the other hand, increasing
RF will reduce bandwidth but improve stability.
The EL4095 can be connected as an inverting
amplifier in the same manner as any CFA:
EL4095C In Inverting Connection
4095 – 27
11
EL4095C
Video Gain Control/Fader/Multiplexer
If maximum bandwidth is not required, distortion can be reduced greatly (and signal voltage
range enlarged) by increasing the value of RF
and any associated gain-setting resistor.
Applications Information Ð Contd.
Stray capacitance at each b VIN terminal should
absolutely be minimized, especially in a positivegain mode, or peaking will occur. Similarly, the
load capacitance should be minimized. If more
than 25 pF of load capacitance must be driven, a
load resistor from 100X to 400X can be added in
parallel with the output to reduce peaking, but
some bandwidth degradation may occur. A
‘‘snubber’’ load can alternatively be used. This is
a resistor in series with a capacitor to ground,
150X and 100 pF being typical values. The advantage of a snubber is that it does not draw DC
load current. A small series resistor, low tens of
ohms, can also be used to isolate reactive loads.
100% Accuracies
When a channel gain is set to 100%, static and
gain errors are similar to those of a simple CFA.
The DC output error is expressed by
VOUT, Offset e VOS* AV a (IB b )*RF.
The input offset voltage scales with fed-back
gain, but the bias current into the negative input,
IB b , adds an error not dependent on gain. Generally, IB b dominates up to gains of about seven.
Distortion
The fractional gain error is given by
The signal voltage range of the a VIN terminals
is within 3.5V of either supply rail.
EGAIN e (RF a AV*RIN b ) RF
a AV RIN)/ROL
One must also consider the range of error currents that will be handled by the b VIN terminals. Since the b VIN of a CFA is the output of a
buffer which replicates the voltage at a VIN, error currents will flow into the b VIN terminal.
When an input channel has 100% gain assigned
to it, only a small error current flows into its negative input; when low gain is assigned to the
channel the output does not respond to the channel’s signal and large error currents flow.
The gain error is about 0.3% for a gain of one,
and increases only slowly for increasing gain.
RIN b is the input impedance of the input stage
buffer, and ROL is the transimpedance of the amplifier, 80 kX and 350 kX respectively.
Gain Control Inputs
The gain control inputs are differential and may
be biased at any voltage as long as VGAIN is less
than 2.5V below V a and 3V above V b . The differential input impedance is 5.5 kX, and a common-mode impedance is more than 500 kX. With
zero differential voltage on the gain inputs, both
signal inputs have a 50% gain factor. Nominal
calibration sets the 100% gain of VINA input at
a 0.5V of gain control voltage, and 0% at b 0.5V
of gain control. VINB’s gain is complementary to
that of VINA; a 0.5V of gain control sets 0% gain
at VINB and b 0.5V gain control sets 100% VINB
gain. The gain control does not have a completely abrupt transition at the 0% and 100% points.
There is about 10 mV of ‘‘soft’’ transfer at the
gain endpoints. To obtain the most accurate
100% gain factor or best attenuation of 0% gain,
it is necessary to overdrive the gain control input
by about 30 mV. This would set the gain control
voltage range as b 0.565 mV to a 0.565V, or
30 mV beyond the maximum guaranteed 0% to
100% range.
Here are a few idealized examples, based on a
gain of a 1 for channels A and B and RF e 1 kX
for different gain settings:
Gain
VINA
VINB
I (bVINA)
I (bVINB)
VOUT
100%
75%
50%
25%
0%
1V
1V
1V
1V
1V
0
0
0
0
0
0
b 250 mA
b 500 mA
b 750 mA
b 1 mA
1 mA
750 mA
500 mA
250 mA
0
1V
0.75V
0.5V
0.25V
0V
Thus, either b VIN can receive up to 1 mA error
current for 1V of input signal and 1 kX feedback
resistors. The maximum error current is 3 mA for
the EL4095, but 2 mA is more realistic. The major contributor of distortion is the magnitude of
error currents, even more important than loading
effects. The performance curves show distortion
versus input amplitude for different gains.
12
EL4095C
Video Gain Control/Fader/Multiplexer
Applications Information Ð Contd.
Force Inputs
In fact, the gain control internal circuitry is very
complex. Here is a representation of the terminals:
The Force inputs completely override the VGAIN
setting and establish maximum attainable 0%
and 100% gains for the two input channels. They
are activated by a TTL logic low on either of the
FORCE pins, and perform the analog switching
very quickly and cleanly. FORCEA causes 100%
gain on the A channel and 0% on the B channel.
FORCEB does the reverse, but there is no defined output state when FORCEA and FORCEB
are simultaneously asserted.
Representation of Gain Control
Inputs VG and VG
The Force inputs do not incur recovery time penalties, and make ideal multiplexing controls. A
typical use would be text overlay, where the A
channel is a video input and the B channel is
digitally created text data. The FORCEA input
is set low normally to pass the video signal, but
released to display overlay data. The gain control
can be used to set the intensity of the digital
overlay.
4095 – 28
For gain control inputs between g 0.5V
( g 90 mA), the diode bridge is a low impedance
and all of the current into VG flows back out
through VG. When gain control inputs exceed
this amount, the bridge becomes a high impedance as some of the diodes shut off, and the VG
impedance rises sharply from the nominal 5.5 KX
to over 500 KX. This is the condition of gain control overdrive. The actual circuit produces a
much sharper overdrive characteristics than does
the simple diode bridge of this representation.
Other Applications Circuits
The EL4095 can also be used as a variable-gain
single input amplifier. If a 0% lower gain extreme is required, one channel’s input should
simply be grounded. Feedback resistors must be
connected to both b VIN terminals; the EL4095
will not give the expected gain range when a
channel is left unconnected.
The gain input has a 20 MHz b 3 dB bandwidth
and 17 ns risetime for inputs to g 0.45V. When
the gain control voltage exceeds the 0% or 100%
values, a 70 ns overdrive recovery transient will
occur when it is brought back to linear range. If
quicker gain overdrive response is required, the
Force control inputs of the EL4095 can be used.
This circuit gives a 0.5 to a 2.0 gain range, and
is useful as a signal leveller, where a constant
output level is regulated from a range of input
amplitudes:
13
EL4095C
Video Gain Control/Fader/Multiplexer
Application Information Ð Contd.
Leveling Circuit with 0.5 s AV s 2
4095 – 29
For video levels, however, these constants can
give fairly high differential gain error. The problem occurs for large inputs. Assume that a
‘‘twice-size’’ video input occurs. The A-side stage
sees the full amplitude, but the gain would be set
to 100% B-input gain to yield an overall gain of
Here the A input channel is configured for a gain
of a 2 and the B channel for a gain of a 1 with
its input attenuated by (/2. The connection is virtuous because the distortions do not increase
monotonically with reducing gain as would the
simple single-input connecton.
14
EL4095C
Video Gain Control/Fader/Multiplexer
RFA could be increased together in value to reduce the error current and distortions, but increasing RFA would lower bandwidth. A solution
would be to simply attenuate the input signal
magnitude and restore the EL4095 output level
to standard level with another amplifier so:
Application Information Ð Contd.
(/2 to produce a standard video output. The
b VIN of the A side is a buffer output that reproduces the input signal, and drives RGA and RFA.
Into the two resistors 2.1 mA of error current
flows for a typical 1.4V of input DC offset, creating distortion in a A-side input stage. RGA and
Reduced-Gain Leveler for Video Inputs and Differential Gain and Phase Performance (see text)
4095 – 30
4095 – 31
15
EL4095C
Video Gain Control/Fader/Multiplexer
than the unrestored possible span of g 0.7V (for
standard-sized signals). For the preceding leveler
circuit, the black level should be set more toward
b 0.7V to accommodate the largest input, or
made to vary with the gain control itself (large
gain, small offset; small gain, larger offset).
Application Information Ð Contd.
Although another amplifier is needed to gain the
output back to standard level, the reduced error
currents bring the differential phase error to less
than 0.1Ê over the entire input range.
A useful technique to reduce video distortion is to
DC-restore the video level going into the EL4095,
and offsetting black level to b 0.35V so that the
entire video span encompasses g 0.35V rather
The EL4095 can be wired as a four quadrant multiplier:
EL4095 Connected as a Four-Quadrant Multiplier
4095 – 32
16
EL4095C
Video Gain Control/Fader/Multiplexer
Application Information Ð Contd.
The two input channels can be connected to a
common input through two dissimilar filters to
create a DC-controlled variable filter. This circuit
provides a controlled range of peaking through
rolloff characteristics:
The A channel gains the input by a 1 and the B
channel by b 1. Feedthrough suppression of the
Y input can be optimized by introducing an offset between channel A and B. This is easily done
by injecting an adjustable current into the summing junction ( b VIN terminal) of the B input
channel.
Variable Peaking Filter
4095 – 33
4095 – 34
17
EL4095C
Video Gain Control/Fader/Multiplexer
package has a thermal resistance of 65§ C/W, and
can thus dissipate 1.15W at a 75§ C ambient temperature. The device draws 20 mA maximum
supply current, only 600 mW at g 15V supplies,
and the circuit has no dissipation problems in
this package.
Applications Information Ð Contd.
The EL4095 is connected as a unity-gain fader,
with an LRC peaking network connected to the
A-input and an RC rolloff network connected to
the B-input. The plot shows the range of peaking
controlled by the VGAIN input. This circuit
would be useful for flattening the frequency response of a system, or for providing equalization
ahead of a lossy transmission line.
The SO-14 surface-mount package has a
105§ C/W thermal resistance with the EL4095,
and only 714 mW can be dissipated at 75§ C ambient temperature. The EL4095 thus can be operated with g 15V supplies at 75§ C, but additional
dissipation caused by heavy loads must be considered. If this is a problem, the supplies should
be reduced to g 5V to g 12V levels.
Noise
The electrical noise of the EL4095 has two components: the voltage noise in series with a VIN is
5 nV 0Hz wideband, and there is a current noise
injected into b VIN of 35 pA0Hz. The output
noise will be
The output will survive momentary short-circuits to ground, but the large available current
will overheat the die and also potentially destroy
the circuit’s metal traces. The EL4095 is reliable
within its maximum average output currents and
operating temperatures.
Vn, out e 0 (AV # Vn, input)2 a (In, input # RF)2,
and the input-referred noise is
Vn, input-referred e 0 (Vn, input)2 a (In, input # RF/AV)2
where AV is the fed-back gain of the EL4095.
Here is a plot of input-referred noise vs AV:
EL4095C Macromodel
This macromodel is offered to allow simulation of
general EL4095 behavior. We have included
these characteristics:
Input-Referred Noise vs Closed-Loop Gain
Small-signal frequency response
Output loading effects
Input impedance
Off-channel feedthrough
Output impedance over
frequency
Signal path DC distoritons
VGAIN I-V characteristics
VGAIN overdrive recovery
delay
100% gain error
FORCE operation
b VIN characteristics and
sensitivity to parasitic
capacitance
These will give a good range of results of various
operating conditions, but the macromodel does
not behave identically as the circuit in these areas:
4095 – 35
Thus, for a gain of three or more the fader has a
noise as good as an op-amp. The only trade-off is
that the dynamic range of the input is reduced by
the gain due to the nonlinearity caused by
gained-up output signals.
Temperature effects
Signal overload effects
Signal and VG operating range
Current-limit
Video and high-frequency
distortions
Glitch and delay from
FORCE inputs
Power Dissipation
Peak die temperature must not exceed 150§ C.
This allows 75§ C internal temperature rise for a
75§ C ambient. The EL4095 in the 14-pin PDIP
18
Manufacturing tolerances
Supply voltage effects
Slewrate limitations
Noise
Power supply interactions
EL4095C
Video Gain Control/Fader/Multiplexer
EL4095C Macromodel Ð Contd.
4095 – 36
19
EL4095C
Video Gain Control/Fader/Multiplexer
EL4095C Macromodel Ð Contd.
4095 – 37
20
EL4095C
Video Gain Control/Fader/Multiplexer
EL4095C Macromodel Ð Contd.
The EL4095 Macromodel Schematic
4095 – 38
21
EL4095C
Video Gain Control/Fader/Multiplexer
EL4095C Macromodel Ð Contd.
4095 – 39
22
23
BLANK
EL4095C
EL4095C
Video Gain Control/Fader/Multiplexer
General Disclaimer
Specifications contained in this data sheet are in effect as of the publication date shown. Elantec, Inc. reserves the right to make changes
in the circuitry or specifications contained herein at any time without notice. Elantec, Inc. assumes no responsibility for the use of any
circuits described herein and makes no representations that they are free from patent infringement.
August 1996 Rev D
WARNING Ð Life Support Policy
Elantec, Inc. products are not authorized for and should not be
used within Life Support Systems without the specific written
consent of Elantec, Inc. Life Support systems are equipment intended to support or sustain life and whose failure to perform
when properly used in accordance with instructions provided can
be reasonably expected to result in significant personal injury or
death. Users contemplating application of Elantec, Inc. products
in Life Support Systems are requested to contact Elantec, Inc.
factory headquarters to establish suitable terms & conditions for
these applications. Elantec, Inc.’s warranty is limited to replacement of defective components and does not cover injury to persons or property or other consequential damages.
Elantec, Inc.
1996 Tarob Court
Milpitas, CA 95035
Telephone: (408) 945-1323
(800) 333-6314
Fax: (408) 945-9305
European Office: 44-71-482-4596
24
Printed in U.S.A.