AD ADA4860-1 High speed, low cost, op amp Datasheet

High Speed, Low Cost,
Op Amp
ADA4860-1
PIN CONFIGURATION
High speed
800 MHz, −3 dB bandwidth
790 V/μs slew rate
8 ns settling time to 0.5%
Wide supply range: 5 V to 12 V
Low power: 6 mA
0.1 dB flatness: 125 MHz
Differential gain: 0.02%
Differential phase: 0.02°
Low voltage offset: 3.5 mV (typ)
High output current: 25 mA
Power down
VOUT 1
–VS 2
+IN 3
+
–
6
+VS
5
POWER DOWN
4
–IN
05709-001
FEATURES
Figure 1. 6-Lead SOT-23 (RJ-6)
APPLICATIONS
Consumer video
Professional video
Broadband video
ADC buffers
Active filters
GENERAL DESCRIPTION
The ADA4860-1 is available in a 6-lead SOT-23 package and
is designed to work over the extended temperature range of
−40°C to +105°C.
G = +2
6.2 VOUT = 2V p-p
RF = RG = 499Ω
6.1
6.0
5.9
VS = +5V
5.8
VS = ±5V
5.7
5.6
5.5
05709-003
The ADA4860-1 is designed to operate on supply voltages as
low as +5 V and up to ±5 V using only 6 mA of supply current.
To further reduce power consumption, the amplifier is
equipped with a power-down feature that lowers the supply
current to 0.25 mA.
6.3
CLOSED-LOOP GAIN (dB)
The ADA4860-1 is a low cost, high speed, current feedback op
amp that provides excellent overall performance. The 800 MHz,
−3 dB bandwidth, and 790 V/μs slew rate make this amplifier
well suited for many high speed applications. With its combination
of low price, excellent differential gain (0.02%), differential
phase (0.02°), and 0.1 dB flatness out to 125 MHz, this amplifier
is ideal for both consumer and professional video applications.
5.4
5.3
0.1
1
10
100
1000
FREQUENCY (MHz)
Figure 2. 0.1 dB Flatness
Rev. 0
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DOCUMENTATION
MT-057: High Speed Current Feedback Op Amps
MT-051: Current Feedback Op Amp Noise Considerations
MT-034: Current Feedback (CFB) Op Amps
MT-059: Compensating for the Effects of Input Capacitance on VFB
and CFB Op Amps Used in Current-to-Voltage Converters
A Stress-Free Method for Choosing High-Speed Op Amps
UG-127: Universal Evaluation Board for High Speed Op Amps in
SOT-23-5/SOT-23-6 Packag
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ADA4860-1
TABLE OF CONTENTS
Features .............................................................................................. 1
Power Supply Bypassing ............................................................ 14
Applications....................................................................................... 1
Feedback Resistor Selection...................................................... 14
Pin Configuration............................................................................. 1
Driving Capacitive Loads.......................................................... 15
General Description ......................................................................... 1
Power Down Pin......................................................................... 15
Revision History ............................................................................... 2
Video Amplifier.......................................................................... 15
Specifications..................................................................................... 3
Single-Supply Operation ........................................................... 15
Absolute Maximum Ratings............................................................ 5
Optimizing Flatness and Bandwidth ....................................... 16
Thermal Resistance ...................................................................... 5
Layout and Circuit Board Parasitics ........................................ 17
ESD Caution.................................................................................. 5
Outline Dimensions ....................................................................... 18
Typical Performance Characteristics ............................................. 6
Ordering Guide .......................................................................... 18
Application Information................................................................ 14
REVISION HISTORY
4/06—Revision 0: Initial Version
Rev. 0 | Page 2 of 20
ADA4860-1
SPECIFICATIONS
VS = +5 V (@ TA = 25°C, G = +2, RL = 150 Ω referred to midsupply, CL = 4 pF, unless otherwise noted). For G = +2, RF = RG = 499 Ω and
for G = +1, RF = 550 Ω.
Table 1.
Parameter
DYNAMIC PERFORMANCE
–3 dB Bandwidth
Bandwidth for 0.1 dB Flatness
+Slew Rate (Rising Edge)
−Slew Rate (Falling Edge)
Settling Time to 0.5%
NOISE/DISTORTION PERFORMANCE
Harmonic Distortion HD2/HD3
Input Voltage Noise
Input Current Noise
Differential Gain
Differential Phase
DC PERFORMANCE
Input Offset Voltage
+Input Bias Current
−Input Bias Current
Open-Loop Transresistance
INPUT CHARACTERISTICS
Input Resistance
Input Capacitance
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
POWER DOWN PIN
Input Voltage
Bias Current
Turn-On Time
Turn-Off Time
OUTPUT CHARACTERISTICS
Output Overdrive Recovery Time (Rise/Fall)
Output Voltage Swing
Short-Circuit Current
POWER SUPPLY
Operating Range
Total Quiescent Current
Quiescent Current
Power Supply Rejection Ratio
+PSR
Conditions
Min
Typ
Max
Unit
VO = 0.2 V p-p
VO = 2 V p-p
VO = 0.2 V p-p, RL = 75 Ω
G = +1, VO = 0.2 V p-p
VO = 2 V p-p
VO = 2 V p-p, RL = 75 Ω
VO = 2 V p-p
VO = 2 V p-p
VO = 2 V step
460
165
430
650
58
45
695
560
8
MHz
MHz
MHz
MHz
MHz
MHz
V/μs
V/μs
ns
fC = 1 MHz, VO = 2 V p-p
fC = 5 MHz, VO = 2 V p-p
f = 100 kHz
f = 100 kHz, +IN/−IN
RL = 150 Ω
RL = 150 Ω
−90/−102
−70/−76
4.0
1.5/7.7
0.02
0.03
dBc
dBc
nV/√Hz
pA/√Hz
%
Degrees
−13
−2
−7
400
−4.25
−1
+1.0
650
−52
10
85
1.5
1.2 to 3.7
−56
MΩ
Ω
pF
V
dB
Enabled
Power down
Enabled
Power down
0.5
1.8
−200
60
200
3.5
V
V
nA
μA
ns
μs
VIN = +2.25 V to −0.25 V
RL = 75 Ω
RL = 150 Ω
RL = 1 kΩ
Sinking and sourcing
60/100
1.2 to 3.8
1 to 4
0.8 to 4.2
45
ns
V
V
V
mA
+IN
−IN
+IN
VCM = 2 V to 3 V
Enabled
POWER DOWN pin = +VS
+VS = 4 V to 6 V, −VS = 0 V
Rev. 0 | Page 3 of 20
1.2 to 3.8
0.9 to 4.1
5
4.5
−60
5.2
0.2
−62
+13
+1
+10
12
6.5
0.5
mV
μA
μA
kΩ
V
mA
mA
dB
ADA4860-1
VS = ±5 V (@ TA = 25°C, G = +2, RL = 150 Ω, CL = 4 pF, unless otherwise noted). For G = +2, RF = RG = 499 Ω and for G = +1, RF = 550 Ω.
Table 2.
Parameter
DYNAMIC PERFORMANCE
–3 dB Bandwidth
Bandwidth for 0.1 dB Flatness
+Slew Rate (Rising Edge)
−Slew Rate (Falling Edge)
Settling Time to 0.5%
NOISE/DISTORTION PERFORMANCE
Harmonic Distortion HD2/HD3
Input Voltage Noise
Input Current Noise
Differential Gain
Differential Phase
DC PERFORMANCE
Input Offset Voltage
+Input Bias Current
−Input Bias Current
Open-Loop Transresistance
INPUT CHARACTERISTICS
Input Resistance
Input Capacitance
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
POWER DOWN PIN
Input Voltage
Bias Current
Turn-On Time
Turn-Off Time
OUTPUT CHARACTERISTICS
Output Overdrive Recovery Time (Rise/Fall)
Output Voltage Swing
Short-Circuit Current
POWER SUPPLY
Operating Range
Total Quiescent Current
Quiescent Current
Power Supply Rejection Ratio
+PSR
−PSR
Conditions
Min
Typ
Max
Unit
VO = 0.2 V p-p
VO = 2 V p-p
VO = 0.2 V p-p, RL = 75 Ω
G = +1, VO = 0.2 V p-p
VO = 2 V p-p
VO = 2 V p-p, RL = 75 Ω
VO = 2 V p-p
VO = 2 V p-p
VO = 2 V step
520
230
480
800
125
70
980
790
8
MHz
MHz
MHz
MHz
MHz
MHz
V/μs
V/μs
ns
fC = 1 MHz, VO = 2 V p-p
fC = 5 MHz, VO = 2 V p-p
f = 100 kHz
f = 100 kHz, +IN/−IN
RL = 150 Ω
RL = 150 Ω
−90/−102
−77/−94
4.0
1.5/7.7
0.02
0.02
dBc
dBc
nV/√Hz
pA/√Hz
%
Degrees
−13
−2
−7
400
−3.5
−1.0
+1.5
700
−55
12
90
1.5
−3.8 to +3.7
−58
MΩ
Ω
pF
V
dB
Enabled
Power down
Enabled
Power down
−4.4
−3.2
−250
130
200
3.5
V
V
nA
μA
ns
μs
VIN = ±3.0 V
RL = 75 Ω
RL = 150 Ω
RL = 1 kΩ
Sinking and sourcing
45/90
±2
±3.1
±4.1
85
ns
V
V
V
mA
+IN
−IN
+IN
VCM = ±2 V
Enabled
POWER DOWN pin = +VS
+VS = +4 V to +6 V, −VS = −5 V
+VS = +5 V, −VS = −4 V to −6 V,
POWER DOWN pin = −VS
Rev. 0 | Page 4 of 20
±2.5
±3.9
5
5
−62
−58
6
0.25
−64
−61
+13
+1
+10
12
8
0.5
mV
μA
μA
kΩ
V
mA
mA
dB
dB
ADA4860-1
ABSOLUTE MAXIMUM RATINGS
Table 3.
The power dissipated in the package (PD) for a sine wave and a
resistor load is the total power consumed from the supply
minus the load power.
Rating
12.6 V
See Figure 3
−VS + 1 V to +VS − 1 V
±VS
−65°C to +125°C
−40°C to +105°C
JEDEC J-STD-20
150°C
PD = Total Power Consumed − Load Power
(
VOUT 2
RL
RMS output voltages should be considered.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Airflow across the ADA4860-1 helps remove heat from the
package, effectively reducing θJA. In addition, more metal
directly in contact with the package leads and through holes
under the device reduces θJA.
Figure 3 shows the maximum safe power dissipation in the
package vs. the ambient temperature for the 6-lead SOT-23
(170°C/W) on a JEDEC standard 4-layer board. θJA values are
approximations.
THERMAL RESISTANCE
Table 4. Thermal Resistance
θJA
170
Unit
°C/W
Maximum Power Dissipation
The maximum safe power dissipation for the ADA4860-1 is
limited by the associated rise in junction temperature (TJ) on
the die. At approximately 150°C, which is the glass transition
temperature, the plastic changes its properties. Even temporarily
exceeding this temperature limit can change the stresses that the
package exerts on the die, permanently shifting the parametric
performance of the amplifiers. Exceeding a junction temperature of
150°C for an extended period can result in changes in silicon
devices, potentially causing degradation or loss of functionality.
MAXIMUM POWER DISSIPATION (W)
2.0
θJA is specified for the worst-case conditions, that is, θJA is
specified for device soldered in circuit board for surface-mount
packages.
Package Type
6-lead SOT-23
)
PD = VSUPPLY VOLTAGE × I SUPPLY CURRENT –
1.5
1.0
0.5
0
–40 –30 –20 –10
05709-002
Parameter
Supply Voltage
Power Dissipation
Common-Mode Input Voltage
Differential Input Voltage
Storage Temperature Range
Operating Temperature Range
Lead Temperature
Junction Temperature
0
10
20
30
40
50
60
70
80
90
100 110
AMBIENT TEMPERATURE (°C)
Figure 3. Maximum Power Dissipation vs. Temperature for a 4-Layer Board
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Rev. 0 | Page 5 of 20
ADA4860-1
TYPICAL PERFORMANCE CHARACTERISTICS
RL = 150 Ω and CL = 4 pF, unless otherwise noted.
G = +1, RF = 550Ω
1
–1
NORMALIZED GAIN (dB)
0
G = +2, RF = RG = 499Ω
–2
G = –1, RF = RG = 499Ω
–3
–4
G = +5, RF = 348Ω, RG = 86.6Ω
–5
G = +10, RF = 348Ω, RG = 38.3Ω
–6
0.1
1
10
100
VS = 5V
VOUT = 0.2V p-p
–1
G = +2, RF = RG = 499Ω
–2
G = –1, RF = RG = 499Ω
–3
–4
G = +5, RF = 348Ω, RG = 86.6Ω
G = +10, RF = 348Ω, RG = 38.3Ω
–6
0.1
1000
1
FREQUENCY (MHz)
2
VS = ±5V
VOUT = 2V p-p
1
G = –1, RF = RG = 499Ω
0
G = +5, RF = 348Ω, RG = 86.6Ω
–2
G = +2, RF = RG = 499Ω
–3
G = +10, RF = 348Ω, RG = 38.3Ω
–4
G = +1, RF = 550Ω
–6
0.1
1
10
100
VS = 5V
VOUT = 2V p-p
0
G = +5, RF = 348Ω, RG = 86.6Ω
–1
G = +2, RF = RG = 499Ω
–2
G = +10, RF = 348Ω, RG = 38.3Ω
–3
G = +1, RF = 550Ω
–4
–6
0.1
1000
1
FREQUENCY (MHz)
100
1000
Figure 8. Large Signal Frequency Response for Various Gains
7
G = +2
6.2 VOUT = 2V p-p
RF = RG = 499Ω
6.1
6
CLOSED-LOOP GAIN (dB)
6.3
6.0
5.9
VS = +5V
VS = ±5V
5.7
5.6
5
VOUT = 4V p-p
4
VOUT = 2V p-p
3
VOUT = 1V p-p
2
5.5
1
10
100
VS = ±5V
G = +2
RF = RG = 499Ω
0
0.1
1000
1
05709-014
5.4
5.3
0.1
1
05709-003
CLOSED-LOOP GAIN (dB)
10
FREQUENCY (MHz)
Figure 5. Large Signal Frequency Response for Various Gains
5.8
G = –1, RF = RG = 499Ω
–5
05709-012
–5
1000
05709-013
–1
100
Figure 7. Small Signal Frequency Response for Various Gains
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
1
10
FREQUENCY (MHz)
Figure 4. Small Signal Frequency Response for Various Gains
2
G = +1, RF = 550Ω
0
–5
05709-008
NORMALIZED GAIN (dB)
1
2
VS = ±5V
VOUT = 0.2V p-p
05709-007
2
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 9. Large Signal Frequency Response for Various Output Levels
Figure 6. Large Signal 0.1 dB Flatness
Rev. 0 | Page 6 of 20
ADA4860-1
6
6
5
RF = 604Ω
4
RF = 499Ω
3
RF = 402Ω
2
1
10
100
RF = 604Ω
5
RF = 499Ω
4
3
2
1
05709-009
1
0
0.1
RF = 301Ω
RF = 402Ω
RF = 301Ω
CLOSED-LOOP GAIN (dB)
CLOSED-LOOP GAIN (dB)
7
7
VS = ±5V
G = +2
RG = RF
VOUT = 0.2V p-p
VS = ±5V
G = +2
RG = RF
VOUT = 2V p-p
0
0.1
1000
1
FREQUENCY (MHz)
2
G = +1, RF = 550Ω
1
0
–1
G = +2, RF = RG = 499Ω
–2
–3
–4
1
10
100
VS = 5V
VOUT = 0.2V p-p
RL = 75Ω
–1
G = +2, RF = RG = 499Ω
–2
–3
–4
05709-005
–6
0.1
1000
1
1
NORMALIZED GAIN (dB)
–1
G = +1, RF = 550Ω
–2
–3
G = +2, RF = RG = 499Ω
–4
10
1000
100
VS = 5V
VOUT = 2V p-p
RL = 75Ω
0
–1
G = +1, RF = 550Ω
–2
–3
G = +2, RF = RG = 499Ω
–4
–5
–6
0.1
1000
FREQUENCY (MHz)
05709-016
–5
05709-015
NORMALIZED GAIN (dB)
2
0
1
100
Figure 14. Small Signal Frequency Response for Various Gains
VS = ±5V
VOUT = 2V p-p
RL = 75Ω
–6
0.1
10
FREQUENCY (MHz)
Figure 11. Small Signal Frequency Response for Various Gains
1
G = +1, RF = 550Ω
0
FREQUENCY (MHz)
2
1000
–5
05709-006
–5
–6
0.1
100
Figure 13. Large Signal Frequency Response vs. RF
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
1
VS = ±5V
VOUT = 0.2V p-p
RL = 75Ω
10
FREQUENCY (MHz)
Figure 10. Small Signal Frequency Response vs. RF
2
05709-004
8
1
10
100
1000
FREQUENCY (MHz)
Figure 15. Large Signal Frequency Response for Various Gains
Figure 12. Large Signal Frequency Response for Various Gains
Rev. 0 | Page 7 of 20
ADA4860-1
–40
–50
–60
VS = ±5V
G = +2
RF = RG = 499Ω
–50
–60
VOUT = 3V p-p, HD3
DISTORTION (dBc)
DISTORTION (dBc)
–40
VS = ±5V
G = +1
RF = 550Ω
–70
VOUT = 3V p-p, HD2
–80
VOUT = 2V p-p, HD2
–90
VOUT = 2V p-p, HD2
–70 VOUT = 3V p-p, HD2
–80
VOUT = 3V p-p, HD3
–90
VOUT = 2V p-p, HD3
1
10
–110
100
1
10
FREQUENCY (MHz)
VS = 5V
G = +1
RF = 550Ω
–50
Figure 19. Harmonic Distortion vs. Frequency
–40
VS = 5V
G = +2
RF = RG = 499Ω
VOUT = 2V p-p, HD2
–50
VOUT = 2V p-p, HD3
–70
VOUT = 1V p-p, HD2
VOUT = 1V p-p, HD3
1
10
VOUT = 1V p-p, HD2
–80
VOUT = 1V p-p, HD3
–90
–100
05709-018
–100
VOUT = 2V p-p, HD2
–70
–110
100
05709-019
–90
–110
VOUT = 2V p-p, HD3
–60
DISTORTION (dBc)
DISTORTION (dBc)
–60
–80
1
10
FREQUENCY (MHz)
–40
DISTORTION (dBc)
–60
VOUT = 1V p-p, HD2
VS = +5V
–80
VOUT = 2V p-p, HD3
VS = ±5V
–90
VOUT = 1V p-p, HD3
VS = +5V
–110
1
10
VOUT = 2V p-p, HD2
VS = ±5V
–70
VOUT = 2V p-p, HD3
VS = ±5V
–80
VOUT = 1V p-p, HD3
VS = +5V
–90
–100
05709-061
–100
VOUT = 1V p-p, HD2
VS = +5V
–110
100
FREQUENCY (MHz)
05709-062
–70
G = +2
RF = RG = 499Ω
RL = 100Ω
–50
VOUT = 2V p-p, HD2
VS = ±5V
–60
DISTORTION (dBc)
Figure 20. Harmonic Distortion vs. Frequency
G = +1
RF = 550Ω
RL = 100Ω
–50
100
FREQUENCY (MHz)
Figure 17. Harmonic Distortion vs. Frequency
–40
100
FREQUENCY (MHz)
Figure 16. Harmonic Distortion vs. Frequency
–40
05709-041
–110
VOUT = 2V p-p, HD3
–100
05709-017
–100
1
10
100
FREQUENCY (MHz)
Figure 21. Harmonic Distortion vs. Frequency for Various Supplies
Figure 18. Harmonic Distortion vs. Frequency for Various Supplies
Rev. 0 | Page 8 of 20
ADA4860-1
200
2.7
200
2.7
VS = ±5V
0
2.5
–100
2.4
2.3
–200
2.6
VS = ±5V
0
2.5
–100
05709-033
G = +1
VOUT = 0.2V p-p
RF = 550Ω
TIME = 5ns/DIV
100
–200
2.4
G = +2
VOUT = 0.2V p-p
RF = RG = 499Ω
TIME = 5ns/DIV
200
200
CL = 9pF
CL = 9pF
CL = 6pF
0
CL = 6pF
VS = ±5V
G = +1
VOUT = 0.2V p-p
RF = 550Ω
TIME = 5ns/DIV
100
CL = 4pF
0
–100
–200
Figure 23. Small Signal Transient Response for Various Capacitor Loads
Figure 26. Small Signal Transient Response for Various Capacitor Loads
2.7
2.7
CL = 9pF
CL = 6pF
CL = 6pF
CL = 4pF
2.6
2.5
2.3
VS = 5V
G = +1
VOUT = 0.2V p-p
RF = 550Ω
TIME = 5ns/DIV
CL = 4pF
2.5
2.4
2.3
Figure 24. Small Signal Transient Response for Various Capacitor Loads
VS = 5V
G = +2
VOUT = 0.2V p-p
RF = RG = 499Ω
TIME = 5ns/DIV
05709-022
OUTPUT VOLTAGE (V)
CL = 9pF
05709-035
OUTPUT VOLTAGE (V)
2.6
2.4
VS = ±5V
G = +2
VOUT = 0.2V p-p
RF = RG = 499Ω
TIME = 5ns/DIV
05709-021
OUTPUT VOLTAGE (mV)
100
05709-034
OUTPUT VOLTAGE (mV)
CL = 4pF
–200
2.3
Figure 25. Small Signal Transient Response for Various Supplies
Figure 22. Small Signal Transient Response for Various Supplies
–100
OUTPUT VOLTAGE (V)
+VS = 5V, –VS = 0V
2.6
05709-020
100
OUTPUT VOLTAGE (mV)
±VS = 5V
VS = +5V
OUTPUT VOLTAGE (V)
+VS = 5V, –VS = 0V
OUTPUT VOLTAGE (mV)
±VS = 5V
VS = +5V
Figure 27. Small Signal Transient Response for Various Capacitor Loads
Rev. 0 | Page 9 of 20
ADA4860-1
0
2.5
–0.5
2.0
1.5
CL = 9pF
3.5
0.5
3.0
0
2.5
–0.5
2.0
1.5
CL = 6pF
CL = 9pF
OUTPUT VOLTAGE (V)
–0.5
4.0
CL = 6pF
VS = ±5V
G = +2
VOUT = 2V p-p
RF = RG = 499Ω
TIME = 5ns/DIV
CL = 9pF
CL = 6pF
3.5
OUTPUT VOLTAGE (V)
3.0
2.5
2.0
VS = 5V
G = +1
VOUT = 2V p-p
RF = 550Ω
TIME = 5ns/DIV
CL = 4pF
3.0
2.5
2.0
1.5
05709-039
OUTPUT VOLTAGE (V)
CL = 4pF
Figure 32. Large Signal Transient Response for Various Capacitor Loads
CL = 4pF
1.0
CL = 6pF
0
–1.5
3.5
1.5
0.5
–1.0
Figure 29. Large Signal Transient Response for Various Capacitor Loads
4.0
CL = 9pF
05709-024
VS = ±5V
G = +1
VOUT = 2V p-p
RF = 550Ω
TIME = 5ns/DIV
05709-037
OUTPUT VOLTAGE (V)
CL = 4pF
–0.5
–1.5
1.0
1.0
0
–1.0
1.5
Figure 31. Large Signal Transient Response for Various Supplies
1.0
0.5
G = +2
VOUT = 2V p-p
RF = RG = 499Ω
TIME = 5ns/DIV
–1.5
Figure 28. Large Signal Transient Response for Various Supplies
1.5
1.0
–1.0
1.0
VS = +5V
1.0
Figure 30. Large Signal Transient Response for Various Capacitor Loads
VS = 5V
G = +2
VOUT = 2V p-p
RF = RG = 499Ω
TIME = 5ns/DIV
05709-025
–1.5
OUTPUT VOLTAGE (V)
±VS = 5V
3.0
OUTPUT VOLTAGE (V)
+VS = 5V, –VS = 0V
0.5
05709-036
OUTPUT VOLTAGE (V)
±VS = 5V
3.5
G = +1
VOUT = 2V p-p
RF = 550Ω
TIME = 5ns/DIV
4.0
VS = ±5V
1.0
–1.0
1.5
VS = +5V
OUTPUT VOLTAGE (V)
+VS = 5V, –VS = 0V
4.0
VS = ±5V
05709-023
1.5
Figure 33. Large Signal Transient Response for Various Capacitor Loads
Rev. 0 | Page 10 of 20
ADA4860-1
2500
1600
VS = ±5V
G = +1
RF = 550Ω
VS = ±5V
G = +2
RF = RG = 499Ω
1400
2000
SLEW RATE (V/µs)
SLEW RATE (V/µs)
1200
POSITIVE SLEW RATE
1500
1000
NEGATIVE SLEW RATE
POSITIVE SLEW RATE
1000
800
NEGATIVE SLEW RATE
600
400
500
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
0
4.5
0
0.25
0.50
INPUT VOLTAGE (V p-p)
900
VS = 5V
G = +1
RF = 550Ω
700
500
NEGATIVE SLEW RATE
400
NEGATIVE SLEW RATE
200
1.5
2.0
100
2.5
POSITIVE SLEW RATE
400
200
0
0.25
INPUT VOLTAGE (V p-p)
1.00
t = 0s
0.75
0.50
0.50
SETTLING TIME (%)
0.75
0.25
1V
0
–0.25
VS = ±5V
G = +2
VOUT = 2V p-p
RF = RG = 499Ω
TIME = 5ns/DIV
1.00
1.25
VS = ±5V
G = +2
VOUT = 2V p-p
RF = RG = 499Ω
TIME = 5ns/DIV
0.25
1V
0
–0.25
–0.50
–0.75
05709-027
SETTLING TIME (%)
VIN
–1.00
0.75
Figure 38. Slew Rate vs. Input Voltage
1.00
t = 0s
0.50
INPUT VOLTAGE (V p-p)
Figure 35. Slew Rate vs. Input Voltage
–0.75
2.25
500
300
–0.50
2.00
600
300
1.0
1.75
05709-029
SLEW RATE (V/µs)
600
05709-026
SLEW RATE (V/µs)
POSITIVE SLEW RATE
0.5
1.50
VS = 5V
G = +2
RF = RG = 499Ω
800
700
0
1.25
Figure 37. Slew Rate vs. Input Voltage
900
100
1.00
INPUT VOLTAGE (V p-p)
Figure 34. Slew Rate vs. Input Voltage
800
0.75
–1.00
Figure 36. Settling Time Rising Edge
VIN
Figure 39. Settling Time Falling Edge
Rev. 0 | Page 11 of 20
05709-030
0
05709-028
05709-043
0
200
ADA4860-1
30
110
20
15
10
5
100
1k
10k
100k
1M
10M
90
80
70
60
50
40
NONINVERTING INPUT
30
INVERTING INPUT
20
05709-032
INPUT CURRENT NOISE (pA/ Hz)
25
0
10
VS = ±5V, +5V
100
05709-031
INPUT VOLTAGE NOISE (nV/ Hz)
VS = ±5V, +5V
10
0
10
100M
100
1k
FREQUENCY (Hz)
–20
–PSR
–40
+PSR
–50
–60
–70
0.1
1
10
100
–10
–30
–40
–50
–60
–70
0.1
1000
1
10
5.5
OUTPUT
VOLTAGE
1
0
–1
–2
–3
–4
–5
200
300
400
500
600
700
800
900
4.5
4.0
3.5
OUTPUT
VOLTAGE
3.0
2.5
2.0
1.5
1.0
0.5
05709-042
OUTPUT AND INPUT VOLTAGE (V)
3
VS = 5V
G = +2
RF = RG = 499Ω
f = 1MHz
INPUT VOLTAGE × 2
5.0
05709-040
OUTPUT AND INPUT VOLTAGE (V)
4
100
1000
Figure 44. Common-Mode Rejection vs. Frequency
VS = ±5V
G = +2
RF = RG = 499Ω
f = 1MHz
INPUT VOLTAGE × 2
0
100
FREQUENCY (MHz)
6
–6
100M
–20
Figure 41. Power Supply Rejection vs. Frequency
2
10M
VS = ±5V
VOUT = 200mV rms
RF = 560Ω
FREQUENCY (MHz)
5
1M
05709-055
COMMON-MODE REJECTION (dB)
–10
05709-053
POWER SUPPLY REJECTION (dB)
0
VS = ±5V
G = +2
–30
100k
Figure 43. Input Current Noise vs. Frequency
Figure 40. Input Voltage Noise vs. Frequency
0
10k
FREQUENCY (Hz)
0
–0.5
1000
TIME (ns)
0
100
200
300
400
500
600
700
800
TIME (ns)
Figure 45. Output Overdrive Recovery
Figure 42. Output Overdrive Recovery
Rev. 0 | Page 12 of 20
900
1000
ADA4860-1
VS = ±5V
G = +2
100
40
0
30
20
–45
–90
1
0.1
1
10
VS = +5V
–10
–30
05709-054
–180
1000
100
VS = ±5V
0
–20
–135
0.1
0.01
10
–40
–5
05709-058
10
INPUT VOS (mV)
PHASE
PHASE (Degrees)
TRANSIMPEDANCE
–4
–3
–2
–1
FREQUENCY (MHz)
0
1
2
3
4
5
VCM (V)
Figure 49. Input VOS vs. Common-Mode Voltage
Figure 46. Transimpedance and Phase vs. Frequency
7.0
6.5
5.5
VS = +5V
5.0
4.5
4.0
–40
–25
–10
5
20
35
50
65
80
95
110
VS = ±5V
VS = +5V
2
0
–2
–4
05709-056
–6
–8
–10
–5
–4
–3
–2
–1
0
1
5.0
4.5
4
5
6
7
8
9
10
Figure 50. Supply Current vs. Supply Voltage
10
4
5.5
SUPPLY VOLTAGE (V)
Figure 47. Supply Current at Various Supplies vs. Temperature
6
6.0
4.0
125
TEMPERATURE (°C)
8
6.5
05709-057
TOTAL SUPPLY CURRENT (mA)
6.0
05709-059
TOTAL SUPPLY CURRENT (mA)
VS = ±5V
INPUT BIAS CURRENT (µA)
TRANSIMPEDANCE (kΩ)
1000
2
3
4
5
OUTPUT VOLTAGE (V)
Figure 48. Inverting Input Bias Current vs. Output Voltage
Rev. 0 | Page 13 of 20
11
12
ADA4860-1
APPLICATION INFORMATION
Figure 51 and Figure 52 show the typical noninverting and
inverting configurations and the recommended bypass
capacitor values.
+VS
0.1µF
VIN
–
Table 5. Recommended Values and Frequency Performance1
Gain
+1
−1
+2
+5
+10
1
RF (Ω)
550
499
499
348
348
RG (Ω)
N/A
499
499
86.6
38.3
VOUT
0.1µF
10µF
+
–VS
RF
RG
The feedback resistor has a direct impact on the closed-loop
bandwidth and stability of the current feedback op amp circuit.
Reducing the resistance below the recommended value can
make the amplifier response peak and even become unstable.
Increasing the size of the feedback resistor reduces the closedloop bandwidth. Table 5 provides a convenient reference for
quickly determining the feedback and gain set resistor values
and bandwidth for common gain configurations.
−3 dB
LS BW
(MHz)
165
400
230
265
195
+
ADA4860-1
FEEDBACK RESISTOR SELECTION
−3 dB
SS BW
(MHz)
800
400
520
335
165
10µF
+
05709-010
Attention must be paid to bypassing the power supply pins of
the ADA4860-1. High quality capacitors with low equivalent
series resistance (ESR), such as multilayer ceramic capacitors
(MLCCs), should be used to minimize supply voltage ripple
and power dissipation. Generally, a 10 μF tantalum capacitor
located in close proximity to the ADA4860-1 is required to
provide good decoupling for lower frequency signals. In
addition, a 0.1 μF decoupling multilayer ceramic chip capacitor
(MLCC) should be located as close to each of the power supply
pins as is physically possible, no more than ⅛ inch away. The
ground returns should terminate immediately into the ground
plane. Locating the bypass capacitor return close to the load
return minimizes ground loops and improves performance.
Large
Signal
0.1 dB
Flatness
40
80
125
100
28
Conditions: VS = ±5 V, TA = 25°C, RL = 150 Ω.
Rev. 0 | Page 14 of 20
Figure 51. Noninverting Gain
RF
+VS
10µF
+
0.1µF
VIN
RG
–
ADA4860-1
+
VOUT
0.1µF
10µF
+
–VS
Figure 52. Inverting Gain
05709-011
POWER SUPPLY BYPASSING
ADA4860-1
DRIVING CAPACITIVE LOADS
POWER DOWN PIN
If driving loads with a capacitive component is desired, the best
frequency response is obtained by the addition of a small series
resistance, as shown in Figure 53. Figure 54 shows the optimum
value for RSERIES vs. capacitive load. The test was performed with
a 50 MHz, 50% duty cycle pulse, with an amplitude of 200 mV p-p.
The criteria for RSERIES selection was based on maintaining
approximately 1 dB of peaking in small signal frequency
response. It is worth noting that the frequency response of the
circuit can be dominated by the passive roll-off of RSERIES and CL.
The ADA4860-1 is equipped with a power-down function.
The POWER DOWN pin allows the user to reduce the quiescent
supply current when the amplifier is not being used. The
power-down threshold levels are derived from the voltage
applied to the −VS pin. When used in single-supply applications,
this is especially useful with conventional logic levels. The
amplifier is powered down when the voltage applied to the
POWER DOWN pin is greater than (−VS + 0.5 V). The
amplifier is enabled whenever the POWER DOWN pin is left
open, or the voltage on the POWER DOWN pin is less than
(−VS + 0.5 V). If the POWER DOWN pin is not used, it should
be connected to the negative supply.
ADA4860-1
VIN
RSERIES
RL
VIDEO AMPLIFIER
05709-052
CL
RF
750Ω
With low differential gain and phase errors and wide 0.1 dB
flatness, the ADA4860-1 is an ideal solution for consumer and
professional video applications. Figure 55 shows a typical video
driver set for a noninverting gain of +2, where RF = RG = 499 Ω.
The video amplifier input is terminated into a shunt 75 Ω resistor.
At the output, the amplifier has a series 75 Ω resistor for
impedance matching to the video load.
Figure 53. Driving Capacitive Loads
14
10
8
RF
6
+VS
10µF
+
4
–
0
10
20
30
40
ADA4860-1
+
50
CAPACITIVE LOAD (pF)
0.1µF
75Ω
CABLE
VOUT
75Ω
10µF
+
75Ω
CABLE
Figure 54. Recommended RSERIES vs. Capacitive Load
75Ω
VIN
75Ω
–VS
05709-038
0
0.1µF
RG
2
05709-060
SERIES RESISTANCE (Ω)
12
Figure 55. Video Driver Schematic
SINGLE-SUPPLY OPERATION
Single-supply operation can present certain challenges for the
designer. For a detailed explanation on op amp single-supply
operation, see Application Note AN-581.
Rev. 0 | Page 15 of 20
ADA4860-1
When using the ADA4860-1, a variety of circuit conditions and
parasitics can affect peaking, gain flatness, and −3 dB
bandwidth. This section discusses how the ADA4860-1 small
signal responses can be dramatically altered with basic circuit
changes and added stray capacitances, see the Layout and
Circuit Board Parasitics section for more information.
Particularly with low closed-loop gains, the feedback resistor
(Rf) effects peaking and gain flatness. However, with gain = +1,
−3 dB bandwidth varies slightly, while gain = +2 has a much
larger variation. For gain = +1, Figure 56 shows the effect that
various feedback resistors have on frequency response. In
Figure 56, peaking is wide ranging yet −3 dB bandwidths vary
by only 6%. In this case, the user must pick what is desired:
more peaking or flatter bandwidth. Figure 57 shows gain = +2
bandwidth and peaking variations vs. RF and RL. Bandwidth
delta vs. RL increase was approximately 17%. As RF is reduced
from 560 Ω to 301 Ω, the −3 dB bandwidth changes 49%, with
excessive compromises in peaking, see Figure 57. For more gain
= +2 bandwidth variations vs. RF, see Figure 10 and Figure 13.
DASH LINE IS PLANE CLEAR OUT AREA
(EXCEPT SUPPLY PINS) DURING PC LAYOUT.
+
VS = ±5V
G = +1
1 VOUT = 0.1V p-p
RL = 100Ω
RF
ADDED C J
EXAMPLE
In Figure 59, a slight −3 dB bandwidth delta of approximately
+10% can be seen going from a small-to-large case size. The
increase in bandwidth with the larger 1206 case size is caused
by an increase in parasitic capacitance across the chip resistor.
0
RF = 910Ω
RF = 1.5kΩ
–2
–3
–4
05709-044
1
10
100
1000
10000
RF = 301Ω, RL = 100Ω
0
–1
RF = 560Ω, RL = 100Ω
RF = 560Ω, RL = 1kΩ
–3
–4
05709-045
1
10
100
1206 RESISTOR SIZE
–4 VS = ±5V
G = +2
VOUT = 0.1V p-p
–5 RG = RF = 560Ω
RL = 100Ω
1
0402 RESISTOR SIZE
10
100
1000
Figure 59. Small Signal Frequency Response vs. Resistor Size
2
–5
–3
FREQUENCY (MHz)
FREQUENCY (MHz)
–2
–2
–6
Figure 56. Small Signal Frequency Response vs. RF
VS = ±5V
G = +2
1 VOUT = 0.1V p-p
RG = RF
–1
05709-046
NORMALIZED GAIN (dB)
RF = 680Ω
–5
NORMALIZED GAIN (dB)
ADDED C LOAD
EXAMPLE
RG
Figure 58. Noninverting Gain Setup for Illustration of
Parasitic Effects, 50 Ω System, RL = 100 Ω
–1
–6
50Ω
–
RF = 560Ω
0
–6
49.9Ω
49.9Ω
1
2
NORMALIZED GAIN (dB)
The impact of resistor case sizes was observed using the circuit
drawn in Figure 58. The types and sizes chosen were 0402 case
sized thin film and 1206 thick film. All other measurement
conditions were kept constant except for the case size and
resistor composition.
05709-049
OPTIMIZING FLATNESS AND BANDWIDTH
1000
FREQUENCY (MHz)
Figure 57. Small Signal Frequency Response vs. RF vs. RL
Rev. 0 | Page 16 of 20
ADA4860-1
LAYOUT AND CIRCUIT BOARD PARASITICS
1
G = +2, RF = 560Ω, CJ = 0.4pF EXTRA
3
VS = ±5V
G = +2
2 V
OUT = 0.1V p-p
RF = RG = 560Ω
1
RL = 1kΩ, CL = 0pF
–3
RL = 100Ω, CL = 0pF
1
10
100
1000
Figure 61. Small Signal Frequency Response vs. Output Capacitive Load
For more information on high speed board layout, go to:
www.analog.com and
www.analog.com/library/analogDialogue/archives/3909/layout.html.
G = +2, RF = 560Ω, CJ = 0pF
–3
–4
05709-047
NORMALIZED GAIN (dB)
–2
FREQUENCY (MHz)
G = –2, RF = 402Ω, CJ = 0pF
100
–1
–6
–2
10
0
–5
G = –2, RF = 402Ω, CJ = 0.4pF EXTRA
–5 VS = ±5V
VOUT = 0.1V p-p
RL = 100Ω
–6
1
RL = 100Ω, CL = 5.6pF EXTRA
–4
0
–1
RL = 1kΩ, CL = 5.6pF EXTRA
05709-048
To illustrate the affects of parasitic capacitance, a small
capacitor of 0.4 pF from the amplifiers summing junction
(inverting input) to ground was intentionally added. This was
done on two boards with equal and opposite gains of +2 and −2.
Figure 60 reveals the effects of parasitic capacitance at the
summing junction for both noninverting and inverting gain
circuits. With gain = +2, the additional 0.4 pF of added
capacitance created an extra 43% −3 dB bandwidth extension,
plus some extra peaking. For gain = −2, a 5% increase in −3 dB
bandwidth was created with an extra 0.4 pF on summing
junction.
In a second test, 5.6 pF of capacitance was added directly at the
output of the gain = +2 amplifier. Figure 61 shows the results.
Extra output capacitive loading on the ADA4860-1 also causes
bandwidth extensions, as seen in Figure 61. The effect on the
gain = +2 circuit is more pronounced with lighter resistive
loading (1 kΩ). For pulse response behavior with added output
capacitances, see Figure 23, Figure 24, Figure 26, Figure 27,
Figure 29, Figure 30, Figure 32, and Figure 33.
NORMALIZED GAIN (dB)
Careful attention to printed circuit board (PCB) layout prevents
associated board parasitics from becoming problematic and
affecting gain flatness and −3 dB bandwidth. In the printed
circuit environment, parasitics around the summing junction
(inverting input) or output pins can alter pulse and frequency
response. Parasitic capacitance can be unintentionally created
on a PC board via two parallel metal planes with a small vertical
separation (in FR4). To avoid parasitic problems near the
summing junction, signal line connections between the
feedback and gain resistors should be kept as short as possible
to minimize the inductance and stray capacitance. For similar
reasons, termination and load resistors should be located as
close as possible to the respective inputs. Removing the ground
plane on all layers from the area near and under the input and
output pins reduces stray capacitance.
1000
FREQUENCY (MHz)
Figure 60. Small Signal Frequency Response vs.
Added Summing Junction Capacitance
Rev. 0 | Page 17 of 20
ADA4860-1
OUTLINE DIMENSIONS
2.90 BSC
6
5
4
1
2
3
2.80 BSC
1.60 BSC
PIN 1
INDICATOR
0.95 BSC
1.30
1.15
0.90
1.90
BSC
1.45 MAX
0.15 MAX
0.50
0.30
0.22
0.08
SEATING
PLANE
10°
4°
0°
0.60
0.45
0.30
COMPLIANT TO JEDEC STANDARDS MO-178-AB
Figure 62. 6-Lead Plastic Surface-Mount Package [SOT-23]
(RJ-6)
Dimensions shown in millimeters
ORDERING GUIDE
Model
ADA4860-1YRJZ-RL 1
ADA4860-1YRJZ-RL71
ADA4860-1YRJZ-R21
1
Temperature Range
–40°C to +105°C
–40°C to +105°C
–40°C to +105°C
Package Description
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
Z = Pb-free part.
Rev. 0 | Page 18 of 20
Ordering Quantity
10,000
3,000
250
Package Option
RJ-6
RJ-6
RJ-6
Branding
HKB
HKB
HKB
ADA4860-1
NOTES
Rev. 0 | Page 19 of 20
ADA4860-1
NOTES
©2006 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D05709-0-4/06(0)
Rev. 0 | Page 20 of 20