Burr-Brown DAC8554IPWG4 16-bit, quad channel, ultralow glitch, voltage output digital-to-analog converter Datasheet

 DAC8554
SLAS431A – JUNE 2005 – REVISED AUGUST 2005
16-BIT, QUAD CHANNEL, ULTRALOW GLITCH, VOLTAGE OUTPUT
DIGITAL-TO-ANALOG CONVERTER
FEATURES
DESCRIPTION
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The DAC8554 is a 16-bit, quad channel, voltage
output, digital-to-analog converter (DAC), offering
low-power operation and a flexible serial host
interface. It offers monotonicity, good linearity, and
exceptionally low glitch. Each on-chip precision output amplifier allows rail-to-rail output swing to be
achieved over the supply range of 2.7 V to 5.5 V. The
device supports a standard 3-wire serial interface
capable of operating with input data clock frequencies
up to 50 MHz for IOVDD = 5 V.
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Relative Accuracy: 12 LSB (Max)
Glitch Energy: 0.15 nV-s
Power Supply: +2.7 V to +5.5 V
MicroPower Operation: 850 µA at 5 V
16-Bit Monotonic Over Temperature
Settling Time: 10 µs to ±0.003% FSR
Ultra-Low AC Crosstalk: –100 dB Typ
Power-On Reset to Zero-Scale
On-Chip Output Buffer Amplifier With
Rail-to-Rail Operation
Double Buffered Input Architecture
Simultaneous or Sequential Output Update
and Power-Down
16-Channel Broadcast Capability
Schmitt-Triggered Inputs
SPI Compatible Serial Interface: Up to 50 MHz
1.8 V to 5.5 V Logic Compatibility
Available in a TSSOP-16 Package
The DAC8554 requires an external reference voltage
to set the output range of each DAC channel. Also
incorporated into the device is a power-on reset
circuit which ensures that the DAC outputs power up
at zero-scale and remain there until a valid write
takes place. The DAC8554 provides a per channel
power-down feature, accessed over the serial
interface, that reduces the current consumption to
200 nA per channel at 5 V.
The low-power consumption of this device in normal
operation makes it ideally suited to portable batteryoperated equipment and other low-power applications. The power consumption is 4.25 mW at 5 V,
reducing to 4 µW in power-down mode.
APPLICATIONS
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Portable Instrumentation
Closed-Loop Servo-Control
Process Control
Data Acquisition Systems
Programmable Attenuation
PC Peripherals
AVDD
The DAC8554 is available in a TSSOP-16 package
with a specified operating temperature range of
–40°C to 105°C.
VrefH
IOVDD
Data
Buffer A
DAC
Register A
DAC A
VOUTA
VOUTB
VOUTC
Data
Buffer D
18
SYNC
SCLK
DIN
24-Bit
Serial-toParallel Shift
Register
8
DAC
Register D
Buffer
Control
VOUTD
DAC D
Register
Control
Power-Down
Control Logic
Resistor
Network
A0
A1
LDAC
ENABLE
VrefL
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
SPI, QSPI are trademarks of Motorola.
Microwire is a trademark of National Semiconductor.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2005, Texas Instruments Incorporated
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated
circuits be handled with appropriate precautions. Failure to observe proper handling and installation
procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision
integrated circuits may be more susceptible to damage because very small parametric changes could
cause the device not to meet its published specifications. This device is rated at 1500 V HBM and 1000
V CDM.
PACKAGING/ORDERING INFORMATION
PRODUCT
PACKAGE
LEAD
PACKAGE
DESIGNATOR (1)
SPECIFICATION
TEMPERATURE RANGE
PACKAGE
MARKING
DAC8554
TSSOP-16
PW
–40°C TO 105°C
D8554
(1)
ORDERING
NUMBER
TRANSPORT
MEDIA, QUANTITY
DAC8554IPW
Tube, 90
DAC8554IPWR
Tape and Reel, 2000
For the most current specifications and package information, refer to our web site at www.ti.com.
ABSOLUTE MAXIMUM RATINGS (1)
UNIT
AVDD to GND
–0.3 V to 6 V
Digital input voltage to GND
–0.3 V to AVDD + 0.3 V
VO(A) to VO(D) to GND
–0.3 V to AVDD + 0.3 V
Operating temperature range
–40°C to 105°C
Storage temperature range
–65°C to 150°C
Junction temperature range (TJ max)
150°C
Power dissipation
118°C/W
θJC Thermal impedance
29°C/W
Lead temperature, soldering
(1)
(TJmax – TA)/θJA
θJA Thermal impedance
Vapor phase (60 s)
215°C
Infrared (15 s)
220°C
Stresses above those listed under absolute maximum ratings may cause permanent damage to the device. Exposure to absolute
maximum conditions for extended periods may affect device reliability.
ELECTRICAL CHARACTERISTICS
over operating free-air temperature range (unless otherwise noted)
PARAMETER
STATIC
TEST CONDITIONS
MIN
TYP
MAX
UNIT
±4
±12
LSB
PERFORMANCE (1)
Resolution
16
Bits
Relative accuracy
Measured by line passing through codes 485 and
64741
Differential nonlinearity
16-bit Monotonic
±0.25
±1
LSB
Zero-scale error
Measured by line passing through codes 485 and
64741
±2
±12
mV
Full-scale error
Measured by line passing through codes 485 and
64741, AVDD = 5 V, Vref = 4.99 V
±0.3
±0.5
% of FSR
Gain error
Measured by line passing through codes 485 and
64741, AVDD = 5 V
±0.05
±0.15
% of FSR
Zero-scale error drift
±5
Gain temperature coefficient
Power Supply Rejection Ratio
(PSRR)
(1)
2
RL = 2 kΩ, CL = 200 pF
Linearity calculated using a reduced code range of 485 to 64741; output unloaded.
µV/°C
±1
ppm of FSR/°C
8
mV
0.75
mV/V
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
ELECTRICAL CHARACTERISTICS (continued)
over operating free-air temperature range (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VrefH
V
10
µs
OUTPUT CHARACTERISTICS (2)
Output voltage range
Output voltage settling time
0
To ±0.003% FSR, 0200H to FD00H, RL = 2 kΩ, 0 pF
< CL < 200 pF
8
RL = 2 kΩ, CL = 500 pF
Slew rate
Capacitive load stability
Code change glitch impulse
RL = ∞
12
µs
1.8
V/µs
470
pF
RL = 2 kΩ
1000
pF
1 LSB change around major carry
0.15
Digital feedthrough
nV-s
0.15
DC crosstalk
Full-scale swing on adjacent channel. AVDD = 5 V,
Vref = 4.096 V
0.25
LSB
AC crosstalk
1 kHz sine wave
–100
dB
DC output impedance
At mid-point input
1
Ω
Short-circuit current
Power-up time
AVDD = 5 V
50
AVDD = 3 V
20
Coming out of power-down mode AVDD = 5 V
2.5
Coming out of power-down mode AVDD = 3 V
5
mA
µs
AC PERFORMANCE
SNR (1st 19 harmonics removed)
THD
95
-85
BW = 20 kHz, AVDD = 5 V, FOUT = 1 kHz
SFDR
dB
87
SINAD
84
REFERENCE INPUT
Vref(H) Voltage
Vref(L) < Vref(H) , AVDD - (Vref(H) + Vref(L)) /2 > 1.2 V
0
AVDD
V
Vref(L) Voltage
Vref(L) < Vref(H) , AVDD - (Vref(H) + Vref(L)) /2 > 1.2 V
0
AVDD/2
V
µA
Reference input current
Reference input impedance
LOGIC INPUTS
Vref(L) = GND, Vref(H) = AVDD = 5 V
180
250
Vref(L) = GND, Vref(H) = AVDD = 3 V
120
200
Vref(L) < Vref(H)
31
µA
kΩ
(3)
VI(L), logic input LOW voltage
VI(H), logic input HIGH voltage
2.7 V ≤ IOVDD≤ 5.5 V
0.3 ×
I0VDD
1.8 V ≤ IOVDD≤ 2.7 V
0.1 ×
I0VDD
2.7 ≤ IOVDD≤ 5.5 V
0.7 ×
I0VDD
1.8 ≤ IOVDD < 2.7 V
0.95 ×
I0VDD
Pin capacitance
V
V
3
pF
POWER REQUIREMENTS
AVDD
2.7
5.5
IOVDD
1.8
5.5
AIDD (normal mode)
(2)
(3)
V
Input code = 32768, reference current included, no
load
Ensured by design and characterization, not production tested.
Ensured by design and characterization, not production tested.
3
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
ELECTRICAL CHARACTERISTICS (continued)
over operating free-air temperature range (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
IOIDD
AVDD = 3.6 V to 5.5 V
VIH = IOVDD and VIL = GND
AVDD = 2.7 V to 3.6 V
TYP
MAX
10
20
0.65
1.0
0.6
0.96
0.2
2
0.05
2
UNIT
µA
mA
AIDD (all power-down modes)
AVDD = 3.6 V to 5.5 V
VIH = IOVDD and VIL = GND
AVDD = 2.7 V to 3.6 V
µA
POWER EFFICIENCY
IOUT/IDD
IL = 2 mA, AVDD = 5 V
89%
TEMPERATURE RANGE
Specified performance
–40
105
°C
PIN CONFIGURATION
VOUTA
1
16 LDAC
VOUTB
2
15 ENABLE
VREFH
3
14 A1
AVDD
4
VREFL
5
12 IOVDD
GND
6
11 DIN
VOUTC
7
10 SCLK
VOUTD
8
9
13 A0
DAC8554
SYNC
PIN DESCRIPTIONS
4
PIN
NAME
DESCRIPTION
1
VOUTA
Analog output voltage from DAC A.
2
VOUTB
Analog output voltage from DAC B.
3
VrefH
Positive reference voltage input.
4
AVDD
Power supply input, 2.7 V to 5.5 V.
5
VrefL
Negative reference voltage input.
6
GND
Ground reference point for all circuitry on the part.
7
VOUTC
Analog output voltage DAC C.
8
VOUTD
Analog output voltage DAC D.
9
SYNC
Level-triggered control input (active LOW). This is the frame synchronization signal for the input data. When
SYNC goes LOW, it enables the input shift register and data is transferred in on the falling edges of the
following clocks. The DAC is updated following the 24th clock (unless SYNC is taken HIGH before this edge
in which case the rising edge of SYNC acts as an interrupt and the write sequence is ignored by the
DAC8554).
10
SCLK
Serial clock input. Data can be transferred at rates up to 50 MHz.
11
DIN
12
IOVDD
13
A0
Address 0 — sets device address, see Table 2
14
A1
Address 1 — sets device address, see Table 2
15
ENABLE
Serial data input. Data is clocked into the 24-bit input shift register on each falling edge of the serial clock
input.
Digital input-output power supply
Active LOW, ENABLE LOW connects the SPI interface to the serial port.
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
PIN DESCRIPTIONS (continued)
PIN
NAME
16
LDAC
DESCRIPTION
Load DACs, rising edge triggered, loads all DAC registers.
TIMING REQUIREMENTS (1) (2)
AVDD = 2.7 V to 5.5 V, all specifications –40°C to 105°C (unless otherwise noted)
PARAMETER
TEST CONDITIONS
t 1 (3) SCLK cycle time
t2
SCLK HIGH time
t3
SCLK LOW time
t4
SYNC falling edge to SCLK rising edge setup time
t5
Data setup time
t6
Data hold time
t7
24th SCLK falling edge to SYNC rising edge
t8
Minimum SYNC HIGH time
t9
24th SCLK falling edge to SYNC falling edge
(1)
(2)
(3)
MIN
IOVDD = AVDD = 2.7 V to 3.6 V
40
IOVDD = AVDD = 3.6 V to 5.5 V
20
IOVDD = AVDD = 2.7 V to 3.6 V
20
IOVDD = AVDD = 3.6 V to 5.5 V
10
IOVDD = AVDD = 2.7 V to 3.6 V
20
IOVDD = AVDD = 3.6 V to 5.5 V
10
IOVDD = AVDD = 2.7 V to 3.6 V
0
IOVDD = AVDD = 3.6 V to 5.5 V
0
IOVDD = AVDD = 2.7 V to 3.6 V
5
IOVDD = AVDD = 3.6 V to 5.5 V
5
IOVDD = AVDD = 2.7 V to 3.6 V
4.5
IOVDD = AVDD = 3.6 V to 5.5 V
4.5
IOVDD = AVDD = 2.7 V to 3.6 V
0
IOVDD = AVDD = 3.6 V to 5.5 V
0
IOVDD = AVDD = 2.7 V to 3.6 V
40
IOVDD = AVDD = 3.6 V to 5.5 V
20
IOVDD = AVDD = 2.7 V to 5.5 V
130
TYP
MAX
UNIT
ns
ns
ns
ns
ns
ns
ns
ns
ns
All input signals are specified with tR = tF = 3 ns (10% to 90% of AVDD) and timed from a voltage level of (VIL + VIH)/2.
See Serial Write Operation timing diagram.
Maximum SCLK frequency is 50 MHz at IOVDD = AVDD = 3.6 V to 5.5 V and 25 MHz at IOVDD = AVDD = 2.7 V to 3.6 V.
SERIAL WRITE OPERATION
t1
SCLK
t9
1
24
t8
t3
t4
t2
t7
SYNC
t6
t5
DIN
DB23
DB0
DB23
5
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
TYPICAL CHARACTERISTICS
At TA = 25°C, unless otherwise noted
8
6
4
2
0
−2
−4
−6
−8
LE (LSB)
0.5
DLE (LSB)
1
0
−0.5
0
8
6
4
2
0
−2
−4
−6
−8
8192
16384 24576 32768 40960
Digital Input Code
0
LINEARITY ERROR AND DIFFERENTIAL
LINEARITY ERROR
vs
DIGITAL INPUT CODE
AVDD = 5 V, Vref = 4.99 V
8
6
4
2
0
−2
−4
−6
−8
1
0.5
0
−0.5
8192
16384 24576 32768 40960
Digital Input Code
Channel D
AVDD = 5 V, Vref = 4.99 V
0
−0.5
−1
49152 57344 65536
0
8192
16384 24576 32768 40960
Digital Input Code
49152 57344
Figure 3.
Figure 4.
LINEARITY ERROR AND DIFFERENTIAL
LINEARITY ERROR
vs
DIGITAL INPUT CODE
LINEARITY ERROR AND DIFFERENTIAL
LINEARITY ERROR
vs
DIGITAL INPUT CODE
AVDD = 2.7 V, Vref = 2.69 V
LE (LSB)
Channel A
8
6
4
2
0
−2
−4
−6
−8
1
1
0.5
0.5
0
−0.5
8192
16384 24576
32768 40960 49152
Digital Input Code
Figure 5.
57344
65536
Channel B
65536
AVDD = 2.7 V, Vref = 2.69 V
0
−0.5
−1
0
16384 24576 32768 40960 49152 57344 65536
Digital Input Code
LINEARITY ERROR AND DIFFERENTIAL
LINEARITY ERROR
vs
DIGITAL INPUT CODE
1
−1
8192
Figure 2.
DLE (LSB)
LE (LSB)
DLE (LSB)
0
−0.5
0.5
8
6
4
2
0
−2
−4
−6
−8
AVDD = 5 V, Vref = 4.99 V
Figure 1.
Channel C
0
Channel B
−1
49152 57344 65536
−1
6
8
6
4
2
0
−2
−4
−6
−8
1
LE (LSB)
LE (LSB)
AVDD = 5 V, Vref = 4.99 V
Channel A
0.5
−1
DLE (LSB)
LINEARITY ERROR AND DIFFERENTIAL
LINEARITY ERROR
vs
DIGITAL INPUT CODE
DLE (LSB)
DLE (LSB)
LE (LSB)
LINEARITY ERROR AND DIFFERENTIAL
LINEARITY ERROR
vs
DIGITAL INPUT CODE
0
8192
16384 24576 32768 40960
Digital Input Code
Figure 6.
49152 57344 65536
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
TYPICAL CHARACTERISTICS (continued)
At TA = 25°C, unless otherwise noted
8
6
4
2
0
−2
−4
−6
−8
Channel C
LINEARITY ERROR AND DIFFERENTIAL
LINEARITY ERROR
vs
DIGITAL INPUT CODE
AVDD = 2.7 V, Vref = 2.69 V
LE (LSB)
LE (LSB)
LINEARITY ERROR AND DIFFERENTIAL
LINEARITY ERROR
vs
DIGITAL INPUT CODE
0
−0.5
−1
Channel D
AVDD = 2.7 V, Vref = 2.69 V
1
0.5
DLE (LSB)
DLE (LSB)
1
8
6
4
2
0
−2
−4
−6
−8
0.5
0
−0.5
−1
0
8192
16384 24576 32768 40960 49152
Digital Input Code
57344 65536
0
8192
16384 24576 32768 40960 49152 57344 65536
Digital Input Code
Figure 7.
Figure 8.
ZERO-SCALE ERROR
vs
TEMPERATURE
ZERO-SCALE ERROR
vs
TEMPERATURE
5
5
AVDD = 2.7 V, Vref = 2.69 V
AVDD = 5 V, Vref = 4.99 V
CH C
CH C
2.5
Error (mV)
Error (mV)
2.5
CH A
0
CH D
CH A
0
CH D
CH B
CH B
−2.5
−2.5
−5
−40
0
40
80
−5
−40
120
0
40
80
120
TA − Temperature − °C
TA − Temperature − °C
Figure 9.
Figure 10.
FULL-SCALE ERROR
vs
TEMPERATURE
FULL-SCALE ERROR
vs
TEMPERATURE
0
0
AVDD = 5 V, Vref = 4.99 V
AVDD = 2.7 V, Vref = 2.69 V
−5
−5
CH C
Error (mV)
Error (mV)
CH A
−10
CH C
−15
−10
CH D
CH B
−15
CH A
CH D
−20
−20
CH B
−25
−40
0
40
TA − Temperature − °C
Figure 11.
80
120
−25
−40
0
40
TA − Temperature − °C
80
120
Figure 12.
7
DAC8554
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TYPICAL CHARACTERISTICS (continued)
At TA = 25°C, unless otherwise noted
SINK CURRENT CAPABILITY (ALL CHANNELS)
SOURCE CURRENT CAPABILITY (ALL CHANNELS)
0.150
6
0.125
VDD = 5.5 V
5.6
VDD = 5.5 V
VDD = 2.7 V
V
(V)
OUT
0.100
V
(V)
OUT
Vref = AVDD −10 mV
DAC Loaded With FFFFH
Vref = AVDD −10 mV
DAC Loaded With 0000H
0.075
5.2
4.8
0.050
4.4
0.025
0
0
2
4
6
8
4
10
ISINK (mA)
4
6
ISIOURCE (mA)
Figure 13.
Figure 14.
SOURCE CURRENT CAPABILITY (ALL CHANNELS)
SUPPLY CURRENT
vs
DIGITAL INPUT CODE
3
2
8
10
1200
Vref = AVDD −10 mV
DAC Loaded With FFFFH
Reference Current Included
1000
2.7
AVDD = Vref = 5.5 V
AVDD = 2.7 V
800
I DD ( µ A )
V
(V)
OUT
0
2.4
2.1
600
AVDD = Vref = 2.7 V
400
1.8
200
1.5
0
2
4
6
ISIOURCE (mA)
8
0
10
0
8192
16384 24576 32768 40960 49152 57344 65536
Digital Input Code
Figure 15.
Figure 16.
SUPPLY CURRENT
vs
FREE-AIR TEMPERATURE
SUPPLY CURRENT
vs
SUPPLY VOLTAGE
1200
900
Reference Current Included
1000
850
Vref = AVDD All DACs Powered,
Reference Current Included, No Load
AVDD = Vref = 5.5 V
800
AVDD = Vref = 2.7 V
600
750
400
700
200
650
0
−40
0
40
TA − Temperature − °C
Figure 17.
8
I DD ( µ A )
I DD ( µ A )
800
80
120
600
2.7
3.05
3.4
3.75
4.1
4.45
VDD (V)
Figure 18.
4.8
5.15
5.5
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TYPICAL CHARACTERISTICS (continued)
At TA = 25°C, unless otherwise noted
SUPPLY CURRENT
vs
LOGIC INPUT VOLTAGE
2000
SUPPLY CURRENT
vs
LOGIC INPUT VOLTAGE
800
TA = 25°C, SYNC Input (All Other Inputs = GND
CHA Powered Up; All Other Channels in Powerdown
Reference Current Included
1600
TA = 25°C, SYNC Input (All Other Inputs = GND
CHA Powered Up; All Other Channels in Powerdown
Reference Current Included
600
IOVDD = AVDD = Vref = 2.7 V
I DD ( µ A )
I DD ( µ A )
IOVDD = AVDD = Vref = 5 V
1200
800
400
200
400
0
0
0
1
2
3
4
0
5
1.5
Figure 19.
Figure 20.
AVDD = Vref = 5 V
Reference Current Included
Frequency
Frequency
2
2.5
HISTOGRAM OF CURRENT CONSUMPTION
1500
1000
AVDD = Vref = 2.7 V
Reference Current Included
1000
500
500
0
1
VLOGIC (V)
HISTOGRAM OF CURRENT CONSUMPTION
1500
0.5
VLOGIC (V)
0
725
750
775
800
825 850 875
IDD (µA)
900
925
950
600 625 650 675 700 725 750 775 800 825 850 875
975
IDD (µA)
Figure 21.
Figure 22.
POWER SPECTRAL DENSITY
TOTAL HARMONIC DISTORTION
vs
OUTPUT FREQUENCY
−40
AVDD = 5 V,
Vref = 4.096,
fclk = 1 MSPS,
Fout = 1 kHz,
THD = 79 dB,
SNR = 96 dB
Gain dB
−30
−50
AVDD = Vref = 5 V,
−1 dB FSR Digital Input, Fs = 1 MSPS
Measurement Bandwidth = 20 kHz
−50
−60
THD (dB)
−10
−70
THD
−70
−90
−80
−110
−90
2nd Harmonic
3rd Harmonic
−130
0
5000
10000
Frequency − Hz
Figure 23.
15000
20000
−100
0
1
2
3
Output Tone (kHz)
4
5
Figure 24.
9
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TYPICAL CHARACTERISTICS (continued)
At TA = 25°C, unless otherwise noted
FULL-SCALE SETTLING TIME: 5 V RISING EDGE
FULL-SCALE SETTLING TIME: 5 V FALLING EDGE
Trigger Pulse
5 V/div
Trigger Pulse
5 V/div
AVDD = 5 V,
Vref = 4.096 V,
From Code: 0000
To Code: FFFF
Rising
Edge
1 V/div
Zoomed Rising Edge
1 mV/div
AVDD = 5 V,
Vref = 4.096 V,
From Code: FFFF
To Code: 0000
Falling
Edge
1 V/div
Zoomed Falling Edge
1 mV/div
Time (2 µs/div)
Time (2 µs/div)
Figure 25.
Figure 26.
HALF-SCALE SETTLING TIME: 5 V RISING EDGE
HALF-SCALE SETTLING TIME: 5 V FALLING EDGE
Trigger Pulse
5 V/div
Trigger Pulse
5 V/div
Falling
Edge
1 V/div
AVDD = 5 V,
Vref = 4.096 V,
From Code: CFFF
To Code: 4000
AVDD = 5 V,
Vref = 4.096 V,
From Code: 4000
To Code: CFFF
Rising
Edge
1 V/div
Zoomed Rising Edge
1 mV/div
Zoomed Falling Edge
1 mV/div
Time (2 µs/div)
Time (2 µs/div)
Figure 27.
Figure 28.
FULL-SCALE SETTLING TIME: 2.7 V RISING EDGE
FULL-SCALE SETTLING TIME: 2.7 V FALLING EDGE
Trigger Pulse
2.7 V/div
Trigger Pulse
2.7 V/div
Rising
Edge
0.5 V/div
Zoomed Rising Edge
1 mV/div
Time (2 µs/div)
Figure 29.
10
AVDD = 2.7 V,
Vref = 2.5 V,
From Code: FFFF
To Code: 0000
AVDD = 2.7 V,
Vref = 2.5 V,
From Code: 0000
To Code: FFFF
Zoomed Falling Edge
1 mV/div
Falling
Edge
0.5 V/div
Time (2 µs/div)
Figure 30.
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
TYPICAL CHARACTERISTICS (continued)
At TA = 25°C, unless otherwise noted
HALF-SCALE SETTLING TIME: 2.7 V RISING EDGE
HALF-SCALE SETTLING TIME: 2.7 V FALLING EDGE
Trigger Pulse
2.7 V/div
Trigger Pulse
2.7 V/div
AVDD = 2.7 V,
Vref = 2.5 V,
From Code: CFFF
To Code: 4000
VDD = 2.7 V
VREF = 2.5 V
From code; 4000
To code: CFFF
Rising
Edge
0.5 V/div
Falling
Edge
0.5 V/div
Zoomed Rising Edge
1 mV / div
Zoomed Falling Edge
1 mV/div
Time (2 µs/div)
Time − 2 s/div
Figure 32.
GLITCH ENERGY: 5 V, 1 LSB STEP, RISING EDGE
GLITCH ENERGY: 5 V, 1 LSB STEP, FALLING EDGE
AVDD = 5 V,
Vref = 4.096 V
From Code: 7FFF
To Code: 8000
Glitch: 0.08 nV-s
AVDD = 5 V,
Vref = 4.096 V
From Code: 8000
To Code: 7FFF
Glitch: 0.16 nV-s
Measured Worst Case
VOUT(500 V/div)
VOUT (500 V/div)
Figure 31.
Time 400 ns/div
Time 400 ns/div
GLITCH ENERGY: 5 V, 16 LSB STEP, RISING EDGE
GLITCH ENERGY: 5 V, 16 LSB STEP, FALLING EDGE
AVDD = 5 V,
Vref = 4.096 V
From Code: 8000
To Code: 8010
Glitch: 0.04 nV-s
Time 400 ns/div
Figure 35.
VOUT (500 V/div)
Figure 34.
VOUT(500 V/div)
Figure 33.
AVDD = 5 V,
Vref = 4.096 V
From Code: 8010
To Code: 8000
Glitch: 0.08 nV-s
Time 400 ns/div
Figure 36.
11
DAC8554
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TYPICAL CHARACTERISTICS (continued)
At TA = 25°C, unless otherwise noted
AVDD = 5 V,
Vref = 4.096 V
From Code: 8000
To Code: 80FF
Glitch: Not Detected
Theoretical Worst Case
GLITCH ENERGY: 5 V, 256 LSB STEP, FALLING EDGE
AVDD = 5 V,
Vref = 4.096 V
From Code: 80FF
To Code: 8000
Glitch: Not Detected
Theoretical Worst Case
VOUT(5 mV/div)
VOUT(5 mV/div)
GLITCH ENERGY: 5 V, 256 LSB STEP, RISING EDGE
Figure 37.
Figure 38.
GLITCH ENERGY:; 2.7 V, 1 LSB STEP, RISING EDGE
GLITCH ENERGY: 2.7 V, 1 LSB STEP, FALLING EDGE
AVDD = 2,7 V,
Vref = 2.5 V
From Code: 7FFF
To Code: 8000
Glitch: 0.08 nV-s
VOUT(200 V/div)
Time 400 ns/div
VOUT(200 V/div)
Time 400 ns/div
AVDD = 2.7 V,
Vref = 2.5 V
From Code: 8000
To Code: 7FFF
Glitch: 0.16 nV-s
Measured Worst Case
Time 400 ns/div
GLITCH ENERGY: 2.7 V, 16 LSB STEP, RISING EDGE
GLITCH ENERGY: 2.7 V, 16 LSB STEP, FALLING EDGE
AVDD = 2.7 V,
Vref = 2.5 V
From Code: 8000
To Code: 8010
Glitch: 0.04 nV-s
Figure 41.
AVDD = 2.7 V,
Vref = 2.5 V
From Code: 8010
To Code: 8000
Glitch: 0.12 nV-s
V/div)
VOUT (200 uV/div)
Figure 40.
VOUT(200 uV/div)
Figure 39.
Time 400 ns/div
12
Time 400 ns/div
Time 400 ns/div
Figure 42.
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
TYPICAL CHARACTERISTICS (continued)
At TA = 25°C, unless otherwise noted
GLITCH ENERGY: 2.7 V, 16 LSB STEP, FALLING EDGE
AVDD = 2.7 V,
Vref = 2.5 V
From Code: 80FF
To Code: 8000
Glitch: Not Detected
Theoretical Worst Case
VOUT (5 mV/div)
VOUT(5 mV/div)
GLITCH ENERGY: 2.7 V, 16 LSB STEP, RISING EDGE
AVDD = 2.7 V,
Vref = 2.5 V
From Code: 8000
To Code: 80FF
Glitch: Not Detected
Theoretical Worst Case
Time 400 ns/div
Time 400 ns/div
Figure 43.
Figure 44.
OUTPUT NOISE DENSITY
SIGNAL-TO-NOISE RATIO
vs
OUTPUT FREQUENCY
98
350
AVDD = 5 V,
V
ref = 4.096 V,
Code = 7FFF
No Load
94
SNR (dB)
Noise − nV/
Hz
300
AVDD = Vref = 5 V,
−1 dB FSR Digital Inputs, Fs = 1 MSPS
Measurement Bandwidth = 20 kHz
96
250
200
92
90
88
150
86
100
100
84
1000
10000
Frequency − Hz
Figure 45.
100000
0
0.5
1
1.5
2
2.5
3
3.5
Output Tone (kHz)
4
4.5
5
Figure 46.
13
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
THEORY OF OPERATION
VREFH
DAC SECTION
The architecture of each channel of the DAC8554
consists of a resistor-string DAC followed by an
output buffer amplifier. Figure 47 shows a simplified
block diagram of the DAC architecture.
Ω
Ω
RDIVIDER
VREF
2
R
62 Ω
R
To Output
Amplifier
(2x Gain)
Figure 47. DAC8554 Architecture
The input coding for each device is unipolar straight
binary, so the ideal output voltage is given by:
V
OUT
X 2V
REF
L V
REF
HV
REF
L D
IN
65536
where DIN = decimal equivalent of the binary code
that is loaded to the DAC register; it can range from 0
to 65535.
R
R
RESISTOR STRING
The resistor string section is shown in Figure 48. It is
simply a divide-by-2 resistor followed by a string of
resistors. The code loaded into the DAC register
determines at which node on the string the voltage is
tapped off. This voltage is then applied to the output
amplifier by closing one of the switches connecting
the string to the amplifier.
OUTPUT AMPLIFIER
Each output buffer amplifier is capable of generating
rail-to-rail voltages on its output which approaches an
output range of 0 V to AVDD (gain and offset errors
must be taken into account). Each buffer is capable
of driving a load of 2 kΩ in parallel with 1000 pF to
GND. The source and sink capabilities of the output
amplifier can be seen in the typical characteristics.
SERIAL INTERFACE
The DAC8554 uses a 3-wire serial interface ( SYNC,
SCLK, and DIN), which is compatible with SPI™,
QSPI™, and Microwire™ interface standards, as well
as most DSPs. See the serial write operation timing
diagram for an example of a typical write sequence.
14
VREFL
Figure 48. Resistor String
The write sequence begins by bringing the SYNC line
LOW. Data from the DIN line is clocked into the 24-bit
shift register on each falling edge of SCLK. The serial
clock frequency can be as high as 50 MHz, making
the DAC8554 compatible with high-speed DSPs. On
the 24th falling edge of the serial clock, the last data
bit is clocked into the shift register and the shift
register gets locked. Further clocking does not
change the shift register data. Once 24 bits are
locked into the shift register, the 8 MSBs are used as
control bits and the 16 LSBs are used as data. After
receiving the 24th falling clock edge, DAC8554 decodes the 8 control bits and 16 data bits to perform
the required function, without waiting for a SYNC
rising edge. A new SPI sequence starts at the next
falling edge of SYNC. A rising edge of SYNC before
the 24-bit sequence is complete resets the SPI
interface; no data transfer occurs.
After the 24th falling edge of SCLK is received, the
SYNC line may be kept LOW or brought HIGH. In
either case, the minimum delay time from the 24th
falling SCLK edge to the next falling SYNC edge
must be met in order to properly begin the next cycle.
DAC8554
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To assure the lowest power consumption of the
device, care should be taken that the levels are as
close to each rail as possible. (Refer to the Typical
Characteristics section for the Supply Current vs
Logic Input Voltage transfer characteristic curve.
IOVDD AND VOLTAGE TRANSLATORS
The IOVDD pin powers the digital input structures of
the DAC8554. For single-supply operation, it can be
tied to AVDD. For dual-supply operation, the IOVDD pin
provides interface flexibility with various CMOS logic
families and it should be connected to the logic
supply of the system. Analog circuits and internal
logic of the DAC8554 use AVDD as the supply
voltage. The external logic high inputs get translated
to AVDD by level shifters. These level shifters use the
IOVDD voltage as a reference to shift the incoming
logic HIGH levels to AVDD. IOVDD is ensured to
operate from 2.7 V to 5.5 V regardless of the AVDD
voltage, which ensures compatibility with various logic
families. Although specified down to 2.7 V, IOVDD will
operate at as low as 1.8 V with degraded timing and
temperature performance. For lowest power consumption, logic VIH levels should be as close as
possible to IOVDD, and logic VIL levels should be as
close as possible to GND voltages
INPUT SHIFT REGISTER
The input shift register (SR) of the DAC8554 is 24
bits wide, as shown in Figure 49, and is made up of 8
control bits (DB23–DB16) and 16 data bits
(DB15–DB0). The first two control bits (DB23 and
DB22) are the address match bits. The DAC8554
offers additional hardware-enabled addressing capability allowing a single host to talk to up to four
DAC8554s through a single SPI bus without any glue
logic, enabling up to 16-channel operation. The state
of DB23 should match the state of pin A1; similarly,
the state of DB22 should match the state of pin A0. If
there is no match, the control command and the data
(DB21...DB0) are ignored by the DAC8554. That is, if
there is no match, the DAC8554 is not addressed.
Address matching can be overridden by the broadcast update, as will be explained.
LD1 (DB21) and LD0 (DB20) control the updating of
each analog output with the specified 16-bit data
value or power-down command. Bit DB19 is a Don't
Care bit which does not affect the operation of the
DAC8554 and can be 1 or 0. The DAC channel select
bits (DB18, DB17) control the destination of the data
(or power-down command) from DAC A through DAC
D. The final control bit, PD0 (DB16), selects the
power-down mode of the DAC8554 channels.
The DAC8554 also supports a number of different
load commands. The load commands include broadcast commands to address all the DAC8554s on an
SPI bus. The load commands can be summarized as
follows:
DB21 = 0 and DB20 = 0: Single-channel store. The
temporary register (data buffer) corresponding to a
DAC selected by DB18 and DB17 is updated with the
contents of SR data (or power-down).
DB21 = 0 and DB20 = 1: Single-channel update. The
temporary register and DAC register corresponding to
a DAC selected by DB18 and DB17 are updated with
the contents of SR data (or power-down).
DB21 = 1 and DB20 = 0: Simultaneous update. A
channel selected by DB18 and DB17 gets updated
with the SR data, and simultaneously, all the other
channels get updated with previous stored data (or
power-down) from temporary registers.
DB21 = 1 and DB20 = 1: Broadcast update. All the
DAC8554s on the SPI bus respond, regardless of
address matching. If DB18 = 0, then SR data gets
ignored, all channels from all DAC8554s get updated
with previously stored data (or power-down). If DB18
= 1, then SR data (or power-down) updates all
channels of all DAC8554s in the system. This broadcast update feature allows the simultaneous update
of up to 16 channels.
Power-down/data selection is as follows:
DB16 is a power-down flag. If this flag is set, then
DB15 and DB14 select one of the four power-down
modes of the device as described in Table 1. If DB16
= 1, DB15 and DB14 no longer represent the two
MSBs of data, they represent a power-down condition
described in Table 1. Similar to data, power-down
conditions can be stored at the temporary registers of
each DAC. It is possible to update DACs simultaneously either with data, power-down, or a combination of both.
Refer to Table 2 for more information.
15
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
Table 1. DAC8554 Power-Down Modes
PD0 (DB16)
PD1 (DB15)
PD2 (DB14)
OPERATING MODE
1
0
0
Output high impedance
1
0
1
Output typically 1 kΩ to GND
1
1
0
Output typically 100 kΩ to GND
1
1
1
Output high impedance
SYNC INTERRUPT
POWER-ON RESET
In a normal write sequence, the SYNC line is kept
LOW for at least 24 falling edges of SCLK and the
addressed DAC register is updated on the 24th falling
edge. However, if SYNC is brought HIGH before the
24th falling edge, it acts as an interrupt to the write
sequence; the shift register is reset and the write
sequence is discarded. Neither an update of the data
buffer contents, DAC register contents, nor a change
in the operating mode occurs (see Figure 50).
The DAC8554 contains a power-on reset circuit that
controls the output voltage during power-up. On
power-up, the DAC registers are filled with zeros and
the output voltages are set to zero-scale; they remain
there until a valid write sequence and load command
is made to the respective DAC channel. This is useful
in applications where it is important to know the state
of the output of each DAC while the device is in the
process of powering up. No device pin should be
brought high before power is applied to the device.
DB23
A1
DB12
A0
LD1
LD0
X
DAC Select 1
DAC Select 0
PD0
D15
D14
D13
D12
DB11
D11
DB0
D10
D9
D8
D7
D6
D5
D4
D3
D2
D1
D0
Figure 49. DAC8554 Data Input Register Format
Table 2. Control Matrix
DB23
DB22
DB21
DB20
DB19
DB18
DB17
DB16
DB15
DB14
DB13-DB0
A1
A0
LD 1
LD 0
Don't
Care
DAC Sel 1
DAC Sel 0
PD0
MSB
MSB-1
MSB-2...LSB
DESCRIPTION
(Address Select)
0/1
0/1
A0 and A1 should
correspond to the
package address
set via pins 13
and 14.
See Below
This address selects 1 of 4 possible devices on a
single SPI data bus based on each device's address
pin(s) state.
0
0
X
0
0
0
Data
Write to buffer A with data
0
0
X
0
1
0
Data
Write to buffer B with data
0
0
X
1
0
0
Data
Write to buffer C with data
0
0
X
1
1
0
Data
0
0
X
(00, 01, 10, or 11)
1
0
1
X
(00, 01, 10, or 11)
0
0
1
X
(00, 01, 10, or 11)
1
1
0
X
(00, 01, 10, or 11)
0
1
0
X
(00, 01, 10, or 11)
1
See Table 1
Write to buffer D with data
0
Data
See Table 1
Write to buffer with data and load DAC (selected by
DB17 and DB18)
0
Data
See Table 1
Write to buffer (selected by DB17 and DB18) with
power-down command
Write to buffer with power-down command and load
DAC (selected by DB17 and DB18)
Write to buffer with data (selected by DB17 and DB18)
and then load all DACs simultaneously from their
corresponding buffers.
0
Write to buffer with power-down command (selected by
DB17 and DB18) and then load all DACs simultaneously from their corresponding buffers.
Broadcast Modes
16
X
X
1
1
X
0
X
X
X
X
1
1
X
1
X
0
X
X
1
1
X
1
X
1
X
Simultaneously update all channels of all DAC8554
devices in the system with data stored in each channels temporary register.
Data
See Table 1
Write to all devices and load all DACs with SR data
0
Write to all devices and load all DACs with power-down
command in SR.
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
24th Falling
Edge
SCLK
1
2
1
24th Falling
Edge
2
SYNC
Invalid Write-Sync Interrupt:
SYNC HIGH Before 24th Falling Edge
DIN
DB23 DB22
DB0
Valid Write-Buffer/DAC Update:
SYNC HIGH After 24th Falling Edge
DB23 DB22
DB1
DB0
Figure 50. Interrupt and Valid SYNC Timing
POWER-DOWN MODES
The DAC8554 utilizes four modes of operation. These
modes are accessed by setting three bits (PD2, PD1,
and PD0) in the shift register and performing a Load
action to the DACs. The DAC8554 offers a very
flexible power-down interface based on channel
register operation. A channel consists of a single
16-bit DAC with power-down circuitry, a temporary
storage register (TR), and a DAC register (DR). TR
and DR are both 18-bit wide. Two MSBs represent
power-down condition and 16 LSBs represent data
for TR and DR. By adding bits 17 and 18 to TR and
DR, a power-down condition can be temporarily
stored and used just like data. Internal circuits ensure
that DB15 and DB14 get transferred to TR17and
TR16 (DR17 and DR16), when DB16 = 1.
The DAC8554 treats the power-down condition like
data and all the operational modes are still valid for
power-down. It is possible to broadcast a power-down
condition to all the DAC8554s in a system, or it is
possible to simultaneously power-down a channel
while updating data on other channels.
Individual channels can separately be powered down,
reducing the total power consumption. When all
channels are powered down, the DAC8554 power
consumption drops below 2 µA. There is no power
-up command. When a channel is updated with data,
it automatically exits power-down. All channels exit
power-down simultaneously after a broadcast data
update. The time to exit power-down is approximately
5 µs. See Table 1 and Table 2 for power-down
operation details.
Resistor
String DAC
Amplifier
Power-down
Circuitry
VOUTX
Resistor
Network
Figure 51. Output Stage During Power-Down
(High-Impedance)
DB16, DB15, and DB14 = 100 (or 111) represent a
power-down condition with Hi-Z output impedance for
a selected channel. 101 represents a power-down
condition with 1k output impedance and 110 represents a power-down condition with 100k output
impedance.
17
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
OPERATION EXAMPLES
Example 1: Write to data buffer A; through buffer D; load DAC A through DAC D simultaneously
• 1st — Write to data buffer A:
•
•
•
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
—
DB1
DB0
0
0
0
0
X
0
0
0
D15
—
D1
D0
2nd — Write to data buffer B:
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
—
DB1
DB0
0
0
0
0
X
0
1
0
D15
—
D1
D0
3rd — Write to data buffer C:
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
—
DB1
DB0
0
0
0
0
X
1
0
0
D15
—
D1
D0
4th — Write to data buffer D and simultaneously update all DACs:
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
—
DB1
DB0
0
0
1
0
X
1
1
0
D15
—
D1
D0
The DAC A, DAC B, DAC C, and DAC D analog outputs simultaneously settle to the specified values upon
completion of the 4th write sequence. (The DAC voltages update simultaneously after the 24th SCLK falling edge
of the 4th write cycle).
Example 2: Load New Data to DAC A through DAC D sequentially
• 1st — Write to data buffer A and load DAC A: DAC A output settles to specified value upon completion:
•
•
•
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
—
DB1
DB0
0
0
0
1
X
0
0
0
D15
—
D1
D0
2nd — Write to data buffer B and load DAC B: DAC B output settles to specified value upon completion:
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
—
DB1
DB0
0
0
0
1
X
0
1
0
D15
—
D1
D0
3rd — Write to data buffer C and load DAC C: DAC C output settles to specified value upon completion:
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
—
DB1
DB0
0
0
0
1
X
1
0
0
D15
—
D1
D0
4th — Write to data buffer D and load DAC D: DAC D output settles to specified value upon completion:
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
—
DB1
DB0
0
0
0
1
X
1
1
0
D15
—
D1
D0
After completion of each write cycle, DAC analog output settles to the voltage specified.
Example 3: Power-down DAC A and DAC B to 1 kΩ and Power-down DAC C and DAC D to 100 kΩ
simultaneously
• Write power-down command to data buffer A: DAC A to 1 kΩ.
•
•
18
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
DB14
DB13
—
0
0
0
0
X
0
0
1
0
1
X
—
Write power-down command to data buffer B: DAC B to 1 kΩ.
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
DB14
DB13
—
0
0
0
0
X
0
1
1
0
1
X
—
Write power-down command to data buffer C: DAC C to 1 kΩ.
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
DB14
DB13
—
0
0
0
0
X
1
0
1
1
0
X
—
DAC8554
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SLAS431A – JUNE 2005 – REVISED AUGUST 2005
•
Write power-down command to data buffer D: DAC D to 100 kΩ and simultaneously update all DACs.
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
DB14
DB13
—
0
0
1
0
X
1
1
1
1
0
X
—
The DAC A, DAC B, DAC C, and DAC D analog outputs simultaneously power-down to each respective specified
mode upon completion of the 4th write sequence.
Example 4: Power-Down DAC A Through DAC D to High-Impedance Sequentially:
• Write power-down command to data buffer A and load DAC A: DAC A output = Hi-Z:
•
•
•
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
DB14
DB13
—
0
0
0
1
X
0
0
1
1
1
X
—
Write power-down command to data buffer B and load DAC B: DAC B output = Hi-Z:
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
DB14
DB13
—
0
0
0
1
X
0
1
1
1
1
x
—
Write power-down command to data buffer C and load DAC C: DAC C output = Hi-Z:
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
DB14
DB13
—
0
0
0
1
X
1
0
1
1
1
X
—
Write power-down command to data buffer D and load DAC D: DAC D output = Hi-Z:
A1
A0
LD1
LD0
DC
DAC Sel 1
DAC Sel 0
PD0
DB15
DB14
DB13
—
0
0
0
1
X
1
1
1
1
1
X
—
The DAC A, DAC B, DAC C, and DAC D analog
outputs sequentially power-down to high-impedance
upon completion of the 1st, 2nd, 3rd, and 4th write
sequences, respectively.
LDAC FUNCTIONALITY
The DAC8554 offers both a software and hardware
simultaneous update function. The DAC8554
double-buffered architecture has been designed so
that new data can be entered for each DAC without
disturbing the analog outputs. The software simultaneous update capability is controlled by the load 1
(LD1) and load 0 (LD0) control bits. By setting load 1
equal to 1 all of the DAC registers will be updated on
the falling edge of the 24th clock signal. When the
new data has been entered into the device, all of the
DAC outputs can be updated simultaneously and
synchronously with the clock.
DAC8554 data updates are synchronized with the
falling edge of the 24th SCLK cycle, which follows a
falling edge of SYNC. For such synchronous updates,
the LDAC pin is not required and it must be connected to GND permanently. The LDAC pin is used as a
positive edge triggered timing signal for asynchronous DAC updates. Data buffers of all channels must
be loaded with desired data before LDAC is triggered.
After a low-to-high LDAC transition, all DACs are
simultaneously updated with the contents of their
corresponding data buffers. If the content of a data
buffer is not changed by the serial interface, the
corresponding DAC output will remain unchanged
after the LDAC trigger.
ENABLE PIN
For normal operation, the enable pin must be tied to
a logic low. If the enable pin is tied high, the
DAC8554 stops listening to the serial port. This can
be useful for applications that share the same serial
port.
MICROPROCESSOR INTERFACING
DAC8554 TO 8051 Interface
See Figure 52 for a serial interface between the
DAC8554 and a typical 8051-type micro controller.
The setup for the interface is as follows: TXD of the
8051 drives SCLK of the DAC8554, while RXD drives
the serial data line of the device. The SYNC signal is
derived from a bit-programmable pin on the port of
the 8051. In this case, port line P3.3 is used. When
data is to be transmitted to the DAC8554, P3.3 is
taken LOW. The 8051 transmits data in 8-bit bytes;
thus only eight falling clock edges occur in the
transmit cycle. To load data to the DAC, P3.3 is left
LOW after the first eight bits are transmitted, then a
second and third write cycle is initiated to transmit the
remaining data. P3.3 is taken HIGH following the
completion of the third write cycle. The 8051 outputs
the serial data in a format which presents the LSB
first, while the DAC8554 requires its data with the
MSB as the first bit received. The 8051 transmit
routine must therefore take this into account, and
mirror the data as needed.
19
DAC8554
www.ti.com
SLAS431A – JUNE 2005 – REVISED AUGUST 2005
80C51/80L51(1)
DAC8554
P3.3
SYNC
TXD
SCLK
RXD
DIN
(1) Additional pins omitted for clarity.
Figure 52. DAC8554 to 80C51/80L51 Interface
causes data appearing on the MOSI output to be
valid on the falling edge of SCLK. When data is being
transmitted to the DAC, the SYNC line is held LOW
(PC7). Serial data from the 68HC11 is transmitted in
8-bit bytes with only eight falling clock edges
occurring in the transmit cycle. (Data is transmitted
MSB first.) In order to load data to the DAC8554,
PC7 is left LOW after the first eight bits are transferred, then a second and third serial write operation
is performed to the DAC. PC7 is taken HIGH at the
end of this procedure.
DAC8554 to Microwire Interface
Figure 53 shows an interface between the DAC8554
and any Microwire compatible device. Serial data is
shifted out on the falling edge of the serial clock and
is clocked into the DAC8554 on the rising edge of the
CK signal.
MicrowireTM
DAC8554 to TMS320 DSP Interface
Figure 55 shows the connections between the
DAC8554 and a TMS320 Digital Signal Processor
(DSP). A Single DSP can control up to four
DAC8554s without any interface logic.
DAC8554
DAC8554
CS
SYNC
SK
SCLK
SO
DIN
Positive Supply
AVDD
0.1∝F
10∝F
TMS320 DSP
FSX
SYNC
(1) Additional pins omitted for clarity.
DX
DIN
Microwire is a registered trademark of National Semiconductor.
CLKX
Figure 53. DAC8554 to Microwire Interface
SCLK
VOUTA
Output A
VOUTD
Output D
VREFL
DAC8554 to 68HC11 Interface
DAC8554
PC7
SYNC
SCK
SCLK
MOSI
DIN
(1) Additional pins omitted for clarity.
Figure 54. DAC8554 to 68HC11 Interface
The 68HC11 should be configured so that its CPOL
bit is 0 and its CPHA bit is 1. This configuration
20
0.1∝F
1∝F to 10∝F
GND
Figure 54 shows a serial interface between the
DAC8554 and the 68HC11 micro controller. SCK of
the 68HC11 drives the SCLK of the DAC8554, while
the MOSI output drives the serial data line of the
DAC. The SYNC signal is derived from a port line
(PC7), similar to the 8051 diagram.
68HC11(1)
Reference
Input
VREFH
Figure 55. DAC8554 to TMS320 DSP
DAC8554
www.ti.com
SLAS431A – JUNE 2005 – REVISED AUGUST 2005
APPLICATION INFORMATION
CURRENT CONSUMPTION
OUTPUT VOLTAGE STABILITY
The DAC8554 consumes a maximum of 250 µA at
AVDD = 5 V and 240 µA at AVDD = 3 V for each active
channel, including reference current consumption.
Additional current consumption can occur at the
digital inputs if VIH << IOVDD. For most efficient power
operation, CMOS logic levels are recommended at
the digital inputs to the DAC.
The DAC8554 exhibits excellent temperature stability
of 5 ppm/°C typical output voltage drift over the
specified temperature range of the device. This enables the output voltage of each channel to stay
within a ±25 µV window for a ±1°C ambient temperature change.
In power-down mode, typical current consumption is
200 nA per channel. A delay time of 10 ms to 20 ms
after a power-down command is issued to the DAC is
typically sufficient for the power-down current to drop
below 10 µA.
Good power-supply rejection ratio (PSRR) performance reduces supply noise present on AVDD from
appearing at the outputs to well below 10 µV-s.
Combined with good dc noise performance and true
16-bit differential linearity, the DAC8554 becomes a
perfect choice for closed-loop control applications.
DRIVING RESISTIVE AND CAPACITIVE
LOADS
SETTLING TIME AND OUTPUT GLITCH PERFORMANCE
The DAC8554 output stage is capable of driving
loads of up to 1000 pF while remaining stable. Within
the offset and gain error margins, the DAC8554 can
operate rail-to-rail when driving a capacitive load.
Resistive loads of 2 kΩ can be driven by the
DAC8554 while achieving good load regulation.
When the outputs of the DAC are driven to the
positive rail under resistive loading, the PMOS transistor of each Class-AB output stage can enter into
the linear region. When this occurs, the added IR
voltage drop deteriorates the linearity performance of
the DAC. This only occurs within approximately the
top 100 mV of the DAC's output voltage characteristic. Under resistive loading conditions, good linearity
is preserved as long as the output voltage is at least
100 mV below the AVDD voltage.
DAC8554 settles to ±0.003% of its full-scale range
within 10 µs, driving a 200 pF 2 KΩ load. For good
settling performance the outputs should not approach
the top and bottom rails. Small signal settling time is
under 1 µs, enabling data update rates exceeding 1
MSPS for small code changes.
CROSSTALK AND AC PERFORMANCE
The DAC8554 architecture uses separate resistor
strings for each DAC channel in order to achieve
ultra-low crosstalk performance. DC crosstalk seen at
one channel during a full-scale change on the
neighboring channel is typically less than 0.5LSBs.
The AC crosstalk measured (for a full-scale, 1 kHz
sine wave output generated at one channel, and
measured at the remaining output channel) is typically under –100 dB.
In addition, the DAC8554 can achieve typical AC
performance of 96 dB signal-to-noise ratio (SNR) and
85 dB total harmonic distortion (THD), making the
DAC8554 a solid choice for applications requiring
high SNR at output frequencies at or below 10 kHz.
Many applications are sensitive to undesired transient
signals such as glitch. DAC8554 has a proprietary,
ultra-low glitch architecture addressing such applications. Code-to-code glitches rarely exceed millivolt
and they last under 0.3 µs. Typical glitch energy is an
outstanding 0.15 nV-s. Theoretical worst cast glitch
should occur during a 256 LSB step, but it is so low, it
cannot be detected.
DIFFERENTIAL AND INTERGRAL
NONLINEARITY
DAC8554 uses precision thin film resistors to achieve
monotonicity and good linearity. Typical linearity error
is ±4 LSBs; ±0.3 mV error for a 5 V range. Differential
linearity is typically ±0.25 LSBs, ±19 µV error for a
consecutive code change.
USING THE REF02 AS A POWER SUPPLY
FOR THE DAC8554
Due to the extremely low supply current required by
the DAC8554, a possible configuration is to use a
REF02 +5 V precision voltage reference to supply the
required voltage to the DAC8554s supply input as
well as the reference input, as shown in Figure 56.
This is especially useful if the power supply is quite
noisy or if the system supply voltages are at some
value other than 5 V. The REF02 will output a steady
supply voltage for the DAC8554. If the REF02 is
21
DAC8554
www.ti.com
SLAS431A – JUNE 2005 – REVISED AUGUST 2005
used, the current it needs to supply to the DAC8554
is 0.85 mA typical for AVDD = 5 V. When a DAC
output is loaded, the REF02 also needs to supply the
current to the load. The total typical current required
(with a 5 kΩ load on a given DAC output) is:
0.85 mA + (5V/5 kΩ) = 1.085 mA
DAC8554
-
Figure 57. Bipolar Operation With the DAC8554
LAYOUT
DAC8554
Figure 56. REF02 as a Power Supply to the
DAC8554
BIPOLAR OPERATION USING THE DAC8554
The DAC8554 has been designed for single-supply
operation, but a bipolar output range is also possible
using the circuit in Figure 57. The circuit shown will
give an output voltage range of ±Vref. Rail-to-rail
operation at the amplifier output is achievable using
an amplifier such as the OPA703, as shown in
REFFigure 57.
The output voltage for any input code can be calculated as follows:
V
OUT
X V
ref
D R1 R2 V R2
65536
ref
R1
R1
where D represents the input code in decimal
(0–65535).
With Vref = 5 V, R1 = R2 = 10 kΩ.
V
OUT
X 10 D 5 V
65536
This is an output voltage range of ±5 V with 0000H
corresponding to a –5 V output and FFFFH corresponding to a 5 V output. Similarly, using Vref = 2.5 V
a ± 2.5 V output voltage range can be achieved.
22
A precision analog component requires careful layout,
adequate bypassing, and clean, well-regulated power
supplies.
The DAC8554 offers single-supply operation, and it
will often be used in close proximity with digital logic,
micro controllers, microprocessors, and digital signal
processors. The more digital logic present in the
design and the higher the switching speed, the more
difficult it will be to keep digital noise from appearing
at the output.
Due to the single ground pin of the DAC8554, all
return currents, including digital and analog return
currents for the DAC, must flow through a single
point. Ideally, GND would be connected directly to an
analog ground plane. This plane would be separate
from the ground connection for the digital
components until they were connected at the
power-entry point of the system.
The power applied to AVDD should be well regulated
and low noise. Switching power supplies and DC/DC
converters will often have high-frequency glitches or
spikes riding on the output voltage. In addition, digital
components can create similar high-frequency spikes
as their internal logic switches states. This noise can
easily couple into the DAC output voltage through
various paths between the power connections and
analog output.
As with the GND connection, AVDD should be connected to a positive power-supply plane or trace that
is separate from the connection for digital logic until
they are connected at the power-entry point. In
addition, a 1 µF to 10 µF capacitor in parallel with a
0.1 µF bypass capacitor is strongly recommended. In
some situations, additional bypassing may be required, such as a 100 µF electrolytic capacitor or
even a Pi filter made up of inductors and capacitors –
all designed to essentially low-pass filter the supply,
removing the high-frequency noise.
DAC8554
www.ti.com
SLAS431A – JUNE 2005 – REVISED AUGUST 2005
Up to four DAC8554 devices can be used on a single
SPI bus without any glue logic to create a high
channel count solution. Special attention is required
to avoid digital signal integrity problems when using
multiple DAC8554s on the same SPI bus. Signal
integrity of SYNC, SCLK, and DIN lines will not be an
issue as long as the rise times of these digital signals
are longer than six times the propagation delay
between any two DAC8554 devices. Propagation
speed is approximately six inches/ns on standard
PCBs. Therefore, if the digital signal rise time is 1 ns,
the distance between any two DAC8554s have to be
further apart on the PCB, the signal rise times should
be reduced by placing series resistors at the drivers
for SYNC, SCLK, and DIN lines. If the largest distance
between any two DAC8554s must to be six inches,
the rise time should be reduced to 6 ns with an RC
network formed by the series resistor at the digital
driver and the total trace and input capacitance on
the PCB.
23
PACKAGE OPTION ADDENDUM
www.ti.com
13-Sep-2005
PACKAGING INFORMATION
Orderable Device
Status (1)
Package
Type
Package
Drawing
Pins Package Eco Plan (2)
Qty
DAC8554IPW
ACTIVE
TSSOP
PW
16
90
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-1-260C-UNLIM
DAC8554IPWG4
ACTIVE
TSSOP
PW
16
90
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-1-260C-UNLIM
DAC8554IPWR
ACTIVE
TSSOP
PW
16
2000 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-1-260C-UNLIM
DAC8554IPWRG4
ACTIVE
TSSOP
PW
16
2000 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-1-260C-UNLIM
Lead/Ball Finish
MSL Peak Temp (3)
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS) or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is
provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the
accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take
reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on
incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited
information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI
to Customer on an annual basis.
Addendum-Page 1
MECHANICAL DATA
MTSS001C – JANUARY 1995 – REVISED FEBRUARY 1999
PW (R-PDSO-G**)
PLASTIC SMALL-OUTLINE PACKAGE
14 PINS SHOWN
0,30
0,19
0,65
14
0,10 M
8
0,15 NOM
4,50
4,30
6,60
6,20
Gage Plane
0,25
1
7
0°– 8°
A
0,75
0,50
Seating Plane
0,15
0,05
1,20 MAX
PINS **
0,10
8
14
16
20
24
28
A MAX
3,10
5,10
5,10
6,60
7,90
9,80
A MIN
2,90
4,90
4,90
6,40
7,70
9,60
DIM
4040064/F 01/97
NOTES: A.
B.
C.
D.
All linear dimensions are in millimeters.
This drawing is subject to change without notice.
Body dimensions do not include mold flash or protrusion not to exceed 0,15.
Falls within JEDEC MO-153
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
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