Intersil EL1511CLZ-T13 Medium power differential line driver Datasheet

EL1511
®
Data Sheet
April 10, 2007
FN7016.2
Medium Power Differential Line Driver
Features
The EL1511 is a dual operational amplifier designed for
customer premise line driving in DMT ADSL solutions. This
device features a high drive capability of 360mA while
consuming only 7.5mA of supply current per amplifier and
operating from a single 5V to 15V supply. This driver
achieves a typical distortion of less than -85dBc, at 150kHz
into a 25Ω load. The EL1511 is available in the thermallyenhanced 16 Ld SOIC (0.150") and a 16 Ld QFN (4x4mm)
packages. The EL1511 is specified for operation over the full
-40°C to +85°C temperature range. Electrical characteristics
are given for typical 15V supply operation.
• Drives up to 360mA from a +15V supply
The EL1511 has two control pins, C0 and C1, which allow
the selection of full IS power, 3/4-IS, 1/2-IS, and power-down
modes.
Applications
The EL1511 is ideal for ADSL, SDSL, and HDSL2 line
driving applications for single power supply, high voltage
swing, and low power.
• ADSL full rate CPE line driving
The EL1511 maintains excellent distortion and load driving
capabilities even in the lowest power settings.
• 24VP-P differential output drive into 25Ω and 26VP-P
differential output drive into 100Ω
• -85dBc typical driver output distortion at full output at
150kHz
• Low quiescent current of 3.5mA per amplifier at 1/2-IS
current mode
• Disable down to 1.5mA
• Pb-free plus anneal available (RoHS compliant)
• ADSL CSA line driving
• G.SHDSL, HDSL2 line driver
• Video distribution amplifier
• Video twisted-pair line driver
Pinouts
NC 1
VIN-A 3
14 VIN-B
GND* 4
13 GND*
GND* 5
12 GND*
VIN+A 6
11 VIN+B
INA- 2
AMP
A
+
INA+ 3
VS- 8
10 C1
NC 5
POWER
CONTROL
LOGIC
13 OUTB
12 NC
11 INB10 INB+
POWER
CONTROL
LOGIC
GND 4
GND 7
AMP
B
+
9 C1
C0 8
15 VOUTB
14 VS+
+
-
VS- 7
+
-
NC 6
VOUTA 2
16 OUTA
16 VS+
NC 1
15 NC
EL1511
(16 LD QFN)
TOP VIEW
EL1511
[16 LD SO (0.150”)]
TOP VIEW
9 C0
NOTE: * These GND pins are heat spreaders
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 2003, 2005, 2007. All Rights Reserved
All other trademarks mentioned are the property of their respective owners.
EL1511
Ordering Information
PART NUMBER
PART MARKING
TAPE & REEL
PACKAGE
PKG. DWG. #
EL1511CS
EL1511CS
-
16 Ld SO (0.150”)
MDP0027
EL1511CS-T7
EL1511CS
7”
16 Ld SO (0.150”)
MDP0027
EL1511CS-T13
EL1511CS
13”
16 Ld SO (0.150”)
MDP0027
EL1511CSZ
(See Note)
EL1511CSZ
-
16 Ld SO (0.150”)
(Pb-Free)
MDP0027
EL1511CSZ-T7
(See Note)
EL1511CSZ
7”
16 Ld SO (0.150”)
(Pb-Free)
MDP0027
EL1511CSZ-T13
(See Note)
EL1511CSZ
13”
16 Ld SO (0.150”)
(Pb-Free)
MDP0027
EL1511CL
1511CL
-
16 Ld QFN
MDP0046
EL1511CL-T7
1511CL
7”
16 Ld QFN
MDP0046
EL1511CL-T13
1511CL
13”
16 Ld QFN
MDP0046
EL1511CLZ
(See Note)
1511CLZ
-
16 Ld QFN
(Pb-Free)
MDP0046
EL1511CLZ-T7
(See Note)
1511CLZ
7”
16 Ld QFN
(Pb-Free)
MDP0046
EL1511CLZ-T13
(See Note)
1511CLZ
13”
16 Ld QFN
(Pb-Free)
MDP0046
NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate
termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL
classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
2
FN7016.2
April 10, 2007
EL1511
Absolute Maximum Ratings (TA = +25°C)
VS+ to VS- Supply Voltage. . . . . . . . . . . . . . . . . . . . . . . . . . . . 16.5V
VS+ Voltage to Ground . . . . . . . . . . . . . . . . . . . . . . -0.3V to +16.5V
VS- Voltage to Ground . . . . . . . . . . . . . . . . . . . . . . . . -16.5V to 0.3V
Input C0/C1 to Ground . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7V
VIN+ Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . VS- to VS+
Current into any Input . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8mA
Continuous Output Current . . . . . . . . . . . . . . . . . . . . . . . . . . . 75mA
Operating Temperature Range . . . . . . . . . . . . . . . . .-40°C to +85°C
Storage Temperature Range . . . . . . . . . . . . . . . . . .-60°C to +150°C
Operating Junction Temperature . . . . . . . . . . . . . . .-40°C to +150°C
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
PARAMETER
VS = ±7.5V, RF = 1.5kΩ, RL = 100Ω to mid supply, TA = +25°C unless otherwise specified.
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
AC PERFORMANCE
BW
-3dB Bandwidth
AV = +4
70
MHz
HD
Total Harmonic Distortion
f = 150kHz, VO = 16VP-P, RL = 25Ω
-85
dBc
dG
Differential Gain
AV = +2, RL = 37.5Ω
0.15
%
dθ
Differential Phase
AV = +2, RL = 37.5Ω
0.1
°
SR
Slewrate
VOUT from -3V to +3V
500
V/µs
DC PERFORMANCE
VOS
Offset Voltage
-20
20
mV
ΔVOS
VOS Mismatch
-10
10
mV
ROL
Transimpedance
2.5
MΩ
VOUT from -4.5V to +4.5V
0.7
1.4
INPUT CHARACTERISTICS
IB+
Non-Inverting Input Bias Current
-5
5
µA
IB-
Inverting Input Bias Current
-30
30
µA
ΔIB-
IB- Mismatch
-30
30
µA
eN
Input Noise Voltage
2.8
nV/√ Hz
iN
-Input Noise Current
19
pA/√ Hz
VIH
Input High Voltage
C0 and C1 inputs
VIL
Input Low Voltage
C0 and C1 inputs
IIH1
Input High Current for C1
C1 = 5V
IIH0
Input High Current for C0
IIL
Input Low Current for C1or C0
2.3
V
1.5
V
0.2
8
µA
C0 = 5V
0.1
4
µA
C1 = 0V, C0 = 0V
-1
1
µA
OUTPUT CHARACTERISTICS
VOUT
IOUT
Loaded Output Swing (single ended)
VS = ±7.5, RL = 100Ω to GND
±6.3
±6.5
V
VS = ±7.5, RL = 25Ω to GND
±5.7
±6.0
V
450
mA
Output Current
RL = 0Ω
VS
Supply Voltage
Single supply
IS+ (Full Power)
Positive Supply Current per Amplifier
All outputs at 0V, C0 = C1 = 0V
IS- (Full Power)
Negative Supply Current per Amplifier
IS+ (3/4 Power)
Positive Supply Current per Amplifier
SUPPLY
3
5
15
V
7
9.25
mA
All outputs at 0V, C0 = C1 = 0V
-6.4
-8.75
mA
All outputs at 0V, C0 = 5V, C1 = 0V
5.3
7.25
mA
FN7016.2
April 10, 2007
EL1511
Electrical Specifications
VS = ±7.5V, RF = 1.5kΩ, RL = 100Ω to mid supply, TA = +25°C unless otherwise specified. (Continued)
PARAMETER
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
IS- (3/4 Power)
Negative Supply Current per Amplifier
All outputs at 0V, C0 = 5V, C1 = 0V
-4.7
-6.75
mA
IS+ (1/2 Power)
Positive Supply Current per Amplifier
All outputs at 0V, C0 = 0V, C1 = 5V
3.3
5.75
mA
IS- (1/2 Power)
Negative Supply Current per Amplifier
All outputs at 0V, C0 = 0V, C1 = 5V
-2.7
-5.2
mA
IS+ (Power Down) Positive Supply Current per Amplifier
All outputs at 0V, C0 = C1 = 5V
0.6
1.025
mA
IS- (Power Down)
Negative Supply Current per Amplifier
All outputs at 0V, C0 = C1 = 5V
0
-0.525
mA
IGND
GND Supply Current per Amplifier
All outputs at 0V
0.6
1
mA
Pin Descriptions
EL1511CS
16 Ld SO
(0.150”)
EL1511CL
16 Ld QFN
PIN NAME
PIN FUNCTION
1
1, 5, 6, 12, 15
NC
Not Connected
2, 15
13, 16
OUT
Output
EQUIVALENT CIRCUIT
VS+
OUT
VSCIRCUIT 1
3, 14
2, 11
VIN-
Inverting Input
VS+
IN+
IN-
VSCIRCUIT 2
4, 5, 7, 12, 13
4
GND
Ground Pins
6, 11
3, 10
VIN+
Non-inverting Input
8
7
VS-
Negative Supply
9
8
C0
Power Control
Reference Circuit 2
VS+
IBIAS
1.8V
+
–
Q1
Q3
500Ω C0
Q2
CIRCUIT 3
10
9
C1
4
Power Control
Reference Circuit 3
FN7016.2
April 10, 2007
EL1511
Typical Performance Curves
28
24
22
VS=±6V
AV=10
RL=100Ω
18
20
RF=2kΩ
16
RF=1.5kΩ
12
14
RF=2kΩ
10
6
8
100K
1M
10M
2
100K
100M
FREQUENCY (Hz)
20
RF=2kΩ
16
18
RF=1kΩ
VS=±6V
AV=5
RL=100Ω
RF=1kΩ
RF=1.5kΩ
GAIN (dB)
GAIN (dB)
100M
22
VS=±6V
AV=10
RL=100Ω
RF=1.5kΩ
12
14
RF=2kΩ
10
6
8
100K
1M
10M
2
100K
100M
FREQUENCY (Hz)
1M
10M
100M
FREQUENCY (Hz)
FIGURE 3. DIFFERENTIAL FREQUENCY RESPONSE
(3/4 POWER MODE)
FIGURE 4. DIFFERENTIAL FREQUENCY RESPONSE
(3/4 POWER MODE)
28
22
VS=±6V
AV=10
RL=100Ω
RF=1.5kΩ
18
RF=1kΩ
GAIN (dB)
GAIN (dB)
10M
FIGURE 2. DIFFERENTIAL FREQUENCY RESPONSE
(FULL POWER MODE)
28
24
1M
FREQUENCY (Hz)
FIGURE 1. DIFFERENTIAL FREQUENCY RESPONSE
(FULL POWER MODE)
24
RF=1kΩ
RF=1kΩ
GAIN (dB)
GAIN (dB)
RF=1.5kΩ
VS=±6V
AV=5
RL=100Ω
20
RF=2kΩ
16
12
8
100K
VS=±6V
AV=5
RL=100Ω
RF=1kΩ
RF=1.5kΩ
14
RF=2kΩ
10
6
1M
10M
100M
FREQUENCY (Hz)
FIGURE 5. DIFFERENTIAL FREQUENCY RESPONSE
(1/2 POWER MODE)
5
2
100K
1M
10M
100M
FREQUENCY (Hz)
FIGURE 6. DIFFERENTIAL FREQUENCY RESPONSE
(1/2 POWER MODE)
FN7016.2
April 10, 2007
EL1511
Typical Performance Curves (Continued)
28
24
22
VS=±7.5V
AV=10
RL=100Ω
18
VS=±7.5V
AV=5
RL=100Ω
RF=1kΩ
RF=1.5kΩ
GAIN (dB)
GAIN (dB)
RF=1kΩ
20
RF=1.5kΩ
16
14
10
RF=2kΩ
RF=2kΩ
12
6
8
100K
1M
10M
2
100K
100M
FREQUENCY (Hz)
100M
FIGURE 8. DIFFERENTIAL FREQUENCY RESPONSE
(FULL POWER MODE)
28
22
VS=±7.5V
AV=10
RL=100Ω
18
RF=1kΩ
20
RF=1.5kΩ
16
VS=±7.5V
AV=5
RL=100Ω
RF=1kΩ
RF=1.5kΩ
GAIN (dB)
GAIN (dB)
10M
FREQUENCY (Hz)
FIGURE 7. DIFFERENTIAL FREQUENCY RESPONSE
(FULL POWER MODE)
24
1M
14
RF=2kΩ
10
RF=2kΩ
12
6
8
100K
1M
10M
2
100K
100M
FREQUENCY (Hz)
100M
FIGURE 10. DIFFERENTIAL FREQUENCY RESPONSE
(3/4 POWER MODE)
28
22
VS=±7.5V
AV=10
RL=100Ω
RF=1kΩ
18
VS=±7.5V
AV=5
RL=100Ω
RF=1kΩ
RF=1.5kΩ
GAIN (dB)
RF=1.5kΩ
GAIN (dB)
10M
FREQUENCY (Hz)
FIGURE 9. DIFFERENTIAL FREQUENCY RESPONSE
(3/4 POWER MODE)
24
1M
20
RF=2kΩ
16
12
8
100K
14
RF=2kΩ
10
6
1M
10M
100M
FREQUENCY (Hz)
FIGURE 11. DIFFERENTIAL FREQUENCY RESPONSE
(1/2 POWER MODE)
6
2
100K
1M
10M
100M
FREQUENCY (Hz)
FIGURE 12. DIFFERENTIAL FREQUENCY RESPONSE
(1/2 POWER MODE)
FN7016.2
April 10, 2007
EL1511
Typical Performance Curves (Continued)
30
30
26
CL=22pF
22
14
10
CL=0pF
6
2
-2
-6
CL=22pF
CL=10pF
GAIN (dB)
GAIN (dB)
22
CL=10pF
18
VS=±6V
RF=1.5kΩ
AV=5
RL=100Ω
-10
100K
14
CL=0pF
6
VS=±7.5V
RF=1.5kΩ
AV=5
RL=100Ω
-2
1M
10M
-10
100k
100M
FIGURE 13. DIFFERENTIAL FREQUENCY RESPONSE vs CL
(FULL POWER MODE)
30
22
22
GAIN (dB)
GAIN (dB)
14
10
CL=0pF
6
VS=±6V
RF=1.5kΩ
AV=5
RL=100Ω
-10
100K
14
CL=0pF
6
-2
10M
1M
VS=±7.5V
RF=1.5kΩ
AV=5
RL=100Ω
-10
100K
100M
1M
FIGURE 15. DIFFERENTIAL FREQUENCY RESPONSE vs CL
(3/4 POWER MODE)
30
CL=22pF
26
22
CL=22pF
22
CL=10pF
CL=10pF
GAIN (dB)
GAIN (dB)
18
14
CL=0pF
10
6
-6
100M
FIGURE 16. DIFFERENTIAL FREQUENCY RESPONSE vs CL
(3/4 POWER MODE)
30
-2
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
2
CL=22pF
CL=10pF
CL=10pF
18
-6
100M
CL=22pF
26
2
10M
FIGURE 14. DIFFERENTIAL FREQUENCY RESPONSE vs CL
(FULL POWER MODE)
30
-2
1M
FREQUENCY (Hz)
FREQUENCY (Hz)
VS=±6V
RF=1.5kΩ
AV=5
RL=100Ω
-10
100K
14
CL=0pF
6
-2
10M
1M
100M
FREQUENCY (Hz)
FIGURE 17. DIFFERENTIAL FREQUENCY RESPONSE vs CL
(1/2 POWER MODE)
7
VS=±7.5V
RF=1.5kΩ
AV=5
RL=100Ω
-10
100K
1M
10M
100M
FREQUENCY (Hz)
FIGURE 18. DIFFERENTIAL FREQUENCY RESPONSE vs CL
(1/2 POWER MODE)
FN7016.2
April 10, 2007
EL1511
Typical Performance Curves (Continued)
70
FULL POWER
VS=±2.5V
AV=5
RF=2kΩ
RL=100Ω
f=150kHz
-50
-55
50
THD (dB)
BANDWIDTH (MHz)
60
-45
AV=5
RF=1.5kΩ
RL=100Ω
3/4 POWER
40
30
1/2 POWER
-60
FULL POWER
-65
-70
3/4 POWER
-75
1/2 POWER
-80
20
-85
2.5
4.5
3.5
5.5
6.5
7.5
2
2.5
3
3.5
FIGURE 19. DIFFERENTIAL BANDWIDTH vs SUPPLY VOLTAGE
-55
-60
THD (dB)
PEAKING (dB)
6
8
4
VS=±6V
AV=5
RF=1.5kΩ
RL=100Ω
f=150kHz
-50
1/2 POWER
3/4 POWER
-65
-70
FULL POWER
-75
3/4 POWER
-80
0
FULL POWER
1/2 POWER
-85
-90
3.5
4.5
5.5
6.5
7.5
2
4
6
8
±VS (V)
10
12
14
16
18
20
VOP-P (V)
FIGURE 21. DIFFERENTIAL PEAKING vs SUPPLY VOLTAGE
FIGURE 22. DIFFERENTIAL TOTAL HARMONIC DISTORTION
vs DIFFERENTIAL OUTPUT VOLTAGE
-10
-30
VS=±7.5V
AV=5
RF=1.5kΩ
RL=100Ω
f=150kHz
-20
-40
-30
-40
-50
THD (dB)
ISOLATION (dB)
5.5
-45
AV=5
RF=1.5kΩ
RL=100Ω
12
-50
-60
5
FIGURE 20. DIFFERENTIAL TOTAL HARMONIC DISTORTION
vs DIFFERENTIAL OUTPUT VOLTAGE
16
-4
2.5
4.5
4
VOP-P (V)
±VS (V)
B→A
-70
FULL POWER
-70
A→B
-80
-60
3/4 POWER
-90
1/2 POWER
-80
-100
-110
10k
-90
100k
1M
10M
100M
FREQUENCY (Hz)
FIGURE 23. CHANNEL ISOLATION vs FREQUENCY
8
2
6
10
14
18
22
26
VOP-P (V)
FIGURE 24. DIFFERENTIAL TOTAL HARMONIC DISTORTION
vs DIFFERENTIAL OUTPUT VOLTAGE
FN7016.2
April 10, 2007
EL1511
Typical Performance Curves (Continued)
-45
-45
VS=±2.5V
AV=5
RF=2kΩ
RL=100Ω
f=1MHz
-55
HD (dB)
-60
VS=±6V
AV=5
RF=1.5kΩ
RL=100Ω
f=1MHz
-50
-55
-65
HD (dB)
-50
HD3
-70
-75
-80
-60
HD3
-65
-70
HD2
-75
HD2
-80
-85
-90
-85
1
1.5
2
2.5
3
3.5
4
4.5
5
5.5
6
2
4
6
8
VOP-P (V)
FIGURE 25. DIFFERENTIAL HARMONIC DISTORTION vs
DIFFERENTIAL OUTPUT VOLTAGE
(FULL POWER MODE)
14
16
18
20
-45
VS=±2.5V
AV=5
RF=2kΩ
RL=100Ω
f=1MHz
-55
-60
VS=±6V
AV=5
RF=1.5kΩ
RL=100Ω
f=1MHz
-50
-55
HD (dB)
-50
HD (dB)
12
FIGURE 26. DIFFERENTIAL HARMONIC DISTORTION vs
DIFFERENTIAL OUTPUT VOLTAGE
(FULL POWER MODE)
-45
HD3
-65
-70
-75
-80
-60
-65
HD3
-70
HD2
-75
HD2
-80
-85
-85
-90
1
1.5
2
2.5
3
3.5
4
4.5
5
5.5
2
6
4
6
8
10
12
14
16
18
20
VOP-P (V)
VOP-P (V)
FIGURE 27. DIFFERENTIAL HARMONIC DISTORTION vs
DIFFERENTIAL OUTPUT VOLTAGE
(3/4 POWER MODE)
FIGURE 28. DIFFERENTIAL HARMONIC DISTORTION vs
DIFFERENTIAL OUTPUT VOLTAGE
(3/4 POWER MODE)
-45
-50
VS=±2.5V
AV=5
RF=2kΩ
RL=100Ω
f=1MHz
-60
VS=±6V
AV=5
RF=1.5kΩ
RL=100Ω
f=1MHz
-50
-55
-65
HD (dB)
-55
HD (dB)
10
VOP-P (V)
HD3
-70
-75
-60
HD3
-65
-70
HD2
-75
HD2
-80
-80
-85
-85
1
1.5
2
2.5
3
3.5
4
4.5
5
5.5
6
VOP-P (V)
FIGURE 29. DIFFERENTIAL HARMONIC DISTORTION vs
DIFFERENTIAL OUTPUT VOLTAGE
(1/2 POWER MODE)
9
2
4
6
8
10
12
14
16
18
20
VOP-P (V)
FIGURE 30. DIFFERENTIAL HARMONIC DISTORTION vs
DIFFERENTIAL OUTPUT VOLTAGE
(1/2 POWER MODE)
FN7016.2
April 10, 2007
EL1511
Typical Performance Curves (Continued)
-30
-45
VS=±7.5V
AV=5
RF=1.5kΩ
RL=100Ω
f=1MHz
HD (dB)
-50
VS=±2.5V
AV=5
RF=2kΩ
RL=100Ω
f=1MHz
-50
-55
THD (dB)
-40
-60
HD3
-70
-60
1/2 POWER
-65
-70
3/4 POWER
HD2
-80
-75
-90
FULL POWER
-80
2
6
10
14
18
22
26
1
1.5
2
2.5
VOP-P (V)
4
4.5
5
5.5
6
FIGURE 32. DIFFERENTIAL TOTAL HARMONIC DISTORTION
vs DIFFERENTIAL OUTPUT VOLTAGE
-30
-45
VS=±7.5V
AV=5
RF=1.5kΩ
RL=100Ω
f=1MHz
-50
VS=±6V
AV=5
RF=1.5kΩ
RL=100Ω
f=1MHz
-50
-55
-60
THD (dB)
-40
HD (dB)
3.5
VOP-P (V)
FIGURE 31. DIFFERENTIAL HARMONIC DISTORTION vs
DIFFERENTIAL OUTPUT VOLTAGE
(FULL POWER MODE)
HD3
-70
-60
-65
1/2 POWER
-70
-75
HD2
-80
FULL POWER
-80
3/4 POWER
-85
-90
2
6
10
14
18
22
26
2
4
6
8
10
12
14
16
18
20
VOP-P (V)
VOP-P (V)
FIGURE 33. DIFFERENTIAL HARMONIC DISTORTION vs
DIFFERENTIAL OUTPUT VOLTAGE
(3/4 POWER MODE)
FIGURE 34. DIFFERENTIAL TOTAL HARMONIC DISTORTION
vs DIFFERENTIAL OUTPUT VOLTAGE
-30
-30
VS=±7.5V
AV=5
RF=1.5kΩ
RL=100Ω
f=1MHz
-50
VS=±7.5V
AV=5
RF=1.5kΩ
RL=100Ω
f=1MHz
-40
-50
THD (dB)
-40
HD (dB)
3
HD3
-60
-70
1/2 POWER
-60
-70
FULL POWER
HD2
-80
-80
-90
-90
3/4 POWER
2
6
10
14
18
22
26
VOP-P (V)
FIGURE 35. DIFFERENTIAL HARMONIC DISTORTION vs
DIFFERENTIAL OUTPUT VOLTAGE
(1/2 POWER MODE)
10
2
6
10
14
18
22
26
VOP-P (V)
FIGURE 36. DIFFERENTIAL TOTAL HARMONIC DISTORTION
vs DIFFERENTIAL OUTPUT VOLTAGE
FN7016.2
April 10, 2007
EL1511
Typical Performance Curves (Continued)
0.14
VS=±6V
AV=2
RF=1.5kΩ
0.12
CH 2
dG (%)
0.1
VOUT
0.08
1/2 POWER
0.06
C0, C1
3/4 POWER
0.04
0.02
CH 1=2V/DIV
CH 2=2V/DIV
CH 1
FULL POWER
0
1.5
1
2
2.5
3
4
3.5
400ns/DIV
NUMBER OF 150Ω LOADS
FIGURE 37. DIFFERENTIAL GAIN
FIGURE 38. DISABLE TIME
0.15
VS=±6V
AV=2
RF=1.5kΩ
0.14
0.13
dP (°)
0.12
CH 1=2V/DIV
CH 2=2V/DIV
1/2 POWER
VOUT
CH 2
0.11
0.1
C0, C1
CH 1
3/4 POWER
0.09
FULL POWER
0.08
0.07
1
1.5
2
3
2.5
3.5
4
40ns/DIV
NUMBER OF 150Ω LOADS
FIGURE 39. DIFFERENTIAL PHASE
FIGURE 40. ENABLE TIME
16
10
14
IS- (FULL POWER)
INPUT BIAS CURRENT (µA)
IS+ (FULL POWER)
IS+ (3/4 POWER)
IS (mA)
12
10
8
IS- (3/4 POWER)
6
4
IS+ (1/2 POWER)
IS+ (1/2 POWER)
2.5
3
3.5
4
4.5
5
5.5
6
6.5
7
7.5
±VS (V)
FIGURE 41. SUPPLY CURRENT vs SUPPLY VOLTAGE
11
6
IB-
4
2
0
-2
IB+
-4
-6
-8
2
2
8
-10
-50
-25
0
25
50
75
100
125
150
DIE TEMPERATURE (°C)
FIGURE 42. INPUT BIAS CURRENT vs TEMPERATURE
FN7016.2
April 10, 2007
EL1511
Typical Performance Curves (Continued)
7
6
14
OFFSET VOLTAGE (mV)
SUPPLY CURRENT (mA)
16
FULL POWER
12
3/4 POWER
10
8
1/2 POWER
6
4
DISABLED
2
0
-50
-25
0
25
50
75
5
4
3
2
1
0
-1
-2
100
125
-3
-50
150
-25
DIE TEMPERATURE (°C)
0
25
50
75
100
125
150
DIE TEMPERATURE (°C)
FIGURE 43. POSITIVE SUPPLY CURRENT vs TEMPERATURE
FIGURE 44. OFFSET VOLTAGE vs TEMPERATURE
5.2
3
5.15
TRANSIMPEDANCE (MΩ)
OUTPUT VOLTAGE (±V)
RL=100Ω
5.1
50.5
5
4.95
4.9
4.85
4.8
-50
2.5
2
1.5
1
0.5
0
-25
0
25
50
75
100
125
-50
150
FIGURE 45. OUTPUT VOLTAGE vs TEMPERATURE
25
50
75
100
125
150
30
20
510
10
500
0
490
PSRR (dB)
SLEW RATE (V/µs)
0
FIGURE 46. TRANSIMPEDANCE vs TEMPERATURE
520
480
470
-10
-20
-30
-40
460
PSRR-
-50
450
440
-50
-25
DIE TEMPERATURE (°C)
DIE TEMPERATURE (°C)
PSRR+
-60
-25
0
25
50
75
100
125
150
DIE TEMPERATURE (°C)
FIGURE 47. SLEW RATE vs TEMPERATURE
12
-70
10K
100K
1M
10M
100M
FREQUENCY (Hz)
FIGURE 48. POWER SUPPLY REJECTION vs FREQUENCY
FN7016.2
April 10, 2007
EL1511
Typical Performance Curves (Continued)
100
OUTPUT IMPEDANCE (Ω)
VOLTAGE NOISE (nV/√Hz),
CURRENT NOISE (pA/Hz)
100
IB10
eN
10
VS=±6V
AV=1
RF=1.5kΩ
1
0.1
0.01
IB+
1
10
100
1K
10K
100K
1M
10M
0.001
10K
100M
100K
FREQUENCY (Hz)
FIGURE 49. VOLTAGE AND CURRENT NOISE vs FREQUENCY
10M
100k
-100
-150
10k
-200
1k
-250
1K
10K
100K
1M
10M
-300
100M
POWER DISSIPATION (W)
-50
PHASE
PHASE (°)
MAGNITUDE (Ω)
4
0
GAIN
100
100
100M
FIGURE 50. OUTPUT IMPEDANCE vs FREQUENCY (ALL
POWER LEVELS)
50
1M
10M
1M
FREQUENCY (Hz)
USING EL1511CS/EL1511CL DEMOBOARD,
2”X2” (4-LAYER) DEMOBOARD WITH
HEATSINK VIA INTERNAL GROUND PLANE
3.5
3
37°C/W
QF
N
47°C/W
2.5
SO
2
16
1.5
(0.
15
16
0”
)
1
0.5
0
-40
-20
0
20
40
60
80
100
AMBIENT TEMPERATURE (°C)
FREQUENCY (Hz)
FIGURE 51. TRANSIMPEDANCE (ROL) vs FREQUENCY
FIGURE 52. PACKAGE POWER DISSIPATION AND THERMAL
RESISTANCE
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY (4-LAYER) TEST BOARD, QFN EXPOSED
DIEPAD SOLDERED TO PCB PER JESD51-5
POWER DISSIPATION (W)
4
3.5
3.125W
3
2.5
40
2
QF
N1
6
°C
/W
1.5
1
0.5
0
0
25
50
75 85 100
125
150
AMBIENT TEMPERATURE (°C)
FIGURE 53. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
13
FN7016.2
April 10, 2007
EL1511
Applications Information
Product Description
The EL1511 is a dual operational amplifier designed for
customer premise driver functions in DMT ADSL solutions
and is built using Elantec's proprietary complimentary bipolar
process. Due to the current feedback architecture, the
EL1511 closed-loop 3dB bandwidth is dependent on the
value of the feedback resistor. First the desired bandwidth is
selected by choosing the feedback resistor, RF, and then the
gain is set by picking the gain resistor, RG. The curves at the
beginning of the Typical Performance Curves section show
the effect of varying both RF and RG.
Power Supply Bypassing and Printed Circuit
Board Layout
As with any high frequency device, good printed circuit
board layout is necessary for optimum performance. Ground
plane construction is highly recommended. Lead lengths
should be as short as possible, below ¼. The power supply
pins must be well bypassed to reduce the risk of oscillation.
A 1.0µF tantalum capacitor in parallel with a 0.01µF ceramic
capacitor is adequate for each supply pin.
For good AC performance, parasitic capacitances should be
kept to a minimum, especially at the inverting input (see
Capacitance at the Inverting Input section). This implies
keeping the ground plane away from this pin. Carbon resistors
are acceptable, while use of wire-wound resistors should not
be used because of their parasitic inductance. Similarly,
capacitors should be low inductance for best performance.
Use of sockets, particularly for the SO (0.150") package,
should be avoided. Sockets add parasitic inductance and
capacitance which will result in peaking and overshoot.
Capacitance at the Inverting Input
Due to the topology of the current feedback amplifier, stray
capacitance at the inverting input will affect the AC and
transient performance of the EL1511 when operating in the
non-inverting configuration.
In the inverting gain mode, added capacitance at the inverting
input has little effect since this point is at a virtual ground and
stray capacitance is therefore not “seen” by the amplifier.
Feedback Resistor Values
The EL1511 has been designed and specified with RF =
1.5kΩ for AV = +5. This value of feedback resistor yields
relatively flat frequency response with <1.5dB peaking out to
60MHz. As is the case with all current feedback amplifiers,
wider bandwidth, at the expense of slight peaking, can be
obtained by reducing the value of the feedback resistor.
Inversely, larger values of feedback resistor will cause rolloff
to occur at a lower frequency. By reducing RF to 1kΩ,
bandwidth can be extended to 70MHz with 3.0dB of peaking.
See the curves in the Typical Performance Curves section
which show 3dB bandwidth and peaking vs frequency for
various feedback resistors.
14
Power Dissipation
The EL1511 amplifier combines both high speed and large
output current drive capability at a moderate supply current
in very small packages. It is possible to exceed the
maximum junction temperature allowed under certain supply
voltage, temperature, and loading conditions. To ensure that
the EL1511 remains within its absolute maximum ratings, the
following discussion will help to avoid exceeding the
maximum junction temperature.
The maximum power dissipation allowed in a package is
determined by its thermal resistance and the amount of
temperature rise according to:
T JMAX – T AMAX
P DMAX = --------------------------------------------θ JA
The maximum power dissipation actually produced by an IC
is the total quiescent supply current times the total power
supply voltage plus the power in the IC due to the load, or:
V OUT
P DMAX = 2 × V S + ( V S – V OUT ) × ---------------RL
where IS is the supply current. (To be more accurate, the
quiescent supply current flowing in the output driver transistor
should be subtracted from the first term because, under
loading and due to the class AB nature of the output stage,
the output driver current is now included in the second term.)
In general, an amplifier's AC performance degrades at
higher operating temperature and lower supply current.
Unlike some amplifiers, the EL1511 maintains almost
constant supply current over temperature so that AC
performance is not degraded as much over the entire
operating temperature range.
Estimating Line Driver Power Dissipation in ADSL
CPE Application
The below figure shows a typical ADSL CPE line driver
implementation. The average line power requirement for the
ADSL CPE application is 13dBM (20mW) into a 100W line.
The average line voltage is 1.41VRMS. The ADSL DMT peak
to average ratio (crest factor) of 5.3 implies peak voltage of
7.5V into the line. Using a differential drive configuration and
transformer coupling with standard back termination, a
transformer ratio of 1:2 is selected. With 1:2 transformer
ratio, the impedance across the driver side of the
transformer is 25Ω, the average voltage is 0.705VRMA and
the average current is 28.2mA. The power dissipated in the
EL1511 is a combination of the quiescent power and the
output stage power when driving the line:
PD = P quiescent + P output-stage
PD = V S × I Q + ( V S – 2 × V OUT-RMS ) × I OUT-RMS
In the ½ power mode, the EL1511 consumes typically 6.6mA
quiescent current and still able to maintain very low
distortion. The distortion results are shown in typical
FN7016.2
April 10, 2007
EL1511
performance section of the data sheet. When driving a load,
a large portion (about 50%) of the quiescent current
becomes output load current:
PD = 12 × ( 6.6mA × 50% ) + ( 12V – 2 × 0.705 ) × 28.2mA
where:
PD = 338mW
Assuming a maximum ambient temperature of 85°C and
keeping the junction temperature less than 150°C, the
maximum thermal resistance from junction to ambient
required is:
TOP (16 Ld QFN)
150 – 85
Θ JA = ---------------------- = 192°C/W
338mW
With proper layout, the EL1511CS package can achieve
47°C/W, well below the thermal resistance required by the
application.
TX+
+
-
From
AFE
2RG
464
TX-
VS+
VSRF
RT
12.5
1.5k
+
-
VS+
VSRF
TXFR
1:2
INTERNAL GROUND PLANE (16 Ld QFN)
100
RT
12.5
1.5k
PCB Layout Considerations for Thermal Packages
The EL1511 die is packaged in two different thermal efficient
packages, the 16 Ld SO and 16 Ld QFN packages. The 16
Ld SO package has the same dimensions as standard 0.15"
wide narrow body 16 Ld SO package with a special fused
lead frame that extends out through the center ground pins.
Both packages can use PCB surface metal vias areas and
internal ground planes, to spread heat away from the
package. The larger the PCB area the lower the junction
temperature of the device will be. In XDSL applications,
multiple layer circuit boards with internal ground plane are
generally used. 13 mil vias are recommended to connect the
metal area under the device with the internal ground plane.
Examples of the PCB layouts are shown in the figures below
that result in thermal resistance θJA of 37°C/W for the QFN
package and 47°C/W for the SO package. The thermal
resistance is obtained with the EL1511CL and CS demo
boards. The demo board is a 4-layer board built with 2oz.
copper and has a dimension of 4in2. Note, the user must
follow the thermal layout guideline to achieve these results.
TOP (16 Ld SO)
INTERNAL GROUND PLANE (16 Ld SO)
A separate Application Note for the QFN package and layout
recommendations is also available.
15
FN7016.2
April 10, 2007
EL1511
QFN (Quad Flat No-Lead) Package Family
MDP0046
QFN (QUAD FLAT NO-LEAD) PACKAGE FAMILY
(COMPLIANT TO JEDEC MO-220)
A
MILLIMETERS
D
N
(N-1)
(N-2)
B
1
2
3
PIN #1
I.D. MARK
E
(N/2)
2X
0.075 C
2X
0.075 C
N LEADS
TOP VIEW
0.10 M C A B
(N-2)
(N-1)
N
b
L
SYMBOL QFN44 QFN38
TOLERANCE
NOTES
A
0.90
0.90
0.90
0.90
±0.10
-
A1
0.02
0.02
0.02
0.02
+0.03/-0.02
-
b
0.25
0.25
0.23
0.22
±0.02
-
c
0.20
0.20
0.20
0.20
Reference
-
D
7.00
5.00
8.00
5.00
Basic
-
Reference
8
Basic
-
Reference
8
Basic
-
D2
5.10
3.80
5.80 3.60/2.48
E
7.00
7.00
8.00
1
2
3
6.00
E2
5.10
5.80
5.80 4.60/3.40
e
0.50
0.50
0.80
0.50
L
0.55
0.40
0.53
0.50
±0.05
-
N
44
38
32
32
Reference
4
ND
11
7
8
7
Reference
6
NE
11
12
8
9
Reference
5
MILLIMETERS
PIN #1 I.D.
3
QFN32
SYMBOL QFN28 QFN24
QFN20
QFN16
A
0.90
0.90
0.90
0.90
0.90
±0.10
-
A1
0.02
0.02
0.02
0.02
0.02
+0.03/
-0.02
-
b
0.25
0.25
0.30
0.25
0.33
±0.02
-
c
0.20
0.20
0.20
0.20
0.20
Reference
-
D
4.00
4.00
5.00
4.00
4.00
Basic
-
D2
2.65
2.80
3.70
2.70
2.40
Reference
-
(E2)
(N/2)
NE 5
7
(D2)
BOTTOM VIEW
0.10 C
e
C
SEATING
PLANE
TOLERANCE NOTES
E
5.00
5.00
5.00
4.00
4.00
Basic
-
E2
3.65
3.80
3.70
2.70
2.40
Reference
-
e
0.50
0.50
0.65
0.50
0.65
Basic
-
L
0.40
0.40
0.40
0.40
0.60
±0.05
-
N
28
24
20
20
16
Reference
4
ND
6
5
5
5
4
Reference
6
NE
8
7
5
5
4
Reference
5
Rev 11 2/07
0.08 C
N LEADS
& EXPOSED PAD
SEE DETAIL "X"
NOTES:
1. Dimensioning and tolerancing per ASME Y14.5M-1994.
2. Tiebar view shown is a non-functional feature.
SIDE VIEW
3. Bottom-side pin #1 I.D. is a diepad chamfer as shown.
4. N is the total number of terminals on the device.
(c)
C
5. NE is the number of terminals on the “E” side of the package
(or Y-direction).
2
A
(L)
A1
N LEADS
DETAIL X
6. ND is the number of terminals on the “D” side of the package
(or X-direction). ND = (N/2)-NE.
7. Inward end of terminal may be square or circular in shape with radius
(b/2) as shown.
8. If two values are listed, multiple exposed pad options are available.
Refer to device-specific datasheet.
16
FN7016.2
April 10, 2007
EL1511
Small Outline Package Family (SO)
A
D
h X 45°
(N/2)+1
N
A
PIN #1
I.D. MARK
E1
E
c
SEE DETAIL “X”
1
(N/2)
B
L1
0.010 M C A B
e
H
C
A2
GAUGE
PLANE
SEATING
PLANE
A1
0.004 C
0.010 M C A B
L
b
0.010
4° ±4°
DETAIL X
MDP0027
SMALL OUTLINE PACKAGE FAMILY (SO)
INCHES
SYMBOL
SO-14
SO16 (0.300”)
(SOL-16)
SO20
(SOL-20)
SO24
(SOL-24)
SO28
(SOL-28)
TOLERANCE
NOTES
A
0.068
0.068
0.068
0.104
0.104
0.104
0.104
MAX
-
A1
0.006
0.006
0.006
0.007
0.007
0.007
0.007
±0.003
-
A2
0.057
0.057
0.057
0.092
0.092
0.092
0.092
±0.002
-
b
0.017
0.017
0.017
0.017
0.017
0.017
0.017
±0.003
-
c
0.009
0.009
0.009
0.011
0.011
0.011
0.011
±0.001
-
D
0.193
0.341
0.390
0.406
0.504
0.606
0.704
±0.004
1, 3
E
0.236
0.236
0.236
0.406
0.406
0.406
0.406
±0.008
-
E1
0.154
0.154
0.154
0.295
0.295
0.295
0.295
±0.004
2, 3
e
0.050
0.050
0.050
0.050
0.050
0.050
0.050
Basic
-
L
0.025
0.025
0.025
0.030
0.030
0.030
0.030
±0.009
-
L1
0.041
0.041
0.041
0.056
0.056
0.056
0.056
Basic
-
h
0.013
0.013
0.013
0.020
0.020
0.020
0.020
Reference
-
16
20
24
28
Reference
-
N
SO-8
SO16
(0.150”)
8
14
16
Rev. M 2/07
NOTES:
1. Plastic or metal protrusions of 0.006” maximum per side are not included.
2. Plastic interlead protrusions of 0.010” maximum per side are not included.
3. Dimensions “D” and “E1” are measured at Datum Plane “H”.
4. Dimensioning and tolerancing per ASME Y14.5M-1994
17
FN7016.2
April 10, 2007
EL1511
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
18
FN7016.2
April 10, 2007
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