TI LMZ10504TZE-ADJ/NOPB 4a simple switcher power module with 5.5-v maximum input voltage Datasheet

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LMZ10504
SNVS610N – DECEMBER 2009 – REVISED SEPTEMBER 2015
LMZ10504 4-A SIMPLE SWITCHER® Power Module With 5.5-V Maximum Input Voltage
1 Features
2 Applications
•
•
•
1
•
•
•
•
•
•
Integrated Shielded Inductor
Flexible Start-up Sequencing Using External SoftStart, Tracking, and Precision Enable
Protection Against In-Rush Currents and Faults
Such as Input UVLO and Output Short-Circuit
Single Exposed Pad and Standard Pinout for Easy
Mounting and Manufacturing
Pin-to-Pin Compatible With
– LMZ10503 (3-A/15-W Maximum)
– LMZ10505 (5-A/25-W Maximum)
Fully Enable for WEBENCH™ and Power
Designer
Electrical Specifications
– 20-W Maximum Total Output Power
– Up to 4-A Output Current
– Input Voltage Range 2.95 V to 5.5 V
– Output Voltage Range 0.8 V to 5 V
– ±1.63% Feedback Voltage Accuracy Over
Temperature
Performance Benefits
– Operates at High Ambient Temperatures
– High Efficiency up to 96% Reduces System
Heat Generation
– Low Radiated Emissions (EMI) Tested to
EN55022 Class B Standard
– Passes 10-V/m Radiated Immunity EMI Tested
to Standard EN61000 4-3
– Fast Transient Response for Powering FPGAs
and ASICs
NOTE: EN 55022:2006, +A1:2007, FCC Part 15 Subpart B: 2007.
See Table 9 and layout for information on device under
test.
Typical Application Circuit
VIN
VOUT
1
VIN
Cin
2
FB
SS
The LMZ10504 SIMPLE SWITCHER® power module
is a complete, easy-to-use, DC-DC solution capable
of driving up to a 4-A load with exceptional power
conversion efficiency, output voltage accuracy, and
line and load regulation. The LMZ10504 is available
in an innovative package that enhances thermal
performance and allows for hand or machine
soldering.
The LMZ10504 can accept an input voltage rail
between 2.95 V and 5.5 V, and can deliver an
adjustable and highly accurate output voltage as low
as 0.8 V. 1-MHz fixed-frequency PWM switching
provides a predictable EMI characteristic. Two
external compensation components can be adjusted
to set the fastest response time, while allowing the
option to use ceramic or electrolytic output capacitors.
Externally
programmable
soft-start
capacitor
facilitates controlled start-up. The LMZ10504 is a
reliable and robust solution with the following
features: lossless cycle-by-cycle peak current limit to
protect for overcurrent or short-circuit fault, thermal
shutdown, input undervoltage lockout, and prebiased
start-up.
Device Information(1)(2)
PART NUMBER
LMZ10504
PACKAGE
BODY SIZE (NOM)
TO-PMOD (7)
9.85 mm × 10.16 mm
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
(2) Peak reflow temperature equals 245°C. See SNAA214 for
more details.
Efficiency VOUT = 3.3 V
CO
5
GND
4, EP
3
3 Description
VOUT
6, 7
LMZ10504
EN
•
•
Point-of-Load Conversions from 3.3-V and 5-V
Rails
Space-Constrained Applications
Noise-Sensitive Applications (Such as
Transceiver, Medical)
Rfbt
CSS
Rcomp
Ccomp
Rfbb
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
LMZ10504
SNVS610N – DECEMBER 2009 – REVISED SEPTEMBER 2015
www.ti.com
Table of Contents
1
2
3
4
5
6
7
Features ..................................................................
Applications ...........................................................
Description .............................................................
Revision History.....................................................
Pin Configuration and Functions .........................
Specifications.........................................................
1
1
1
2
3
4
6.1
6.2
6.3
6.4
6.5
6.6
4
4
4
4
5
7
Detailed Description ............................................ 10
7.1
7.2
7.3
7.4
8
Absolute Maximum Ratings ......................................
ESD Ratings..............................................................
Recommended Operating Conditions.......................
Thermal Information ..................................................
Electrical Characteristics...........................................
Typical Characteristics ..............................................
Overview .................................................................
Functional Block Diagram .......................................
Feature Description.................................................
Device Functional Modes........................................
10
10
10
13
Application and Implementation ........................ 14
8.1 Application Information............................................ 14
8.2 Typical Application .................................................. 14
8.3 System Examples ................................................... 20
9 Power Supply Recommendations...................... 23
10 Layout................................................................... 23
10.1 Layout Guidelines .................................................
10.2 Layout Examples...................................................
10.3 Estimate Power Dissipation and Thermal
Considerations .........................................................
10.4 Power Module SMT Guidelines ............................
23
24
26
27
11 Device and Documentation Support ................. 28
11.1
11.2
11.3
11.4
11.5
11.6
Device Support......................................................
Documentation Support ........................................
Community Resources..........................................
Trademarks ...........................................................
Electrostatic Discharge Caution ............................
Glossary ................................................................
28
28
28
28
28
28
12 Mechanical, Packaging, and Orderable
Information ........................................................... 29
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision M (October 2013) to Revision N
•
Page
Added ESD Ratings table, Feature Description section, Device Functional Modes, Application and Implementation
section, Power Supply Recommendations section, Layout section, Device and Documentation Support section, and
Mechanical, Packaging, and Orderable Information section. ................................................................................................. 1
Changes from Revision L (April 2013) to Revision M
Page
•
Deleted 10 mils....................................................................................................................................................................... 4
•
Changed 10 mils................................................................................................................................................................... 23
•
Changed 10 mils................................................................................................................................................................... 26
•
Added Power Module SMT Guidelines................................................................................................................................. 27
2
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SNVS610N – DECEMBER 2009 – REVISED SEPTEMBER 2015
5 Pin Configuration and Functions
NDW Package
7-Lead TO-PMOD
Top View
Exposed Pad
Connect to GND
7
VOUT
6
VOUT
5
FB
4
GND
3
SS
2
EN
1
VIN
Pin Functions
PIN
NAME
NO.
TYPE
DESCRIPTION
EN
2
Analog
Active-high enable input for the device.
Exposed Pad
—
Ground
Exposed pad is used as a thermal connection to remove heat from the device. Connect this
pad to the PCB ground plane in order to reduce thermal resistance value. EP must also
provide a direct electrical connection to the input and output capacitors ground terminals.
Connect EP to pin 4.
FB
5
Analog
Feedback pin. This is the inverting input of the error amplifier used for sensing the output
voltage. Keep the copper area of this node small.
GND
4
Ground
Power ground and signal ground. Provide a direct connection to the EP. Place the bottom
feedback resistor as close as possible to GND and FB pin.
SS
3
Analog
Soft-start control pin. An internal 2-µA current source charges an external capacitor
connected between SS and GND pins to set the output voltage ramp rate during start-up.
The SS pin can also be used to configure the tracking feature.
VIN
1
Power
Power supply input. A low-ESR input capacitance should be located as close as possible to
the VIN pin and exposed pad (EP).
6, 7
Power
The output terminal of the internal inductor. Connect the output filter capacitor between
VOUT pin and EP.
VOUT
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SNVS610N – DECEMBER 2009 – REVISED SEPTEMBER 2015
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6 Specifications
6.1 Absolute Maximum Ratings (1) (2) (3)
VIN, VOUT, EN, FB, SS to GND
MIN
MAX
UNIT
–0.3
6
V
150
°C
245
°C
150
°C
Power Dissipation
Internally Limited
Junction Temperature
Peak Reflow Case Temperature (30 sec)
Storage Temperature, Tstg
(1)
(2)
(3)
–65
Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/ Distributors for availability and
specifications.
For soldering specifications, refer to the following document: SNOA549
6.2 ESD Ratings
V(ESD)
(1)
Electrostatic discharge
Human body model (HBM), per ANSI/ESDA/JEDEC JS-001
VALUE
UNIT
±2000
V
(1)
The human body model is a 100-pF capacitor discharged through a 1.5-kΩ resistor into each pin. Test method is per JESD22-AI14S.
6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted)
MIN
MAX
VIN to GND
2.95
5.5
UNIT
V
Junction Temperature (TJ)
–40
125
°C
6.4 Thermal Information
LMZ10504
THERMAL METRIC (1)
NDW (TO-PMOD)
UNIT
7 PINS
RθJA
Junction-to-ambient thermal resistance (2)
20
°C/W
RθJC(top)
Junction-to-case (top) thermal resistance (no air flow)
1.9
°C/W
(1)
(2)
4
For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.
RθJA measured on a 2.25-in × 2.25-in (5.8 cm × 5.8 cm) 4-layer board, with 1-oz. copper, thirty six thermal vias, no air flow, and 1-W
power dissipation. Refer to Layout Examples or Evaluation Board Application Note: AN-2022 (SNVA421).
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6.5 Electrical Characteristics
Specifications are for TJ = 25°C unless otherwise specified. Minimum and maximum limits are ensured through test, design,
or statistical correlation. Typical values represent the most likely parametric norm at TJ = 25°C, and are provided for reference
purposes only. VIN = VEN = 3.3 V, unless otherwise indicated in the conditions column.
PARAMETER
TEST CONDITIONS
MIN (1)
TYP (2)
MAX (1)
UNIT
SYSTEM PARAMETERS
VIN = 2.95 V to 5.5 V
VOUT = 2.5 V
IOUT = 0 A to 4 A
0.8
V FB
Total Feedback Voltage
Variation Including Line
and Load Regulation
V FB
VIN = 3.3 V, VOUT = 2.5
over the operating junction
Feedback Voltage Variation V
temperature range TJ of
IOUT = 0 A
–40°C to 125°C
V FB
VIN = 3.3 V, VOUT = 2.5
over the operating junction
Feedback Voltage Variation V
temperature range TJ of
IOUT = 4 A
–40°C to 125°C
over the operating junction
temperature range TJ of
–40°C to 125°C
0.78
0.82
V
0.8
0.787
0.812
V
0.798
0.785
0.81
V
2.6
over the operating junction
temperature range TJ of
–40°C to 125°C
Rising
VIN(UVLO)
Input UVLO Threshold
(Measured at VIN pin)
Soft-Start Current
V
2.4
over the operating junction
temperature range TJ of
–40°C to 125°C
Falling
ISS
2.95
1.95
Charging Current
2
µA
1.7
IQ
Non-Switching Input
Current
ISD
Shutdown Quiescent
Current
IOCL
Output Current Limit
(Average Current)
VOUT = 2.5 V
fFB
Frequency Fold-back
In current limit
over the operating junction
temperature range TJ of
–40°C to 125°C
VFB = 1 V
3
mA
260
VIN = 5.5 V, VEN = 0 V
over the operating junction
temperature range TJ of
–40°C to 125°C
500
µA
5.5
over the operating junction
temperature range TJ of
–40°C to 125°C
4.1
6.7
250
A
kHz
PWM SECTION
1000
fSW
Switching Frequency
Drange
PWM Duty Cycle Range
over the operating junction temperature range TJ of
–40°C to 125°C
750
1160
over the operating junction temperature range TJ of
–40°C to 125°C
0%
100%
kHz
ENABLE CONTROL
1.23
VEN-IH
EN Pin Rising Threshold
over the operating junction temperature range TJ of
–40°C to 125°C
VEN-IF
EN Pin Falling Threshold
over the operating junction temperature range TJ of
–40°C to 125°C
1.8
V
1.06
(1)
(2)
0.8
V
Min and Max limits are 100% production tested at an ambient temperature (TA) of 25°C. Limits over the operating temperature range are
ensured through correlation using Statistical Quality Control (SQC) methods. Limits are used to calculate Average Outgoing Quality
Level (AOQL).
Typical numbers are at 25°C and represent the most likely parametric norm.
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Electrical Characteristics (continued)
Specifications are for TJ = 25°C unless otherwise specified. Minimum and maximum limits are ensured through test, design,
or statistical correlation. Typical values represent the most likely parametric norm at TJ = 25°C, and are provided for reference
purposes only. VIN = VEN = 3.3 V, unless otherwise indicated in the conditions column.
PARAMETER
TEST CONDITIONS
MIN (1)
TYP (2)
MAX (1)
UNIT
THERMAL CONTROL
TSD
TJ for Thermal Shutdown
TSD-HYS
Hysteresis for Thermal
Shutdown
145
°C
10
°C
PERFORMANCE PARAMETERS
ΔVOUT
Output Voltage Ripple
Refer to Table 1
VOUT = 2.5 V
Bandwidth Limit = 2 MHz
Refer to Table 5 Bandwidth Limit = 20 MHz
ΔVFB /
VFB
Feedback Voltage Line
Regulation
ΔVOUT /
VOUT
Output Voltage Line
Regulation
10
mVpk-pk
5
ΔVIN = 2.95 V to 5.5 V
IOUT = 0 A
0.04%
IOUT = 0 A to 4 A
0.25%
ΔVIN = 2.95 V to 5.5 V
IOUT = 0 A, VOUT = 2.5 V
0.04%
IOUT = 0 A to 4 A
VOUT = 2.5 V
0.25%
VOUT = 3.3 V
96.1%
VOUT = 2.5 V
94.8%
VOUT = 1.8 V
93.1%
EFFICIENCY
η
η
η
η
6
Peak Efficiency (1 A) VIN =
5V
Peak Efficiency (1 A) VIN =
3.3 V
Full Load Efficiency (4 A)
VIN = 5 V
Full Load Efficiency (4 A)
VIN = 3.3 V
VOUT = 1.5 V
92%
VOUT = 1.2 V
90.4%
VOUT = 0.8 V
86.8%
VOUT = 2.5 V
95.7%
VOUT = 1.8 V
94.1%
VOUT = 1.5 V
93%
VOUT = 1.2 V
91.6%
VOUT = 0.8V
88.3%
VOUT = 3.3 V
94.1%
VOUT = 2.5 V
92.4%
VOUT = 1.8 V
90%
VOUT = 1.5 V
88.3%
VOUT = 1.2 V
86.1%
VOUT = 0.8 V
80.8%
VOUT = 2.5 V
91.4%
VOUT = 1.8 V
90%
VOUT = 1.5 V
87.2%
VOUT = 1.2 V
84.9%
VOUT = 0.8 V
79.3%
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6.6 Typical Characteristics
Unless otherwise specified, the following conditions apply: VIN = VEN = 5 V, CIN is 47-µF 10-V X5R ceramic capacitor; TA =
25°C for efficiency curves and waveforms.
VOUT = 3.3 V
VOUT = 2.5 V
Figure 1. Efficiency
VOUT = 1.8 V
Figure 2. Efficiency
VOUT = 1.5 V
Figure 3. Efficiency
VOUT = 1.2 V
Figure 4. Efficiency
VOUT = 0.8 V
Figure 5. Efficiency
Figure 6. Efficiency
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Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = VEN = 5 V, CIN is 47-µF 10-V X5R ceramic capacitor; TA =
25°C for efficiency curves and waveforms.
VIN = 5 V, RθJA = 20°C/W
VIN = 3.3 V, RθJA = 20°C/W
Figure 7. Current Derating
Figure 8. Current Derating
VOUT = 2.5 V, IOUT = 0 A
VIN = 5 V, VOUT = 2.5 V, IOUT = 4 A Evaluation Board
Figure 10. Start-Up
Figure 9. Radiated Emissions (EN 55022, Class B)
VOUT = 2.5 V, IOUT = 0 A
VIN = 3.3 V, VOUT = 2.5 V, IOUT = 0.4-A to 3.6-A to 0.4-A step
20 mV/DIV, 20-MHz Bandwidth Limited
Refer to Table 5 for BOM, includes optional components
Figure 12. Load Transient Response
Figure 11. Prebiased Start-Up
8
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Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = VEN = 5 V, CIN is 47-µF 10-V X5R ceramic capacitor; TA =
25°C for efficiency curves and waveforms.
VIN = 5.0 V, VOUT = 2.5 V, IOUT = 0.4-A to 3.6-A to 0.4-A step
20 mV/DIV, 20-MHz Bandwidth Limited
Refer to Table 5 for BOM, includes optional components
VIN = 3.3 V, VOUT = 2.5 V, IOUT = 4 A, 20 mV/DIV
Refer to Table 5 for BOM
Figure 13. Load Transient Response
Figure 14. Output Voltage Ripple
VIN = 5.0 V, VOUT = 2.5 V, IOUT = 4 A,
20 mV/DIV, Refer to Table 5 for BOM
Figure 15. Output Voltage Ripple
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7 Detailed Description
7.1 Overview
The LMZ10504 SIMPLE SWITCHER power module is a complete, easy-to-use DC-DC solution capable of
driving up to a 4-A load with exceptional power conversion efficiency, output voltage accuracy, line and load
regulation. The LMZ10504 is available in an innovative package that enhances thermal performance and allows
for hand or machine soldering. The LMZ10504 is a reliable and robust solution with the following features:
lossless cycle-by-cycle peak current limit to protect for overcurrent or short-circuit fault, thermal shutdown, input
undervoltage lockout, and prebiased start-up.
7.2 Functional Block Diagram
VIN
1
1:
SS
5
FB
Drivers
Voltage
Mode
Control
3
2.2 PF
1.5 PH
6, 7
VOUT
N-MOSFET
2
EN
P-MOSFET
2.2 PF
4, EP
GND
7.3 Feature Description
7.3.1 Enable
The LMZ10504 features an enable (EN) pin and associated comparator to allow the user to easily sequence the
LMZ10504 from an external voltage rail, or to manually set the input UVLO threshold. The turnon or rising
threshold and hysteresis for this comparator are typically 1.23 V and 0.15 V, respectively. The precise reference
for the enable comparator allows the user to ensure that the LMZ10504 will be disabled when the system
demands it to be.
The EN pin should not be left floating. For always-on operation, connect EN to VIN.
7.3.2 Enable and UVLO
Using a resistor divider from VIN to EN as shown in the schematic diagram below, the input voltage at which the
part begins switching can be increased above the normal input UVLO level according to:
R + Renb
VIN (UVLO ) = 1.23V ´ ent
Renb
(1)
For example, suppose that the required input UVLO level is 3.69 V. Choosing Renb = 10 kΩ, then we calculate
Rent = 20 kΩ.
10
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Feature Description (continued)
VIN
VIN
LMZ10504
Rent
Cin1
EN
Renb
GND
Figure 16. Setting Enable and UVLO
Alternatively, the EN pin can be driven from another voltage source to cater to system sequencing requirements
commonly found in FPGA and other multi-rail applications. Figure 17 shows an LMZ10504 that is sequenced to
start based on the voltage level of a master system rail (VOUT1).
VOUT1
VIN
VIN
VOUT2
VOUT
Rent
Cin1
LMZ10504
CO1
EN
Renb
GND
Figure 17. Setting Enable and UVLO Using External Power Supply
7.3.3 Soft-Start
The LMZ10504 begins to operate when both the VIN and EN, voltages exceed the rising UVLO and enable
thresholds, respectively. A controlled soft-start eliminates inrush currents during start-up and allows the user
more control and flexibility when sequencing the LMZ10504 with other power supplies.
In the event of either VIN or EN decreasing below the falling UVLO or enable threshold respectively, the voltage
on the soft-start pin is collapsed by discharging the soft-start capacitor by a 14-µA (typical) current sink to
ground.
7.3.4 Soft-Start Capacitor
Determine the soft-start capacitance with the following relationship:
t ´I
CSS = ss ss
VFB
where
•
•
•
VFB is the internal reference voltage (nominally 0.8 V),
ISS is the soft-start charging current (nominally 2 µA)
and CSS is the external soft-start capacitance.
(2)
Thus, the required soft-start capacitor per unit output voltage start-up time is given by:
CSS = 2.5 nF / ms
(3)
For example, a 4-ms soft-start time will yield a 10-nF capacitance. The minimum soft-start capacitance is 680 pF.
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Feature Description (continued)
7.3.5 Tracking
The LMZ10504 can track the output of a master power supply during soft-start by connecting a resistor divider to
the SS pin. In this way, the output voltage slew rate of the LMZ10504 will be controlled by a master supply for
loads that require precise sequencing. When the tracking function is used, a small value soft-start capacitor
should be connected to the SS pin to alleviate output voltage overshoot when recovering from a current limit
fault.
Master Power
Supply
VOUT1
VIN
VOUT2
VIN
VOUT
Rtrkt
Cin1
EN
LMZ10504
CO1
SS
VSS
Rtrkb
GND
Figure 18. Tracking Using External Power Supply
7.3.6 Tracking - Equal Soft-Start Time
One way to use the tracking feature is to design the tracking resistor divider so that the master supply output
voltage, VOUT1, and the LMZ10504 output voltage, VOUT2, both rise together and reach their target values at the
same time. This is termed ratiometric start-up. For this case, the equation governing the values of tracking divider
resistors Rtrkb and Rtrkt is given by:
Rtrkt
Rtrkb =
VOUT 1 - 1.0V
(4)
The above equation includes an offset voltage, of 200 mV, to ensure that the final value of the SS pin voltage
exceeds the reference voltage of the LMZ10504. This offset will cause the LMZ10504 output voltage to reach
regulation slightly before the master supply. For a value of 33 kΩ, 1% is recommended for Rtrkt as a compromise
between high-precision and low-quiescent current through the divider while minimizing the effect of the 2-µA softstart current source.
For example, if the master supply voltage VOUT1 is 3.3 V and the LMZ10504 output voltage was 1.8 V, then the
value of Rtrkb needed to give the two supplies identical soft-start times would be 14.3 kΩ. Figure 19 shows an
example of tracking using the equal soft-start time.
RATIOMETRIC STARTUP
VOUT1
VOLTAGE
VOUT2
EN
TIME
Figure 19. Timing Diagram for Tracking Using Equal Soft-Start Time
12
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Feature Description (continued)
7.3.7 Tracking - Equal Slew Rates
Alternatively, the tracking feature can be used to have similar output voltage ramp rates. This is referred to as
simultaneous start-up. In this case, the tracking resistors can be determined based on Equation 5:
0.8V
´ Rtrkt
Rtrkb =
VOUT 2 - 0.8V
(5)
and to ensure proper overdrive of the SS pin
VOUT 2 < 0.8 ´ VOUT1
(6)
For the example case of VOUT1 = 5 V and VOUT2 = 2.5 V, with Rtrkt set to 33 kΩ as before, Rtrkb is calculated from
the above equation to be 15.5 kΩ. Figure 20 shows an example of tracking using the equal slew rates.
SIMULTANEOUS STARTUP
VOUT1
VOLTAGE
VOUT2
EN
TIME
Figure 20. Timing Diagram for Tracking Using Equal Slew Rates
7.3.8 Current Limit
When a current greater than the output current limit (IOCL) is sensed, the ON-time is immediately terminated and
the low-side MOSFET is activated. The low-side MOSFET stays on for the entire next four switching cycles.
During these skipped pulses, the voltage on the soft-start pin is reduced by discharging the soft-start capacitor by
a current sink on the soft-start pin of nominally 14 µA. Subsequent overcurrent events will drain more and more
charge from the soft-start capacitor, effectively decreasing the reference voltage as the output droops due to the
pulse skipping. Reactivation of the soft-start circuitry ensures that when the overcurrent situation is removed, the
part will resume normal operation smoothly.
7.3.9 Overtemperature Protection
When the LMZ10504 senses a junction temperature greater than 145°C (typical), both switching MOSFETs are
turned off and the part enters a standby state. Upon sensing a junction temperature below 135°C (typical), the
part will re-initiate the soft-start sequence and begin switching once again.
7.4 Device Functional Modes
7.4.1 Prebias Start-Up Capability
At start-up, the LMZ10504 is in a prebiased state when the output voltage is greater than zero. This often occurs
in many multi-rail applications such as when powering an ASIC, FPGA, or DSP. The output can be prebiased in
these applications through parasitic conduction paths from one supply rail to another. Even though the
LMZ10504 is a synchronous converter, it will not pull the output low when a prebias condition exists. The
LMZ10504 will not sink current during start-up until the soft-start voltage exceeds the voltage on the FB pin.
Because the device does not sink current it protects the load from damage that might otherwise occur if current
is conducted through the parasitic paths of the load.
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8 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The LMZ10504 is a step-down DC-to-DC power module. It is typically used to convert a higher DC voltage to a
lower DC voltage with a maximum output current of 4 A. The following design procedure can be used to select
components for the LMZ10504. Alternately, the WEBENCH software may be used to generate complete designs.
When generating a design, the WEBENCH software uses iterative design procedure and accesses
comprehensive databases of components. Please go to www.ti.com for more details.
8.2 Typical Application
This section provides several application solutions with an associated bill of materials. The compensation for
each solution was optimized to work over the full input range. Many applications have a fixed input voltage rail. It
is possible to modify the compensation to obtain a faster transient response for a given input voltage operating
point.
U1
VIN
1
2
VOUT
VIN
VOUT
6, 7
CO1
LMZ10504
EN
FB
Cin1
SS
3
5
GND
4, EP
Rfbt
CSS
Rcomp
Ccomp
Rfbb
Figure 21. Typical Applications Schematic
8.2.1 Design Requirements
For this example the following application parameters exist.
• VIN = 5 V
• VOUT = 2.5 V
• IOUT = 4 A
• ΔVOUT = 20 mVpk-pk
• ΔVo_tran = ±20 mVpk-pk
Table 1. Bill of Materials, VIN = 3.3 V to 5 V, VOUT = 2.5 V, IOUT (MAX) = 4 A, Optimized for Electrolytic Input
and Output Capacitance
DESIGNATOR
14
DESCRIPTION
CASE SIZE
MANUFACTURER
MANUFACTURER P/N
QUANTITY
U1
SIMPLE SWITCHER
PFM-7
Texas Instruments
LMZ10504TZ-ADJ
1
Cin1
150 µF, 6.3 V, 18 mΩ
C2, 6.0 x 3.2 x 1.8 mm
Sanyo
6TPE150MIC2
1
CO1
330 µF, 6.3 V, 18 mΩ
D3L, 7.3 x 4.3 x 2.8
mm
Sanyo
6TPE330MIL
1
Rfbt
100 kΩ
0603
Vishay Dale
CRCW0603100KFKEA
1
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Typical Application (continued)
Table 1. Bill of Materials, VIN = 3.3 V to 5 V, VOUT = 2.5 V, IOUT (MAX) = 4 A, Optimized for Electrolytic Input
and Output Capacitance (continued)
DESIGNATOR
DESCRIPTION
CASE SIZE
MANUFACTURER
MANUFACTURER P/N
QUANTITY
Rfbb
47.5 kΩ
0603
Vishay Dale
CRCW060347K5FKEA
1
Rcomp
15 kΩ
0603
Vishay Dale
CRCW060315K0FKEA
1
Ccomp
330 pF, ±5%, C0G, 50 V
0603
TDK
C1608C0G1H331J
1
CSS
10 nF, ±10%, X7R, 16 V
0603
Murata
GRM188R71C103KA01
1
Table 2. Bill of Materials, VIN = 3.3 V, VOUT = 0.8 V, IOUT (MAX) = 4 A, Optimized for Solution Size and
Transient Response (1)
DESIGNATOR
DESCRIPTION
CASE SIZE
MANUFACTURER
MANUFACTURER P/N
QUANTITY
U1
SIMPLE SWITCHER
PFM-7
Texas Instruments
LMZ10504TZ-ADJ
1
Cin1, CO1
47 µF, X5R, 6.3 V
1206
TDK
C3216X5R0J476M
2
(1)
Rfbt
110 kΩ
0402
Vishay Dale
CRCW0402100KFKED
1
Rcomp
1.0 kΩ
0402
Vishay Dale
CRCW04021K00FKED
1
Ccomp
27 pF, ±5%, C0G, 50 V
0402
Murata
GRM1555C1H270JZ01
1
CSS
10 nF, ±10%, X7R, 16 V
0402
Murata
GRM155R71C103KA01
1
In the case where the output voltage is 0.8 V, TI recommends to remove Rfbb and keep Rfbt, Rcomp, and Ccomp for a type III
compensation.
8.2.2 Detailed Design Procedure
LMZ10504 is fully supported by WEBENCH and offers the following: component selection, performance,
electrical, and thermal simulations as well as the Build-It board, for a reduced design time. On the other hand, all
external components can be calculated by following the design procedure below.
1. Determine the input voltage and output voltage. Also, make note of the ripple voltage and voltage transient
requirements.
2. Determine the necessary input and output capacitance.
3. Calculate the feedback resistor divider.
4. Select the optimized compensation component values.
5. Estimate the power dissipation and board thermal requirements.
6. Follow the PCB design guideline.
7. Learn about the LMZ10504 features such as enable, input UVLO, soft-start, tracking, prebiased start-up,
current limit, and thermal shutdown.
8.2.2.1 Input Capacitor Selection
A 22-µF or 47-µF high-quality dielectric (X5R, X7R) ceramic capacitor rated at twice the maximum input voltage
is typically sufficient. The input capacitor must be placed as close as possible to the VIN pin and GND exposed
pad to substantially eliminate the parasitic effects of any stray inductance or resistance on the PCB and supply
lines.
Neglecting capacitor equivalent series resistance (ESR), the resultant input capacitor AC ripple voltage is a
triangular waveform. The minimum input capacitance for a given peak-to-peak value (ΔVIN) of VIN is specified as
follows:
I
´ D ´ (1 - D )
Cin ³ OUT
fsw ´ DVIN
where
•
the PWM duty cycle, D, is given by Equation 8
(7)
V
D = OUT
VIN
(8)
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If ΔVIN is 1% of VIN, this equals to 50 mV and fSW = 1 MHz.
æ 2.5V ö æ 2.5V ö
4A ´ ç
÷ ´ ç 1 - 5V ÷
è 5V ø è
ø ³ 20 mF
Cin ³
1 MHz ´ 50 mV
(9)
A second criteria before finalizing the Cin bypass capacitor is the RMS current capability. The necessary RMS
current rating of the input capacitor to a buck regulator can be estimated by:
ICin(RMS ) = IOUT ´ D(1 - D )
ICin(RMS ) = 4 A ´
2.5V
5V
(10)
æ 2.5V ö
ç 1 - 5V ÷ = 2 A
è
ø
(11)
With this high AC current present in the input capacitor, the RMS current rating becomes an important
parameter. The maximum input capacitor ripple voltage and RMS current occur at 50% duty cycle. Select an
input capacitor rated for at least the maximum calculated ICin(RMS).
Additional bulk capacitance with higher ESR may be required to damp any resonance effects of the input
capacitance and parasitic inductance.
8.2.2.2 Output Capacitor Selection
In general, 22-µF to 100-µF, high-quality dielectric (X5R, X7R) ceramic capacitor rated at twice the maximum
output voltage is sufficient given the optimal high-frequency characteristics and low ESR of ceramic dielectrics.
Although, the output capacitor can also be of electrolytic chemistry for increased capacitance density.
Two output capacitance equations are required to determine the minimum output capacitance. One equation
determines the output capacitance (CO) based on PWM ripple voltage. The second equation determines CO
based on the load transient characteristics. Select the largest capacitance value of the two.
The minimum capacitance, given the maximum output voltage ripple (ΔVOUT) requirement, is determined by the
following equation:
DiL
CO ³
8 ´ fsw ´ [DVOUT - ( DiL ´ RESR )]
where
•
DiL =
the peak to peak inductor current ripple (ΔiL) is equal to Equation 13:
(VIN - VOUT ) ´ D
L ´ fsw
(12)
(13)
RESR is the total output capacitor ESR, L is the inductance value of the internal power inductor, where L = 1.5
µH, and fSW = 1 MHz. Therefore, per the design example:
V
(5V - 2.5V ) ´ 2.5
5V
DiL =
= 833 mA
1.5 mH ´ 1 MHz
(14)
The minimum output capacitance requirement due to the PWM ripple voltage is:
833 mA
CO ³
8 ´ 1 MHz ´ éë20 mV - (833 mA ´ 3 mW )ùû
CO ³ 6 mF
(15)
(16)
Three mΩ is a typical RESR value for ceramic capacitors.
Equation 17 provides a good first pass capacitance requirement for a load transient:
Istep ´ VFB ´ L ´ VIN
CO ³
4 ´ VOUT ´ (VIN - VOUT ) ´ DVo _ tran
where
•
•
16
Istep is the peak to peak load step,
VFB = 0.8 V,
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•
and ΔVo_tran is the maximum output voltage deviation, which is ±20 mV.
(17)
Therefore the capacitance requirement for the given design parameters is:
3.2 A ´ 0.8V ´ 1.5mH ´ 5V
CO ³
4 ´ 2.5V ´ (5V - 2.5V ) ´ 20mV
(18)
CO ³ 39 mF
(19)
In this particular design the output capacitance is determined by the load transient requirements.
Table 3 lists some examples of commercially available capacitors that can be used with the LMZ10504.
Table 3. Recommended Output Filter Capacitors
CO (µF)
VOLTAGE (V), RESR (mΩ)
MAKE
MANUFACTURER
PART NUMBER
CASE SIZE
22
6.3, < 5
Ceramic, X5R
TDK
C3216X5R0J226M
1206
47
6.3, < 5
Ceramic, X5R
TDK
C3216X5R0J476M
1206
47
6.3, < 5
Ceramic, X5R
TDK
C3225X5R0J476M
1210
1210
47
10.0, < 5
Ceramic, X5R
TDK
C3225X5R1A476M
100
6.3, < 5
Ceramic, X5R
TDK
C3225X5R0J107M
1210
100
6.3, 50
Tantalum
AVX
TPSD157M006#0050
D, 7.5 × 4.3 × 2.9 mm
100
6.3, 25
Organic Polymer
Sanyo
6TPE100MPB2
B2, 3.5 × 2.8 × 1.9 mm
150
6.3, 18
Organic Polymer
Sanyo
6TPE150MIC2
C2, 6.0 × 3.2 × 1.8 mm
330
6.3, 18
Organic Polymer
Sanyo
6TPE330MIL
D3L, 7.3 × 4.3 × 2.8
mm
470
6.3, 23
Niobium Oxide
AVX
NOME37M006#0023
E, 7.3 × 4.3 × 4.1 mm
8.2.2.2.1 Output Voltage Setting
A resistor divider network from VOUT to the FB pin determines the desired output voltage as follows:
R + Rfbb
VOUT = 0.8V ´ fbt
Rfbb
(20)
Rfbt is defined based on the voltage loop requirements and Rfbb is then selected for the desired output voltage.
Resistors are normally selected as 0.5% or 1% tolerance. Higher accuracy resistors such as 0.1% are also
available.
The feedback voltage (at VOUT = 2.5 V) is accurate to within –2.5% / +2.5% over temperature and over line and
load regulation. Additionally, the LMZ10504 contains error nulling circuitry to substantially eliminate the feedback
voltage variation over temperature as well as the long-term aging effects of the internal amplifiers. In addition the
zero nulling circuit dramatically reduces the 1/f noise of the bandgap amplifier and reference. The manifestation
of this circuit action is that the duty cycle will have two slightly different but distinct operating points, each evident
every other switching cycle.
8.2.2.3 Loop Compensation
The LMZ10504 preserves flexibility by integrating the control components around the internal error amplifier while
using three small external compensation components from VOUT to FB. An integrated type II (two pole, one zero)
voltage-mode compensation network is featured. To ensure stability, an external resistor and small value
capacitor can be added across the upper feedback resistor as a pole-zero pair to complete a type III (three pole,
two zero) compensation network. The compensation components recommended in Table 4 provide type III
compensation at an optimal control loop performance. The typical phase margin is 45° with a bandwidth of 80
kHz. Calculated output capacitance values not listed in Table 4 should be verified before designing into
production. A detailed application note is available to provide verification support, AN-2013 SNVA417. In general,
calculated output capacitance values below the suggested value will have reduced phase margin and higher
control loop bandwidth. Output capacitance values above the suggested values will experience a lower
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bandwidth and increased phase margin. Higher bandwidth is associated with faster system response to sudden
changes such as load transients. Phase margin changes the characteristics of the response. Lower phase
margin is associated with underdamped ringing and higher phase margin is associated with overdamped
response. Losing all phase margin will cause the system to be unstable; an optimized area of operation is 30° to
60° of phase margin, with a bandwidth of 100 kHz ±20 kHz.
VIN
VOUT
VIN
EN
Ccomp
Rfbt
LMZ10504
Rcomp
FB
GND
Rfbb
Figure 22. Loop Compensation Control Components
Table 4. LMZ10504 Compensation Component Values
VIN (V)
5
3.3
(1)
18
CO (µF)
ESR (mΩ)
Rfbt (kΩ) (1)
Ccomp (pF) (1)
Rcomp (kΩ) (1)
MIN
MAX
22
2
20
200
27
1.5
47
2
20
124
68
1.4
100
1
10
82.5
150
0.681
150
1
5
63.4
220
1
150
10
25
63.4
220
3.48
150
26
50
226
62
12.1
220
15
30
150
100
6.98
220
31
60
316
560
14
22
2
20
118
43
9.09
47
2
20
76.8
100
3.32
100
1
10
49.9
180
2.49
150
1
5
40.2
330
1
150
10
25
43.2
330
4.99
150
26
50
143
100
7.5
220
15
30
100
180
4.99
220
31
60
200
100
8.06
In the special case where the output voltage is 0.8 V, TI recommends to remove Rfbb and keep Rfbt, Rcomp, and Ccomp for a type III
compensation.
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8.2.3 Application Curves
VOUT = 3.3 V
VOUT = 3.3 V
Figure 23. Current Derating
Figure 24. Efficiency
Figure 25. Radiated Emissions (EN 55022, Class B)
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8.3 System Examples
8.3.1 Application Schematic for 3.3-V to 5-V Input and 2.5-V Output With Optimized Ripple and Transient
Response
The compensation for each solution was optimized to work over the stated input range. Many applications have a
fixed input voltage rail. It is possible to modify the compensation to obtain a faster transient response for a given
input voltage operating point. This schematic is intended to serve as a helpful starting point towards an optimized
design.
U1
Optional
VIN
1
Cin2
+
2
VOUT
VIN
EN
CO1
LMZ10504
Cin1
Ccomp
FB
CO2
CO3
5 Rfbt
GND
SS
3
VOUT
6, 7
Rcomp
4, EP
CSS
Optional
Rfbb
Figure 26. Schematic for 2.5-V Output Based on 3.3-V to 5-V Input
Table 5. Bill of Materials, VIN = 3.3 V to 5 V, VOUT = 2.5 V, IOUT (MAX) = 4 A,
Optimized for Low Input and Output Ripple Voltage and Fast Transient Response (1)
DESIGNATOR
DESCRIPTION
CASE SIZE
MANUFACTURER
MANUFACTURER P/N
QUANTITY
1
(1)
U1
SIMPLE SWITCHER
PFM-7
Texas Instruments
LMZ10504TZ-ADJ
Cin1
22 µF, X5R, 10 V
1210
AVX
1210ZD226MAT
2
Cin2
220 µF, 10 V, AL-Elec
E
Panasonic
EEE1AA221AP
1*
CO1
4.7 µF, X5R, 10 V
0805
AVX
0805ZD475MAT
1*
CO2
22 µF, X5R, 6.3 V
1206
AVX
12066D226MAT
1*
CO3
100 µF, X5R, 6.3 V
1812
AVX
18126D107MAT
1
Rfbt
75 kΩ
0402
Vishay Dale
CRCW040275K0FKED
1
Rfbb
34.8 kΩ
0402
Vishay Dale
CRCW040234K8FKED
1
Rcomp
1.0 kΩ
0402
Vishay Dale
CRCW04021K00FKED
1
Ccomp
100 pF, ±5%, C0G, 50 V
0402
Murata
GRM1555C1H101JZ01
1
CSS
10 nF, ±10%, X7R, 16 V
0402
Murata
GRM155R71C103KA01
1
* Optional components, include for low input and output voltage ripple.
Table 6. Output Voltage Setting (Rfbt = 75 kΩ)
20
VOUT
Rfbb
2.5 V
34.8 kΩ
1.8 V
59 kΩ
1.5 V
84.5 kΩ
1.2 V
150 kΩ
0.9 V
590 kΩ
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8.3.2 Application Schematic for 3.3-V to 5-V Input and 2.5-V Output
The compensation for each solution was optimized to work over the stated input range. Many applications have a
fixed input voltage rail. It is possible to modify the compensation to obtain a faster transient response for a given
input voltage operating point. This schematic is intended to serve as a helpful starting point towards an optimized
design.
U1
VIN
1
+
Cin4
Cin3
Cin2
Cin1
CO1
LMZ10504
Ren1
Cin5
VOUT
6, 7
VOUT
VIN
FB
EN
2
SS
3
CO2
CO3
5
GND
4, EP
Rfbt
CSS
Rcomp
Ccomp
Rfbb
Figure 27. Schematic for 2.5-V Output Based on 3.3-V to 5-V Input
Table 7. Bill of Materials, VIN = 3.3 V to 5 V, VOUT = 2.5 V, IOUT (MAX) = 4 A
DESIGNATOR
DESCRIPTION
CASE SIZE
MANUFACTURER
MANUFACTURER P/N
QUANTITY
U1
SIMPLE SWITCHER
PFM-7
Texas Instruments
LMZ10504TZ-ADJ
1
Cin1
1 µF, X7R, 16 V
0805
TDK
C2012X7R1C105K
1
Cin2, CO1
4.7 µF, X5R, 6.3 V
0805
TDK
C2012X5R0J475K
2
Cin3, CO2
22 µF, X5R, 16 V
1210
TDK
C3225X5R1C226M
2
Cin4
47 µF, X5R, 6.3 V
1210
TDK
C3225X5R0J476M
1
Cin5
220 µF, 10 V, AL-Elec
E
Panasonic
EEE1AA221AP
1
CO3
100 µF, X5R, 6.3 V
1812
TDK
C4532X5R0J107M
1
Rfbt
75 kΩ
0805
Vishay Dale
CRCW080575K0FKEA
1
Rfbb
34.8 kΩ
0805
Vishay Dale
CRCW080534K8FKEA
1
Rcomp
1.1 kΩ
0805
Vishay Dale
CRCW08051K10FKEA
1
Ccomp
180 pF, ±5%, C0G, 50 V
0603
TDK
C1608C0G1H181J
1
Ren1
100 kΩ
0805
Vishay Dale
CRCW0805100KFKEA
1
CSS
10 nF, ±5%, C0G, 50 V
0805
TDK
C2012C0G1H103J
1
Table 8. Output Voltage Setting (Rfbt = 75 kΩ)
VOUT
Rfbb
3.3 V
23.7 kΩ
2.5 V
34.8 kΩ
1.8 V
59 kΩ
1.5 V
84.5 kΩ
1.2 V
150 kΩ
0.9 V
590 kΩ
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8.3.3 EMI Tested Schematic for 2.5-V Output Based on 3.3-V to 5-V Input
The compensation for each solution was optimized to work over the stated input range. Many applications have a
fixed input voltage rail. It is possible to modify the compensation to obtain a faster transient response for a given
input voltage operating point. This schematic is intended to serve as a helpful starting point towards an optimized
design.
U1
VIN
1
VOUT
VIN
VOUT
6, 7
CO1
LMZ10504
Cin3
Cin2
Cin1
2
FB
EN
SS
3
5
GND
4, EP
Rfbt
CSS
Rcomp
Ccomp
Rfbb
Figure 28. EMI Tested Schematic for 2.5-V Output Based on 3.3-V to 5-V Input
Table 9. Bill of Materials, VIN = 5 V, VOUT = 2.5 V, IOUT (MAX) = 4 A,
Tested With EN55022 Class B Radiated Emissions
DESIGNATOR
DESCRIPTION
CASE SIZE
MANUFACTURER
MANUFACTURER P/N
QUANTITY
U1
SIMPLE SWITCHER
PFM-7
Texas Instruments
LMZ10504TZ-ADJ
1
Cin1
1 µF, X7R, 16 V
0805
TDK
C2012X7R1C105K
1
Cin2
4.7 µF, X5R, 6.3 V
0805
TDK
C2012X5R0J475K
1
Cin3
47 µF, X5R, 6.3 V
1210
TDK
C3225X5R0J476M
1
CO1
100 µF, X5R, 6.3 V
1812
TDK
C4532X5R0J107M
1
Rfbt
75 kΩ
0805
Vishay Dale
CRCW080575K0FKEA
1
Rfbb
34.8 kΩ
0805
Vishay Dale
CRCW080534K8FKEA
1
Rcomp
1.1 kΩ
0805
Vishay Dale
CRCW08051K10FKEA
1
Ccomp
180 pF, ±5%, C0G, 50 V
0603
TDK
C1608C0G1H181J
1
CSS
10 nF, ±5%, C0G, 50 V
0805
TDK
C2012C0G1H103J
1
Table 10. Output Voltage Setting (Rfbt = 75 kΩ)
22
VOUT
Rfbb
3.3 V
23.7 kΩ
2.5 V
34.8 kΩ
1.8 V
59 kΩ
1.5 V
84.5 kΩ
1.2 V
150 kΩ
0.9 V
590 kΩ
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9 Power Supply Recommendations
The LMZ10504 device is designed to operate from an input voltage supply range between 2.95 V and 5.5 V. This
input supply should be well regulated and able to withstand maximum input current and maintain a stable
voltage. The resistance of the input supply rail should be low enough that an input current transient does not
cause a high enough drop at the LMZ10504 supply voltage that can cause a false UVLO fault triggering and
system reset. If the input supply is more than a few inches from the LMZ10504, additional bulk capacitance may
be required in addition to the ceramic bypass capacitors. The amount of bulk capacitance is not critical, but a 47μF or 100-μF electrolytic capacitor is a typical choice.
10 Layout
10.1 Layout Guidelines
PCB layout is an important part of DC-DC converter design. Poor board layout can disrupt the performance of a
DC-DC converter and surrounding circuitry by contributing to EMI, ground bounce and resistive voltage drop in
the traces. These can send erroneous signals to the DC-DC converter resulting in poor regulation or instability.
Good layout can be implemented by following a few simple design rules.
1. Minimize area of switched current loops.
From an EMI reduction standpoint, it is imperative to minimize the high di/dt current paths. The high current
that does not overlap contains high di/dt, see Figure 29. Therefore physically place input capacitor (Cin1) as
close as possible to the LMZ10504 VIN pin and GND exposed pad to avoid observable high-frequency noise
on the output pin. This will minimize the high di/dt area and reduce radiated EMI. Additionally, grounding for
both the input and output capacitor should consist of a localized top side plane that connects to the GND
exposed pad (EP).
2. Have a single point ground.
The ground connections for the feedback, soft-start, and enable components should be routed only to the
GND pin of the device. This prevents any switched or load currents from flowing in the analog ground traces.
If not properly placed, poor grounding can result in degraded load regulation or erratic output voltage ripple
behavior. Provide the single point ground connection from pin 4 to EP.
3. Minimize trace length to the FB pin.
Both feedback resistors, Rfbt and Rfbb, and the compensation components, Rcomp and Ccomp, should be
located close to the FB pin. Since the FB node is high impedance, keep the copper area as small as
possible. This is most important as relatively high-value resistors are used to set the output voltage.
4. Make input and output bus connections as wide as possible.
This reduces any voltage drops on the input or output of the converter and maximizes efficiency. To optimize
voltage accuracy at the load, ensure that a separate feedback voltage sense trace is made at the load. Doing
so will correct for voltage drops and provide optimum output accuracy.
5. Provide adequate device heat-sinking.
Use an array of heat-sinking vias to connect the exposed pad to the ground plane on the bottom PCB layer.
If the PCB has multiple copper layers, thermal vias can also be employed to make connection to inner layer
heat-spreading ground planes. For best results use a 6 × 6 via array with minimum via diameter of 8 mils
thermal vias spaced 59 mils (1.5 mm). Ensure enough copper area is used for heat-sinking to keep the
junction temperature below 125°C.
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10.2 Layout Examples
VIN
VOUT
LMZ10504
VIN
VOUT
High dI
dt
Cin1
CO1
GND
Loop 2
Loop 1
Figure 29. Critical Current Loops to Minimize
Top View
Thermal V ias
GND
GND
E XP OSE D P AD
1
2
3
4 5
6 7
VIN
SS
EN
FB
GND
VOUT
VOUT
CIN
VIN
RENT
CSS
RENB
COUT
VOUT
RFB T
CFF
RFB B
GND Plane
Figure 30. PCB Layout Guide
Figure 31. Top Copper
24
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Layout Examples (continued)
Figure 32. Internal Layer 1 (Ground)
Figure 33. Internal Layer 2 (Ground and Signal Traces)
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Layout Examples (continued)
Figure 34. Bottom Copper
10.3 Estimate Power Dissipation and Thermal Considerations
Use the current derating curves in the Typical Characteristics section to obtain an estimate of power loss
(PIC_LOSS). For the design case of VIN = 5 V, VOUT = 2.5 V, IOUT = 4 A, TA(MAX) = 85°C , and TJ(MAX) = 125°C, the
device must see a thermal resistance from case to ambient (θCA) of less than:
TJ (MAX ) - TA(MAX )
qCA ³
- qJC
PIC _ LOSS
(21)
θCA <
o
o
C
C
125 oC - 85 oC
- 1.9
< 41
W
W
930 mW
(22)
Given the typical thermal resistance from junction to case (θJC) to be 1.9°C/W (typical). Continuously operating at
a TJ greater than 125°C will have a shorten life span.
To reach θCA = 41°C/W, the PCB is required to dissipate heat effectively. With no airflow and no external heat, a
good estimate of the required board area covered by 1-oz. copper on both the top and bottom metal layers is:
Board Area_cm 2 ³
Board Area_cm 2 ³
500 oC ´ cm 2
g
qCA
W
o
C ´ cm
W
41 C
500
o
(23)
2
g
(24)
As a result, approximately 12 square cm of 1-oz. copper on top and bottom layers is required for the PCB
design.
The PCB copper heat sink must be connected to the exposed pad (EP). Approximately thirty six, 8 mils thermal
vias spaced 59 mils (1.5 mm) apart must connect the top copper to the bottom copper. For an extended
discussion and formulations of thermal rules of thumb, refer to AN-2020 (SNVA419) and for an example of a high
thermal performance PCB layout, refer to the evaluation board application note AN-2022 (SNVA421).
26
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10.4 Power Module SMT Guidelines
The recommendations below are for a standard module surface mount assembly.
• Land Pattern – Follow the PCB land pattern with either soldermask defined or non-soldermask defined pads
• Stencil Aperture
– For the exposed die attach pad (DAP), adjust the stencil for approximately 80% coverage of the PCB land
pattern
– For all other I/O pads use a 1:1 ratio between the aperture and the land pattern recommendation
• Solder Paste – Use a standard SAC Alloy such as SAC 305, type 3 or higher
• Stencil Thickness – 0.125 to 0.15 mm
• Reflow - Refer to solder paste supplier recommendation and optimized per board size and density
• Maximum number of reflows allowed is one
• Refer to AN Design Summary LMZ1xxx and LMZ2xxx Power Modules Family (SNAA214) for reflow
information.
Figure 35. Sample Reflow Profile
Table 11. Sample Reflow Profile Table
PROBE
MAX TEMP
(°C)
REACHED
MAX TEMP
TIME ABOVE
235°C
REACHED
235°C
TIME ABOVE
245°C
REACHED
245°C
TIME ABOVE
260°C
REACHED
260°C
1
242.5
6.58
0.49
6.39
0.00
–
0.00
–
2
242.5
7.10
0.55
6.31
0.00
7.10
0.00
–
3
241.0
7.09
0.42
6.44
0.00
–
0.00
–
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11 Device and Documentation Support
11.1 Device Support
11.1.1 Third-Party Products Disclaimer
TI'S PUBLICATION OF INFORMATION REGARDING THIRD-PARTY PRODUCTS OR SERVICES DOES NOT
CONSTITUTE AN ENDORSEMENT REGARDING THE SUITABILITY OF SUCH PRODUCTS OR SERVICES
OR A WARRANTY, REPRESENTATION OR ENDORSEMENT OF SUCH PRODUCTS OR SERVICES, EITHER
ALONE OR IN COMBINATION WITH ANY TI PRODUCT OR SERVICE.
11.1.2 Development Support
For developmental support, see the following:
WEBENCH Tool, http://www.ti.com/webench
11.2 Documentation Support
11.2.1 Related Documentation
For related documentation, see the following:
• AN-2027 Inverting Application for the LMZ14203 SIMPLE SWITCHER Power Module, SNVA425)
• Absolute Maximum Ratings for Soldering, (SNOA549)
• AN-2024 LMZ1420x / LMZ1200x Evaluation Board (SNVA422)
• AN-2020 Thermal Design By Insight, Not Hindsight (SNVA419)
• AN-2026 Effect of PCB Design on Thermal Performance of SIMPLE SWITCHER Power Modules (SNVA424)
• Design Summary LMZ1xxx and LMZ2xxx Power Modules Family (SNAA214)
11.3 Community Resources
The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.
11.4 Trademarks
WEBENCH, E2E are trademarks of Texas Instruments.
SIMPLE SWITCHER is a registered trademark of Texas Instruments.
All other trademarks are the property of their respective owners.
11.5 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
11.6 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
28
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12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
www.ti.com
6-Aug-2015
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
Lead/Ball Finish
MSL Peak Temp
(2)
(6)
(3)
Op Temp (°C)
Device Marking
(4/5)
LMZ10504TZ-ADJ/NOPB
ACTIVE
TO-PMOD
NDW
7
250
Green (RoHS
& no Sb/Br)
CU SN
Level-3-245C-168 HR
-40 to 85
LMZ10504
TZ-ADJ
LMZ10504TZE-ADJ/NOPB
ACTIVE
TO-PMOD
NDW
7
45
Green (RoHS
& no Sb/Br)
CU SN
Level-3-245C-168 HR
-40 to 85
LMZ10504
TZ-ADJ
LMZ10504TZX-ADJ/NOPB
ACTIVE
TO-PMOD
NDW
7
500
Green (RoHS
& no Sb/Br)
CU SN
Level-3-245C-168 HR
-40 to 85
LMZ10504
TZ-ADJ
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3)
MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4)
There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5)
Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead/Ball Finish - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead/Ball Finish values may wrap to two lines if the finish
value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
Addendum-Page 1
Samples
PACKAGE OPTION ADDENDUM
www.ti.com
6-Aug-2015
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
6-Aug-2015
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
LMZ10504TZ-ADJ/NOPB
LMZ10504TZX-ADJ/NOP
B
Package Package Pins
Type Drawing
SPQ
Reel
Reel
A0
Diameter Width (mm)
(mm) W1 (mm)
B0
(mm)
K0
(mm)
P1
(mm)
W
Pin1
(mm) Quadrant
TOPMOD
NDW
7
250
330.0
24.4
10.6
14.22
5.0
16.0
24.0
Q2
TOPMOD
NDW
7
500
330.0
24.4
10.6
14.22
5.0
16.0
24.0
Q2
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
6-Aug-2015
*All dimensions are nominal
Device
Package Type
Package Drawing
Pins
SPQ
Length (mm)
Width (mm)
Height (mm)
LMZ10504TZ-ADJ/NOPB
TO-PMOD
NDW
7
250
367.0
367.0
45.0
LMZ10504TZX-ADJ/NOPB
TO-PMOD
NDW
7
500
367.0
367.0
45.0
Pack Materials-Page 2
MECHANICAL DATA
NDW0007A
BOTTOM SIDE OF PACKAGE
TOP SIDE OF PACKAGE
TZA07A (Rev D)
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