NCV33163 Product Preview 2.5 A, Step−Up/Down/ Inverting Switching Regulators The NCV33163 series are monolithic power switching regulators that contain the primary functions required for dc-to-dc converters. This series is specifically designed to be incorporated in step-up, step-down, and voltage-inverting applications with a minimum number of external components. These devices consist of two high gain voltage feedback comparators, temperature compensated reference, controlled duty cycle oscillator, driver with bootstrap capability for increased efficiency, and a high current output switch. Protective features consist of cycle-by-cycle current limiting, and internal thermal shutdown. Also included is a low voltage indicator output designed to interface with microprocessor based systems. These devices are contained in a 16 pin dual-in-line heat tab plastic package for improved thermal conduction. • Output Switch Current in Excess of 2.0 A • Operation from 2.5 V to 60 VOC Input • Low Standby Current • Precision 2% Reference • Controlled Duty Cycle Oscillator • Driver with Bootstrap Capability for Increased Efficiency • Cycle-by-Cycle Current Limiting • Internal Thermal Shutdown Protection • Low Voltage Indicator Output for Direct Microprocessor Interface • Heat Tab Power Package • Moisture Sensitivity Level (MSL) Equals 1 • NCV Prefix, for Automotive and Other Applications Requiring Site and Change Control http://onsemi.com MARKING DIAGRAMS 16 PDIP-16 P SUFFIX CASE 648C 16 NCV33163P AWLYYWW 1 1 16 SO-16W DW SUFFIX CASE 751G 16 NCV33163DW AWLYYWW 1 A WL YY WW = Assembly Location 1 = Wafer Lot = Year = Work Week PIN CONNECTIONS LVI Output 1 16 Bootstrap Input Voltage Feedback 2 2 15 Voltage Feedback 1 3 14 4 13 5 12 Timing Capacitor 6 11 VCC 7 10 Ipk Sense 8 9 Driver Collector Switch Emitter Gnd Gnd Switch Collector (Top View) ORDERING INFORMATION Device Package Shipping NCV33163DW SO-16W 47 Units/Rail NCV33163DWR2 SO-16W 1000 Tape & Reel NCV33163P PDIP-16 25 Units/Rail This document contains information on a product under development. ON Semiconductor reserves the right to change or discontinue this product without notice. Semiconductor Components Industries, LLC, 2002 November, 2002 - Rev. 0 1 Publication Order Number: NCV33163/D NCV33163 Ipk Sense 8 ILimit − 9 Driver Collector + VCC Timing Capacitor 7 10 + 6 11 OSC 5 12 Control Logic and Thermal Shutdown Gnd 4 Voltage Feedback 1 Switch Collector Gnd 13 + 3 Voltage Feedback 2 2 LVI Output 1 14 + + − Switch Emitter VFB 15 LVI + + − 16 Bootstrap Input + (Bottom View) This device contains 114 active transistors. Figure 1. Representative Block Diagram MAXIMUM RATINGS (Note 1) Symbol Value Unit VCC 60 V VC(switch) -1.0 to + 60 V Switch Emitter Voltage Range VE(switch) - 2.0 to VC(switch) V Switch Collector to Emitter Voltage VCE(switch) 60 V Switch Current (Note 2) ISW 2.5 A Driver Collector Voltage VC(driver) -1.0 to +60 V Driver Collector Current IC(driver) 150 mA IBS -100 to +100 mA VIpk (Sense) (VCC-7.0) to (VCC+1.0) V Vin -1.0 to + 7.0 V Low Voltage Indicator Output Voltage Range VC(LVI) -1.0 to + 60 V Low Voltage Indicator Output Sink Current IC(LVI) 10 mA Rating Power Supply Voltage Switch Collector Voltage Range Bootstrap Input Current Range (Note 2) Current Sense Input Voltage Range Feedback and Timing Capacitor Input Voltage Range °C/W Thermal Characteristics P Suffix, Dual-In-Line Case 648C Thermal Resistance, Junction-to-Air Thermal Resistance, Junction- to- Case (Pins 4, 5, 12, 13) DW Suffix, Surface Mount Case 751G Thermal Resistance, Junction-to-Air Thermal Resistance, Junction- to- Case (Pins 4, 5, 12, 13) RJA RJC 80 15 RJA RJC 94 18 Operating Junction Temperature TJ +150 °C Operating Ambient Temperature TA - 40 to + 115 °C Storage Temperature Range Tstg - 65 to +150 °C http://onsemi.com 2 NCV33163 ELECTRICAL CHARACTERISTICS (VCC = 15 V, Pin 16 = VCC, CT = 620 pF, for typical values TA = 25°C, for min/max values TA = -40°C to +115°C.) Symbol Characteristic Min Typ Max 46 45 50 - 54 55 Unit OSCILLATOR Frequency TA = 25°C Total Variation over VCC = 2.5 V to 60 V, and Temperature fOSC Charge Current Ichg - 225 - A Idischg - 25 - A Ichg/Idischg 8.0 9.0 10 - Sawtooth Peak Voltage VOSC(P) - 1.25 - V Sawtooth Valley Voltage VOSC(V) - 0.55 - V 4.9 4.85 5.05 0.008 - 5.2 0.03 5.25 V %/V V - 100 200 A 1.225 1.213 1.25 0.008 - 1.275 0.03 1.287 V %/V V - 0.4 0 0.4 A 230 250 - 270 - 1.0 20 - 0.6 1.0 1.0 1.4 IC(off) - 0.02 100 A Isource(DRV) 0.5 2.0 4.0 mA VZ VCC + 6.0 VCC + 7.0 VCC + 9.0 V Input Threshold (VFB2 Increasing) Vth 1.07 1.125 1.18 V Input Hysteresis (VFB2 Decreasing) VH - 15 - mV Output Sink Saturation Voltage (Isink = 2.0 mA) VOL(LVI) - 0.15 0.4 V Output Off-State Leakage Current (VOH = 15 V) IOH - 0.01 5.0 A ICC - 6.0 10 mA Discharge Current Charge to Discharge Current Ratio kHz FEEDBACK COMPARATOR 1 Threshold Voltage TA = 25°C Line Regulation (VCC = 2.5 V to 60 V, TA = 25°C) Total Variation over Line, and Temperature Vth(FB1) Input Bias Current (VFB1 = 5.05 V) IIB(FB1) FEEDBACK COMPARATOR 2 Threshold Voltage TA = 25°C Line Regulation (VCC = 2.5 V to 60 V, TA = 25°C) Total Variation over Line, and Temperature Vth(FB2) Input Bias Current (VFB2 = 1.25 V) IIB(FB2) CURRENT LIMIT COMPARATOR Vth(Ipk Sense) Threshold Voltage TA = 25°C Total Variation over VCC = 2.5 V to 60 V, and Temperature Input Bias Current (VIpk (Sense) = 15 V) IIB(sense) mV A DRIVER AND OUTPUT SWITCH (Note 3) Sink Saturation Voltage (ISW = 2.5 A, Pins 14, 15 grounded) Non-Darlington Connection (RPin 9 = 110 to VCC, ISW/IDRV ≈ 20) Darlington Connection (Pins 9, 10, 11 connected) Collector Off-State Leakage Current (VCE = 60 V) Bootstrap Input Current Source (VBS = VCC + 5.0 V) VCE(sat) Bootstrap Input Zener Clamp Voltage (IZ = 25 mA) V LOW VOLTAGE INDICATOR TOTAL DEVICE Standby Supply Current (VCC = 2.5 V to 60 V, Pin 8 = VCC, Pins 6, 14, 15 = Gnd, remaining pins open) 1. This device series contains ESD protection and exceeds the following tests: Human Body Model 1500 V per MIL-STD-883, Method 3015. Machine Model Method 150 V. 2. Maximum package power dissipation limits must be observed. 3. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible. http://onsemi.com 3 100 10 VCC = 15 V TA = 25°C 1)ton, RDT = ∞ 2)ton, RDT = 20 k 3)ton, toff, RDT = 10 k 4)toff, RDT = 20 k 5)toff, RDT = ∞ ∆ f OSC, OSCILLATOR FREQUENCY CHANGE (%) t on −t off , OUTPUT SWITCH ON−OFF TIME ( µ s) NCV33163 1 2 3 4 5 1.0 0.1 1.0 CT, OSCILLATOR TIMING CAPACITOR (nF) 10 2.0 VCC = 15 V CT = 620 pF 0 −2.0 −4.0 −6.0 −55 −25 IIB , INPUT BIAS CURRENT (A) µ 140 VCC = 15 V VFB1 = 5.05 V 120 100 80 60 −55 −25 0 25 50 75 TA, AMBIENT TEMPERATURE (°C) 100 125 V Z, BOOTSTRAP INPUT ZENER CLAMP VOLTAGE (V) I source (DRV), BOOTSTRAP INPUT CURRENT SOURCE (mA) Figure 4. Feedback Comparator 1 Input Bias Current versus Temperature 2.8 VCC = 15 V Pin 16 = VCC + 5.0 V 2.4 2.0 1.6 1.2 −55 −25 0 25 50 75 TA, AMBIENT TEMPERATURE (°C) 100 100 125 Figure 3. Oscillator Frequency Change versus Temperature V th(FB2) , COMPARATOR 2 THRESHOLD VOLTAGE (mV) Figure 2. Output Switch On-Off Time versus Oscillator Timing Capacitor 0 25 50 75 TA, AMBIENT TEMPERATURE (°C) 125 1300 Vth Max = 1275 mV VCC = 15 V 1280 1260 Vth Typ = 1250 mV 1240 Vth Min = 1225 mV 1220 125 1200 −55 −25 0 25 50 75 TA, AMBIENT TEMPERATURE (°C) 100 Figure 5. Feedback Comparator 2 Threshold Voltage versus Temperature 7.6 IZ = 25 mA 7.4 7.2 7.0 125 6.8 −55 Figure 6. Bootstrap Input Current Source versus Temperature −25 0 25 50 75 TA, AMBIENT TEMPERATURE (°C) 100 Figure 7. Bootstrap Input Zener Clamp Voltage versus Temperature http://onsemi.com 4 NCV33163 1.2 VCC −0.4 −0.8 Bootstrapped, Pin 16 = VCC + 5.0 V −1.2 −1.6 −2.0 Darlington Configuration Emitter Sourcing Current to Gnd Pins 7, 8, 10, 11 = VCC Pins 4, 5, 12, 13 = Gnd TA = 25°C, (Note 2) VCE (sat), SINK SATURATION (V) VCE (sat), SOURCE SATURATION (V) 0 Non−Bootstrapped, Pin 16 = VCC 0 0.8 2.4 1.6 IE, EMITTER CURRENT (A) 0.8 Grounded Emitter Configuration Collector Sinking Current From VCC Pins 7, 8 = VCC = 15 V Pins 4, 5, 12, 13, 14, 15 = Gnd TA = 25°C, (Note 2) Saturated Switch, RPin9 = 110 to VCC 0.6 0.4 0.2 0 3.2 Darlington, Pins 9, 10, 11 Connected 1.0 Gnd 0 0.8 Figure 8. Output Switch Source Saturation versus Emitter Current V OL (LVI) , OUTPUT SATURATION VOLTAGE (V) V E , EMITTER VOLTAGE (V) −0.4 IC = 10 A −0.8 IC = 10 mA −1.2 VCC = 15 V Pins 7, 8, 9, 10, 16 = VCC Pins 4, 6 = Gnd Pin 14 Driven Negative −1.6 −2.0 −55 −25 0 25 50 75 TA, AMBIENT TEMPERATURE (°C) 100 125 0.5 VCC=5 V TA=25°C 0.4 0.3 0.2 0.1 0 0 252 250 248 −25 8.0 1.6 VCC = 15 V 246 −55 2.0 4.0 6.0 Isink, OUTPUT SINK CURRENT (mA) Figure 11. Low Voltage Indicator Output Sink Saturation Voltage versus Sink Current IIB (Sense), INPUT BIAS CURRENT (µ A) V th (Ipk Sense) , THRESHOLD VOLTAGE (mV) Figure 10. Output Switch Negative Emitter Voltage versus Temperature 254 3.2 Figure 9. Output Switch Sink Saturation versus Collector Current 0 Gnd 1.6 2.4 IC, COLLECTOR CURRENT (A) 0 25 50 75 TA, AMBIENT TEMPERATURE (°C) 100 VCC = 15 V VIpk (Sense) = 15 V 1.4 1.2 1.0 0.8 0.6 −55 125 Figure 12. Current Limit Comparator Threshold Voltage versus Temperature −25 0 25 50 75 TA, AMBIENT TEMPERATURE (°C) 100 125 Figure 13. Current Limit Comparator Input Bias Current versus Temperature http://onsemi.com 5 NCV33163 7.2 I CC, SUPPLY CURRENT (mA) 6.0 4.0 Pins 7, 8, 16 = VCC Pins 4, 6, 14 = Gnd Remaining Pins Open TA = 25°C 0 0 10 20 30 VCC, SUPPLY VOLTAGE (V) 6.4 5.6 4.8 4.0 −55 40 3.0 1.8 Pin 16 Open JUNCTION−TO−AIR (° C/W) 2.2 Pin 16 = VCC 1.4 −25 0 25 50 75 100 80 5.0 RJA 4.0 2.0 oz Copper L 3.0 mm Graphs represent symmetrical layout 3.0 2.0 40 PD(max) for TA = 70°C 20 0 125 L 60 0 10 20 1.0 30 40 0 50 L, LENGTH OF COPPER (mm) Figure 16. Minimum Operating Supply Voltage versus Temperature Figure 17. P Suffix (DIP-16) Thermal Resistance and Maximum Power Dissipation versus P.C.B. Copper Length 100 2.8 PD(max) for TA = 50°C 90 80 2.4 ÎÎÎ ÎÎ ÎÎÎ ÎÎÎ ÎÎÎ ÎÎ ÎÎ Graph represents symmetrical layout 70 L 60 2.0 oz. Copper L 50 3.0 mm RJA 40 10 2.0 1.6 1.2 0.8 0.4 30 0 125 Printed circuit board heatsink example TA, AMBIENT TEMPERATURE (°C) JUNCTION−TO−AIR ( °C/W) 1.0 −55 100 ÎÎÎÎÎ ÎÎÎÎÎ ÎÎÎÎÎ 100 R θ JA, THERMAL RESISTANCE 2.6 0 25 50 75 TA, AMBIENT TEMPERATURE (°C) Figure 15. Standby Supply Current versus Temperature CT = 620 pF Pins 7,8 = VCC Pins 4, 14 = Gnd Pin 9 = 1.0 k to 15 V Pin 10 = 100 to 15 V R θ JA, THERMAL RESISTANCE V CC(min) , MINIMUM OPERATING SUPPLY VOLTAGE (V) Figure 14. Standby Supply Current versus Supply Voltage −25 20 30 40 0 50 L, LENGTH OF COPPER (mm) Figure 18. DW Suffix (SOP-16L) Thermal Resistance and Maximum Power Dissipation versus P.C.B. Copper Length http://onsemi.com 6 P D , MAXIMUM POWER DISSIPATION (W) 2.0 VCC = 15 V Pins 7, 8, 16 = VCC Pins 4, 6, 14 = Gnd Remaining Pins Open PD, MAXIMUM POWER DISSIPATION (W) I CC, SUPPLY CURRENT (mA) 8.0 NCV33163 Ipk Sense RSC 7 VCC Timing Capacitor CT RDT Shutdown 0.25 V + 8 6 Current Limit − + 9 10 + Switch Collector Oscillator 11 Q1 Q2 R Q S Latch 5 Thermal Gnd 4 Voltage Feedback 1 12 60 Gnd 13 + 3 14 45 k Voltage Feedback 2 LVI Output Driver Collector 2 + + + − 1 LVI Switch Emitter Feedback Comparator + + − 15 2.0 mA 1.25 V 15 k + 1.125 V + 7.0 V 16 Bootstrap Input + − (Bottom View) Figure 19. Representative Block Diagram 1 Comparator Output 0 1.25 V Timing Capacitor CT 0.55 V t 9t 1 Oscillator Output 0 On Output Switch Off Nominal Output Voltage Level Output Voltage Startup Quiescent Operation Figure 20. Typical Operating Waveforms http://onsemi.com 7 = Sink Only Positive True Logic NCV33163 INTRODUCTION of an external deadtime resistor (RDT) placed across CT. The resistor increases the discharge current which reduces the on-time of the output switch. A graph of the Output Switch On-Of f Time versus Oscillator Timing Capacitance for various values of RDT is shown in Figure 2. Note that the maximum output duty cycle, ton/ton + toff, remains constant for values of CT greater than 0.2 nF. The converter output can be inhibited by clamping CT to ground with an external NPN small-signal transistor. The NCV33163 series are monolithic power switching regulators optimized for dc-to-dc converter applications. The combination of features in this series enables the system designer to directly implement step-up, step-down, and voltage-inverting converters with a minimum number of external components. Potential applications include cost sensitive consumer products as well as equipment for the automotive, computer, and industrial markets. A Representative Block Diagram is shown in Figure 19. Feedback and Low Voltage Indicator Comparators Output voltage control is established by the Feedback comparator. The inverting input is internally biased at 1.25 V and is not pinned out. The converter output voltage is typically divided down with two external resistors and monitored by the high impedance noninverting input at Pin 2. The maximum input bias current is ±0.4 A, which can cause an output voltage error that is equal to the product of the input bias current and the upper divider resistance value. For applications that require 5.0 V, the converter output can be directly connected to the noninverting input at Pin 3. The high impedance input, Pin 2, must be grounded to prevent noise pickup. The internal resistor divider is set for a nominal voltage of 5.05 V. The additional 50 mV compensates for a 1.0% voltage drop in the cable and connector from the converter output to the load. The Feedback comparator’s output state is controlled by the highest voltage applied to either of the two noninverting inputs. The Low Voltage Indicator (LVI) comparator is designed for use as a reset controller in microprocessor-based systems. The inverting input is internally biased at 1.125 V, which sets the noninverting input thresholds to 90% of nominal. The LVI comparator has 15 mV of hysteresis to prevent erratic reset operation. The Open Collector output is capable of sinking in excess of 6.0 mA (see Figure 11). An external resistor (RLVI) and capacitor (CDLY) can be used to program a reset delay time (tDLY) by the formula shown below, where Vth(MPU) is the microprocessor reset input threshold. Refer to Figure 21. OPERATING DESCRIPTION The NCV33163 operates as a fixed on-time, variable off-time voltage mode ripple regulator. In general, this mode of operation is somewhat analogous to a capacitor charge pump and does not require dominant pole loop compensation for converter stability. The Typical Operating Waveforms are shown in Figure 20. The output voltage waveform shown is for a step-down converter with the ripple and phasing exaggerated for clarity. During initial converter startup, the feedback comparator senses that the output voltage level is below nominal. This causes the output switch to turn on and off at a frequency and duty cycle controlled by the oscillator, thus pumping up the output filter capacitor. When the output voltage level reaches nominal, the feedback comparator sets the latch, immediately terminating switch conduction. The feedback comparator will inhibit the switch until the load current causes the output voltage to fall below nominal. Under these conditions, output switch conduction can be inhibited for a partial oscillator cycle, a partial cycle plus a complete cycle, multiple cycles, or a partial cycle plus multiple cycles. Oscillator The oscillator frequency and on-time of the output switch are programmed by the value selected for timing capacitor CT. Capacitor CT is charged and discharged by a 9 to 1 ratio internal current source and sink, generating a negative going sawtooth waveform at Pin 6. As CT charges, an internal pulse is generated at the oscillator output. This pulse is connected to the NOR gate center input, preventing output switch conduction, and to the AND gate upper input, allowing the latch to be reset if the comparator output is low. Thus, the output switch is always disabled during ramp-up and can be enabled by the comparator output only at the start of ramp-down. The oscillator peak and valley thresholds are 1.25 V and 0.55 V, respectively, with a charge current of 225A and a discharge current of 25 A, yielding a maximum on-time duty cycle of 90%. A reduction of the maximum duty cycle may be required for specific converter configurations. This can be accomplished with the addition tDLY = RLVI CDLY In 1 Vth(MPU) 1 Vout Current Limit Comparator, Latch and Thermal Shutdown With a voltage mode ripple converter operating under normal conditions, output switch conduction is initiated by the oscillator and terminated by the Voltage Feedback comparator. Abnormal operating conditions occur when the converter output is overloaded or when feedback voltage sensing is lost. Under these conditions, the Current Limit comparator will protect the Output Switch. http://onsemi.com 8 NCV33163 additional device heating and reduced conversion efficiency. Figure 10 shows that by clamping the emitter to 0.5 V, the collector current will be in the range 10 A over temperature. A 1N5822 or equivalent Schottky barrier rectifier is recommended to fulfill these requirements. A bootstrap input is provided to reduce the output switch saturation voltage in step-down and voltage-inverting converter applications. This input is connected through a series resistor and capacitor to the switch emitter and is used to raise the internal 2.0 mA bias current source above VCC. An internal zener limits the bootstrap input voltage to VCC +7.0 V. The capacitor’s equivalent series resistance must limit the zener current to less than 100 mA. An additional series resistor may be required when using tantalum or other low ESR capacitors. The equation below is used to calculate a minimum value bootstrap capacitor based on a minimum zener voltage and an upper limit current source. The switch current is converted to a voltage by inserting a fractional ohm resistor, RSC, in series with VCC and output switch transistor Q2. The voltage drop across RSC is monitored by the Current Sense comparator. If the voltage drop exceeds 250 mV with respect to VCC, the comparator will set the latch and terminate output switch conduction on a cycle-by-cycle basis. This Comparator/Latch configuration ensures that the Output Switch has only a single on-time during a given oscillator cycle. The calculation for a value of RSC is: RSC 0.25 V Ipk (Switch) Figures 12 and 13 show that the Current Sense comparator threshold is tightly controlled over temperature and has a typical input bias current of 1.0 A. The propagation delay from the comparator input to the Output Switch is typically 200 ns. The parasitic inductance associated with RSC and the circuit layout should be minimized. This will prevent unwanted voltage spikes that may falsely trip the Current Limit comparator. Internal thermal shutdown circuitry is provided to protect the IC in the event that the maximum junction temperature is exceeded. When activated, typically at 170°C, the Latch is forced into the “Set” state, disabling the Output Switch. This feature is provided to prevent catastrophic failures from accidental device overheating. It is not intended to be used as a replacement for proper heatsinking. CB(min) I t 4.0 mA ton 0.001 ton V 4.0 V Parametric operation of the NCV33163 is guaranteed over a supply voltage range of 2.5 V to 40 V. When operating below 3.0 V, the Bootstrap Input should be connected to VCC. Figure 16 shows that functional operation down to 1.7 V at room temperature is possible. Package The NCV33163 is contained in a heat-sinkable 16-lead plastic dual-in-line package in which the die is mounted on a special heat tab copper alloy lead frame. This tab consists of the four center ground pins that are specifically designed to improve thermal conduction from the die to the circuit board. Figures 17 and 18 show a simple and effective method of utilizing the printed circuit board medium as a heat dissipater by soldering these pins to an adequate area of copper foil. This permits the use of standard layout and mounting practices while having the ability to halve the junction-to-air thermal resistance. These examples are for a symmetrical layout on a single-sided board with two ounce per square foot of copper. Driver and Output Switch To aid in system design flexibility and conversion efficiency, the driver current source and collector, and output switch collector and emitter are pinned out separately. This allows the designer the option of driving the output switch into saturation with a selected force gain or driving it near saturation when connected as a Darlington. The output switch is designed to switch a maximum of 60 V collector to emitter, with up to 2.5 A peak collector current. The minimum value for RSC is: RSC(min) 0.25 V 0.100 2.5 A When configured for step-down or voltage-inverting applications, as in Figures 21 and 25, the inductor will forward bias the output rectifier when the switch turns off. Rectifiers with a high forward voltage drop or long turn-on delay time should not be used. If the emitter is allowed to go sufficiently negative, collector current will flow, causing APPLICATIONS The following converter applications show the simplicity and flexibility of this circuit architecture. Three main converter topologies are demonstrated with actual test data shown below each of the circuit diagrams. http://onsemi.com 9 NCV33163 0.25 V + 8 RSC Vin 12 V 0.075 9 10 7 + Cin 330 Current Limit − + + 6 CT 680 pF Oscillator 11 Q1 Thermal 4 Q2 R Q S Latch 5 12 60 13 + 14 3 45 k 2 RLVI 10 k Low Voltage Indicator Output 1 CDLY + + − + LVI Feedback Comparator 1N5822 0.02 2.0 mA 1.25 V 15 k + 1.125 V + + − 15 16 + 7.0 V CB L 2200 (Bottom View) Test RB Condition 180 H Coilcraft LO451−A Vout + 5.05 V/3.0 A CO Results Line Regulation Vin = 8.0 V to 24 V, IO = 3.0 A 6.0 mV = ± 0.06% Load Regulation Vin = 12 V, IO = 0.6 A to 3.0 A 2.0 mV = ± 0.02% Output Ripple Vin = 12 V, IO = 3.0 A 36 mVpp Short Circuit Current Vin = 12 V, RL = 0.1 3.3 A Efficiency, Without Bootstrap Vin = 12 V, IO = 3.0 A 76.7% Efficiency, With Bootstrap Vin = 12 V, IO = 3.0 A 81.2% Figure 21. Step-Down Converter 8 7 + 8 10 7 9 Q3 10 + 6 11 Q1 Q2 5 4 9 + 12 5 13 4 11 Q1 Q2 12 13 + 3 14 15 2 15 16 1 3 14 2 1 6 Q3 + 16 + (Bottom View) (Bottom View) Figure 22A. External NPN Switch Figure 22B. External PNP Saturated Switch Figure 22. External Current Boost Connections for Ipk (Switch) Greater Than 2.5 A http://onsemi.com 10 NCV33163 0.25 V + 8 RSC 0.075 Vin 12 V Cin + Current Limit − + L 9 7 180 H Coilcraft LO451−A 10 + 330 6 Oscillator CT 680 pF 11 Q1 Thermal 4 Q2 R Q S Latch 5 12 60 13 + 1N5822 3 14 45 k 2 Low Voltage Indicator Output 1 RLVI 1.0 k R1 2.2 k + + − + LVI + + − Feedback Comparator 1.25 V 15 k + 1.125 V R2 47 k 15 2.0 mA 16 7.0 V + Vout +C O (Bottom View) 28 V/600 mA 330 Test Condition Results Line Regulation Vin = 9.0 V to 16 V, IO = 0.6 A 30 mV = ± 0.05% Load Regulation Vin = 12 V, IO = 0.1 A to 0.6 A 50 mV = ± 0.09% Output Ripple Vin = 12 V, IO = 0.6 A 140 mVpp Efficiency Vin = 12 V, IO = 0.6 A 88.1% Figure 23. Step-Up Converter 8 7 + 6 4 Q2 + 8 10 7 11 Q1 5 9 5 13 4 14 2 1 10 + 6 12 3 9 11 Q1 Q2 12 13 + 3 14 15 2 15 16 1 Q3 Q3 16 + + (Bottom View) (Bottom View) Figure 24A. External NPN Switch Figure 24B. External PNP Saturated Switch Figure 24. External Current Boost Connections for Ipk (Switch) Greater Than 2.5 A http://onsemi.com 11 NCV33163 0.25 V + 8 RSC Vin 12 V 0.075 Cin 330 Current Limit − + 9 7 + 10 + 6 CT 470 pF Oscillator 11 Q1 Q2 R Q S Latch 5 Thermal 4 12 60 13 + Coilcraft LO451−A 3 14 L 180 H 45 k 2 + 1 LVI R2 8.2 k + + − Feedback Comparator 1.25 V 15 k + 1.125 V + + − R1 953 15 0.02 2.0 mA 16 + 7.0 V 1N5822 2200 (Bottom View) Test RB CB Vout −12 V/1.0 A + CO Condition Results Line Regulation Vin = 9.0 V to 16 V, IO = 1.0 A 5.0 mV = ± 0.02% Load Regulation Vin = 12 V, IO = 0.6 A to 1.0 A 2.0 mV = ± 0.01% Output Ripple Vin = 12 V, IO = 1.0 A 130 mVpp Short Circuit Current Vin = 12 V, RL = 0.1 3.2 A Efficiency, Without Bootstrap Vin = 12 V, IO = 1.0 A 73.1% Efficiency, With Bootstrap Vin = 12 V, IO = 1.0 A 77.5% Figure 25. Voltage-Inverting Converter 8 7 + 6 Q1 Q2 9 8 10 7 11 6 9 10 + 11 Q1 Q2 12 5 13 4 3 14 3 14 2 15 2 15 5 4 + Q3 16 1 12 13 + 16 1 + Q3 + (Bottom View) (Bottom View) Figure 26A. External NPN Switch Figure 26B. External PNP Saturated Switch Figure 26. External Current Boost Connections for Ipk (Switch) Greater Than 2.5 A http://onsemi.com 12 NCV33163 Calculation Step-Down Step-Up Voltage-Inverting ton (Notestoff 1, 2, 3) V out V V out V – V F in V – V sat in |V out| V F V V sat V out in ton ƒ t on t off t on 1 t off CT 32.143 · 10 –6 ƒ IL(avg) Iout Ipk (Switch) ƒ I L 2 V in t on V IL V Vout R2 ref R1 I L 2 (ESR)2 1 V R2 ref R1 t on 1 t off t on 1 t off IL(avg) t on V t on I out C t on t off I L 2 0.25 Ipk (Switch) L I out I V sat in F V sat in 32.143 · 10 –6 ƒ t on 1 t off 2 Vripple(pp) ƒ 0.25 Ipk (Switch) V sat V out I L 8 ƒ1CO IL(avg) 0.25 Ipk (Switch) L t on 1 t off 32.143 · 10 –6 ƒ I out IL(avg) RSC t on t off V in C O V L R2 ref t on t on I out 1 V sat I R1 O 1 The following Converter Characteristics must be chosen: Nominal operating input voltage. Desired output voltage. Desired output current. Desired peak-to-peak inductor ripple current. For maximum output current it is suggested that IL be chosen to be less than 10% of the average inductor current IL(avg). This will help prevent Ipk (Switch) from reaching the current limit threshold set by RSC. If the design goal is to use a minimum inductance value, let IL = 2(IL(avg)). This will proportionally reduce converter output current capability. - Maximum output switch frequency. Vripple(pp) - Desired peak-to-peak output ripple voltage. For best performance the ripple voltage should be kept to a low value since it will directly affect line and load regulation. Capacitor CO should be a low equivalent series resistance (ESR) electrolytic designed for switching regulator applications. Vin Vout Iout IL - NOTES: NOTES: NOTES: NOTES: 1. 2. 3. 3. Vsat - Saturation voltage of the output switch, refer to Figures 8 and 9. VF - Output rectifier forward voltage drop. Typical value for 1N5822 Schottky barrier rectifier is 0.5 V. The calculated ton/toff must not exceed the minimum guaranteed oscillator charge to discharge ratio of 8, at the minimum operating input voltage. Figure 27. Design Equations http://onsemi.com 13 NCV33163 PACKAGE DIMENSIONS PDIP-16 P SUFFIX CASE 648C-04 ISSUE D A K C N F T E G 16X SEATING PLANE D 0.005 (0.13) M T A http://onsemi.com 14 0.005 (0.13) J 8 16X 1 L 9 B 16 M M T B B A NOTES: 1. DIMENSIONING AND TOLERANCING PER ASME Y14.5M, 1994. 2. CONTROLLING DIMENSION: INCH. 3. DIMENSION L TO CENTER OF LEADS WHEN FORMED PARALLEL. 4. DIMENSION B DOES NOT INCLUDE MOLD FLASH. DIM A B C D E F G J K L M N INCHES MIN MAX 0.744 0.783 0.240 0.260 0.145 0.185 0.015 0.021 0.050 BSC 0.040 0.70 0.100 BSC 0.008 0.015 0.115 0.135 0.300 BSC 0 10 0.015 0.040 MILLIMETERS MIN MAX 18.90 19.90 6.10 6.60 3.69 4.69 0.38 0.53 1.27 BSC 1.02 1.78 2.54 BSC 0.20 0.38 2.92 3.43 7.62 BSC 0 10 0.39 1.01 NCV33163 PACKAGE DIMENSIONS SO-16W DW SUFFIX CASE 751G-03 ISSUE B A D 9 1 8 NOTES: 1. DIMENSIONS ARE IN MILLIMETERS. 2. INTERPRET DIMENSIONS AND TOLERANCES PER ASME Y14.5M, 1994. 3. DIMENSIONS D AND E DO NOT INLCUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 PER SIDE. 5. DIMENSION B DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.13 TOTAL IN EXCESS OF THE B DIMENSION AT MAXIMUM MATERIAL CONDITION. 16X M T A S B h X 45 S 14X e L A 0.25 B B A1 H E 0.25 8X M B M 16 SEATING PLANE T C http://onsemi.com 15 DIM A A1 B C D E e H h L MILLIMETERS MIN MAX 2.35 2.65 0.10 0.25 0.35 0.49 0.23 0.32 10.15 10.45 7.40 7.60 1.27 BSC 10.05 10.55 0.25 0.75 0.50 0.90 0 7 NCV33163 ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. 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