Analogic AAT1151IKS-3.3-T1 850khz 700ma synchronous buck dc/dc converter Datasheet

AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
General Description
Features
The AAT1151 SwitchReg™ is a member of
AnalogicTech's Total Power Management IC™
(TPMIC™) product family. The step-down switching
converter is ideal for applications where high efficiency is required over the full range of output load
conditions. The 2.7V to 5.5V input voltage range
makes the AAT1151 ideal for single-cell lithiumion/polymer battery applications. Capable of more
than 700mA with internal MOSFETs, the currentmode controlled IC provides high efficiency using
synchronous rectification. Fully integrated compensation simplifies system design and lowers external
parts count.
•
•
•
•
•
•
•
•
•
•
•
•
•
The device operates at a fixed 850kHz switching frequency and enters PFM mode for light load current
to maintain high efficiency across all load conditions.
The AAT1151 is available in MSOP-8 and QFN33-16
packages and is rated over the -40°C to +85°C temperature range.
•
•
•
•
•
SwitchReg™
VIN Range: 2.7V to 5.5V
Up to 95% Efficiency
High Initial Accuracy ±1%
110mΩ RDS(ON) Internal Switches
<1µA Shutdown Current
850kHz Switching Frequency
Fixed VOUT or Adjustable VOUT ≥1.0V
Integrated Power Switches
Synchronous Rectification
Current Mode Operation
Internal Compensation
Stable with Ceramic Capacitors
PWM and PFM for Optimum Efficiency for All
Load Conditions
Internal Soft Start
Over-Temperature Protection
Current Limit Protection
MSOP-8 and QFN33-16 Packages
-40°C to +85°C Temperature Range
Applications
•
•
•
•
•
•
•
Cellular Phones
Digital Cameras
MP3 Players
Notebook Computers
PDAs
USB-Powered Equipment
Wireless Notebook Adapters
Typical Application
INPUT
VP
10µF
FB
AAT1151
3.0µH
LX
ENABLE
100Ω
VCC
OUTPUT
SGND
PGND
2x 22µF
0.1µF
1151.2005.11.1.4
1
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Pin Descriptions
Pin #
MSOP-8
QFN33-16
Symbol
Function
1
4
FB
Feedback input pin. This pin is connected to the converter output. It
is used to set the output of the converter to regulate to the desired
value via an internal resistive divider. For an adjustable output, an
external resistive divider is connected to this pin on the 1V model.
2
5, 6
SGND
Signal ground. Connect the return of all small signal components to
this pin. (See board layout rules.)
3
7
EN
Enable input pin. A logic high enables the converter; a logic low
forces the AAT1151 into shutdown mode reducing the supply current
to less than 1µA. The pin should not be left floating.
4
9
VCC
Bias supply. Supplies power for the internal circuitry. Connect to input
power via low pass filter with decoupling to SGND.
5
10, 11, 12
VP
Input supply voltage for the converter power stage. Must be closely
decoupled to PGND.
6, 7
13, 14, 15
LX
Connect inductor to these pins. Switching node internally connected
to the drain of both high- and low-side MOSFETs.
8
1, 2, 3
PGND
8, 16
NC
Main power ground return pin. Connect to the output and input
capacitor return. (See board layout rules.)
Not internally connected.
EP
Exposed paddle (bottom); connect to PGND directly beneath package.
Pin Configuration
MSOP-8
(Top view)
QFN33-16
(Top view)
LX
LX
LX
NC
12
2
11
3
10
4
9
VP
VP
VP
VCC
8
VP
1
7
5
13
LX
14
VCC
4
6
PGND
PGND
PGND
FB
6
3
LX
5
EN
7
15
2
PGND
16
SGND
8
2
1
1
FB
NC
EN
SGND
SGND
2
1151.2005.11.1.4
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Absolute Maximum Ratings1
Symbol
VCC, VP
VLX
VFB
VEN
TJ
VESD
Description
VCC, VP to GND
LX to GND
FB to GND
EN to GND
Operating Junction Temperature Range
ESD Rating2 - HBM
Value
Units
6
-0.3 to VP+0.3
-0.3 to VCC+0.3
-0.3 to 6
-40 to 150
3000
V
V
V
V
°C
V
Value
Units
150
667
50
2.0
°C/W
mW
°C/W
W
Value
Units
-40 to 85
°C
Thermal Characteristics3
Symbol
ΘJA
PD
ΘJA
PD
Description
Thermal Resistance (MSOP-8)
Maximum Power Dissipation (MSOP-8) (TA = 25°C)4
Thermal Resistance (QFN33-16)
Maximum Power Dissipation (QFN33-16) (TA = 25°C)5
Recommended Operating Conditions
Symbol
T
Description
Ambient Temperature Range
1. Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. Functional operation at conditions other than the operating conditions specified is not implied. Only one Absolute Maximum Rating should be applied at any one time.
2. Human body model is a 100pF capacitor discharged through a 1.5kΩ resistor into each pin.
3. Mounted on a demo board.
4. Derate 6.7mW/°C above 25°C.
5. Derate 20mW/°C above 25°C.
1151.2005.11.1.4
3
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Electrical Characteristics1
VIN = VCC = VP = 5V, TA = -40°C to 85°C, unless otherwise noted. Typical values are at TA = 25°C.
Symbol
Description
VIN
VOUT
Input Voltage Range
Output Voltage Tolerance
VUVLO
Under-Voltage Lockout
VUVLO(HYS)
IIL
IIH
IQ
ISHDN
ILIM
RDS(ON)H
RDS(ON)L
η
∆VOUT (VOUT*∆VIN)
∆VOUT/VOUT
FOSC
VEN(L)
VEN(H)
TSD
THYS
Under-Voltage Lockout Hysteresis
Input Low Current
Input High Current
Quiescent Supply Current
Shutdown Current
Current Limit
High Side Switch On Resistance
Low Side Switch On Resistance
Efficiency
Load Regulation
Line Regulation
Oscillator Frequency
Enable Threshold Low
Enable Threshold High
Over-Temperature Shutdown
Threshold
Over-Temperature Shutdown
Hysteresis
Conditions
VIN = VOUT + 0.2 to 5.5V,
IOUT = 0 to 700mA
VIN Rising
VIN Falling
Min
Typ
2.7
-3.0
Max
Units
5.5
+3.0
V
%
2.5
1.2
250
VIN = VFB = 5.5V
VIN = VFB = 0 V
No Load, VFB = 0 V, VIN = 4.2V
TA = 25°C
VEN = 0 V, VIN = 5.5V
TA = 25°C
TA = 25°C
TA = 25°C
IOUT = 300mA, VIN = 3.5V
VIN = 4.2V, ILOAD = 0 to 700mA
VIN = 2.7V to 5.5V
TA = 25°C
210
1.0
1.0
300
1.0
mV
µA
µA
µA
140
µA
A
mΩ
mΩ
%
%
%/V
KHz
V
V
°C
15
°C
1.2
600
V
110
100
92
±0.9
±0.1
850
1.4
150
150
1200
0.6
1. The AAT1151 is guaranteed to meet performance specifications over the -40°C to +85°C operating range and is assured by design,
characterization, and correlation with statistical process controls.
4
1151.2005.11.1.4
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Typical Characteristics
No Load Supply Current vs. Input Voltage
Frequency vs. Input Voltage
890
T = 85°C
250
Frequency (kHz)
Supply Current (µ
µA)
300
200
150
T = -40°C
T = 25°C
100
50
880
870
860
850
0
2.5
3
3.5
4
4.5
5
2.5
5.5
3
3.5
4
4.5
5
5.5
Input Voltage (V)
Input Voltage (V)
Output Voltage vs. Temperature
Load and Line Regulation
3.0
1.794
2.0
1.79
VOUT Error (%)
Output Voltage (V)
1.792
1.788
1.786
1.784
1.782
VIN = 4.2V
VIN = 3.6V
1.0
0.0
VIN = 2.7V
-1.0
-2.0
1.78
-40
-20
0
20
40
60
80
-3.0
100
1
10
Temperature (°°C)
100
1000
Load Current (mA)
Switching Frequency vs. Temperature
AAT1151 Efficiency
(VOUT = 2.5V; L = 4.2µ
µH)
1200
100
95
Efficiency (%)
Frequency (kHz)
1000
800
600
400
200
90
85
80
75
70
65
60
55
0
-40
-20
0
20
40
Temperature (°°C)
1151.2005.11.1.4
60
80
100
50
1
10
100
1000
10000
Output Current (mA)
5
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Typical Characteristics
Line Transient Response 1.8V, 50mA
Circuit of Figure 1
1.4
4.4
120
10
1.2
4.2
100
1
-10
0.8
-20
0.6
-30
0.4
-40
0.2
-50
0
-60
-0.2
4
80
3.8
60
3.6
40
3.4
20
3.2
0
3
3.5
4.4
120
10
3
4.2
100
2.5
-10
2
-20
1.5
-30
1
-40
0.5
-50
0
-60
-0.5
4
80
3.8
60
3.6
40
3.4
20
3.2
0
3
-20
2.8
-40
Time (20µ
µs/div)
Load Transient Response 50mA to 0.7A
VIN = 3.6V − Circuit of Figure 1
Soft Start 1.8V, 0.7A, VIN = 3.6V
Circuit of Figure 1
3.5
20
3
3
3
2
2.5
1
2
0
1.5
2.5
-20
2
-40
1.5
-60
1
-80
0.5
-100
0
-120
-0.5
Time (200µs/div)
Enable (top)
Output (middle) (V)
4
-1
1
-2
0.5
-3
0
-4
-0.5
Inductor Current
(bottom) (A)
3.5
Inductor Current
(bottom) (A)
40
0
Output Voltage
(bottom) (mV)
0
Input Voltage
(top) (V)
20
Inductor Current
(bottom) (A)
Output Voltage
(AC coupled) (top) (mV)
Line Transient Response 1.8V, 0.7A
Circuit of Figure 1
Time (2µ
µs/div)
Output Voltage (top) (mV)
(AC coupled)
-40
Time (20µ
µs/div)
Output Ripple 1.8V, 0.7A, VIN = 3.6V
Circuit of Figure 1
6
-20
2.8
Time (2µ
µs/div)
Output Voltage
(bottom) (mV)
0
Input Voltage
(top) (V)
20
Inductor Current
(bottom) (A)
Output Voltage
(AC coupled) (top) (mV)
Output Ripple 1.8V, 50mA, VIN = 3.6V
Circuit of Figure 1
Time (200µ
µs/div)
1151.2005.11.1.4
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Typical Characteristics
Output Ripple
Circuit of Figure 1
20
Ripple (mV)
15
VIN = 2.7V
VIN = 3.6V
10
5
VIN = 4.2V
0
1
10
100
1000
Output Current (mA)
1151.2005.11.1.4
7
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Functional Block Diagram
VCC
VP = 2.7V- 5.5V
1.0V REF
FB
OP. AMP
CMP
DH
LOGIC
1MΩ
LX
DL
Temp.
Sensing
OSC
SGND
Operation
Control Loop
The AAT1151 is a peak current mode buck converter. The inner, wide bandwidth loop controls the
peak current of the output inductor. The output
inductor current is sensed through the P-channel
MOSFET (high side) and is also used for short-circuit and overload protection. A fixed slope compensation signal is added to the sensed current to
maintain stability. The loop appears as a voltage
programmed current source in parallel with the output capacitor.
The voltage error amplifier output programs the current loop for the necessary inductor current to force
a constant output voltage for all load and line conditions. The voltage feedback resistive divider is internal, dividing the output voltage to the error amplifier
reference voltage of 1.0V. The voltage error amplifier does not have the large DC gain typical of most
error amplifiers. This eliminates the need for external compensation components, while still providing
sufficient DC loop gain for load regulation. The voltage loop crossover frequency and phase margin are
set by the output capacitor value only.
8
EN
PGND
PFM/PWM Operation
Light load efficiency is maintained by way of Pulse
Frequency Modulation (PFM) control. The AAT1151
PFM control forces the peak inductor current to a
minimum level regardless of load demand. At medium to high load demand, this has no effect on circuit
operation and normal PWM controls take over. PFM
reduces the switching frequency at light loads, thus
reducing the associated switching losses.
Soft Start/Enable
Soft start increases the inductor current limit point in
discrete steps when the input voltage or enable
input is applied. It limits the current surge seen at
the input and eliminates output voltage overshoot.
When pulled low, the enable input forces the
AAT1151 into a low-power, non-switching state. The
total input current during shutdown is less than 1µA.
Power and Signal Source
Separate small signal ground and power supply pins
isolate the internal control circuitry from the noise
associated with the output MOSFET switching. The
low pass filter R1 and C2 in schematic Figure 1 filters the noise associated with the power switching.
1151.2005.11.1.4
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Efficiency vs. Load Current
U1
AAT1151-QFN
R1
100
C1
10µF
R2
100k
C2
0.1µF
R6
100k
(VOUT = 1.8V)
12
Vp
Out
4
11
Vp
LX
15
10
Vp
LX
14
9
Vcc
LX
13
7
EN
n/c
8
6
gnd
Pgnd
3
16
n/c
Pgnd
2
5
gnd
Pgnd
1
1.8V
100
2.7V
90
L1
3.3µH
Efficiency (%)
2.7V-4.2V
C3, C4
2x22µF
80
3.6V
4.2V
70
60
C1 Murata 10µF 6.3V X5R GRM42-6X5R106K6.3
C3-C4 MuRata 22µF 6.3V GRM21BR60J226ME39L X5R 0805
L1 Sumida CDRH3D16-4R7NC or CDRH3D16-3R3NC
50
1
10
100
1000
Load Current (mA)
Figure 1: AAT1151 Evaluation Board.
Current Limit and Over-Temperature
Protection
For overload conditions, the peak input current is
limited. As load impedance decreases and the
output voltage falls closer to zero, more power is
dissipated internally, raising the device temperature. Thermal protection completely disables
switching when internal dissipation becomes
excessive, protecting the device from damage.
The junction over-temperature threshold is 140°C
with 10°C of hysteresis.
peak and average current ratings yet result in excessive losses due to a high DCR. Always consider the
losses associated with the DCR and its effect on the
total converter efficiency when selecting an inductor.
For a 1.0 Amp load and the ripple set to 40% at the
maximum input voltage, the maximum peak-topeak ripple current is 280mA. The inductance
value required is 2.84µH.
VOUT
VOUT⎞
⎛
L= I ·k·F · 1- V
⎝
O
IN ⎠
Inductor
The output inductor is selected to limit the ripple current to some predetermined value, typically 20% to
40% of the full load current at the maximum input
voltage. Manufacturer's specifications list both the
inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. The inductor
should not show any appreciable saturation under
normal load conditions. During overload and transient conditions, the average current in the inductor
can meet or exceed the current limit point of the
AAT1151. These conditions can tolerate greater saturation in the inductor without degradation in converter performance. Some inductors may meet the
1151.2005.11.1.4
=
1.5V
⎞
⎛
⎞ ⎛
· 1 - 1.5V
4.2V ⎠
⎝ 1A · 0.4 · 850kHz ⎠ ⎝
= 2.84µH
The factor "k" is the fraction of full load selected for
the ripple current at the maximum input voltage. For
ripple current at 40% of the full load current, the
peak current will be 120% of full load. Selecting a
standard value of 3.0µH gives 38% ripple current. A
3.0µH inductor selected from the Sumida
CDRH5D28 series has a 24mΩ DCR and a 2.4A DC
current rating. At full load, the inductor DC loss is
24mW, which amounts to a 1.6% loss in efficiency.
9
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Input Capacitor
The primary function of the input capacitor is to provide a low impedance loop for the edges of pulsed
current drawn by the AAT1151. A low ESR/ESL
ceramic capacitor is ideal for this function. To minimize stray inductance, the capacitor should be
placed as close as possible to the IC. This keeps the
high frequency content of the input current localized,
minimizing radiated and conducted EMI while facilitating optimum performance of the AAT1151.
Ceramic X5R or X7R capacitors are ideal for this
function. The size required will vary depending on the
load, output voltage, and input voltage source impedance characteristics. A typical value is around 10µF.
The input capacitor RMS current varies with the input
voltage and the output voltage. The equation for the
RMS current in the input capacitor is:
IRMS = IO ·
VO ⎛
V ⎞
· 1- O
VIN ⎝
VIN ⎠
The input capacitor RMS ripple current reaches a
maximum when VIN is two times the output voltage
where it is approximately one half of the load current. Losses associated with the input ceramic
capacitor are typically minimal and are not an issue.
Proper placement of the input capacitor can be seen
in the reference design layout in Figures 2 and 4.
IRMS =
10
VOUT · (VIN - VOUT)
L · F · VIN
2· 3
·
For a ceramic capacitor, the ESR is so low that dissipation due to the RMS current of the capacitor is
not a concern. Tantalum capacitors with sufficiently
low ESR to meet output voltage ripple requirements also have an RMS current rating well
beyond that actually seen in this application.
Layout
Figures 2 through 5 display the suggested PCB
layout for the AAT1151. The following guidelines
should be used to help ensure a proper layout.
•
•
•
•
Output Capacitor
Since there are no external compensation components, the output capacitor has a strong effect on
loop stability. Lager output capacitance will reduce
the crossover frequency with greater phase margin. For the 1.5V 1A design using the 4.1µH inductor, two 22µF capacitors provide a stable output. In
addition to assisting stability, the output capacitor
limits the output ripple and provides holdup during
large load transitions. The output capacitor RMS
ripple current is given by:
1
•
The input capacitor (C1) should connect as
closely as possible to VPOWER (Pin 5) and
PGND (Pin 8).
C2 and L1 should be connected as closely as
possible. The connection L1 to the LX node
should be as short as possible.
The feedback trace (Pin 1) should be separate from any power trace and connect as
closely as possible to the load point. Sensing
along a high-current load trace will degrade
DC load regulation.
The resistance of the trace from the load
return to the PGND (Pin 8) should be kept to
a minimum. This will help to minimize any
error in DC regulation due to differences in
the potential of the internal signal ground
and the power ground.
Low pass filter R1 and C3 provide a cleaner
bias source for the AAT1151 active circuitry.
C3 should be placed as closely as possible
to SGND (Pin 2) and VCC (Pin 4). See
Figures 2 and 7.
1151.2005.11.1.4
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Figure 2: MSOP Evaluation
Board Top Layer.
Figure 3: MSOP Evaluation
Board Bottom Layer.
Figure 4: QFN Evaluation Board
Top Side.
Figure 5: QFN Evaluation Board
Bottom Side.
45
R4=10kΩ
40
2.7V-5.5V
AAT1151-1.0
5
35
R1 100
R3 (kΩ)
30
R2
25
20
100k
C1
10µF
15
C3
0.1 µF
4
3
2
Vp
FB
Vcc
LX
EN
LX
gnd Pgnd
1
Vo+ 1.25V 0.7A
R3
2.55k 1%
7
6
8
L1
3.3µH
C2, C4
2x 22µF
R4
10kΩ 1%
10
5
0
1
1.5
2
2.5
3
3.5
4
4.5
5
5.5
VC1 Murata 10µF 6.3V X5R GRM42-6X5R106K6.3
C2, C4 MuRata 22µF 6.3V GRM21BR60J226ME39L X5R 0805
L1 Sumida CDRH3D16-3R3 NC
Output Voltage (V)
Figure 6: R3 vs. VOUT for Adjustable Output
Using the AAT1151-1.0V.
1151.2005.11.1.4
Figure 7: Adjustable Output Schematic.
11
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Thermal Calculations
There are two types of losses associated with the
AAT1151 output switching MOSFET: switching losses and conduction losses. Conduction losses are
associated with the RDS(ON) characteristics of the
output switching device. At the full load condition,
assuming continuous conduction mode (CCM), a
simplified form of the total losses is given by:
P=
IO2 · (RDSON(HS) · VO + RDSON(LS) · (VIN · VO))
VIN
+ (t SW · F · I O · VIN + IQ) · VIN
Once the total losses have been determined, the
junction temperature can be derived from the θJA
for the MSOP-8 package.
TJ = P · θJA + TAMB
Adjustable Output
For applications requiring an output other than the
fixed available, the 1V version can be programmed
externally. Resistors R3 and R4 of Figure 7 force
the output to regulate higher than 1 volt. R4 should
be 100 times less than the 1MΩ internal resistance
of the FB pin (recommended 10kΩ). Once R4 is
selected, R3 can be calculated. For a 1.25 volt output with R4 set to 10.0kΩ, R3 is 2.55kΩ.
where Iq is the AAT1151 quiescent current.
R3 = (VO - 1) · R4 = 0.25 · 10kΩ = 2.55kΩ
12
1151.2005.11.1.4
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Design Example
Specifications
IOUT
0.7A
IRIPPLE
40% of Full Load at Max VIN
VOUT
1.5V
VIN
2.7V to 4.2V (3.6V nominal)
FS
850kHz
TAMB
85°C
Maximum Input Capacitor Ripple:
IRMS = I O ·
VO ⎛
V ⎞
· 1 - O = 0.35Arms, VIN = 2 × VO
VIN ⎝ VIN ⎠
P = esr · IRMS2 = 5mΩ · 0.352 A = 0.6mW
Inductor Selection:
L=
⎛ V ⎞
VOUT
1.5V
⎛ 1.5V ⎞
⋅ 1 - OUT =
⋅1= 4.05µH
IO ⋅ k ⋅ F ⎝
VIN ⎠ 0.7A ⋅ 0.4 ⋅ 850kHz ⎝ 4.2V ⎠
Select Sumida inductor CDRH3D16 3.3µH 63mΩ 1.8mm height.
∆I =
⎛ 1.5V⎞
VO ⎛
V ⎞
1.5V
⋅ 1- O =
⋅ 1= 340mA
L ⋅ F ⎝ VIN ⎠ 3.3µH ⋅ 850kHz ⎝ 4.2V⎠
IPK = IOUT +
∆I
= 0.7A + 0.17A = 0.87A
2
P = IO2 ⋅ DCR = (0.7)2 ⋅ 63mΩ = 31mW
Output Capacitor Ripple Current:
IRMS =
VOUT · (VIN - VOUT)
1
1.5V · (4.2V - 1.5V)
·
= 99mArms
=
L · F · VIN
2 · 3 3.3µH · 850kHz · 4.2V
2· 3
1
·
Pesr = esr · IRMS2 = 5mΩ · 992 mA = 50µW
1151.2005.11.1.4
13
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
AAT1151 Dissipation:
PTOTAL =
=
IO2 · (RDSON(H) · VO + RDSON(L) · (VIN -VO))
VIN
+ (tsw · F · IO + IQ) · VIN
(0.7A)2 · (0.2Ω · 1.5V + 0.187Ω · (4.2V - 1.5V))
4.2V
+ (20nsec · 850kHz · 0.7A + 0.3mA) · 4.2V = 0.145W
TJ(MAX) = TAMB + ΘJA · PLOSS = 85°C + 150°C/W · 0.145W = 107°C (MSOP-8)
= 85°C + 50°C/W · 0.145W = 92°C (QFN33-16)
Surface Mount Inductors
Manufacturer
Part Number
Value
Max DC
Current
Ω)
DCR (Ω
TaiyoYuden
Toko
Sumida
Sumida
Sumida
MuRata
MuRata
MuRata
NPO5DB4R7M
A914BYW-3R5M-D52LC
CDRH5D28-3R0
CDRH5D28-4R2
CDRH5D18-4R1
LQH55DN4R7M03
LQH66SN4R7M03
CDRH3D16-3R3
4.7µH
3.5µH
3.0µH
4.2µH
4.1µH
4.7µH
4.7µH
3.3µH
1.4A
1.34A
2.4A
2.2A
1.95A
2.7A
2.2A
1.1A
0.038
0.073
0.024
0.031
0.057
0.041
0.025
0.063
Size (mm)
L×W×H
5.9
5.0
5.7
5.7
5.7
5.0
6.3
3.8
x
x
x
x
x
x
x
x
6.1
5.0
5.7
5.7
5.7
5.0
6.3
3.8
x
x
x
x
x
x
x
x
2.8
2.0
3.0
3.0
2.0
4.7
4.7
1.8
Type
Shielded
Shielded
Shielded
Shielded
Shielded
Non-Shielded
Shielded
Shielded
Surface Mount Capacitors
14
Manufacturer
Part Number
MuRata
MuRata
MuRata
MuRata
GRM40 X5R 106K 6.3
GRM42-6 X5R 106K 6.3
GRM21BR60J226ME39L
GRM21BR60J106ME39L
Value
Voltage
Temp. Co.
Case
10µF
10µF
22µF
10µF
6.3V
6.3V
6.3V
6.3V
X5R
X5R
X5R
X5R
0805
1206
0805
0805
1151.2005.11.1.4
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
Ordering Information
Output Voltage1
Package
Marking2
Part Number (Tape and Reel)3
1.0V (Adj VOUT ≥ 1.0V)
MSOP-8
JHXYY
AAT1151IKS-1.0-T1
1.0V (Adj VOUT ≥ 1.0V)
QFN33-16
JHXYY
AAT1151IVN-1.0-T1
1.8V
MSOP-8
JIXYY
AAT1151IKS-1.8-T1
1.8V
QFN33-16
JIXYY
AAT1151IVN-1.8-T1
2.5V
MSOP-8
JJXYY
AAT1151IKS-2.5-T1
2.5V
QFN33-16
JJXYY
AAT1151IVN-2.5-T1
3.3V
MSOP-8
NKXYY
AAT1151IKS-3.3-T1
Package Information
MSOP-8
4° ± 4°
4.90 ± 0.10
3.00 ± 0.10
1.95 BSC
0.95 REF
0.60 ± 0.20
PIN 1
3.00 ± 0.10
0.85 ± 0.10
0.95 ± 0.15
10° ± 5°
GAUGE PLANE
0.254 BSC
0.155 ± 0.075
0.075 ± 0.075
0.65 BSC
0.30 ± 0.08
All dimensions in millimeters.
1. Contact local sales office for custom options.
2. XYY = assembly and date code.
3. Sample stock is generally held on part numbers listed in BOLD.
1151.2005.11.1.4
15
AAT1151
850kHz 700mA Synchronous Buck DC/DC Converter
QFN33-16
0.230 ± 0.05
Pin 1 Identification
1
1.55 ± 0.15
13
9
0.500 ± 0.05
Top View
0.025 ± 0.025
Bottom View
0.850 ± 0.05
3.000 ± 0.05
0.400 ± 0.05
Pin 1 Dot By Marking
3.000 ± 0.05
5
0.203 ± 0.0254
Side View
All dimensions in millimeters.
© Advanced Analogic Technologies, Inc.
AnalogicTech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an AnalogicTech product. No circuit patent licenses, copyrights, mask work rights,
or other intellectual property rights are implied. AnalogicTech reserves the right to make changes to their products or specifications or to discontinue any product or service without notice.
Customers are advised to obtain the latest version of relevant information to verify, before placing orders, that information being relied on is current and complete. All products are sold
subject to the terms and conditions of sale supplied at the time of order acknowledgement, including those pertaining to warranty, patent infringement, and limitation of liability. AnalogicTech
warrants performance of its semiconductor products to the specifications applicable at the time of sale in accordance with AnalogicTech’s standard warranty. Testing and other quality control techniques are utilized to the extent AnalogicTech deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed.
Advanced Analogic Technologies, Inc.
830 E. Arques Avenue, Sunnyvale, CA 94085
Phone (408) 737-4600
Fax (408) 737-4611
16
1151.2005.11.1.4