LINER LTC1064AM Low noise, fast, quad universal filter building block Datasheet

LTC1064
Low Noise, Fast, Quad
Universal Filter Building Block
U
FEATURES
DESCRIPTION
■
The LTC®1064 consists of four high speed, low noise
switched-capacitor filter building blocks. Each filter building block, together with an external clock and three to five
resistors can provide various 2nd order functions like
lowpass, highpass, bandpass and notch. The center frequency of each 2nd order function can be tuned with an
external clock, or a clock and resistor ratio. For Q ≤ 5, the
center frequency range is from 0.1Hz to 100kHz. For Q ≤
3, the center frequency range can be extended to 140kHz.
Up to 8th order filters can be realized by cascading all four
2nd order sections. Any classical filter realization (such as
Butterworth, Cauer, Bessel and Chebyshev) can be formed.
■
■
■
■
■
■
■
■
Four Filters in a 0.3-Inch Wide Package
One Half the Noise of the LTC1059/LTC1060/
LTC1061 Devices
Maximum Center Frequency: 140kHz
Maximum Clock Frequency: 7MHz
Clock-to-Center Frequency Ratio of 50:1 and 100:1
Simultaneously Available
Power Supplies: ±2.375V to ±8V
Low Offsets
Low Harmonic Distortion
Customized Version with Internal Resistors
Available
U
APPLICATIONS
■
■
■
Anti-Aliasing Filters
Wide Frequency Range Tracking Filters
Spectral Analysis
Loop Filters
The LTC1064 is manufactured using Linear Technology’s
enhanced LTCMOSTM silicon gate process.
, LTC and LT are registered trademarks of Linear Technology Corporation.
LTCMOS is a trademark of Linear Technology Corporation.
U
■
A customized monolithic version of the LTC1064 including internal thin film resistors can be obtained for high
volume applications. Consult LTC Marketing for details.
TYPICAL APPLICATION
Clock-Tunable 8th Order Cauer Lowpass Filter with fCUTOFF up to 100kHz
13k
66.5k
1
10k
18.25k
10.7k
2
3
4
5
6
7
8V
0.1µF
10k
9
49.9K
10
11.5K
(FROM
RH2, RL2)
8
11
12
INV B
INV C
HPB/NB
HPC/NC
BPB
BPC
LPB
LPC
SB
SC
AGND
V–
V+
LTC1064
SA
CLK
50/100
LPA
LPD
BPA
BPD
HPA/NA
INV A
HPD
INV D
23
10k
22
12.1k
21
Gain vs Frequency
PIN 12
24
17.4k
0
–15
RL2
26.7k
–30
20
19
18
17
–8V
0.1µF
5MHz
8V
VOUT
16
15
41.2k
14
12.7k
13
14k
GAIN (dB)
22.1k
VIN
RH2
102k
–45
fCLK = 5MHz
RIPPLE = ±0.1dB
–60
–75
fCLK = 1MHz
RIPPLE = ±0.05dB
–90
–105
–120
–135
1k
121k
10k
100k
INPUT FREQUENCY (Hz)
1M
1064 TA02
10k
FOR fCLK = 5MHz, ADD C1 = 10pF BETWEEN PINS 4, 1
C2 = 10pF BETWEEN PINS 21, 24
C3 = 27pF BETWEEN PINS 9, 12
WIDEBAND NOISE ≅ 140µVRMS
1064 TA01
1
LTC1064
U
W W
W
ABSOLUTE MAXIMUM RATINGS
Total Supply Voltage (V + to V –) ............................. 16V
Power Dissipation............................................. 500mW
Operating Temperature Range
LTC1064AC/LTC1064C.................... – 40°C to 85°C
LTC1064AM/LTC1064M ................ – 55°C to 125°C
Storage Temperature Range ................ – 65°C to 150°C
Lead Temperature (Soldering, 10 sec)................. 300°C
U
W
U
PACKAGE/ORDER INFORMATION
TOP VIEW
INV B
1
24 INV C
HPB/NB
2
23 HPC/NC
BPB
3
22 BPC
LPB
4
21 LPC
SB
5
20 SC
AGND
6
19 V –
V+
7
18 CLK
SA
8
17 50/100
LPA
9
16 LPD
BPA 10
15 BPD
HPA/NA 11
14 HPD
INV A 12
J PACKAGE
24-LEAD CERAMIC DIP
ORDER PART
NUMBER
LTC1064ACJ
LTC1064CJ
LTC1064AMJ
LTC1064MJ
LTC1064ACN
LTC1064CN
INV B
1
24 INV C
HPB/NB
2
23 HPC/NC
BPB
3
22 BPC
LPB
4
21 LPC
SB
5
20 SC
AGND
6
19 V –
V+
7
18 CLK
SA
8
17 50/100
LPA
9
16 LPD
BPA 10
15 BPD
HPA/NA 11
14 HPD
INV A 12
13 INV D
ORDER PART
NUMBER
TOP VIEW
LTC1064CS
13 INV D
SW PACKAGE
24-LEAD PLASTIC SO
N PACKAGE
24-LEAD PLASTIC DIP
TJMAX = 150°C, θJA = 100°C/ W (J)
TJMAX = 110°C, θJA = 65°C/ W (N)
TJMAX = 100°C, θJA = 85°C/ W
Consult factory for Industrial grade parts.
ELECTRICAL CHARACTERISTICS
(Internal Op Amps) TA = 25°C, unless otherwise specified.
PARAMETER
Operating Supply Voltage Range
Voltage Swings
CONDITIONS
VS = ±5V, RL = 5k
●
Output Short-Circuit Current (Source/Sink)
DC Open-Loop Gain
GBW Product
Slew Rate
2
VS = ±5V
VS = ±5V, RL = 5k
VS = ±5V
VS = ±5V
MIN
±2.375
±3.2
±3.1
TYP
±3.6
3
80
7
10
MAX
±8
UNITS
V
V
V
mA
dB
MHz
V/µs
LTC1064
ELECTRICAL CHARACTERISTICS
(Complete Filter) VS = ±5V, TA = 25°C, TTL clock input level, unless otherwise specified.
PARAMETER
Center Frequency Range, fO
Input Frequency Range
Clock-to-Center Frequency
Ratio, fCLK /fO
CONDITIONS
VS = ±8V, Q ≤ 3
LTC1064
LTC1064A (Note 1)
LTC1064
LTC1064A (Note 1)
Clock-to-Center Frequency
Ratio, Side-to-Side Matching
Clock-to-Center Frequency
Ratio, fCLK/fO (Note 2)
LTC1064
LTC1064A (Note 1)
LTC1064
LTC1064A (Note 1)
LTC1064
LTC1064 A (Note 1)
Q Accuracy
fO Temperature Coefficient
Q Temperature Coefficient
DC Offset Voltage
Clock Feedthrough
Maximum Clock Frequency
Power Supply Current
VOS1 (Table 1)
VOS2 (Table 1)
VOS3 (Table 1)
MIN
fCLK = 1MHz, fO = 20kHz, Pin 17 High
Sides A, B, C: Mode 1,
R1 = R3 = 5k, R2 = 5k, Q = 10,
Sides D: Mode 3, R1 = R3 = 50k
R2 = R4 = 5k
Same as Above, Pin 17 Low, fCLK = 1MHz
fO = 10kHz
Sides A, B, C
Side D
fCLK = 1MHz
TYP
0.1 to 140
0 to 1
50 ± 0.3
●
50 ± 0.8
UNITS
kHz
MHz
%
%
●
50 ± 0.9
%
100 ± 0.3
%
0.4
%
%
%
%
1
50 ± 0.6
100 ± 0.6
●
●
●
●
●
9
●
The ● denotes specifications which apply over the full operating
temperature range.
%
100 ± 0.8
100 ± 0.9
●
●
●
fCLK = 4MHz, fO = 80kHz, Pin 17 High
Sides A, B, C: Mode 1, VS = ±7.5V
R1 = R3 = 50k, R2 = 5k, Q = 5
Side D: Mode 3, R1 = R3 = 50k
R2 = R4 = 5k, fCLK = 4MHz
Same as Above, Pin 17 Low
fCLK = 4MHz, fO = 40kHz
Sides A, B, C: Mode 1, Q = 10
Side D: Mode 3, fCLK = 1MHz
Mode 1, 50:1, fCLK < 2MHz
Mode 1, 100:1, fCLK < 2MHz
Mode 3, fCLK < 2MHz
fCLK = 1MHz, 50:1 or 100:1
fCLK = 1MHz, 50:1 or 100:1
fCLK = 1MHz, 50:1 or 100:1
fCLK < 1MHz
Mode 1, Q < 5, VS ≥ ±5V
MAX
±2
±3
±1
±5
±5
2
3
3
0.2
7
12
50 ± 1.3
100 ± 1.3
6
8
15
45
45
23
26
%
%
%
%
ppm/°C
ppm/°C
ppm/°C
mV
mV
mV
mVRMS
MHz
mA
mA
Note 1: Contact LTC Marketing.
Note 2: Not tested, guaranteed by Design.
Table 1. Output DC Offsets, One 2nd Order Section
MODE
1
1b
2
3
VOSN
PINS 2, 11, 14, 23
VOS1 [(1/Q) + 1 + HOLP] – VOS3 /Q
VOS1 [(1/Q) + 1 + (R2/R1)] – VOS3 /Q
VOS1 [(1 + (R2/R1) + (R2/R3) + (R2/R4) – VOS3 (R2/R3)]
× [R4/(R2 + R4)] + VOS2[R2/(R2 + R4)]
VOS2
VOSBP
PINS 3, 10, 15, 22
VOS3
VOS3
VOS3
VOS3
VOSLP
PINS 4, 9, 16, 21
VOSN – VOS2
~(VOSN – VOS2)[1 + (R5/R6)]
VOSN – VOS2
VOS1[1 + (R4/R1) + (R4/R2) + (R4/R3)]
– VOS2(R4/R2) – VOS3(R4/R3)
3
LTC1064
W
BLOCK DIAGRA
HPA/NA
(11)
BPA
(10)
LPA
(9)
V + (7)
INV A
(12)
–
AGND
(6)
+
+
–
CLK (18)
LPB
(4)
SA
(8)
+
Σ
+∫
V – (19)
+∫
–
HPC/NC
(23)
–
+
LPC
(21)
BPC
(22)
SB
(5)
+
Σ
+∫
BY TYING PIN 17 TO V +, ALL SECTIONS
OPERATE WITH (fCLK/fO) = 50:1.
+∫
BY TYING PIN 17 TO V –, ALL SECTIONS
OPERATE WITH (fCLK/fO) = 100:1.
–
HPD
(14)
INV D
(13)
50/100 (17)
+∫
BPB
(3)
+
INV C
(24)
+∫
–
HPB/NB
(2)
INV B
(1)
Σ
LPD
(16)
BPD
(15)
SC
(20)
BY TYING PIN 17 TO AGND, SECTIONS B, C
OPERATE WITH (fCLK/fO) = 50:1 AND
SECTIONS A, D OPERATE AT 100:1.
–
+∫
+∫
+
1064 BD
U W
TYPICAL PERFORMANCE CHARACTERISTICS
VS = ±2.5V
VS = ±7.5V
0
1.0
VS = ±7.5V
VS = ±5V
VS = ±2.5V
0.5
0
0 10 20 30 40 50 60 70 80 90 100110 120
CENTER FREQUENCY (kHz)
1064 G01
4
VS = ±5V
10
VS = ±7.5V
5
0
–5
TA = 25°C
Q = 5 OR 10
1.5
15
1.5
VS = ±2.5V
0.5
15
10
5
VS = ±2.5V
CC = 15pF
0
VS = ±5V
CC = 15pF
–5
VS = ±5V
1.0 VS = ±2.5V
TA = 25°C
Q = 10
PIN 17 AT V +
(R2/R4) = 3
20
Q ERROR (%)
5
Q ERROR (%)
10
Mode 2, (fCLK /fO) = 25:1
TA = 25°C
Q=5
Q = 10
20
VS = ±5V
15
–5
CENTER FREQUENCY
ERROR (%)
TA = 25°C
Q=5
Q = 10
CENTER FREQUENCY
ERROR (%)
Q ERROR (%)
20
Mode 1, (fCLK /fO) = 100:1
TA = 25°C
Q = 5 OR 10
VS = ±7.5V
0
0 10 20 30 40 50 60 70 80 90 100110 120
CENTER FREQUENCY (kHz)
1064 G02
CENTER FREQUENCY
ERROR (%)
Mode 1, (fCLK /fO) = 50:1
1.5
1.0
0.5
VS = ±2.5V
VS = ±5V
0
0 10 20 30 40 50 60 70 80 90 100110 120
CENTER FREQUENCY (kHz)
1064 G03
LTC1064
U W
TYPICAL PERFORMANCE CHARACTERISTICS
10
5
Q=5
CC = 22pF
Q=2
CC = 39pF
0
–5
15
10
TA = 25°C
PIN 17 AT V –
(R2/R4) = 3
Q=5
Q = 10
VS = ±7.5V
5
0
20
1.5
Q=2
Q=5
1.0
0.5
0
0 20 40 60 80 100 120140160180 200
CENTER FREQUENCY (kHz)
TA = 25°C
CC = 5pF
R2 = R4
Q=5
Q = 10
VS = ±5V
15
VS = ±2.5V
10
5
VS = ±7.5V
0
–5
–5
CENTER FREQUENCY
ERROR (%)
CENTER FREQUENCY
ERROR (%)
VS = ±2.5V VS = ±5V
20
Mode 3, (fCLK /fO) = 50:1
1.5
VS = ±5V
1.0
VS = ±2.5V
0.5
VS = ±7.5V
0
0 10 20 30 40 50 60 70 80 90 100110 120
CENTER FREQUENCY (kHz)
1064 G04
CENTER FREQUENCY
ERROR (%)
15
TA = 25°C
VS = ±7.5V
PIN 17 AT V +
(R2/R4) = 3
Q ERROR (%)
Q ERROR (%)
20
Mode 2, (fCLK /fO) = 50:1
Q ERROR (%)
Mode 2, (fCLK /fO) = 25:1
1.5
1.0
VS = ±5V
VS = ±2.5V
0.5
0
0 10 20 30 40 50 60 70 80 90 100110 120
CENTER FREQUENCY (kHz)
1064 G06
1064 G05
Mode 3, (fCLK /fO) = 50:1
VS = ±7.5V
Wideband Noise vs Q
Mode 3, (fCLK /fO) = 100:1
240
20
10
Q=2
5
Q=1
0
1.0
VS = ±7.5V
VS = ±2.5V
VS = ±5V
0.5
0
0 10 20 30 40 50 60 70 80 90 100 110 120
CENTER FREQUENCY (kHz)
CENTER FREQUENCY
ERROR (%)
1.5
VS = ±5V
10
5
VS = ±7.5V
0
–5
VS = ±2.5V
VS = ±5V
1.5
VS = ±7.5V
1.0
ANY OUTPUT
R3 = R1
ONE SECOND ORDER
SECTION
MODE 1 OR 3
100:1 OR 50:1
220
200
180
160
140
120
±7.5V
±5V
±2.5V
100
80
60
40
0.5
20
0
0
0 10 20 30 40 50 60 70 80 90 100110 120
CENTER FREQUENCY (kHz)
0
2
4
6
8 10 12 14 16 18 20 22 24
Q
1064 G08
1064 G07
1064 G09
Harmonic Distortion, 8th Order
LP Butterworth, fC = 20kHz,
THD = 0.015% for 3VRMS Input
Power Supply Current vs
Supply Voltage
48
44
POWER SUPPLY CURRENT (mA)
CENTER FREQUENCY
ERROR (%)
–5
VS = ±2.5V
15
TA = 25°C
CC = 5pF
R2 = R4
Q = 10
WIDEBAND NOISE (µV/RMS)
15
TA = 25°C
CC = 15pF
R2 = R4
VS = ±7.5V
Q ERROR (%)
Q ERROR (%)
20
40
36
32
28
24
–55°C
25°C
125°C
20
16
12
8
4
0
0
2
4 6 8 10 12 14 16 18 20 22 24
POWER SUPPLY VOLTAGE (V + – V –)
1064 G11
1064 G10
5
LTC1064
U
U
U
PIN FUNCTIONS
V +, V – (Pins 7, 19): Power Supplies. They should be
bypassed with a 0.1µF ceramic capacitor. Low noise,
nonswitching power supplies are recommended. The device operates with a single 5V supply and with dual
supplies. The absolute maximum operating power supply
voltage is ±8V.
AGND (Pin 6): Analog Ground. When the LTC1064 operates with dual supplies, Pin 6 should be tied to system
ground. When the LTC1064 operates with a single positive
supply, the analog ground pin should be tied to 1/2 supply
and it should be bypassed with a 1µF solid tantalum in
parallel with a 0.1µF ceramic capacitor, Figure 1. The
positive input of all the internal op amps, as well as the
common reference of all the internal switches, are internally tied to the analog ground pin. Because of this, a very
“clean” ground is recommended.
CLK (Pin 18): Clock. For ±5V supplies the logic threshold
level is 1.4V. For ±8V and 0V to 5V supplies the logic
threshold levels are 2.2V and 3V respectively. The logic
threshold levels vary ±100mV over the full military temperature range. The recommended duty cycle of the input
clock is 50%, although for clock frequencies below 500kHz,
the clock “on” time can be as low as 200ns. The maximum
clock frequency for ±5V supplies is 4MHz. For ±7V
supplies and above, the maximum clock frequency is
7MHz.
50/100 (Pin 17): By tying Pin 17 to V +, all filter sections
operate with a clock-to-center frequency ratio internally
set at 50:1. When Pin 17 is at mid-supplies, sections B and
C operate with (fCLK /fO) = 50:1 and sections A and D
operate at 100:1. When Pin 17 is shorted to the negative
supply pin, all filter sections operate with (fCLK /fO) =
100:1.
1
24
2
V+
23
LTC1064
3
22
4
5k
V+/2
+
1µF
5
20
6
19
V–
7
5k
0.1µF
ANALOG
GROUND
PLANE
21
8
AGND
V+
CLK
50/100
CLOCK INPUT
V + = 15V, TRIP VOLTAGE = 7V
V + = 10V, TRIP VOLTAGE = 6.4V
V + = 5V, TRIP VOLTAGE = 3V
18
17
9
16
10
15
11
14
12
13
TO DIGITAL
GROUND
1064 F01
NOTE: PINS 5, 8, 20, IF NOT USED, SHOULD BE CONNECTED TO PIN 6
Figure 1. Single Supply Operation
6
LTC1064
U
W
U
U
APPLICATIONS INFORMATION
ANALOG CONSIDERATIONS
Grounding and Bypassing
Figure 2 shows an example of an ideal ground plane design
for a two-sided board. Of course this much ground plane
will not always be possible, but users should strive to get
as close to this as possible. Protoboards are not
recommended.
The LTC1064 should be used with separated analog and
digital ground planes and single point grounding
techniques.
Pin 6 (AGND) should be tied directly to the analog ground
plane.
Buffering the Filter Output
Pin 7 (V +) should be bypassed to the ground plane with a
0.1µF ceramic capacitor with leads as short as possible.
Pin 19 (V –) should be bypassed with a 0.1µF ceramic
capacitor. For single supply applications, V – can be tied to
the analog ground plane.
When driving coaxial cables and 1× scope probes, the
filter output should be buffered. This is important especially when high Qs are used to design a specific filter.
Inadequate buffering may cause errors in noise, distortion, Q and gain measurements. When 10 × probes are
used, buffering is usually not required. An inverting buffer
is recommended especially when THD tests are performed. As shown in Figure 3, the buffer should be
adequately bypassed to minimize clock feedthrough.
For good noise performance, V + and V – must be free of
noise and ripple.
All analog inputs should be referenced directly to the
single point ground. The clock inputs should be shielded
from and/or routed away from the analog circuitry and a
separate digital ground plane used.
VIN
2
23
3
22
FOR BEST HIGH FREQUENCY RESPONSE
PLACE RESISTORS PARALLEL TO DOUBLESIDED COPPER CLAD BOARD AND LAY FLAT
(4 RESISTORS SHOWN HERE TYPICAL)
4
21
5
7.5V
0.1µF
CERAMIC
ANALOG
GROUND
PLANE
PIN 1 IDENT
24
1
LTC1064
20
6
19
7
18
8
17
9
16
10
15
11
14
12
13
5k
–7.5V
0.1µF CERAMIC
CLOCK
DIGITAL
GROUND
PLANE
(SINGLE POINT
GROUND)
NOTE: CONNECT ANALOG AND DIGITAL
GROUND PLANES AT A SINGLE POINT AT
THE BOARD EDGE
1064 F02
Figure 2. Example Ground Plane Breadboard Technique for LTC1064
7
LTC1064
U
W
U
U
APPLICATIONS INFORMATION
Offset Nulling
Noise
Lowpass filters may have too much DC offset for some
users. A servo circuit may be used to actively null the
offsets of the LTC1064 or any LTC switched-capacitor
filter. The circuit shown in Figure 4 will null offsets to better
than 300µV. This circuit takes seconds to settle because of
the integrator pole frequency.
All the noise performance mentioned excludes the clock
feedthrough. Noise measurements will degrade if the
already described grounding bypassing and buffering
techniques are not practiced. The graph Wideband Noise
vs Q in the Typical Performance Characteristics section is
a very good representation of the noise performance of
this device.
SEPARATE V + POWER SUPPLY TRACE FOR BUFFER
R12
+
R11
VIN
0.1µF
R21
R22
R31
R32
10k
LTC1064
POSITIVE
SUPPLY
19
7
10k
–
R1
1M
4
LT ®318
LT1007
LT1056
V + TRACE FOR FILTER
0.1µF
FROM
FILTER OUTPUT
1µF
+
TO FILTER
FIRST SUMMING
NODE
7
+
R3
100k
C1
0.1µF
LT1012
–
0.1µF
NEGATIVE
SUPPLY
0.1µF
+
1µF
R2
1M
C2
0.1µF
C1 = C2 = LOW LEAKAGE FILM
(I.E. POLYPROPYLENE)
R1 = R2 = METAL FILM 1%
1064 F04
1064 F03
Figure 3. Buffering the Output of a 4th Order Bandpass Realization
Figure 4. Servo Amplifier
W
U
ODES OF OPERATIO
PRIMARY MODES
Mode 1
In Mode 1, the ratio of the external clock frequency to the
center frequency of each 2nd order section is internally
fixed at 50:1 or 100:1. Figure 5 illustrates Mode 1 providing 2nd order notch, lowpass and bandpass outputs.
Mode 1 can be used to make high order Butterworth
lowpass filters; it can also be used to make low Q notches
and for cascading 2nd order bandpass functions tuned at
the same center frequency with unity gain. Mode 1 is faster
than Mode 3. Note that Mode 1 can only be implemented
with three of the four LTC1064 sections because Section
D has no externally available summing node. Section D,
however, can be internally connected in Mode 1 upon
special request.
8
R3
R2
N
R1
–
VIN
BP
S
+
Σ
–
+
∫
LP
∫
1/4 LTC1064
AGND
fO =
R2
R3
R2
R3
fCLK
; f n = fO; HOLP = –
;H
=–
;H
=–
;Q=
R1 OBP
R1 ON1
R1
R2
100(50)
1064 F05
Figure 5. Mode 1: 2nd Order Filter Providing Notch,
Bandpass and Lowpass
LTC1064
W
U
ODES OF OPERATIO
Mode 3
SECONDARY MODES
Mode 3 is the second of the primary modes. In Mode 3, the
ratio of the external clock frequency to the center frequency of each 2nd order section can be adjusted above or
below 50:1 or 100:1. Side D of the LTC1064 can only be
connected in Mode 3. Figure 6 illustrates Mode 3, the
classical state variable configuration, providing highpass,
bandpass and lowpass 2nd order filter functions. Mode 3
is slower than Mode 1. Mode 3 can be used to make high
order all-pole bandpass, lowpass, highpass and notch
filters.
Mode 1b
When the internal clock-to-center frequency ratio is set at
50:1, the design equations for Q and bandpass gain are
different from the 100:1 case. This was done to provide
speed without penalizing the noise performance.
Mode 1b is derived from Mode 1. In Mode 1b, Figure 7, two
additional resistors R5 and R6 are added to alternate the
amount of voltage fed back from the lowpass output into
the input of the SA (or SB or SC) switched-capacitor
summer. This allows the filter’s clock-to-center frequency
ratio to be adjusted beyond 50:1 or 100:1. Mode 1b
maintains the speed advantages of Mode 1.
R6
R5
R3
R2
N
R1
–
VIN
CC
BP
S
+
Σ
–
∫
+
LP
∫
1064 F07
1/4 LTC1064
R4
AGND
R3
R2
HP
R1
–
VIN
BP
S
+
Σ
–
+
∫
LP
fO =
fCLK
100(50)
(
∫
1064 F06
HOBP = –
AGND
MODE 3 (50:1):
√
√
R2
;H
=–
R1 OBP
√
R3
R4
R1
; H OLP = –
R3
R1
1–
16R4
R2
√
; THEN CALCULATE R1 TO SET
R2 + R2 THE DESIRED GAIN.
R4 16R4
√R5R6+ R6 ;
R3
; R5R6 ≤ 5k
R1
R2
R1
;
R6
R5 + R6
1064 F07 Eq
Mode 2
√
NOTE: THE 50:1 EQUATIONS FOR MODE 3 ARE DIFFERENT FROM THE EQUATIONS
FOR MODE 3 OPERATIONS OF THE LTC1059, LTC1060 AND LTC1061. START WITH
fO, CALCULATE R2/R4, SET R4; FROM THE Q VALUE, CALCULATE R3:
1.005
Q
)
R3
R2
Figure 7. Mode 1b: 2nd Order Filter Providing Notch,
Bandpass and Lowpass
R2
R3 R2
R2
;Q=
; H OHP = –
;
R4
R2 R4
R1
R3
R4
HOBP = –
;H
=–
R1 OLP
R1
R2
1.005 R4
f
R2
fO = CLK
;Q=
;
R2
R2
50
R4
–
R3 16R4
f
fO = CLK
100
HOHP = –
R3 =
n = fO; Q =
R2
f
HON1(f→ 0) = HON2 f→ CLK = –
;H
=–
R1 OLP
2
1/4 LTC1064
MODE 3 (100:1):
√R5R6+ R6; f
1064 F06 Eq
Figure 6. Mode 3: 2nd Order Filter Providing Highpass,
Bandpass and Lowpass
Mode 2 is a combination of Mode 1 and Mode 3, as shown
in Figure 8. With Mode 2, the clock-to-center frequency
ratio fCLK /fO is always less than 50:1 or 100:1. The
advantage of Mode 2 is that it provides less sensitivity to
resistor tolerances than does Mode 3. As in Mode 1, Mode
2 has a notch output which depends on the clock frequency and the notch frequency is therefore less than the
center frequency fO.
When the internal clock-to-center frequency ratio is set at
50:1, the design equations for Q and bandpass gain are
different from the 100:1 case.
9
LTC1064
W
U
ODES OF OPERATIO
R4
MODE 2 (100:1):
R3
R2
N
R1
–
VIN
BP
S
+
Σ
–
∫
+
√
1+
f
R3
R2
; f = CLK ; Q =
50
R2
R4 n
√
1+
R2
; HOLP = –
R4
(
)
R2
R1
;
R2
1+
R4
R2
R2
R3
f
R1
HOBP = –
; H (f→ 0) = –
; HON2 f→ CLK = –
R1
R1 ON1
2
R2
1+
R4
LP
∫
f
fO = CLK
100
MODE 2 (50:1):
√
R2
R2
1.005 1 +
R2
f
R1
R4 ; H
; fn = CLK ; Q =
=
–
;
OLP
R4
50
R2
R2
R2
1+
–
R3 16R4
R4
f
fO = CLK
50
√
HOBP = –
R3
R2
f
R2
R1
R1
; HON1(f→ 0) = –
;H
= f→ CLK = –
2
R3
R1
R2 ON2
1–
1+
16R4
R4
1+
1064 F08
1/4 LTC1064
AGND
(
)
NOTE: THE 50:1 EQUATIONS FOR MODE 2 ARE DIFFERENT FROM THE EQUATIONS
FOR MODE 2 OPERATION OF THE LTC1059, LTC1060 AND LTC1061. START WITH
fO, CALCULATE R2/R4, SET R4; FROM THE Q VALUE, CALCULATE R3:
R2
R3 =
1.005
Q
R2
√1 + R2R4 + 16R4
; THEN CALCULATE R1 TO SET THE DESIRED GAIN.
1064 F08Eq
Figure 8. Mode 2: 2nd Order Filter Providing Notch, Bandpass and Lowpass
Mode 3a
This is an extension of Mode 3 where the highpass and
lowpass outputs are summed through two external resistors RH and RL to create a notch. This is shown in Figure
9. Mode 3a is more versatile than Mode 2 because the
notch frequency can be higher or lower than the center
frequency of the 2nd order section. The external op amp of
Figure 9 is not always required. When cascading the
sections of the LTC1064, the highpass and lowpass out-
puts can be summed directly into the inverting input of the
next section. The topology of Mode 3a is useful for elliptic
highpass and notch filters with clock-to-cutoff frequency
ratios higher than 100:1. This is often required to extend
the allowed input signal frequency range and to avoid
premature aliasing.
When the internal clock-to-center frequency ratio is set at
50:1, the design equations for Q and bandpass gain are
different from the 100:1 case.
MODE 3a (100:1):
CC
R4
MODE 3a (50:1):
R2
R1
–
+
HP
S
+
–
Σ
BP
∫
∫
1/4 LTC1064
AGND
√ R2R4 ; f = 100 √ R ; H
HOLP = –
RG R2
R R4
R4
f
; H (f→ 0) = G
;H
f→ CLK =
;
RH R1
RL R1 ON2
R1 ON1
2
n
HON(f = fO) = Q
R3
VIN
f
fO = CLK
100
RL
–
NOTCH
+
RH
EXTERNAL OP AMP OR INPUT
OP AMP OF THE LTC1064,
SIDE A, B, C, D
1064 F09
RH
L
OHP = –
( )( ) (
)
(
√
R
RG
R3
H
– GH
;Q=
RL OLP RH OHP
R2
) ( )( )
√ R2R4
)
√1 + R2R4 ; f = f50
HOBP = –
R3
R2
1.005
R4
R1
R4
; HOLP(f = 0) = –
;Q =
R3
R1
R2
R2
1–
–
16R4
R3 16R4
n
CLK
R2
f
RH
;
; HOHP f→ CLK = –
R1
2
RL
√
NOTE: THE 50:1 EQUATIONS FOR MODE 3A ARE DIFFERENT FROM
THE EQUATIONS FOR MODE 3A OPERATION OF THE LTC1059,
LTC1060 AND LTC1061. START WITH fO, CALCULATE R2/R4, SET R4;
FROM THE Q VALUE, CALCULATE R3:
R2
R3 =
; THEN CALCULATE R1 TO
1.005
Q
R2 SET THE DESIRED GAIN.
√ R2R4 + 16R4
Figure 9. Mode 3a: 2nd Order Filter Providing Highpass, Bandpass, Lowpass and Notch
10
R3
R2
; HOBP = –
;
R1
R1
f
fO = CLK
50
RG
LP
(
fCLK
1064 F09Eq
LTC1064
U
TYPICAL APPLICATIONS
Amplitude Response
Wideband Bandpass: Ratio of High to Low Corner Frequency Equal to 2
R14
15
R23
2
R33
3
R43
4
5
6
C1
7
5V TO 8V
0.1µF
8
R41
9
R31
10
R21
11
R11
12
VIN
INV B
INV C
HPB/NB
HPC/NC
BPB
BPC
LPB
LPC
SB
SC
AGND
V–
LTC1064
V+
24
SA
BPA
BPD
INV A
21
R44
18
fCLK = 7MHz
–15
VOUT
–5V TO –8V
0.1µF
fCLK ≤ 7MHz
–30
–45
fCLK = 2MHz
–60
–75
17
–90
VS = ±8V
16
HPD
HPA/NA
22
R34
0
19
50/100
LPD
R24
20
CLK
LPA
23
GAIN (dB)
1
INV D
15
R42
14
R32
13
R22
C2
–105
10k
100k
INPUT FREQUENCY (Hz)
1M
1064 TA04
R12
R13
RESISTOR VALUES:
R11 = 16k R21 = 16k R31 = 7.32k R41 = 10k
R12 = 10k R22 = 10k R32 = 22.6k R42 = 13.3k
R13 = 23.2k R23 = 13.3k R33 = 21.5k R43 = 10k
R14 = 6.8k R24 = 20k R34 = 15.4k R44 = 32.4k
NOTE: FOR fCLK ≥ 3MHz, USE C1 = C2 = 22pF
1064 TA03
Amplitude Response
Quad Bandpass Filter with Center Frequency Equal to fO, 2fO, 3fO, and 4fO
10.5k
5
VIN1
1
R22
2
R32
3
4
5
6
7
5V TO 8V
0.1µF
8
9
R31
R21
R11
VIN3
10
11
12
INV C
INV B
HPB/NB
HPC/NC
BPB
BPC
LPB
LPC
SB
SC
AGND
V–
V+
LTC1064
SA
CLK
50/100
LPA
LPD
BPA
BPD
HPA/NA
INV A
HPD
INV D
R13
24
23
R23
22
R33
21
R43
VIN2
–5
–10
20
19
18
–5V TO –8V
fCLK
fCLK = 2MHz
0
GAIN (dB)
R12
–15
–20
–25
0.1µF
–30
17
16
R44
–35
15
R34
–40
14
R24
0
20
30
40
50
INPUT FREQUENCY (kHz)
R14
13
10
1064 TA06
VIN4
20k
17.4k
20k
20k
RESISTOR VALUES:
R11 = 249k R21 = 10k
R12 = 249k R22 = 10k
R13 = 499k R23 = 10k
R14 = 453k R24 = 10k
R31 = 249k
R32 = 249k
R33 = 174k
R34 = 249k
–
LT1056
VOUT
+
R43 = 17.8k
R44 = 40.2k
1064 TA05
11
LTC1064
U
TYPICAL APPLICATIONS
Amplitude Response
8th Order Bandpass Filter with 2 Stopband Notches
RL2
10
VS = ±5V
fCLK = 1.28MHz
PIN 17 AT V +
RH2
0
RH3
1
R22
2
R32
3
R42
5
6
7
R31
R21
R11
BPC
LPB
LPC
SB
SC
AGND
V–
LTC1064
SA
9
10
11
12
VIN
BPB
V+
8
0.1µF
R41
HPC/NC
HPB/NB
4
5V TO 8V
INV C
INV B
CLK
50/100
LPA
LPD
BPA
BPD
HPA/NA
HPD
INV A
INV D
24
–10
23
R23
22
R33
21
R43
GAIN (dB)
R12
RL3
20
19
18
1.28MHz
0.1µF
R44
15
R34
14
R24
–40
–60
TO V +
16
–30
–50
–5V TO –8V
17
–20
–70
1
5
10
20
40
INPUT FREQUENCY (kHz)
100
1064 TA08
13
VOUT
RESISTOR VALUES:
R11 = 46.95k R21 = 10k
R12 = 93.93k R22 = 10k
R23 = 16.3k
R24 = 13.19k
R31 = 38.25k
R32 = 81.5k
R33 = 70.3k
R34 = 39.42k
R41 = 11.81k
R42 = 14.72k R L2 = 27.46k R H2 = 6.9k
R43 = 10k
R L3 = 17.9k R H3 = 69.7k
R44 = 10.5k
NOTE1: THE V +, V – PINS SHOULD BE BYPASSED WITH A 0.1µF TO 0.22µF
CERAMIC CAPACITOR, RIGHT AT THE PINS.
NOTE 2: THE RATIOS OF ALL (R2/R4) RESISTORS SHOULD BE MATCHED
TO BETTER THAN 0.25%. THE REMAINING RESISTORS SHOULD BE
BETTER THAN 0.5% ACCURATE.
1064 TA07
C-Message Filter
Amplitude Response
R13
R22
2
R32
3
R42
4
5
6
7
5V
R12 0.1µF
8
R41
9
R31
10
R21
R11
12
VIN
RESISTOR VALUES:
R11 = 88.7k R21 = 10k
R12 = 10k
R22 = 44.8k
R13 = 15.8k R23 = 48.9k
R14 = 15.8k R24 = 44.8k
12
11
INV C
INV B
HPB/NB
HPC/NC
BPB
BPC
LPB
LPC
SB
SC
V–
AGND
V+
LTC1064
SA
CLK
50/100
LPA
LPD
BPA
BPD
HPA/NA
INV A
HPD
INV D
10
24
23
R23
22
R33
21
R43
20
–10
0.1µF
R14
19
–5V
18
fCLK =
17
16
R44
15
R34
14
R24
R41 = 88.7k
R42 = 24.9k
R43 = 25.5k
R44 = 24.9k
3.5795MHz
16
–20
–30
–40
–50
–60
–70
0
1
3
2
4
INPUT FREQUENCY (kHz)
5
1064 TA10
13
VOUT
R31 = 35.7k
R32 = 33.2k
R33 = 63.5k
R34 = 16.5k
VS = ±5V
0
GAIN (dB)
1
1064 TA09
LTC1064
U
TYPICAL APPLICATIONS
8th Order Chebyshev Lowpass Filter with a Passband
Ripple of 0.1dB and Cutoff Frequency up to 100kHz
Amplitude Response
R13
15
R22
2
R32
R12
INV B
HPB/NB
3
R42
10
R21
SA
11
R11
CLK
LPA
LPD
BPA
BPD
HPD
INV A
24
INV D
0
23
R23
22
R33
–15
21
R43
–30
20
R14
– 19
50/100
HPA/NA
12
VIN
V
LTC1064
V+
8
R31
SC
AGND
7
9
LPC
SB
6
R41
BPC
LPB
5
0.1µF
HPC/NC
BPB
4
5V TO 8V
INV C
–5V TO –8V
18
GAIN (dB)
1
0.1µF
–45
–60
fCLK = 5MHz
17
16
5V TO 8V
R44
15
R34
14
R24
–75
VS = ±8V
fCLK = 5MHz
PASSBAND RIPPLE = 0.1dB
–90
–105
10k
100k
INPUT FREQUENCY (Hz)
13
1M
1064 TA12
VOUT
RESISTOR VALUES:
R11 = 100.86k R21 = 16.75k
R12 = 25.72k R22 = 20.93k
R13 = 16.61k R23 = 10.18k
R14 = 13.84k R24 = 11.52k
R31 = 23.6k
R32 = 45.2k
R33 = 68.15k
R34 = 17.72k
R41 = 99.73k
R42 = 25.52k
R43 = 99.83k
R44 = 25.42k
1064 TA11
FOR fCLK > 3MHz, ADD C2 = 10pF ACROSS R42
C3 = 10pF ACROSS R43
C4 = 10pF ACROSS R44
WIDEBAND NOISE = 170µVRMS
8th Order Clock-Sweepable Lowpass Elliptic Antialiasing Filter
Amplitude Response
RH1
0
RL1
–15
RH2
RL2
1
R22
R32
R42
2
3
4
5
6
7
7.5V
0.1µF
8
R43
9
R33
10
R23
11
12
INV B
INV C
HPB/NB
HPC/NC
BPB
BPC
LPB
LPC
SB
SC
AGND
V–
V+
LTC1064
SA
LPA
CLK
50/100
LPD
BPA
BPD
HPA/NA
HPD
INV A
INV D
24
23
R21
22
R31
21
R41
VIN
–60
–75
–90
19
18
17
–7.5V
fCLK ≤ 2MHz
–105
0.1µF
0
–7.5V
16
R44
15
R34
14
R24
20
30
40
50
60
70
8TH ORDER CLOCK-SWEEPABLE LOWPASS
ELLIPTIC ANTIALIASING FILTER MAINTAINS,
FOR 0.1Hz ≤ fCUTOFF ≤ 20kHz, A ±0.1dB MAX
PASSBAND ERROR AND 72dB MIN STOPBAND
ATTENUATION AT 1.5 × fCUTOFF.
13
R41 = 15.4k
R42 = 10.2k
R43 = 10k
R44 = 42.7k
10
FREQUENCY (kHz)
VOUT
RH3
R31 = 13.7k
R32 = 23.7k
R33 = 84.5k
R34 = 15.2k
–45
20
RL3
RESISTOR VALUES:
R11 = 19.1k R21 = 10k
R22 = 10k
R23 = 11.3k
R24 = 15.4k
VOUT/VIN (dB)
–30
R11
TOTAL WIDEBAND NOISE = 150µVRMS,
THD = 70dB (0.03%) FOR VIN = 3VRMS,
fCLK /fCUTOFF = 100:1. THIS FILTER AVAILABLE
AS LTC1064-1 WITH INTERNAL THIN FILM
1064 TA14
RESISTORS.
R H1 = 30.9k
R L1 = 14k
R L2 = 26.7k R H2 = 76.8k
R H3 = 60.2k
R L3 = 10k
NOTE: FOR tCUTOFF >15kHz, ADD A 5pF CAPACITOR ACROSS R41 AND R43
1064 TA13
13
LTC1064
U
TYPICAL APPLICATIONS
Dual 4th Order Bessel Filter with 140kHz Cutoff Frequency
Amplitude Response
R13
VIN1
1
R22
R32
R42
2
3
4
5
6
7
8V
0.1µF
8
9
R41
R11
10
R31
11
R21
12
VIN2
INV B
INV C
HPB/NB
HPC/NC
BPB
BPC
LPB
LPC
SB
SC
V–
AGND
R23
22
R33
– 15
21
R43
–30
20
VOUT1
19
–8V
0.1µF
18 7MHz
CLK
CLOCK
17
50/100
8V
16
LPD
R44
15
BPD
R34
14
HPD
R24
13
INV D
R14
SA
LPA
BPA
HPA/NA
INV A
RESISTOR VALUES:
R11 = 14.3k R21 = 13k
R12 = 15.4k R22 = 15.4k
R13 = 3.92k R23 = 20k
R14 = 3.92k R24 = 20k
0
23
LTC1064
V+
15
24
R31 = 7.5k
R32 = 7.5k
R33 = 27.4k
R34 = 6.8k
GAIN (dB)
R12
–105
10k
R31
R41
2
3
4
5
6
7
5V TO 8V
0.1µF
8
9
R43
FROM
PIN 20
R13
10
R33
11
R23
12
INV B
INV C
HPB/NB
fCLK 65
=
f –3dB 1
Amplitude Response
HPC/NC
22
R32
– 15
21
R42
–30
LPC
SB
SC
AGND
19
V–
50/100
SA
LPA
LPD
BPA
BPD
HPD
HPA/NA
INV D
INV A
20
18
17
TO R13
fCLK
≤7MHz
TO V +
16
15
R44
14
R34
13
R24
–5V TO –8V
0.1µF
VOUT
R31 = 14.3k
R32 = 22.1k
R33 = 24.3k
R34 = 13.3k
WIDEBAND NOISE = 70µVRMS
–45
–60
–75
–90
–105
10k
VS = ±8V
fCLK = 4.5MHz
fCLK = 50% DUTY CYCLE
f–3dB = 70kHz
100k
INPUT FREQUENCY (Hz)
1M
1064 TA18
R14
RESISTOR VALUES:
R11 = 34.8k R21 = 34.8k
R12 = 10.5k R22 = 45.3k
R13 = 12.7k R23 = 34.8k
R14 = 20k
R24 = 34.8k
14
R22
LPB
CLK
0
23
BPC
LTC1064
15
24
BPB
V+
1M
1064 TA15
GAIN (dB)
R21
100k
INPUT FREQUENCY (Hz)
1064 TA16
R12
VIN1
VS = ±8V
fCLK = 7MHz
–90
R41 = 10k
R42 = 10k
R43 = 40k
R44 = 10k
8th Order Linear Phase (Bessel) Filter with
1
–60
–75
VOUT2
WIDEBAND NOISE = 64µVRMS
R11
–45
R41 = 40.2k
R42 = 39.2k
R43 = 20k
R44 = 20k
1064 TA17
LTC1064
U
TYPICAL APPLICATIONS
Amplitude Response
Dual 5th Order Chebyshev Lowpass Filter with
50kHz and 100kHz Cutoff Frequencies
15
PASSBAND RIPPLE = 0.2dB
R14
0
R13b
VIN2
C2
1000pF
1
R23
2
R33
3
R43
4
5
2pF
6
7
8V
22pF
0.1µF
8
9
R41
R11a
R11b
VIN1
10
R31
11
R21
12
INV C
INV B
HPB/NB
HPC/NC
BPC
BPB
LPB
LPC
SB
SC
AGND
V–
V+
LTC1064
SA
CLK
50/100
LPA
LPD
BPA
BPD
HPA/NA
HPD
INV A
INV D
24
23
R24
22
R34
21
R44
– 15
4pF
VOUT2
fC = 100kHz
20
19
18
17
–30
GAIN (dB)
R13a
–45
–60
–8V
5MHz
T 2L
16
R42
15
R32
14
R22
13
C1
1000pF
–75
0.1µF
R12
–90
VOUT1
fC = 50kHz
–105
10k
50k 100k
INPUT FREQUENCY (Hz)
39pF
RESISTOR VALUES:
R11a = 4.32k R21 = 11.8k
R11b = 27.4k R22 = 20k
R12 = 10.5k R23 = 11.8k
R13a = 3k
R24 = 20k
R13b = 29.4k
R14 = 10.5k
1M
1064 TA20
R31 = 29.4k
R32 = 21.5k
R33 = 29.4k
R34 = 21.6k
R41 = 10k
R42 = 31.6k
R43 = 10k
R44 = 31.6k
1064 TA19
Clock-Tunable, 30kHz to 90kHz 8th Order Notch
Filter Providing Notch Depth in Excess of 60dB
R13
C2
R14
R22
2
R32
3
R42
4
5
6
C1
7
8V
0.1µF
8
R12
9
R31
10
R21
11
R11
12
VIN1
INV C
INV B
HPB/NB
HPC/NC
BPB
BPC
LPB
LPC
SB
SC
AGND
V–
V+
LTC1064
SA
CLK
50/100
LPA
LPD
BPA
BPD
HPA/NA
HPD
INV A
INV D
10
23
R23
0
22
R33
–10
R31 = 50k
R32 = 88.7k
R33 = 100k
R34 = 63.4k
R42 = 48.7k
–30
0.1µF
20
19
BW
–20
21
–8V
18
fCLK ≤ 5MHz
17
–40
–50
–60
–70
C3
–80
16
–90
15
R44
C1 = C2 = C3 = 15pF
14
R34
THE NOTCH DEPTH FROM
5kHz TO 30kHz IS 50dB
13
R24
R G = 68.1k
R L4 = 10k (0.1%)
R H4 = 10k (0.1%)
R44 = 12.4k
VS = ±8V
fCLK = 4MHz
–100
–110
10
WIDEBAND NOISE = 300µVRMS
RL4
0.1%
RH4
0.1%
RESISTOR VALUES:
R11 = 50k
R21 = 5k
R12 = 15.4k R22 = 10k
R13 = 10k
R23 = 10k
R14 = 9.09k R24 = 10k
Amplitude Response
24
GAIN (dB)
1
20
30
40
50
60
INPUT FREQUENCY (kHz)
RG
70
1064 TA22
–
LT1056
VOUT
+
1064 TA21
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENT
LTC1061
Triple Universal Filter Building Block
Three Filter Building Blocks in a 20-Pin Package
LTC1164
Low Power, Quad Universal Filter Building Block
Low Noise, Low Power Pin-for-Pin LTC1064 Compatible
LTC1264
High Speed, Quad Universal Building Block
Up to 250kHz Center Frequency
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
15
LTC1064
U
PACKAGE DESCRIPTION
Dimension in inches (millimeters) unless otherwise noted.
1.290
(32.77)
MAX
CORNER LEADS OPTION
(4 PLCS)
24
22
21
20
19
18
17
16
15
14
13
2
3
4
5
6
7
8
9
10
11
12
0.220 – 0.310 0.025
(5.588 – 7.874) (0.635)
RAD TYP
0.023 – 0.045
(0.584 – 1.143)
HALF LEAD
OPTION
J Package
24-Lead Ceramic DIP
23
0.045 – 0.068
(1.143 – 1.727)
FULL LEAD
OPTION
1
0.005
(0.127)
MIN
0.300 BSC
(0.762 BSC)
0.200
(5.080)
MAX
0.015 – 0.060
(0.381 – 1.524)
0.008 – 0.018
(0.203 – 0.457)
0° – 15°
0.385 ± 0.025
(9.779 ± 0.635)
0.045 – 0.068
(1.143 – 1.727)
0.125
(3.175)
MIN
0.100 ± 0.010
(2.540 ± 0.254)
0.014 – 0.026
(0.360 – 0.660)
NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE OR TIN PLATE LEADS.
J24 0695
1.265*
(32.131)
24
23
22
21
20
19
18
17
16
15
14
13
1
2
3
4
5
6
7
8
9
10
11
12
0.255 ± 0.015*
(6.477 ± 0.381)
N Package
24-Lead Plastic DIP
0.300 – 0.325
(7.620 – 8.255)
0.130 ± 0.005
(3.302 ± 0.127)
0.045 – 0.065
(1.143 – 1.651)
0.015
(0.381)
MIN
0.009 – 0.015
(0.229 – 0.381)
0.065
(1.651)
TYP
0.125
(3.175)
MIN
0.005
(0.127)
MIN
+0.635
8.255
0.100 ± 0.010
–0.381
(2.540 ± 0.254)
*THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.010 INCH (0.254mm)
(
+0.025
0.325 –0.015
)
24
NOTE:
1. PIN 1 IDENT, NOTCH ON TOP AND CAVITIES ON THE BOTTOM
OF PACKAGES ARE THE MANUFACTURING OPTIONS.
THE PART MAY BE SUPPLIED WITH OR WITHOUT ANY OF
THE OPTIONS.
23
22
21
0.018 ± 0.003
(0.457 ± 0.076)
N24 0695
0.598 – 0.614
(15.190 – 15.600)
(NOTE 2)
20 19 18 17 16
15
14
13
0.394 – 0.419
(10.007 – 10.643)
NOTE 1
* DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH
SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE
SW Package
24-Lead Plastic SO
** DIMENSION DOES NOT INCLUDE INTERLEAD FLASH.
INTERLEAD FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE
0.291 – 0.299
(7.391 – 7.595)
(NOTE 2)
0.010 – 0.029 × 45°
(0.254 – 0.737)
1
2
3
0.093 – 0.104
(2.362 – 2.642)
4
5
6
7
8
9
10
11
12
0.037 – 0.045
(0.940 – 1.143)
0° – 8° TYP
0.009 – 0.013
(0.229 – 0.330)
NOTE 1
0.016 – 0.050
(0.406 – 1.270)
16
Linear Technology Corporation
0.050
(1.270)
TYP
0.014 – 0.019
(0.356 – 0.482)
0.004 – 0.012
(0.102 – 0.305)
SW24 0695
LT/GP 0895 2K REV A • PRINTED IN USA
1630 McCarthy Blvd., Milpitas, CA 95035-7487
(408) 432-1900 ● FAX: (408) 434-0507 ● TELEX: 499-3977
 LINEAR TECHNOLOGY CORPORATION 1989