ON MC33033PG Brushless dc motor controller Datasheet

MC33033, NCV33033
Brushless DC
Motor Controller
The MC33033 is a high performance second generation, limited
feature, monolithic brushless dc motor controller which has evolved
from ON Semiconductor’s full featured MC33034 and MC33035
controllers. It contains all of the active functions required for the
implementation of open loop, three or four phase motor control. The
device consists of a rotor position decoder for proper commutation
sequencing, temperature compensated reference capable of supplying
sensor power, frequency programmable sawtooth oscillator, fully
accessible error amplifier, pulse width modulator comparator, three
open collector top drivers, and three high current totem pole bottom
drivers ideally suited for driving power MOSFETs. Unlike its
predecessors, it does not feature separate drive circuit supply and
ground pins, brake input, or fault output signal.
Included in the MC33033 are protective features consisting of
undervoltage lockout, cycle−by−cycle current limiting with a
selectable time delayed latched shutdown mode, and internal thermal
shutdown.
Typical motor control functions include open loop speed, forward or
reverse direction, and run enable. The MC33033 is designed to operate
brushless motors with electrical sensor phasings of 60°/300° or
120°/240°, and can also efficiently control brush dc motors.
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PDIP−20
P SUFFIX
CASE 738
20
1
SO−20L
DW SUFFIX
CASE 751D
20
1
PIN CONNECTIONS
Features
•
•
•
•
•
•
•
•
•
•
•
10 to 30 V Operation
Undervoltage Lockout
6.25 V Reference Capable of Supplying Sensor Power
Fully Accessible Error Amplifier for Closed Loop Servo
Applications
High Current Drivers Can Control External 3−Phase MOSFET
Bridge
Cycle−By−Cycle Current Limiting
Internal Thermal Shutdown
Selectable 60°/300° or 120°/240° Sensor Phasings
Also Efficiently Control Brush DC Motors with External MOSFET
H−Bridge
NCV Prefix for Automotive and Other Applications Requiring Site
and Control Changes
Pb−Free Packages are Available
Top Drive
Output
BT 1
20 CT
AT 2
19 Output Enable
Fwd/Rev
3
18 60°/120° Select
SA
4
17 AB
SB
5
16 BB
SC
6
15 CB
Reference Output
7
14 VCC
Oscillator
8
13 Gnd
Sensor
Inputs
Error Amp
9
Non Inverting Input
Error Amp 10
Inverting Input
Bottom
Drive
Outputs
12 Current Sense
Non Inverting Input
11 Error Amp Out/
PWM Input
(Top View)
ORDERING INFORMATION
See detailed ordering and shipping information in the package
dimensions section on page 25 of this data sheet.
DEVICE MARKING INFORMATION
See general marking information in the device marking
section on page 25 of this data sheet.
© Semiconductor Components Industries, LLC, 2007
January, 2007 − Rev. 9
1
Publication Order Number:
MC33033/D
MC33033, NCV33033
VM
N
S
S
N
Rotor
Position
Decoder
FWR/REV
60°/120°
Motor
Enable
Undervoltage
VCC
Output
Buffers
Lockout
Reference
Regulator
Speed
Set
Error Amp
Thermal
Shutdown
Faster
RT
PWM
R
Q
S
Oscillator
S
CT
Q
R
Current Sense
This device contains 266 active transistors.
Figure 1. Representative Schematic Diagram
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2
MC33033, NCV33033
MAXIMUM RATINGS
Rating
Power Supply Voltage
Digital Inputs (Pins 3, 4, 5, 6, 18, 19)
Oscillator Input Current (Source or Sink)
Symbol
Value
Unit
VCC
30
V
−
Vref
V
IOSC
30
mA
(Pins 9, 10, Note 1)
VIR
−0.3 to Vref
V
(Source or Sink, Note 2)
IOut
10
mA
Current Sense Input Voltage Range
VSense
−0.3 to 5.0
V
Top Drive Voltage (Pins 1, 2, 20)
VCE(top)
40
V
Top Drive Sink Current (Pins 1, 2, 20)
ISink(top)
50
mA
IDRV
100
mA
−
−
−
2000
200
2000
V
V
V
PD
RθJA
867
75
mW
°C/W
PD
RθJA
619
105
mW
°C/W
TJ
150
°C
TA
−40 to + 85
−40 to +125
°C
Tstg
−65 to +150
°C
Error Amp Input Voltage Range
Error Amp Output Current
Bottom Drive Output Current
(Source or Sink, Pins 15,16, 17)
Electrostatic Discharge Sensitivity (ESD)
Human Body Model (HBM) Class 2, JESD22 A114−C
Machine Model (MM) Class A, JESD22 A115−A
Charged Device Model (CDM), JESD22 C101−C
Power Dissipation and Thermal Characteristics
P Suffix, Dual−In−Line, Case 738
Maximum Power Dissipation @ TA = 85°C
Thermal Resistance, Junction−to−Air
DW Suffix, Surface Mount, Case 751D
Maximum Power Dissipation @ TA = 85°C
Thermal Resistance, Junction−to−Air
Operating Junction Temperature
Operating Ambient Temperature Range (Note 3)
MC33033
NCV33033
Storage Temperature Range
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the
Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect
device reliability.
1. The input common mode voltage or input signal voltage should not be allowed to go negative by more than 0.3 V.
2. The compliance voltage must not exceed the range of − 0.3 to Vref.
3. NCV33033: Tlow = −40°C, Thigh = 125°C. Guaranteed by design. NCV prefix is for automotive and other applications requiring site and change
control.
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3
MC33033, NCV33033
ELECTRICAL CHARACTERISTICS (VCC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.)
Characteristic
Symbol
Min
Typ
Max
5.9
5.82
6.24
−
6.5
6.57
Unit
REFERENCE SECTION
Reference Output Voltage (Iref = 1.0 mA)
TA = 25°C
(Note 4)
Vref
V
Line Regulation (VCC = 10 V to 30 V, Iref = 1.0 mA)
Regline
−
1.5
30
mV
Load Regulation (Iref = 1.0 mA to 20 mA)
Regload
−
16
30
mV
Output Short−Circuit Current (Note 5)
ISC
40
75
−
mA
Reference Under Voltage Lockout Threshold
Vth
4.0
4.5
5.0
V
Input Offset Voltage (Note 4)
VIO
−
0.4
10
mV
Input Offset Current (Note 4)
IIO
−
8.0
500
nA
Input Bias Current (Note 4)
IIB
−
−46
−1000
nA
80
−
dB
ERROR AMPLIFIER
Input Common Mode Voltage Range
VICR
Open Loop Voltage Gain (VO = 3.0 V, RL = 15 k)
AVOL
70
Input Common Mode Rejection Ratio
CMRR
55
86
−
dB
Power Supply Rejection Ratio (VCC = 10 V to 30 V)
PSRR
65
105
−
dB
VOH
VOL
4.6
−
5.3
0.5
−
1.0
Output Voltage Swing
High State (RL = 15 k to Gnd)
Low State (RL = 17 k to Vref)
(0 V to Vref)
V
V
4. MC33033: TA = −40°C to + 85°C; NCV33033: TA = −40°C to +125°C.
5. Maximum package power dissipation limits must be observed.
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4
MC33033, NCV33033
ELECTRICAL CHARACTERISTICS (continued) (VCC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.)
Characteristic
Symbol
Min
Typ
Max
Unit
fOSC
22
25
28
kHz
OSCILLATOR SECTION
Oscillator Frequency
ΔfOSC/ΔV
−
0.01
5.0
%
Sawtooth Peak Voltage
VOSC(P)
−
4.1
4.5
V
Sawtooth Valley Voltage
VOSC(V)
1.2
1.5
−
V
Input Threshold Voltage (Pins 3, 4, 5, 6, 18, 19)
High State
Low State
VIH
VIL
3.0
−
2.2
1.7
−
0.8
Sensor Inputs (Pins 4, 5, 6)
High State Input Current (VIH = 5.0 V)
Low State Input Current (VIL = 0 V)
IIH
IIL
−150
−600
−70
−337
−20
−150
Frequency Change with Voltage (VCC = 10 V to 30 V)
LOGIC INPUTS
V
μA
μA
Forward/Reverse, 60°/120° Select and Output Enable
(Pins 3, 18, 19)
High State Input Current (VIH = 5.0 V)
Low State Input Current (VIL = 0 V)
IIH
IIL
−75
−300
−36
−175
−10
−75
Vth
85
101
115
VICR
−
3.0
−
V
IIB
−
−0.9
−5.0
μA
Top Drive Output Sink Saturation (ISink = 25 mA)
VCE(sat)
−
0.5
1.5
V
Top Drive Output Off−State Leakage (VCE = 30 V)
IDRV(leak)
−
0.06
100
μA
tr
tf
−
−
107
26
300
300
VOH
VOL
(VCC − 2.0)
−
(VCC − 1.1)
1.5
−
2.0
tr
tf
−
−
38
30
200
200
Vth(on)
VH
8.2
0.1
8.9
0.2
10
0.3
ICC
−
15
22
CURRENT−LIMIT COMPARATOR
Threshold Voltage
Input Common Mode Voltage Range
Input Bias Current
mV
OUTPUTS AND POWER SECTIONS
Top Drive Output Switching Time (CL = 47 pF, RL = 1.0 k)
Rise Time
Fall Time
ns
Bottom Drive Output Voltage
High State (VCC = 30 V, Isource = 50 mA)
Low State (VCC = 30 V, Isink = 50 mA)
V
Bottom Drive Output Switching Time (CL = 1000 pF)
Rise Time
Fall Time
ns
Under Voltage Lockout
Drive Output Enabled (VCC Increasing)
Hysteresis
V
Power Supply Current
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5
mA
Δf OSC, OSCILLATOR FREQUENCY CHANGE (%)
MC33033, NCV33033
f OSC, OSCILLATOR FREQUENCY (kHz)
100
VCC = 20 V
TA = 25°C
10
CT = 10 nF
CT = 100 nF
0
1.0
10
CT = 1.0 nF
100
1000
4.0
VCC = 20 V
RT = 4.7 k
CT = 10 nF
2.0
0
− 2.0
− 4.0
− 55
− 25
0
RT, TIMING RESISTOR (kΩ)
48
40
80
32
100
Phase
120
140
16
VCC = 20 V
VO = 3.0 V
0 RL = 15 k
C = 100 pF
− 8.0 T L = 25°C
A
−16
− 24
1.0 k
10 k
160
Gain
180
200
220
100 k
240
10M
1.0 M
Vsat , OUTPUT SATURATION VOLTAGE (V)
40
60
φ, EXCESS PHASE (DEGREES)
AVOL, OPEN−LOOP VOLTAGE GAIN (dB)
56
8.0
0
− 0.8
100
125
Vref
VCC = 20 V
TA = 25°C
Source Saturation
(Load to Ground)
1.6
0.8
0
0
Figure 4. Error Amp Open Loop Gain and
Phase versus Frequency
Gnd
1.0
Sink Saturation
(Load to Vref)
2.0
3.0
4.0
IO, OUTPUT LOAD CURRENT (mA)
Figure 5. Error Amp Output Saturation
Voltage versus Load Current
AV = +1.0
No Load
TA = 25°C
VO, OUTPUT VOLTAGE (V)
VO, OUTPUT VOLTAGE (V)
75
−1.6
f, FREQUENCY (Hz)
3.05
50
Figure 3. Oscillator Frequency Change
versus Temperature
Figure 2. Oscillator Frequency versus
Timing Resistor
24
25
TA, AMBIENT TEMPERATURE (°C)
3.0
2.95
AV = +1.0
No Load
TA = 25°C
4.5
3.0
1.5
1.0 μs/DIV
5.0 μs/DIV
Figure 6. Error Amp Small−Signal
Transient Response
Figure 7. Error Amp Large−Signal
Transient Response
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5.0
Vref, REFERENCE OUTPUT VOLTAGE (V)
0
− 4.0
− 8.0
− 12
− 16
VCC = 20 V
TA = 25°C
− 20
− 24
0
10
20
30
40
50
60
7.0
6.0
5.0
4.0
3.0
2.0
No Load
TA = 25°C
1.0
0
0
10
20
30
40
Iref, REFERENCE OUTPUT SOURCE CURRENT (mA)
VCC, SUPPLY VOLTAGE (V)
Figure 8. Reference Output Voltage Change
versus Output Source Current
Figure 9. Reference Output Voltage versus
Supply Voltage
100
40
OUTPUT DUTY CYCLE (%)
ΔVref, NORMALIZED REFERENCE VOLTAGE CHANGE (mV)
Δ Vref, REFERENCE OUTPUT VOLTAGE CHANGE (mV)
MC33033, NCV33033
20
0
− 20
VCC = 20 V
No Load
VCC = 20 V
RT = 4.7 k
CT = 10 nF
TA = 25°C
80
60
40
20
− 40
0
− 55
− 25
0
25
50
75
TA, AMBIENT TEMPERATURE (°C)
100
125
0
Vsat , OUTPUT SATURATION VOLTAGE (V)
t HL , BOTTOM DRIVE RESPONSE TIME (ns)
VCC = 20 V
RL = 1
CL = 1.0 nF
TA = 25°C
100
50
0
1.0
2.0
3.0
4.0
3.0
4.0
5.0
Figure 11. Output Duty Cycle versus
PWM Input Voltage
250
150
2.0
PWM INPUT VOLTAGE (V)
Figure 10. Reference Output Voltage
versus Temperature
200
1.0
5.0 6.0 7.0 8.0 9.0 10
1.2
VCC = 20 V
TA = 25°C
0.8
0.4
0
0
VSense, CURRENT SENSE INPUT VOLTAGE (NORMALIZED TO Vth)
Figure 12. Bottom Drive Response Time versus
Current Sense Input Voltage
10
20
30
ISink, SINK CURRENT (mA)
40
Figure 13. Top Drive Output Saturation Voltage
versus Sink Current
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MC33033, NCV33033
100
OUTPUT VOLTAGE (%)
VCC = 20 V
RL = 1.0 k
CL = 15 pF
TA = 25°C
0
50 ns/DIV
50 ns/DIV
Figure 14. Top Drive Output Waveform
Figure 15. Bottom Drive Output Waveform
VCC = 20 V
CL = 15 pF
TA = 25°C
0
VCC
−1.0
0
50 ns/DIV
Source Saturation
(Load to Ground)
VCC = 20 V
TA = 25°C
− 2.0
Sink Saturation
(Load to VCC)
2.0
1.0
Gnd
0
0
40
20
60
IO, OUTPUT LOAD CURRENT (mA)
Figure 16. Bottom Drive Output Waveform
Figure 17. Bottom Drive Output Saturation
Voltage versus Load Current
20
I CC, POWER SUPPLY CURRENT (mA)
OUTPUT VOLTAGE (%)
0
100
Vsat, OUTPUT SATURATION VOLTAGE (V)
OUTPUT VOLTAGE (%)
100
VCC = 20 V
CL = 1.0 nF
TA = 25°C
18
16
14
12
10
RT = 4.7 k
CT = 10 nF
Pins 3−6, 12, 13 = Gnd
Pins 18, 19 = Open
TA = 25°C
8.0
6.0
4.0
2.0
0
0
5.0
10
15
20
25
VCC, SUPPLY VOLTAGE (V)
Figure 18. Supply Current versus Voltage
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30
80
MC33033, NCV33033
PIN FUNCTION DESCRIPTION
Pin
Symbol
Description
1, 2, 20
BT, AT, CT
These three open collector Top Drive Outputs are designed to drive the external upper
power switch transistors.
3
Fwd//Rev
The Forward/Reverse Input is used to change the direction of motor rotation.
SA, SB, SC
These three Sensor Inputs control the commutation sequence.
7
Reference Output
This output provides charging current for the oscillator timing capacitor CT and a
reference for the Error Amplifier. It may also serve to furnish sensor power.
8
Oscillator
The Oscillator frequency is programmed by the values selected for the timing
components, RT and CT.
9
Error Amp Noninverting Input
This input is normally connected to the speed set potentiometer.
10
Error Amp Inverting Input
This input is normally connected to the Error Amp Output in open loop applications.
4, 5, 6
11
Error Amp Out/PWM Input
This pin is available for compensation in closed loop applications.
12
Current Sense Noninverting Input
A 100 mV signal, with respect to Pin 13, at this input terminates output switch
conduction during a given oscillator cycle. This pin normally connects to the top side
of the current sense resistor.
13
Gnd
This pin supplies a separate ground return for the control circuit and should be
referenced back to the power source ground.
14
VCC
This pin is the positive supply of the control IC. The controller is functional over a VCC
range of 10 to 30 V.
CB, BB, AB
These three totem pole Bottom Drive Outputs are designed for direct drive of the
external bottom power switch transistors.
18
60°/120° Select
The electrical state of this pin configures the control circuit operation for either 60°
(high state) or 120° (low state) sensor electrical phasing inputs.
19
Output Enable
A logic high at this input causes the motor to run, while a low causes it to coast.
15, 16, 17
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MC33033, NCV33033
INTRODUCTION
The Forward/Reverse input (Pin 3) is used to change the
direction of motor rotation by reversing the voltage across
the stator winding. When the input changes state, from high
to low with a given sensor input code (for example 100), the
enabled top and bottom drive outputs with the same alpha
designation are exchanged (AT to AB, BT to BB, CT to CB).
In effect the commutation sequence is reversed and the
motor changes directional rotation.
Motor on/off control is accomplished by the Output
Enable (Pin19). When left disconnected, an internal pull−up
resistor to a positive source enables sequencing of the top
and bottom drive outputs. When grounded, the Top Drive
Outputs turn off and the bottom drives are forced low,
causing the motor to coast.
The commutation logic truth table is shown in Figure 20.
In half wave motor drive applications, the Top Drive
Outputs are not required and are typically left disconnected.
The MC33033 is one of a series of high performance
monolithic dc brushless motor controllers produced by
ON Semiconductor. It contains all of the functions required
to implement a limited−feature, open loop, three or four
phase motor control system. Constructed with Bipolar
Analog technology, it offers a high degree of performance
and ruggedness in hostile industrial environments. The
MC33033 contains a rotor position decoder for proper
commutation sequencing, a temperature compensated
reference capable of supplying sensor power, a frequency
programmable sawtooth oscillator, a fully accessible error
amplifier, a pulse width modulator comparator, three open
collector top drive outputs, and three high current totem pole
bottom driver outputs ideally suited for driving power
MOSFETs.
Included in the MC33033 are protective features
consisting of undervoltage lockout, cycle−by−cycle current
limiting with a latched shutdown mode, and internal thermal
shutdown.
Typical motor control functions include open loop speed
control, forward or reverse rotation, and run enable. In
addition, the MC33033 has a 60°/120° select pin which
configures the rotor position decoder for either 60° or 120°
sensor electrical phasing inputs.
Error Amplifier
A high performance, fully compensated Error Amplifier
with access to both inputs and output (Pins 9, 10, 11) is
provided to facilitate the implementation of closed loop
motor speed control. The amplifier features a typical dc
voltage gain of 80 dB, 0.6 MHz gain bandwidth, and a wide
input common mode voltage range that extends from ground
to Vref. In most open loop speed control applications, the
amplifier is configured as a unity gain voltage follower with
the Noninverting Input connected to the speed set voltage
source. Additional configurations are shown in Figures 30
through 34.
FUNCTIONAL DESCRIPTION
A representative internal block diagram is shown in
Figure 19, with various applications shown in Figures 35,
37, 38, 42, 44, and 45. A discussion of the features and
function of each of the internal blocks given below and
referenced to Figures 19 and 37.
Oscillator
The frequency of the internal ramp oscillator is
programmed by the values selected for timing components
RT and CT. Capacitor CT is charged from the Reference
Output (Pin 7) through resistor RT and discharged by an
internal discharge transistor. The ramp peak and valley
voltages are typically 4.1 V and 1.5 V respectively. To
provide a good compromise between audible noise and
output switching efficiency, an oscillator frequency in the
range of 20 to 30 kHz is recommended. Refer to Figure 2 for
component selection.
Rotor Position Decoder
An internal rotor position decoder monitors the three
sensor inputs (Pins 4, 5, 6) to provide the proper sequencing
of the top and bottom drive outputs. The Sensor Inputs are
designed to interface directly with open collector type Hall
Effect switches or opto slotted couplers. Internal pull−up
resistors are included to minimize the required number of
external components. The inputs are TTL compatible, with
their thresholds typically at 2.2 V. The MC33033 series is
designed to control three phase motors and operate with four
of the most common conventions of sensor phasing. A
60°/120° Select (Pin 18) is conveniently provided which
affords the MC33033 to configure itself to control motors
having either 60°, 120°, 240° or 300° electrical sensor
phasing. With three Sensor Inputs there are eight possible
input code combinations, six of which are valid rotor
positions. The remaining two codes are invalid and are
usually caused by an open or shorted sensor line. With six
valid input codes, the decoder can resolve the motor rotor
position to within a window of 60 electrical degrees.
Pulse Width Modulator
The use of pulse width modulation provides an energy
efficient method of controlling the motor speed by varying
the average voltage applied to each stator winding during the
commutation sequence. As CT discharges, the oscillator sets
both latches, allowing conduction of the Top and Bottom
Drive Outputs. The PWM comparator resets the upper latch,
terminating the Bottom Drive Output conduction when the
positive−going ramp of CT becomes greater than the Error
Amplifier output. The pulse width modulator timing
diagram is shown in Figure 21. Pulse width modulation for
speed control appears only at the Bottom Drive Outputs.
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MC33033, NCV33033
VM
Sensor Inputs
SA
4
SB
5
SC
20 k
AT
6
20 k
20 k
Top
Drive
Outputs
BT
40 k
18
60°/120° Select
1
Rotor
Position
Decoder
40 k
3
Forward/Revers
e
2
20
19
Output Enable
VCC
40 k
CT
Undervoltage
14
Lockout
Reference
Regulator
Reference Output
8.9 V
17
7
AB
4.5 V
Noninv. Input
Faster
RT
9
Error Amp
11
PWM
Error Amp Out
PWM Input
8
CT
Sink Only
Positive True
= Logic With
Hysteresis
16
Thermal
Shutdown
10
Oscillator
Latch
R
Q
S
Latch
S
Q
R
15
ILimit
100 mV
13
Gnd
Figure 19. Representative Block Diagram
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11
12
BB
Bottom
Drive
Outputs
CB
Current Sense
Input
MC33033, NCV33033
Inputs (Note 2)
Outputs (Note 3)
Sensor Electrical Phasing (Note 4)
Top Drives
Bottom Drives
SA
60°
SB
SC
SA
120°
SB
SC
F/R
Enable
Current
Sense
AT
BT
CT
AB
BB
CB
1
1
1
0
0
0
0
1
1
1
0
0
0
0
1
1
1
0
1
1
0
0
0
1
0
1
1
1
0
0
0
0
0
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
1
1
1
1
0
1
0
0
1
1
1
1
1
1
0
0
1
0
0
1
1
0
0
0
0
0
0
1
1
1
1
0
0
0
0
(Note 5)
F/R = 1
1
1
1
0
0
0
0
1
1
1
0
0
0
0
1
1
1
0
1
1
0
0
0
1
0
1
1
1
0
0
0
0
0
1
1
1
0
0
0
0
0
0
1
1
1
1
1
1
0
0
0
0
0
0
1
1
0
0
1
1
1
1
1
1
0
0
0
0
1
1
1
1
1
0
0
0
0
1
0
1
1
0
0
0
0
0
0
1
1
0
(Note 5)
F/R = 0
1
0
0
1
1
0
1
0
1
0
1
0
X
X
X
X
X
X
1
1
1
1
1
1
0
0
0
0
0
0
(Note 6)
V
V
V
V
V
V
X
0
X
1
1
1
0
0
0
(Note 7)
V
V
V
V
V
V
X
1
1
1
1
1
0
0
0
(Note 8)
NOTES: 1. V = Any one of six valid sensor or drive combinations.
X = Don’t care.
2. The digital inputs (Pins 3, 4, 5, 6, 18, 19) are all TTL compatible. The current sense input (Pin 12) has a 100 mV threshold with respect to Pin 13. A
logic 0 for this input is defined as < 85 mV, and a logic 1 is > 115 mV.
3. The top drive outputs are open collector design and active in the low (0) state.
4. With 60°/120° (Pin 18) in the high (1) state, configuration is for 60° sensor electrical phasing inputs. With Pin 18 in the low (0) state, configuration is
for 120° sensor electrical phasing inputs.
5. Valid 60° or 120° sensor combinations for corresponding valid top and bottom drive outputs.
6. Invalid sensor inputs; All top and bottom drives are off.
7. Valid sensor inputs with enable = 0; All top and bottom drives are off.
8. Valid sensor inputs with enable and current sense = 1; All top and bottom drives are off.
Figure 20. Three Phase, Six Step Commutation Truth Table (Note 1)
Current Limit
Reference
Continuous operation of a motor that is severely
over−loaded results in overheating and eventual failure.
This destructive condition can best be prevented with the use
of cycle−by−cycle current limiting. That is, each on−cycle
is treated as a separate event. Cycle−by−cycle current
limiting is accomplished by monitoring the stator current
build−up each time an output switch conducts, and upon
sensing an over current condition, immediately turning off
the switch and holding it off for the remaining duration of
oscillator ramp−up period. The stator current is converted to
a voltage by inserting a ground−referenced sense resistor RS
(Figure 35) in series with the three bottom switch transistors
(Q4, Q5, Q6). The voltage developed across the sense
resistor is monitored by the current sense input (Pin 12), and
compared to the internal 100 mV reference. If the current
sense threshold is exceeded, the comparator resets the lower
latch and terminates output switch conduction. The value for
the sense resistor is:
The on−chip 6.25 V regulator (Pin 7) provides charging
current for the oscillator timing capacitor, a reference for the
Error Amplifier, and can supply 20 mA of current suitable
for directly powering sensors in low voltage applications. In
higher voltage applications it may become necessary to
transfer the power dissipated by the regulator off the IC. This
is easily accomplished with the addition of an external pass
transistor as shown in Figure 22. A 6.25 V reference level
was chosen to allow implementation of the simpler NPN
circuit, where Vref − VBE exceeds the minimum voltage
required by Hall Effect sensors over temperature. With
proper transistor selection, and adequate heatsinking, up to
one amp of load current can be obtained.
R +
S
I
Undervoltage Lockout
A dual Undervoltage Lockout has been incorporated to
prevent damage to the IC and the external power switch
transistors. Under low power supply conditions, it
guarantees that the IC and sensors are fully functional, and
that there is sufficient Bottom Drive Output voltage. The
positive power supply to the IC (VCC) is monitored to a
threshold of 8.9 V. This level ensures sufficient gate drive
necessary to attain low RDS(on) when interfacing with
standard power MOSFET devices. When directly powering
the Hall sensors from the reference, improper sensor
0.1
stator(max)
The dual−latch PWM configuration ensures that only one
single output conduction pulse occurs during any given
oscillator cycle, whether terminated by the output of the
Error Amplifier or the current limit comparator.
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12
MC33033, NCV33033
operation can result if the reference output voltage should
fall below 4.5 V. If one or both of the comparators detects an
undervoltage condition, the top drives are turned off and the
Bottom Drive Outputs are held in a low state. Each of the
comparators contain hysteresis to prevent oscillations when
crossing their respective thresholds.
Capacitor CT
UVLO
14
Vin
REF
Error Amp Out/
PWM Input
7
MPS
U01A
To
Control
Sensor
Power Circuitry
≈5.6 V 6.25 V
Current Sense
Input
Latch Set"
Inputs
Vin
36
REF
MPS
U51A
Top Drive
Outputs
UVLO
14
7
0.1
Bottom Drive
Outputs
To Control Circuitry
and Sensor Power
6.25 V
The NPN circuit is recommended for powering Hall or opto sensors,
where the output voltage temperature coefficient is not critical. The PNP
circuit is slightly more complex, but also more accurate. Neither circuit
has current limiting.
Figure 21. PWM Timing Diagram
Figure 22. Reference Output Buffers
VM
VCC = 12 V
2
Rotor
Position
Decoder
Q2
VCC
AT
1
Q1
2
Q3
Rotor
Position
Decoder
BT
20
CT
AT
1
BT
20
CT
Load
17
16
1.0 k
1
2
VBoost VM = 170 V
6
1.0 M
5
4
4.7 k
1N4744
MOC8204
Optocoupler
17
Q4
16
15
15
Transistor Q1 is a common base stage used to level shift from VCC to the high
motor voltage, VM. The collector diode is required if VCC is present while VM
is low.
Figure 23. High Voltage Interface with
NPN Power Transistors
Figure 24. High Voltage Interface with
N−Channel Power MOSFETs
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Load
MC33033, NCV33033
17
Rg
17
D
16
Rg
16
D
15
Rg
15
D
R
12
12
RS
C
100 mV
100 mV
D = 1N5819
Series gate resistor Rg will damp any high frequency oscillations caused
by the MOSFET input capacitance and any series wiring induction in the
gate−source circuit. Diode D is required if the negative current into the
Bottom Drive Outputs exceeds 50 mA.
The addition of the RC filter will eliminate current−limit
instability caused by the leading edge spike on the current
waveform. Resistor RS should be a low inductance type.
Figure 25. Current Waveform Spike Suppression
Figure 26. MOSFET Drive Precautions
C
D
17
G
17
M
SENSEFET
S
K
C
16
16
C
15
15
IB
12
0
−
100 mV
t
100 mV
13
The totem pole output can furnish negative base current for
enhanced transistor turn−off, with the addition of capacitor C.
7
6
R
5
Q
S
2
3
VBoost Voltage (V)
4
0.001
If : SENSEFET = MPT10N10M
RS = 200 Ω , 1/4 W
Then : V Pin 9 [ 0.75 Ipk
Figure 28. Current Sensing Power MOSFETs
VM + 12
REF
7
VM + 8.0
40 k
19
VM + 4.0
20
40
60
Boost Current (mA)
1.0 μ/200 V
1N5352A
1
Gnd
R @ I pk @ R
S
DS(on)
r DM(on) ) R
S
Virtually lossless current sensing can be achieved with the
implementation of SENSEFET power switches.
Figure 27. Bipolar Transistor Drive
8
V Pin 9 [
RS
Base Charge
Removal
VC = 12 V
Power Ground:
To Input Source Return
12
+
*
*
VA
VB
VBoost
R3
R4
22
MC1455
18 k
R1
VM = 170 V
* = MUR115
V
This circuit generates VBoost for Figure 24.
Figure 29. High Voltage Boost Supply
9
R2
EA
10
11
ǒ
PWM
Ǔ ǒ Ǔ
R ) R4 R
R
+V 3
2 – 4 V
Pin 11
A R )R
R
R3 B
1
2
3
Figure 30. Differential Input Speed Controller
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MC33033, NCV33033
5.0 V
16
11
166 k
10
145 k
9
126 k
7
108 k
19
Q5 6
5
Q4
4
Q3
3
Q2
2
Q1
1
Q
92.3 k
9
VCC Q9
Q8
REF
Enable
R1
Increase
Speed
12
13
40 k
19
P3
BCD
Inputs
P2
14
P1
15
9
SN74LS145
7
Q7
P0
EA
R2
10
C
PWM
11
Gnd
Q6
REF
100 k 7
77.6 k
40 k
EA
10
63.6 k
PWM
11
51.3 k
40.4 k
0
8
Resistor R1 with capacitor C sets the acceleration time constant while R2
controls the deceleration. The values of R1 and R2 should be at least ten times
greater than the speed set potentiometer to minimize time constant variations
with different speed settings.
The SN74LS145 is an open collector BCD to One of Ten decoder. When
connected as shown, input codes 0000 through 1001 steps the PWM in
increments of approximately 10% from 0 to 90% on−time. Input codes 1010
through 1111 will produce 100% on−time or full motor speed.
Figure 31. Controlled Acceleration/Deceleration
Figure 32. Digital Speed Controller
REF
V
7
To Sensor
Input (Pin 4)
0.01
10 k
19
10 k
V +
B
9
100 k
Increase
Speed 10
1.0 M
10 M 11
0.1
40 k
ǒ
ǒ
V ref
R5
R6
EA
Ǔ ǒ Ǔ
R ) R4 R
R
+V 3
2 – 4 V
Pin 11
ref R ) R
R
R3 B
1
2
3
Ǔ
) 1
R1
T
R5
R2
R3
PWM
R 3§§ R6 ø R 6
0.22
The rotor position sensors can be used as a tachometer. By differentiating the
positive−going edges and then integrating them over time, a voltage
proportional to speed can be generated. The error amp compares this voltage
to that of the speed set to control the PWM.
R6
R4
REF
7
40 k
19
9
EA
10
11
PWM
This circuit can control the speed of a cooling fan proportional to the difference
between the sensor and set temperatures. The control loop is closed as the
forced air cools the NTC thermistor. For controlled heating applications,
exchange the positions of R1 and R2.
Figure 33. Closed Loop Speed Control
Figure 34. Closed Loop Temperature Control
Drive Outputs
SYSTEM APPLICATIONS
The three Top Drive Outputs (Pins 1, 2, 20) are open
collector NPN transistors capable of sinking 50 mA with a
minimum breakdown of 30 V. Interfacing into higher
voltage applications is easily accomplished with the circuits
shown in Figures 23 and 24.
The three totem pole Bottom Drive Outputs (Pins 15, 16,
17) are particularly suited for direct drive of N−Channel
MOSFETs or NPN bipolar transistors (Figures 25, 26, 27,
and 28). Each output is capable of sourcing and sinking up
to 100 mA.
Three Phase Motor Commutation
The three phase application shown in Figure 35 is an open
loop motor controller with full wave, six step drive. The
upper power switch transistors are Darlington PNPs while
the lower switches are N−Channel power MOSFETs. Each
of these devices contains an internal parasitic catch diode
that is used to return the stator inductive energy back to the
power supply. The outputs are capable of driving a delta or
wye connected stator, and a grounded neutral wye if split
supplies are used. At any given rotor position, only one top
and one bottom power switch (of different totem poles) is
enabled. This configuration switches both ends of the stator
winding from supply to ground which causes the current
flow to be bidirectional or full wave. A leading edge spike
is usually present on the current waveform and can cause a
current−limit error. The spike can be eliminated by adding
Thermal Shutdown
Internal thermal shutdown circuity is provided to protect
the IC in the event the maximum junction temperature is
exceeded. When activated, typically at 170°C, the IC acts as
though the regulator was disabled, in turn shutting down the
IC.
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MC33033, NCV33033
an RC filter in series with the Current Sense Input. Using a
low inductance type resistor for RS will also aid in spike
reduction. Figure 36 shows the commutation waveforms
over two electrical cycles. The first cycle (0° to 360°) depicts
motor operation at full speed while the second cycle (360°
to 720°) shows a reduced speed with about 50% pulse width
modulation. The current waveforms reflect a constant
torque load and are shown synchronous to the commutation
frequency for clarity.
VM
2
4
Q1
N
A
5
60°/120°
1
Rotor
Position
Decoder
Q2
B
3
18
20
Enable
Q3
19
C
Undervoltage
14
VM
Motor
Lockout
Reference
Regulator
7
Speed
Set
Faster
RT
S
N
6
FWR/REV
S
9
17
Error Amp
16
Thermal
Shutdown
10
11
Q4
Q5
PWM
R
15
Q
Q6
S
8
Oscillator
S
CT
Q
ILimit
R
R
12
C
13
Gnd
Figure 35. Three Phase, Six Step, Full Wave Motor Controller
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RS
MC33033, NCV33033
Rotor Electrical Position (Degrees)
0
60
120
180
240
300
360
420
480
540
600
660
720
SA
Sensor Inputs
60°/120°
Select Pin
Open
SB
SC
Code
100
110
111
011
001
000
100
110
111
011
001
000
100
110
010
011
001
101
100
110
010
011
001
101
Q1 + Q6
Q2 + Q6
SA
Sensor Inputs
60°/120°
Select Pin
Grounded
SB
SC
Code
AT
Top Drive
Outputs
BT
CT
AB
Bottom Drive
Outputs
BB
CB
Conducting
Power Switch
Transistors
Q2 + Q4 Q3 + Q4 Q3 + Q5 Q1 + Q5
Q1 + Q6 Q2 + Q6
Q2 + Q4 Q3 + Q4 Q3 + Q5
+
A
O
−
+
Motor Drive
Current
B
O
−
+
C
O
−
Full Speed (No PWM)
Reduced Speed (≈ 50% PWM)
FWD/REV = 1
Figure 36. Three Phase, Six Step, Full Wave Commutation Waveforms
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17
Q1 + Q5
MC33033, NCV33033
Figure 37 shows a three phase, three step, half wave motor
controller. This configuration is ideally suited for
automobile and other low voltage applications since there is
only one power switch voltage drop in series with a given
stator winding. Current flow is unidirectional or half wave
because only one end of each winding is switched. The stator
flyback voltage is clamped by a single zener and three
diodes.
Motor
2
4
N
S
5
VM
FWR/REV
60°/120°
1
Rotor
Position
Decoder
6
3
18
20
Enable
19
Undervoltage
14
VM
Lockout
Reference
Regulator
7
Speed
Set
Faster
RT
9
17
Error Amp
10
11
PWM
16
Thermal
Shutdown
R
15
Q
S
8
Oscillator
S
CT
Q
ILimit
R
13
12
Gnd
Figure 37. Three Phase, Three Step, Half Wave Motor Controller
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18
S
N
MC33033, NCV33033
Three Phase Closed Loop Controller
The MC33033, by itself, is capable of open loop motor
speed control. For closed loop speed control, the MC33033
requires an input voltage proportional to the motor speed.
Traditionally this has been accomplished by means of a
tachometer to generate the motor speed feedback voltage.
Figure 38 shows an application whereby an MC33039,
powered from the 6.25 V reference (Pin 7) of the MC33033,
is used to generate the required feedback voltage without the
need of a costly tachometer. The same Hall sensor signals
used by the MC33033 for rotor position decoding are
utilized by the MC33039. Every positive or negative going
transition of the Hall sensor signals on any of the sensor lines
causes the MC33039 to produce an output pulse of defined
amplitude and time duration, as determined by the external
resistor R1 and capacitor C1. The resulting output train of
1
8
2
3
pulses present at Pin 5 of the MC33039 are integrated by the
Error Amplifier of the MC33033 configured as an
integrator, to produce a dc voltage level which is
proportional to the motor speed. This speed proportional
voltage establishes the PWM reference level at Pin 11 of the
MC33033 motor controller and completes or closes the
feedback loop. The MC33033 outputs drive a TMOS power
MOSFET 3−phase bridge. High current can be expected
during conditions of start−up and when changing direction
of the motor.
The system shown in Figure 38 is designed for a motor
having 120/240 degrees Hall sensor electrical phasing. The
system can easily be modified to accommodate 60/300
degree Hall sensor electrical phasing by removing the
jumper (J1) at Pin 18 of the MC33033.
1.0 M
R1
7
MC33039
4
6
VM (18 to 30 V)
750 pF
C1
5
1.1 k
1.1 k
330
0.1
1.1 k
1000
TP1
1.0 k
1.0 k
20
1
19
2
F/R
3
18
4
17
6
Speed
Faster
5.1 k
N
Enable
MC33033
J1
470
470
16
470
15
7
14
8
13
9
12
10
11
Motor
1N5819
1N4742
100
0.1
1.0 M
10 k
S
S
N
5
0.01
1.0 k
4.7 k
0.1
33
TP2
0.05/1.0 W
0.1
100 k
Close Loop
Figure 38. Closed Loop Brushless DC Motor Control With the MC33033 Using the MC33039
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19
MC33033, NCV33033
Sensor Phasing Comparison
There are four conventions used to establish the relative
phasing of the sensor signals in three phase motors. With six
step drive, an input signal change must occur every 60
electrical degrees, however, the relative signal phasing is
dependent upon the mechanical sensor placement. A
comparison of the conventions in electrical degrees is shown
in Figure 39. From the sensor phasing table (Figure 40), note
that the order of input codes for 60° phasing is the reverse of
300°. This means the MC33033, when the 60°/120° select
(Pin 18) and the FWD/REV (Pin 3) both in the high state
(open), is configured to operate a 60° sensor phasing motor
in the forward direction. Under the same conditions a 300°
sensor phasing motor would operate equally well but in the
reverse direction. One would simply have to reverse the
FWD/REV switch (FWD/REV closed) in order to cause the
300° motor to also operate in the same direction. The same
difference exists between the 120° and 240° conventions.
In this data sheet, the rotor position has always been given
in electrical degrees since the mechanical position is a
function of the number of rotating magnetic poles. The
relationship between the electrical and mechanical position
is:
ǒ
Electrical Degrees + Mechanical Degrees #Rotor Poles
2
An increase in the number of magnetic poles causes more
electrical revolutions for a given mechanical revolution.
General purpose three phase motors typically contain a four
pole rotor which yields two electrical revolutions for one
mechanical.
Two and Four Phase Motor Commutation
The MC33033 configured for 60° sensor inputs is capable
of providing a four step output that can be used to drive two
or four phase motors. The truth table in Figure 41 shows that
by connecting sensor inputs SB and SC together, it is possible
to truncate the number of drive output states from six to four.
The output power switches are connected to BT, CT, BB, and
CB. Figure 42 shows a four phase, four step, full wave motor
control application. Power switch transistors Q1 through Q8
are Darlington type, each with an internal parasitic catch
diode. With four step drive, only two rotor position sensors
spaced at 90 electrical degrees are required. The
commutation waveforms are shown in Figure 43.
Figure 44 shows a four phase, four step, half wave motor
controller. It has the same features as the circuit in Figure 37,
except for the deletion of speed adjust.
Rotor Electrical Position (Degrees)
0 60 120 180 240 300 360 420 480 540 600 660 720
SA
Sensor Electrical Phasing
60°
SB
SC
SA
120°
SB
SC
SA
240°
SB
MC33033 (60°/120° Select Pin Open)
SC
Inputs
Sensor Electrical
Spacing* = 90°
SA
SB
SA
300°
SB
SC
Figure 39. Sensor Phasing Comparison
Sensor Electrical Phasing (Degrees)
60°
120°
240°
300°
SA
SB
SC
SA
SB
SC
SA
SB
SC
SA
SB
SC
1
0
0
1
0
1
1
1
0
1
1
1
1
1
0
1
0
0
1
0
0
1
1
0
1
1
1
1
1
0
1
0
1
1
0
0
0
1
1
0
1
0
0
0
1
0
0
0
0
0
1
0
1
1
0
1
1
0
0
1
0
0
0
0
0
1
0
1
0
0
1
1
Ǔ
Outputs
Top Drives
Bottom Drives
F/R
BT
CT
BB
CB
1
1
0
0
0
1
1
0
1
1
1
1
1
0
1
1
1
1
0
1
0
0
0
1
1
0
0
0
1
1
0
0
0
1
1
0
0
0
0
0
1
1
1
0
0
1
1
1
0
1
0
0
0
0
1
0
*With MC33033 sensor input SB connected to SC
Figure 41. Two and Four Phase, Four Step,
Commutation Truth Table
Figure 40. Sensor Phasing Table
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20
Figure 42. Four Phase, Four Step, Full Wave Controller
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21
CT
RT
Enable
VM
FWR/REV
8
11
10
9
7
14
19
18
3
6
5
4
Oscillator
PWM
Error Amp
Reference
Regulator
R
S
S
R
13
Thermal
Shutdown
Q
Q
Gnd
Lockout
Undervoltage
Rotor
Position
Decoder
ILimit
12
15
16
17
20
1
2
C
R
Q8
Q4
RS
Q7
Q3
VM
Q6
Q2
Q5
Q1
D
C
B
A
N
S
Motor
S
N
MC33033, NCV33033
MC33033, NCV33033
Rotor Electrical Position (Degrees)
0
90
180
270
360
450
540
630
720
SA
Sensor Inputs
60°/120°
Select Pin
Open
SB
Code
10
10
01
00
10
11
01
00
Q3 + Q5
Q4 + Q6
Q1 + Q7
Q2 + Q8
Q3 + Q5
Q4 + Q6
Q1 + Q7
Q2 + Q8
BT
Top Drive
Outputs
CT
BB
Bottom Drive
Outputs
CB
Conducting
Power Switch
Transistors
+
A O
−
+
B
O
−
+
Motor Drive
Current
C
O
−
+
D
O
−
Full Speed (No PWM)
FWD/REV = 1
Figure 43. Four Phase, Four Step, Full Wave Commutation Waveforms
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22
Figure 44. Four Phase, Four Step, Half Wave Motor Controller
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23
CT
RT
Enable
VM
FWR/REV
8
11
10
9
7
14
19
18
3
6
5
4
Oscillator
PWM
Error Amp
Reference
Regulator
R
S
S
R
13
Thermal
Shutdown
Q
Q
Gnd
Lockout
Undervoltage
Rotor
Position
Decoder
ILimit
12
15
16
17
20
1
2
C
R
RS
VM
Motor
S
N
N
S
MC33033, NCV33033
MC33033, NCV33033
Brush Motor Control
fly, using the normal Forward/Reverse switch, and not have
to completely stop before reversing.
Though the MC33033 was designed to control brushless dc
motors, it may also be used to control dc brush−type motors.
Figure 45 shows an application of the MC33033 driving a
H−bridge affording minimal parts count to operate a
brush−type motor. Key to the operation is the input sensor
code [100] which produces a top−left (Q1) and a bottom−right
(Q3) drive when the controller’s Forward/Reverse pin is at
logic [1]; top−right (Q4), bottom−left (Q2) drive is realized
when the Forward/Reverse pin is at logic [0]. This code
supports the requirements necessary for H−bridge drive
accomplishing both direction and speed control.
The controller functions in a normal manner with a pulse
width modulated frequency of approximately 25 kHz.
Motor speed is controlled by adjusting the voltage presented
to the noninverting input of the Error Amplifier establishing
the PWM′s slice or reference level. Cycle−by−cycle current
limiting of the motor current is accomplished by sensing the
voltage (100 mV threshold) across the RS resistor to ground
of the H−bridge motor current. The over current sense circuit
makes it possible to reverse the direction of the motor, on the
LAYOUT CONSIDERATIONS
Do not attempt to construct any of the motor control
circuits on wire−wrap or plug−in prototype boards. High
frequency printed circuit layout techniques are imperative to
prevent pulse jitter. This is usually caused by excessive noise
pick−up imposed on the current sense or error amp inputs.
The printed circuit layout should contain a ground plane
with low current signal and high drive and output buffer
grounds returning on separate paths back to the power
supply input filter capacitor VM. Ceramic bypass capacitors
(0.01 μF) connected close to the integrated circuit at VCC,
Vref and error amplifier noninverting input may be required
depending upon circuit layout. This provides a low
impedance path for filtering any high frequency noise. All
high current loops should be kept as short as possible using
heavy copper runs to minimize radiated EMI.
+12 V
2
4
5
1.0 k
Rotor
Position
Decoder
6
1
Q 1*
3
FWR/REV
1.0 k
18
20
Q 4*
19
Enable
Undervoltage
14
+12 V
Lockout
0.1
DC Brush
Motor
Reference
Regulator
7
M
Q 2*
17
22
9
10 k
Faster
10 k
Error Amp
10
11
PWM
16
Thermal
Shutdown
R
Q
Q 3*
15
S
8
Oscillator
22
S
Q
0.005
ILimit
R
12
0.001
13
Gnd
Figure 45. H−Bridge Brush−Type Controller
http://onsemi.com
24
1.0 k
RS
MC33033, NCV33033
ORDERING INFORMATION
Device
Operating Temperature Range
Package
Shipping †
SO−20L
38 Units / Rail
MC33033DW
MC33033DWG
SO−20L
(Pb−Free)
MC33033DWR2
SO−20L
TA = −40°C to +85°C
MC33033DWR2G
SO−20L
(Pb−Free)
MC33033P
PDIP−20
MC33033PG
PDIP−20
(Pb−Free)
NCV33033DWR2*
SO−20L
TA = −40°C to +125°C
NCV33033DWR2G*
1000 Tape & Reel
18 Units / Rail
1000 Tape & Reel
SO−20L
(Pb−Free)
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specification Brochure, BRD8011/D.
*NCV33033: Tlow = −40C, Thigh = +125C. Guaranteed by design. NCV prefix is for automotive and other applications requiring site and change
control.
MARKING DIAGRAMS
SO−20L
DW SUFFIX
CASE 751D
PDIP−20
P SUFFIX
CASE 738
20
20
MC33033DW
AWLYYWWG
MC33033P
AWLYYWWG
1
1
20
20
NCV33033DW
AWLYYWWG
NCV33033P
AWLYYWWG
1
1
A
WL
YY
WW
G
= Assembly Location
= Wafer Lot
= Year
= Work Week
= Pb−Free Package
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25
MC33033, NCV33033
PACKAGE DIMENSIONS
PDIP−20
P SUFFIX
CASE 738−03
ISSUE E
−A−
20
11
1
10
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
3. DIMENSION L TO CENTER OF LEAD WHEN
FORMED PARALLEL.
4. DIMENSION B DOES NOT INCLUDE MOLD
FLASH.
B
C
−T−
L
K
SEATING
PLANE
M
E
G
N
F
J 20 PL
0.25 (0.010)
D 20 PL
0.25 (0.010)
M
T A
M
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26
M
T B
M
DIM
A
B
C
D
E
F
G
J
K
L
M
N
INCHES
MIN
MAX
1.010 1.070
0.240 0.260
0.150 0.180
0.015 0.022
0.050 BSC
0.050 0.070
0.100 BSC
0.008 0.015
0.110 0.140
0.300 BSC
0°
15°
0.020 0.040
MILLIMETERS
MIN
MAX
25.66 27.17
6.10
6.60
3.81
4.57
0.39
0.55
1.27 BSC
1.27
1.77
2.54 BSC
0.21
0.38
2.80
3.55
7.62 BSC
0°
15°
0.51
1.01
MC33033, NCV33033
PACKAGE DIMENSIONS
SO−20L
DW SUFFIX
CASE 751D−05
ISSUE G
q
A
20
X 45 _
h
H
M
E
0.25
10X
NOTES:
1. DIMENSIONS ARE IN MILLIMETERS.
2. INTERPRET DIMENSIONS AND TOLERANCES
PER ASME Y14.5M, 1994.
3. DIMENSIONS D AND E DO NOT INCLUDE MOLD
PROTRUSION.
4. MAXIMUM MOLD PROTRUSION 0.15 PER SIDE.
5. DIMENSION B DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE PROTRUSION SHALL
BE 0.13 TOTAL IN EXCESS OF B DIMENSION AT
MAXIMUM MATERIAL CONDITION.
11
B
M
D
1
10
20X
B
B
0.25
M
T A
S
B
S
L
A
18X
e
A1
SEATING
PLANE
C
T
DIM
A
A1
B
C
D
E
e
H
h
L
q
MILLIMETERS
MIN
MAX
2.35
2.65
0.10
0.25
0.35
0.49
0.23
0.32
12.65
12.95
7.40
7.60
1.27 BSC
10.05
10.55
0.25
0.75
0.50
0.90
0_
7_
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.
“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All
operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights
nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications
intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should
Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates,
and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death
associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal
Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT:
Literature Distribution Center for ON Semiconductor
P.O. Box 5163, Denver, Colorado 80217 USA
Phone: 303−675−2175 or 800−344−3860 Toll Free USA/Canada
Fax: 303−675−2176 or 800−344−3867 Toll Free USA/Canada
Email: [email protected]
N. American Technical Support: 800−282−9855 Toll Free
USA/Canada
Europe, Middle East and Africa Technical Support:
Phone: 421 33 790 2910
Japan Customer Focus Center
Phone: 81−3−5773−3850
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27
ON Semiconductor Website: www.onsemi.com
Order Literature: http://www.onsemi.com/orderlit
For additional information, please contact your local
Sales Representative
MC33033/D