LINER LTC1407 16-bit, 5msps differential input adc with wide input common mode range Datasheet

LTC2311-16
16-Bit, 5Msps
Differential Input ADC with Wide
Input Common Mode Range
DESCRIPTION
FEATURES
5Msps Throughput Rate
nn ±3LSB INL (Typ), ±8LSB INL Guaranteed
nn Guaranteed 16-Bit, No Missing Codes
nn 8V
P-P Differential Inputs with Wide Input Common
Mode Range
nn 81dB SNR (Typ) at f = 2.2MHz
IN
nn –90dB THD (Typ) at f = 2.2MHz
IN
nn Guaranteed Operation –40°C to 125°C
nn Single 3.3V or 5V Supply
nn Low Drift (20ppm/°C Max) 2.048V or 4.096V Internal
Reference with 1.25V External Reference Input
nn 1.8V to 2.5V I/O Voltages
nn CMOS or LVDS SPI-Compatible Serial I/O
nn Power Dissipation 50mW at V
DD = 5V (Typ)
nn Small 16-Lead (4mm × 5mm) MSOP Package
nn
APPLICATIONS
High Speed Data Acquisition Systems
Communications
nn Remote Data Acquisition
nn Imaging
nn Optical Networking
nn Automotive
nn Multiphase Motor Control
nn
nn
The LTC®2311-16 is a low noise, high speed 16-bit
successive approximation register (SAR) ADC with
differential inputs and wide input common mode range.
Operating from a single 3.3V or 5V supply, the LTC231116 has an 8VP-P differential input range, making it ideal
for applications which require a wide dynamic range with
high common mode rejection. The LTC2311-16 achieves
±3LSB INL typical, no missing codes at 16 bits and 81dB
SNR typical.
The LTC2311-16 has an onboard low drift (20ppm/°C max)
2.048V or 4.096V temperature-compensated reference and
provides an external 1.25V buffered reference input. The
LTC2311-16 also has a high speed SPI-compatible serial
interface that supports CMOS or LVDS. The fast 5Msps
throughput with one-cycle latency makes the LTC2311-16
ideally suited for a wide variety of high speed applications.
The LTC2311-16 dissipates only 50mW with a 5V supply
and offers nap and sleep modes to reduce the power
consumption to 5μW for further power savings during
inactive periods.
L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear
Technology Corporation. All other trademarks are the property of their respective owners.
TYPICAL APPLICATION
3.3V OR 5V
DIFFERENTIAL INPUTS
NO CONFIGURATION REQUIRED
IN+, IN –
DIFFERENTIAL
VDD REFOUT
25Ω
0V
AIN+
UNIPOLAR
25Ω
10µF
SDO
SCK
AIN–
CMOS/LVDS
0V
0V
10µF
REFIN
47pF
GND
SNR = 81.6dB
THD = –90dB
SINAD = 81.1dB
SFDR = 96dB
–20
LTC2311-16
0V
BIPOLAR
0
1µF
AMPLITUDE (dBFS)
ARBITRARY
32k Point FFT fSMPL = 5Msps, fIN = 2.2MHz
LVDS OR CMOS
CONFIGURABLE
I/O
–40
–60
–80
–100
–120
–140
CNV
OVDD
1.8V TO 2.5V
1µF
0
0.5
1
1.5
FREQUENCY (MHz)
2
2.5
231116 TA01b
231116 TA01a
231116fa
For more information www.linear.com/LTC2311-16
1
LTC2311-16
ABSOLUTE MAXIMUM RATINGS
PIN CONFIGURATION
(Notes 1, 2)
Supply Voltage (VDD)...................................................6V
Supply Voltage (OVDD).................................................3V
Analog Input Voltage
AIN+, AIN – (Note 3).................... –0.3V to (VDD + 0.3V)
REFIN, REFOUT........................ –0.3V to (VDD + 0.3V)
CNV (Note 15)........................... –0.3V to (VDD + 0.3V)
Digital Input Voltage
(Note 3)........................... (GND – 0.3V) to (OVDD + 0.3V)
Digital Output Voltage
(Note 3)........................... (GND – 0.3V) to (OVDD + 0.3V)
Power Dissipation................................................200mW
Operating Temperature Range
LTC2311C.................................................. 0°C to 70°C
LTC2311I...............................................–40°C to 85°C
LTC2311H........................................... –40°C to 125°C
Storage Temperature Range................... –65°C to 150°C
ORDER INFORMATION
TOP VIEW
GND
REFIN
REFOUT
VDD
GND
AIN+
AIN–
GND
1
2
3
4
5
6
7
8
17
GND
16
15
14
13
12
11
10
9
SCK+
SCK–
SDO+
SDO–
OVDD
GND
CMOS/LVDS
CNV
MSE PACKAGE
16-LEAD (4mm × 5mm) PLASTIC MSOP
TJMAX = 150°C, θJA = 40°C/W
EXPOSED PAD (PIN 17) IS GND, MUST BE SOLDERED TO PCB
http://www.linear.com/product/LTC2311-16#orderinfo
LEAD FREE FINISH
TAPE AND REEL
PART MARKING*
PACKAGE DESCRIPTION
TEMPERATURE RANGE
LTC2311CMSE-16#PBF
LTC2311CMSE-16#TRPBF
231116
16-Lead (4mm × 5mm) Plastic MSOP
0°C to 70°C
LTC2311IMSE-16#PBF
LTC2311IMSE-16#TRPBF
231116
16-Lead (4mm × 5mm) Plastic MSOP
–40°C to 85°C
LTC2311HMSE-16#PBF
LTC2311HMSE-16#TRPBF
231116
16-Lead (4mm × 5mm) Plastic MSOP
–40°C to 125°C
Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/. Some packages are available in 500 unit reels through
designated sales channels with #TRMPBF suffix.
2
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL
PARAMETER
CONDITIONS
VIN+
Absolute Input Range (AIN+)
VIN–
Absolute Input Range (AIN–)
VIN+ – VIN–
VCM
IIN
Analog Input DC Leakage Current
MIN
MAX
UNITS
0
VDD
V
0
VDD
V
l
–REFOUT
REFOUT
V
l
0
VDD
V
l
–1
1
µA
(Note 5)
l
(Note 5)
l
Input Differential Voltage Range
VIN = VIN+ – VIN–
Common Mode Input Range
VCM = (VIN+ + VIN–)/2
CIN
Analog Input Capacitance
CMRR
Input Common Mode Rejection Ratio
VIHCNV
CNV High Level Input Voltage
l
VILCNV
CNV Low Level Input Voltage
l
VINCNV
CNV Input Current
fIN = 2.2MHz
VIN = 0V to VDD
l
TYP
10
pF
85
dB
1.3
V
–10
0.5
V
10
µA
CONVERTER CHARACTERISTICS
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
Resolution
l
16
Bits
No Missing Codes
l
16
Bits
Transition Noise
INL
Integral Linearity Error
DNL
Differential Linearity Error
BZE
Bipolar Zero-Scale Error
FSE
1.7
(Note 6)
LSBRMS
l
–8
±3
8
LSB
l
–0.99
±0.4
0.99
LSB
(Note 7)
l
–12
0
12
LSB
Bipolar Full-Scale Error
VREFOUT = 4.096V (REFIN Grounded) (Note 7)
l
–30
Bipolar Full-Scale Error Drift
VREFOUT = 4.096V (REFIN Grounded)
Bipolar Zero-Scale Error Drift
0.01
±10
15
LSB/°C
30
LSB
ppm/°C
231116fa
For more information www.linear.com/LTC2311-16
3
LTC2311-16
DYNAMIC ACCURACY
The l denotes the specifications which apply over the full operating temperature range,
otherwise specifications are at TA = 25°C and AIN = –1dBFS (Notes 4, 8).
SYMBOL PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
SINAD
Signal-to-(Noise + Distortion) Ratio fIN = 2.2MHz, VREFOUT = 4.096V, Internal Reference
fIN = 2.2MHz, VREFOUT = 5V, External Reference
l
76
81
81.5
dB
dB
SNR
Signal-to-Noise Ratio
fIN = 2.2MHz, VREFOUT = 4.096V, Internal Reference
fIN = 2.2MHz, VREFOUT = 5V, External Reference
l
76.5
81.6
82.3
dB
dB
THD
Total Harmonic Distortion
fIN = 2.2MHz, VREFOUT = 4.096V, Internal Reference
fIN = 2.2MHz, VREFOUT = 5V, External Reference
l
SFDR
Spurious Free Dynamic Range
fIN = 2.2MHz, VREFOUT = 4.096V, Internal Reference
fIN = 2.2MHz, VREFOUT = 5V, External Reference
l
–90
–88
78
–79
dB
dB
95
90
dB
dB
–3dB Input Bandwidth
100
MHz
Aperture Delay
500
ps
Aperture Jitter
Transient Response
Full-Scale Step
1
psRMS
3
ns
INTERNAL REFERENCE CHARACTERISTICS
The l denotes the specifications which apply over the
full operating temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
VREFOUT
REFOUT Output Voltage
4.75V < VDD < 5.25V
3.13V < VDD < 3.47V
l
l
4.082
2.042
4.096
2.048
4.110
2.054
V
V
REFOUT Input Voltage
4.75V < VDD < 5.25V, REFIN = 0V (Note 5)
3.13V < VDD < 3.47V, REFIN = 0V (Note 5)
l
l
0.5
0.5
VDD
VDD
V
V
REFOUT Temperature Coefficient
(Note 14)
l
20
ppm/°C
REFOUT Short-Circuit Current
VDD = 5.25V, Forcing Output to GND
l
30
mA
3
REFOUT Line Regulation
VDD = 4.75V to 5.25V
0.3
mV/V
REFOUT Load Regulation
IREFOUT < 2mA
0.5
mV/mA
REFOUT Input Resistance (External Reference
Mode)
REFIN = 0V
60
kΩ
IREFOUT
REFOUT Input Current (External Reference
Mode)
REFIN = 0V, REFOUT = 4.096V
(Notes 9, 10)
700
µA
VREFIN
REFIN Output Voltage
3.13V < VDD < 3.47V
4.75V < VDD < 5.25V
l
1.245
REFIN Input Voltage
3.13V < VDD < 3.47V (Note 5)
4.75V < VDD < 5.25V (Note 5)
l
l
1
1
REFIN Short-Circuit Current
VDD = 5.25V, Forcing Output to GND
3.13V < VDD < 3.47V
4.75V < VDD < 5.25V
VIL (VREFIN) REFIN Low Level Input Voltage (External
Reference Mode)
4
1.25
1.255
V
1.85
1.45
V
V
l
250
µA
l
l
0.5
0.5
V
V
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
DIGITAL INPUTS AND DIGITAL OUTPUTS
The l denotes the specifications which apply over the
full operating temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
CMOS Digital Inputs and Outputs
VIH
High Level Input Voltage
VIL
Low Level Input Voltage
IIN
Digital Input Current
CIN
Digital Input Capacitance
VOH
High Level Output Voltage
IO = –500µA
l
VOL
Low Level Output Voltage
IO = 500µA
l
IOZ
Hi-Z Output Leakage Current
VOUT = 0V to OVDD
l
ISOURCE
Output Source Current
VOUT = 0V
ISINK
Output Sink Current
VOUT = OVDD
l
0.8 • OVDD
V
l
VIN = 0V to OVDD
l
–10
0.2 • OVDD
V
10
μA
5
pF
OVDD – 0.2
V
–10
0.2
V
10
µA
–10
mA
10
mA
LVDS Digital Inputs and Outputs
VID
LVDS Differential Input Voltage
100Ω Differential Termination, OVDD = 2.5V
l
240
600
mV
VIS
LVDS Common Mode Input Voltage
100Ω Differential Termination, OVDD = 2.5V
l
1
1.45
V
VOD
LVDS Differential Output Voltage
100Ω Differential Load, LVDS Mode,
OVDD = 2.5V
l
100
250
300
mV
VOS
LVDS Common Mode Output Voltage
100Ω Differential Load, LVDS Mode,
OVDD = 2.5V
l
0.85
1.2
1.4
V
VOD_LP
Low Power LVDS Differential Output
Voltage
100Ω Differential Load, Low Power,
LVDS Mode, OVDD = 2.5V
l
50
125
200
mV
VOS_LP
Low Power LVDS Common Mode
Output Voltage
100Ω Differential Load, Low Power,
LVDS Mode, OVDD = 2.5V
l
0.9
1.2
1.4
V
231116fa
For more information www.linear.com/LTC2311-16
5
LTC2311-16
POWER REQUIREMENTS
The l denotes the specifications which apply over the full operating temperature
range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL PARAMETER
CONDITIONS
MIN
5V Operation
3.3V Operation
MAX
UNITS
l
4.75
3.13
TYP
5.25
3.47
V
V
l
1.71
2.63
V
VDD
Supply Voltage
OVDD
Supply Voltage
IVDD
Supply Current
5Msps Sample Rate (AIN+ = AIN– = 0V)
l
9.5
12
mA
INAP
Nap Mode Current
Conversion Done (IVDD)
l
2.8
3.5
mA
ISLEEP
Sleep Mode Current
VDD = 3.3V, Sleep Mode (IVDD + IOVDD)
l
0.1
10
μA
l
1.1
1.75
CMOS I/O Mode
IOVDD
Supply Current
5Msps Sample Rate (CL = 5pF)
PD_3.3V
Power Dissipation
VDD = 3.3V 5Msps Sample Rate (AIN+ = AIN– = 0V)
30
mW
PD_5V
mA
Nap Mode
VDD = 3.3V Conversion Done (IVDD + IOVDD)
7.5
mW
Sleep Mode
VDD = 3.3V Sleep Mode (IVDD + IOVDD)
0.3
μW
Power Dissipation
VDD = 5V 5Msps Sample Rate (AIN+ = AIN– = 0V)
l
45
65
mW
Nap Mode
VDD = 5V Conversion Done (IVDD + IOVDD)
l
14
18
mW
Sleep Mode
VDD = 5V Sleep Mode (IVDD + IOVDD)
l
0.5
60
μW
l
2.7
4.5
mA
LVDS I/O Mode
IOVDD
Supply Current
5Msps Sample Rate (RL = 100Ω)
PD_3.3V
Power Dissipation
VDD = 3.3V 5Msps Sample Rate (AIN+ = AIN– = 0V)
PD_5V
36
mW
Nap Mode
VDD = 3.3V Conversion Done (IVDD + IOVDD)
14
mW
Sleep Mode
VDD = 3.3V Sleep Mode (IVDD + IOVDD)
0.3
µW
Power Dissipation
VDD = 5V 5Msps Sample Rate (AIN+ = AIN– = 0V)
l
Nap Mode
VDD = 5V Conversion Done (IVDD + IOVDD)
l
Sleep Mode
VDD = 5V Sleep Mode (IVDD + IOVDD)
l
55
72
mW
20
30
mW
0.5
60
µW
ADC TIMING CHARACTERISTICS
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
5
Msps
CMOS, LVDS I/O Modes
fSMPL
Maximum Sampling Frequency
tCYC
Time Between Conversions
(Note 11)
l
200
tACQ
Acquisition Time
(Note 11)
l
28.5
l
1000000
ns
ns
tCONV
Conversion Time
l
171.5
ns
tCNVH
CNV High Time
l
25
ns
tDCNVSCKL
SCK Quiet Time from CNV↓
(Note 11)
l
9.5
ns
tDSCKLCNVH
SCK Delay Time to CNV↑
(Note 11)
l
19.1
ns
tSCK
SCK Period
(Notes 12, 13)
l
9.4
ns
tSCKH
SCK High Time
l
4
ns
tSCKL
SCK Low Time
l
4
ns
6
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
ADC TIMING CHARACTERISTICS
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL
PARAMETER
CONDITIONS
tDSCKSDOV
SDO Data Valid Delay from SCK↓
CL = 5pF (Note 11)
l
tHSDO
SDO Data Remains Valid Delay from
SCK↓
CL = 5pF (Note 11)
l
tDCNVSDOV
SDO Data Valid Delay from CNV↓
CL = 5pF (Note 11)
l
tDCNVSDOZ
Bus Relinquish Time After CNV↑
(Note 11)
l
tWAKE
REFOUT Wake-Up Time
CREFOUT = 10μF
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: All voltage values are with respect to ground.
Note 3: When these pin voltages are taken below ground, or above VDD
or OVDD, they will be clamped by internal diodes. This product can handle
input currents up to 100mA below ground, or above VDD or OVDD, without
latch-up.
Note 4: VDD = 5V, OVDD = 2.5V, REFOUT = 4.096V, fSMPL = 5MHz.
Note 5: Recommended operating conditions.
Note 6: Integral nonlinearity is defined as the deviation of a code from a
straight line passing through the actual endpoints of the transfer curve.
The deviation is measured from the center of the quantization band.
Note 7: Bipolar zero error is the offset voltage measured from –0.5LSB
when the output code flickers between 0000 0000 0000 0000 and 1111
1111 1111 1111. Full-scale bipolar error is the worst-case of –FS or +FS
MIN
TYP
MAX
4
7.4
2
UNITS
ns
ns
2.5
10
5
ns
5
ns
ms
untrimmed deviation from ideal first and last code transitions and includes
the effect of offset error.
Note 8: All specifications in dB are referred to a full-scale ±4.096V input
with REFOUT = 4.096V.
Note 9: When REFOUT is overdriven, the internal reference buffer must be
turned off by setting REFIN = 0V.
Note 10: fSMPL = 5MHz, IREFOUT varies proportionally with sample rate.
Note 11: Guaranteed by design, not subject to test.
Note 12: Parameter tested and guaranteed at OVDD = 1.71V and
OVDD = 2.5V.
Note 13: tSCK of 9.4ns minimum allows a shift clock frequency up to
105MHz for falling edge capture.
Note 14: Temperature coefficient is calculated by dividing the maximum
change in output voltage by the specified temperature range.
Note 15: CNV is driven from a low jitter digital source, typically at OVDD
logic levels. This input pin has a TTL style input that will draw a small
amount of current.
0.8 • OVDD
tWIDTH
0.2 • OVDD
tDELAY
tDELAY
0.8 • OVDD
0.8 • OVDD
0.2 • OVDD
0.2 • OVDD
50%
50%
231116 F01
Figure 1. Voltage Levels for Timing Specifications
231116fa
For more information www.linear.com/LTC2311-16
7
LTC2311-16
TYPICAL PERFORMANCE CHARACTERISTICS
4.096V, fSMPL = 5Msps, unless otherwise noted.
Integral Nonlinearity
vs Output Code
TA = 25°C, VDD = 5V, OVDD = 2.5V, REFOUT =
Differential Nonlinearity
vs Output Code
DC Histogram
1
4
20000
1
0
–1
14000
COUNTS
DNL ERROR (LSB)
INL ERROR (LSB)
16000
0.5
2
0
12000
10000
4000
–3
2000
–4
–32768
–16384
0
16384
OUTPUT CODE
–1
–32768
32768
–16384
0
16384
OUTPUT CODE
32k Point FFT, fSMPL = 5Msps,
fIN = 2.2MHz
–100
THD, HARMONICS (dBFS)
SNR, SINAD (dBFS)
AMPLITUDE (dBFS)
–80
82.0
SNR
81.5
SINAD
81.0
80.5
–120
0
0.5
1
1.5
FREQUENCY (MHz)
2
2.5
80.0
0
0.5
1
1.5
FREQUENCY (MHz)
2
THD, Harmonics vs Input Common
Mode (100kHz to 2.2MHz)
–80
84
–100
HD2
2.1 2.3 2.5 2.7 2.9 3.1
INPUT COMMON MODE (V)
3.3
231116 G07
HD2
–105
HD3
0
0.5
1
1.5
FREQUENCY (MHz)
2
SNR
78
76
74
68
2.5
8k Point FFT, IMD, fSMPL = 5Msps,
AIN+ = 100kHz, AIN– = 2.2MHz
–20
–40
–60
–80
–100
–120
70
1.9
–100
0
SINAD
72
–105
THD
231116 G06
AMPLITUDE (dBFS)
SNR, SINAD (dBFS)
HD3
–95
–110
1.7
2.5
SNR, SINAD vs Reference Voltage,
fIN = 500kHz
80
THD
6
–95
–110
82
–85
5
–90
231116 G05
231116 G04
–90
4
–85
82.5
–60
3
THD, Harmonics vs Input
Frequency (100kHz to 2.2MHz)
83.0
SNR = 81.6dB
THD = –90dB
–20
SINAD = 81.1dB
SFDR = 96dB
–40
–5 –4 –3 –2 –1 0 1 2
OUTPUT CODE
231116 G03
SNR, SINAD vs Input Frequency
(100kHz to 2.2MHz)
0
THD, HARMONICS (dBFS)
0
32768
231116 G02
231116 G01
8
8000
6000
–0.5
–2
–140
σ = 1.7
18000
3
0.5
1
1.5
2
2.5 3 3.5
VREF (V)
4
4.5
5
231116 G08
–140
0
0.5
1
1.5
FREQUENCY (MHz)
2
2.5
231116 G09
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
TYPICAL PERFORMANCE CHARACTERISTICS
TA = 25°C, VDD = 5V, OVDD = 2.5V, REFOUT =
4.096V, fSMPL = 5Msps, unless otherwise noted.
Gain Error vs Temperature
1.5
1.5
–83
1.0
1.0
–86
0.5
–89
0.5
0
–0.5
CMRR (dB)
–80
0
–0.5
–92
–95
–1.0
–1.0
–98
–1.5
–1.5
–101
–2.0
–50
–25
0
25
50
75
TEMPERATURE (°C)
100
–2.0
–50
125
–25
231116 G10
708
2.048V
4.096V
300
REFERENCE CURRENT (µA)
200
100
0
–100
–200
–300
–400
100
–104
125
IREFOUT vs Temperature,
VREF = 4.096V
0
0.5
1
1.5
FREQUENCY (MHz)
2
2.5
231116 G12
REFOUT Output Load Regulation
4.0970
706
4.0965
704
4.0960
VREF (V)
400
0
25
50
75
TEMPERATURE (°C)
231116 G11
REFOUT Output vs Temperature
702
4.0955
700
4.0950
698
4.0945
–500
–25
0
25
50
75
TEMPERATURE (°C)
100
125
696
–50
–25
0
25
50
75
TEMPERATURE (°C)
100
125
4.0940
0
0.5
1
1.5
REFOUT LOAD CURRENT (mA)
Supply Current
vs Sample Frequency
10
1.5
2
231116 G15
231116 G14
231116 G13
OVDD Current vs SCK Frequency,
CLOAD = 10pF
9
OVDD CURRENT (mA)
–600
–50
SUPPLY CURRENT (mA)
REFOUT ERROR (ppm, NORMALIZED TO 25°C)
CMRR vs Input Frequency
2.0
GAIN ERROR (LSB)
OFFSET ERROR (LSB)
Offset Error vs Temperature
2.0
8
8
7
1.0
0.5
6
5
0
1
2
3
4
SAMPLE FREQUENCY (Msps)
5
0
0 10 20 30 40 50 60 70 80 90 100 110
SCK FREQUENCY (MHz)
231116 G16
231116 G17
231116fa
For more information www.linear.com/LTC2311-16
9
LTC2311-16
PIN FUNCTIONS
GND (Pins 1, 5, 8, 11): Ground. These pins and the exposed
pad (Pin 17) must be tied directly to a solid ground plane.
REFIN (Pin 2): Reference Buffer 1.25V Input/Output. An
onboard buffer nominally outputs 1.25V to this pin. This
pin should be decoupled closely to the pin (no vias) with
a 10μF (X5R, 0805 size) ceramic capacitor. The internal
buffer driving this pin may be overdriven with an external
reference. The REFIN pin, when pulled to GND disables
the REFOUT pin buffer allowing an external reference to
drive REFOUT directly.
REFOUT (Pin 3): Reference Buffer Output. An onboard
buffer nominally outputs 4.096V to this pin. This pin should
be decoupled closely to the pin (no vias) with a 10μF (X5R,
0805 size) ceramic capacitor. The internal buffer driving
this pin may be disabled by grounding the REFIN pin. If
the buffer is disabled, an external reference may drive this
pin in the range of 1.25V to VDD.
VDD (Pin 4): Power Supply. Bypass VDD to GND with a
1µF ceramic capacitor close to the VDD pin.
AIN+, AIN– (Pins 6, 7): Analog Differential Input Pins. Fullscale range (AIN+ to AIN–) is ±REFOUT voltage. These pins
can be driven from VDD to GND.
CNV (Pin 9): Convert Input. This pin, when high, defines
the sampling phase. When this pin is driven low, the conversion phase is initiated and output data is clocked out.
This input pin is a TTL style input typically driven at OVDD
levels with a low jitter pulse, but it is bound to VDD levels.
This pin is unaffected by the CMOS/LVDS pin.
OVDD (Pin 12): I/O Interface Digital Power. The range of
OVDD is 1.71V to 2.5V. This supply is nominally set to the
same supply as the host interface (CMOS: 1.8V or 2.5V,
LVDS: 2.5V). Bypass OVDD to GND with a 1μF ceramic
capacitor close to the OVDD pin.
Exposed Pad (Pin 17): Ground. Solder this pad to ground.
CMOS I/O Mode
SDO+ (Pin 14): Serial Data Output. The conversion result
is shifted MSB first on each falling edge of SCK. The result
is output on SDO+. The logic level is determined by OVDD.
Do not connect SDO–.
SCK+ (Pin 16): Serial Data Clock Input. The falling edge
of this clock shifts the conversion result MSB first onto
the SDO pins. Drive SCK+ with a single-ended clock. The
logic level is determined by OVDD. Do not connect SCK–.
LVDS I/O Mode
SDO+, SDO– (Pins 14, 13): Serial Data Output. The conversion result is shifted MSB first on each falling edge of
SCK. The result is output differentially on SDO+ and SDO–.
These pins must be differentially terminated by an external
100Ω resistor at the receiver (FPGA).
SCK+, SCK– (Pins 16, 15): Serial Data Clock Input. The
falling edge of this clock shifts the conversion result MSB
first onto the SDO pins. Drive SCK+ and SCK– with a differential clock. These pins must be differentially terminated
by an external 100Ω resistor at the receiver (ADC).
CMOS/LVDS (Pin 10): I/O mode select. Ground this pin
to enable CMOS mode, tie to OVDD to enable LVDS mode.
Float this pin to enable low power LVDS mode.
10
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
FUNCTIONAL BLOCK DIAGRAM
CMOS I/O Mode
4
6
7
VDD
AIN+
AIN–
LDO
+
16-BIT
SAR ADC
S/H
–
LVDS/CMOS
TRI-STATE
SERIAL OUTPUT
GND
1, 5, 8, 11, 17
3
2
9
SDO+
14
OVDD 12
REFOUT
1.25V REF
G
CMOS/LVDS
10
REFIN
CNV
TIMING CONTROL
LOGIC
LVDS/CMOS
RECEIVERS
SCK+
16
231116 BDa
LVDS I/O Mode
4
6
7
VDD
AIN+
AIN–
LDO
+
16-BIT
SAR ADC
S/H
–
LVDS/CMOS
TRI-STATE
SERIAL OUTPUT
GND
1, 5, 8, 11, 17
3
2
9
REFOUT
SDO+
SDO–
14
13
OVDD 12
G
1.25V REF
CMOS/LVDS
10
REFIN
CNV
TIMING CONTROL
LOGIC
LVDS/CMOS
RECEIVERS
SCK+
SCK –
16
15
231116 BDb
231116fa
For more information www.linear.com/LTC2311-16
11
LTC2311-16
TIMING DIAGRAM
CMOS, LVDS I/O Modes
ACQUISITION
CONVERSION AND READOUT
ACQUISITION
CNV
SCK
HI-Z
SDO
B15
B14
B13
B12
B11
B10
B9
B8
B7
B6
B5
B4
B3
B2
B1
B0
HI-Z
231116 TD
SERIAL DATA BITS B[15:0] CORRESPOND TO PREVIOUS CONVERSION
12
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
OVERVIEW
The LTC2311-16 is a low noise, high speed 16-bit successive approximation register (SAR) ADC with differential
inputs and a wide input common mode range. Operating
from a single 3.3V or 5V supply, the LTC2311-16 has an
8VP-P differential input range, making it ideal for applications which require a wide dynamic range. The LTC2311-16
achieves ±3LSB INL typical, no missing codes at 16 bits
and 81dB SNR typical.
The LTC2311-16 has an onboard reference buffer and low
drift (20ppm/°C max) 4.096V temperature-compensated
reference. The LTC2311-16 also has a high speed SPIcompatible serial interface that supports CMOS or LVDS.
The fast 5Msps throughput with one-cycle latency makes
the LTC2311-16 ideally suited for a wide variety of high
speed applications. The LTC2311-16 dissipates only 50mW
operating at a 5V supply. Nap and sleep modes are also
provided to reduce the power consumption of the LTC231116 during inactive periods for further power savings.
CONVERTER OPERATION
OUTPUT CODE (TWO’S COMPLEMENT)
The LTC2311-16 operates in two phases. During the
acquisition phase, the sample capacitor is connected to
the analog input pins AIN+ and AIN – to sample the differential analog input voltage, as shown in Figure 3. A
falling edge on the CNV pin initiates a conversion. During the conversion phase, the 16-bit CDAC is sequenced
through a successive approximation algorithm for each
input SCK pulse, effectively comparing the sampled input
with binary-weighted fractions of the reference voltage
(e.g., VREFOUT/2, VREFOUT/4 … VREFOUT/65536) using a
differential comparator. At the end of conversion, the CDAC
output approximates the sampled analog input. The ADC
control logic then prepares the 16-bit digital output code
for serial transfer.
TRANSFER FUNCTION
The LTC2311-16 digitizes the full-scale voltage of 2 ×
REFOUT into 216 levels, resulting in an LSB size of
125µV with REFOUT = 4.096V. The ideal transfer function
is shown in Figure 2. The output data is in 2’s complement format.
Analog Input
The differential inputs of the LTC2311-16 provide great
flexibility to convert a wide variety of analog signals with
no configuration required. The LTC2311-16 digitizes the
difference voltage between the AIN+ and AIN – pins while
supporting a wide common mode input range. The analog
input signals can have an arbitrary relationship to each
other, provided that they remain between VDD and GND.
The LTC2311-16 can also digitize more limited classes of
analog input signals such as pseudo-differential unipolar/
bipolar and fully differential with no configuration required.
The analog inputs of the LTC2311-16 can be modeled
by the equivalent circuit shown in Figure 3. The back-toback diodes at the inputs form clamps that provide ESD
protection. In the acquisition phase, 10pF (CIN) from the
VDD
011...111
RON
15Ω
011...110
AIN+
CIN
10pF
000...001
000...000
111...111
BIAS
VOLTAGE
VDD
FSR = +FS – –FS
1LSB = FSR/65535
100...001
100...000
–FSR/2
–1 0 1
LSB
LSB
INPUT VOLTAGE (V)
AIN–
RON
15Ω
CIN
10pF
231116 F03
+FSR/2 – 1LSB
231116 F02
Figure 2. LTC2311-16 Transfer Function
Figure 3. The Equivalent Circuit for the Differential
Analog Input of the LTC2311-16
231116fa
For more information www.linear.com/LTC2311-16
13
LTC2311-16
APPLICATIONS INFORMATION
sampling capacitor in series with approximately 15Ω
(RON) from the on-resistance of the sampling switch is
connected to the input. Any unwanted signal that is common to both inputs will be reduced by the common mode
rejection of the ADC sampler. The inputs of the ADC core
draw a small current spike while charging the CIN capacitors during acquisition.
mode input range relaxes the accuracy requirements of
any signal conditioning circuits prior to the analog inputs.
Pseudo-Differential Bipolar Input Range
The pseudo-differential bipolar configuration represents
driving one of the analog inputs at a fixed voltage, typically
VREF /2, and applying a signal to the other AIN pin. In this
case the analog input swings symmetrically around the
fixed input yielding bipolar two’s complement output codes
with an ADC span of half of full-scale. This configuration
is illustrated in Figure 4, and the corresponding transfer
function in Figure 5. The fixed analog input pin need not
be set at VREF /2, but at some point within the VDD rails
allowing the alternate input to swing symmetrically around
this voltage. If the input signal (AIN+ – AIN –) swings beyond
±REFOUT/2, valid codes will be generated by the ADC and
must be clamped by the user, if necessary.
Single-Ended Signals
Single-ended signals can be directly digitized by the
LTC2311-16. These signals should be sensed pseudodifferentially for improved common mode rejection. By
connecting the reference signal (e.g., ground sense) of
the main analog signal to the other AIN pin, any noise or
disturbance common to the two signals will be rejected
by the high CMRR of the ADC. The LTC2311-16 flexibility
handles both pseudo-differential unipolar and bipolar signals, with no configuration required. The wide common
VREF
0V
LT1819
VREF
+
–
0V
LTC2311-16
25Ω
AIN+
REFOUT
VREF
REFIN
47pF
10k
VREF /2
10k
1µF
+
–
25Ω
VREF /2
AIN–
SDO
SCK
CNV
10µF
10µF
TO CONTROL
LOGIC
(FPGA, CPLD,
DSP, ETC.)
231116 F04
Figure 4. Pseudo-Differential Bipolar Application Circuit
ADC CODE
(2’s COMPLEMENT)
32767
16384
–VREF
–VREF /2
–16385
–32768
0
VREF /2
VREF
AIN
(AIN+ – AIN–)
DOTTED REGIONS AVAILABLE
BUT UNUSED
231116 F05
Figure 5. Pseudo-Differential Bipolar Transfer Function
14
For more information www.linear.com/LTC2311-16
231116fa
LTC2311-16
APPLICATIONS INFORMATION
Pseudo-Differential Unipolar Input Range
complement output codes with an ADC span of half of
full-scale. This configuration is illustrated in Figure 6, and
the corresponding transfer function in Figure 7. If the input
signal (AIN+ – AIN –) swings negative, valid codes will be
generated by the ADC and must be clamped by the user,
if necessary.
The pseudo-differential unipolar configuration represents
driving one of the analog inputs at ground and applying a
signal to the other AIN pin. In this case, the analog input
swings between ground and VREF yielding unipolar two’s
VREF
0V
LT1818
VREF
+
–
0V
LTC2311-16
25Ω
AIN+
REFIN
47pF
25Ω
REFOUT
AIN–
SDO
SCK
CNV
10µF
10µF
TO CONTROL
LOGIC
(FPGA, CPLD,
DSP, ETC.)
231116 F06
Figure 6. Pseudo-Differential Unipolar Application Circuit
ADC CODE
(2’s COMPLEMENT)
32767
16384
–VREF
–VREF /2
–16385
–32768
0
VREF /2
VREF
AIN
(AIN+ – AIN–)
DOTTED REGIONS AVAILABLE
BUT UNUSED
231116 F07
Figure 7. Pseudo-Differential Unipolar Transfer Function
231116fa
For more information www.linear.com/LTC2311-16
15
LTC2311-16
APPLICATIONS INFORMATION
Single-Ended-to-Differential Conversion
While single-ended signals can be directly digitized as previously discussed, single-ended to differential conversion
circuits may also be used when higher dynamic range is
desired. By producing a differential signal at the inputs of
the LTC2311-16, the signal swing presented to the ADC is
maximized, thus increasing the achievable SNR.
The LT®1819 high speed dual operational amplifier is
recommended for performing single-ended-to-differential
conversions, as shown in Figure 8. In this case, the first
amplifier is configured as a unity-gain buffer and the
single-ended input signal directly drives the high impedance input of this amplifier.
Fully-Differential Inputs
To achieve the full distortion performance of the LTC2311-16,
a low distortion fully-differential signal source driven
through the LT1819 configured as two unity-gain buffers,
as shown in Figure 9, can be used. This circuit achieves a
THD specification of –85dB at input frequencies of 500kHz
and less. Data sheet typical performance curves are taken
using a harmonic rejection filter between the ADC and the
VREF
0V
200Ω
VREF /2
LT1819
+
–
VREF
+
–
VREF
200Ω
0V
0V
The fully-differential configuration yields an analog input
span (AIN+ – AIN –) of ±REFOUT. In this configuration, the
input signal is driven on each AIN pin, typically at equal
spans but opposite polarity. This yields a high common
mode rejection on the input signals. The common mode
voltage of the analog input can be anywhere within the VDD
input range, but will be limited by the peak swing of the
full-range input signal. For example, if the internal reference is used with VDD = 5VDC, the full-range input span
will be ±4.096V. Half of the input span is typically driven
on each AIN pin, yielding a signal span for each AIN pin of
4.096VP-P. This leaves ~0.9V of common mode variation
tolerance. When using external references, it is possible
to increase common mode tolerance by compressing the
ADC full-range codes into a tighter range. For example,
using an external 2.048V reference with VDD = 5V the total
span would be ±2.048V and each AIN span would be limited to 2.048VP-P allowing a common mode range of ~3V.
Compressing the input span would incur a SNR penalty
of approximately 2dB. Input span compression may be
useful if single-supply analog input drivers are used which
VREF
0V
VREF
0V
231116 F08
LT1819
+
–
VREF
+
–
VREF
0V
0V
231116 F09
Figure 8. Single-Ended to Differential Driver
16
signal source to eliminate the op amp as the dominant
source of distortion.
Figure 9. LT1819 Buffering a Fully-Differential Signal Source
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
cannot swing rail-to-rail. The fully-differential configuration
is illustrated in Figure 10, with the corresponding transfer
function illustrated in Figure 11.
is important even for DC inputs, because the ADC inputs
draw a current spike at the start of the acquisition phase.
For best performance, a buffer amplifier should be used to
drive the analog inputs of the LTC2311-16. The amplifier
provides low output impedance to minimize gain error
and allow for fast settling of the analog signal during the
acquisition phase. It also provides isolation between the
signal source and the ADC inputs, which draw a small
current spike during acquisition.
INPUT DRIVE CIRCUITS
A low impedance source can directly drive the high impedance inputs of the LTC2311-16 without gain error. A
high impedance source should be buffered to minimize
settling time during acquisition and to optimize the distortion performance of the ADC. Minimizing settling time
VREF
0V
VREF
LT1819
+
–
0V
LTC2311-16
25Ω
AIN+
REFIN
47pF
VREF
0V
REFOUT
VREF
+
–
0V
25Ω
AIN–
SDO
SCK
CNV
10µF
10µF
TO CONTROL
LOGIC
(FPGA, CPLD,
DSP, ETC.)
231116 F10
Figure 10. Fully-Differential Application Circuit
ADC CODE
(2’s COMPLEMENT)
32767
16384
–VREF
–VREF /2
0
VREF /2
VREF
AIN
(AIN+ – AIN–)
–16385
–32768
231116 F11
Figure 11. Fully-Differential Transfer Function
231116fa
For more information www.linear.com/LTC2311-16
17
LTC2311-16
APPLICATIONS INFORMATION
Input Filtering
The noise and distortion of the buffer amplifier and signal
source must be considered since they add to the ADC noise
and distortion. Noisy input signals should be filtered prior
to the buffer amplifier input with a low bandwidth filter
to minimize noise. The simple 1-pole RC lowpass filter
shown in Figure 12 is sufficient for many applications.
SINGLE-ENDED
INPUT SIGNAL
50Ω
3.3nF
BW = 1MHz
10µF capacitor should be soldered as close as possible
to the REFOUT pin to minimize wiring inductance. The
REFIN pin produces a 1.25V precision reference which
should also be bypassed with a 10μF (X5R, 0805 size)
ceramic capacitor. The REFIN pin may be overdriven with
an external precision reference as shown in Figure 13a.
5V TO 13.2V
0.1µF
IN+
LTC2311
IN–
SINGLE-ENDED
TO DIFFERENTIAL
DRIVER
LTC6655-1.25V
VIN
VOUT_F
SHDN VOUT_S
REFIN
10µF
LTC2311-16
REFOUT
10µF
231116 F12
GND
Figure 12. Input Signal Chain
231116 F13a
Figure 13a. LTC2311-16 with an External REFIN Voltage
The input resistor divider network, sampling switch onresistance (RON) and the sample capacitor (CIN) form a
second lowpass filter that limits the input bandwidth to the
ADC core to 110MHz. A buffer amplifier with a low noise
density must be selected to minimize the degradation of
the SNR over this bandwidth.
High quality capacitors and resistors should be used in the
RC filters since these components can add distortion. NPO
and silver mica type dielectric capacitors have excellent
linearity. Carbon surface mount resistors can generate
distortion from self heating and from damage that may
occur during soldering. Metal film surface mount resistors
are much less susceptible to both problems.
Table 1. Internal Reference with Internal Buffer
FULLY
DIFFERENTIAL
VDD REFIN REFOUT INPUT RANGE
5V 1.25V 4.096V
±4.096V
UNIPOLAR
INPUT RANGE
BIPOLAR
INPUT
RANGE
0V to 4.096V
±2.048V
3.3V 1.25V
0V to 2.048V
±1.024V
REFIN
FULLY
(OVERDIFFERENTIAL
VDD DRIVEN) REFOUT INPUT RANGE
5V
1V
3.3V
±3.3V
ADC REFERENCE
The LTC2311-16 has an on-chip, low noise, low drift
(20ppm/°C max), temperature compensated bandgap reference that is internally buffered and is available at REFIN
(Pin 2). The internal reference buffer gains the REFIN pin
voltage (1.25V) to REFOUT (pin 3) and is 4.096V for a 5V
supply and 2.048V for 3.3V supply. Bypass REFOUT to
GND with a 10μF (X5R, 0805 size) ceramic capacitor. The
18
±2.048V
Table 2. External Reference with Internal Buffer
3.3V
Internal Reference
2.048V
UNIPOLAR
INPUT RANGE
BIPOLAR
INPUT
RANGE
0V to 3.3V
±1.65V
1.25V
4.096V
±4.096V
0V to 4.096V
±2.048V
1.45V
4.7V
±4.7V
0V to 4.7V
±2.35V
1V
1.65V
±1.65V
0V to 1.65V
±0.825V
1.25V
2.048V
±2.048V
0V to 2.048V
±1.024V
1.85
3V
±3V
0V to 3V
±1.5V
Table 3. External Reference Unbuffered
REFOUT
FULLY
DIFFERENTIAL
INPUT RANGE
0V
0.5V
±0.5V
0V to 0.5V
±0.25V
0V
5V
±5V
0V to 5V
±2.5V
VDD REFIN
5V
3.3V
UNIPOLAR
INPUT RANGE
BIPOLAR
INPUT
RANGE
0V
0.5V
±0.5V
0V to 0.5V
±0.25V
0V
3.3V
±3.3V
0V to 3.3V
±1.65V
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
External Reference
REFIN
LTC2311-16
5V TO 13.2V
0.1µF
LTC6655-4.096
VIN
VOUT_F
SHDN VOUT_S
CNV
IDLE
PERIOD
231116 F14
Figure 14. CNV Waveform Showing Burst Sampling
35000
30000
25000
OUTPUT CODE
The internal reference buffer can also be overdriven from
1.25V to 5V with an external reference at REFOUT as
shown in Figure 13b. In this configuration, REFIN must
be grounded to disable the internal reference buffer. A
55kΩ internal resistance loads the REFOUT pin when
the reference buffer is disabled. To maximize the input
signal swing and corresponding SNR, the LTC6655-5 is
recommended when overdriving REFOUT. The LTC6655-5
offers the same small size, accuracy, drift and extended
temperature range as the LTC6655-4.096. By using a 5V
reference, a higher SNR can be achieved. We recommend
bypassing the LTC6655-5 with a 10μF ceramic capacitor
(X5R, 0805 size) as close as possible to the REFOUT pin.
will affect the accuracy of the output code. Due to the
one-cycle conversion latency, the first conversion result
at the beginning of a burst sampling period will be invalid.
If an external reference is used to buffer/drive the REFOUT
pin, the fast settling LTC6655 reference is recommended.
20000
15000
10000
5000
0
REFOUT
–5000
10µF
0
100
TIME (ns)
GND
231116 F13b
Figure 13b. LTC2311-16 with an External REFOUT Voltage
Internal Reference Buffer Transient Response
The REFOUT pin of the LTC2311-16 draws charge (QCONV)
from the external bypass capacitors during each conversion cycle. If the internal reference buffer is overdriven,
the external reference must provide all of this charge
with a DC current equivalent to IREFOUT = QCONV/tCYC.
Thus, the DC current draw of REFOUT depends
on the sampling rate and output code. In applications
where a burst of samples is taken after idling for long
periods, as shown in Figure 14 , IREFOUT quickly goes from
approximately ~75µA to a maximum of 700µA for REFOUT
= 5V at 5Msps. This step in DC current draw triggers a
transient response in the external reference that must be
considered since any deviation in the voltage at REFOUT
200
231116 F15
Figure 15. Transient Response of the LTC2311-16
DYNAMIC PERFORMANCE
Fast Fourier transform (FFT) techniques are used to test
the ADC’s frequency response, distortion and noise at the
rated throughput. By applying a low distortion sine wave
and analyzing the digital output using an FFT algorithm,
the ADC’s spectral content can be examined for frequencies outside the fundamental. The LTC2311-16 provides
guaranteed tested limits for both AC distortion and noise
measurements.
Signal-to-Noise and Distortion Ratio (SINAD)
The signal-to-noise and distortion ratio (SINAD) is the
ratio between the RMS amplitude of the fundamental input
frequency and the RMS amplitude of all other frequency
components at the A/D output. The output is bandlimited
to frequencies from above DC and below half the sampling
231116fa
For more information www.linear.com/LTC2311-16
19
LTC2311-16
APPLICATIONS INFORMATION
frequency. Figure 16 shows that the LTC2311-16 achieves
a typical SINAD of 81dB at a 5MHz sampling rate with a
2.2MHz input.
0
SNR = 81.6dB
THD = –90dB
SINAD = 81.1dB
SFDR = 96dB
–40
The LTC2311-16 requires two power supplies: the 5V
power supply (VDD), and the digital input/output interface
power supply (OVDD). The flexible OVDD supply allows
the LTC2311-16 to communicate with any digital logic
operating between 1.8V and 2.5V. When using LVDS I/O,
the OVDD supply must be set to 2.5V.
–60
Power Supply Sequencing
–80
The LTC2311-16 does not have any specific power supply sequencing requirements. Care should be taken to
adhere to the maximum voltage relationships described
in the Absolute Maximum Ratings section. The LTC231116 has a power-on-reset (POR) circuit that will reset the
LTC2311-16 at initial power-up or whenever the power
supply voltage drops below 2V. Once the supply voltage
re-enters the nominal supply voltage range, the POR will
reinitialize the ADC. No conversions should be initiated
until 10ms after a POR event to ensure the reinitialization
period has ended. Any conversions initiated before this
time will produce invalid results.
–100
–120
–140
0
0.5
1
1.5
FREQUENCY (MHz)
2
2.5
231116 F16
Figure 16. 32k Point FFT of the LTC2311-16
Signal-to-Noise Ratio (SNR)
The signal-to-noise ratio (SNR) is the ratio between the
RMS amplitude of the fundamental input frequency and
the RMS amplitude of all other frequency components
except the first five harmonics and DC. Figure 16 shows
that the LTC2311-16 achieves a typical SNR of greater
than 81dB at a 5MHz sampling rate with a 2.2MHz input.
Total Harmonic Distortion (THD)
Total harmonic distortion (THD) is the ratio of the RMS sum
of all harmonics of the input signal to the fundamental itself.
The out-of-band harmonics alias into the frequency band
between DC and half the sampling frequency (fSMPL /2).
THD is expressed as:
V22 + V32 + V42 +…+ VN2
THD= 20log
V1
10
9
SUPPLY CURRENT (mA)
AMPLITUDE (dBFS)
–20
POWER CONSIDERATIONS
8
8
7
6
5
0
1
2
3
4
SAMPLE FREQUENCY (Msps)
5
231116 G16
Figure 17. Power Supply Current of the LTC2311-16
Versus Sampling Rate
where V1 is the RMS amplitude of the fundamental
frequency and V2 through VN are the amplitudes of the
second through Nth harmonics. The THD specifications
for the LTC2311-16 consider the first seven harmonics
(i.e. N=7). Figure 16 shows that the LTC2311-16 achieves
a typical THD of –90dB at a 5MHz sampling rate with a
2.2MHz input.
20
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
TIMING AND CONTROL
CNV Timing
The LTC2311-16 sampling and conversion is controlled
by CNV. A rising edge on CNV will start sampling and the
falling edge starts the conversion and readout process. The
conversion process is timed by the SCK input clock. For
optimum performance, CNV should be driven by a clean
low jitter signal. The Typical Application at the back of the
data sheet illustrates a recommended implementation to
reduce the relatively large jitter from an FPGA CNV pulse
source. Note the low jitter input clock times the falling edge
of the CNV signal. The rising edge jitter of CNV is much
less critical to performance. The typical pulse width of the
CNV signal is 30ns at a 5Msps conversion rate.
SCK Serial Data Clock Input
The falling edge of this clock shifts the conversion result
MSB first onto the SDO pins. A 105MHz external clock must
be applied at the SCK pin to achieve 5Msps throughput.
Nap/Sleep Modes
Nap mode is a method to save power without sacrificing
power-up delays for subsequent conversions. Sleep mode
has substantial power savings, but a power-up delay is
CNV
1
incurred to allow the reference and power systems to
become valid. To enter nap mode on the LTC2311-16,
the SCK signal must be held high or low and a series of
two CNV pulses must be applied. This is the case for both
CMOS and LVDS modes. The second rising edge of CNV
initiates the nap state. The nap state will persist until either
a single rising edge of SCK is applied, or further CNV pulses
are applied. The SCK rising edge will put the LTC2311-16
back into the operational (full-power) state. When in nap
mode, two additional pulses will put the LTC2311-16 in
sleep mode. When configured for CMOS I/O operation, a
single rising edge of SCK can return the LTC2311-16 into
operational mode. A 10ms delay is necessary after exiting
sleep mode to allow the reference buffer to recharge the
external filter capacitor. In LVDS mode, exit sleep mode
by supplying a fifth CNV pulse. The fifth pulse will return
the LTC2311-16 to operational mode, and further SCK
pulses will keep the part from re-entering nap and sleep
modes. The fifth SCK pulse also works in CMOS mode
as a method to exit sleep. In the absence of SCK pulses,
repetitive CNV pulses will cycle the LTC2311-16 between
operational, nap and sleep modes indefinitely.
Refer to the timing diagrams in Figure 18, Figure 19, Figure 20
and Figure 21 for more detailed timing information about
sleep and nap modes.
2
FULL POWER MODE
NAP MODE
SCK
HOLD STATIC HIGH OR LOW
WAKE ON 1ST SCK EDGE
SDO
Z
Z
231116 F18
Figure 18. CMOS and LVDS Mode NAP and WAKE Using SCK
231116fa
For more information www.linear.com/LTC2311-16
21
LTC2311-16
APPLICATIONS INFORMATION
REFOUT
REFOUT
RECOVERY
4.096V
4.096V
tWAKE
CNV
1
2
3
4
NAP MODE
SCK
SLEEP MODE
FULL POWER MODE
HOLD STATIC HIGH OR LOW
WAKE ON 1ST SCK EDGE
SDO
Z
Z
Z
Z
231116 F19
Figure 19. CMOS Mode SLEEP and WAKE Using SCK
REFOUT
REFOUT
RECOVERY
4.096V
4.096V
tWAKE
CNV
1
2
3
4
NAP MODE
SCK
WAKE ON 5TH
CSB EDGE
5
SLEEP MODE
FULL POWER MODE
HOLD STATIC HIGH OR LOW
Z
SDO
Z
Z
Z
Z
231116 F20
Figure 20. LVDS and CMOS Mode SLEEP and WAKE Using CNV
tCNVH
tDSCKLCNVH
CNV
tDCNVSCKL
SCK
HI-Z
SDO
tACQ
1
2
tSCKL
3
4
5
6
tSCKH
7
8
tDCNVSDOZ
tSCK
9
10
11
12
13
14
15
16
tDCNVSDOV
B15
B14
B13
B12
B11
B10
B9
B8
B7
B6
tHSDO
B5
B4
B3
B2
B1
B0
HI-Z
tDSCKSDOV
tCONV
tCYC
SERIAL DATA BITS B[15:0] CORRESPOND TO PREVIOUS CONVERSION
231116 F21
Figure 21. LTC2311-16 Timing Diagram, CMOS, LVDS I/O Modes
22
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
DIGITAL INTERFACE
BOARD LAYOUT
The LTC2311-16 features a serial digital interface that
is simple and straightforward to use. The flexible OVDD
supply allows the LTC2311-16 to communicate with any
digital logic operating between 1.8V and 2.5V. A 105MHz
external clock must be applied at the SCK pin to achieve
5Msps throughput.
To obtain the best performance from the LTC2311-16, a
four layer printed circuit board is recommended. Layout
for the printed circuit board (PCB) should ensure the
digital and analog signal lines are separated as much as
possible. In particular, care should be taken not to run
any digital clocks or signals adjacent to analog signals or
underneath the ADC.
In addition to a standard CMOS SPI interface, the
LTC2311‑16 provides an optional LVDS SPI interface to
support low noise digital design. The CMOS/LVDS pin is
used to select the digital interface mode.
The falling edge of SCK outputs the conversion result MSB
first on the SDO pins. In CMOS mode, use the SDO+ pin
as the serial data output and the SCK+ pin as the serial
clock input. Do not connect the SDO– and SCK– pins as
they have internal pull-downs to GND.
In LVDS mode, use the SDO+/SDO– pins as a differential
output. These pins must be differentially terminated by an
external 100Ω resistor at the receiver (FPGA). The SCK+/
SCK– pins are a differential input and must be terminated
differentially by an external 100Ω resistor at the receiver
(ADC), see Figure 22.
LTC2311-16
A single solid ground plane is used. Bypass capacitors to
the supplies are placed as close as possible to the supply
pins. Low impedance common returns for these bypass
capacitors are essential to the low noise operation of the
ADC. The analog input traces are screened by ground.
Reference Design
For a detailed look at the reference design for this converter,
including schematics and PCB layout, please refer to the
DC2425, the evaluation kit for the LTC2311-16.
FPGA OR DSP
2.5V
OVDD
SDO+
SDO–
2.5V
100Ω
SCK+
CMOS/LVDS
100Ω
SCK–
+
–
+
–
CNV
231116 F22
Figure 22. LTC2311-16 Using the LVDS Interface
231116fa
For more information www.linear.com/LTC2311-16
23
LTC2311-16
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/product/LTC2311-16#packaging for the most recent package drawings.
MSE Package
16-Lead Plastic MSOP, Exposed Die Pad
(Reference LTC DWG # 05-08-1667 Rev F)
BOTTOM VIEW OF
EXPOSED PAD OPTION
2.845 ±0.102
(.112 ±.004)
5.10
(.201)
MIN
2.845 ±0.102
(.112 ±.004)
0.889 ±0.127
(.035 ±.005)
8
1
1.651 ±0.102
(.065 ±.004)
1.651 ±0.102 3.20 – 3.45
(.065 ±.004) (.126 – .136)
0.305 ±0.038
(.0120 ±.0015)
TYP
16
0.50
(.0197)
BSC
4.039 ±0.102
(.159 ±.004)
(NOTE 3)
RECOMMENDED SOLDER PAD LAYOUT
0.254
(.010)
0.35
REF
0.12 REF
DETAIL “B”
CORNER TAIL IS PART OF
DETAIL “B” THE LEADFRAME FEATURE.
FOR REFERENCE ONLY
9
NO MEASUREMENT PURPOSE
0.280 ±0.076
(.011 ±.003)
REF
16151413121110 9
DETAIL “A”
0° – 6° TYP
3.00 ±0.102
(.118 ±.004)
(NOTE 4)
4.90 ±0.152
(.193 ±.006)
GAUGE PLANE
0.53 ±0.152
(.021 ±.006)
DETAIL “A”
1.10
(.043)
MAX
0.18
(.007)
SEATING
PLANE
0.17 – 0.27
(.007 – .011)
TYP
1234567 8
0.50
(.0197)
BSC
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
6. EXPOSED PAD DIMENSION DOES INCLUDE MOLD FLASH. MOLD FLASH ON E-PAD SHALL
NOT EXCEED 0.254mm (.010") PER SIDE.
24
0.86
(.034)
REF
0.1016 ±0.0508
(.004 ±.002)
MSOP (MSE16) 0213 REV F
231116fa
For more information www.linear.com/LTC2311-16
LTC2311-16
REVISION HISTORY
REV
DATE
DESCRIPTION
A
07/16
Updated the max value for REFOUT Short-Circuit Current
Removed power consumption max values
Changed the note for tDSCKSDOV
PAGE NUMBER
4
6
7
231116fa
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection
of itsinformation
circuits as described
herein will not infringe on existing patent rights.
For more
www.linear.com/LTC2311-16
25
LTC2311-16
TYPICAL APPLICATION
Low Jitter Clock Timing with RF Sine Generator Using Clock Squaring/Level-Shifting Circuit and Retiming Flip-Flop
VCC
0.1µF
50Ω
1k
NC7SVUO4P5X
MASTER_CLOCK
VCC
1k
D
PRE
NC7SV74KBX Q
CLR
CONV
CONV ENABLE
CONTROL
LOGIC
(FPGA, CPLD,
DSP, ETC.)
CNV
SCK
LTC2311-16
GND
CMOS/LVDS
SDO
NC7SVUO4P5X
10Ω
231116 TA02
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
ADCs
LTC2323-16/LTC2323-14/ 16-/14-/12-Bit, 5Msps, Simultaneous Sampling
LTC2323-12
Dual ADCs
3.3V/5V Supply, 40mW/Ch, 20ppm/°C Max Internal Reference, Flexible
Inputs, 4mm × 5mm QFN-28 Package
LTC1407/LTC1407-1
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Unipolar/Bipolar Inputs, 14mW, MSOP Package
LTC2314-14
14-Bit, 4.5Msps Serial ADC
3V/5V Supply, 18mW/31mW, 20ppm/°C Max Internal Reference,
Unipolar Inputs, 8-Lead TSOT-23 Package
LTC2321-16/LTC2321-14/ 16-/14-/12-Bit, 2Msps, Simultaneous Sampling
LTC2321-12
Dual ADCs
3.3V/5V Supply, 33mW/Ch, 10ppm°C Max Internal Reference,
Flexible Inputs, 4mm × 5mm QFN-28 Package
LTC2370-16/LTC2368-16/ 16-Bit, 2Msps/1Msps/500ksps/250ksps Serial,
LTC2367-16/LTC2364-16 Low Power ADC
2.5V Supply, Pseudo-Differential Unipolar Input, 94dB SNR, 5V Input Range,
DGC, Pin-Compatible Family in MSOP-16 and 4mm × 3mm DFN-16 Packages
LTC2380-16/LTC2378-16/ 16-Bit, 2Msps/1Msps/500ksps/250ksps Serial,
LTC2377-16/LTC2376-16 Low Power ADC
2.5V Supply, Differential Input, 96.2dB SNR, ±5V Input Range, DGC,
Pin-Compatible Family in MSOP-16 and 4mm × 3mm DFN-16 Packages
DACs
LTC2632
Dual 12-/10-/8-Bit, SPI VOUT DACs with Internal
Reference
2.7V to 5.5V Supply Range, 10ppm/°C Reference, External REF Mode,
Rail-to-Rail Output, 8-Pin ThinSOT™ Package
LTC2602/LTC2612/
LTC2622
Dual 16-/14-/12-Bit SPI VOUT DACs with External
Reference
300μA per DAC, 2.5V to 5.5V Supply Range, Rail-to-Rail Output, 8-Lead
MSOP Package
LTC6655
Precision Low Drift, Low Noise Buffered Reference
5V/4.096V/3.3V/3V/2.5V/2.048V/1.25V, 2ppm/°C, 0.25ppm
Peak-to-Peak Noise, MSOP-8 Package
LTC6652
Precision Low Drift, Low Power Buffered Reference 5V/4.096V/3.3V/3V/2.5V/2.048V/1.25V, 5ppm/°C, 2.1ppm
Peak-to-Peak Noise, MSOP-8 Package
References
Amplifiers
LT1818/LT1819
400MHz, 2500V/µs, 9mA Single/Dual Operational
Amplifiers
LT1806
325MHz, Single, Rail-to-Rail Input and Output, Low –80dBc Distortion at 5MHz, 3.5nV/√Hz Input Noise Voltage,
Distortion, Low Noise Precision Op Amps
9mA Supply Current, Unity-Gain Stable
LT6200
165MHz, Rail-to-Rail Input and Output, 0.95nV/√Hz Low Noise, Low Distortion, Unity-Gain Stable
Low Noise, Op Amp Family
26 Linear Technology Corporation
–85dBc Distortion at 5MHz, 6nV/√Hz Input Noise Voltage, 9mA Supply
Current, Unity-Gain Stable
1630 McCarthy Blvd., Milpitas, CA 95035-7417
For more information www.linear.com/LTC2311-16
(408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com/LTC2311-16
231116fa
LT 0716 REV A • PRINTED IN USA
 LINEAR TECHNOLOGY CORPORATION 2016